JPH0341007B2 - - Google Patents
Info
- Publication number
- JPH0341007B2 JPH0341007B2 JP57094488A JP9448882A JPH0341007B2 JP H0341007 B2 JPH0341007 B2 JP H0341007B2 JP 57094488 A JP57094488 A JP 57094488A JP 9448882 A JP9448882 A JP 9448882A JP H0341007 B2 JPH0341007 B2 JP H0341007B2
- Authority
- JP
- Japan
- Prior art keywords
- filter
- harmonic
- reactor
- load
- intermediate tap
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired - Lifetime
Links
Classifications
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02E—REDUCTION OF GREENHOUSE GAS [GHG] EMISSIONS, RELATED TO ENERGY GENERATION, TRANSMISSION OR DISTRIBUTION
- Y02E40/00—Technologies for an efficient electrical power generation, transmission or distribution
- Y02E40/40—Arrangements for reducing harmonics
Landscapes
- Supply And Distribution Of Alternating Current (AREA)
- Filters And Equalizers (AREA)
Description
〔産業上の利用分野〕
本発明は需要家側に設置される高調波フイルタ
に係わる。
〔従来の技術〕
需要家において、電力変換設備のように高調波
の発生負荷を有するときは、これより発生する高
調波除去のため、高調波フイルタを設備する。
第１図に需要家側に設けられる通常の高調波フ
イルタの概略を示す。図において、１は、例えば
需要家に設置される６相変換器であり、２はフイ
ルタであり、３は交流電源である。フイルタ２は
高調波を発生する変換器１と並列に接続される。
電源側インピーダンスをZ〓S、フイルタインピーダ
ンスをZ〓F、変換器１よりの高調波電流をI〓oとすれ
ば、変換器運転時における需要家側より配電系統
へ流出する高調波電流I〓SはI〓S＝ZF／ZF＋ZSI〓oで表
わさ
れる。
この式で示すように、高調波フイルタ効果は、
フイルタインピーダンスZ〓Fと高調波に対する電源
側インピーダンスZ〓Sの相対関係で決定される。と
ころが、同一系統内に例えば抑制対象とする６相
ブリツジ変換器１以外の高調波発生源があると、
これらの高調波がフイルタに入力するため、フイ
ルタの設計には、対象物以外の高調波源の調査が
必要であり、フイルタ容量も過大なものとなる。
このようなフイルタ容量の過大化防止対策とし
て、第２図に示すように、電源側に直列にバツフ
ア用リアクトル（BR）４を設置し、高調波フイ
ルタに流入する高調波電流分をブロツクする方式
が試みられている。
この方式において、高調波フイルタ効果を大き
くするためには、BRの値を大きくしたいが、基
本波の電圧降下のため上限がある。
〔発明が解決しようとする課題〕
前記のようにBRを電源側に直列に設置したと
き、フイルタ効果を大きくしたいが、基本波の電
圧降下のため上限があるので、フイルタ効果を増
すため、回路は２分路以上の構成とすることが必
要である。本発明は前記BRをフイルタの交流リ
アクトルと兼用させることで、リアクトルを１台
節約できる構成となすものである。
〔発明の構成〕
以下図面により本発明を説明する。
第３図は本発明の実施例を示す。同一鉄心に巻
かれた中間タツプ付BR５の一端に電源側のＰ端
子を設けて交流電源３と接続し、前記BR５の巻
線の中間タツプにＴ端子を設け、負荷であり、高
調波を発生する６相ブリツジ変換器１と接続し、
巻線他端に端子Ｓを設け、これを高調波交流フイ
ルタを形成するコンデンサ６に接続する。
Ｐ−Ｔ端子の巻線間リアクタンスをXTP、Ｐ−
Ｓ端子の巻線間リアクタンスをXPS、Ｓ−Ｔ端子
の巻線間リアクタンスをXSTとし、Ｐ−Ｔ端子間
の巻線数とＳ−Ｔ端子間の巻線数の巻線比１：α
とし、リアクタンスXTPを負荷容量ベース（この
場合は変換器）でｌ（％）とし、第４図に示す回
路で各巻線の等価リアクタンスがXP，XS，XTと
なる第３図中間タツプ付BRの等価回路を設定
し、XP，XS，XTを算出する。この場合、リアク
トルにおけるリアクタンスは巻線数の２乗に比例
するから、
XTP＝(1)2.l，XPS＝（１＋α）2.l XST＝a2.l
第３図と第４図より、
XTP＝XT＋XP＝ｌ (1)
XPS＝XP＋XS＝（１＋α）2.l (2)
XST＝XS＋XT＝a2.l (3)
となり、｛(1)＋(2)＋(3)｝÷２より
XP＋XS＋XT＝（１＋α＋d2）．ｌ (4)
(1)、(2)、(3)、(4)式より
XP＝（１＋α）．ｌ (5)
XS＝（α＋d2）．ｌ (6)
XT＝−α.l (7)
となる。
従つてXSを交流フイルタ用リアクトルとして
兼用すれば、リアクトル１台節約することができ
る。すなわち、第７図イ，ロは従来の交流フイル
タと本発明フイルタの吸収効果を比較したもので
ある。負荷から発生する高調波電流Ioは、０点で
交流フイルタ側と電源側に分流する。ｎ次調波に
おける交流フイルタの残留抵抗をRoとすると電
源側へ流出する高調波電流は、従来のBRを直列
接続したものの電流をI〓′Sとし、本発明の中間タツ
プ付BRによるものの電流をI〓Sとすると、それぞ
れ
I〓′S＝Rn／jnl＋Rn・I〓n (8)
I〓S＝Rn／ｊ（１＋α）．nl＋Rn・I〓n(9
)
となるので、｜nl｜≫Rnと考えると、
｜I〓′S｜：｜I〓S｜≒（１＋α）：１となる。
すなわち、第７図ロに示す回路では、電源とフ
イルタとの間にイ図に示す従来例の（１＋α）倍
のBRがあるのと等価であるので、交流フイルタ
の吸収効果および電源側の既存高調波をブロツク
する効果は従来例の（１＋α）倍となる。このこ
とは、従来例と同一のフイルタ効果を得るための
フイルタ容量が従来の１／（１＋α）ですむこと
を示している。ただし、基本波における電圧降下
を少なくするため、電源−負荷間のリアクタンス
（XTP）は負荷容量ベースで数％ないし10数％程
度としなければならない。
負荷と並列に接続されるコンデンサは、負荷の
力率改善も兼用するが、進相になるのを防ぐた
め、上限があり、負荷容量ベースで６相ダイオー
ドブリツジで40％、６相サイリスタブリツジ60％
程度の進相容量であり、基本波リアクタンスで示
せは250％と167％になる。
以上のような条件を考慮して、中間タツプ付
BRの基本波リアクタンスを負荷容量ベースで、
６％、10％として、６相ダイオードブリツジ負荷
Ｄ、および６相サイリスタブリツジ負荷SCRに
ついて、最適な中間タツプ付BRの巻数比より
(5)、(6)、(7)式によりXP，XT，XSを求め、本発明
における高調波吸収効果を求め、第２図の従来構
成で、HP分路を使用しない、第５分路だけの構
成のものと対比した。第２図の第５高調波フイル
タの例は、BRに中間タツプがないBRで巻数比
αは零であつて、高調波吸収効果を１とし、表１
には本発明の実施によるもののみが示される。な
お、第２図の従来例で、BRの基本波リアクタン
スは本発明の実施例と等しく、第５高調波フイル
タにおけるコンデンサの進相容量もそれぞれ前記
６相ダイオードブリツジ負荷Ｄおよび６相サイリ
スタブリツジ負荷SCRにおいてそれぞれ等しく
している。
高調波吸収効果は、BRの交流電源側等価リア
クタンスXPがBRの基本波リアクタンスよりも大
きくなる分だけ吸収効果が大きくなり、(9)式でみ
られるように外部に流出する高調波電流は抑制さ
れる。
[Industrial Application Field] The present invention relates to a harmonic filter installed on the consumer side. [Prior Art] When a consumer has a load that generates harmonics, such as a power conversion facility, a harmonic filter is installed to remove the harmonics generated by the load. FIG. 1 shows an outline of a normal harmonic filter installed on the consumer side. In the figure, 1 is a six-phase converter installed, for example, in a consumer, 2 is a filter, and 3 is an AC power source. Filter 2 is connected in parallel with converter 1 which generates harmonics.
If the power supply side impedance is Z〓 S , the filter impedance is Z〓 F , and the harmonic current from converter 1 is I〓 o , then the harmonic current flowing from the consumer side to the distribution system when the converter is operating is I〓 S is expressed as I〓 S = Z F /Z F + Z S I〓 o . As shown in this equation, the harmonic filter effect is
It is determined by the relative relationship between the filter impedance Z〓 F and the power supply side impedance Z〓 S for harmonics. However, if there is a harmonic generation source other than the six-phase bridge converter 1 to be suppressed in the same system, for example,
Since these harmonics are input to the filter, it is necessary to investigate harmonic sources other than the object when designing the filter, and the filter capacity becomes excessive. As a measure to prevent the filter capacity from becoming too large, as shown in Figure 2, a buffer reactor (BR) 4 is installed in series on the power supply side to block the harmonic current flowing into the harmonic filter. is being attempted. In this method, in order to increase the harmonic filter effect, it is desirable to increase the value of BR, but there is an upper limit due to the voltage drop of the fundamental wave. [Problem to be solved by the invention] When the BR is installed in series on the power supply side as described above, it is desired to increase the filter effect, but there is an upper limit due to the voltage drop of the fundamental wave, so in order to increase the filter effect, it is necessary to increase the filter effect. It is necessary to have a configuration of two or more branch paths. The present invention has a configuration in which one reactor can be saved by using the BR as the AC reactor of the filter. [Structure of the Invention] The present invention will be explained below with reference to the drawings. FIG. 3 shows an embodiment of the invention. A P terminal on the power supply side is provided at one end of the BR5 with an intermediate tap wound on the same core, and connected to the AC power source 3, and a T terminal is provided at the intermediate tap of the winding of the BR5, which is a load and generates harmonics. Connect to the 6-phase bridge converter 1,
A terminal S is provided at the other end of the winding, and this is connected to a capacitor 6 forming a harmonic AC filter. The reactance between the windings of the P-T terminal is X TP , P-
Let the reactance between windings of the S terminal be X PS and the reactance between windings of the S-T terminal be X ST , and the turns ratio of the number of windings between the P-T terminal and the number of windings between the S-T terminal is 1: α
The reactance X TP is expressed as l (%) based on the load capacity (in this case, the converter), and in the circuit shown in Figure 4, the equivalent reactance of each winding is X P , X S , and X T in the middle of Figure 3. Set up the equivalent circuit of the BR with taps and calculate X P , X S , and X T . In this case, the reactance in the reactor is proportional to the square of the number of windings, so X TP = (1) 2 .l, X PS = (1 + α) 2 .l X ST = a 2 .l From the figure, X TP = X T + X P =l (1) X PS =X P +X S = (1+α ) 2 .l (2) (1)+(2)+(3)}÷2, X P +X S +X T = (1+α+d 2 ). l (4) From equations (1), (2), (3), and (4), X P = (1+α). l (5) X S = (α+d 2 ). l (6) X T =-α.l (7). Therefore, if the X S is also used as a reactor for the AC filter, one reactor can be saved. That is, FIGS. 7A and 7B compare the absorption effects of the conventional AC filter and the filter of the present invention. The harmonic current I o generated from the load is divided into the AC filter side and the power supply side at the zero point. If the residual resistance of the AC filter at the n-th harmonic is R o , the harmonic current flowing to the power supply side is the current of the conventional BR connected in series, I〓′ S , and the current of the BR with intermediate tap of the present invention. If the current is I〓 S , then I〓' S = Rn/jnl + Rn・I〓n (8) I〓 S = Rn/j (1 + α). nl＋Rn・I〓n(9
), so considering |nl|≫Rn, |I〓′ S |: |I〓 S |≒(1+α):1. In other words, the circuit shown in Figure 7B is equivalent to having (1+α) times as much BR between the power supply and the filter as in the conventional example shown in Figure A, so the absorption effect of the AC filter and the existing The effect of blocking harmonics is (1+α) times that of the conventional example. This indicates that the filter capacity required to obtain the same filter effect as the conventional example is 1/(1+α) of the conventional example. However, in order to reduce the voltage drop in the fundamental wave, the reactance (X TP ) between the power supply and the load must be set to about several to ten-odd percent based on the load capacity. The capacitor connected in parallel with the load also serves to improve the power factor of the load, but in order to prevent the phase from advancing, there is an upper limit: 40% for a 6-phase diode bridge and 40% for a 6-phase thyristorib based on the load capacitance. Azalea 60%
The phase advance capacity is approximately 250% and 167% in terms of fundamental wave reactance. Taking into account the above conditions, we have developed an intermediate tap
The fundamental wave reactance of BR is based on the load capacity,
Assuming 6% and 10%, for the 6-phase diode bridge load D and the 6-phase thyristor bridge load SCR, from the turns ratio of the optimal BR with intermediate tap.
(5), (6), and (7) to determine X P , X T , and X S to determine the harmonic absorption effect of the present invention. This was compared with a configuration with only five branches. The example of the fifth harmonic filter in Fig. 2 is a BR without an intermediate tap, the turns ratio α is zero, the harmonic absorption effect is 1, and Table 1
Only those according to the implementation of the present invention are shown. In the conventional example shown in FIG. 2, the fundamental wave reactance of the BR is the same as that of the embodiment of the present invention, and the phase advance capacitance of the capacitor in the fifth harmonic filter is also the same as that of the six-phase diode bridge load D and the six-phase thyristor stabilizer, respectively. The load SCR is made equal to each other. The harmonic absorption effect increases as the equivalent reactance X P on the AC power side of the BR becomes larger than the fundamental reactance of the BR, and as seen in equation (9), the harmonic current flowing to the outside is suppressed.
以上説明したように、本発明によれば、サイリ
スタ、ダイオードのような高調波発生源をもつ回
路のみでなく、例えばテレビなどひろく高調波発
生源を含む回路に適用することができる。
更に、本発明によれば、中間タツプ付リアクト
ルを用いることにより、これを高調波フイルタ用
リアクトルとして兼用し、負荷により発生する高
調波の吸収効果をあげ、系統より流入する高調波
を抑制し、且つ、前記兼用によりリアクトルを１
台節約することができる。
As described above, the present invention can be applied not only to circuits having harmonic generation sources such as thyristors and diodes, but also to a wide range of circuits including harmonic generation sources, such as televisions. Furthermore, according to the present invention, by using a reactor with an intermediate tap, it can also be used as a reactor for a harmonic filter, increasing the effect of absorbing harmonics generated by the load, suppressing harmonics flowing in from the system, Moreover, due to the above-mentioned dual use, one reactor
You can save money.
第１図は需要家側に設けられる通常の高調波フ
イルタの一例である。第２図は高調波流入を抑制
する高調波フイルタの一例である。第３図は本発
明の一実施例を示す。第４図は第３図実施例の等
価回路を示す。第５図は本発明による高調波吸収
効果を示すグラフである。第６図は本発明の他の
実施例を示す。第７図イ，ロは従来例と本発明比
較のために示す等価回路図である。
１……６相ブリツジ変換器、２……高調波フイ
ルタ、３……交流電源、４……バツフア用リアク
トル（BR）、５……中間タツプ付バツフア用リ
アクトル、６……コンデンサ、７……制動抵抗。
FIG. 1 is an example of a normal harmonic filter provided on the consumer side. FIG. 2 is an example of a harmonic filter that suppresses the inflow of harmonics. FIG. 3 shows an embodiment of the invention. FIG. 4 shows an equivalent circuit of the embodiment shown in FIG. FIG. 5 is a graph showing the harmonic absorption effect according to the present invention. FIG. 6 shows another embodiment of the invention. FIGS. 7A and 7B are equivalent circuit diagrams shown for comparison of the conventional example and the present invention. 1... 6-phase bridge converter, 2... Harmonic filter, 3... AC power supply, 4... Buffer reactor (BR), 5... Buffer reactor with intermediate tap, 6... Capacitor, 7... braking resistance.
Claims (1)
電源に接続し、前記中間タツプを高調波発生負荷
に接続し、前記巻線の他端をコンデンサに接続し
て高調波フイルタを形成したことを特徴とする高
調波フイルタ。 ２ 中間タツプ付リアクトルの基本波リアクタン
スを負荷容量ベースで４〜15％、前記リアクトル
の巻数比を0.4〜1.0以内、コンデンサの基本波リ
アクタンスを負荷の容量ベース150〜300％に選定
したことを特徴とする特許請求の範囲第１項記載
の高調波フイルタ。 ３ 中間タツプ付リアクトルの中間タツプとコン
デンサの間に負荷容量ベースで100〜1000％の制
動抵抗を接続したことを特徴とする特許請求の範
囲第２項記載の高調波フイルタ。[Claims] 1 One end of the winding of a reactor with an intermediate tap is connected to an AC power source, the intermediate tap is connected to a harmonic generation load, and the other end of the winding is connected to a capacitor to form a harmonic filter. A harmonic filter characterized by forming. 2. The fundamental wave reactance of the reactor with intermediate tap is selected to be 4 to 15% based on the load capacity, the turns ratio of the reactor is selected to be within 0.4 to 1.0, and the fundamental wave reactance of the capacitor is selected to be 150 to 300% based on the load capacity. A harmonic filter according to claim 1. 3. The harmonic filter according to claim 2, characterized in that a braking resistance of 100 to 1000% based on load capacity is connected between the intermediate tap of the reactor with an intermediate tap and the capacitor.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP57094488A JPS58212326A (en) | 1982-06-01 | 1982-06-01 | Harmonic filter |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP57094488A JPS58212326A (en) | 1982-06-01 | 1982-06-01 | Harmonic filter |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPS58212326A JPS58212326A (en) | 1983-12-10 |
| JPH0341007B2 true JPH0341007B2 (en) | 1991-06-20 |
Family
ID=14111673
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP57094488A Granted JPS58212326A (en) | 1982-06-01 | 1982-06-01 | Harmonic filter |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JPS58212326A (en) |
Families Citing this family (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPH03143227A (en) * | 1989-10-25 | 1991-06-18 | Toyo Electric Mfg Co Ltd | Harmonic voltage suppressor |
| JPH03207222A (en) * | 1989-10-30 | 1991-09-10 | Fuji Electric Co Ltd | Higher harmonic suppressor |
| JPH04236129A (en) * | 1991-01-16 | 1992-08-25 | Fuji Electric Co Ltd | Higher harmonic preventing/suppressing device |
-
1982
- 1982-06-01 JP JP57094488A patent/JPS58212326A/en active Granted
Also Published As
| Publication number | Publication date |
|---|---|
| JPS58212326A (en) | 1983-12-10 |
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