JPH0238510Y2 - - Google Patents
Info
- Publication number
- JPH0238510Y2 JPH0238510Y2 JP17026584U JP17026584U JPH0238510Y2 JP H0238510 Y2 JPH0238510 Y2 JP H0238510Y2 JP 17026584 U JP17026584 U JP 17026584U JP 17026584 U JP17026584 U JP 17026584U JP H0238510 Y2 JPH0238510 Y2 JP H0238510Y2
- Authority
- JP
- Japan
- Prior art keywords
- coaxial line
- circuit
- bridging
- arm
- line
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired
Links
- 238000006243 chemical reaction Methods 0.000 claims description 5
- 239000004020 conductor Substances 0.000 description 8
- 238000010586 diagram Methods 0.000 description 5
- 230000005855 radiation Effects 0.000 description 5
- 230000000694 effects Effects 0.000 description 4
- 230000005540 biological transmission Effects 0.000 description 3
- PNEYBMLMFCGWSK-UHFFFAOYSA-N aluminium oxide Inorganic materials [O-2].[O-2].[O-2].[Al+3].[Al+3] PNEYBMLMFCGWSK-UHFFFAOYSA-N 0.000 description 1
- 230000003111 delayed effect Effects 0.000 description 1
- 230000004069 differentiation Effects 0.000 description 1
- 239000000758 substrate Substances 0.000 description 1
Description
【考案の詳細な説明】
〔産業上の利用分野〕
本考案は、非直線性タイミング信号の抽出に用
いられる微分操作が行われる波形変換回路に関す
る。この回路は高速デイジタル通信装置に利用す
るに適する。[Detailed Description of the Invention] [Industrial Application Field] The present invention relates to a waveform conversion circuit that performs a differential operation used to extract a nonlinear timing signal. This circuit is suitable for use in high speed digital communication equipment.
このような波形微分操作を行う従来例回路とし
て、第３図に示すような集中定数で構成された回
路と第４図に示すような分布定数で構成された回
路などが広く用いられている。前者の回路では、
受信等化波形がトランス１２で入力に対し同相お
よび逆相の二つの信号に分けられ、一方は遅延回
路１３により「１」ビツトシフトさせられトラン
ス３で合成されて微分波形が得られる。後者の回
路では、分布定数線路１７および１８の先端で生
ずる反射作用と遅延作用により微分操作が行われ
る。
As conventional circuits that perform such waveform differentiation operations, a circuit configured with lumped constants as shown in FIG. 3 and a circuit configured with distributed constants as shown in FIG. 4 are widely used. In the former circuit,
The received equalized waveform is divided by the transformer 12 into two signals of in-phase and anti-phase with respect to the input, one of which is shifted by "1" bit by the delay circuit 13 and combined by the transformer 3 to obtain a differential waveform. In the latter circuit, a differential operation is performed by reflection and delay effects occurring at the tips of distributed constant lines 17 and 18.
このような従来例回路には次の欠点がある。集
中定数で構成された回路では、伝送速度が数百
Mb／ｓ以上になると、トランスでの帯域制限作
用により良好な微分波形を得ることが困難にな
る。
Such a conventional circuit has the following drawbacks. In circuits composed of lumped constants, transmission speeds are in the hundreds.
If it exceeds Mb/s, it becomes difficult to obtain a good differential waveform due to the band-limiting effect of the transformer.
また、分布定数で構成された回路では、数百
Mb／ｓ以上の伝送速度でも微分操作を良好に行
うことができるが、分布定数線路にアルミナ基板
上のストリツプ線路を用いる場合などでは、この
ストリツプ線路の長さが実装上の問題になること
がある。例えば、伝送速度500Mb／ｓに対して
ストリツプ線路の長さは約12cmになり大形の基板
が必要になり実装上不利になると同時に、先端開
放側のストリツプ線路からの放射が問題になる。 In addition, in a circuit composed of distributed constants, hundreds of
Differential operation can be performed well even at transmission speeds of Mb/s or higher, but when using a strip line on an alumina substrate as a distributed constant line, the length of this strip line can become a problem in implementation. be. For example, for a transmission speed of 500 Mb/s, the length of the strip line is about 12 cm, which requires a large board, which is disadvantageous in terms of mounting, and at the same time, radiation from the strip line on the open end side becomes a problem.
また、分布定数線路として同軸線路を用いた場
合でも、先端開放側の同軸線路と接地面との間に
存在する浮遊容量の影響が及んで安定かつ良好な
微分波形を得ることができない欠点がある。 Furthermore, even when a coaxial line is used as a distributed constant line, there is a drawback that a stable and good differential waveform cannot be obtained due to the influence of stray capacitance that exists between the coaxial line on the open end side and the ground plane. .
本考案は、上記の分布定数線路を用いた回路の
欠点を除去するもので、実装面積が狭く、放射現
象が抑制され、浮遊容量の影響が除去された波形
変換回路を提供することを目的とする。 The present invention eliminates the drawbacks of the circuit using the distributed constant line described above, and aims to provide a waveform conversion circuit that has a small mounting area, suppresses radiation phenomena, and eliminates the influence of stray capacitance. do.
本考案は、橋絡腕および並列腕が同軸線路を用
いた分布定数回路により構成された橋絡Ｔ形回路
を含み、上記橋絡腕および並列腕はそれぞれ所望
波長の二分の一の電気長に設定され、その橋絡腕
および並列腕の一方が先端開放であり、他方が先
端短絡である波形変換回路で前述の問題点を解決
するための手段として、上記先端開放の同軸線路
はコイル状に形成され、上記先端開放の同軸線路
の先端にこの同軸線路の特性インピーダンスに比
べて大きい値の抵抗器が接続されたことを特徴と
する。
The present invention includes a bridging T-shaped circuit in which the bridging arm and the parallel arm are configured by a distributed constant circuit using a coaxial line, and the bridging arm and the parallel arm each have an electrical length of one half of the desired wavelength. As a means to solve the above-mentioned problem in a waveform conversion circuit in which one of the bridging arm and parallel arm has an open end and the other has a short-circuited end, the coaxial line with an open end is coiled. A resistor having a value larger than the characteristic impedance of the coaxial line is connected to the tip of the open-ended coaxial line.
本考案は分布定数線路を使用した橋絡Ｔ形回路
を基本構成とし、この分布定数線路として同軸線
路を使用し先端開放側の同軸線路をコイル状に形
成して実装面積を少なくするとともに、同軸線路
からの信号の放射を軽減させ、また同軸線路の先
端を抵抗で接地することにより、外部導体と接地
面との間に存在する浮遊容量の影響を軽減させ
る。
The basic structure of this invention is a bridging T-type circuit using a distributed constant line. A coaxial line is used as the distributed constant line, and the coaxial line on the open end side is formed into a coil shape to reduce the mounting area and to reduce the mounting area. By reducing signal radiation from the line and by grounding the tip of the coaxial line with a resistor, the influence of stray capacitance that exists between the external conductor and the ground plane is reduced.
以下、本考案実施例回路を図面に基づいて説明
する。
Hereinafter, a circuit according to an embodiment of the present invention will be explained based on the drawings.
第１図は本考案実施例回路の回路接続図であ
る。 FIG. 1 is a circuit connection diagram of an embodiment of the present invention.
まず、この実施例回路の構成を第１図に基づい
て説明する。抵抗値R0なる直列に接続された二
つの抵抗３，４の両端に、λ／２（ただし、λは
タイミングパルスの波長とする。）の長さを有し、
その先端が開放された入力インピーダンスZ2の同
軸線路５の他端の中心導体および外部導体が接続
される。また、同軸線路５と同じ長さを有し、外
部導体が基準電位に接地され、かつ一端の中心導
体が基準電位に接地された入力インピーダンスZ1
の同軸線路６の他端の中心導体が、抵抗３と抵抗
４との接続点に接続される。ここで、Z1，Z2およ
びR0の間にはZ1・Z2＝R0 2の条件が満足されてい
る。 First, the configuration of this embodiment circuit will be explained based on FIG. Two resistors 3 and 4 connected in series with a resistance value R 0 have a length of λ/2 (where λ is the wavelength of the timing pulse) at both ends,
The center conductor and the outer conductor at the other end of the coaxial line 5 having an input impedance Z 2 whose tip is open are connected. In addition, an input impedance Z 1 has the same length as the coaxial line 5, has an outer conductor grounded to a reference potential, and has a center conductor at one end grounded to a reference potential.
The center conductor at the other end of the coaxial line 6 is connected to the connection point between the resistors 3 and 4. Here, the condition Z 1 ·Z 2 =R 0 2 is satisfied between Z 1 , Z 2 and R 0 .
次に、この実施例回路の動作を第１図および第
２図に基づいて説明する。 Next, the operation of this embodiment circuit will be explained based on FIGS. 1 and 2.
このような橋絡Ｔ形回路に抵抗値R0の信号源
抵抗２を介して電圧源１から振幅Ｅの信号が入力
されると、抵抗値R0の負荷抵抗７に振幅Ｅ／４
の同相信号と同軸線路５および６の先端で反射さ
れ、かつ１ビツト遅延された振幅Ｅ／４の逆相信
号とが得られて微分波形が生成される。 When a signal with an amplitude E is input from the voltage source 1 to such a bridge T-shaped circuit via the signal source resistor 2 with a resistance value R 0 , the signal with an amplitude E/4 is input to the load resistor 7 with a resistance value R 0 .
A differential waveform is generated by obtaining an in-phase signal and an anti-phase signal of amplitude E/4 which is reflected at the tips of coaxial lines 5 and 6 and delayed by 1 bit.
ここで、同軸線路５と接地面との間の浮遊容量
の影響が軽減されていない状態では第２図の符号
１０に示すように、その周波数特性の一部に共振
が生ずる。同軸線路５の外部導体が適切な抵抗値
の抵抗９を介して接地されると、この浮遊容量の
影響が軽減され、第２図の符号１１に示す特性に
なり、安定でかつ良好な微分波形が得られる。ま
た、同軸線路５がコイル状に成形され、同軸線路
からの信号の放射による他回路への影響が軽減さ
れる。 Here, if the influence of stray capacitance between the coaxial line 5 and the ground plane is not reduced, resonance will occur in a part of the frequency characteristic, as shown by reference numeral 10 in FIG. 2. When the outer conductor of the coaxial line 5 is grounded via a resistor 9 with an appropriate resistance value, the influence of this stray capacitance is reduced, resulting in the characteristics shown by reference numeral 11 in Fig. 2, resulting in a stable and good differential waveform. is obtained. Further, the coaxial line 5 is formed into a coil shape, and the influence of signal radiation from the coaxial line on other circuits is reduced.
本考案は、以上説明したように、分布定数線路
として同軸線路を使用し反射を利用した橋絡Ｔ形
微分回路を基本構成として、先端開放側の同軸線
路がコイル状に形成され、同軸線路の外部導体が
適切な値の抵抗で接地されているので、同軸線路
からの信号の放射による他回路への影響が軽減さ
れ、また実装面積が縮小され、かつ先端開放側の
同軸線路と接地面との間に存在する浮遊容量の影
響が軽減されるので安定でかつ良好な微分波形を
生成することができる効果がある。
As explained above, the present invention has a basic configuration of a bridged T-type differential circuit that uses a coaxial line as a distributed constant line and utilizes reflection, and the coaxial line on the open end side is formed in a coil shape. Since the external conductor is grounded with a resistor of an appropriate value, the influence of signal radiation from the coaxial line on other circuits is reduced, the mounting area is reduced, and the connection between the coaxial line on the open end side and the ground plane is reduced. Since the influence of stray capacitance existing between the two is reduced, a stable and good differential waveform can be generated.
第１図は本考案実施例回路の回路接続図。第２
図は本考案実施例回路および従来例回路のそれぞ
れの周波数−損失を示す特性図。第３図は集中定
数で構成された従来例回路の構成を示す回路接続
図。第４図は分布定数で構成された従来例回路の
回路の構成を示す回路接続図。
１……電圧源、２……信号源抵抗、３，４，
９，１５，１６……抵抗、５，６……同軸線路、
７……負荷抵抗、８……浮遊容量、１０……従来
の特性例、１１……本考案実施後の特性例、１
２，１４……トランス、１３……遅延回路、１
７，１８……分布定数線路。
FIG. 1 is a circuit connection diagram of an embodiment of the present invention. Second
The figure is a characteristic diagram showing the frequency-loss of the circuit according to the present invention and the conventional circuit. FIG. 3 is a circuit connection diagram showing the configuration of a conventional circuit configured with lumped constants. FIG. 4 is a circuit connection diagram showing the configuration of a conventional circuit configured with distributed constants. 1... Voltage source, 2... Signal source resistance, 3, 4,
9, 15, 16...Resistance, 5, 6...Coaxial line,
7... Load resistance, 8... Stray capacitance, 10... Conventional characteristic example, 11... Characteristic example after implementation of the present invention, 1
2, 14...Transformer, 13...Delay circuit, 1
7, 18...distributed constant line.
Claims (1)
数回路により構成された橋絡Ｔ形回路を含み、 上記橋絡腕および並列腕はそれぞれ所望波長の
二分の一の電気長に設定され、その橋絡腕および
並列腕の一方が先端開放であり、他方が先端短絡
である 波形変換回路において、 上記先端開放の同軸線路はコイル状に形成さ
れ、上記先端開放の同軸線路の先端にこの同軸線
路の特性インピーダンスに比べて大きい値の抵抗
器が接続された ことを特徴とする波形変換回路。[Claims for Utility Model Registration] The bridging arm and the parallel arm include a bridging T-shaped circuit constituted by a distributed constant circuit using a coaxial line, and the bridging arm and the parallel arm each have a wavelength of one-half of the desired wavelength. One of the bridging arm and parallel arm has an open end, and the other has a short-circuited end.In the waveform conversion circuit, the open-ended coaxial line is formed into a coil shape, and A waveform conversion circuit characterized in that a resistor having a value larger than the characteristic impedance of the coaxial line is connected to the tip of the coaxial line.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP17026584U JPH0238510Y2 (en) | 1984-11-09 | 1984-11-09 |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP17026584U JPH0238510Y2 (en) | 1984-11-09 | 1984-11-09 |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPS6185931U JPS6185931U (en) | 1986-06-05 |
| JPH0238510Y2 true JPH0238510Y2 (en) | 1990-10-17 |
Family
ID=30727973
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP17026584U Expired JPH0238510Y2 (en) | 1984-11-09 | 1984-11-09 |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JPH0238510Y2 (en) |
-
1984
- 1984-11-09 JP JP17026584U patent/JPH0238510Y2/ja not_active Expired
Also Published As
| Publication number | Publication date |
|---|---|
| JPS6185931U (en) | 1986-06-05 |
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