JPH0193203A - Phase controlled microstrip line antenna - Google Patents

Abstract

PURPOSE:To prevent the direction of a beam to be generated from being changed even when an exciting frequency changes by arranging a single or plural resonant devices at every cycle of a strip conductor. CONSTITUTION:The strip conductor 12 of cyclically curved shape is formed on the surface on one side of a substrate 11 made of a flat dielectric material, and a ground conductor 13 is adhered on the surface on the opposite side. Also, rectangular first resonant device 14 and second resonant device 15 are arranged at every cycle of the curved shape of the strip conductor 12. An antenna 10 having such structure radiates a beam of circularly polarized wave by the strip conductor 12, and also, changes the beam generated from the resonant devices 14 and 15 to the circularly polarized waves, and synthesizes them. In such a way, it is possible to improve the radiation efficiency of the beam radiated from the antenna 10, and to prevent the direction of the beam to be generated from being easily changed even when the exciting frequency changes.

Description

DETAILED DESCRIPTION OF THE INVENTION Field of Industrial Application The present invention is directed to a microstrip line antenna known as a so-called planar antenna, by controlling the phase of the generated beam, even when the excitation frequency changes. This article relates to a phase system (wholesale microstrip line antenna) that suppresses changes in beam directionality.

BACKGROUND OF THE INVENTION Conventionally, a beam antenna with a circular flattened wave and high gain has been required in, for example, satellite communications, microwave communications, or radar. In addition to such beam antennas, microstrip line antennas are often used as planar antennas.

Such a microstrip line antenna has a problem in that when the excitation frequency is changed, the direction of beam generation changes as will be described later.

FIG. 30 is a diagram illustrating the strip conductor 1 of a typical microstrip line antenna of the prior art. In FIG. 30, the dielectric substrate, ground conductor, etc. are omitted. Here, a case where a beam is generated in a direction displaced by an angle θ (indicated by arrow A1 in FIG. 30) with respect to the normal 2 of the dielectric substrate on which the strip conductor 1 is arranged will be described. When the strip conductors 1 are arranged at an arrangement pitch (arrangement period), the portion of the strip conductor 1 for each repetition period (
The explanation will be made assuming the above-mentioned arrow A1 in units of 3 (hereinafter referred to as anti-8 units).

At the adjacent arrow A1, when the foot 4 of the perpendicular line is lowered from the left side to the starting end of the arrow on the right side in FIG. 30, the intersection of the foot 4 of the perpendicular line with the left arrow mark The distance d from the starting point of is expressed as d=Lsinθ·(1). Here, with respect to the wave number k of the excitation frequency of the strip conductor 1, if a beam is generated from the strip conductor 1 in the direction of the arrow A1, then the spatial phase difference between the start and end of the period is kLsinθ
・(2), and for the wave number k in the above equation, ゛=2π/λ (λ: free space wavelength)...(2a)
It is expressed as

On the other hand, a current ■ is flowing through the strip conductor 1, and it is assumed that the strength of this current I is I=I@s'β' - (3). Here Io is the maximum amplitude and symbol 8 is the quantity measured along the length of the strip conductor 1. Regarding the variable β, β-2π/λ (λg: current wavelength). Regarding β in the fourth equation, β=δk...(4a) δ=
β/=λ/λg (4b) holds true.

Between the starting point 3a and the ending point 3b of the antenna unit 3 of the strip conductor 1, the phase of the current I is βL2(L2
is the total length measured along the strip conductor 1 of the antenna unit 3 of the strip conductor 1).Therefore, in conjunction with the second equation above, for the spatial wave generated from the strip conductor 1, βL2−kLsinθ
・There will be a phase difference of (5). Also, βL
2−kLsinθ= 2 nπ(n; integer T&) − <
This means that the beam is generated in the direction of the angle θ where 6 > holds.

Substituting the above equations 4a and 4b into equation 6, k(δL.−Lsinθ)=2 nyr −
(6a) is obtained.

Problems to be Solved by the Invention In the above equation 6, the wave number has a value that varies depending on the excitation frequency as shown in equation 4. Therefore, the strip conductor 1 shown in FIG. 30 of the prior art is used. The conventional microstrip line antenna had a problem in that the beam generation direction changed undesirably when the excitation frequency changed.

SUMMARY OF THE INVENTION An object of the present invention is to provide an improved phase-controlled microstrip line antenna that solves the above-mentioned problems and suppresses undesired deviation of the generated beam direction even when the excitation frequency is changed. The goal is to provide the following.

Means for Solving the Problems The present invention provides a strip line antenna in which a periodically curved strip conductor is arranged on one surface of a dielectric substrate, and a ground conductor is provided on the entire surface of the other surface of the dielectric substrate. The phase control microstrip line antenna according to the present invention is characterized in that at least one of a single resonant element or a plurality of resonant elements is arranged for each period of the strip/tube conductor to perform phase control.

The present invention also provides a microstrip line antenna that includes a dielectric substrate, one or more periodically curved strip conductors, and a ground conductor, in which each period of the strip conductor is curved. A phase control microstrip line antenna characterized in that either a single or a plurality of resonant elements electrically coupled through a strip conductor and a dielectric are arranged to perform phase control. be.

According to the present invention, in a microstrip line antenna in which a periodically curved strip conductor is arranged on one side surface of a dielectric substrate, and a ground conductor is provided on the entire back surface, One or more resonant elements are provided which are supplied with power from a predetermined position of a single or plural strip conductors for each cycle. This makes it possible to control the configuration of each period of the strip conductor and the phase of the excitation S current flowing through the resonant element, thereby preventing the beam direction from changing even if the excitation frequency is changed. can.

Further, for each period of the strip conductor, either a single resonant element or a plurality of resonant elements are provided which are electrically coupled to the strip conductor within the period with a dielectric interposed therebetween. With such a configuration, the phase of the excitation current can also be controlled.

Embodiment FIG. 1 shows a phase control microstrip line antenna (hereinafter abbreviated as antenna) according to an embodiment of the present invention.
10 is a perspective view of FIG. Referring to FIG.
The basic structure of is explained.

The antenna 10 includes a substrate 11 made of a flat dielectric material, and a strip conductor 12 made of copper or the like and having a periodically curved shape as shown in the first figure is provided on one surface of the substrate 11. is formed. A ground conductor 13 is bonded to the entire surface of the substrate 11 opposite to the surface on which the strip conductor 12 is formed (back surface). Further, on the surface of the strip conductor 12ff1 of the substrate 11, a first resonant element 14 and a second resonant element 15 each having a rectangular plate shape, for example, are arranged for each cycle of the curved shape of the strip conductor 12, as described later.

FIG. 2 is an enlarged plan view of one period portion (hereinafter referred to as an antenna unit) 22 of the strip conductor 12. The configuration of the antenna 1o will be described in detail with reference to FIG. 2. The curved shape of the strip conductor 12 may be any shape, and various shapes such as a rank shape as described later may be arbitrarily selected. This strip conductor 12 is connected to the antenna unit 22.
A power supply line 16 that supplies power to the first resonant element 14 is provided at a position of length Ll along the strip conductor 12 from the starting end 12a of each cycle. At a position of length L2 along the strip conductor 12 from the end 12b of the repetition cycle to the start end 12a,
A power supply line 17 that supplies power to the second resonant element 15 is provided.

The length of these feed lines 16.17, measured along their shape, is L3. L4, a substantially rectangular resonant element 14.1
The lengths of 5 are selected as L 5 and L 6.

Further, the starting end 12a and the terminal end 1 of the strip conductor 12
2b, the starting end is the power supply side to the strip conductor 12.

The antenna 10 having the above-described structure emits a circular frequency beam through the strip conductor 12, converts the beams generated from the resonant elements 14 and 15 into circularly polarized waves, and combines them. As a result, the radiation efficiency of the beam radiated from the antenna 10 is improved, and the direction of the generated beam does not change unnecessarily even if the excitation frequency changes. The principles for obtaining these characteristics will be explained below.

Regarding the above-described improvement in radiation efficiency, it is known that microstrip line antennas that generally include a strip conductor having a periodically curved shape have relatively low radiation efficiency. On the other hand, it is known that a standing wave type wave source, such as the resonant elements 14 and 15 used in this example, has much higher radiation efficiency than a microstrip line antenna. Therefore, the antenna 1o of this embodiment, which is realized by combining these elements, can achieve high radiation efficiency not found in conventional microstrip line antennas, as will be described later.

In explaining the operating principle of the antenna 10 of the present invention shown in the first drawing having the above-mentioned characteristics, the curved shape of the strip conductor 12 will be explained as a crank shape as shown in the third drawing for the sake of simplicity. The conclusions and various effects of this example can be similarly concluded for the arbitrarily curved antenna 10 shown in FIG.

4th [2I] is a diagram illustrating the principle by which the antenna unit 22 shown in the third figure can generate a circularly polarized beam. This principle will be explained with reference to FIGS. 1 to 4. Here, the lengths 1 to L6 are set as follows. The parameters used are: ■ Strip conductor 12 of power supply line 17 from starting end 12a
Length X in the left and right direction in Figure 3 up to one connection point. , ■ Length so in the left-right direction in Figure 3 from the terminal end 12b to the connection point 19'i, ■ Length so in the left-right direction in Figure 3 from the terminal end 12b to the connection point 19'i;> Length of the part along Al 2Xa, ■ Length of the strip conductor 12 in the direction perpendicular to the arrangement direction A1, ■ Total length of the strip conductor 12 from the starting end 12a to the terminal end 12b, 'L=2a+c... <
7).

Based on these parameters, each of the above lengths Ll, B2
Set as below.

L 1 = XO+ b ・=
(9) L2 = so + c/2
- (10) The variables on the right side of the ninth and tenth equations and the lengths L3 to L6 described above are set as shown in the following equations.

xo+b=λg/2−(11)s
o+ e/2 = 3λg/4...
(12) L3=L4=λg/4...(
13) L5=L6=λg/2...(1
4) The principle by which the antenna unit 22 shown in FIG. 3 can realize circularly polarized waves under the conditions where each length is set in this way will be explained. Figure 4 (1) shows the direction of current in the strip conductor 12 when a current of wavelength λg is passed from the starting end 12a side of the strip conductor 12 at time t=Q.
Assume that from the starting end 12a to the connection point 18, a half period of the current is in the direction shown by the arrow B1.

Therefore, a current flows in the direction of arrow B2 toward the connection point 18 in the power supply line 16, but the length B3 of the power supply line 16 is λg/4 as shown in the above equation 13, and therefore The current in the B2 direction exists for half the length of the first resonant element 14 in the longitudinal direction, as indicated by the arrow B3. In the remaining portion (length λg/4) of the first resonant element 14, a current of λg/4 appears as indicated by arrow B4 in the opposite direction to arrow B3.

Moreover, the distance between the connection points 18 and 19 of the strip conductor 12 is 3λ
It has a length of g/4, and thus half a cycle of the current, indicated by arrow B5, appears in a portion of this section.

In the remaining portion, a half period of current appears, which passes through one connection point and extends to the portion of the strip conductor 12 in the vertical direction in FIG. 4, as indicated by arrow B6. A portion of this current flows into the power supply line 17 by a length of λg/4. Therefore, a half cycle of current appears in the resonant element 15, as indicated by arrow B7. On the other hand, opposite to the current indicated by arrow B6 in the strip conductor 12, a half-cycle current indicated by arrow B8 appears toward the terminal end 12b. At this time, the fourth
As shown in Figure (1), the components in the horizontal direction in Figure 4 are canceled out and become zero, leaving only the components in the vertical direction in Figure 4. In this way, at the time of Figure 4 (1), , the generated beam will be directed in the direction of arrow F1.

The state at the time when 1/4 fQ has elapsed from the time point in FIG. 4(1) is shown in FIG. 4(2). At this time, the strip conductor 12, the feed line 16, 17 and the resonant element 1
The direction of each current in 4.15 is indicated by arrows C1 to CIO in FIG. 4(2). In this case, Section 4 [21(1)
According to the principle explained with reference to FIG. 9, the clear direction of the generated beam will be rotated by 90 degrees from the case of FIG. 4(1), as shown by arrow F2.

From the point in Figure 4 (2), an additional 1/4 fa
has passed, and from the case of Figure 4 (1), time 2/4
After f, the direction of the current in each part such as the strip conductor 12 becomes as shown in FIG. 4(3), and the generated beam 11 is deflected in the direction of arrow F3.

The state of the current in the strip conductor 12, etc. at the time when 1/4F has elapsed from the time point in FIG. 4(3) and the time 3/4f has elapsed from the time point in FIG. 4(1) is shown in FIG.
4). In this case, the strip conductor (ltc 1
The current for each half wavelength in 2 is indicated by arrows E1 and ~E10, and the f of the generated beam obtained by combining them is
lf direction meat direction i) is indicated by F 4.

In this way, the above figures 4(1) to 4(4)
As shown in FIG. 3, the configuration shown in FIG. 3 generates a clockwise circularly polarized beam for each period 1/f0 of the current flowing through the strip conductor 12.

FIG. 5 is an equivalent circuit diagram of the antenna unit '22 shown in FIG. Regarding the resonant element 14.15, the impedance Z
l, Z2 is assumed, and an impedance ZO is assumed for the remaining strip conductor 12. Also, the input voltage ■i
, input impedance Zi and excitation current Ii, it is assumed that an output voltage Vout and an output current I out are obtained. At this time, regarding the four-terminal circuit constants A, B, C, and D, the following holds true.

On the other hand, the iterative propagation constant O is expressed as follows with respect to the attenuation amount αi and the phase amount βi of the antenna 1o: 0−“i+βi (16).Regarding such a recurrent propagation constant e, 0 += = <^+D)/2+[(^+D)/2) 2
-1 ,,,(17)-O=<^+D)/2- JT(
^+D)/2:I 2-1-(18) holds true.

Figure 6 shows the results of measuring the continuous displacement amount Δ(βi) of the attenuation amount αi and phase amount βi obtained by solving Equations 16 to 18 above under the east CF shown in Table 1 below. The horizontal axis in FIG. 6, shown in the graph, is a value obtained by normalizing the deviation amount Δf of the used center frequency f, divided by the used center frequency f0. Line No. 1 is the phase displacement amount Δ(βi
), the line, /2. , f3 is antenna 1
3 shows changes in the phase displacement amount Δ(βi) and the attenuation amount αi at zero.

Here, the direction of the beam generated from the antenna 10 is
It is determined by the principle described in the prior art section, and specifically, it is generated in a direction that satisfies the condition of equation 6. Here, regarding the above-mentioned formula 6, if the used center frequency f0 changes, a change will also appear in the wave number, etc. The condition corresponding to Equation 6 in such a case is shown by the following equation.

[βL2+Δ(βL2)] −(k+Δk) L +5in(θ+Δθ)=2nyr
...(19) At this time, by setting the approximation condition of 1Δθ1(1...(20) and solving Equation 19 using the directional displacement amount Δθ, Δθ=[Δ(βL2)−ΔkL sinθ]/ kLco
sθ
, , -(21) is obtained.

゛Also, the direction of the beam to be radiated from the antenna 10 is θ=
Assuming 90 degrees, for directional displacement 1Δθ, Δθ=Δ(βL,)/kL...(
22) is obtained.

The antenna 1o of this embodiment includes a resonant element 14.15 in addition to the strip conductor 12, and therefore the calculated directional displacement amount Δθ is Δθ = Δβi/kL
...(23) is obtained. Therefore, in order to suppress the directional displacement Δθ of the radiation beam at 1° of the antenna of this embodiment, 1Δβ;1 (1Δ(βL2)1...(
24) must hold true.

The condition of Equation 24 above appears as a tendency for the slope of the curve representing the obtained phase amount to approach zero as much as possible in the graph shown in FIG.

It goes without saying that a smaller attenuation amount αi is a better condition.

The antenna 10 of this embodiment under the above conditions is LINE! As shown in Figure 2, very good results were obtained.

FIG. 7 shows the total length of the strip conductor 12 along the extending direction of the antenna 10 shown in FIG. 3! 6 is a graph showing changes in the attenuation amount αi and the phase displacement amount Δ(βi) when the length L3°L4 of the power supply line 16.17 is slightly shorter than the case shown in FIG. 6. . The solid line! 1° Noah indicates the case of only the strip conductor 12, and the broken line 5. No. 8 is the full length mentioned above! The dotted line /6.79 represents the attenuation amount αi and the phase displacement amount Δ(βi) when the total length l is slightly increased.

It is understood that under the conditions described above, characteristics different from those in the case of FIG. 6 can be obtained. FIG. 8 is a graph showing data when the Q value of the antenna 10 is decreased under basically the same conditions as in FIG. 7. Each curve in FIG. 8 corresponds to each curve in FIG. 7, so that the corresponding curves have the reference numeral J! used in FIG. 4 to 9 are shown with a subscript a.

Antenna 10 having the basic configuration shown in FIG. 3 as described above
The same phenomenon as described above can be achieved even if the shape of the strip conductor 12 is not limited to a crank shape, but is also a strip conductor 12 having an arbitrary periodic shape as shown in the second figure. In such a case, the resonant elements 14 and 15 connected to the strip conductor 12
The shape is not limited to the shape shown in FIG. 21, but can be similarly realized by a shape obtained by stacking these shapes in a cross shape, that is, a resonant element 20 having a shape as shown in FIG. 9.

The resonant element 20 is basically obtained by cutting off four joints of a rectangular metal plate into a square shape.

Further, the present invention provides a resonant element 21 having a shape as shown in FIG. 10.
This can be similarly achieved using .

The resonant element 21 has the shape of a rectangular metal plate with the top portion on one diagonal line cut off, and is connected to the strip conductor 12 by a single power supply line 22 .

The antenna 10a as shown in FIG.
This is shown in the illustrated circuit. Equations corresponding to the 15th to 18th equations in such an equivalent circuit include the following 25th and 26th equations as the 15th and 16th equations.

O; αi+jβi =, 17nV, /V2 = , l' ++ I I/ I 2
(26) Also, for the 17th equation and the 18th equation, formulas with the same expression are used.

Regarding the configuration shown in No. 1012I, the attenuation amount αi and the phase displacement amount Δ(β
The data measured for i) is shown in the 12th [hJ.

The line in Figure 12! 1 is the data in the case of only the strip conductor 12 as described above, and the line J! 10. )
11 indicates the phase displacement amount Δ(βi) and the attenuation amount αi of the configuration shown in FIG. 10, respectively.

As described above, the present invention does not limit the shape of the strip conductor 12 to the crank shape, and the use of the crank-shaped strip conductor 12 in the above explanation is for convenience of explanation only.

That is, the shape of the strip conductor 12 of the present invention is
Various shapes as shown in FIGS. 1 to 15 can be similarly realized.

Furthermore, the beam generated by the phase-controlled microstrip linen antenna of the present invention is not limited to circularly polarized waves. For example, by having the configuration of the strip conductor 12 shown in FIG. A linear polarization in the direction and arrow F6 direction can be realized. Furthermore, although the turned-edge shape of the strip conductor 12 in this embodiment will be described as a crank shape, it goes without saying that it may be any repeating shape as in each of the above-described embodiments.

In the configuration shown in FIG. 16, by selecting the lengths H1 to H3 of each side constituting the crank-shaped strip conductor 12 to be λ8/2 with respect to the wavelength λg of the current used, the same structure as described in FIG. 4 can be obtained. From consideration, it is confirmed that linear polarization in the direction of arrow F5 is realized.

In FIG. 17, a crank-shaped strip conductor 1
Regarding the lengths H1 to H3 of each part constituting 2, H1=H2=λ[1/4...(27
)H3=5Ag/4...(2
8), it is confirmed that linear polarization in the direction of arrow F6 is realized by similar consideration.

At this time, the length H4 of the resonant element 21 is selected to be λg/2, and the installation position on the strip conductor 12 is selected such that the length F5 in FIG. 17 is λg/2.

With such a configuration, it is possible to obtain the same effects as those described in each of the above-described embodiments.

Furthermore, the manner of connection between the strip conductor and the resonant element in the present invention is not limited to the above-mentioned embodiments. For example, as shown in FIG. According to the principles described in each of the above embodiments, the arrangement of the feed lines 33 and 34 to the strip conductor 30 with respect to the resonant element 32 may be arranged respectively. The position is provided at a length LIO along the strip conductor 30 from the feed point 37 of the strip conductor 30/\.

At this time, the strip conductor 3 connecting the power supply line 34
1 connection position 35 and the feed point 3 to the strip conductor 31
The length along the strip conductor 31 between 7 and the feed point 36 that feeds power in the same phase is selected as the above-mentioned length LIO. As a result, the phase of the current flowing into the power supply line 34 from the strip conductor 31 becomes the same as that of the strip conductor 30.

Even with such a configuration, the same effects as those described in each of the above embodiments can be obtained.

FIG. 18A shows an antenna 10 according to a further embodiment of the present invention.
It is a top view which shows the example of a structure of e. In the antenna 10e, as shown in FIG. 18A, feed lines 44 and 44 for feeding power to the resonant element 42 are arranged on two strip conductors 40 and 41 that are adjacent to each other. Here, according to the principle described in each of the above embodiments, the arrangement position of the feed line 43 to the strip conductor 40 with respect to the resonant element 42 is from the feed point 45 of the strip conductor 40/\ to the strip conductor 4.
0 at a position of length Lll.

At this time, the length L12 along the strip conductor 41 between the connection position 46 of the strip conductor 41 to which the feed line 44 is connected and the feed point 47 that feeds power in the same phase as the feed point 45 to the strip conductor 41 is defined as: choose.

FIG. 18B is a diagram illustrating the principle by which the antenna 10e shown in FIG. 18A can generate a circularly polarized beam. This principle will be explained with reference to FIGS. 18A and 18B. The dimensions of each part of the antenna 10e correspond to the antenna unit 22 in FIG. 4, respectively.

The principle by which such an antenna 10e can realize circularly polarized waves will be explained. The direction of current in the strip conductor 42, etc. when a current of wavelength λg is passed from the starting end 45.47 side of the strip conductor (*40° 41 at time t=Q) is shown in FIG. 18B (1). 45. From 47 to the connection point 48, it is assumed that the half-cycle of the current is in the direction indicated by the arrow F1.Therefore, in the power supply line 43, a current flows in the direction of the arrow F2 toward the connection point 48. However, the length L3 of the power supply line 43 is λg1/4 as shown in Equation 43 above, so that the current in the direction of arrow F2 is only half the length of the first resonant element 49 in the longitudinal direction. The remaining portion (length λg, /4) of the first resonant element tl9 has a length of λg+/4 shown by arrow F4 in the opposite direction to arrow F3. A current appears.

Furthermore, the length between the connection points 48° and 46 of the strip conductors 40 and 41 is 5Ag/4, so that a half-period bone of the current shown by the arrow RF5 appears in this portion. The remaining part is marked with arrow F6. ．． Each half-cycle bone current shown as F7 appears. A portion of this current F7 flows into the power supply line 44 by a length of λg/4. Therefore, a half cycle of current appears in the resonant element 50, as indicated by arrow F8.

At this time, as shown in FIG. 18B (1), the components in the horizontal direction in FIG. 18B are canceled out and become zero, leaving only the component in the vertical direction in FIG.
At the time of Figure 8B (1), the generated beano is arrow G
It will be deflected in one direction.

The state at the time when 1/4L has elapsed from the time point in FIG. 18B (1) is shown in FIG. 18B (2).

At this time, the strip conductor 40. ．． 41, power supply line 4
3.44 and the direction of each current in the resonant element 49.50 is indicated by arrows 1-14 to H10 in FIG. 18B (2). In this case, according to the principle explained with reference to FIG. 18B (1), the deflection direction of the generated beam is indicated by the arrow G2.
As shown in FIG. 18B, the state is rotated by 90 degrees from the position shown in FIG. 18B (1).

From the time point in FIG. 18B (2), another time 1/4 r0 has elapsed, and from the case in FIG. 18B (1), time 2/>4 "
. The strip conductor 40.111
The direction of the current in each part is as shown in FIG. 18B (3), and the generated beam is deflected in the direction of arrow G3.

Time 1 from the time point in FIG. 18B (3). /4f has elapsed, and time 3/4f has passed since the time point in FIG. 18B (1).

The state of the current in the strip conductors 40, 41, etc. at the elapsed time is shown in FIG. 18B (1). The currents for each half wavelength in the strip conductors 40, 41 in this case are indicated by arrows J4 to J8, and the deflection direction of the generated beam obtained by combining these is indicated by arrow G4.

In this way, the above-mentioned Figures 18B (1) to 18B
As shown in FIG. 4, a clockwise circularly polarized beam is generated for each period of 1/f of the current flowing through the strip conductor 40, 41.

FIG. 18C shows an antenna 10 according to a further embodiment of the present invention.
It is a top view which shows the example of a structure of f. 18C (Referring to 2I, the antenna 10f has the same configuration as the power supply line 41 connected in parallel, in addition to the configuration provided in the power supply line 40 of the embodiment described with reference to FIG. 18A. I am trying to set it up.

With such a configuration as well, the same effects as those of the above-described embodiments can be achieved.

Further, the resonant element used in the present invention is not limited to the shape of each of the above-mentioned embodiments, and may be a resonant element 38 having a substantially elliptical shape as shown in FIG. 19. When power is supplied to the resonant element 38 at one point, the power is supplied at a position other than the long sleeve and short axis of the ellipse shown in FIG. 19. This single point power supply position 3
The angle φ between the two long sleeves may be selected, for example, from about 35° to 45°. When power is supplied in this way, the resonant element 3
8, currents flow in the directions of arrows Gl and G2, thereby realizing, for example, circularly polarized waves.

When power is supplied to the resonant element 38 at two points, the power is supplied at power supply positions 40 and 41 on the long and short axes of the ellipse shown in FIG. When power is supplied in this way, the resonant element 3
8, currents flow in the directions of the arrows Gl and G2. After all, it is possible to achieve circularly polarized waves.

FIG. 20 shows an antenna unit 2 of still another embodiment of the present invention.
2 is a plan view of FIG. This embodiment is similar to the embodiment described above, for example, shown in FIG. 9, and corresponding parts are given the same reference numerals. What is noteworthy about this embodiment is that the strip conductor 12 is formed into a crank shape, and recesses 50 and 51 are formed in the mounting portions of the resonance element 2o to which the power supply lines 16 and 17 extending from the strip conductor 12 are attached. That's what I did.

Generally, in a batch antenna with the shortest distance d2 to the center position 52 as shown in FIG. It is known that the impedance Z1 of the batch antenna in which 50.51 is formed can be obtained by the following formula.

Z1 = (d2-di) Z/d2-(
30) Therefore, by appropriately selecting the depth dl of the recesses 50, 51, it is possible to easily achieve the desired impedance for the batch antenna.

FIG. 21 shows an antenna unit 2 of still another embodiment of the present invention.
2 is a plan view of FIG. This example will be described with reference to No. 21121. This example is similar to the previous example;
Corresponding parts are given the same reference numerals. The noteworthy point of this embodiment is that the strip conductor 12 is formed into a crank shape, and the strip portions 12a, 12 of the strip conductor 12 are
A strip conductor 12a is placed on the head surrounded by +1, 12c.
, 12 b , and 12 c at a distance α1 . α2. α
Strip-shaped resonant elements 53a, 53 are spaced apart by 3.
b, 53c were arranged. Resonant element 53a is provided parallel to strip portion 12a, and resonant element 53b
is provided parallel to the strip portion 12b, and the resonant element 5
3c is provided parallel to the strip portion 12c.

Further, the length of each resonant element 53a, 53b, 53c is selected to be λg/2.

The distance α1°α2 between these strip portions 12a, 12b, 12c and the resonant elements 53a, 53b, 53c
．． The gaps 54a, 54b, and 54c of α3 are provided to cover the antenna unit 22. ! , a film, etc., virtually create an electrostatic window ff1c1. C2, C3, resistances R1, R2, R3 and inductance) I 1 .

R2,83 occurs.

FIG. 22 is an equivalent circuit diagram of the antenna unit 22 shown in FIG. 21. No. 21 (see Figures 21 and 22, No. 2
In the antenna unit 22 shown in Fig. 1, the strip conductor 12 and the strip portion 53 are electrically connected through electrostatic induction and electromagnetic induction over their entire length, and their equivalent impedance is as shown in Fig. 22. First, with respect to the strip conductor 12, a plurality of impedance units 55 connected in parallel are assumed.

FIG. 23 is an equivalent circuit diagram of the impedance unit 55 shown in FIG. 22. With reference to FIGS. 21 to 23,
In the configuration example shown in the figure, the various electrical constants described above are assumed for the gap 54, so the impedance unit 55 includes capacitance, ! EC1
A resistance R and an inductance H are respectively assumed.

Here, in the antenna unit 22 as shown in 21 [1], the formulas corresponding to the 15th and 16th formulas include the 25th and 26th formulas, and regarding the 17th and 18th formulas, , the same expression is used. At this time, the four-terminal circuit constants A, B, C, in Equation 25,
D, the above-mentioned electric constants C, R,
This will include H.

No. 24 [2I is a plan view showing a configuration example of still another embodiment of the present invention. This embodiment will be described with reference to FIG. 24. This example is similar to each of the previous examples.
, corresponding parts are given the same reference numerals. The noteworthy point of this embodiment is that the strip-shaped resonant elements 53a and 53b
, 53c are selected to be λg/4. Although such a configuration example can also achieve the effects described in each of the above-mentioned embodiments, in the case of this embodiment, the resonant element 53
a, 53b, and 53C must each be grounded at one end.

FIG. 25 is a plan view showing a configuration example of still another embodiment of the present invention. This embodiment is similar to the previous embodiments, and corresponding parts are given the same reference numerals.

The noteworthy point of this embodiment is that the resonant element 53 is a rectangular batch. Even in such a configuration example, the gaps 51111.54b, 54 realize the electrical constant due to the electrical connection between the strip conductor 12 and the resonant element 53.
c. Such a configuration also makes it possible to achieve the effects described in each of the above-described embodiments.

FIG. 26 is a perspective view showing the configuration of still another embodiment of the present invention, and FIG. 27 is a section line XXXI-X in FIG. 26.
It is a sectional view seen from XX[[. Figures 26 and 27
111, this embodiment will be described. This embodiment is similar to the previous embodiments, and corresponding parts are given the same reference numerals.The noteworthy point of this embodiment is that the antenna 1
For example, a strip conductor 12 is formed on the side opposite to the ground conductor 13 of the dielectric substrate 11 constituting 0, and a dielectric layer 55 is formed thereon. Then, a batch 53 was formed on this dielectric layer 55.

In this embodiment, a portion corresponding to the gap 54 in each of the above embodiments is a dielectric portion 56 having a distance t1 and an overlap width s1 between the batch 53 and the strip conductor 12. That is, the gap 54 in the embodiment described above was the interval between the strip conductor 12 and the batch 53 formed on the same plane, but in this embodiment it is the interval in the direction perpendicular to the plane.

Even with such a configuration, the electrical coupling between the strip conductor 12 and the patch 53 described above can be achieved, and therefore the same effects as those described in each of the above embodiments can be achieved.

Furthermore, in this embodiment, the strip conductor 12 and the patch 53
Since the antennas 10 and 10 are arranged vertically, a large degree of freedom is allowed in their arrangement, and various types of antennas 10 can be manufactured.

FIGS. 28 and 29 are plan views showing the configuration of still another embodiment of the present invention. Each embodiment will be described with reference to these drawings. The configuration example in FIG. 28 is similar to the configuration examples in FIGS. 10 and 25. The feature of this embodiment is that a pair of corners on one diagonal line of the batch 53 formed in the area surrounded by the strip conductor 12 and separated from the strip conductor 12 are cut out.

The configuration example of No. 29121 is similar to the configuration example of FIG. 21.
The feature of this embodiment is that the resonant element 5 in the configuration example shown in FIG.
3b and 53c are integrated into an abbreviated resonant element 53d
The purpose of this is to provide a .

The total length of this resonant element 53d is selected to be, for example, λg/2. With such a configuration, the same effects as those described in each of the above-mentioned embodiments can be achieved.

In each of the above-mentioned embodiments, power is fed to each strip conductor 12, 30, 31 from the left side of the drawing to achieve, for example, right-handed circularly polarized waves, but by feeding from the right side of the drawing, left-handed circularly polarized waves are realized. Of course, waves can be easily realized.

Effects As described above, according to the present invention, single or plural resonant elements are arranged in a periodic array of strip conductors.

This makes it possible to control the configuration of each period of the strip conductor and the phase of the excitation current flowing through the resonant element, thus preventing the direction of the generated beam from changing even if the excitation frequency is changed. I was able to do that.

Further, for each period of the strip conductor, either a single resonant element or a plurality of resonant elements electrically connected to the strip conductor within the period through a dielectric material were disposed. A similar effect can also be achieved by this.

[Brief explanation of the drawing]

FIG. 1 is a perspective view of an antenna 10 according to an embodiment of the present invention, FIG. 2 is a plan view of the antenna 10 with a repetition period, and FIG. 3 is a perspective view of a strip conductor 12 having a crank shape according to an embodiment of the present invention. 4 is a diagram explaining the present invention in detail, FIG. 5 is an equivalent circuit diagram of the configuration shown in FIG. 3, and FIGS. 6 to 8 are diagrams showing the antenna 10 of this embodiment. A graph explaining the characteristics, FIG. 9 is a plan view showing the configuration of another embodiment of the present invention, FIG. 10 is a plan view showing the configuration of a further embodiment of the present invention, and FIG. 12 is an equivalent circuit diagram of the configuration shown in FIG. 10. 13 to 15 are perspective views illustrating the shape of the strip conductor 12 in other embodiments of the present invention, and FIGS. 16 and 17 are graphs illustrating the characteristics of the strip conductor 12. ! A plan view illustrating the shape of a strip conductor 12 that realizes polarization,
FIG. 18 is a plan view showing the connection state of each part of still another embodiment of the present invention, FIG. 18A is a plan view showing a configuration example of an antenna 10e of still another embodiment of the present invention, and FIG. 18B is a 18A is a diagram illustrating the principle by which the antenna 10e shown in FIG. FIG. 20 is a plan view of a resonant element 38 according to still another embodiment of the present invention, FIG. 20 is a plan view of an antenna unit 22 according to still another embodiment of the present invention, and FIG. A plan view of the unit 22, FIG. 22 is an equivalent circuit diagram of the antenna unit 22 shown in FIG. 21, FIG. 23 is an equivalent circuit diagram of the impedance unit 55 shown in FIG. 22,
FIG. 24 is a plan view showing a configuration example of still another embodiment of the present invention, FIG. 25 is a plan view showing a configuration example of still another embodiment of the present invention, and FIG. 26 is a plan view showing a configuration example of still another embodiment of the present invention. A perspective view showing the configuration of the embodiment, FIG. 27 is taken along the section line XXX of FIG. 26.
Sectional view from II-XXXI, Figures 28 and 29
The figures are plan views showing the configurations of still other embodiments of the present invention, and FIG. 30 is a plan view showing a typical conventional technique ((:1). 10
f-phase control microstrip linen antenna, 12° 30.31... strip conductor, 12a... starting end,
12b...Terminal, 14, 15, 20, 21, 32.3
8... Resonant element, 16.17, 22, 33.34...
・Power supply line agent Patent attorney Number of strokes Keiichi 12 Figure No. 4 (1) (t=o) (3Xt-%fo) (2) (t=!/4fo) (4) (t=%fo) N9 Prisoner No. Figure 10 Δf/fo ('/,) 11 1j Figure 16 Figure 17 Figure 18 Figure 19 Figure 18B O-01 (1) (t=o) (3) (t '' (t-,) Fig. 20 Fig. 21 Fig. 22 Fig. N23 Fig. 24 Fig. 25 b3 Fig. 26 Fig. 22 No' Fig. 27 Fig. 28

Claims (2)

[Claims] (1) In a microstrip line antenna including a dielectric substrate, one or more periodically curved strip conductors, and a ground conductor, each period of the strip conductor has a single or plural strips. 1. A phase control microstrip line antenna characterized in that either a single or a plurality of resonant elements that are supplied with power from a predetermined position on a conductor are arranged to perform phase control. (2) In a microstrip line antenna including a dielectric substrate, one or more periodically curved strip conductors, and a ground conductor, for each period of the strip conductor, the strip conductor within the period is 1. A phase control microstrip line antenna characterized in that either a single or a plurality of resonant elements electrically coupled to a resonant element via a dielectric are arranged to perform phase control.