JPH01129772A - Controller for pulse width modulation power converter - Google Patents
Controller for pulse width modulation power converterInfo
- Publication number
- JPH01129772A JPH01129772A JP28539287A JP28539287A JPH01129772A JP H01129772 A JPH01129772 A JP H01129772A JP 28539287 A JP28539287 A JP 28539287A JP 28539287 A JP28539287 A JP 28539287A JP H01129772 A JPH01129772 A JP H01129772A
- Authority
- JP
- Japan
- Prior art keywords
- pulse width
- gate signal
- input current
- converter
- width modulation
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Pending
Links
- 239000003990 capacitor Substances 0.000 claims abstract description 4
- 229920006395 saturated elastomer Polymers 0.000 abstract description 5
- 230000010287 polarization Effects 0.000 abstract 1
- 238000010586 diagram Methods 0.000 description 5
- 238000000034 method Methods 0.000 description 5
- 230000007423 decrease Effects 0.000 description 2
- 230000000694 effects Effects 0.000 description 2
- 238000005516 engineering process Methods 0.000 description 2
- 230000008929 regeneration Effects 0.000 description 2
- 238000011069 regeneration method Methods 0.000 description 2
- 230000005856 abnormality Effects 0.000 description 1
- 238000006243 chemical reaction Methods 0.000 description 1
- 230000001276 controlling effect Effects 0.000 description 1
- 238000001514 detection method Methods 0.000 description 1
- 238000009499 grossing Methods 0.000 description 1
- 230000005389 magnetism Effects 0.000 description 1
- 230000005415 magnetization Effects 0.000 description 1
- 230000002265 prevention Effects 0.000 description 1
- 230000001105 regulatory effect Effects 0.000 description 1
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Abstract
Description
【発明の詳細な説明】
〔産業上の利用分野〕
本発明は単相交流を直流に変換するパルス幅変調電力変
換器(以下、PWMコンバータと略称)の制御装置に係
り、特に、交流電流の過電流防止に好適な制御方式に関
する。[Detailed Description of the Invention] [Field of Industrial Application] The present invention relates to a control device for a pulse width modulation power converter (hereinafter abbreviated as PWM converter) that converts single-phase alternating current to direct current, and particularly relates to a control device for a pulse width modulation power converter (hereinafter referred to as a PWM converter) that converts single-phase alternating current to direct current. The present invention relates to a control method suitable for overcurrent prevention.
PWMコンバータは力率がほぼ1での順逆変換動作が可
能であり、また、発生高調波を低減できるなどの特徴を
もつ、このような特徴を実現し、マイクロプロセッサの
適用に適した制御装置として1例えば、特開昭58−7
9478号公報の方式が挙げられる。この方式は、また
、主回路を構成するGTOの最小オン・オフ時間の管理
が容易で。PWM converters are capable of forward and reverse conversion operations with a power factor of approximately 1, and can also reduce generated harmonics, making them ideal control devices for use with microprocessors. 1 For example, JP-A-58-7
An example is the method disclosed in Japanese Patent No. 9478. This method also makes it easy to manage the minimum on/off time of the GTO that constitutes the main circuit.
PWMコンパご夕を多重接続した際に、高周波を効果的
に低減できる相差運転が可能な方式でもある。It is also a method that allows phase difference operation that can effectively reduce high frequencies when multiple PWM comparators are connected.
交流電気車両の架線側電力変換器としてPWMコンバー
タを適用した場合、装置の小形・軽量化を図るため、変
圧器の漏れインダクタンスを太きくとって、交流リアク
トルを省略するか、あるいは、ごく小容量の交流リアク
トルを補助的に設けるのが一般的である。この様な装置
では、変圧器が直流偏磁等の原因により飽和すると、交
流側のインダクタンスは通常の数分の一程度にまで減少
し、上記のような従来技術ではPWMコンバータの交流
入力電流が増加して、運転が困難となる問題があった。When a PWM converter is applied as a power converter on the overhead line side of an AC electric vehicle, in order to make the device smaller and lighter, the leakage inductance of the transformer is made large and the AC reactor is omitted, or the AC reactor is omitted, or the capacity is very small. It is common to provide an auxiliary AC reactor. In such devices, when the transformer becomes saturated due to DC bias, the inductance on the AC side decreases to a fraction of its normal inductance, and in the conventional technology described above, the AC input current of the PWM converter is There were problems that increased and made driving difficult.
本発明の目的は、交流入力電流の増加を防止し、継続し
て運転が可能となるPWMコンバータの制御方式を提供
することにある。An object of the present invention is to provide a control method for a PWM converter that prevents an increase in AC input current and enables continuous operation.
上記目的は、変圧器のインダクタンスの変化をPWMコ
ンバータの交流入力電流の時間変化率により検知して、
異常時には入力電流のピーク値を瞬時レベルで制御可能
なゲート信号発生手段に切換えることにより達成される
。The above purpose is to detect the change in the inductance of the transformer by the time rate of change of the AC input current of the PWM converter,
This is achieved by switching to a gate signal generating means that can control the peak value of the input current at an instantaneous level when an abnormality occurs.
交流入力電流の時間変化率が所定値を超えたとき、変圧
器が直流偏磁等により飽和したと判断して、通常のゲー
ト信号から交流入力電流のピーク値の管理に適したゲー
ト信号に切換える。これによって、交流入力電流が過電
流となるのを防止する。When the time rate of change of AC input current exceeds a predetermined value, it is determined that the transformer is saturated due to DC bias, etc., and the normal gate signal is switched to a gate signal suitable for managing the peak value of AC input current. . This prevents the AC input current from becoming an overcurrent.
第1図は本発明の一実施例を示す0図において、FDR
は交流架線、PANはパンク、MTRは架線電圧を降圧
するための変圧器、ACLは交流リアクトル、DCCは
直流電圧平滑用の直流コンデンサ、LOADは負荷装置
、61〜G4は主回路を構成するゲートターンオフサイ
リスタ(以下、GTOと略称)、D1〜D4は逆並列ダ
イオードである。また、AVEは平均値検出器、PMS
は実効値検出器、PDDは位相検出器である。FIG. 1 shows an embodiment of the present invention in which FDR
is an AC overhead line, PAN is a puncture, MTR is a transformer to step down the overhead line voltage, ACL is an AC reactor, DCC is a DC capacitor for DC voltage smoothing, LOAD is a load device, and 61 to G4 are gates that make up the main circuit. Turn-off thyristors (hereinafter abbreviated as GTO) and D1 to D4 are anti-parallel diodes. Also, AVE is an average value detector, PMS
is an effective value detector, and PDD is a phase detector.
AVRは、直流電圧指令E−とAVEの出力である直流
電圧平均値E4との偏差から入力電流isの実効値指令
IS傘(入力電流指令)を作成する電圧調節器、ACR
はIS・とRMSの出力であるisの検出実効値Isと
の偏差からPWMコンバータの交流側端子電圧8c
(以下、コンバータ入力電圧と略称)のパンク電圧ep
との直交成分指令値Ec−(虚軸成分)を作成する電流
調節器、APRは力率角指令値φ拳と位相検出器PDD
の出力である力率角検出値φとの偏差からコンバータ入
力電圧ecのパンク電圧epとの同相成分Ecr・実軸
成分)を作成する力率調節器、CTRは直交座標上の指
令値Ecr” %及び、Ec−を極座標上の振幅指令E
CS、及び1位相角指令o傘に変換する座標変換器、P
WMIはEc*と0・によりパルス幅変調を行い、ゲー
ト信号を作成する第一のパルス幅変調器である。一方、
PWM2はIs・、φ−及び入力電流の瞬時値fsより
パルス幅変調を行いゲート信号を作成する第二のパルス
幅変調器であり、GSLはisの時間変化率に応じてゲ
ート信号を切換えるゲート信号切換え器である。AVR is a voltage regulator that creates an effective value command IS umbrella (input current command) for input current is from the deviation between DC voltage command E- and DC voltage average value E4, which is the output of AVE.
is the AC side terminal voltage 8c of the PWM converter from the deviation between IS・ and the detected effective value Is of is, which is the RMS output.
(hereinafter abbreviated as converter input voltage) puncture voltage ep
The current regulator creates the orthogonal component command value Ec- (imaginary axis component), APR is the power factor angle command value φ fist and the phase detector PDD.
CTR is a power factor regulator that creates the in-phase component Ecr and real axis component of the converter input voltage ec with the puncture voltage ep from the deviation from the detected power factor angle value φ, which is the output of the converter input voltage ec. % and Ec- as amplitude command E on polar coordinates
CS, and a coordinate converter that converts one phase angle command o umbrella, P
WMI is a first pulse width modulator that performs pulse width modulation using Ec* and 0* to create a gate signal. on the other hand,
PWM2 is a second pulse width modulator that performs pulse width modulation from Is・, φ− and the instantaneous value fs of the input current to create a gate signal, and GSL is a gate that switches the gate signal according to the time rate of change of is. It is a signal switch.
次に、動作について説明する。Next, the operation will be explained.
変圧器の二次電圧e3のベクトルEl (=ES )を
基準として、入力電流i3.及び、コンバータ入力電圧
ecの基本波ベクトルをIs 、Ecとすれば1
、Es−Ec
jωL
ωL ωL
ここに、ω:電源角周波数
L:ACLのインダクタンス
Ecr:Ecの実軸成分
Eci:Ecの虚軸成分
上式のように、PWMコンバータではコンバータ流を、
また、Ecの実数成分Ecrの調節により無効電流を、
それぞれ、独立に制御できる。従って、第1図に示すよ
うに、EctをAVR,及び、ACRから成る電圧制御
系で調節することにより直流出力電圧E−は所定値に制
御され、APRを含む力率調節系でEcrを調節するこ
とにより力率を、はぼ1(φ=O)に制御することがで
きる。Based on the vector El (=ES) of the secondary voltage e3 of the transformer, the input current i3. And, if the fundamental wave vector of converter input voltage ec is Is and Ec, then 1, Es-Ec jωL ωL ωL where, ω: power supply angular frequency L: inductance of ACL Ecr: real axis component of Ec Eci: imaginary of Ec As shown in the above equation for the axis component, in a PWM converter, the converter flow is
In addition, by adjusting the real component Ecr of Ec, the reactive current can be
Each can be controlled independently. Therefore, as shown in Fig. 1, the DC output voltage E- is controlled to a predetermined value by adjusting Ect with a voltage control system consisting of AVR and ACR, and Ecr is adjusted with a power factor control system including APR. By doing so, the power factor can be controlled to approximately 1 (φ=O).
実際には、コンバータ入力電圧ecはGTOに与えるゲ
ート信号を制御することにより調節されるため、このゲ
ート信号を作成するパルス幅変調器PWMIが必要とな
る。第2図は、第1図中に示したパルス幅変調器PWM
Iの構成の一例を示したものである。同図において、E
CGは基本正弦波発生器、GPGIはゲート信号発生器
である。In practice, the converter input voltage ec is regulated by controlling the gate signal applied to the GTO, so a pulse width modulator PWMI is required to generate this gate signal. Figure 2 shows the pulse width modulator PWM shown in Figure 1.
This figure shows an example of the configuration of I. In the same figure, E
CG is a basic sine wave generator, and GPGI is a gate signal generator.
基本正弦波発生器ECGはコンバータ入力電圧ecの振
幅指令Ec*と位相角指令0傘からecの基本正弦波指
令ec−を作成し、これを直流電圧平均値E−で除する
ことにより変調正弦波y、を作成する。この変調正弦波
y、と三角搬送波ycとの差をとり、その符号によりゲ
ート信号発生器GPGIはGTOに与えるゲート信号G
S1を作成する。The basic sine wave generator ECG creates the basic sine wave command ec- of ec from the amplitude command Ec* of the converter input voltage ec and the phase angle command 0, and divides this by the DC voltage average value E- to generate a modulated sine wave. Create a wave y. The difference between this modulated sine wave y and the triangular carrier wave yc is taken, and based on the sign, the gate signal generator GPGI gives the gate signal G to the GTO.
Create S1.
一方、第1図における変圧器MTRが直流偏磁等の影響
により変圧器が飽和すると、変圧器のりアクタンスは急
激に減少し、入力電流isの時間変化率dss/dtは
第3図(C)のように変化す条、ゲート信号切換え器G
SLは、この時間変化率dzs/dtの大きさを検知し
て、その値が所定値を超えたとき、ゲート信号をGSl
からGS2に切換える。第二のパルス幅変調器PWM2
は、入力電流isのピーク値がGTOの遮断電流の許容
値を超えないように、GTOにゲート信号を与える。第
4図に、第二のパルス幅変調器PWM2の構成の一例を
示す、同図において、ISOは基本正弦波発生器、AB
Sは絶対値検出器、HCMはヒステリシス特性を持つ比
較器、GPG2はゲート信号発生器である。基本正弦波
発生器ISOは、入力電流isの実効値指令Is・と位
相角指令φ・(力行時φ傘=O°、回生時φ串=180
°)から第5図(a)に示すような基本正弦波指令is
*を作成する。このi−と入力電流isとの差が設定値
を超えると、比較器HCMは第5図(Q)に示す符号を
持った信号を出力し、ゲート信号発生器GPG2は比較
器HCMの出力とカ行/回生判別信号P/BによりPW
Mコンバータの運転モードを第5図(d)のように決定
して、これに応じたゲート信号を作成する。なお、第5
図(d)において、モードCは主回路の交流側と直流側
とが接続される充電モードであり、01オン、G4オン
、又は、02オン、03オンとなるモードである。また
、モードSは交流側と直流側が切り離され、交流側を短
絡する短絡モードであり、01オン、03オン、又は、
G2オン、64オンとなるモードである。On the other hand, when the transformer MTR in Fig. 1 becomes saturated due to the influence of DC bias magnetization, the transformer actance rapidly decreases, and the time rate of change dss/dt of the input current is becomes as shown in Fig. 3 (C). Gate signal switch G
SL detects the magnitude of this time rate of change dzs/dt, and when the value exceeds a predetermined value, the gate signal is changed to GSL.
Switch from GS2 to GS2. Second pulse width modulator PWM2
gives a gate signal to the GTO so that the peak value of the input current is does not exceed the allowable value of the cut-off current of the GTO. FIG. 4 shows an example of the configuration of the second pulse width modulator PWM2. In the same figure, ISO is a basic sine wave generator, AB
S is an absolute value detector, HCM is a comparator with hysteresis characteristics, and GPG2 is a gate signal generator. The basic sine wave generator ISO has an effective value command Is of input current is and a phase angle command φ (φ umbrella = 0° during power running, φ skewer = 180 during regeneration)
°) to the fundamental sine wave command is as shown in Figure 5(a).
Create *. When the difference between this i- and the input current is exceeds the set value, the comparator HCM outputs a signal with the sign shown in FIG. 5 (Q), and the gate signal generator GPG2 Power line/PW by regeneration discrimination signal P/B
The operating mode of the M converter is determined as shown in FIG. 5(d), and a gate signal corresponding to this is created. Furthermore, the fifth
In Figure (d), mode C is a charging mode in which the AC side and DC side of the main circuit are connected, and is a mode in which 01 on, G4 on, 02 on, and 03 on. Mode S is a short-circuit mode in which the AC side and DC side are separated and the AC side is short-circuited, and 01 on, 03 on, or
This is a mode in which G2 is on and 64 is on.
このようにして、入力電流Lsは、第5図(a)に示す
ように、指令値Is”に対して一定の幅を持って追従す
る。In this way, the input current Ls follows the command value Is'' with a certain width, as shown in FIG. 5(a).
本実施例によれば、変圧器が直流偏磁等により飽和した
場合にも、過電流に至ることはなく、継続した運転が可
能となる。According to this embodiment, even if the transformer becomes saturated due to direct current biased magnetism or the like, no overcurrent occurs and continuous operation is possible.
〔発明の効果〕
本発明によれば、変圧器の飽和によるインダクタンスの
変化を効果的に検出し、過電流を防止し。[Effects of the Invention] According to the present invention, changes in inductance due to transformer saturation can be effectively detected and overcurrent can be prevented.
PWMコンバータを停止させることなく継続した運転が
可能となる。Continuous operation is possible without stopping the PWM converter.
第1図は本発明の一実施例の回路図、第2図は第1図に
おける第一のパルス幅変調器の制御系統図、第3図は検
出方法の説明図、第4図は第1図における第二のパルス
幅変調器の制御系統図、第5図は第4図の動作説明図で
ある。
PWMI・・・第一のパルス幅変調器、PWM2・・・
第二のパルス幅変調器、GSL・・・ゲート信号切操え
第 2 目
′$ ≠閲
第51!1FIG. 1 is a circuit diagram of an embodiment of the present invention, FIG. 2 is a control system diagram of the first pulse width modulator in FIG. 1, FIG. 3 is an explanatory diagram of the detection method, and FIG. FIG. 5 is a control system diagram of the second pulse width modulator in the figure, and FIG. 5 is an explanatory diagram of the operation of FIG. 4. PWMI...first pulse width modulator, PWM2...
Second pulse width modulator, GSL...Gate signal control 2nd '$ ≠View 51!1
Claims (1)
ッチング素子をブリッジ接続し、その交流側端子は交流
リアクトルと変圧器を介して単相交流電源に接続され、
直流側端子足に直流コンデンサを備え、これと並列に負
荷を接続したパルス幅変調電力変換器と、前記パルス幅
変調電力変換器の直流出力電圧と力率を所定値に保つよ
うにパルス幅変調制御を行う制御装置とから構成される
パルス幅変調電力変換装置において、 ゲート信号を発生する手段を複数個備え、前記パルス幅
変調電力変換器の交流入力電流の時間変化率に応じて前
記ゲート信号を発生する手段を切換える手段を設けたこ
とを特徴とするパルス幅変調電力変換器の制御装置。[Claims] 1. A self-extinguishing switching element in which diodes are connected in antiparallel is bridge-connected, and its AC side terminal is connected to a single-phase AC power source via an AC reactor and a transformer,
A pulse width modulation power converter is equipped with a DC capacitor on the DC side terminal leg and a load is connected in parallel with the DC capacitor, and the pulse width modulation is performed to maintain the DC output voltage and power factor of the pulse width modulation power converter at predetermined values. A pulse width modulation power converter comprising a control device that performs control, comprising a plurality of means for generating a gate signal, the gate signal being generated in accordance with a time rate of change of an AC input current of the pulse width modulation power converter. 1. A control device for a pulse width modulation power converter, comprising means for switching means for generating.
Priority Applications (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP28539287A JPH01129772A (en) | 1987-11-13 | 1987-11-13 | Controller for pulse width modulation power converter |
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
JP28539287A JPH01129772A (en) | 1987-11-13 | 1987-11-13 | Controller for pulse width modulation power converter |
Publications (1)
Publication Number | Publication Date |
---|---|
JPH01129772A true JPH01129772A (en) | 1989-05-23 |
Family
ID=17690942
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
JP28539287A Pending JPH01129772A (en) | 1987-11-13 | 1987-11-13 | Controller for pulse width modulation power converter |
Country Status (1)
Country | Link |
---|---|
JP (1) | JPH01129772A (en) |
Cited By (1)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
WO2009050943A1 (en) * | 2007-10-19 | 2009-04-23 | Murata Manufacturing Co., Ltd. | Switching power supply |
-
1987
- 1987-11-13 JP JP28539287A patent/JPH01129772A/en active Pending
Cited By (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
WO2009050943A1 (en) * | 2007-10-19 | 2009-04-23 | Murata Manufacturing Co., Ltd. | Switching power supply |
US7852647B2 (en) | 2007-10-19 | 2010-12-14 | Murata Manufacturing Co., Ltd. | Switching power supply digital control circuit protecting from magnetic saturation effects |
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