JP7250236B2 - Drive control device for power converter - Google Patents

Description

TECHNICAL FIELD The present invention relates to a drive control device for a power converter that controls on/off of a drive circuit of the power converter.

In a switching power supply, which is an example of a power conversion device, output power is controlled by the ON/OFF time ratio of a drive circuit. ON/OFF by the drive circuit is performed by feedback control by the drive control device so that the output voltage becomes the target voltage. The output voltage overshoots and undershoots in the transitional period due to the ON/OFF of the drive circuit, and converges to the target voltage while repeating the gradually attenuating amplitude. Therefore, it is important to suppress this overshoot, undershoot, ringing, and the like.

Japanese Patent Laid-Open Publication No. 2002-100001 discloses such ON/OFF control of the drive circuit.
The control circuit and control method for the power conversion device described in Patent Document 1 add an overshoot or undershoot suppression amount that decays over time during the period of overshoot or undershoot, thereby suppressing overshoot or undershoot within a short period of time. It suppresses undershoot and brings the output closer to the reference value.
Specifically, when the output overshoots, an overshoot suppression amount including a temporal attenuation suppression amount defined in the overshoot period is added to the output feedback control amount, and when the output undershoots, An undershoot suppression amount including a temporal attenuation control amount defined in the period of undershoot is added to the output feedback control amount.

Japanese Patent No. 5401729

It is desirable that the overshoot and undershoot can converge to the target value by rapid suppression. Since it calculates the on-time of the switch, it may take a long time to respond.
Therefore, further improvement is desired for suppression of overshoot and undershoot.

SUMMARY OF THE INVENTION Accordingly, it is an object of the present invention to provide a drive control device for a power converter that can more effectively suppress overshoot and undershoot.

The present invention provides a drive control device for a power conversion device that controls current to a load, in which a first calculation unit calculates a deviation between an output to the load and a target value as a first gain; a second calculation unit for calculating a second gain by exponentiating a slope; an addition unit for adding the first gain and the second gain and outputting a gain adjustment value; and a feedback control section that performs the gain to correct the deviation between the output to and the target value.

According to the drive control device for the power conversion device of the present invention, the first calculation unit calculates the deviation between the output to the load and the target value as the first gain. Also, the second calculation unit exponentiates the slope of the output to the load to calculate the second gain. Then, based on the gain adjustment value obtained by adding the first gain and the second gain by the addition section, the feedback control section performs gain control to correct the deviation between the output to the load and the target value. Therefore, the transient response can be initially suppressed by the second gain based on the slope of the output, and thereafter suppressed by the first gain based on the deviation. Therefore, overshoot and undershoot can be suppressed and converged quickly.

The feedback control section performs only proportional control using the gain adjustment value as a proportional gain, or a combination of either one or both of integral control and differential control with proportional control. can be realized by a simple process of

The first calculation unit includes: a deviation calculation unit that calculates a deviation between the output to the load and a target value; a first absolute value calculation unit that calculates an absolute value of the deviation from the deviation calculation unit; and a first gain calculation section for calculating the first gain by adding a bias value to the output from the value calculation section multiplied by a constant.
By using the first calculation section including the deviation calculation section, the first absolute value calculation section, and the first gain calculation section, the deviation between the output and the target value can be output as the first gain.

The second calculation unit includes a buffer unit that stores the output and outputs the previous output, a slope calculation unit that calculates a slope by obtaining a difference between the output and the previous output, and a slope from the slope calculation unit. and a bias value is added to the result obtained by multiplying the output from the second absolute value computing unit to an exponentiation by a constant to calculate the second gain. and a 2-gain calculator.
By using the second calculation section including the buffer section, the slope calculation section, the second absolute value calculation section, and the second gain calculation section, the slope of the output can be output as the second gain.

If the gain adjustment value from the addition unit is equal to or greater than a predetermined threshold value, the gain adjustment value is directly output to the feedback control unit, and if the gain adjustment value is less than the threshold value, the gain adjustment value is used to suppress the gain. can be provided with a gain suppressing section that outputs a constant of to the feedback control section.
If the gain adjustment value is greater than or equal to the threshold, large deviations can be corrected, and if the gain adjustment value is less than the threshold, adverse effects on convergence can be avoided at large gains.

If the sign obtained by multiplying the deviation by the first calculation unit and the slope by the second calculation unit is a plus sign, the gain adjustment value is directly output to the feedback control unit, and if the sign is a minus sign. For example, it is possible to provide a gain suppressing section that outputs the gain adjustment value to the feedback control section as a constant for suppressing the gain.
During the period when the output is moving away from the target value, the multiplication of the deviation and the slope has a positive sign. can be greatly suppressed.
Also, during the period when the output changes toward the target value, the sign is negative, so setting the gain adjustment value to a constant to suppress the gain causes undershoot and overshoot due to overcompensation. can be prevented.

According to the drive control device for a power conversion device of the present invention, overshoot and undershoot can be suppressed and quickly converged, so that they can be suppressed more effectively.

BRIEF DESCRIPTION OF THE DRAWINGS It is a figure for demonstrating the structure of the power converter device which concerns on embodiment of this invention. 2 is a diagram for explaining the configuration of the drive control device shown in FIG. 1; FIG. 3 is a diagram for explaining the configuration of a gain calculation section of the drive control device shown in FIG. 2; FIG. 3 is a flowchart for explaining the operation of the drive control device shown in FIG. 2; FIG. 4 is a diagram for explaining that voltage thresholds are set in the positive direction and the negative direction from the target voltage; FIG. 10 is a diagram for explaining switching of gain adjustment values depending on overshoot and rise or fall, and undershoot fall or rise; FIG. 10 is a waveform diagram showing the results of the first simulation, and is a waveform diagram obtained by simulating transient characteristics when gain adjustment is not performed. As a second simulation, it is a waveform diagram showing the result of simulating the case where the first gain is adjusted with respect to the deviation of the output voltage, (A) is a waveform diagram when K _error is set to 1, (B) is a waveform diagram when FIG. 4 is a waveform diagram when K _error is 10; As a second simulation, it is a waveform diagram showing the result of simulating the case where the first gain is adjusted with respect to the deviation of the output voltage, (A) is a waveform diagram when K _error is 20, (B) is a waveform diagram when FIG. 4 is a waveform diagram when K _error is 30; As a third simulation, it is a waveform diagram showing the result of simulating the case where the second gain is adjusted with respect to the slope of the output voltage, (A) is a waveform diagram when K _dev is set to 1, (B) is a waveform diagram when FIG. 4 is a waveform diagram when K _dev is 10; As a third simulation, it is a waveform diagram showing the result of simulating the case where the second gain is adjusted with respect to the slope of the output voltage, (A) is a waveform diagram when K _dev is 20, (B) is a waveform diagram when FIG. 4 is a waveform diagram when _Kdev is 40; As a fourth simulation, it is a waveform diagram showing the result of simulating the case where the deviation and the slope of the output voltage are adjusted by combining the first gain and the second gain, where K _error is 10 and K _dev is 20. It is a waveform diagram when .

(Embodiment)
A power converter according to an embodiment of the present invention will be described with reference to the drawings.
The power conversion device 1 shown in FIG. 1 includes a DC-DC converter section 2, a drive section 3, and a drive control device 4.

The DC-DC converter unit 2 is a voltage conversion device that transforms and supplies a DC voltage, and is a step-down converter in this embodiment. The DC-DC converter section 2 has input terminals T11 and T12 connected to a power line L1 and a ground line L2 from a DC power supply B, and a load R connected to output terminals T21 and T22.
The DC-DC converter section 2 includes a switching element Tr, a reactor L, a flywheel diode D, and a capacitor C.

The switching element Tr is a transistor that passes or blocks current to the load R. In this embodiment, the switching element Tr is an n-type FET.
The switching element Tr has a drain connected to the power supply line L<b>1 and also connected to the drive unit 3 .

Diode D is connected between power supply line L1 and ground line L2.
The reactor L is inserted in series with the power line L1. One end of the reactor L is connected to the source of the switching element Tr and to the cathode of the diode D. The other end of reactor L is connected to capacitor C and load R.
The capacitor C is connected between the power line L1 and the ground line L2.

The drive unit 3 drives a signal for instructing the switching element Tr to turn on/off based on the signal S _PWM for PWM control from the drive control device 4 .

As shown in FIG. 2 , the drive control device 4 includes a preamplifier 41 , an AD converter 42 , a gain calculator 43 , a PID controller 44 and a PWM signal generator 45 .
The pre-amplifier 41 amplifies the output voltage e _o (load voltage) of the DC-DC converter 2 and cuts off high frequency components with a low-pass filter so as to satisfy the sampling theorem.
The AD converter section 42 converts an analog signal (analog value) into a digital signal (digital value). In the present embodiment, the AD converter section 42 converts, for example, a 12-bit digital value.

The gain calculator 43 adds the absolute value of the deviation between the target voltage Nr and the output voltage _eo and the absolute value of the change in the output voltage _eo , and outputs the result as a gain adjustment value.
The PID control unit 44 functions as a feedback control unit that performs gain control to correct the deviation between the output to the load R (output voltage _eo ) and the target value (target voltage Nr) based on the gain adjustment value. .
The PWM signal generation unit 45 outputs a signal S _PWM for performing gain control by PWM control based on the switching signal N _Ton from the PID control unit 44 to the drive unit 3 .

Here, the gain calculator 43 will be described in detail with reference to FIG.
The gain computing unit 43 shown in FIG _. A second calculation unit 432 for calculating the absolute value of the slope of (output voltage e _o ), an addition unit 433 , and a gain suppression unit 434 are provided.

The first calculator 431 includes a deviation calculator 43a, a first absolute value calculator 43b, and a first gain calculator 43c.

The deviation calculator 43a receives the output voltage e ₀ [n] (digital value) from the AD converter 42, obtains the deviation from the target voltage Nr, and outputs the deviation N _error .
The first absolute value calculator 43b calculates the absolute value |N _error | of the deviation N _error from the deviation calculator 43a.
The first gain calculator 43c calculates the first gain K P1 by adding the bias value K _C1 to the output _| N _error | from the first absolute value calculator 43 b multiplied by the constant K _error .

The second computing section 432 includes a buffer section 43d, an inclination computing section 43e, a second absolute value computing section 43f, and a second gain computing section 43g.
The buffer unit 43d stores the output voltage e ₀ [n] and outputs the previous output voltage e ₀ [n−1].
The gradient calculator 43e obtains the difference between the output voltage e _o [n] and the previous output voltage e _o [n−1], and outputs the gradient N _dev .
The second absolute value calculator 43f calculates the absolute value |N _dev | of the slope N _dev from the slope calculator 43e.
The second gain calculator 43g multiplies the output |N _dev | from the second absolute value calculator 43f by the exponent M and the constant K _dev , and adds the bias value K _C2 to the result. 2 Gain K _P2 is calculated. In this embodiment, the absolute value of N _dev (|N _dev |) is squared.

The adder 433 adds the first gain K _P1 from the first gain calculator 43c, the second gain K _P2 from the second gain calculator 43g, and the bias value K _C to obtain the gain adjustment value K _P0 Calculate
The gain suppression unit 434 compares the absolute _value of the deviation |N _error | with the absolute value of the threshold voltage value |V _th | Output.

Here, the voltage threshold V _th can be, for example, 1% of the target voltage Nr, but can be determined as appropriate according to the voltage accuracy required by the load R.
The voltage threshold V _th can be set to a second value smaller than the first value |V _th | when |N _error | increases and becomes equal to or greater than the first value |V _th |. Further, when |N _error | decreases and becomes less than the third value |V _th |, the third value |V _th | can be increased to a fourth value. As for the first to fourth values, the first value and the fourth value can be the same value, and the second value and the third value can be the same value.

By changing the value of │V _th │ in accordance with the increase or decrease of │N _error │ in this way, it is possible to provide the gain suppression unit 434 with a hysteresis characteristic, and │N _error │ is close to │V _th │ It is possible to prevent the gain adjustment value K _P from oscillating when it fluctuates.

The operation of the power converter 1 according to the embodiment of the present invention configured as described above will be described according to the flow of the flowchart shown in FIG.
First, when the pre-amplifier section 41 shown in FIG. 2 detects the output voltage e _O to the load R, it amplifies it and outputs it to the AD converter section 42 (step S10).
The AD converter section 42 shown in FIGS. 2 and 3 converts the output voltage e _O amplified by the pre-amplification section 41 into a digital value e _O [n], and the gain calculation section 43 and the PID control section 44.

First, the deviation calculator 43a shown in FIG. 3 subtracts the output voltage e ₀ [n] from the target voltage Nr to calculate the deviation N _error . Further, the slope calculator 43e reads the previous output voltage e ₀ [n−1] from the buffer 43d and calculates the slope N _dev which is the amount of change from the difference from the output voltage e ₀ [n]. (Step S20).
Next, the first absolute value calculator 43b calculates the absolute value |N _error | of the deviation N _error .
Also, the second absolute value calculator 43f calculates the absolute value |N _dev | of N _dev (step S30).

Next, the gain suppression unit 434 determines whether or not |N _error |, which is the absolute value of the deviation, is greater than or equal to the absolute value |V _th | of the predetermined voltage threshold (step S40).

When |N _error | is less than the absolute value |V _th | of the predetermined voltage threshold, the gain suppression unit 434 sets the constant K _pmin for suppressing the gain as the gain adjustment value K _P (step S50). The constant K _pmin can be 1, for example.

As shown in FIGS. 2 and 3, the PID control unit 44 performs PID control (P control) according to K _P (Nr-e _O [n]) based on the gain adjustment value K _P which is a proportional gain, and the deviation A switching signal N _Ton for correcting is output (step S60).

On the other hand, when _it is determined in step S40 that the absolute value of the deviation |N _error | is equal to or greater than the absolute value of the voltage threshold |V _th | It is determined whether _error is less than 0 (step S70).
When N _dev ×N _error is equal to or greater than 0, the gain suppressing unit 434 proceeds to step S50, where the constant K _pmin is a constant smaller than the gain adjustment value K _P0 and for suppressing the gain. is the gain adjustment value K _P .

When it is determined in step S70 that N _dev ×N _error is less than 0, the first gain calculator 43c calculates the first gain K _P1 , and the second gain calculator 43g calculates the second gain K _P2 is calculated (step S80).
Specifically, the first gain calculator 43c calculates the first gain K _P1 by multiplying the absolute value |N _error | of the deviation N _error by the constant K _error and adding the bias value K _C1 .
Further, the second gain calculator 43g calculates the second gain K _P2 by exponentiating the absolute value |N _dev | of the slope N _dev , multiplying it by a constant K _dev , and adding the bias value K _C2 .

When the first gain K _P1 is calculated and the second gain K _P2 is calculated, the adding section 433 adds the first gain K _P1 , the second gain K _P2 , and the bias value K _C to obtain a gain An adjustment value K _P0 is output (step S90).

Then, the gain suppression unit 434 outputs the gain adjustment value K _P0 as the gain adjustment value K _P to the PID control unit 44, and proceeds to step S60 (step S100).

Then, the PWM signal generation unit 45 outputs a signal S _PWM for PWM control to the drive unit 3 based on the switching signal N _Ton . The drive unit 3 amplifies the signal S _PWM and turns on or off the switching element Tr to pass or cut off the current to the load R.

Here, gain suppression by the gain suppression unit 434 will be described in detail with reference to the drawings.
First, the switching of the gain adjustment value _Kp depending on whether the output voltage e _O is in a transient state will be described.
As shown in FIG. 5, in order to determine whether or not the output voltage _eO is in a transient state, the voltage threshold is set with a width of _Vth in the positive and negative directions from the target voltage _Eo ^* . .
As shown in FIG. 4, in step S40, it is determined whether |N _error |, which is the absolute value of the deviation, is greater than or equal to |V _th |, the absolute value of the predetermined voltage threshold.
Then, if |N _error | is less than |V _th |, the gain suppression unit 434 sets the constant K _pmin as the gain adjustment value K _P in step S50.
is greater than or equal to |V _th |, the gain suppression unit 434 _sets K _P0 as the gain adjustment value K _P in step S100, depending on the signs of N _dev and N _error .

Therefore, when the output voltage e _O exceeds the voltage threshold V _{th ,} it is regarded as a transient _state , and the system may become unstable. can do.
In a steady state where the output voltage e _O is not in a transient state, adjustment with a small gain (K _pmin →K _P ) can suppress adverse effects on convergence due to adjustment with a large gain, and the output smoothing capacitor can be reduced. Since the capacitance can be small, miniaturization can be achieved.
In addition, when the output smoothing capacitor is small, the frequency of the transient oscillation becomes high and the time constant becomes small, so that the convergence can be made quickly.

Next, the switching of the gain adjustment value _Kp depending on the overshoot and rise or fall, and the fall or rise of undershoot will be described.
As shown in FIG. 6, during the T1 period in which the output voltage e _o changes away from the target voltage E _o ^* in the negative direction due to undershoot, the deviation N _error has a negative sign and the slope N _dev minus sign.
During the T2 period when the voltage changes from the T1 period toward the target voltage E _o ^* , the deviation N _error has a negative sign and the slope N _dev has a positive sign.
In the T3 period when the voltage exceeds the target voltage E _o ^* from the T2 period and moves away in the positive direction, the deviation N _error has a positive sign and the slope N _dev has a negative sign.
During the T4 period when the voltage changes from the T3 period toward the target voltage E _o ^* , the deviation N _error has a positive sign and the slope N _dev has a negative sign.

Therefore, in the period (T1 period, T3 period) in which the output voltage e ₀ is changing away from the target voltage E ₀ ^* , the multiplication of the deviation N _error and the slope N _dev has a positive sign.
Therefore, by setting the gain adjustment value K _P0 to the gain adjustment value K _P in step S100, it is possible to greatly suppress the fall of undershoot and the rise of overshoot.
Conversely, in the period (T2 period, T4 period) in which the voltage changes toward the target voltage E _o ^* , the multiplication of the deviation N _error and the slope N _dev has a negative sign.
Therefore, by setting the gain adjustment value K _P to the constant K _pmin in step S60, the value can be sufficiently smaller than K _P0 , thereby preventing undershoot and overshoot due to overcompensation.

(Implementation of simulation)
Transient characteristics such as overshoot and undershoot are confirmed by simulation for the power converters shown in FIGS. 1 to 3 .
In addition, the reactor L of the DC-DC converter section 2 was set to 189 μH, the capacitor C to 1000 μF, and the step change of the load R from 25Ω to 5Ω.
Further, as the gains of the PID control, gain K _I =0.01 for I control and gain K _D =1 for D control. Further, the simulation is performed by setting K _C1 =K _C2 =1 and M=2. Note that these parameters can be determined as appropriate in an actual circuit according to the load. For example, K _C1 and K _C2 may be 0 if K _{P1 or} K _P2 are not 0.

(First simulation)
First, as a first simulation, the transient characteristics were simulated when the gain was not adjusted.
The gain of PID control is K _P =1 because no gain adjustment is performed. The results are shown in FIG.
For the waveforms shown in FIG. 7, the e _O undershoot and convergence time were about 5% and about 4.5 ms, respectively, and the i _L overshoot was 60%.

(Second simulation)
Next, as a second simulation, transient characteristics when the gain is adjusted according to K _P1 =K _error |N _error |+K _C1 calculated by the first gain calculation section 43c are simulated. Simulation results are shown in FIGS. 8 and 9. FIG.
In the waveforms shown in FIGS. 8 and 9, the response changes to an oscillatory response as a whole, and the coefficient K _error of the absolute value of the deviation is 1 (see FIG. 8 (A)) or 10 (see FIG. 8 (B) ), the undershoot of e ₀ is suppressed and the convergence speeds up. However, the overshoot of i _L increases accordingly.

Also, looking at the change in K _P , it can be seen that the gain is adjusted according to the deviation of e ₀ . Accordingly, the change in N _Ton also rises sharply compared to when the gain is not adjusted. When K _error is 20 (see FIG. 9(A)) or 30 (see FIG. 9(B)), the K _error is too large, and the stability of the system gradually deteriorates, delaying convergence, or convergence in the first place. sometimes they don't.
In this second simulation, the best transient characteristics were obtained when K _error was 10 when compared with the e _O waveform, and the e _O undershoot and convergence time were about 1% and about 1 ms, respectively. .

(Third simulation)
Next, as a third simulation, transient characteristics were simulated when the gain was adjusted according to K _P2 =K _dev |N _dev | ² +K _C2 calculated by the second gain calculation section 43g. Simulation results are shown in FIGS. 10 and 11. FIG.
As shown in FIGS. 10 and 11, there was a tendency for the waveform oscillation to be suppressed as a whole, and the convergence of e ₀ became moderate. However, if K _dev is sufficiently large, a high-speed response can be obtained, but the gain changes greatly with a slight inclination of e _O in the state where e _O is almost converged, so oscillation remains. I know you are.

In addition, since the slope of e ₀ is steep immediately after entering the transient state, K _P becomes considerably large, and N _Ton changes sharply accordingly. As a result, the undershoot of e _O is suppressed, but the overshoot of i _L increases accordingly, and a steep peak current appears. After that, the slope becomes gentle until e ₀ converges, so that N _Ton does not change as much as in the initial stage of the transient state, and improvement in response cannot be expected so much. From the point of view of the initial improvement in the transient state, when _Kdev is 20 (see FIG. 11A), it is possible to suppress the undershoot of _eO and avoid the overshoot of _iL . there is

(Fourth simulation)
Finally, as a fourth simulation, adjustment of K _P1 by the deviation of e ₀ in the second simulation (see FIGS. 8 and 9) and adjustment of K _P2 by the slope of e ₀ in the third simulation (see FIG. 10 and FIG. 11) were combined for simulation.

Because of the combination of deviation and slope, the gain adjustment formulas are K _P0 =K _P1 +K _P2 +K _C, K _P1 =K _error |N _error |,K _P2 =K _dev |N _dev | ^M +K _C. be.
In this way _, K _{P1 and} K _P2 are added to determine the final K _P0 value (K _P value). The constant K _C is set to 1 so that is 1.
Simulation results are shown in FIG. FIG. 12 shows transient characteristics when K _error =10 and K _dev =20.

First, in the second simulation, when K _P is adjusted for the deviation of e _O , as shown in FIGS. 8 and 9, there is a large I know it's making an impact.
In addition, the third simulation, in which K _P is adjusted with respect to the slope of e _O , has a large effect on undershoot or overshoot, as shown in FIGS. 10 and 11. I understand.

Therefore, when K _P is adjusted with respect to the deviation and slope of e ₀ , as can _be seen from the waveform of the transient characteristics shown in FIG. After that, the adjustment due to the deviation of e ₀ becomes dominant.
At this time, since the second gain calculator 43g shown in FIG. 3 raises |N _dev | to the power of |Ndev| can be enhanced.
As a result, the undershoot of e ₀ is suppressed, and although the response is oscillating, it can be quickly converged. The undershoot and convergence times of eo were about 1% and about 1 ms, respectively, and the overshoot of i _L was 80%.
Such good results were obtained in the fourth simulation, and it can be said that combining the deviation and the slope as a gain adjustment to make it a voltage function is very effective in improving transient characteristics.

In the present embodiment, a DC-DC converter has been described as an example of the power converter 1, but an AC-DC converter or a DC-AC inverter may also be used.
The power conversion device 1 performs PWM control by the signal S _PWM from the PWM signal generation unit 45, but may be controlled by a series method.
Although the PID control unit 44 that performs PID control is used as a feedback control unit, it may be P control (proportional control) only, or P control may be combined with either I control (integral control) or D control (differential control). You can
Further, the PID control section 44 may employ a digital filter as a feedback control section.
Furthermore, in the present embodiment, the gain adjustment value is calculated based on the output voltage from the DC-DC converter section 2, but the deviation and slope may be obtained based on the output current, power, and impedance. . In this case, the target values are target current, target power, and target impedance.

INDUSTRIAL APPLICABILITY The drive control device for a power conversion device of the present invention is suitable for devices that supply power to various loads ranging from direct current, alternating current, small current to large current.

1 power conversion device 2 DC-DC converter section 3 drive section 4 drive control device 41 pre-amplification section 42 AD converter section 43 gain calculation section 431 first calculation section 432 second calculation section 433 addition section 434 gain suppression section 43a deviation calculation Section 43b First Absolute Value Calculator 43c First Gain Calculator 43d Buffer Section 43e Gradient Calculator 43f Second Absolute Value Calculator 43g Second Gain Calculator 44 PID Controller 45 PWM Signal Generator B DC Power Supply Tr Switching Element L Reactor D Diode C Capacitor R Load L1 Power supply line L2 Ground line T11, T12 Input terminals T21, T22 Output terminals

Claims (6)

In a drive control device for a power conversion device that gain-controls current to a load,
a first calculation unit that calculates a deviation between the output to the load and a target value as a first gain;
a second calculation unit that calculates a second gain by exponentiating the slope of the output to the load;
an addition unit that adds the first gain and the second gain and outputs a gain adjustment value;
A drive control device for a power converter, comprising: a feedback control unit that performs the gain control for correcting a deviation between an output to the load and a target value based on the gain adjustment value. 2. The power conversion apparatus according to claim 1, wherein the feedback control unit is a proportional control using the gain adjustment value as a proportional gain, or a combination of the proportional control and either one or both of the integral control and the differential control. drive controller. The first calculation unit includes: a deviation calculation unit that calculates a deviation between the output to the load and a target value; a first absolute value calculation unit that calculates an absolute value of the deviation from the deviation calculation unit; 3. A drive control device for a power conversion device according to claim 1, further comprising a first gain calculation section for calculating said first gain by adding a bias value to an output from said value calculation section multiplied by a constant. The second calculation unit includes a buffer unit that stores the output and outputs the previous output, a slope calculation unit that calculates a slope by obtaining a difference between the output and the previous output, and a slope from the slope calculation unit. and a bias value is added to the result obtained by multiplying the output from the second absolute value computing unit to an exponentiation by a constant to calculate the second gain. 4. The drive control device for a power conversion device according to claim 1, further comprising a 2-gain computing section. If the gain adjustment value from the addition unit is equal to or greater than a predetermined threshold value, the gain adjustment value is directly output to the feedback control unit, and if the gain adjustment value is less than the threshold value, the gain adjustment value is used to suppress the gain. 5. The drive control device for a power conversion device according to claim 1, further comprising a gain suppressing section that outputs a constant of to the feedback control section. If the sign obtained by multiplying the deviation by the first calculation unit and the slope by the second calculation unit is a plus sign, the gain adjustment value is directly output to the feedback control unit, and if the sign is a minus sign. 6. The drive control device for a power conversion device according to claim 1, further comprising a gain suppression unit that outputs a constant for suppressing the gain to the feedback control unit as the gain adjustment value.

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