JP6616078B2 - Method and apparatus for transmitting control information in wireless communication system - Google Patents

Description

  The present invention relates to a wireless communication system, and more particularly to a method and apparatus for transmitting control information. A wireless communication system may support carrier aggregation (CA).

  Wireless communication systems are widely deployed to provide various communication services such as voice and data. Generally, a wireless communication system is a multiple access system that can support communication with multiple users by sharing available system resources (bandwidth, transmission power, etc.). Examples of multiple access systems include code division multiple access (CDMA) systems, frequency division multiple access (FDMA) systems, time division multiple access (TDMA) systems, orthogonal frequency division multiple access (OFDMA) systems, single carrier frequency division There are multiple access (SC-FDMA) systems.

  An object of the present invention is to provide a method and an apparatus for efficiently transmitting control information in a wireless communication system. Another object of the present invention is to provide a channel format, signal processing, and an apparatus therefor for efficiently transmitting control information. It is still another object of the present invention to provide a method and apparatus for efficiently allocating resources for transmitting control information.

  The technical problem to be achieved by the present invention is not limited to the technical problem mentioned above, and other technical problems that are not mentioned are described below. It will be clear to those with ordinary knowledge in this field.

  In one aspect of the present invention, a method for a communication apparatus to transmit a physical uplink control channel (PUCCH) signal in a wireless communication system includes setting transmission power for a PUCCH signal, wherein the PUCCH signal is a schedule request (SR The PUCCH signal includes one or more hybrid automatic repeat request acknowledgment (HARQ-ACK) bits and SR bits, and the transmission power for the PUCCH is as follows: A method is provided that is determined by:

ここで、ｎ_ＨＡＲＱはＨＡＲＱ−ＡＣＫの情報ビット数に対応し、Ｎは正の整数を表し、ｎ_ＳＲはサブフレームにアップリンク共有チャネル（ＵＬ−ＳＣＨ）のための伝送ブロックがないとき１であり、ＵＬ−ＳＣＨのための伝送ブロックがあるとき０である。

Here, n _HARQ corresponds to the number of information bits of HARQ-ACK, N represents a positive integer, and n _SR is 1 when there is no transport block for the uplink shared channel (UL-SCH) in the subframe. Yes, 0 when there is a transport block for UL-SCH.

  As another aspect of the present invention, in a communication device configured to transmit a PUCCH signal in a wireless communication system, a processor configured to set a radio frequency (RF) unit and transmission power for the PUCCH signal When the PUCCH signal is transmitted in a subframe configured for SR, the PUCCH signal includes one or more HARQ-ACK bits and SR bits, and the transmission power for the PUCCH is expressed by the following equation: A communication device is provided, as determined by

ここで、ｎ_ＨＡＲＱはＨＡＲＱ−ＡＣＫの情報ビット数に対応し、Ｎは正の整数を表し、ｎ_ＳＲはサブフレームにアップリンク共有チャネル（ＵＬ−ＳＣＨ）のための伝送ブロックがないとき１であり、ＵＬ−ＳＣＨのための伝送ブロックがあるとき０である。

Here, n _HARQ corresponds to the number of information bits of HARQ-ACK, N represents a positive integer, and n _SR is 1 when there is no transport block for the uplink shared channel (UL-SCH) in the subframe. Yes, 0 when there is a transport block for UL-SCH.

ここで、Ｐ_{ＰＵＣＣＨ}（ｉ）はＰＵＣＣＨのための送信電力を表し、
Ｐ_{ＣＭＡＸ，ｃ}（ｉ）はサービス提供セルｃのために設定された最大送信電力を表し、
Ｐ_{０ ＰＵＣＣＨ}は上位層によって設定されたパラメータを表し、
ＰＬ_Ｃはサービス提供セルｃのダウンリンク経路損失推定値を表し、
Δ_{Ｆ ＰＵＣＣＨ}（Ｆ）はＰＵＣＣＨフォーマットに対応する値を表し、
Δ_ＴｘＤ（Ｆ’）は上位層によって設定された値又は０を表し、
ｇ（ｉ）は現在のＰＵＣＣＨ電力制御調整状態を表す。 Preferably, the transmission power for the PUCCH signal in subframe i is determined by the following equation:

Where P _PUCCH (i) represents the transmit power for PUCCH,
P _{CMAX, c} (i) represents the maximum transmit power set for the serving cell c,
P _{0 PUCCH} represents a parameter set by an upper layer,
PL _C denotes a downlink path loss estimate serving cell c,
Δ _{F PUCCH} (F) represents a value corresponding to the PUCCH format,
Δ _TxD (F ′) represents a value set by the upper layer or 0,
g (i) represents the current PUCCH power control adjustment state.

  Preferably, if there is no transport block for UL-SCH in the subframe, the SR bit represents actual SR information, and if there is a transport block for UL-SCH in the subframe, the SR bit contains dummy information. Represent. The dummy information can have an arbitrary specific value set in advance. For example, when the SR bit represents dummy information, the SR bit is set to a predetermined value of 0 or 1, preferably 0.

  Preferably, an SR bit is added to the end of the one or more HARQ-ACK bits.

  Preferably, the SR bit is set to 1 for positive SR, and the SR bit is set to 0 for negative SR.

  Preferably, one or more HARQ-ACK bits and SR bits are joint-coded.

  Preferably, the communication device is set to the PUCCH and physical uplink shared channel (PUSCH) simultaneous transmission mode.

  Preferably N is 2 or 3.

  Preferably, one or more HARQ-ACK bits and SR bits are jointly encoded.

  Preferably, the PUCCH signal is a PUCCH format 3 signal.

  According to the present invention, control information can be efficiently transmitted in a wireless communication system. Further, it is possible to provide a channel format and a signal processing method for efficiently transmitting control information. Also, resources for transmitting control information can be efficiently allocated.

  The effects obtained by the present invention are not limited to the effects mentioned above, and other effects that are not mentioned will be apparent to those having ordinary knowledge in the technical field to which the present invention belongs from the following description. Will be understood.

  The accompanying drawings, which are included as part of the detailed description to assist in understanding the present invention, provide examples of the present invention and together with the detailed description, explain the technical idea of the present invention.

It is a figure which illustrates the general signal transmission method using the physical channel used for 3GPP LTE system which is an example of a radio | wireless communications system, and these channels. It is a figure which illustrates the structure of a radio frame. It is a figure which illustrates an uplink signal processing procedure. It is a figure which illustrates a downlink signal processing procedure. It is a figure which illustrates SC-FDMA system and OFDMA system. FIG. 6 is a diagram illustrating a signal mapping scheme on a frequency domain for satisfying a single carrier characteristic. FIG. 6 is a diagram illustrating a signal processing procedure in which DFT process output samples are mapped to a single carrier in cluster SC-FDMA. FIG. 11 is a diagram illustrating a signal processing procedure in which DFT process output samples are mapped to multiple carriers in cluster SC-FDMA. FIG. 11 is a diagram illustrating a signal processing procedure in which DFT process output samples are mapped to multiple carriers in cluster SC-FDMA. It is a figure which illustrates the signal processing procedure in segment SC-FDMA. It is a figure which illustrates the structure of an uplink sub-frame. It is a figure which illustrates the signal processing procedure for transmitting a reference signal (RS) by an uplink. FIG. 3 is a diagram illustrating a demodulation reference signal (DMRS) structure for PUSCH. FIG. 3 is a diagram illustrating a demodulation reference signal (DMRS) structure for PUSCH. It is a figure which illustrates the slot level structure of PUCCH format 1a and 1b. It is a figure which illustrates the slot level structure of PUCCH format 1a and 1b. It is a figure which illustrates the slot level structure of PUCCH format 2 / 2a / 2b. It is a figure which illustrates the slot level structure of PUCCH format 2 / 2a / 2b. It is a figure which illustrates ACK / NACK channelization with respect to PUCCH formats 1a and 1b. It is a figure which illustrates channelization with respect to the mixed structure of PUCCH format 1 / 1a / 1b and format 2 / 2a / 2b in the same PRB. It is a figure which illustrates PRB allocation for PUCCH transmission. It is a figure which illustrates the concept which manages a downlink component carrier wave in a base station. It is a figure which illustrates the concept which manages an uplink component carrier wave in a terminal. It is a figure which illustrates the concept that one MAC manages multiple carriers in a base station. It is a figure which illustrates the concept that one MAC manages multiple carriers in a terminal. It is a figure which illustrates the concept that one MAC manages multiple carriers in a base station. It is a figure which illustrates the concept that several MAC manages multiple carriers in a terminal. It is a figure which illustrates the concept that several MAC manages several carrier waves in a base station. It is a figure which illustrates the concept that one or more MAC manages several carrier waves from a receiving viewpoint of a terminal. It is a figure which illustrates the asymmetrical carrier aggregation with which several DL CC and one UL CC were combined. It is a figure which illustrates the structure of PUCCH format 3, and a signal processing procedure. It is a figure which illustrates the structure of PUCCH format 3, and a signal processing procedure. It is a figure which illustrates the structure of PUCCH format 3, and a signal processing procedure. It is a figure which illustrates the structure of PUCCH format 3, and a signal processing procedure. It is a figure which illustrates the structure of PUCCH format 3, and a signal processing procedure. It is a figure which illustrates the structure of PUCCH format 3, and a signal processing procedure. FIG. 6 is a diagram illustrating a UL transmission process based on existing 3GPP Rel-8 / 9. FIG. 6 is a diagram illustrating a process of transmitting control information through a PUCCH according to an embodiment of the present invention. It is a figure which shows the base station and terminal which can be applied to this invention.

  The following techniques can be used for various wireless access systems such as CDMA, FDMA, TDMA, OFDMA, SC-FDMA, etc. CDMA can be implemented by a radio technology such as a universal terrestrial radio access (UTRA) or CDMA2000. TDMA can be realized by a radio technology such as Global System for Mobile Communications (GSM) / General Packet Radio Service (GPRS) / Enhanced Data Rate for Evolution (EDGE). OFDMA can be realized by a radio technology such as IEEE 802.11 (Wi-Fi), IEEE 802.16 (WiMAX), IEEE 802-20, Evolved UTRA (E-UTRA) and the like. UTRA is part of a general purpose mobile communication system (UMTS). Third Generation Partnership Project (3GPP) Long-term Evolution (LTE) system is part of Evolved UMTS (E-UMTS) using E-UTRA, Advanced LTE (LTE-A) is an advanced version of 3GPP LTE . In order to clarify the explanation, 3GPP LTE / LTE-A will be mainly described, but the technical idea of the present invention is not limited thereto.

  In a wireless communication system, a terminal receives information from a base station through a downlink (DL), and the terminal transmits information to the base station through an uplink (UL). Information transmitted and received by the base station and the terminal includes data and various control information, and various physical channels exist depending on the type / use of information transmitted and received by these.

  FIG. 1 is a diagram for explaining a physical channel used in the 3GPP LTE system and a general signal transmission method using these channels.

  A terminal that is turned on again or has newly entered a cell from a state in which the power is turned off performs an initial cell search operation such as synchronization with the base station in step S101. For this purpose, the terminal receives the primary synchronization channel (P-SCH) and the secondary synchronization channel (S-SCH) from the base station, synchronizes with the base station, and acquires information such as a cell ID. Thereafter, the terminal can receive the physical broadcast channel from the base station and acquire the broadcast information in the cell. Meanwhile, the UE can confirm the downlink channel state by receiving the DL reference signal (DL RS) in the initial cell search stage.

  In step S102, the terminal that has completed the initial cell search receives the physical downlink control channel (PDCCH) and the physical downlink shared channel (PDSCH) corresponding to the physical downlink control channel information, and more specifically, System information can be acquired.

  Thereafter, the terminal may perform a random access procedure as in steps S103 to S106 to establish a connection to the base station. Therefore, the terminal transmits a preamble through the physical random access channel (PRACH) (S103), and can receive a response message to the preamble through the physical downlink control channel and the corresponding physical downlink shared channel ( S104). In the case of contention based random access, collision resolution procedures (Contention Resolution) such as transmission of an additional physical random access channel (S105) and reception of a physical downlink control channel and a corresponding physical downlink shared channel (S106). Procedure) can be performed.

  The terminal that has performed the above procedure thereafter receives the physical downlink control channel / the physical downlink shared channel (S107) and the physical uplink shared channel (PUSCH) / as a general uplink / downlink signal transmission procedure. A physical uplink control channel (PUCCH) can be transmitted (S108). The control information transmitted from the terminal to the base station is collectively referred to as uplink control information (UCI). UCI includes hybrid automatic repeat request acknowledgment / negative acknowledgment (HARQ-ACK / NACK), schedule request (SR), channel quality indicator (CQI), precoding matrix indicator (PMI), rank indicator (RI), etc. Including. In this specification, HARQ ACK / NACK is simply referred to as HARQ-ACK or ACK / NACK (A / N). HARQ-ACK includes at least one of positive ACK (simply ACK), negative ACK (NACK), DTX, and NACK / DTX. UCI is mainly transmitted through PUCCH, but may be transmitted through PUSCH when control information and traffic data are to be transmitted at the same time. Moreover, UCI may be transmitted aperiodically through PUSCH according to the request / instruction of the network.

  FIG. 2 is a diagram illustrating the structure of a radio frame. In the cellular OFDM wireless packet communication system, transmission of uplink / downlink data packets is performed in units of subframes, and one subframe is defined as a certain time interval including a plurality of OFDM symbols. The 3GPP LTE standard supports a type 1 radio frame structure applicable to frequency division duplex communication (FDD) and a type 2 radio frame structure applicable to time division duplex communication (TDD).

  FIG. 2A illustrates the structure of a type 1 radio frame. The downlink radio frame is composed of 10 subframes, and one subframe is composed of 2 slots in the time domain. The time taken to transmit one subframe is called a transmission time interval (TTI). For example, the length of one subframe may be 1 ms, and the length of one slot may be 0.5 ms. One slot includes a plurality of OFDM symbols in the time domain, and includes a plurality of resource blocks (RBs) in the frequency domain. In the 3GPP LTE system, since OFDMA is used in the downlink, an OFDM symbol represents one symbol period. An OFDM symbol may also be referred to as an SC-FDMA symbol or symbol period. A resource block (RB) as a resource allocation unit can include a plurality of consecutive subcarriers in one slot.

  The number of OFDM symbols included in one slot may vary depending on the configuration of the cyclic prefix (CP). The CP includes an extended CP (extended CP) and a regular CP (normal CP). For example, when the OFDM symbol is configured by a regular CP, the number of OFDM symbols included in one slot may be seven. When an OFDM symbol is configured by an extended CP, the length of one OFDM symbol increases, so the number of OFDM symbols included in one slot is smaller than that in the case of a regular CP. In the case of the extended CP, for example, the number of OFDM symbols included in one slot may be six. An extended CP can be used to further reduce intersymbol interference when the channel conditions are not stable, such as when the terminal moves at high speed.

  When regular CP is used, since one slot includes 7 OFDM symbols, one subframe includes 14 OFDM symbols. In this case, a maximum of three OFDM symbols at the head of each subframe can be assigned to the PDCCH, and the remaining OFDM symbols can be assigned to the PDSCH.

  FIG. 2B illustrates the structure of a type 2 radio frame. Type 2 radio frame consists of 2 half frames, each half frame consists of 5 subframes, downlink pilot time slot (DwPTS), protection period (GP), and uplink pilot time slot (UpPTS) One subframe is composed of two slots. DwPTS is used for initial cell search, synchronization or channel estimation at the terminal. UpPTS is used to match channel estimation at the base station with uplink transmission synchronization with the terminal. The protection period is a period for removing interference generated in the uplink due to multipath delay of the downlink signal between the uplink and the downlink.

  The structure of the above radio frame is merely an example, and the number of subframes included in the radio frame, the number of slots included in the subframe, and the number of symbols included in the slots can be variously changed.

  FIG. 3A is a diagram for explaining a signal processing procedure for a terminal to transmit an uplink signal.

  In order to transmit the uplink signal, the terminal can scramble the transmission signal using the terminal specific scramble signal in the scramble module 201. The scrambled signal is input to a modulation mapper 202, and two-phase phase shift keying (BPSK), four-phase phase shift keying (QPSK) or 16-value quadrature amplitude modulation ( 16QAM) / 64-value quadrature amplitude modulation (64QAM) scheme is used to modulate to complex symbols. After the modulated complex symbols are processed by transform precoder 203, they are input to resource element mapper 204, which can map the complex symbols to time frequency resource elements. The signal processed in this way can be transmitted from the antenna to the base station via the SC-FDMA signal generator 250.

  FIG. 3B is a diagram for explaining a signal processing procedure for the base station to transmit a downlink signal.

  In the 3GPP LTE system, the base station may transmit one or more codewords in the downlink. Each codeword may be a complex symbol through scramble module 301 and modulation mapper 302, similar to the uplink of FIG. 3A. The complex symbols can then be mapped to multiple layers by the layer mapper 303 and each layer can be multiplied by a precoding matrix by the precoding module 304 and assigned to each transmit antenna. Each antenna-specific transmission signal processed in this way can be mapped to a time-frequency resource element by the resource element mapper 305, and then transmitted from each antenna via an orthogonal frequency division multiplexing (OFDM) signal generator 306.

  When a terminal transmits a signal on the uplink in a wireless communication system, the peak-to-average power ratio (PAPR) becomes a problem as compared with a case where a base station transmits a signal on the downlink. Therefore, as described in FIG. 3A and FIG. 3B, the SC-FDMA scheme is used for uplink signal transmission, not the OFDMA scheme used for downlink signal transmission.

  FIG. 4 is a diagram for explaining the SC-FDMA scheme and the OFDMA scheme. The 3GPP system employs OFDMA in the downlink and SC-FDMA in the uplink.

  Referring to FIG. 4, a terminal for uplink signal transmission and a base station for downlink signal transmission include a serial-to-parallel converter 401, a subcarrier mapper 403, an M-point IDFT module 404, a parallel-to-serial converter 405, and a CP. It is the same in that an additional module 406 is provided. However, a terminal for transmitting a signal using the SC-FDMA scheme further includes an N-point DFT module 402. The N-point DFT module 402 partially cancels the IDFT processing effect of the M-point IDFT module 404 so that the transmitted signal has a single carrier characteristic.

  FIG. 5 is a diagram for explaining a signal mapping method on the frequency domain for satisfying a single carrier characteristic in the frequency domain. FIG. 5A shows a local map method, and FIG. 5B shows a distributed map method.

  Cluster SC-FDMA, which is a modified form of SC-FDMA, will be described. Cluster SC-FDMA divides the DFT process output samples into subgroups in the subcarrier mapping process and maps them discontinuously in the frequency domain (or subcarrier domain).

  FIG. 6 is a diagram illustrating a signal processing procedure in which DFT process output samples are mapped to a single carrier in cluster SC-FDMA. 7 and 8 are diagrams illustrating a signal processing procedure in which DFT process output samples are mapped to a plurality of carriers in cluster SC-FDMA. FIG. 6 shows an example in which intra-carrier cluster SC-FDMA is applied, and FIGS. 7 and 8 correspond to an example in which inter-carrier cluster SC-FDMA is applied. FIG. 7 shows a case where a signal is generated through a single IFFT block in a situation where component carriers are continuously allocated in the frequency domain and when subcarrier intervals between adjacent component carriers are aligned. An example is shown. FIG. 8 illustrates a case where a signal is generated through a plurality of IFFT blocks in a situation where component carriers are allocated discontinuously in the frequency domain.

  FIG. 9 is a diagram illustrating a signal processing procedure of segment SC-FDMA.

  In segment SC-FDMA, the same number of IFFTs as any number of DFTs are applied and the relationship between DFT and IFFT has a one-to-one relationship. It is an extension of the carrier map configuration and is also expressed as NxSC-FDMA or NxDFT-s-OFDMA. These are collectively referred to as segment SC-FDMA in this specification. Referring to FIG. 9, segment SC-FDMA divides the entire time domain modulation symbols into N (N is an integer greater than 1) groups and relaxes the DFT process on a group basis in order to relax the single carrier characteristic condition. I do.

  FIG. 10 is a diagram illustrating a structure of an uplink subframe.

  Referring to FIG. 10, the uplink subframe includes a plurality of (eg, two) slots. Each slot may have a different number of SC-FDMA symbols depending on the length of the CP. As an example, for a regular CP, a slot can have 7 SC-FDMA symbols. The uplink subframe is classified into a data area and a control area. The data area includes PUSCH and is used for transmitting a data signal such as voice. The control area includes PUCCH and is used for transmitting control information. The PUCCH includes RB pairs (for example, m = 0, 1, 2, 3) (for example, RB pairs at frequency-inverted positions) located at both ends of the data area on the frequency axis, with the slot as a boundary. Hop. Uplink control information (ie, UCI) includes HARQ ACK / NACK, CQI, PMI, RI, and so on.

  FIG. 11 is a diagram for explaining a signal processing procedure for transmitting a reference signal in the uplink. Compared to the case where data is converted to a frequency domain signal through the DFT precoder and then transmitted through IFFT after the frequency map, the RS does not go through the DFT precoder. That is, after the RS sequence is directly generated (S11) in the frequency domain, the RS is transmitted sequentially through the localization map (S12), the IFFT process (S13), and the CP (Cyclic Prefix) addition process (S14).

ここで、Ｍ^ＲＳ _ＳＣ＝ｍＭ^ＲＢ _ＳＣはＲＳシーケンスの長さであり、Ｎ^ＲＢ _ＳＣは副搬送波単位で表したリソースブロックのサイズであり、ｍは１≦ｍ≦Ｎ^{ｍａｘ，ＵＬ} _ＲＢである。Ｎ^{ｍａｘ，ＵＬ} _ＲＢは、最大アップリンク送信帯域を表す。

The RS sequence r ^(α) _{u, v} (n) is defined by the cyclic shift α of the basic sequence and can be expressed as in Equation 1.
(Formula 1)

Here, M ^RS _SC = mM ^RB _SC is the length of the RS sequence, N ^RB _SC is the size of the resource block expressed in units of subcarriers, and m is 1 ≦ m ≦ N ^{max, UL} _RB . N ^{max, UL} _RB represents the maximum uplink transmission band.

The basic sequence bar-r _{u, v} (n) is divided into several groups. uε {0, 1,..., 29} represents a group number, and ν corresponds to the basic sequence number of the group. Each group has one basic sequence (ν = 0) with a length of M ^RS _SC = mM ^RB _SC (1 ≦ m ≦ 5) and a length of M ^RS _SC = mM ^RB _SC (6 ≦ m ≦ N). ^{max, UL} _RB ) containing two basic sequences (ν = 0, 1). Within the corresponding group, the sequence group number u and the corresponding number ν may change with time. Basic sequence bar-ru, ν (0) , ..., the definition of ^{_{bar-r u, ν (M}} RS SC -1) is due to the sequence length ^M _{RS SC.}

A basic sequence having a length of 3N ^RB _SC or more can be defined as follows.

ここで、ｑ番目のルートザドフチュー（Ｚａｄｏｆｆ−Ｃｈｕ）シーケンスは、下記の式３によって定義できる。 For M ^RS _SC ≧ 3N ^RB _SC , the basic sequence bar-r _{u, ν} (0),..., Bar-r _{u, ν} (M ^RS _SC −1) is given by Equation 2 below.
(Formula 2)

Here, the q-th root Zadhoo-Chu sequence can be defined by Equation 3 below.

ここで、ｑは、下記の式４を満たす。
（式４）

ここで、ザドフチューシーケンスの長さＮ^ＲＳ _ＺＣは、最大の素数によって与えられ、よって、Ｎ^ＲＳ _ＺＣ＜Ｍ^ＲＳ _ＳＣを満たす。 (Formula 3)

Here, q satisfies the following Expression 4.
(Formula 4)

Here, the length N ^RS _ZC of the Zadofutu sequence is given by the largest prime number, and therefore satisfies N ^RS _ZC <M ^RS _SC .

ここで、Ｍ^ＲＳ _ＳＣ＝Ｎ^ＲＢ _ＳＣ及びＭ^ＲＳ _ＳＣ＝２Ｎ^ＲＢ _ＳＣに対するφ（ｎ）の値は、下記の表１及び表２でそれぞれ与えられる。 A basic sequence having a length of less than 3N ^RB _SC can be defined as follows: First, the basic sequence is given by Equation 5 for M ^RS _SC = N ^RB _SC and M ^RS _SC = 2N ^RB _SC .
(Formula 5)

Here, the values of φ (n) for M ^RS _SC = N ^RB _SC and M ^RS _SC = 2N ^RB _SC are given in Table 1 and Table 2 below, respectively.

  On the other hand, the RS hop will be described as follows.

ここで、ｍｏｄは、モジュロ演算を表す。 By the sequence shift pattern _{f ss} and group hop pattern _f gh _{(n s),} the sequence group number u in slot _{n s} can be defined as Equation 6 below.
(Formula 6)

Here, mod represents a modulo operation.

  There are 17 distinct hop patterns and 30 distinct sequence shift patterns. The sequence group hop is enabled or disabled by a parameter that activates the group hop provided by the upper layer.

  PUCCH and PUSCH have the same hop pattern, but can have separate sequence shift patterns.

ここで、ｃ（ｉ）は、擬似ランダムシーケンスに該当し、擬似ランダムシーケンス生成器は、各無線フレームの開始において

によって初期化することができる。 Group hop pattern _f gh _{(n s)} is the same for PUSCH and PUCCH, given as equation 7 below.
(Formula 7)

Here, c (i) corresponds to a pseudo-random sequence, and the pseudo-random sequence generator is at the start of each radio frame.

Can be initialized by.

The definition of the sequence shift pattern f _ss differs between PUCCH and PUSCH.

For PUCCH, the sequence shift pattern f ^PUCCH _SS is given by f ^PUCCH _SS = N ^cell _ID mod 30 and for the PUSCH, the sequence shift pattern f ^PUSCH _SS is given by f ^PUSCH _SS = (f ^PUCCH _SS + Δ _ss ) mod 30 It is done. Δ _ss ε {0, 1,..., 29} is set by the upper layer.

  Hereinafter, the sequence hop will be described.

The sequence hop is only applied to reference signals with a length of M ^RS _SC ≧ 6N ^RB _SC .

For a reference signal whose length is M ^RS _SC <6N ^RB _SC , the basic sequence number ν is given as ν = 0 in the basic sequence group.

ここで、ｃ（ｉ）は、擬似ランダムシーケンスに該当し、上位層によって提供されるシーケンスホップを有効（ｅｎａｂｌｅｄ）にするパラメータは、シーケンスホップが可能か否かを決定する。擬似ランダムシーケンス生成器は、無線フレームの開始点において

で初期化することができる。 For a reference signal having a length of M ^RS _SC ≧ 6N ^RB _SC , the basic sequence number ν in the basic sequence group in the slot n _s is given by Equation 8 below.
(Formula 8)

Here, c (i) corresponds to a pseudo-random sequence, and a parameter for enabling a sequence hop provided by an upper layer determines whether a sequence hop is possible. The pseudo-random sequence generator is at the start of the radio frame.

It can be initialized with.

  The reference signal for PUSCH is determined as follows.

と定義される。ｍ及びｎはｍ＝０，１、ｎ＝０，…，Ｍ^ＲＳ _ＳＣ−１を満たし、かつＭ^ＲＳ _ＳＣ＝Ｍ^{ＰＵＳＣＨ} _ＳＣを満たす。 The reference signal sequence r ^PUSCH (•) for ^PUSCH is

Is defined. m and n satisfy m = 0, 1, n = 0,..., M ^RS _SC −1, and M ^RS _SC = M ^PUSCH _SC .

と共にα＝２・ｎ_ｃｓ／１２と与えられる。 In one slot, the cyclic shift is

And α = 2 · n _cs / 12.

のように与えられる。 n _{⁽¹⁾ DMRS} is a value ^broadcast, _{n (2) DMRS} is given by the uplink scheduling _{assignment, n} PRS _{(n s)} is the cell specific cyclic shift value. _{n PRS} (n _s) may vary depending on the slot number ^{n s,}

Is given as follows.

で初期化することができる。 c (i) is a pseudo-random sequence, and c (i) is a cell specific value. The pseudo-random sequence generator is at the start of the radio frame.

It can be initialized with.

Table 3 shows the cyclic shift field and n ⁽²⁾ _DMRS in the downlink control information (DCI) format 0.

  The physical mapping method for uplink RS in PUSCH is as follows.

The sequence is multiplied by an amplitude scaling factor β _PUSCH and mapped to the same set of physical resource blocks (PRBs) used for the corresponding PUSCH in the sequence starting from r ^PUSCH (0). When mapping to a resource element (k, l) in a subframe with l = 3 for a regular CP and l = 2 for an extended CP, the slot number is increased after the order of k is first increased.

In short, a ZC sequence is used with cyclic extension if the length is 3N ^RB _SC or more, and a computer generated sequence is used if the length is less than 3N ^RB _SC . The cyclic shift is determined by a cell specific cyclic shift, a terminal specific cyclic shift, a hop pattern, and the like.

  FIG. 12A is a diagram illustrating a demodulation reference signal (DMRS) structure for PUSCH in the case of regular CP, and FIG. 12B is a diagram illustrating a DMRS structure for PUSCH in the case of extended CP. In FIG. 12A, DMRS is transmitted through the fourth and eleventh SC-FDMA symbols, and in FIG. 12B, DMRS is transmitted through the third and ninth SC-FDMA symbols.

  FIG. 13 to FIG. 16 are examples showing the slot level structure of the PUCCH format. The PUCCH includes the following format for transmitting control information.

    (1) Format 1: Used for on / off keying (OOK) modulation and schedule request (SR)

(2) Format 1a and Format 1b: Used for ACK / NACK transmission 1) Format 1a: BPSK ACK / NACK for one codeword
2) Format 1b: QPSK ACK / NACK for two codewords

(3) Format 2: Used for QPSK modulation and CQI transmission (4) Format 2a and Format 2b: Used for simultaneous transmission of CQI and ACK / NACK

  Table 4 shows the modulation scheme according to the PUCCH format and the number of bits per subframe. Table 5 shows the number of RSs per slot according to the PUCCH format. Table 6 shows the SC-FDMA symbol positions of the RS according to the PUCCH format. In Table 4, PUCCH formats 2a and 2b correspond to regular CPs.

  FIG. 13 shows PUCCH formats 1a and 1b in the case of regular CP. FIG. 14 shows PUCCH formats 1a and 1b in the case of extended CP. In the PUCCH formats 1a and 1b, control information having the same content is repeated for each slot in a subframe. The ACK / NACK signal is received from each terminal by a separate cyclic shift (CS) (frequency domain code) of a computer generated constant amplitude zero autocorrelation (CG-CAZAC) sequence and an orthogonal cover code (OC or OCC) (time domain spreading). Code) and is transmitted through a separate resource. The OC includes, for example, a Walsh / DFT orthogonal code. If the number of CSs is 6 and the number of OCs is 3, a total of 18 terminals can be multiplexed in the same physical resource block (PRB) based on a single antenna. The orthogonal sequences w0, w1, w2, w3 may be applied in any time domain (after FFT modulation) or in any frequency domain (before FFT modulation).

  For SR and persistent schedule, ACK / NACK resources composed of CS, OC and PRB can be given to the terminal through Radio Resource Control (RRC). For dynamic ACK / NACK and non-persistent schedules, ACK / NACK resources can be implicitly provided to the terminal by the minimum control channel element (CCE) index of the PDCCH corresponding to the PDSCH.

  FIG. 15 shows PUCCH format 2 / 2a / 2b in the case of regular CP. FIG. 16 shows PUCCH format 2 / 2a / 2b in the case of extended CP. Referring to FIGS. 15 and 16, in the case of regular CP, one subframe includes 10 QPSK data symbols in addition to RS symbols. Each QPSK symbol is spread in the frequency domain by CS and then mapped to the corresponding SC-FDMA symbol. SC-FDMA symbol level CS hops can be applied to randomize inter-cell interference. RSs can be multiplexed by CDM using cyclic shifts. For example, if the number of available CSs is 12 or 6, 12 or 6 terminals can be multiplexed in the same PRB, respectively. In short, in the PUCCH formats 1 / 1a / 1b and 2 / 2a / 2b, a plurality of terminals can be multiplexed by CS + OC + PRB and CS + PRB, respectively.

The length 4 and length 3 orthogonal sequences (OC) for PUCCH format 1 / 1a / 1b are as shown in Table 7 and Table 8 below.

In PUCCH format 1a / 1b, the orthogonal sequence (OC) for RS is as shown in Table 9 below.

FIG. 17 is a diagram for explaining ACK / NACK channelization for PUCCH formats 1a and 1b. FIG. 17 corresponds to the case of Δ ^PUCCH _shift = 2.

  FIG. 18 is a diagram illustrating channelization for a mixed structure of PUCCH format 1a / 1b and format 2 / 2a / 2b in the same PRB.

Cyclic shift (CS) hops and orthogonal cover (OC) remapping are applicable as follows.
(1) Symbol-based cell-specific CS hop for randomization of inter-cell interference (2) Slot level CS / OC remapping 1) For inter-cell interference randomization 2) ACK / NACK channel Slot-based connection for maps with resource (k)

On the other hand, the resource (n _r ) for PUCCH format 1a / 1b includes the following combinations.
(1) CS (same as DFT orthogonal code at symbol level) (n _cs )
(2) OC (orthogonal cover at slot level) ( _noc )
(3) Frequency RB (Resource Block) (n _rb )

If the indexes representing CS, OC, and RB are n _cs , n _oc , and n _rb , respectively, the representative index n _r includes n _cs , n _oc , and n _rb . n _r satisfies n _r = (n _cs , n _oc , n _rb ).

  The combination of CQI, PMI, RI, and CQI and ACK / NACK can be transmitted through PUCCH format 2 / 2a / 2b. Reed-Muller (RM) channel coding can be applied.

For example, the channel coding for UL CQI in the LTE system will be described as follows. Bit streams a ₀ , a ₁ , a ₂ , a ₃ ,..., _{A A-1} are channel-coded using (20, A) RM codes. Table 10 shows the basic sequence for the (20, A) code. a ₀ and a _A-1 represent the most significant bit (MSB) and the least significant bit (LSB). In the case of the extended CP, the maximum information bit is 11 bits except for the case where CQI and ACK / NACK are transmitted simultaneously. QPSK modulation can be applied after encoding to 20 bits using the RM code. Prior to QPSK modulation, the encoded bits can be scrambled.

ここで、ｉ＝０，１，２，…，Ｂ−１を満たす。 Channel coded bits b ₀ , b ₁ , b ₂ , b ₃ ,..., B _B-1 can be generated by Equation 9.
(Formula 9)

Here, i = 0, 1, 2,..., B-1 is satisfied.

Table 11 represents the uplink control information (UCI) field for wideband reporting (single antenna port, transmit diversity or open loop spatial multiplexing PDSCH) CQI feedback.

Table 12 represents the UCI field for CQI and PMI feedback for wideband, which reports a closed-loop spatial multiplexing PDSCH transmission.

Table 13 represents the UCI field for RI feedback for wideband reporting.

FIG. 19 is a diagram illustrating PRB allocation. As shown in FIG. 19, it is possible to use a PRB for PUCCH transmission in slot _{n s.}

  A multi-carrier system or a carrier aggregation system refers to a system that uses a combination of a plurality of carriers having a band smaller than a target band for broadband support. When combining a plurality of carriers having a band smaller than the target band, the band of the combined carriers may be limited to the bandwidth used in the existing system for backward compatibility with the existing system. For example, existing LTE systems support 1.4, 3, 5, 10, 15, and 20 MHz bandwidths, and LTE-A systems that have evolved from LTE systems use only 20 MHz of bandwidth supported by LTE. Greater bandwidth can be supported. Or, regardless of the bandwidth used in the existing system, a new bandwidth may be defined to support carrier aggregation. Multiple carrier is a name that can be used in combination with carrier aggregation and bandwidth combination. Carrier aggregation is a generic term for adjacent carrier aggregation and non-adjacent carrier aggregation.

  FIG. 20 is a diagram illustrating a concept of managing downlink component carriers in a base station, and FIG. 21 is a diagram illustrating a concept of managing uplink component carriers in a terminal. For the convenience of explanation, in the following, in FIG. 20 and FIG.

  FIG. 22 illustrates the concept that one MAC manages multiple carriers in a base station. FIG. 23 illustrates the concept that one MAC manages multiple carriers in a terminal.

  Referring to FIGS. 22 and 23, one MAC manages and operates one or more frequency carriers to perform transmission / reception. Since the frequency carriers managed by one MAC do not need to be adjacent to each other, there is an advantage that they are more flexible in terms of resource management. 22 and 23, one PHY means one component carrier wave for convenience. Here, one PHY does not necessarily mean an independent radio frequency (RF) device. In general, one independent RF device refers to one PHY, but is not limited thereto, and one RF device may include a plurality of PHYs.

  FIG. 24 illustrates a concept in which a plurality of MACs manage a plurality of carriers in a base station. FIG. 25 illustrates a concept in which a plurality of MACs manage a plurality of carriers in a terminal. FIG. 26 illustrates another concept in which multiple MACs manage multiple carriers in a base station. FIG. 27 illustrates another concept in which multiple MACs manage multiple carriers in a terminal.

  The structure is not limited to that shown in FIGS. 22 and 23, and a plurality of carrier waves can be controlled by a plurality of MACs instead of one MAC as shown in FIGS.

  As shown in FIG. 24 and FIG. 25, each MAC can be controlled by 1: 1 for each MAC. As shown in FIG. 26 and FIG. The MAC can be controlled 1: 1, and one MAC can control one or more remaining carriers.

  The above system is a system including a plurality of 1 to N carrier waves, and each carrier wave may be used adjacently or non-adjacently. This is applicable regardless of uplink / downlink. The TDD system is configured to operate N multiple carriers including downlink and uplink transmissions within each carrier, and the FDD system is configured to use multiple carriers for the uplink and downlink, respectively. Is done. In the case of an FDD system, it is also possible to support asymmetric carrier aggregation in which the number of carriers combined in the uplink and downlink and / or the carrier bandwidth is different.

  If the number of component carriers combined in the uplink and downlink is the same, all the component carriers can be configured to be compatible with the existing system. However, component carriers that do not consider compatibility are not excluded from the present invention.

  Hereinafter, for convenience of explanation, when the PDCCH is transmitted on the downlink component carrier # 0, the corresponding PDSCH is transmitted on the downlink component carrier # 0. It is obvious that the corresponding PDSCH may be transmitted through other downlink component carriers by applying carrier scheduling. The term “component carrier” may be any other equivalent term (eg, cell).

  FIG. 28 illustrates a scenario in which uplink control information (UCI) is transmitted in a wireless communication system that supports carrier aggregation. For convenience, this example assumes that UCI is ACK / NACK (A / N). However, this is for convenience of explanation, and UCI includes control information such as channel state information (CSI) (for example, CQI, PMI, RI) and schedule request information (for example, SR) without limitation. Can do.

FIG. 28 illustrates asymmetric carrier aggregation in which 5 DL CCs are combined with 1 UL CC. It can be said that the illustrated asymmetric carrier aggregation is set from the viewpoint of UCI transmission. That is, the DL CC-UL CC combination for UCI and the DL CC-UL CC combination for data can be set differently. For convenience, when one DL CC can transmit a maximum of two codewords, the UL ACK / NACK bit also needs at least two bits. In this case, at least 10 ACK / NACK bits are required to transmit ACK / NACK for data received through 5 DL CCs through one UL CC. In order to support the DTX state for each DL CC, at least 12 bits (= 5 ⁵ = 3125 = 11.61 bits) are required for ACK / NACK transmission. Since the existing PUCCH format 1a / 1b can send ACK / NACK up to 2 bits, this structure cannot transmit increased ACK / NACK information. Although the carrier aggregation is cited as the cause of the increase in the amount of UCI information, it is also caused by the increase in the number of antennas, the presence of backhaul subframes in the TDD system, and the relay system. Similarly to ACK / NACK, when control information related to a plurality of DL CCs is to be transmitted through one UL CC, the amount of control information to be transmitted increases. For example, the UCI payload may increase when CQI / PMI / RI for multiple DL CCs must be transmitted.

  A DL primary CC can be defined as a DL CC combined with a UL primary CC. Here, the binding includes both implicit binding and explicit binding. In LTE, one DL CC and one UL CC are uniquely paired. For example, a DL CC combined with a UL primary CC by LTE pairing may be referred to as a DL primary CC. This can be called an implicit join. Explicit coupling means that the network sets the coupling in advance, and can be signaled by RRC or the like. In explicit combining, a DL CC that is paired with a UL primary CC may be referred to as a primary DL CC. Here, the UL primary (or anchor) CC may be a UL CC in which the PUCCH is transmitted. Alternatively, the UL primary CC may be a UL CC in which UCI is transmitted through PUCCH or PUSCH. Alternatively, the DL primary CC may be set through higher layer signal notification. Alternatively, the DL primary CC may be a DL CC to which the terminal has made initial connection. Also, DL CCs other than the DL primary CC can be referred to as DL secondary CCs. Similarly, UL CCs other than UL primary CCs can be referred to as UL secondary CCs.

  LTE-A uses the concept of cells to manage radio resources. A cell is defined by a combination of a downlink resource and an uplink resource, and the uplink resource is not an essential element. Therefore, a cell can be configured with downlink resources alone or with downlink resources and uplink resources. If carrier aggregation is supported, the coupling between the carrier frequency (or DL CC) of the downlink resource and the carrier frequency (or UL CC) of the uplink resource may be indicated by system information. A cell operating on the primary frequency (or PCC) may be referred to as a primary cell (PCell), and a cell operating on the secondary frequency (or SCC) may be referred to as a secondary cell (SCell). For simplicity, the DL CC and UL CC may be referred to as a DL cell and a UL cell, respectively. Also, the anchor (or primary) DL CC and the anchor (or primary) UL CC can be referred to as DL PCell and UL PCell, respectively. The PCell is used for a terminal to perform an initial connection establishment procedure or a connection re-establishment procedure. The PCell may be a cell indicated in the handover process. The SCell can be configured after the RRC connection is established and can be used to provide additional radio resources. PCell and SCell can also be collectively referred to as service providing cells. Therefore, in the case of a terminal that is in the RRC_CONNECTED state but does not set up carrier aggregation or does not support carrier aggregation, there is only one service providing cell configured only by PCell. On the other hand, in the case of a terminal in the RRC_CONNECTED state and carrier aggregation is set, one or more service providing cells exist, and the overall service providing cell includes a PCell and an overall SCell. For carrier aggregation, the network configures one or more SCells for terminals that support carrier aggregation in addition to the PCell that is initially configured in the connection establishment process after the initial security activation process is started. can do.

  DL-UL pairing may be limited to FDD. Since TDD uses the same frequency, there is no need to define DL-UL pairing separately. In addition, the DL-UL combination can be determined from the UL combination through SEAR2 UL EARFCN (E-UTRA Absolute Radio Frequency Channel Number) information. For example, the DL-UL combination can be acquired through SIB2 decoding at the initial connection, and the other can be acquired through RRC signal notification. Therefore, only SIB2 binding exists and other DL-UL pairings may not be explicitly defined. For example, in the 5DL: 1UL structure of FIG. 28, DL CC # 0 and UL CC # 0 are in SIB2 coupling relationship, and the remaining DL CCs are in SIB2 coupling relationship with other UL CCs not set in the terminal. Can have.

  A new method is required to support the scenario as shown in FIG. Hereinafter, in a communication system that supports carrier aggregation, the PUCCH format for feeding back UCI (for example, multiple A / N bits) is referred to as CA PUCCH format (or PUCCH format 3). For example, PUCCH format 3 is used for transmitting A / N information (which may include a DTX state) corresponding to PDSCH (or PDCCH) transmitted from multiple DL service providing cells.

  29A to 29F illustrate the structure of PUCCH format 3 and the signal processing procedure.

  FIG. 29A illustrates a case where PUCCH format 3 is applied to the structure of PUCCH format 1 (regular CP). Referring to FIG. 29A, a channel coding block performs channel coding on information bits a_0, a_1,..., A_M−1 (for example, multiple ACK / NACK bits) to generate coded bits (or codewords). ) B — 0, b — 1,..., B — N−1 are generated. M represents the size of the information bit, and N represents the size of the encoded bit. The information bits include uplink control information (UCI), for example, multiple ACK / NACK for a plurality of data (or PDSCH) received through a plurality of DL CCs. Here, the information bits a_0, a_1,..., A_M−1 are jointly encoded regardless of the type / number / size of the UCIs constituting the information bits. For example, when the information bits include multiple ACK / NACK for multiple DL CCs, channel coding is performed on the entire bit information without performing the DL CC and individual ACK / NACK bits separately, thereby A codeword is generated. Channel coding includes but is not limited to simple repetition, simple coding, RM coding, punctured RM coding, tail bit convolutional coding (TBCC), low density parity check (LDPC) Alternatively, turbo coding can be used. Although not shown, the coded bits may be rate-matched in consideration of the modulation order and the resource amount. The rate matching function may be included as part of the channel coding block or may be performed by another functional block. For example, the channel coding block can perform (32,0) RM coding on a plurality of control information to obtain a single codeword, and perform circular buffer rate matching on this codeword.

  The modulator modulates the coded bits b_0, b_1, ..., b_N-1 to generate modulation symbols c_0, c_1, ..., c_L-1. L represents the size of the modulation symbol. Modulation is done by modifying the size and phase of the transmitted signal. The modulation method includes, for example, n-phase phase shift keying (n-PSK) and n-value quadrature amplitude modulation (n-QAM) (n is an integer of 2 or more). Specifically, BPSK, QPSK, 8PSK, QAM, 16QAM, 64QAM, or the like can be used as a modulation method.

  The frequency divider divides the modulation symbols c_0, c_1, ..., c_L-1 into slots. The order / pattern / system for dividing the modulation symbol into each slot is not particularly limited. For example, the frequency divider can divide the modulation symbols into respective slots in order from the front (local scheme). In this case, as shown in the figure, modulation symbols c_0, c_1,..., C_L / 2-1 are divided into slot 0, and modulation symbols c_L / 2, c_L / 2 + 1,. I can go around. Further, the modulation symbols can be interleaved (or rearranged) when the frequency is divided into the respective slots. For example, even-numbered modulation symbols can be divided into slots 0, and odd-numbered modulation symbols can be divided into slots 1. The order of the modulation process and the frequency division process may be switched.

  The DFT precoder performs DFT precoding (eg, 12-point DFT) on the modulation symbols divided in each slot to generate a single carrier waveform. In the same figure, modulation symbols c_0, c_1,..., C_L / 2-1 that have been frequency-divided into slot 0 are DFT precoded as DFT symbols d_0, d_1,. The modulated symbols c_L / 2, c_L / 2 + 1,..., C_L−1 are DFT precoded as DFT symbols d_L / 2, d_L / 2 + 1,. DFT precoding can be replaced by other corresponding linear operations (eg, Walsh precoding).

  The spreading block spreads the DFT signal at the SC-FDMA symbol level (time domain). SC-FDMA symbol level time domain spreading is performed using spreading codes (or spreading sequences). The spreading code includes a quasi-orthogonal code and an orthogonal code. Quasi-orthogonal codes include, but are not limited to, pseudo-noise (PN) codes. The orthogonal code includes, but is not limited to, a Walsh code and a DFT code. An orthogonal code (OC) may be mixed with an orthogonal sequence, an orthogonal cover (OC), and an orthogonal cover code (OCC). In this specification, for ease of explanation, an orthogonal code will be described as a representative example of a spread code. However, this is an example, and the orthogonal code can be replaced with a quasi-orthogonal code. The maximum value of the spreading code size (or spreading factor (SF)) is limited by the number of SC-FDMA symbols used for control information transmission. As an example, when four SC-FDMA symbols are used for control information transmission in one slot, (quasi) orthogonal codes w0, w1, w2, and w3 of length 4 can be used for each slot. SF means the degree of spreading of control information, and can be related to the multiplexing order of the terminal or the antenna multiplexing order. The SF can be changed according to system requirements such as 1, 2, 3, 4,..., And can be defined in advance between the base station and the terminal, or can be notified to the terminal through DCI or RRC signal notification. Can do. For example, when one of the control information SC-FDMA symbols is punctured to transmit the SRS, the control information of the slot is reduced in SF (for example, SF = 3 instead of SF = 4). ) Spreading code can be applied.

  The signal generated through the above process is mapped to a subcarrier in the PRB, and then converted into a time domain signal through IFFT. CP is added to the time domain signal, and the generated SC-FDMA symbol is transmitted through the RF end.

  Each process will be described more specifically with reference to the case of transmitting ACK / NACK for five DL CCs. When each DL CC can transmit two PDSCHs, the ACK / NACK bit for this can be 12 bits when it includes a DTX state. If QPSK modulation and SF = 4 time spreading are assumed, the encoded block size (after rate matching) may be 48 bits. The coded bits are modulated into 24 QPSK symbols, and the generated QPSK symbols are divided by 12 into each slot. In each slot, 12 QPSK symbols are converted to 12 DFT symbols through a 12-point DFT operation. In each slot, 12 DFT symbols are spread and mapped into 4 SC-FDMA symbols using a spreading code of SF = 4 in the time domain. Since 12 bits are transmitted through [2 bits * 12 subcarriers * 8 SC-FDMA symbols], the coding rate is 0.0625 (= 12/192). When SF = 4, a maximum of 4 terminals can be multiplexed per 1 PRB.

  The signal processing procedure described with reference to FIG. 29A is merely an example, and the signal mapped to the PRB in FIG. 29A may be obtained through various equivalent signal processing procedures. A signal processing procedure equivalent to that illustrated in FIG. 29A will be described with reference to FIGS. 29B to 29F.

  FIG. 29B is obtained by switching the processing order of the DFT precoder and the spreading block in FIG. 29A. In FIG. 29A, the function of the spreading block is equivalent to multiplying the DFT symbol sequence output from the DFT precoder by a specific constant at the SC-FDMA symbol level. The value of the signal to be performed is the same. Therefore, the signal processing procedure for PUCCH format 3 can be in the order of channel coding, modulation, frequency division, spreading, and DFT precoding. In this case, the frequency division process and the diffusion process may be performed by one functional block. As an example, each modulation symbol can be spread at the SC-FDMA symbol level simultaneously with the frequency division while the modulation symbol is alternately divided into each slot. As another example, when a modulation symbol is divided into each slot, each modulation symbol is copied so as to correspond to the size of the spreading code, and each modulation symbol and each element of the spreading code are 1: 1. Can be multiplied. For this reason, the modulation symbol sequence generated for each slot is spread to a plurality of SC-FDMA symbols at the SC-FDMA symbol level. Thereafter, the complex symbol sequence corresponding to each SC-FDMA symbol is DFT precoded in units of SC-FDMA symbols.

  FIG. 29C is obtained by switching the processing order of the modulator and the frequency divider in FIG. 29A. Therefore, the processing procedure for PUCCH format 3 is performed in the order of joint channel coding and frequency division at the subframe level, and in the order of modulation, DFT precoding, and spreading at each slot level.

  FIG. 29D is obtained by further replacing the processing order of the DFT precoder and the spreading block in FIG. 29C. As described above, the function of the spreading block is equivalent to multiplying the DFT symbol sequence output from the DFT precoder by a specific constant at the SC-FDMA symbol level. The value of the signal mapped to the FDMA symbol is the same. Accordingly, in the signal processing procedure for PUCCH format 3, joint channel coding and frequency division are performed at the subframe level, and modulation is performed at each slot level. The modulation symbol sequence generated for each slot is spread into a plurality of SC-FDMA symbols at the SC-FDMA symbol level, and the modulation symbol sequence corresponding to each SC-FDMA symbol is in DFT precoding order in units of SC-FDMA symbols. Become. In this case, the modulation process and the spreading process may be performed by one functional block. As an example, while modulating the coded bits, the generated modulation symbols can be immediately spread at the SC-FDMA symbol level. As another example, the modulation symbols generated during the modulation of the coded bits can be copied so as to correspond to the size of the spread code, and these modulation symbols and each element of the spread code can be multiplied on a one-to-one basis. .

  FIG. 29E shows a case where PUCCH format 3 is applied to the structure of PUCCH format 2 (regular CP), and FIG. 29F shows a case where PUCCH format 3 is applied to the structure of PUCCH format 2 (extended CP). The basic signal processing procedure is as described with reference to FIGS. 29A to 29D. Since the existing LTE PUCCH format 2 structure is reused, the number / position of UCI SC-FDMA symbols and RS SC-FDMA symbols in PUCCH format 3 are different from those in FIG. 29A.

Table 14 shows the positions of RS SC-FDMA symbols in the illustrated PUCCH format 3. In the case of regular CP, the number of SC-FDMA symbols in the slot is 7 (index: 0 to 6), and in the case of extended CP, the number of SC-FDMA symbols in the slot is 6 (index: 0 to 5). To do.

  Here, the RS can inherit the structure of the existing LTE. For example, the RS sequence can be defined by a cyclic shift of the basic sequence (see Equation 1).

  The signal processing process of PUCCH format 3 will be described using equations. For convenience, the case where an OCC having a length of 5 is used (for example, FIGS. 29E to 31) will be taken up.

ここで、ｃ（ｉ）は、スクランブルシーケンスを表す。ｃ（ｉ）は、長さ３１のゴールドシーケンスによって定義される擬似ランダムシーケンスを含み、かつ、下記の式によって生成可能である。ｍｏｄは、モジュロ演算を表す。 First, bit blocks b (0),..., B (M _bit −1) are scrambled into a terminal-specific scramble sequence. Bit blocks b (0),..., B (M _bit −1) can correspond to the encoded bits b_0, b_1,. Bit block b (0),..., B (M _bit −1) includes at least one of an ACK / NACK bit, a CSI bit, and an SR bit. The scrambled bit block tilda-b (0),..., Tilda-b (M _bit −1) can be generated by the following equation.
(Formula 10)

Here, c (i) represents a scramble sequence. c (i) includes a pseudo-random sequence defined by a gold sequence of length 31 and can be generated by the following equation. mod represents a modulo operation.

ここで、Ｎ_ｃ＝１６００である。１番目のｍシーケンスは、ｘ_１（０）＝１，ｘ_１（ｎ）＝０，ｎ＝１，２，…，３０と初期化する。２番目のｍシーケンスの初期化は

と与えられる。ｃ_ｉｎｉｔは、毎サブフレームの開始時に

と初期化してもよい。ｎ_ｓは、無線フレーム内でのスロット番号であり、Ｎ^ｃｅｌｌ _ＩＤは、物理層セル識別子であり、ｎ_ＲＮＴＩは、無線ネットワーク一時識別子である。 (Formula 11)

Here, N _c = 1600. The first m-sequence is initialized as x ₁ (0) = 1, x ₁ (n) = 0, n = 1, 2,. The initialization of the second m-sequence is

And given. c _init is at the start of every subframe

And may be initialized. n _s is a slot number in a radio frame, N ^cell _ID is a physical layer cell identifier, and n _RNTI is a radio network temporary identifier.

The scrambled bit blocks tilda-b (0),..., Tilda-b (M _bit −1) are modulated to generate complex modulation symbol blocks d (0),... D (M _sym −1). At the time of QPSK modulation, M _symbol = M _bit / 2 = 2N ^RB _SC . Complex modulation symbol blocks d (0),... D (M _sym −1) correspond to the modulation symbols c_0, c_1,.

ここで、Ｎ^{ＰＵＣＣＨ} _ＳＦ，０及びＮ^{ＰＵＣＣＨ} _ＳＦ，１はそれぞれ、スロット０及びスロット１においてＰＵＣＣＨ送信に用いられるＳＣ−ＦＤＭＡシンボルの個数に該当する。正規ＰＵＣＣＨフォーマット３を用いる場合は、Ｎ^{ＰＵＣＣＨ} _ＳＦ，０＝Ｎ^{ＰＵＣＣＨ} _ＳＦ，１＝５である。短縮したＰＵＣＣＨフォーマット３を用いる場合は、Ｎ^{ＰＵＣＣＨ} _ＳＦ，０＝５,Ｎ^{ＰＵＣＣＨ} _ＳＦ，１＝４である。

及び

はそれぞれスロット０及びスロット１に適用される直交シーケンスを表し、下記の表１５によって与えられる。

は、直交シーケンスインデクス（あるいは、直交符号インデクス）を表す。

は、床（ｆｌｏｏｒ）関数を表す。ｎ^ｃｅｌｌ _ｃｓ（ｎ_ｓ，ｌ）は、

と与えることができる。ｃ（ｉ）は、式１１によって与えることができ、かつ毎無線フレームの開始点でｃ_ｉｎｉｔ＝Ｎ^ｃｅｌｌ _ＩＤと初期化できる。ｎ＝０，…，Ｎ^{ＰＵＣＣＨ} _ＳＦ，０＋Ｎ^{ＰＵＣＣＨ} _ＳＦ，１−１である。ｔｉｌｄａ−Ｐは、アンテナポート番号に対応するインデクスである。 The complex modulation symbol blocks d (0),... D (M _sym −1) are spread in a block manner using the orthogonal sequence W _noc (i). N ^PUCCH _{SF, 0} + N ^PUCCH _{SF, one} complex symbol set is generated according to the following equation. The frequency division / diffusion process of FIG. 29B is performed according to the following equation. Each complex symbol set corresponds to one SC-FDMA symbol and has N ^RB _SC (for example, 12) complex modulation values.
(Formula 12)

Here, N ^PUCCH _{SF, 0} and N ^PUCCH _{SF, 1} correspond to the number of SC-FDMA symbols used for PUCCH transmission in slot 0 and slot 1, respectively. When the regular PUCCH format 3 is used, N ^PUCCH _{SF, 0} = N ^PUCCH _{SF, 1} = 5. When the shortened PUCCH format 3 is used, N ^PUCCH _{SF, 0} = 5 and N ^PUCCH _{SF, 1} = 4.

as well as

Represent orthogonal sequences applied to slot 0 and slot 1, respectively, and are given by Table 15 below.

Represents an orthogonal sequence index (or an orthogonal code index).

Represents a floor function. n ^cell _cs (n _s , l) is

And can be given. c (i) can be given by Equation 11 and can be initialized with c _init = N ^cell _ID at the start of every radio frame. n = 0,..., N ^PUCCH _{SF, 0} + N ^PUCCH _{SF, 1} −1. tilda-P is an index corresponding to the antenna port number.

Table 15 shows an orthogonal sequence W _noc (i) according to an existing scheme.

In Table 15, the orthogonal sequence N ^PUCCH _SF = 5 (or code) is generated by the following equation.
(Formula 13)

ここで、ｎ^{（ｔｉｌｄａ−ｐ）} _ｏｃ，０は、スロット０のためのシーケンスインデクス値（ｎ^{（ｔｉｌｄａ−ｐ）} _ｏｃ）を表し、ｎ^{（ｔｉｌｄａ−ｐ）} _ｏｃ，１は、スロット１のためのシーケンスインデクス値（ｎ^{（ｔｉｌｄａ−ｐ）} _ｏｃ）を表す。正規ＰＵＣＣＨフォーマット３の場合、Ｎ^{ＰＵＣＣＨ} _ＳＦ，０＝Ｎ^{ＰＵＣＣＨ} _ＳＦ，１＝５である。短縮ＰＵＣＣＨフォーマット３の場合は、Ｎ^{ＰＵＣＣＨ} _ＳＦ，０＝５、Ｎ^{ＰＵＣＣＨ} _ＳＦ，１＝４である。 On the other hand, the resource for PUCCH format 3 is identified by resource index n ^{(3, tilda-p)} _PUCCH . For example, n ^(tilda-p) _oc can be given by n ^(tilda-p) _oc = n ^{(3, tilda-p)} _PUCCH ^mod N ^PUCCH _{SF, 1} . The n ^{(3, tilda-p)} _PUCCH may be indicated through the transmission power control (TPC) field of the SCell PDCCH. More specifically, n ^(tilda-p) _oc for each slot can be given by:
(Formula 14)

Here, n ^(tilda-p) _{oc, 0} represents the sequence index value (n ^(tilda-p) _oc ) for slot 0, and n ^(tilda-p) _{oc, 1} is for slot 1 This represents the sequence index value (n ^(tilda-p) _oc ). For regular PUCCH format 3, N ^PUCCH _{SF, 0} = N ^PUCCH _{SF, 1} = 5. In the case of the shortened PUCCH format 3, N ^PUCCH _{SF, 0} = 5 and N ^PUCCH _{SF, 1} = 4.

According to the above equation, in the shortened PUCCH format 3 (ie, N ^PUCCH _{SF, 1} = 4), the orthogonal sequence of the same index (n ^(tilda-p) _{oc, 1} ) is used in slot 0 and slot 1. It is done.

ここで、ｎ_ｓは、無線フレーム内のスロット番号を表し、ｌは、スロット内でＳＣ−ＦＤＭＡシンボル番号を表す。ｎ^ｃｅｌｌ _ｃｓ（ｎｓ、ｌ）は、式１２で定義したとおりである。ｎ＝０，…，Ｎ^{ＰＵＣＣＨ} _ＳＦ，０＋Ｎ^{ＰＵＣＣＨ} _ＳＦ，１−１である。 The block-spread complex symbol set may be cyclically shifted by the following equation.
(Formula 15)

Here, _{n s} denotes a slot number within a radio frame, l represents an SC-FDMA symbol number within a slot. n ^cell _cs (ns, l) is as defined in Equation 12. n = 0,..., N ^PUCCH _{SF, 0} + N ^PUCCH _{SF, 1} −1.

が生成される。
（式１６）

Each complex symbol set that is cyclically shifted is transformed and precoded by the following equation. As a result, complex symbol block

Is generated.
(Formula 16)

は、電力制御の後に物理リソースにマップされる。電力制御の詳細については後述する。ＰＵＣＣＨは、サブフレーム内の各スロットで一つのリソースブロックを使用する。該当のリソースブロックにおいて、

は、ＲＳ送信（表１４参照）に用いられない、アンテナポートｐ上のリソース要素（ｋ，ｌ）にマップされる。サブフレームの最初のスロットから始めて、ｋ、次にｌ、次にスロット番号の増加する順にマップがなされる。ｋは、副搬送波インデクスを表し、ｌはスロット内のＳＣ−ＦＤＭＡシンボルインデクスを表す。Ｐは、ＰＵＣＣＨ送信に用いられるアンテナポートの個数を表す。ｐは、ＰＵＣＣＨ送信に用いられるアンテナポート番号を表し、ｐとｔｉｌｄａ−ｐの関係は下記の表のとおりである。 Complex symbol block

Are mapped to physical resources after power control. Details of the power control will be described later. The PUCCH uses one resource block in each slot in the subframe. In the corresponding resource block,

Are mapped to resource elements (k, l) on antenna port p that are not used for RS transmission (see Table 14). Starting from the first slot of the subframe, the mapping is done in the order of k, then l, then slot number. k represents the subcarrier index, and l represents the SC-FDMA symbol index in the slot. P represents the number of antenna ports used for PUCCH transmission. p represents an antenna port number used for PUCCH transmission, and the relationship between p and tilda-p is as shown in the following table.

Hereinafter, conventional PUCCH power control will be described. The explanation will be focused on PUCCH format 3. When the serving cell c is a primary cell, the terminal transmission power P _PUCCH (i) for PUCCH transmission in subframe i is given as follows.
(Formula 17)

P _{CMAX, c} (i) represents the maximum transmission power of the terminal set for the serving cell c.

_{PO PUCCH} is P _{O NOMINAL PUCCH} and _{PO UE} It is a parameter composed of the sum with _PUCCH . _{PO NOMINAL PUCCH} and _{PO UE The PUCCH} is provided by an upper layer (eg, RRC layer).

PL _c represents the downlink path loss estimated value of the serving cell c.

Parameter Δ _{F PUCCH} (F) is provided by higher layers. Each Δ _F The value of _PUCCH (F) represents a value corresponding to the PUCCH format for PUCCH format 1a.

If the terminal is configured by the upper layer to transmit PUCCH via two antenna ports, the parameter Δ _TxD (F ′) is provided by the upper layer. Otherwise, i.e., if the PUCCH is configured to be transmitted from a single antenna port, _ΔTxD (F ′) is zero. That is, Δ _TxD (F ′) corresponds to a power compensation value considering the antenna port transmission mode.

h (·) is a PUCCH format dependent value. h (·) is a function having at least one of n _CQI , n _HARQ and n _SR as a parameter.

In the case of PUCCH format 3, h (·) = n _HARQ + n _SR −1/2 is given. Here, n _CQI represents a power compensation value associated with channel quality information. Specifically, n _CQI corresponds to the number of information bits for channel quality information. n _SR represents the power compensation value associated with SR. Specifically, n _SR corresponds to the number of SR bits. If the time point at which HARQ-ACK is to be transmitted using PUCCH format 3 is a subframe set for SR transmission (simply, SR subframe), the terminal uses PUCCH format 3 to perform congruence. Encoded SR bits (eg, 1 bit) and one or more HARQ-ACK bits are transmitted. Therefore, the size of the control information transmitted using PUCCH format 3 in the SR subframe is always 1 larger than the HARQ-ACK payload size. Therefore, _nSR is 1 when subframe i is an SR subframe, and 0 when subframe i is a non-SR subframe.

n _HARQ represents a power compensation value associated with HARQ-ACK. Specifically, n _HARQ corresponds to the number of (valid) information bits of HARQ-ACK. Also, n _HARQ is defined as the number of transmission blocks received in the corresponding downlink subframe. That is, power control is scheduled by the base station and is determined by the number of terminals successfully decoded PDCCH for the corresponding packet. On the other hand, the HARQ-ACK payload size is determined by the number of configured DL cells. Therefore, when the terminal is configured to have one serving cell, n _HARQ is the number of HARQ bits transmitted in subframe i. When the terminal has a plurality of service providing cells, n _HARQ can be given as follows. In TDD, when the terminal receives the SPS release PDCCH in any one of the subframes i−k _m (k _m εK, 0 ≦ m ≦ M−1) in the serving cell c, n _{HARQ, c} = ( The number of transmission blocks received in subframe i−k _m ) +1. The terminal uses the SPS release PDCCH in any one of the subframes i−k _m (k _m εK: (k ₀ , k ₁ ,... K _M−1 ), 0 ≦ m ≦ M−1) in the service providing cell c. If not _{received, n HARQ,} is given by c = (the number of transmission blocks received in subframe _{i-k m).} In FDD, n _HARQ is given in the same way as in TDD, M = 1 and k ₀ = 4.

と与えることができる。Ｃは、設定されたサービス提供セルの個数を表す。Ｎ^{ｒｅｃｅｉｖｅｄ} _ｋｍ，ｃは、サービス提供セルｃのサブフレームｉ−ｋ_ｍで受信した伝送ブロック及びＳＰＳリリースＰＤＣＣＨの個数を表す。ＦＤＤでは、

で与えることができる。Ｎ^{ｒｅｃｅｉｖｅｄ} _ｃは、サービス提供セルｃのサブフレームｉ−４において受信した伝送ブロック及びＳＰＳリリースＰＤＣＣＨの個数を表す。 Specifically, in TDD,

And can be given. C represents the number of set service providing cells. N ^{received The} _{miles, c} represents the transmission blocks and the number of SPS release PDCCH received in subframe _{i-k m} of the serving cell c. In FDD,

Can be given in N ^received _c represents the number of transmission blocks and SPS release PDCCHs received in subframe i-4 of service providing cell c.

で与えることができる。ｇ（０）は、リセット後の１番目の値である。δ_{ＰＵＣＣＨ}は、端末特定補正（ｃｏｒｒｅｃｔｉｏｎ）値であり、ＴＰＣコマンドと呼ばれることもある。δ_{ＰＵＣＣＨ}は、ＰＣｅｌｌの場合、ＤＣＩフォーマット１Ａ／１Ｂ／１Ｄ／１／２Ａ／２／２Ｂ／２Ｃを持つＰＤＣＣＨに含まれる。また、δ_{ＰＵＣＣＨ}は、ＤＣＩフォーマット３／３Ａを持つＰＤＣＣＨ上で他の端末特定ＰＵＣＣＨ補正値と合同符号化される。 g (i) represents the current PUCCH power control adjustment state. In particular,

Can be given in g (0) is the first value after reset. δ _PUCCH is a terminal-specific correction value and may be called a TPC command. In the case of PCell, δ _PUCCH is included in PDCCH having DCI format 1A / 1B / 1D / 1 / 2A / 2 / 2B / 2C. Also, δ _PUCCH is jointly encoded with other terminal specific PUCCH correction values on PDCCH having DCI format 3 / 3A.

Example: PUCCH power control when PUCCH and PUSCH simultaneous transmission mode is set

  FIG. 30 illustrates a UL transmission process based on the existing 3GPP Rel-8 / 9. FIG. 30 shows the MAC layer buffer status report (BSR) and the SR process.

  Referring to FIG. 30, when UL data is available for transmission to an upper layer entity (eg, RLC entity, PDCP entity) (S3002), a BSR process is started (S3004). The BSR process is used to provide the serving base station with information about the amount of data available for transmission in the terminal's UL buffer. When the BSR is activated, the MAC layer checks whether there is an UL resource (for example, UL-SCH resource) allocated for new transmission (S3006). When there is an assigned UL-SCH resource, the MAC layer generates a MAC PDU (S3008). The MAC PDU may include a BSR MAC control element (CE) and / or pending data that can be used for transmission. Thereafter, the MAC layer transmits the generated MAC PDU to the physical layer (S3010). The MAC PDU is transmitted to the physical layer through the UL-SCH channel, and the MAC PDU becomes a UL-SCH transport block for the physical layer. Next, the activated BSR process is canceled (S3012). After the BSR MAC CE is transmitted, if there is pending data in the buffer, the base station allocates UL-SCH resources to the terminal in consideration of the BSR, and the terminal transmits the pending data using the allocated resource. be able to.

  On the other hand, if there is no UL resource allocated for new transmission, the SR process is triggered (S3014). The SR process is used to request UL-SCH resources for new transmissions. When the SR process is activated, the MAC layer instructs the physical layer to transmit SR (S3016). The physical layer transmits the SR on the SR subframe (subframe set for SR transmission) according to the instruction of the MAC layer. Thereafter, the MAC layer checks whether there is a UL-SCH resource that can be used for BSR or new data transmission (S3018). If there is no UL-SCH resource available, the SR process is put on hold and steps S3014 to S3016 are repeated. On the other hand, when there is a usable UL-SCH resource, that is, when the UL-SCH resource is allocated through the UL grant, the activated SR process is canceled (S3020). When the UL-SCH resource becomes available through the SR process, steps S3006 to S3012 are performed through the BSR process.

  In short, in the existing 3GPP Rel-8 / 9, when SR is activated and there is no PUSCH transmission in the SR subframe (that is, when there is no UL-SCH resource / UL-SCH transport block for SR subframe) The terminal transmits an affirmative SR using PUCCH format 1. On the other hand, when the SR is activated and there is PUSCH transmission in the SR subframe (that is, when there is a UL-SCH resource / UL-SCH transmission block for the SR subframe), the terminal stops SR transmission (drop). Instead, BSR MAC CE and / or pending data is transmitted through PUSCH.

On the other hand, in the existing 3GPP Rel-8 / 9, SR is activated and “CQI only PUSCH” may be activated in the SR subframe. The “CQI only PUSCH” signal includes only CQI and does not include data (ie, UL-SCH transport block). Therefore, when the CQI only PUSCH is activated, the activated SR is not canceled because there is no UL-SCH resource that can be used. That is, simultaneous transmission of the CQI only PUSCH signal and the SR PUCCH signal is requested in the same subframe. However, the existing 3GPP Rel-8 / 9 does not allow PUCCH + PUSCH simultaneous transmission. Therefore, in this example, the terminal regards CQI only PUSCH activation as a mis-configuration. As a result, the terminal stops the aperiodic CQI PUSCH transmission, and transmits only the positive SR using the PUCCH format 1. For reference, when the value of the CQI request field is 1, the MCS index (I _MCS ) is 29, and the number of allocated PRBs is 4 or less (N _PRB ≦ 4) in the PDCCH signal for UL grant, This signal notification is interpreted as CQI only PUSCH allocation.

  As described above, the existing 3GPP Rel-8 / 9 does not allow simultaneous transmission of PUCCH and PUSCH because of UL transmission having low PAPR characteristics. However, in 3GPP Rel-10, the PUCCH and PUSCH simultaneous transmission modes can be set through RRC signal notification. That is, the terminal transmits UCI (eg, HARQ-ACK and / or SR) via PUCCH on the same subframe, and data (eg, UL-SCH transport block) or CSI (eg, UL-SCH transport block) via PUSCH. Only CQI) can be transmitted.

On the other hand, according to the conventional PUCCH format 3 power control method described with reference to Equation 17, when transmitting control information in the SR subframe using PUCCH format 3, the control information is always SR bits (for example, 1 bit), and the added SR bits were used to increase the transmission power of PUCCH (n _SR = 1). The conventional power control method assumes a case where PUCCH + PUSCH simultaneous transmission is not set. That is, when only PUCCH or PUSCH is transmitted in one subframe, and PUCCH and PUSCH should be transmitted in the same subframe, the control information that was scheduled to be transmitted via PUCCH is transmitted via PUSCH. Sent. Therefore, the presence of PUCCH transmission in the SR subframe means that there is no UL-SCH resource / UL-SCH transport block for the SR subframe. In this case, the SR bit added to the control information can always be used to carry valid information.

  However, considering that the terminal may be set to the PUCCH and PUSCH simultaneous transmission mode, it is necessary to perform power control more efficiently. For example, assuming a case where the PUCCH and PUSCH simultaneous transmission mode is set, a simultaneous transmission scenario of the PUCCH format 3 signal and the PUSCH signal in the SR subframe is possible. In this case, the PUCCH format 3 signal may include SR bits, and the PUSCH signal may include a UL-SCH transmission block. Also, the PUSCH signal may include only CSI. As described with reference to FIG. 30, when there is a UL-SCH resource / UL-SCH transport block for the SR subframe, the activated SR is canceled. That is, the presence of the UL-SCH transmission block in the PUSCH signal can mean negative SR by itself. Therefore, when the PUSCH signal includes a UL-SCH transport block, the SR bits included in the PUCCH format 3 signal carry duplicate information. In this case, since the SR bit may have any value (don't care), the value of the SR bit may be considered invalid information. That is, when there is a UL-SCH transport block for the SR subframe, the SR bits included in the PUCCH format 3 signal correspond to dummy bits without information. Therefore, handling the case where a dummy bit is included in the PUCCH format 3 signal and the case where it is not the same in the PUCCH power control causes waste of power efficiency.

  Hereinafter, a method for efficiently performing PUCCH power control in consideration of the PUCCH and PUSCH simultaneous transmission modes will be described. In the following description, the method of correcting h (•) according to the UL signal transmission scenario in Expression 17 will be mainly described.

  When PUCCH + PUSCH simultaneous transmission is set, the UL transmission scenario is as follows.

  (1) When a PUCCH format 3 signal for HARQ-ACK and a PUSCH signal are simultaneously transmitted in a non-SR subframe, the PUSCH signal includes data (for example, UL-SCH transport block) or includes only CSI. Can be drunk.

  (2) When the PUCCH format 3 signal and the PUSCH signal are simultaneously transmitted for HARQ-ACK in the SR subframe, the PUSCH signal may include data (for example, UL-SCH transport block) or only CSI. Can do.

In (1), the SR bits are not included in the control information for PUCCH format 3. Therefore, h (•) for PUCCH power control can be determined by the following equation.
(Formula 18)

  In (2), when considering SR, the following cases can be considered.

i) HARQ-ACK + SR can be transmitted using PUCCH format 3, and only CSI can be transmitted via PUSCH. In this case, since the SR bit is a meaningful value representing actual SR information, power control of the PUCCH can be performed in consideration of the SR bit. In this case, h (•) for PUCCH power control can be determined by the following equation.
(Formula 19)

ii) HARQ-ACK + SR can be transmitted using PUCCH format 3, and UL-SCH transport blocks (for example, BSR, data) can be transmitted via PUSCH. In this example, the SR bit can represent actual SR information regardless of whether or not the UL-SCH transmission block is transmitted in the SR subframe. According to this example, if there is a UL-SCH transmission block transmission in the SR subframe, the SR bit must always indicate a value (eg, 0) indicating negative SR. Therefore, when there is a UL-SCH transmission block in the SR subframe, the SR bit in the PUCCH signal can be used for the purpose of error checking of control information transmitted via the PUCCH. Since the SR bit carries valid information, h (•) for PUCCH power control can be determined by the following equation.
(Formula 20)

  iii) HARQ-ACK + SR can be transmitted using PUCCH format 3, and UL-SCH transport blocks (eg, BSR, data) can be transmitted via PUSCH. In this example, the SR bit may be treated as a dummy bit without any information. That is, when there is no UL-SCH transport block in the SR subframe, the SR bits included in the PUCCH signal represent actual SR bits (that is, actual SR information and valid bits). In this case, the MAC layer of the terminal transmits SR instruction information to the PHY layer, and the PHY layer sets the value of the SR bit based on the SR instruction information. The case where there is no UL-SCH transmission block in the SR subframe includes the case where there is CSI only PUSCH transmission in the SR subframe (that is, aperiodic CSI without the UL-SCH transmission block). On the other hand, when there is a UL-SCH transmission block in the SR subframe, the SR bit included in the PUCCH signal represents a dummy bit (that is, dummy information, invalid bit). In this case, the MAC layer does not have to transmit the SR instruction information to the PHY layer. Instead, the PHY layer can set the SR bit to a dummy value depending on whether or not the corresponding condition is satisfied. The dummy bit can have an arbitrary specific value set in advance. For example, the dummy bit may be set to a predetermined value of 0 or 1, preferably 0.

Specifically, control information generated by multiplexing the HARQ-ACK bit sequence [b ₀ b ₁ ... B _m−1 ] and the SR bit s ₀ is transmitted using the PUCCH format 3, and UL-SCH is transmitted via the PUSCH. A transmission block (eg, BSR, data) can be transmitted. The multiplexing of the HARQ-ACK bit sequence and the SR bit is performed by adding the SR bit s ₀ to the end (or the top) of the HARQ-ACK bit sequence [b ₀ b ₁ ... B _m−1 ] and [b ₀ b ₁ . _m−1 s ₀ ] and encoding (ie, joint encoding) [b ₀ b ₁ ... b _m−1 s ₀ ]. In this example, the SR bit simply serves as a bit that is fixedly inserted for disambiguating the control information size. The SR bit is set to a predetermined value (eg, 0 or 1, preferably 0), and the base station can ignore the SR bit when decoding the control information. Instead, the base station can determine whether the SR of the terminal is activated due to the presence of the UL-SCH transport block (eg, BSR, data) of the PUSCH signal.

As described above, in this example, the SR bit does not indicate actual SR information, and the SR bit may not be considered during power control. In other words, when a PUCCH + PUSCH simultaneous transmission situation occurs in the SR subframe, HARQ-ACK + dummy SR is transmitted using PUCCH format 3, and UL-SCH transport block (for example, BSR, data) is transmitted via PUSCH. sell. H (·) for PUCCH power control can be determined by the following equation.
(Formula 21)

In this example, unlike the equation 17, in the SR _subframe, since the power control of the PUCCH is performed by _{n SR} = _{n SR} = 0 instead of 1, it is possible to increase the power efficiency for the UL transmission. In this example, n _SR can represent the number of valid SR bits (in other words, SR bits that actually have information). In addition, when HARQ-ACK is transmitted in an SR subframe using PUCCH format 3, the payload size of the control information is always kept the same using dummy SR bits, thereby improving the decoding efficiency of the base station. Can do.

  iv) HARQ-ACK can be transmitted using PUCCH format 3, and UL-SCH transport blocks (for example, BSR, data) can be transmitted via PUSCH. In this example, the SR bit is omitted. That is, if there is no UL-SCH transmission block in the SR subframe and the payload size of the control information included in the PUCCH signal is N, the SR subframe is included in the PUCCH signal when there is a UL-SCH transmission block in the SR subframe. The payload size of the received control information is N + 1.

Since SR bit is not transmitted, even if the transmitted PUCCH in SR subframe, unlike Equation _17, the power control of the PUCCH is performed by _{n SR} = _{n SR} = 0, not 1. Therefore, h (•) for PUCCH power control can be determined by the following equation.
(Formula 22)

Regardless of the presence / absence of the PUCCH + PUSCH simultaneous transmission mode setting, the above-described method can be generalized as follows.
(Formula 23)

When transmitting a PUCCH format 3 signal in a non-SR subframe, n _SR = 0

When transmitting a PUCCH format 3 signal in the SR subframe,
-N _SR = 1 when there is no UL-SCH transport block
-When there is a UL-SCH transport block, n _SR = 1 (Equation 20), n _SR = 0 (Equations 21 and 22)

  FIG. 31 is a diagram illustrating a process of transmitting control information through PUCCH according to an embodiment of the present invention.

  Referring to FIG. 31, the base station transmits a PDCCH and a corresponding PDSCH to the terminal (S3102). The terminal can receive at least one of PDCCH and PDSCH on the SCell. After that, the terminal generates control information for transmission using PUCCH format 3. The control information includes HARQ-ACK information for PDSCH. When HARQ-ACK is transmitted in the SR subframe, the control information further includes SR bits. An SR bit is added to the end (or top) of the HARQ-ACK bit string, and these are jointly encoded. A PUCCH format 3 signal is generated from the control information through the process illustrated in FIG. The terminal sets PUCCH transmission power for PUCCH transmission (S3104), and the PUCCH format 3 signal is transmitted to the base station through processes such as power control (S3106).

  In this example, when a PUCCH format 3 signal is transmitted in an SR subframe, transmission power for PUCCH transmission is set in consideration of the presence or absence of a UL-SCH transmission block associated with the SR subframe. For example, although the transmission power setting method of Expression 17 is used, h (•) can be replaced with Expression 23 in consideration of the presence or absence of the UL-SCH transmission block associated with the SR subframe. The SR subframe refers to a subframe set for SR transmission. The SR subframe is set by an upper layer (eg, RRC) and can be specified by a period / offset.

  FIG. 32 is a diagram illustrating a base station and a terminal that can be applied to an embodiment of the present invention. When the wireless communication system includes a relay, communication is performed between the base station and the relay on the backhaul link, and communication is performed between the relay and the terminal on the access link. Therefore, the base station or terminal in the figure may be replaced with a relay depending on the situation.

  Referring to FIG. 32, the wireless communication system includes a base station (BS) 110 and a terminal (UE) 120. Base station 110 includes a processor 112, a memory 114 and a radio frequency (RF) unit 116. The processor 112 can be configured to implement the procedures and / or methods proposed in the present invention. The memory 114 is connected to the processor 112 and stores various information related to the operation of the processor 112. The RF unit 116 is connected to the processor 112 and transmits and / or receives a radio signal. The terminal 120 includes a processor 122, a memory 124, and an RF unit 126. The processor 122 can be configured to implement the procedures and / or methods proposed in the present invention. The memory 124 is connected to the processor 122 and stores various information related to the operation of the processor 122. The RF unit 126 is connected to the processor 122 and transmits and / or receives a radio signal. Base station 110 and / or terminal 110 may have a single antenna or multiple antennas.

  In the embodiment described above, the constituent elements and features of the present invention are combined in a predetermined form. Each component or feature should be considered optional unless stated otherwise. Each component or feature may be implemented in a form that is not combined with other components or features, or some components and / or features may be combined to form an embodiment of the present invention. The order of operations described in the embodiments of the present invention can be changed. Some configurations or features of one embodiment may be included in another embodiment, and may be replaced with corresponding configurations or features of another embodiment. It is obvious that claims which are not explicitly cited in the claims can be combined to constitute an embodiment, or can be included as new claims by amendment after application.

  In the present specification, an embodiment of the present invention is described centering on a data transmission / reception relationship between a terminal and a base station. Such a transmission / reception relationship is extended in the same / similar manner to signal transmission / reception between the terminal and the relay or between the base station and the relay. The specific operation assumed to be performed by the base station in this specification may be performed by an upper node in some cases. That is, it is apparent that various operations performed for communication with a terminal in a network including a plurality of network nodes including a base station can be executed by the base station or another network node other than the base station. The base station can be replaced with terms such as a fixed station, a Node B, an evolved Node B (eNB), and an access point. Further, the term “terminal” may be used in terms of user equipment (UE), mobile station (MS), mobile subscriber station (MSS), and the like.

  Embodiments according to the present invention can be implemented by various means, for example, hardware, firmware, software, or a combination thereof. When implemented in hardware, one embodiment of the invention includes one or more application specific integrated circuits (ASICs), digital signal processors (DSPs), digital signal processing devices (DSPDs), programmable logic devices (PLDs). ), A field programmable gate array (FPGA), a processor, a controller, a microcontroller, a microprocessor, and the like.

  In the case of implementation by firmware or software, an embodiment of the present invention may be implemented in the form of a module, procedure, function, or the like that performs the functions or operations described above. The SWC can be stored in a memory unit and driven by a processor. The memory unit is provided inside or outside the processor, and can exchange data with the processor by various known means.

  It will be apparent to those skilled in the art that the present invention can be embodied in other specific forms without departing from the characteristics of the present invention. Therefore, the above detailed description should not be construed as limiting in any way, and should be considered exemplary. The scope of the present invention should be determined by reasonable interpretation of the appended claims, and all modifications within the equivalent scope of the present invention are included in the scope of the present invention.

  The present invention is applicable to a terminal, a base station, or other equipment in a wireless mobile communication system. In particular, the present invention is applicable to a method and apparatus for transmitting uplink control information.

Claims (12)

A method of transmitting a physical uplink control channel (PUCCH) signal in a wireless communication system operating in a time division duplex (TDD) mode, comprising:
When the transmission of the hybrid automatic repeat request acknowledgment (HARQ-ACK) is simultaneous with the subframe #n set for the transmission of the schedule request (SR), one or more HARQ-ACK bits and SR bits are set. Generating the PUCCH signal including:
Setting transmit power for the PUCCH signal according to the following equation:

Where n _HARQ is: (i) if a semi-persistent schedule (SPS) release physical downlink control channel (PDCCH) is received in subframe # n-k _m via multiple configured cells , ( the number of the plurality of set via the cell received in subframe # _{n-k m} the one or more transmission blocks) is +1, (ii) the SP S Li lease P DCC H is the If not received in sub-frame # n-k _m via a plurality of the cell set, (the plurality subframe via the configured cell # n-k _m one or more transmission blocks received in a _{number), k m ∈K: {k} 0, k 1, ··· k M-1}, and a _{0 ≦ m ≦ M-1,} n SR , the sub-frame #n uplink Shared channel 1 when there is no transmission block related to the UL (SCH), and 0 when the subframe #n has a transmission block related to the UL-SCH. The method according to claim 1, wherein the transmission power for the PUCCH signal in subframe #n is determined by the following equation.

  The method of claim 1, wherein a size of the one or more HARQ-ACK bits is fixed according to a number of the plurality of configured cells.   The method of claim 1, wherein the SR bits are appended to the end of the one or more HARQ-ACK bits.   The method of claim 1, wherein the one or more HARQ-ACK bits and the SR bits are jointly encoded.   The method of claim 1, wherein the apparatus is set to a PUCCH and Physical Uplink Shared Channel (PUSCH) simultaneous transmission mode. An apparatus configured to transmit a physical uplink control channel (PUCCH) signal in a wireless communication system operating in a time division duplex (TDD) mode,
A radio frequency (RF) unit;
And a processor,
The processor is
When the transmission of the hybrid automatic repeat request acknowledgment (HARQ-ACK) is simultaneous with the subframe #n set for the transmission of the schedule request (SR), one or more HARQ-ACK bits and SR bits are set. Generating said PUCCH signal including:
An apparatus configured to set transmit power for the PUCCH signal according to the following equation:

Where n _HARQ is: (i) if a semi-persistent schedule (SPS) release physical downlink control channel (PDCCH) is received in subframe # n-k _m via multiple configured cells , ( the number of the plurality of set via the cell received in subframe # _{n-k m} the one or more transmission blocks) is +1, (ii) the SP S Li leases P DCCH) is the If not received in sub-frame # n-k _m via a plurality of the cell set, (the plurality subframe via the configured cell # n-k _m one or more transmission blocks received in a _{number), k m ∈K: {k} 0, k 1, ··· k M-1}, and a _{0 ≦ m ≦ M-1,} n SR , the sub-frame #n uplink Shared tea Is 1 when has no transmission block associated with Le (UL-SCH), a 0 when it has a transport block the sub frame #n associated with the UL-SCH. The apparatus of claim 7, wherein transmission power for the PUCCH signal in subframe #n is determined by the following equation:

  The apparatus of claim 7, wherein a size of the one or more HARQ-ACK bits is fixed according to a number of the plurality of configured cells.   The apparatus of claim 7, wherein the SR bit is appended to the end of the one or more HARQ-ACK bits.   The apparatus of claim 7, wherein the one or more HARQ-ACK bits and the SR bits are jointly encoded.   8. The apparatus of claim 7, configured for PUCCH and Physical Uplink Shared Channel (PUSCH) simultaneous transmission mode.

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