JP5645135B2 - Wireless communication system and wireless communication method - Google Patents

Description

  The present invention relates to a wireless communication system and a wireless communication method.

  In recent years, studies are being made to realize high-speed wireless communication of several megabits per second [Mbps] to several gigabits per second [Gbps] in a limited frequency band. Of these, MIMO (Multiple-Input Multiple-Output) communication that can increase the communication capacity in proportion to the increase in the number of antennas used for transmission and reception has attracted attention. In MIMO communication, a plurality of signals are simultaneously communicated using a multipath environment, so that the communication speed in a wireless section can be improved without widening the frequency band.

  On the other hand, in recent years, near field communication represented by RF-ID has been studied, and near field / high speed communication using millimeter wave or UWB (Ultra-Wide-Band) communication has attracted attention. Also, it is possible to apply the MIMO technology to short-range communication, and a short-range ultrahigh-speed wireless relay system using the inside of an obstacle such as a concrete wall as a propagation path has been proposed. For example, Non-Patent Document 1 shows that high-speed communication is possible using MIMO communication even when there is no line-of-sight array antenna due to a wall or the like in the near field. Since MIMO communication does not require a wide frequency band, it is possible to effectively use frequency resources.

  In addition, in the non-patent documents 2 and 3, the inventors of the present application show the basic characteristics of short-range MIMO communication in which the transmission / reception array antenna is closer than the aperture. For example, in Non-Patent Document 2, the optimum element spacing of the array antenna can be obtained by considering the relationship between the spatial correlation characteristics with respect to the distance between the transmitting and receiving array antennas and the signal-to-noise ratio (SNR). It has been shown.

  Here, in Non-Patent Document 2, a study for increasing the channel capacity is performed. In addition to this, signal processing technology in transmission and reception is necessary to realize actual MIMO communication. Therefore, in Non-Patent Document 3, the characteristics of eigenmode transmission (hereinafter referred to as EM-BF) known as the optimum transmission / reception method of MIMO communication and the zero-four known as a method of performing signal processing only on the receiving side. The characteristics of Sing (hereinafter referred to as ZF) are compared. Then, it is shown that the characteristics of the EM-BF and the characteristics of the ZF substantially coincide with each other at the optimum element spacing of the array antenna shown in Non-Patent Document 2.

G. J. Foschini and M. J. Gans, “Capacity when using diversity at transmit and receive sites and the Rayleigh-faded matrix channel is unknown at the transmitter”, Proc. WINLAB Workshop on Wireless Information Network, March 1996. Seki, Nishimori, Honma, Nishikawa, "Short range ultra high-speed relay system", IEICE Technical Report, AP2008-124, November 2008 Honma, Nishimori, Seki, Mizoguchi, “Evaluation of Communication Capacity in Nearby MIMO Communication”, IEICE Technical Report, AP2008-125, November 2008

  In EM-BF and ZF, heavy load signal processing such as inverse matrix calculation and eigenvalue expansion at the digital signal level is required. If short-distance MIMO communication can be realized by signal processing with a smaller load, the manufacturing cost and power consumption of the communication system can be reduced, and the device can be downsized.

  The present invention has been made in view of such circumstances, and an object of the present invention is to provide a wireless communication system and a wireless communication method capable of realizing short-range MIMO communication with signal processing with a smaller load. is there.

The present invention has been made to solve the above-described problems, and a wireless communication system according to an aspect of the present invention includes a first antenna element and a second antenna element included in a first communication device. A wireless communication system in which a first array antenna and a second array antenna including a third antenna element and a fourth antenna element included in a second communication device are arranged, wherein the first communication A distance between the first antenna element and the second antenna element at an interval where the apparatus has a maximum channel capacity with respect to the distance between the first array antenna and the second array antenna. And the second communication device has an interval at which the channel capacity is maximized with respect to the distance between the first array antenna and the second array antenna. , A serial second array antenna distance is selected between the third antenna element and the fourth antenna element, 2 branches the input signal from said third antenna element, the one signal A first weighting means for applying a phase rotation of 90 degrees to the signal and outputting a signal to which the phase rotation is applied and a signal to which the phase rotation is not applied; and a signal input from the fourth antenna element. A second weighting unit that bifurcates the signal, applies a phase rotation of 90 degrees to one of the signals, and outputs a signal with the phase rotation and a signal without the phase rotation; a first decoding means for decoding performs summing the signal phase rotation has been imparted in the output of the phase rotation is not applied signal and said second weighting means among the outputs of the weighting means synthesis, the First weight A second decoding means for decoding performs only adds up the signal phase rotation is not applied among the output of the the phase rotation is imparted signal second weighting means of the output means synthesis, It is characterized by comprising.

  A wireless communication system according to an aspect of the present invention is the above wireless communication system, wherein the second antenna element is a channel in an eigenmode communication method of MIMO communication with respect to a distance from the first antenna element. It is arranged at a position where the capacity is maximized.

  A wireless communication system according to an aspect of the present invention is the above wireless communication system, wherein the second antenna element is a channel capacity in a zero forcing method of MIMO communication with respect to a distance from the first antenna element. It is arranged at a position where is maximum.

A wireless communication system according to an aspect of the present invention is the above-described wireless communication system, in which the first antenna element and the second antenna element are polarized waves in which two signals are orthogonal to each other. The third antenna element and the fourth antenna element receive the orthogonally polarized waves independently for each polarization angle , and the second communication device The first weighting means, the second weighting means, the first decoding means, and the second decoding means are provided for each polarization .

A wireless communication system according to an aspect of the present invention includes a first array antenna including the first to fourth antenna elements included in the first communication device, and fifth to fifth included in the second communication device. And a second array antenna including eight antenna elements, wherein the first communication device is configured to reduce a distance between the first array antenna and the second array antenna. The first array antenna having a distance between the first to fourth antenna elements selected at an interval at which the channel capacity is maximized, and the second communication device includes the first communication antenna. The second array antenna in which the distance between the fifth to eighth antenna elements is selected at an interval that maximizes the channel capacity with respect to the distance between the array antenna and the second array antenna; The fifth to eighth ann 4 branches the respective input signals from the Na element, for each antenna element imparts phase rotation of the two 90 degree branch signals imparts phase rotation of 180 degrees to one another, Weighting means for outputting one signal to which no phase rotation is applied, two signals to which phase rotation of 90 degrees is applied, and one signal to which phase rotation of 180 degrees is applied; Among the signals to be output, the signal input from the fifth antenna element, the signal input from the sixth antenna element and given a phase rotation of 90 degrees, and the signal input from the seventh antenna element 90 and signal phase rotation has been imparted a degree, a first decoding means for phase rotation of 180 degrees is input from the antenna elements of the eighth decodes was synthesized summing the signal added, wherein the weighting means Is output Among the signals, the signal input from the sixth antenna element, the signal input from the fifth antenna element and given a phase rotation of 90 degrees, and the signal input from the eighth antenna element are 90 degrees of the signal phase rotation has been applied, a second decoding means for the seventh phase rotation of 180 degrees is input from the antenna elements is decoded by performing the synthesis summing the signal added, wherein said weighting means Among the signals to be output, the signal input from the seventh antenna element, the signal input from the fifth antenna element and given a phase rotation of 90 degrees, and the signal input from the eighth antenna element 90 A third decoding means for performing decoding by combining the signal to which the phase rotation of the degree is added and the signal input from the sixth antenna element and to which the phase rotation of 180 degrees is added ; Of the signals output by the weighting means, the signal inputted from the eighth antenna element, the signal inputted from the sixth antenna element and given a phase rotation of 90 degrees, and the seventh antenna element And a fourth decoding means for performing decoding by performing a synthesis of adding the signal inputted from 90 and provided with the phase rotation of 90 degrees and the signal inputted from the fifth antenna element and given the phase rotation of 180 degrees; It is characterized by comprising.

  In addition, a wireless communication system according to an aspect of the present invention includes any one or more of the above-described wireless communication systems, and shielding means that electromagnetically shields the plurality of wireless communication systems from each other.

In addition, a wireless communication method according to one embodiment of the present invention includes a first array antenna including a first antenna element and a second antenna element included in a first communication device, and a second communication device. A second array antenna including a third antenna element and a fourth antenna element is disposed, and the first communication device is configured to reduce a distance between the first array antenna and the second array antenna. The first array antenna having a distance between the first antenna element and the second antenna element selected at an interval at which the channel capacity is maximized, and the second communication device includes: The distance between the third antenna element and the fourth antenna element is selected at an interval that maximizes the channel capacity with respect to the distance between the first array antenna and the second array antenna. Said second A wireless communication method of a wireless communication system including the array antenna, the third to 2 branches the input signal from the antenna element imparts a phase rotation of 90 degrees with respect to one signal, phase rotation A first weighting step for outputting a given signal and a signal to which no phase rotation is given; a signal inputted from the fourth antenna element is branched into two , and a phase of 90 degrees with respect to one signal A second weighting step for providing rotation and outputting a signal to which phase rotation is given and a signal to which phase rotation is not given, and a signal to which phase rotation is not given among the outputs of the first weighting step first and decoding step, said first weighting step of phase rotation is decoded by performing the synthesis summing the signal added in the output of said second weighting step with Be provided with a, a second decoding step of phase rotation of an output of the the phase rotation is imparted signal second weighting step decodes was synthesized summing the signals that have not been granted in the output It is characterized by.

  According to the present invention, near field MIMO communication can be realized by signal processing with a smaller load.

It is a block diagram which shows schematic structure of the radio | wireless communications system in the 1st Embodiment of this invention. It is explanatory drawing which shows the example of arrangement | positioning of the antenna element in near field MIMO communication. It is explanatory drawing of the channel capacity | capacitance characteristic in 2x2 short-distance MIMO communication. It is explanatory drawing which shows the relationship between the antenna element space | interval, the phase difference between transmission / reception, and an amplitude ratio at the time of using ZF in short distance MIMO communication demonstrated in FIG. It is explanatory drawing which shows the relationship between the phase difference (theta) _w of a receiving weight, and amplitude ratio ratio in the optimal element space _| interval _dopt determined based on the transmission / reception space _| interval D and the said transmission / reception space _| interval. It is a flowchart which shows the process sequence which determines arrangement | positioning of the antenna element in the radio | wireless communications system of the embodiment. It is a block diagram which shows schematic structure of the radio | wireless communications system in the 2nd Embodiment of this invention. It is a block diagram which shows schematic structure of the radio | wireless communications system in the 3rd Embodiment of this invention. It is explanatory drawing which shows arrangement | positioning of the antenna in the communication apparatus of the embodiment. It is explanatory drawing which shows the weighting synthesis | combination in the weight calculating circuit of the embodiment. It is explanatory drawing which shows the example of arrangement | positioning of the antenna element of the receiving side of the radio | wireless communications system which comprises several pairs of antennas in the 4th Embodiment of this invention.

<First Embodiment>
Embodiments of the present invention will be described below with reference to the drawings.
FIG. 1 is a configuration diagram showing a schematic configuration of a radio communication system according to the first embodiment of the present invention. In FIG. 1, a wireless communication system 1 includes a communication device (first wireless communication device) 100 and a communication device (second wireless communication device) 200. The communication apparatus 100 includes transmission units 111 to 112, an antenna element (first antenna element) 121, and an antenna element (second antenna element) 122. The communication device 200 includes an antenna element (third antenna element) 211, an antenna element (fourth antenna element) 212, a weight calculation circuit 220, and receiving units 251 to 252. The weight calculation circuit 220 includes distributors 221 to 222, 90-degree phase shifters 231 to 232, a synthesizer 241, and a synthesizer 242.

The wireless communication system 1 communicates (transmits and receives) two series of data (series S11 and series S12) from the communication apparatus 100 to the communication apparatus 200 using a 2 × 2 MIMO (2-input 2-output MIMO) communication system. I do.
In the present embodiment, communication from the communication apparatus 100 to the communication apparatus 200 will be described. In addition, the wireless communication system 1 may perform communication from the communication apparatus 200 to the communication apparatus 100. . In this case, various communication methods from the communication device 200 to the communication device 100 can be used. For example, communication from the communication device 200 to the communication device 100 may be performed by a communication method to which the present invention is applied, as in the case of communication from the communication device 100 to the communication device 200, or other communication methods. It may be performed at.

The communication device 100 does not need to perform signal weighting. For this reason, a general communication device in 2 × 2 MIMO short-range communication can be used as the communication device 100.
The transmission unit 111 acquires the data sequence S11 (data thereof), performs processing such as encoding and modulation (modulation from digital data to a baseband signal and modulation to a signal of a transmission frequency), and the like, and performs the data sequence S11. The transmission signal is generated, and the generated transmission signal is output to the antenna element 121. Similarly, the transmission unit 112 acquires data of the data series S12, performs processing such as encoding and modulation, generates a transmission signal of the data series S12, and outputs the generated transmission signal to the antenna element 122.

Here, the data series S11 and the data series S12 may be series independent from each other, or may be series having correlation. The communication apparatus 100 acquires these data series from the outside of the communication apparatus 100 such as a computer connected to the communication apparatus 100, for example.
Various modulation schemes can be used by the transmission unit 111 and the transmission unit 112. For example, the transmission units 111 and 112 may perform modulation using a QPSK (Quadrature Phase-Shift Keying) method, or may perform modulation using a 1024 QAM (Quadrature Amplitude Modulation) method. Furthermore, the transmission units 111 and 112 may perform adaptive modulation that selects a modulation scheme according to the state of the propagation path. However, in near field MIMO communication, since the distance between the transmitting antenna and the receiving antenna is short, it is expected that the state of the propagation path is stable. In such a case, the transmission unit 111 and the transmission unit 112 perform modulation in a fixed modulation scheme, thereby simplifying the circuit configuration, reducing the size and weight of the communication device 100 and reducing the manufacturing cost, and the communication device 100 and the communication device. The amount of communication of control data with 200 can be reduced.

The antenna element 121 wirelessly transmits a transmission signal output from the transmission unit 111. Similarly, the antenna element 122 wirelessly transmits the transmission signal output from the transmission unit 112. Here, the interval between the antenna element 121 and the antenna element 122 is set to an optimum element interval d _opt described later. As will be described later, the optimum element spacing d _opt is a predetermined distance determined according to the distance between the antenna element 121 and the antenna element 211 (a distance at which the channel capacity in the eigenmode transmission method of MIMO communication is maximized, or The distance at which the channel capacity is maximized in the zero forcing method of MIMO communication).

  As will be described later with reference to FIG. 2, the antenna element 121 and the antenna element 122 are arranged on the same plane. Hereinafter, an antenna having a plurality of antenna elements arranged on the same plane is referred to as an array antenna. That is, the antenna element 121 and the antenna element 122 constitute an array antenna.

The communication device 200 extracts each series of data from the signal transmitted from the communication device 100.
Both the antenna element 211 and the antenna element 212 receive the radio signal transmitted from the antenna element 121 and the radio signal transmitted from the antenna element 122 as a radio signal in which both radio signals are combined. The antenna element 211 outputs the received signal to the distributor 221, and the antenna element 212 outputs the received signal to the distributor 222.

Here, the interval between the antenna element 211 and the antenna element 212 is set to an optimum element interval d _opt described later, as with the antenna element 121 and the antenna element 122 described above. The antenna element 211 is disposed at a distance D from the antenna element 121 so as to face the antenna element 121.

The antenna element 212 is disposed at a distance D from the antenna element 122 so as to face the antenna element 122. That is, the antenna element 212 faces the antenna element 122, and the distance between the antenna element 122 and the antenna element 211 is the same as the distance between the antenna element 121 and the antenna element 211. It is disposed at a position equal to the distance between 121 and the antenna element 122.
As in the case of the antenna element 121 and the antenna element 122, the antenna element 211 and the antenna element 212 constitute an array antenna.

The weight calculation circuit 220 extracts a data series by performing phase rotation and synthesis on the signal received by the antenna element 211 and the signal received by the antenna element 212.
The distributor 221 distributes the signal received by the antenna element 211 into two and outputs the signal to the 90-degree phase shifter 231 and the combiner 241. The distributor 222 distributes the signal received by the antenna element 212 into two and outputs the signal to the 90-degree phase shifter 232 and the combiner 242.

  The 90-degree phase shifter 231 applies a phase rotation of 90 degrees to the signal received by the distributor 221 (that is, advances the phase by 90 degrees) and outputs the resultant signal to the combiner 242. The 90-degree phase shifter 232 rotates the phase of the signal output from the distributor 222 by 90 degrees and outputs it to the combiner 241.

The combiner 241 combines the signal output from the distributor 221 and the signal output from the 90-degree phase shifter 232. That is, the combiner 241 combines the signal received by the antenna element 211 and the signal received by the antenna element 212 and rotated by 90 degrees by the 90-degree phase shifter 232.
Signal synthesis here is signal superposition (addition). The combiner 241 generates a signal of the data sequence S11 ′ corresponding to the signal of the data sequence S11 transmitted by the antenna element 121 by the combination. The combiner 241 outputs a signal obtained by combining to the receiving unit 251.

  Here, the distributor 221 and the 90-degree phase shifter 231 constitute the first weighting means in the present invention. That is, the signal input from the antenna element 211 is branched into two by the distributor 221, and the 90-degree phase shifter 231 gives a phase rotation of 90 degrees to a part of the signals, and the phase rotation is given. And a signal to which no phase rotation is applied. Further, the distributor 222 and the 90-degree phase shifter 232 constitute the second weighting means in the present invention. That is, the divider 222 divides the signal input from the antenna element 212 into two, and the 90-degree phase shifter 232 gives a 90-degree phase rotation to a part of the signal and outputs it.

  For example, the combiner 241 uses the distributor in reverse (that is, inputs the signal output from the distributor 221 and the signal output from the 90-degree phase shifter 232 to the output terminal of the distributor, This is realized by taking out a signal from an input terminal of the distributor.

Similarly, the combiner 242 combines the signal output from the distributor 222 and the signal output from the 90-degree phase shifter 231. That is, the combiner 242 combines the signal received by the antenna element 212 and the signal received by the antenna element 211 and subjected to the 90-degree phase shift rotation by the 90-degree phase shifter 231.
The combiner 242 generates a signal of the data sequence S12 ′ corresponding to the signal of the data sequence S12 transmitted by the antenna element 122 by the combination. The combiner 242 outputs the signal obtained by the combining to the receiving unit 252.
The combiner 242 is realized, for example, by using a distributor in reverse.

The receiving unit 251 performs processing such as demodulation and decoding on the signal output from the combiner 241 to generate a data sequence S11 ′ (data thereof). The reception unit 251 outputs the generated data series to the outside of the communication device 200 such as a computer connected to the communication device 200 (reception unit 251).
Here, the synthesizer 241 and the receiving unit 251 constitute the first decoding means in the present invention. That is, the combiner 241 combines the signal to which phase rotation is not given among the outputs of the first weighting means and the signal to which phase rotation is given among the outputs of the second weighting means, and the receiving unit 251 The signal synthesized by the synthesis unit 241 is decoded.

The receiving unit 252 performs processing such as demodulation and decoding on the signal output from the combiner 242 to generate a data series S12 ′. The receiving unit 252 outputs the generated data series to the outside of the communication device 200 such as a computer connected to the communication device 200 (receiving unit 252).
Here, the synthesizer 242 and the receiving unit 252 constitute second decoding means in the present invention. That is, the synthesizer 242 synthesizes the signal to which phase rotation is given out of the output of the first weighting means and the signal to which phase rotation is not given out of the output of the second weighting means, and the receiving unit 252 The signal synthesized by the synthesis unit 242 is decoded.

Next, with reference to FIG. 2 to FIG. 5, the interval between the antenna elements and the reception weight in this embodiment will be described.
FIG. 2 is an explanatory diagram illustrating an arrangement example of antenna elements in short-range MIMO communication.
In the figure, the number of antenna elements on the transmitting side and the number of antenna elements on the receiving side are both M (M is a positive integer satisfying M ≧ 2). These antenna elements ET _j on the transmission side (j is a positive integer of 1 ≦ j ≦ M) are arranged on the plane PT, and antenna elements ER _i on the reception side (i is a positive number of 1 ≦ i ≦ M). (Integer) is arranged on the plane PR.
In the figure, a vertically polarized antenna element is shown, but the scope of application of the present invention is not limited to this. For example, various antenna elements such as horizontally polarized antenna elements can be used in the wireless communication system according to the present invention.

In FIG. 2, the distance between the plane PT and the plane PR is the distance D. Hereinafter, the distance between the plane PT and the plane PR is referred to as “transmission / reception interval”.
Here, the transmission / reception interval D is set to a distance approximately equal to the aperture length of the array antenna. The distance similar to the aperture length of the array antenna here is a distance indicating short-range MIMO communication, and is a distance that cannot be ignored with respect to the distance between the antenna elements with respect to the transmission / reception interval. For example, the transmission / reception interval D is set in a range of 30 to 300 millimeters.
The antenna element interval is the distance d on both the transmission side and the reception side. More specifically, the antenna elements on the transmission side are arranged at equal intervals of distance d both vertically (in the y-axis direction shown in FIG. 2) and horizontally (in the x-axis direction shown in FIG. 2). The antenna elements on the receiving side are arranged at equal intervals of the distance d in both the vertical and horizontal directions so as to face the antenna elements on the transmitting side.

The coordinates of the antenna element ET _j on the transmission side are indicated by Q _j = (x _Tj , y _Tj , 0) using the three-dimensional orthogonal coordinate system shown in FIG. 3, and the coordinates of the antenna element ER _i on the reception side are P _i = When expressed by (x _Ri , y _Ri , D), a vector r _ij from the coordinate Q _j to the coordinate P _i (in the specification, a bold notation indicating a matrix or a vector is omitted. The same applies hereinafter) is expressed by the equation (1 ).

As the coordinates of the antenna element on the transmission side, for example, the center coordinates of the antenna element on the plane PT are used. Similarly, as the coordinates of the antenna element on the receiving side, for example, the center coordinates of the antenna element in the plane PR are used.
Further, the response value h _ij between the antenna elements is expressed by Expression (2).

Here, the vector r _ij is expressed in polar coordinates by combining the angles θ _ij and φ _ij and the distance γ _ij (θ _ij , φ _ij , γ _ij ). As shown in FIG. 2, the angle θ indicates the angle from the positive z-axis direction to the positive y-axis direction, and the angle φ indicates the positive x-axis direction from the positive y-axis direction. Indicates the angle.
The wavelength λ ₀ indicates the wavelength in free space of the radio wave transmitted and received between the antenna elements in FIG. 2, and the frequency k (= 2π / λ ₀ ) indicates the frequency of the radio wave.

The vectors E _T and E _R are functions of the angles θ _ij and φ _ij in the polar coordinate display of the vector r _ij , and indicate the square roots of the gains of the transmitting side antenna element and the receiving side antenna element, respectively. .
Further, the distance γ _ij in the polar coordinate display of the vector r _ij is expressed by Expression (3).

Also, the channel capacity of EM-BF (upper limit of the number of bits that can be transmitted in 1 second and 1 Hz) C _EM-BF [bits per second hertz (bit / s / Hz)] is expressed by equation (4).

Here, P _t represents transmission power, and σ ² represents noise power. Λ _i indicates an eigenvalue obtained by eigenvalue decomposition of the correlation matrix (HH ^H or H ^H H) of the channel matrix (M × M matrix).

Also, the channel capacity C _ZF [bits per second Hertz] of _ZF is expressed by equation (5).

Here, the vector || w _i || represents a column vector of the weight (weighting for each data series in the radio wave transmitted by the antenna element ET _i) due to ZF in the antenna element ET _i on the transmission side.
The reception weight matrix in ZF (weighting when combining the radio waves received by the respective antenna elements on the reception side) is expressed by the following equation.

FIG. 3 is an explanatory diagram of channel capacity characteristics in 2 × 2 short-range MIMO communication.
As shown in FIG. 5A, here, the number of antenna elements M = 2 on both the transmission and reception sides, and the transmission / reception interval D is set to 120 millimeters. The polarization of each antenna element is vertical polarization.

In such short-range MIMO communication, the relationship between the antenna element interval and the channel capacity is as shown in FIG. Here, the antenna element interval is shown as a relative distance to the wavelength λ ₀ . A line L311 indicates the channel capacity in EM-BF calculated based on Expression (4), and a line L312 indicates the channel capacity in ZF calculated based on Expression (5).
As shown in FIG. 5B, there is an element spacing (hereinafter referred to as “optimum element spacing”) that maximizes the channel capacity in both EM-BF and ZF. Further, in EM-BF and ZF, the channel capacity is maximized at the same element spacing (d = 1λ).

  In addition, the eigenvalue distribution in the short-range MIMO communication is as shown in FIG. In FIG. 5C, at the optimum element spacing d = 1λ, both the first eigenvalue and the second eigenvalue are the same value as the signal-to-noise ratio. That is, the optimum condition for MIMO is satisfied at the optimum element spacing d = 1λ.

FIG. 4 is an explanatory diagram showing the relationship between the antenna element spacing and the phase difference and amplitude ratio between transmission and reception when ZF is used in the short-range MIMO communication described in FIG.
Here, the above-described channel matrix H in 2 × 2 MIMO communication is expressed as in Expression (7).

The element h _ij (where i and j are positive integers of 2 or less, respectively) indicates the phase and amplitude change rate of the propagation path from the transmitting-side antenna element ET _j to the receiving-side antenna element ET _i in a complex number expression, for example. Show.
Further, the above reception weight matrix (matrix W) in 2 × 2 MIMO communication is expressed as in Expression (8).

An element w _ij (i, j is a positive integer of 2 or less) indicates a weight given when a signal received by the receiving-side antenna element ER _j is supplied to the i-th receiving circuit. Here, the i-th receiving circuit is a circuit that generates a data series corresponding to the i-th data series (signal thereof) transmitted by the transmitting-side antenna element ET _i . That is, the element w _ij indicates a weight given to the signal received by the antenna element ER _j in order to extract the i-th data series.
In FIG. 4A, a line L411 indicates the channel phase difference θ _H = tan ⁻¹ (h ₁₂ / h ₁₁ ). A line L412 indicates the phase difference θ _w = tan ⁻¹ (w ₁₂ / w ₁₁ ) of the reception weight.

Here, at the optimum element interval d = 1λ ₀ shown in FIG. 3, the phase difference between the channel phase difference θ _H and the reception weight phase difference θ _w is 180 degrees. In FIG. 3, the channel capacity is maximal at several antenna element intervals including the optimum element interval d = 1λ ₀ while oscillating. In FIG. 4, the channel phase difference θ _H at these antenna element intervals. phase difference between the phase difference θ _w of the reception weight has become a 180 degrees and.
The phase difference theta _w reception weights at the optimum element spacing d = 1 [lambda ₀ is almost 90 degrees.
In FIG. 4B, a line L421 indicates an amplitude ratio ratio = | w ₁₁ | / | w ₁₂ |. As shown in the figure, the amplitude ratio ratio at the optimum element spacing d = 1 [lambda ₀ is of the order of 1.1.

Figure 5 is an explanatory diagram showing the transmission and reception interval D, the optimal element spacing d _opt determined based on the reception interval, and the phase difference theta _w of reception weight, the relationship between the amplitude ratio ratio. As shown in FIG. 6 (a), to the extent that reception interval D is from 30 to 300 mm, the antenna element spacing d, in the case of setting the optimal element spacing d _opt, and the phase difference theta _w of receive weights, amplitude The ratio ratio is shown in FIG.
Note that the optimum element interval d _opt changes according to the transmission / reception interval D, as shown in the equations (1) and (2). The relationship between the transmission / reception interval D and the optimum element interval d _opt is as shown in Table 1.

5, a line L511 indicates a phase difference theta _w of receive weights, the line L512 indicates the amplitude ratio ratio.
Here, the phase difference theta _w of receive weights indicated by line L511, shows about 90 degrees, a substantially constant value for each value of the reception interval D.
That is, as shown in the equations (1) and (2), the optimum element interval d _opt changes according to the transmission / reception interval D, but the phase difference θ _w of the reception weight at the optimum element interval d _opt is substantially constant. It is the value of. Note that the value of the amplitude ratio ratio is close to 1 as the transmission / reception interval D increases.

According to the phase difference theta _w reception weights indicated by line L511, the antenna element spacing d is in a state which is optimum element spacing d _opt calculated based on the equation (2), neglecting the ratio of the amplitude For example, the phase difference between the antenna elements on the receiving side may be 90 degrees.
That is, in the state where the antenna element interval d is the optimum element interval d _opt , the path length from the antenna element 121 to the antenna element 212 is a quarter wavelength than the path length from the antenna element 121 to the antenna element 211. (Phase difference 90 degrees) becomes longer. Similarly, the path length from the antenna element 122 to the antenna element 211 is about a quarter wavelength longer than the path length from the antenna element 122 to the antenna element 212.

Thus, regardless of the distance between the transmission antenna and the reception antenna, the reception weight in ZF is substantially constant at the optimum element spacing at which the channel capacity is maximized.
Therefore, in communication apparatus 200 (FIG. 1), combiner 241 combines the signal received by antenna element 211 and the signal obtained by rotating the signal received by antenna element 212 by 90 degrees. The combiner 242 combines the signal received by the antenna element 212 and the signal obtained by rotating the signal received by the antenna element 211 by 90 degrees. That is, the synthesizer 241 and the synthesizer 242 combine with a received signal reception weight phase difference of 90 degrees.
Here, the reception weight matrix W _analog in the communication apparatus 200 is expressed by Expression (9).

  On the other hand, when the transmission / reception interval D = 120 millimeters, the reception weight matrix by ZF in 2 × 2 short-range MIMO communication is expressed by Expression (10).

In equation (10), normalization is performed so that the value of the diagonal term is 1.
Here, when Expression (9) is compared with Expression (10), the values of the diagonal terms are all “1” and are the same. In addition, in the off-diagonal term of Expression (10), the magnitude of the value of the imaginary part “0.8879” is much larger than the magnitude of the value of the real part “0.0415”. The value of the division is dominant. Therefore, it can be said that the value of the off-diagonal term in Equation (10) is equivalent to the value “j” of the off-diagonal term in Equation (9), and Equation (10) is also equivalent to Equation (9) in the entire matrix. I can say that.

Thus, the reception weight matrix equivalent to that in the case of ZF can be obtained by the configuration shown in FIG. Therefore, in the radio communication system 1, the same channel capacity as in the case of ZF can be obtained.
It should be noted that the value of the off-diagonal term differs between Equation (9) and Equation (10), as shown in FIG. 4, while the amplitude ratio ratio is about 1.1, while the weight according to the present invention is This is because this is ignored.

Next, a method for determining the arrangement of antenna elements will be described with reference to FIG.
FIG. 6 is a flowchart illustrating a processing procedure for determining the arrangement of antenna elements in the wireless communication system 1. The process is performed by, for example, a user of the wireless communication system 1.

First, the transmission / reception interval D in the environment where the wireless communication system 1 is used is determined (step S101). For example, when antenna elements are arranged on both surfaces of a building wall and communication is performed through the wall, the thickness of the wall is set as the transmission / reception interval D.
Next, using the model of FIG. 2 and equations (2) to (5), the relationship between the antenna element interval d and the channel capacity C _{ZF of ZF} is obtained (step S102). For example, the channel capacity C _ZF is calculated for several antenna element intervals d, and a graph showing the relationship between the antenna element intervals and the channel capacity is generated as shown in FIG.

Then, based on the relationship between the antenna element spacing d and the channel capacity C _{ZF of ZF} , the optimum element spacing d _opt that maximizes the channel capacity is determined (step S103). For example, the antenna element spacing that maximizes the channel capacity in the graph generated in step S102 is the optimum element spacing _dopt .
Thereafter, the processing in the figure is ended, antennas are arranged at the obtained optimum element spacing d _opt , and communication using the wireless communication system 1 is performed.

As shown in FIG. 3B, the optimum element spacing in ZF matches the optimum element spacing in EM-BF. Therefore, in step S102, instead of the relationship between the antenna element interval d and the ZF channel capacitance C _ZF , the relationship between the antenna element interval d and the EM-BF channel capacitance C _DM-BF may be obtained. Good. Again, in step S103, to determine the optimal element spacing d _opt maximizing the channel capacity C _DM-BF.

  As described above, in the weight calculation circuit 220 (FIG. 1), the distributors 211 and 212 that distribute the reception signal, the 90-degree phase shifters 231 and 232 that rotate the phase of the distributed reception signal by 90 degrees, and the reception Weighting in short-range MIMO communication can be performed with a very simple configuration including synthesizers 241 and 242 that synthesize a signal and a phase-shifted signal.

  The difference between the amplitude in equation (9) and the amplitude in equation (10) is 1 decibel (dB) or less, and the difference between the two can be made substantially the same by adjusting the length of the cable line. It is. Thus, in the wireless communication system 1, near field MIMO communication can be realized by signal processing with a smaller load. Thereby, the manufacturing cost and power consumption of the wireless communication system can be reduced, and the apparatus can be downsized.

In the configuration of FIG. 1, a weight calculation circuit is configured on the reception side. However, this circuit is provided on the transmission side, and the antenna element and the reception unit are directly connected to the reception side as in the transmission side of FIG. It is good also as a structure to be.
Specifically, the signal output from the transmission unit 111 (data series S11) is transmitted through the antenna element 121 after being rotated by 90 degrees, and the signal output from the transmission unit 111 is not rotated in phase. Is transmitted from the antenna element 122. As a result, in the signal received by the antenna element 211, the phase of the signal of the data series S11 transmitted by the antenna element 121 and the signal of the data series S11 transmitted by the antenna element 122 coincide with each other and strengthen each other. Therefore, the data sequence S11 ′ corresponding to the data sequence S11 can be extracted by outputting a signal received by the antenna element 211 to the reception unit 251.
Similarly, the signal (data series S12) output from the transmission unit 112 is rotated by 90 degrees and transmitted from the antenna element 122, and the signal output from the transmission unit 112 is transmitted to the antenna without phase rotation. Transmit from element 121. As a result, in the signal received by the antenna element 212, the phase of the signal of the data series S12 transmitted by the antenna element 121 and the signal of the data series S12 transmitted by the antenna element 122 match each other and strengthen each other. Therefore, the data sequence S12 ′ corresponding to the data sequence S12 can be extracted by outputting a signal received by the antenna element 212 to the receiving unit 252.
In this way, the weight calculation circuit only needs to be included in either the transmission-side communication device or the reception-side communication device. Therefore, an apparatus with a simpler configuration that does not include a weight calculation circuit can be used as the other communication apparatus.

<Second Embodiment>
In the wireless communication system 1 according to the first embodiment, the antenna elements are arranged at different positions. However, antenna elements that transmit and receive mutually orthogonal polarized waves may be arranged at the same position. In the second embodiment, a radio communication system including such an antenna element will be described.

  FIG. 7 is a configuration diagram illustrating a schematic configuration of a wireless communication system according to the second embodiment of the present invention. In FIG. 1, the wireless communication system 2 includes a communication device (first wireless communication device) 300 and a communication device (second wireless communication device) 400. The communication apparatus 300 includes transmission units 311 to 314 and antenna elements 321 to 324. The communication apparatus 400 includes antenna elements 411 to 414, a weight calculation circuit 420, and receiving units 451 to 454. The weight calculation circuit 420 includes distributors 421 to 424, 90-degree phase shifters (phase shift units) 431 to 434, and combiners (combining units) 441 to 444.

Similarly to the transmission units 111 to 112, the transmission units 311 to 314 acquire the data sequences S21 to S24, respectively, perform processing such as encoding and modulation, generate transmission signals of the data sequences S21 to S24, and generate the generated transmissions. The signal is output to the antenna elements 321 to 324.
The antenna elements 321 to 324 wirelessly transmit transmission signals output from the transmission units 311 to 314. Details will be described later.

The antenna elements 411 to 424 receive the signals transmitted from the antenna elements 321 to 324 and output the signals to the distributors 421 to 424, respectively. Details will be described later.
The distributors 421 to 424 distribute and output the signals output from the antenna elements 411 to 424, similarly to the distributors 221 to 222.
The 90-degree phase shifters 431 to 434 perform 90-degree phase rotation on the signals output from the distributors 421 to 424 in the same manner as the 90-degree phase shifters 231 to 232.

The combiners 441 to 444 synthesize the reception signal that has not been phase rotated and the reception signal that has been phase rotated by 90 degrees, and output the combined signals to the reception units 451 to 254, as with the combiners 241 to 144.
Similarly to the receiving units 251 to 152, the receiving units 451 to 254 perform processing such as demodulation and decoding on the signal output from the combiner 441, and generate data sequences S21 ′ to S24 ′ (data thereof). To do.

Here, the antenna element 321 and the antenna element 323 are arranged with their centers aligned (that is, at the positions where the coordinates described in FIG. 2 are the same) to form the first antenna element, and two signals are transmitted. Transmit with polarized waves orthogonal to each other. That is, the polarization (radio wave) transmitted by the antenna element 321 and the polarization transmitted by the antenna element 323 are orthogonal to each other.
Similarly, antenna element 322 and antenna element 324 are arranged with their centers aligned to form a second antenna element, and transmit two signals with mutually orthogonal polarizations. That is, the polarization transmitted by the antenna element 322 and the polarization transmitted by the antenna element 324 are orthogonal to each other.
The antenna elements 321 to 324 form an array antenna. That is, the antenna elements 321 to 324 are arranged on the same plane.

Here, the polarization transmitted by the antenna element 322 has the same inclination as the polarization transmitted by the antenna element 121. The polarization transmitted by the antenna element 324 has the same inclination as the polarization transmitted by the antenna element 323. More specifically, the antenna element 121 and the antenna element 122 are installed in the vertical direction (the y-axis direction shown in FIG. 2) and transmit vertically polarized waves. The antenna element 323 and the antenna element 324 are installed in the horizontal direction (the x-axis direction shown in FIG. 2) and transmit horizontally polarized waves.
However, the application range of the present invention is not limited to vertical polarization and horizontal polarization, and the polarization transmitted by the antenna element 321 and the antenna element 322 and the polarization transmitted by the antenna element 323 and the antenna element 324 are mutually different. What is necessary is just to be orthogonal.

  On the receiving side, the antenna element 411 and the antenna element 413 are arranged with their centers aligned to form a third antenna element, and the orthogonally polarized waves transmitted from the antenna elements 321 to 324 are converted into polarized waves. Receive independently for each angle. More specifically, the antenna element 411 faces the antenna element 321 and is arranged in the vertical direction in the same manner as the antenna element 321 at the transmission / reception interval D, and the vertically polarized wave transmitted by the antenna element 121 and the antenna element 122 are transmitted. Receive the vertically polarized wave transmitted. Further, the antenna element 413 is disposed in the lateral direction in the same manner as the antenna element 323 at the transmission / reception interval D so as to face the antenna element 323, and the horizontal polarization transmitted by the antenna element 323 and the horizontal element transmitted by the antenna element 324 Receive polarization.

Further, the antenna element 412 and the antenna element 414 are arranged with their centers aligned to constitute a fourth antenna element, and the orthogonally polarized waves transmitted from the antenna elements 321 to 324 are converted for each angle of the polarization. Receive independently. More specifically, the antenna element 412 faces the antenna element 322 and is arranged in the vertical direction in the same manner as the antenna element 322 at the transmission / reception interval D, and the vertically polarized wave transmitted by the antenna element 121 and the antenna element 122 are transmitted. Receive the vertically polarized wave transmitted. The antenna element 414 faces the antenna element 324 and is disposed in the horizontal direction in the same manner as the antenna element 324 at the transmission / reception interval D, and the horizontal polarization transmitted by the antenna element 323 and the horizontal element transmitted by the antenna element 324 are arranged. Receive polarization.
The antenna elements 411 to 414 form an array antenna. That is, the antenna elements 411 to 414 are arranged on the same plane.

And these 1st-4th antenna elements are arrange _| positioned by the transmission / reception space _| interval D and the optimal element space _| interval _dopt similarly to the 1st-4th antenna element in 1st Embodiment. That is, the distance between the first antenna element and the second antenna element and the distance between the third antenna element and the fourth antenna element are the optimum element distance _dopt . Further, the distance between the first antenna element and the third antenna element and the distance between the second antenna element and the fourth antenna element are the transmission / reception distance D.

  Here, the inventors of the present application can completely eliminate the correlation between orthogonally polarized waves (for example, vertically polarized waves and horizontally polarized waves, or +45 degree polarized waves) in short-range MIMO communication. (For example, see Nishimori, Seki, Honma, Hiraga, Mizoguchi, “Study on communication methods suitable for short-range MIMO communication”, IEICE Tech. Report, AP2009-83, September 2009).

  Using this property, the wireless communication system 2 transmits and receives four data sequences using two orthogonal polarizations. In other words, the wireless communication system 2 includes a 2 × 2 short-range MIMO communication system using vertical polarization and a 2 × 2 short-range MIMO communication system using horizontal polarization. By transmitting and receiving two data sequences in each short-range MIMO communication system, four data sequences (S21 to S24) are transmitted and received.

  In this way, by using polarized waves that are orthogonal to each other, the wireless communication system 2 can perform communication of twice as many data sequences as the wireless communication system 1 and is necessary for the arrangement of antenna elements in the wireless communication system 2. Such a region can be the same as a necessary region in the wireless communication system 1.

<Third Embodiment>
The application range of the present invention is not limited to 2 × 2 MIMO communication. In the third embodiment, a case where the present invention is applied to 4 × 4 MIMO communication will be described.
FIG. 8 is a configuration diagram illustrating a schematic configuration of a wireless communication system according to the third embodiment of the present invention. In the figure, the wireless communication system 3 includes a communication device (first wireless communication device) 500 and a communication device (second wireless communication device) 600. Communication apparatus 500 includes transmission units 511 to 514 and antenna elements 521 to 524 (first antenna element to fourth antenna element). The communication apparatus 600 includes antenna elements 611 to 614 (fifth antenna element to eighth antenna element), a weight calculation circuit 620, and receiving units 651 to 654.

Similar to the transmission units 111 to 112, the transmission units 511 to 514 respectively acquire the data sequences S31 to S34, perform processing such as encoding and modulation, generate transmission signals of the data sequences S31 to S34, and generate the generated transmissions. The signal is output to the antenna elements 521 to 524.
Similarly to the antenna elements 121 to 122, the antenna elements 521 to 524 wirelessly transmit the transmission signals output from the transmission units 311 to 314.

Similarly to antenna elements 211 to 212, antenna elements 611 to 624 receive signals transmitted from antenna elements 521 to 524 and output the signals to weight calculation circuit 620, respectively.
The weight calculation circuit 620 weights and synthesizes the signals output from the antenna elements 411 to 624 and outputs the combined signals to the receiving units 651 to 654. Details will be described later.
Similarly to the receiving units 251 to 152, the receiving units 451 to 254 perform processing such as demodulation and decoding on the signal output from the combiner 441, and generate data sequences S31 ′ to S34 ′ (data thereof). To do.

FIG. 9 is an explanatory diagram showing the arrangement of antennas in the communication apparatus 600.
Here, as described in FIG. 2, the antenna elements 521 to 524 and the antenna elements 211 to 614 are arranged to face each other on the transmission side and the reception side at the transmission / reception interval D and the optimum element interval d _opt . .
The weight calculation circuit 620 includes distributors 621 to 624 and distributes reception signals output from the antenna elements 211 to 614 into four.

FIG. 10 is an explanatory diagram showing weighted synthesis in the weight calculation circuit 620.
The weight calculation circuit 620 includes 90-degree phase shifters 631a to 637b and 180-degree phase shifters 632 to 638, and performs phase rotation on signals output from the distributors 621 to 624.
Furthermore, the weight calculation circuit 620 includes synthesizers 641 to 644, and synthesizes the signals output from the antenna elements 211 to 614 and the phase rotated signals.

  Here, the reception weight matrix obtained by the weight calculation circuit 620 is expressed by Equation (11).

  On the other hand, the reception weight matrix obtained by ZF in the 4 × 4 short-range MIMO communication is as shown in Expression (12).

In the equation (12), the diagonal term value “1” is the same as the diagonal term value “1” in the equation (11). In addition, the value “−0.09 + 0.89j” of the elements w ₁₂ , w ₁₃ , w ₂₁ , w ₂₄ , w ₃₁ , w ₃₄ , w _42, and w _{43 in} the expression (12) is the magnitude of the value of the imaginary part “0.89” is very large with respect to the value “0.09” of the real part, and the value of the imaginary part is dominant. Therefore, the values of these elements are expressed by the equation (11). ) Is equivalent to the value “j” of each corresponding element. In addition, the value “−0.78−0.04j” of the elements w ₁₄ , w ₂₃ , w ₃₂ , and w ₄₁ in Expression (12) is the real part value “0.78” is the imaginary part. It is very large with respect to the value size “0.04”, and the value of the real part is dominant. Therefore, the value of these elements is the value “−” of each corresponding element in the equation (11). 1 ”. From the above, it can be said that the expression (11) is equivalent to the expression (12) in the entire matrix.

Thus, the reception weight matrix equivalent to that in the case of ZF can be obtained by the configuration shown in FIG. Therefore, the wireless communication system 3 can obtain the same channel capacity as in the case of ZF.
In the equation (12), the amplitude ratio is 1.14 to 1.27. However, in the equation (11), the amplitude ratio is ignored as in the case of the equation (9).

  As described above, in the weight calculation circuit 620, as in the case of the weight calculation circuit 220, weighting in short-range MIMO communication can be performed with a very simple configuration including a distributor, a phase shifter, and a combiner. it can.

<Fourth Embodiment>
Note that the wireless communication system may include a plurality of pairs of antennas.
FIG. 11 is an explanatory diagram illustrating an arrangement example of antenna elements on the reception side in a wireless communication system including a plurality of pairs of antennas.

In the figure, three sets of receiving side antenna elements 711a to 711d, 712a to 712d, and 713a to 713d included in the wireless communication system 4 are shown. The wireless communication system 4 includes three systems of wireless communication systems equivalent to the wireless communication system 3 shown in FIG. The shield plates 791 to 793 are electromagnetic shields that divide the antenna included in the wireless communication system 4 for each system.
The weight calculation circuit 731 includes two 90-degree phase shifters 741a and 741b, an 18-degree phase shifter 751, and a synthesizer 761, and a signal received by any one of the antenna elements 711a to 711d. (No phase rotation is applied), a signal obtained by applying 90 degree phase rotation to the signal received by the other two, and a signal obtained by applying 180 degree phase rotation to the signal received by the other two .
Similarly to the receiving unit 651 (FIG. 8), the receiving unit 771 performs processing such as demodulation and decoding on the signal output from the combiner 761.

The antenna elements 711a to 711d are reception-side antenna elements equivalent to the antenna elements 611 to 614 in FIG. 8, and are arranged on the same plane with the optimum element interval d _opt in the same manner as the antenna elements 611 to 614. Configure the antenna. As in the case of the wireless communication system 3, the antenna elements on the transmission side are arranged facing the antenna elements 711a to 711d at a transmission / reception interval D as described with reference to FIG. Also, as in FIG. 9, the antenna element spacing is the optimum element spacing d _opt on both the transmission side and the reception side.

  Moreover, the one-system radio | wireless communications system containing the antenna elements 711a-711d has the structure similar to having demonstrated in FIG. That is, one different transmission unit is connected to each of the antenna elements on the transmission side, and four antenna elements 711a to 711d on the reception side are connected via the weight calculation circuit (the number of antenna elements on the reception side). The same number of receivers).

  The weight calculation circuit to which the antenna elements 711a to 711d are connected may be the same as that of the wireless communication system 3. Alternatively, as shown in FIG. 11, the antenna elements 711 a to 711 d may be connected to the weight calculation circuit 731 via the matrix switch 721.

  In the configuration shown in FIG. 11, the matrix switch 721 switches the connection relationship between the antenna elements 711 a to 711 d and the weight calculation circuit 731 and has the same connection and data series as the connection that outputs the data series S31 ′ shown in FIG. A connection similar to the connection outputting S32 ′, a connection similar to the connection outputting data series S33 ′, and a connection similar to the connection outputting data series S34 ′ are generated in order. The matrix switch 721 switches this series of connections within one data transmission time.

  As a result, in the configuration shown in FIG. 11, one weight calculation circuit and one receiving unit sequentially acquire data of four data series. Then, for example, four data series are extracted (separated) by a computer connected to the wireless communication system 4.

  Also in the antenna elements 712a to 712d, a one-system radio communication system is configured as in the case of the antenna elements 711a to 711d. In addition, in the antenna elements 713a to 713d, a single-system wireless communication system is configured as in the case of the antenna elements 711a to 711d. And the electromagnetic wave output in a certain system | strain is interrupted | blocked electromagnetically for every system | strain by the shield plates 791-793 so that it may not leak to another system | strain.

  As described above, by arranging a plurality of wireless communication systems to be electromagnetically shielded from each other, a number of data series corresponding to the number of wireless communication systems can be communicated. For example, the wireless communication system 4 includes three wireless communication systems and can communicate three times the amount of data as the wireless communication system 3.

  The embodiment of the present invention has been described in detail with reference to the drawings. However, the specific configuration is not limited to this embodiment, and includes design changes and the like within a scope not departing from the gist of the present invention.

1, 2, 3 Wireless communication system 100, 200, 300, 400, 500, 600 Communication device 111-112, 311-314, 511-514 Transmitter 121-122, 211-212, 321-324, 411-414, 521 to 524, 611 to 614 Antenna element 220, 420, 620 Weight calculation circuit 221 to 222, 421 to 424, 621 to 624 Distributor 231 to 232, 431 to 434, 631a to 637b 90 degree phase shifter 632 to 638 180 Phase shifters 241-242, 441-444, 641-644 Synthesizers 251-252, 451-454, 651-654 Receiver

Claims (7)

A first array antenna including a first antenna element and a second antenna element included in the first communication device, and a third antenna element and a fourth antenna element included in the second communication device. Including a second array antenna including a wireless communication system,
In the first communication device, the first antenna element and the second antenna element are spaced at an interval where the channel capacity is maximum with respect to the distance between the first array antenna and the second array antenna. Comprising the first array antenna with a selected distance between and
The second communication device is
The distance between the third antenna element and the fourth antenna element is selected at an interval that maximizes the channel capacity with respect to the distance between the first array antenna and the second array antenna. Said second array antenna;
The third is 2 branches the input signal from the antenna element imparts a phase rotation of 90 degrees with respect to one signal output and a signal signal and the phase rotation phase rotation has been imparted is not added First weighting means for
The fourth is 2 branches the input signal from the antenna element imparts a phase rotation of 90 degrees with respect to one signal output and a signal signal and the phase rotation phase rotation has been imparted is not added Second weighting means for:
First decoding of decoding performed synthetic summing the signal phase rotation has been imparted in the output of the phase rotation is not applied signal and said second weighting means among the outputs of said first weighting means Means,
Second decoding of decoding performed synthetic summing the signal phase rotation is not applied among the output of the signal phase rotation has been imparted second weighting means among the outputs of said first weighting means And a wireless communication system.   2. The radio according to claim 1, wherein the second antenna element is arranged at a position where a channel capacity in the eigenmode communication method of MIMO communication is maximized with respect to a distance from the first antenna element. Communications system.   2. The wireless communication according to claim 1, wherein the second antenna element is arranged at a position where a channel capacity in a zero forcing method of MIMO communication is maximized with respect to a distance from the first antenna element. system. The first antenna element and the second antenna element each transmit two signals with mutually orthogonal polarizations,
The third antenna element and the fourth antenna element receive the polarized waves orthogonal to each other independently for each polarization angle ,
The second communication apparatus includes the first weighting unit, the second weighting unit, the first decoding unit, and the second decoding unit for each polarization. The wireless communication system according to any one of 1 to 3. A second array antenna including a first array antenna including first to fourth antenna elements included in the first communication device; and a fifth to eighth antenna element included in the second communication device; Is a wireless communication system in which
The first communication device has a distance between the first to fourth antenna elements at an interval at which a channel capacity is maximized with respect to a distance between the first array antenna and the second array antenna. Comprising the selected first array antenna,
The second communication device is
The distance between the fifth to eighth antenna elements is selected at an interval that maximizes the channel capacity with respect to the distance between the first array antenna and the second array antenna. An array antenna,
Each of the signals inputted from the fifth to eighth antenna elements is branched into four , and for each antenna element, 90 degrees of phase rotation is given to two of the branched signals and 180 degrees to the other one . weighting the grant phase rotation, and outputs one signal and the phase rotation is not applied, the 90-degree and two signal phase rotation has been imparted, and one signal phase rotation has been imparted in 180 degrees Means,
Of the signals output from the weighting means, the signal input from the fifth antenna element, the signal input from the sixth antenna element and given a phase rotation of 90 degrees, and the seventh antenna element And a first decoding means for decoding by performing a synthesis of adding the signal inputted from 90 and given the phase rotation of 90 degrees and the signal inputted from the eighth antenna element and given the phase rotation of 180 degrees ,
Of the signals output from the weighting means, a signal input from the sixth antenna element, a signal input from the fifth antenna element and given a phase rotation of 90 degrees, and the eighth antenna element And a second decoding means for decoding by performing a synthesis of adding the signal input from the second phase and having the phase rotation of 90 degrees added thereto and the signal input from the seventh antenna element and having the phase rotation of 180 degrees added thereto; ,
Of the signals output from the weighting means, the signal input from the seventh antenna element, the signal input from the fifth antenna element and given a phase rotation of 90 degrees, and the eighth antenna element And a third decoding means for decoding by performing a synthesis of adding the signal input from the signal to which the phase rotation of 90 degrees is applied and the signal input from the sixth antenna element to which the phase rotation of 180 degrees is applied; ,
Of the signals output from the weighting means, the signal input from the eighth antenna element, the signal input from the sixth antenna element and given a phase rotation of 90 degrees, and the seventh antenna element And a fourth decoding means for performing decoding by performing a synthesis of adding the signal inputted from 90 and provided with the phase rotation of 90 degrees and the signal inputted from the fifth antenna element and given the phase rotation of 180 degrees; A wireless communication system comprising: A plurality of wireless communication systems according to any one of claims 1 to 5;
Shielding means for electromagnetically shielding the plurality of wireless communication systems from each other. A first array antenna including a first antenna element and a second antenna element included in the first communication device, and a third antenna element and a fourth antenna element included in the second communication device. Including a second array antenna including,
In the first communication device, the first antenna element and the second antenna element are spaced at a maximum channel capacity with respect to a distance between the first array antenna and the second array antenna. Comprising the first array antenna with a selected distance between and
The second communication device is configured such that the third antenna element and the fourth antenna element are spaced apart from each other at a maximum channel capacity with respect to the distance between the first array antenna and the second array antenna. A wireless communication method of a wireless communication system comprising the second array antenna with a selected distance between
The third is 2 branches the input signal from the antenna element imparts a phase rotation of 90 degrees with respect to one signal output and a signal signal and the phase rotation phase rotation has been imparted is not added A first weighting step,
The fourth is 2 branches the input signal from the antenna element imparts a phase rotation of 90 degrees with respect to one signal output and a signal signal and the phase rotation phase rotation has been imparted is not added A second weighting step,
First decoding of decoding performed synthetic summing the signal phase rotation has been imparted among the output of the first weighting the second weighted steps and signal phase rotation is not applied among the output of step Steps,
Second decoding of decoding performed synthetic summing the signal phase rotation is not applied among the output of said second weighting step and phase rotation has been imparted signal among outputs of said first weighting step A wireless communication method comprising the steps of:

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