JP5470677B2 - Method for detecting fundamental wave component of single-phase AC signal - Google Patents

Description

Single-phase AC power system interconnection power converter, uninterruptible power supply, power harmonic suppression device, single-phase transformer inrush current prevention device, special charger, power supply synchronous detection device, etc. The frequency and phase of the component are the most basic information, and this detection is required. The present invention relates to a method for instantaneously detecting the frequency and phase of a fundamental wave component of a single-phase AC signal useful for these devices.

Prior art documents relevant to the present invention include those described below.
(1) Shinnaka Shinji: “Power conversion apparatus using the same method as the phase detection method for single-phase AC signals”, Japanese Patent Laid-Open No. 2006-129681 (2004-10)
(2) Toshihisa Shimizu and Makoto Saito: “Control Circuit of Semiconductor Power Converter”, Japanese Patent Laid-Open No. 2003-143860 (2001-11)
(3) L. N. Arruda, B.I. J. et al. C. Filho, S .; M.M. Silva, S.M. R. Silva, and A.A. S. A. C. Diniz: “Wide Bandwidth Single and Three-Phase PLL Structures for Grid-Tied PV Systems”, Record of the 28th IEEE Photovoltaic Spect. 1660-1663 (2000)
(4) S.M. M.M. Silva, L.M. N. Arruda, and B.A. J. et al. C. Filho: “Wide Bandwidth Single and Three-Phase PLL Structures for Utility Connected Systems”, CD-Proc. of 9th European Conference on Power Electronics and Applications (EPE 2001) (2001-8)
(5) L.L. N. Arruda, S .; M.M. Silva, and B.M. J. et al. C. Filho: “PLL Structures for Utility Connected Systems”, Conference Record of the 2001, IEEE Industry Applications Conf., 36th IAS Ane. 4, pp. 2655-2660 (2001-9)
(6) L. M.M. Silva, B.M. M.M. Loopes, B.M. J. et al. C. Filho, R.A. P. Campana, and W.C. C. Boventura: “Performance Evaluation of PLL, Algorithms for Singles, Phase Grid, Connected Systems, and Conference Record of the 2004.” 4, pp. 2259-2263 (2004-10)
(7) M.M. Ciobotaru, R.A. Teodorescu, and F.M. Braabjerg: “Improved PLL structures for single-phase grid inverters”, CD-Proc. of International Conference on Power Electronics and Intelligent Control for Energy Conservation (PELINCEC 2005) (2005-10)
(8) M.M. Ciobotaru, R.A. Teodorescu, and F.M. Braabjerg: “A New Single-Phase PLL Structures Based on Second Order Generalized Integrator”, CD-Proc. of 37th IEEE Power Electronics Specialties Conference (PESC 2006) (2006-6)
(9) S.M. Sakamoto, T .; Izumi, T .; Yokoyama, and T.K. Haneyoshi: “A New Method for Digital PLL Control Using Estimated Two Quadrature Two Phase Frequency Detection”, Proc. of Power Conversion Conference (PCC-2002), pp. 671-676 (2002-4)

Known methods for instantaneously detecting the phase of a single-phase AC signal include a PLL method, a feedback filter method, a Hilbert transform method, a DFT method, and the like. The common approach in these instantaneous detection methods is that the principal component of the fundamental component of the single-phase AC signal to be detected is the same as the frequency of the fundamental component and the phase is advanced by π / 2 (rad) (or A delayed signal (hereinafter referred to as a quadrature signal) and a signal whose main component is the same as the frequency of the fundamental component and in phase (hereinafter referred to as an in-phase signal). The instantaneous phase of the single-phase AC signal of the source is detected using a two-phase signal composed of a signal and an in-phase signal. For example, the feedback type filter method for detecting the phase by generating an in-phase signal and a quadrature signal from a single-phase AC signal by using one or more stable feedback filters is described in detail in Document (1). . The Hilbert transform method, in which a quadrature signal is obtained through Hilbert transform of the source single-phase AC signal and the in-phase signal is used as the source single-phase AC signal itself, is described in detail in Document (2). As is clear from this example, the single-phase AC signal itself of the source may be an in-phase signal. Therefore, the generation of a quadrature signal is particularly important in phase detection. In other words, the various methods described above can be said to be instantaneous phase detection methods for single-phase AC signals using at least a quadrature signal.

The feedback filter method, the Hilbert transform method, the DFT method, and the like generate a quadrature signal on the condition that the frequency of the fundamental wave component of the single-phase AC signal is known and constant. It is a basic condition for use. In contrast, the frequency of the fundamental component of a single-phase AC signal varies, and it is expected to have the potential to detect the phase of the fundamental component even when this exact value is unknown. It is the PLL method. The PLL method acquires the ability to cope with frequency fluctuations by detecting the frequency in addition to the phase of the fundamental wave component. In other words, the PLL method can be said to be an instantaneous detection method of the frequency and phase of the fundamental wave component. A PLL method applicable to a source single-phase AC signal composed of a fundamental wave component having a varying frequency is described in detail in the above-mentioned documents (3) to (9).

According to these prior documents, the PLL method applicable to a single-phase AC signal composed of a fundamental component of a variable frequency is an adaptive system that feeds back the frequency detection value obtained by the PLL to the PLL input signal generation process and reuses it. It has a configuration. As a result of this configuration, the detection system based on the PLL method becomes nonlinear as a whole system. Although it seems that it is far from this non-linearity, the conventional PLL method as the prior invention has left the following problems.
(A) Overall, the detection system tends to become unstable.
(B) One phase of the generated two-phase voltage is used as an input signal to the PLL. For this reason, the design of the phase controller for PLL (controller used in the PLL) requires the derivation of “small signal model”, and the design of the phase controller for system stabilization is complicated. . Furthermore, it is difficult to design and use a broadband high-order phase controller that provides a high degree of follow-up, leading to system instability.
(C) Even if the true value of the frequency is constant, the frequency detection value always causes high-frequency pulsation and is not stable.

Problems to be solved by the invention

The present invention has been made based on the above background, and its purpose is to detect at least the frequency and phase of a fundamental wave component of a single-phase AC signal, and to realize the following performance of a fundamental wave component having a new structure. A detection method is provided. The provided detection method makes it possible to systematically design a wideband and higher-order phase controller while ensuring the stability of the detection system, and consequently, frequency fluctuation, phase jump, amplitude fluctuation, signal distortion, noise Even when contamination is present at a high level, adaptive detection can be performed with good amplitude in addition to the phase and frequency of the fundamental wave component. Adaptive detection by the provided detection method is stably performed, and for example, a frequency detection value without pulsation can be obtained for a certain frequency.

Means for solving the problem

In order to achieve the above object, in the invention described in claim 1, a quadrature signal having a π / 2 (rad) phase advance or delay with respect to a fundamental component of a single-phase AC signal with unknown frequency fluctuation, Using a feedback type adaptive filter with a stable variable filter coefficient , it is generated from a single-phase AC signal of unknown fluctuation frequency , and at least using the generated quadrature signal, the phase corresponding to the fluctuation frequency of the fundamental wave component and the fluctuation frequency or A method for detecting a fundamental wave component of a single-phase AC signal having an unknown fluctuation frequency , wherein at least a fluctuation frequency of the fundamental wave component and a phase cosine sine value corresponding to the fluctuation frequency are detected. The filter characteristic is a bandpass characteristic added with a differential characteristic or an integral characteristic, and the detected phase detection value is used to find that the corresponding phase detection value is the same value. As the corresponding phase cosine and sine detection value converges to the true value, and only the adaptive adjustment variable filter coefficient corresponding to the center frequency of the band-pass characteristic, coefficients corresponding to the pass band width was set to be kept constant It is characterized by that.

According to the second aspect of the present invention, a quadrature signal having a π / 2 (rad) phase advance or delay with respect to the fundamental component of a single-phase AC signal with unknown frequency fluctuation is fed back with a stable variable filter coefficient. Generated from a single-phase AC signal of unknown variation frequency using a shape adaptive filter, and using at least the generated quadrature signal, the variation frequency of the fundamental component and the variation frequency and variation of the fundamental component corresponding to the variation frequency A method of detecting a fundamental wave component of a single-phase AC signal having an unknown variation frequency that detects at least a phase cosine sine value corresponding to the frequency, wherein the fundamental component frequency detected from the variation frequency single-phase AC signal is used, the variable filter coefficients governing the stability characteristics of the filters for quadrature phase signal generated was so adapted to adjust while keeping the longer period constant frequency detection period And wherein the door.

According to a third aspect of the present invention, in the fundamental wave component detection method according to any one of the first and second aspects, the fundamental wave component phase detected from the variable frequency single-phase AC signal is used in a feedback manner. The phase deviation equivalent value, which is an estimated deviation between the phase true value and the phase detection value, is first determined, and the frequency detection value of the fundamental wave component is then determined using the phase deviation equivalent value. It is characterized in that the phase of the fundamental wave component is detected through a process corresponding to the integration of the detected fluctuation frequency of the wave component.

According to the fourth aspect of the present invention, a quadrature signal having a π / 2 (rad) phase advance or delay with respect to a fundamental component of a single-phase AC signal with unknown frequency fluctuation is fed back with a stable variable filter coefficient. Using the adaptive filter to generate a variable frequency single-phase AC signal, and using at least the generated quadrature signal, change the phase corresponding to the fundamental frequency component and the variation frequency to the variation frequency and variation frequency of the fundamental component. the detection process of the fundamental wave component of the single-phase AC signals of unknown variation frequency obtained by the phase cosine and sine values corresponding to to detect firstly the cosine and sine values of the fundamental wave component of the variation frequency single-phase alternating current signal detected, then using the detected phase or phase cosine and sine value to produce a phase cosine and sine differential equivalent value after processing of the differential equivalent of the phase, the phase cosine and sine values and the phase cosine and sine differential equivalent Characterized by being adapted to detect the frequency of the fundamental wave component through the inner product calculation processing with.

According to a fifth aspect of the present invention, there is provided a fundamental wave component detection method for a variable frequency single-phase AC signal according to any one of the first , second, third, or fourth aspects , comprising: The stable filter is realized as a digital filter in discrete time.

Hereinafter, the operation and embodiments of the present invention will be described in detail with reference to mathematical expressions and drawings. In order to provide a clear rational explanation, first, the technical problem to be solved by the present invention will be described again using mathematical expressions.

（１）式における基本周波数ω_α、同成分の位相φ_α及び振幅Ｖは未知かつ変動するものとす

数ω_αの正弦信号として表現できないノイズ、高調波成分等とする。なお、以降では、これらは簡単にノイズ等と略記する。単相交流信号の基本波成分の周波数・位相検出問題、特に、本発明の解決すべき課題は、入手可能な単相交流信号ｖを用いて、同信号の基本波成分の周波数ω_αと、次の（２）式で定義された基本波成分の位相θ_αと、

さらには基本波成分の振幅Ｖの瞬時値を、ノイズ等の影響を排除して正確に、安定的に、実時間で検出することである。As a single-phase AC signal, let us consider v in the equation (1) having a fundamental component frequency (abbreviated as fundamental frequency) ω _α .

It is assumed that the fundamental frequency ω _α , the phase φ _{α of the} same component, and the amplitude V in Equation (1) are unknown and fluctuate.

Noise, harmonic components, etc. that cannot be expressed as a sine signal of several ω _α . Hereinafter, these are simply abbreviated as noise and the like. The frequency / phase detection problem of the fundamental wave component of the single-phase AC signal, in particular, the problem to be solved by the present invention is to obtain the frequency ω _α of the fundamental wave component of the same signal using the available single-phase AC signal v, The phase θ _α of the fundamental wave component defined by the following equation (2),

Furthermore, the instantaneous value of the amplitude V of the fundamental wave component is accurately and stably detected in real time without the influence of noise or the like.

は、マルチレイトサンプルホールダ４を介して、二相信号生成器１へフィードバックされ、再利用されている。すなわち本発明による基本波成分検出システムは、システム全体としては、適応的な検出システムとなっている。図１の提供システムは、後述の説明で明らかになるように、広義の意味において、ＰＬＬシステムの範疇に属する。文献（３）−（９）もＰＬＬシステムの範疇に属するが、システムの構造、及び構造を形づくるサブシステム１−４（詳細は後述）は、本発明の基づく新規なものであり、従来の何れとも異なる。以下、これらサブシステム１−４の詳細を個別に説明する。FIG. 1 shows an embodiment of the detection system for instantaneously detecting the frequency, phase, and amplitude of a fundamental wave component of a single-phase AC signal. The fundamental wave component detection system shown in FIG. 1 includes four subsystems, a two-phase signal generator 1, an amplitude / phase deviation detector 2, a phase synchronizer 3, and a multi-rate sample holder 4. A single-phase AC signal v is received as an input signal to the fundamental wave component detection system, and the phase, frequency,

Are fed back to the two-phase signal generator 1 through the multi-rate sample holder 4 and reused. That is, the fundamental wave component detection system according to the present invention is an adaptive detection system as a whole system. The providing system in FIG. 1 belongs to the category of a PLL system in a broad sense, as will be apparent from the following description. Documents (3) to (9) also belong to the category of the PLL system, but the structure of the system and the subsystem 1-4 (details will be described later) that form the structure are novel based on the present invention. Also different. Hereinafter, details of these subsystems 1-4 will be described individually.

The role of the two-phase signal generator is that the principal component of the single-phase AC signal v is the same as the fundamental component frequency and the phase is advanced (or delayed) by π / 2 (rad). Generating a quadrature signal ν _α . For single-phase AC signals containing large noise, etc., in addition to the quadrature signal, an in-phase signal ν _β whose main component is the same as the frequency of the fundamental wave component and in phase is generated. is there.

One embodiment of the two-phase signal generator uses a quadrature signal ν _α and an in-phase signal ν _β for detecting fundamental wave components as stable filters G _α (s) and G _β (s) (s, respectively. : Laplace operator) to generate a single-phase AC signal v. Based on the inventions of claims 1 and 2, these can be configured as follows (see (3) and the following mathematical expressions).

上式におけるフィルタは、次の特性をもつものとしている。

後に詳述）。なお、上式におけるｊは、複素数の虚数部を意味する。単相交流信号を（４）

単相交流信号の基本波成分に対して、一応、π／２（ｒａｄ）位相進みの矩相信号となる点には注意されたい。

The filter in the above equation has the following characteristics.

Will be detailed later). Note that j in the above equation means an imaginary part of a complex number. Single phase AC signal (4)

It should be noted that, for the fundamental wave component of the single-phase AC signal, it becomes a quadrature signal with a π / 2 (rad) phase advance.

ただし、

If based on invention of Claim 1, the following can be comprised as simple and stable filter G ( _alpha ) (*) and G ( _beta ) (*) which satisfy | fill the conditions of (4) Formula.

However,

た。図２より、Ｇ_β（・）がバンドパス特性をもつこと、更には（５）、（６）式が（４）式の条件を満足していることは明らかである。（５）式のＧ_α（・）は、バンドパス特性をもつＧ_β（・）に対して微分処理を行い（４）式第１行の関係を達成している。一方、（６）式のＧ_α（・）は、バンドパス特性をもつＧ_β（・）に対して積分と符号反転の処理を行い（４）式第１行の関係を達成している（積分形は、位相遅れ特性−ｊの反転を利用）。すなわち、矩相信号生成用の安定フィルタＧ_α（・）の特性は、請求項１の発明に基づき、バンドパス特性に微分特性あるいは積分特性を付加した特性としている。

It was. From FIG. 2, it is clear that G _β (•) has a bandpass characteristic, and that the expressions (5) and (6) satisfy the condition of the expression (4). G _α (·) in the equation (5) performs a differentiation process on G _β (·) having a bandpass characteristic to achieve the relationship in the first row of the equation (4). On the other hand, G _α (·) in equation (6) achieves the relationship of the first row of equation (4) by performing integration and sign inversion processing on G _β (·) having bandpass characteristics ( (Integral type uses phase lag characteristic -j inversion). That is, the characteristic of the stable filter G _α (•) for generating a quadrature signal is a characteristic obtained by adding a differential characteristic or an integral characteristic to the bandpass characteristic based on the invention of claim 1.

のみを適応調整するようにする」とした請求項１の発明に基づき、提供フィルタにおいて

（５）、（６）式のバンドパス特性をもつＧ_β（・）の中心周波数は、図２より明白なように、０次係数によってのみ定まる。

Based on the invention of claim 1, in the provision filter

As is apparent from FIG. 2, the center frequency of G _β (•) having the bandpass characteristics of the equations (5) and (6) is determined only by the zeroth order coefficient.

のみですなわち単一の係数で、これを行うことになる。一般論であるが、適応システムにおける係数の適応調整においては、調整対象係数の数を極力少なく抑えることが、システム安定化に有効である。提供の検出システムも適応システムの１種であり、これを構成する二相信号生成器に関し、本一般論が適用されることが実験的に確認されている（後述の実験データ、図６〜１１を参照）。すなわち、請求項１の発明によれば、周波数変動を伴う単相交流信号に対する基本波成分検出システムの安定性を向上させることができると言う作用が得られる。The dynamic characteristics of the filters G _α (·) and G _β (·) are governed by the coefficients of the denominator polynomial common to these filters.

This will be done only with a single factor. In general terms, in adaptive adjustment of coefficients in an adaptive system, it is effective for system stabilization to keep the number of adjustment target coefficients as small as possible. The provided detection system is also a kind of adaptive system, and it has been experimentally confirmed that this general theory is applied to a two-phase signal generator constituting the detection system (experimental data described later, FIGS. 6 to 11). See). That is, according to the first aspect of the present invention, there is obtained an effect that the stability of the fundamental wave component detection system with respect to a single-phase AC signal accompanied by frequency fluctuation can be improved.

よって生成された信号を、マルチレイトサンプルホールダ４を介して得ている。このため、

定ではあるが）、長時間的には可変である。図３では、矩相信号ν_αとして微分形（上段）と積分形（下段）の２種類を示しているが、実際の利用には、何れか１つを選択することになる。FIG. 3 shows one implementation example of the equations (5) and (6). 1 / s in the figure means an integrator, and a penetrating arrow

Thus, the generated signal is obtained via the multi-rate sample holder 4. For this reason,

It is variable over time. In FIG. 3, two types of the quadrature signal ν _α , the differential form (upper stage) and the integral form (lower stage), are shown, but one of them is selected for actual use.

In the above-described embodiment example described using the equations (1) to (7) and FIGS. 2 and 3, the in-phase signal is generated integrally with the quadrature signal, but both signals are generated separately. Also good. When the noise of the single-phase AC signal of the source is small, the in-phase signal may be the source single-phase AC signal itself. FIG. 3 is one implementation of the filter, and the implementation of the filter is not limited to FIG. 3, as will be readily appreciated by those skilled in the art. In the above embodiment, a simple second-order filter is used as the quadrature signal generation filter, but it should be pointed out that a higher-order filter of the second or higher order may be used.

上式における頭符Ｔは行列の転値を意味する。ベクトル回転器に使用する位相信号として

４では、位相検出値のフィードバック利用を貫徹矢印で表現している。Next, the amplitude / phase deviation detector 2 will be described. The amplitude / phase deviation detector is configured in accordance with the invention of claim 3, and its main role is to determine a phase deviation equivalent value which is an estimated deviation between the true phase value and the detected phase value. The subordinate role is to detect the amplitude of the basic component. FIG. 4 shows one configuration example of the amplitude / phase deviation detector. The vector rotator R (•) in FIG. 4 performs the following processing.

The prefix T in the above equation means a matrix inversion. As phase signal used for vector rotator

In FIG. 4, the feedback of the phase detection value is expressed by a penetrating arrow.

なお、（１０）式は、２相信号ν_γ，ν_δに対して、ローパスフィルタにより独立にフィルタリング処理を行うことを意味する。F _l (•) in the amplitude / phase deviation detector of FIG. 4 is a low-pass filter, whose role is to remove noise and the like contained in the two-phase signal after the vector rotator, and performs the following processing: .

Equation (10) means that the filtering process is independently performed on the two-phase signals ν _γ and ν _δ by a low-pass filter.

The low-pass filtering for the two-phase signals ν _γ and ν _δ after the vector rotator has an effect equivalent to the band-pass filtering for the signals ν _α and ν _β before the vector rotator. That is, the processing procedures of the vector rotator and the filter may be changed from each other. When the filter process is preceded, the filter needs to be a band pass filter. As is well known to those skilled in the art, a second-order or higher transfer function is required to design and implement a bandpass filter, but a low-pass filter can be designed and realized from a first-order transfer function. In the configuration example of FIG. 4, it is possible to use a simple next primary filter.

As apparent from the role of the low-pass filter, when the source single-phase AC signal contains a small amount of noise and the like, naturally, the noise and the like contained in the two-phase signal after the vector rotator are also small. In such a case, this low-pass filter is unnecessary. In consideration of this point, in the amplitude / phase deviation detector of FIG. 4, the low-pass filter is indicated by a broken line block.

図４の構成より明白なように、振幅検出値に関しては、フィードバック再利用は行っていない。従って、必要に応じ、ノルム計算の前後に追加的なローパスフィルタリング処理を行ってよいことを指摘しておく。The amplitude / phase deviation detector provided in FIG. 4 detects the amplitude of the fundamental wave component of the single-phase AC signal, which is the subordinate role of the amplitude / phase deviation detector, through the norm calculation of the filtered signals ν _γl and ν _δl. doing. That is,

As apparent from the configuration of FIG. 4, feedback reuse is not performed for the amplitude detection value. Therefore, it should be pointed out that an additional low-pass filtering process may be performed before and after the norm calculation if necessary.

すなわち、

（１３）式により算定された位相は、位相真値と位相検出値との推定的偏差である位相偏差に相当する。すなわち、次の関係が成立する。

In the amplitude / phase deviation detector provided in FIG. 4, the phase detection value is fed back to the vector rotator.

That is,

The phase calculated by the equation (13) corresponds to a phase deviation that is an estimated deviation between the phase true value and the phase detection value. That is, the following relationship is established.

号の基本周波数の周波数検出値し、次に、検出周波数の積分相当の処理を通じて基本波成

りである。

上記の位相制御器Ｃ_ＰＬＬ（・）は、（１６）式のｍ次有理多項式で構成されている。

Next, the phase synchronizer 3 will be described. The phase synchronizer is configured according to the invention of claim 3.

Frequency detection value of the fundamental frequency of the signal, and then fundamental wave generation through processing equivalent to integration of the detection frequency.

It is.

The phase controller C _PLL (·) is composed of an m-order rational polynomial of equation (16).

FIG. 5 illustrates the configuration of the phase synchronizer 3. 3-1 in the figure is a phase controller, and 3-2 is a phase integrator. The phase synchronizer according to the invention of claim 3 first obtains a phase deviation equivalent value from the amplitude / phase deviation detector 2 and uses the phase deviation equivalent value to adaptively adjust the filter coefficients inside the two-phase signal generator. The frequency of the fundamental wave component used in is detected. Next, the phase of the fundamental wave component is detected through integration processing of the detection frequency. In this example, the phase is detected through the pure integration process of the detection frequency, but the pure integration process may be replaced by the approximate integration process. In other words, it should be pointed out that processing equivalent to integration is generally sufficient.

更に、周波数変動、位相変動に関して、次の漸近特性が成立し、

When the phase controller C _PLL (·) having the phase deviation equivalent value as an input signal is designed so that the next (m + 1) th order H (·) is a stable polynomial, the frequency detection value and the phase detection value are Stabilize.

Furthermore, the following asymptotic characteristics are established for frequency fluctuation and phase fluctuation,

（１７）式が安定多項式になるような位相制御器の設計は、次の文献（１０）を活用すれば、容易に行うことができる。
（１０）新中新二：「１次遅れ特性をもつ制御対象の制御方法」、特開２００６−０３１６５４When it is necessary to consider the frequency fluctuation of the basic component of the single-phase AC signal, as understood from the equation (18), at least the phase controller denominator polynomial C _d (•) is used as the phase controller. It is necessary to make one form with one s-factor. When the frequency fluctuation is severe, a high-order controller having two or more phase controllers whose denominator polynomial has two s factors is preferable. The simple types 1 and 2 are as follows.

The design of the phase controller so that equation (17) becomes a stable polynomial can be easily performed by utilizing the following document (10).
(10) Shinnaka Shinji: “Control Method for Controlled Object with First-Order Delay Characteristics”, JP-A-2006-031654

According to the phase synchronizer using the phase deviation equivalent value based on the invention of claim 3, as described above, the design and use of a broadband high-order phase controller that provides high followability to frequency fluctuation and phase fluctuation. Is possible. Moreover, the design is simple. That is, according to the third aspect of the invention, it is possible to design and use a broadband high-order phase controller that provides high followability with respect to frequency fluctuation and phase fluctuation, and the design can be easily performed. Is obtained.

れる。本フィードバックこそが、周波数変動を伴う単相交流信号の位相・周波数検出における有効な解決策であるが、同時に検出システム全体の不安定化をもたらす主要因の１つでもある。Next, the multi-rate sample holder 4 will be described. Base generated by phase synchronizer 3

It is. This feedback is an effective solution for phase / frequency detection of single-phase AC signals with frequency fluctuations, but at the same time is one of the main factors that cause the entire detection system to become unstable.

るフィードバックループを構成し、二相信号生成器の係数を瞬時瞬時に変化した場合、周波数変動を伴う単相交流信号の位相・周波数検出の可能性が出てくるが、上記の時不変を前提とした議論はもはや成立せず、個々のサブシステムが線形で安定であっても、全システムとしては非線形となり、安定性の保証はできない。この種の問題は、二相信号生成器において適応的な係数調整を行っている周波数位相検出法（広くは、基本波成分検出法）では、例外なく直面する深刻な問題である。If this feedback is not present and a constant positive value is always used as the coefficient of the two-phase signal generator, the entire system of FIG. 1 can have two stable linear time-invariants with a two-phase signal generator and a PLL. Subsystem feed-forward coupling. The entire system in this case is linear time-invariant, and inevitably this stability is ensured. However, the fundamental frequency of the single-phase AC signal is constant and known.

If the coefficient of the two-phase signal generator is changed instantaneously and instantaneously, the possibility of phase / frequency detection of a single-phase AC signal with frequency fluctuation appears. However, even if the individual subsystems are linear and stable, the entire system is nonlinear and stability cannot be guaranteed. This type of problem is a serious problem faced without exception in the frequency phase detection method (generally, the fundamental wave component detection method) in which adaptive coefficient adjustment is performed in the two-phase signal generator.

を担う。すなわち、

The multi-rate sample holder based on the invention of claim 2 solves this problem from a practical viewpoint, that is, ensuring the followability to the frequency fluctuation of the single-phase AC signal and ensuring the stability of the detection system. Engineering trade-offs can be made. This holder

Take on. That is,

If the hold time _Th is equal to or greater than the time constant of the two-phase signal generator, the stability of the entire system can be ensured from the stability of the individual subsystems. On the other hand, hold time T _h is, with respect to frequency variation of the single-phase AC signal, if sufficiently short, it is possible also ensure the followability to fluctuations. As is clear from the above, according to the invention of claim 2, it is possible to obtain an effect that it is possible to achieve the followability to the frequency fluctuation while ensuring the stability of the fundamental wave component detection system.

The fundamental wave component detection system provided in FIG. 1 is preferably realized in discrete time by software using an arithmetic element such as a microcomputer. In particular, the two-phase signal generator which is a filter having an adaptive adjustment coefficient is preferably realized in discrete time based on the invention of claim 5. In the case of discrete time realization, the adaptive adjustment of the coefficients can be realized easily. That is, according to the invention of claim 5, it is possible to obtain an effect that the adaptive function can be easily realized.

In the case of realizing the discrete time of the two-phase signal generator, the configuration of the fundamental wave component detection system can be further facilitated if other devices are similarly discrete timed. In the case of realizing discrete time, the sampling period T _s for sampling the single-phase AC signal is determined based on the fundamental frequency of the single-phase AC signal to be processed. The discrete-time realization fundamental component detection system, multirate samples holder hold time T _h may be selected to an integral multiple of the sampling period T _s, also two signal sampling period T _s and the hold time T _h There will be a processing cycle. The reason why the sample holder according to the present invention is given "multi-rate" is because of this point.

An example of the results of a numerical experiment conducted to confirm the performance and effects of the provided fundamental wave component detection method is introduced. As described above, the fundamental wave component detection system shown in FIG. 1 is practically realized in discrete time. If the discrete time realization of the system is taken into consideration, the verification of the system performance and effect by numerical experiments is sufficiently practical.

二相信号生成器における矩相信号生成のためのフィルタＧ_α（・）としては、（５）式の微分形を採用した。また、位相同期器内の位相制御器Ｃ_ＰＬＬ（・）としては、（２０）式の２形を採用し、同係数は（１７）式に従い設計した。The conditions and main design parameters of the single-phase AC signal used in the experiment were determined as follows.

As the filter G _α (•) for generating the quadrature signal in the two-phase signal generator, the differential form of the equation (5) is adopted. Further, as the phase controller C _PLL (·) in the phase synchronizer, the two forms of the equation (20) are adopted, and the coefficient is designed according to the equation (17).

本単相交流信号に対し、以下の設計を行った。

Basically, in order to confirm the pulsation of the detected frequency value at the steady state, which is one of the most important performances and effects, the following ideal condition was given to the single-phase AC signal of the equation (1).

The following design was performed for this single-phase AC signal.

位相真値と同検出値の表示は、波形データの重複・輻輳をさけるべく、２（ｒａｄ）相当の原点シフトを行い表示している（以下の位相表示も同様）。周波数検出値、振幅検出値のスケールは、各々０．０１（ｒａｄ／ｄｉｖ）、１（Ｖ／ｄｉｖ）であり、周波数検出値に対し大スケールを利用している点には特に注意されたい。なお、振幅検出値のスケールには、他のスケールとの区別のため、単位（Ｖ）を付してある。図より明らかなように、位相、周波数、振幅のいずれも極めて良好に検出されている。大スケールで明示したように、周波数が高周波脈動もなく更には非常に高い精度で検出されている点に注目されたい。文献（３）〜（８）に示された従来のＰＬＬ法による周波数検出においては、周波数検出値における高周波脈動の存在は不可避のように思われるが、提供の方法ではこの種の高周波脈動が実質的に消滅している。The experimental results are shown in FIG. FIG (a) the phase true value on the time axis 0.02 (s / div) (dashed line) theta _alpha same detection value

The phase true value and the detected value are displayed by shifting the origin corresponding to 2 (rad) in order to avoid duplication / congestion of the waveform data (the same applies to the following phase display). The scales of the frequency detection value and the amplitude detection value are 0.01 (rad / div) and 1 (V / div), respectively, and it should be particularly noted that a large scale is used for the frequency detection value. A unit (V) is added to the scale of the amplitude detection value for distinction from other scales. As is clear from the figure, all of the phase, frequency, and amplitude are detected very well. Note that the frequency is detected with very high accuracy without high frequency pulsation, as demonstrated on a large scale. In the frequency detection by the conventional PLL method shown in the literatures (3) to (8), the presence of high frequency pulsation in the frequency detection value seems unavoidable, but this type of high frequency pulsation is substantially not provided in the provided method. Has disappeared.

すなわち、変動幅±１０％、変動周波数２０（ｒａｄ／ｓ）の周波数変動をもつ信号を用意した。
基本周波数の変動としては、文献（３）〜（９）に示された従来のいずれの周波数位相検出法あるいは基本成分検出法によっても困難な極めて大きいものである。The greatest feature of the fundamental wave component detection method according to the present invention lies in that the phase and frequency can be correctly detected by adapting to the fundamental frequency fluctuation of the single-phase AC signal. In order to confirm this performance and effect, a single-phase AC signal with the following conditions was prepared instead of the equation (23).

That is, a signal having a fluctuation range of ± 10% and a fluctuation frequency of 20 (rad / s) was prepared.
The fluctuation of the fundamental frequency is extremely large, which is difficult by any of the conventional frequency phase detection methods or fundamental component detection methods shown in documents (3) to (9).

している。周波数の検出は、その変動にもかかわらず、極めて良好である。位相、振幅の検出も同様に良好である。所期の周波数変動に適応した検出が達成されていることが確認される。The system design was the same as that of the basic performance / effect (24). The experimental results are shown in FIG.

doing. The frequency detection is very good despite its variation. The detection of the phase and amplitude is equally good. It is confirmed that detection adapted to the intended frequency fluctuation is achieved.

In order to confirm the performance and effect of the fundamental wave component detection method according to the present invention for the phase jump of a single-phase AC signal, a single-phase AC signal having a large phase jump φ _α = π / 2 (rad) was prepared at an instant. . The conditions for the single-phase AC signal are the same as those in the equation (23) except for the phase jump. The experimental results are shown in FIG. FIG. 4A shows the phase true value and the detected value on the time axis 0.05 (s / div). The phase detection value almost completes reconvergence (that is, phase lock again) at about 0.15 (s) after the phase jump. FIG. 5B shows the view phase, the frequency detection value, and the amplitude detection value on the time axis 0.2 (s). The pulsation attenuation of the frequency detection value and the amplitude detection value requires about 0.5 (s) after the phase jump. The main reason why the phase detection value converges faster than the frequency detection value and the amplitude detection value is due to the effect of reducing the pulsation by the integrator immediately after the phase controller (see FIG. 5).

In order to confirm the performance and effect of the fundamental wave component detection method of the present invention for the amplitude fluctuation of a single-phase AC signal, a single-phase AC having an instantaneous amplitude decrease of 50% and an instantaneous amplitude increase of 150% with respect to a reference value at a certain instant. A signal was prepared. The other conditions excluding the amplitude are the same as the equation (23). The experimental results are shown in FIG. FIG. 5A shows the phase true value and the detected value on the time axis 0.02 (s / div), and FIG. 5B shows the frequency detected value, the amplitude true value, and the amplitude on the time axis 0.2 (s). The detected value is shown. The amplitude V was instantaneously changed from 1 → 0.5 → 1.5. The figure (a) is for the case of instantaneous amplitude decrease (1 → 0.5), but it is confirmed that the phase detection is hardly affected by the amplitude fluctuation. The same applies to the phase detection when the instantaneous amplitude increases (0.5 → 1.5). Note that this increase in amplitude is relatively equivalent to a 300% instantaneous increase. The frequency detection value has a pulsation with a period of 0.04 (s) due to the source single-phase AC signal, but the average value is stable. In addition, amplitude detection has succeeded in high-speed detection, as is clear from comparison between the true value and the detected value.

In order to confirm the performance and effect of the fundamental wave component detection method of the present invention against distortion of a single-phase AC signal, a rectangular single-phase AC signal with an amplitude of ± 1 was prepared. This rectangular signal is composed of a fundamental wave component and a harmonic component having an amplitude V = 4 / π, and has extremely high distortion (48.3% THD) due to the harmonic component. Conditions other than the distortion of this signal are the same as in equation (23).

Considering the harmonic distortion of the single-phase AC signal, the low-pass filter and phase controller were redesigned as follows.

The experimental results are shown in FIG. FIG. 6A shows the source single-phase AC signal and phase detection value on the time axis 0.02 (s / div), and FIG. 5B shows the frequency detection value and amplitude detection value on the time axis 0.2 (s). Is shown. In the amplitude detection value, there are pulsations due to residual components of harmonics (contribution to 48.3% THD) that could not be removed by the low-pass filter immediately after the vector rotator, but the phase and frequency were detected well. Yes. As is clear from the system configuration of FIG. 1, feedback reuse is not performed for the amplitude detection value. Therefore, there is no problem in determining the final amplitude detection value by performing an additional low-pass filtering process before and after the norm calculation as necessary to reduce the pulsation of the amplitude detection value. Additional filtering is not performed on the detected amplitude value in FIG.

In order to confirm the performance and effect of the provided fundamental wave component detection method against noise, a single-phase AC signal having noise was prepared. The noise was white noise distributed uniformly between ± 0.5. Considering the amplitude V = 1 of the single-phase AC signal fundamental wave component, it can be said that this noise level is extremely high. Conditions other than the noise of this signal are the same as in equation (23). The design of the low-pass filter and the phase controller is the same as the equation (26).

The experimental results are shown in FIG. FIG. 4A shows the phase true value and the detected value, and FIG. 4B shows the source single-phase AC signal, the frequency detection value, and the amplitude detection value. Both time axes are 0.02 (s / div). Despite a high noise level, the phase, frequency, and amplitude are not affected by noise and are properly detected.

As can be clearly seen from the above experimental results, the fundamental wave component detection method provided by the present invention exhibits performance that is impossible or difficult to achieve with the conventional methods of Documents (3) to (9). In particular, it has very high performance and effects.

成器１へフィードバックされ、再利用されている。すなわち本発によるシステムは、システム全体としては、適応的な検出システムとなっている。しかし、提供の基本波成分検出システムは、位相同期器を有せず、ＰＬＬシステムではない。この点には、注意されたい。以下、これらサブシステムの詳細を個別に説明する。Subsequently, embodiments according to the inventions of claims 1, 2, and 4 will be described. FIG. 12 shows a detection system for instantaneously detecting a fundamental wave component of a single-phase AC signal, which is an embodiment according to the first, second, and fourth aspects of the invention. The system is composed of four subsystems: a two-phase signal generator 1, an amplitude / phase detector 5, a frequency detector 6, and a multi-rate sample holder 4. A single-phase AC signal v is received as an input signal to the system, and the phase, frequency,

It is fed back to the generator 1 and reused. That is, the system according to the present invention is an adaptive detection system as a whole system. However, the provided fundamental wave component detection system does not have a phase synchronizer and is not a PLL system. Please be careful about this point. Hereinafter, details of these subsystems will be described individually.

The roles and actions of the two-phase signal generator 1 and the multi-rate sample holder 4 in the fundamental wave component detection system of FIG. 12 are the same as those of the detection system of FIG. That is, as the two-phase signal generator 1 and the multi-rate sample holder 4 in the detection system of FIG. 12, the same ones as those of the detection system of FIG. 1 can be used. Since the embodiments of these subsystems have already been described in detail in connection with the fundamental wave component detection system of FIG. 1, description thereof is omitted here.

FIG. 13 is a configuration example of an amplitude / phase detector which is one of the new subsystems. F _b (•) in the figure is a band filter, and its first role is to remove noise and the like contained in the input two-phase signals ν _α and ν _β and remove the two-phase signals ν _αb , It is in the generation of ν _βb . The second role is to generate a signal (differential signal) corresponding to the differential value of the two-phase signals ν _αb and ν _βb .

The center frequency of the bandpass filter is adaptively adjusted using a frequency detection value obtained from the multi-rate sample holder. In the figure, the state of this adaptive adjustment is represented by a penetrating arrow. Regarding an example of the configuration of a band-pass filter having a variable coefficient that is adaptively adjusted, it has already been described in detail using Equations (5) and (6) and FIGS. 2 and 3 in connection with the two-phase signal generator. As described (G _β (•) corresponds to a bandpass filter). A similar bandpass filter can be used here as well. However, in these uses, it is necessary to determine the coefficient g in consideration of the fact that the coefficient g in the equation (7) becomes a rough passband value. Of course, other known bandpass filters may be used, as will be readily understood by those skilled in the art. However, the center frequency of the bandpass filter to be used needs to be variable according to the frequency detection value.

As is apparent from the example of the bandpass filter of FIG. 3, in the bandpass filter, this differential signal can be generated simultaneously with the signal obtained by the bandpass filtering. In the example of FIG. 3, the differential quadrature signal corresponds to the differential signal of the in-phase signal that is the bandpass filtering signal. In general, the bandpass filter is not limited to the example of FIG. 3, and the differential signal can be generated simultaneously with the signal obtained by the bandpass filtering.

As apparent from the role of the bandpass filter, this band filter may be omitted when the noise or the like contained in the two-phase signal obtained from the two-phase signal generator is small. However, in this case, it is necessary to perform a differential equivalent process on the two-phase signal obtained from the two-phase signal generator to generate these differential equivalent signals. When the bandpass filter is omitted, this bandpass filter is replaced with a differentiator. In the generation of the differential equivalent signal, as a matter of course, it is not necessary to use the frequency detection value.

In the amplitude / phase detector 5 provided in FIG. 13, if the filtered two-phase signals ν _αb and ν _βb are obtained, the phase of the single-phase AC signal of the source is obtained by arc tangent processing of these two-phase signals. Is detected. That is,

The amplitude / phase detector 5 provided in FIG. 13 detects the amplitude of the fundamental wave component of the single-phase AC signal through the norm calculation of the filtered two-phase signal. That is,

上記の正規化フィルタ信号は、位相検出値の余弦正弦信号になっている点には、特に注意されたい。すなわち、

以降では、（３０）式の２ｘ１ベクトル信号を位相ベクトルと呼称する。単相交流信号の位相検出値を利用する応用では、位相検出値そのものではなく、位相検出値の位相ベクトルを必要とすることが少なくない。この種の応用では、（２７）式の位相検出は必要なく、（２９）、（３０）式の正規化フィルタ信号こそが有用である。In the amplitude / phase detector 5 provided in FIG. 13, as shown in the following equation (29), the filtered two-phase signal is divided by the amplitude detection value of the equation (28) and normalized. A processed signal is generated and output to a frequency detector.

It should be particularly noted that the normalized filter signal is a cosine sine signal of the phase detection value. That is,

Hereinafter, the 2 × 1 vector signal of Equation (30) is referred to as a phase vector. In applications using the phase detection value of a single-phase AC signal, it is often necessary to use the phase vector of the phase detection value instead of the phase detection value itself. In this type of application, the phase detection of equation (27) is not necessary, and only the normalized filter signal of equations (29) and (30) is useful.

The amplitude / phase detector 5 provided in FIG. 13 divides the differential value of the bandpass filter signal by the amplitude detection value of the equation (28) as shown in the following equation (31), thereby A differential equivalent signal is generated and output to a frequency detector.

（３２）式の第１式は、請求項４の発明に基づく周波数検出の原理を示したものであり、同第３式は周波数検出の実際の処理手順の１例を示したものである。すなわち、原理的には、単相交流信号の基本波成分の位相を先ず検出し、次に、検出した位相の微分相当の処理を行い、基本波成分の周波数を検出するようにしている。実際の検出は、位相余弦正弦値を先ず検出し、これを用いて、位相の微分相当の処理（本例では、位相ベクトルと位相ベクトル微分値とによる内積的演算処理）を行い、基本波成分の周波数を検出するようにしている。The frequency detector which is one of the new subsystems is configured according to the invention of claim 4. An example of a configuration according to the present invention can be described as the following simple vector dot product equation.

The first equation (32) shows the principle of frequency detection based on the invention of claim 4, and the third equation shows an example of the actual processing procedure of frequency detection. That is, in principle, the phase of the fundamental wave component of the single-phase AC signal is detected first, and then the processing corresponding to the differentiation of the detected phase is performed to detect the frequency of the fundamental wave component. In actual detection, the phase cosine sine value is detected first, and using this, processing equivalent to phase differentiation (in this example, inner product calculation processing using the phase vector and phase vector differential value) is performed, and the fundamental component The frequency is detected.

As will be readily understood by those skilled in the art, even through a process corresponding to the differentiation with respect to the phase detection value shown in the expression (27) (that is, through a process directly according to the first expression of the expression (32)), It is possible to detect the frequency. There are many applications that require a phase vector instead of the phase itself, and in these applications, the frequency detection value provided in the third equation of equation (32) is more useful.

Similar to the fundamental wave component detection system of FIG. 1, the fundamental wave component detection system of FIG. 12 is preferably realized in discrete time by software using an arithmetic element such as a microcomputer. In the case of discrete implementation by a microcomputer or the like, the amplitude / phase detector 5 and the frequency detector 6 can be realized more easily.

Both the amplitude / phase detector 5 and the frequency detector 6 described above are based on the invention of claim 4. As is clear from the above description, according to the invention of claim 4, the phase vector required for many applications can be obtained directly without obtaining the phase of the fundamental wave component. In addition, when band-pass filtering is performed as pre-processing, the differential signal of the phase vector can be obtained without the need for additional differential processing, and the frequency detection value of the fundamental wave component can be obtained by simple inner product calculation. Can be obtained. As a result, according to the fourth aspect of the invention, it is possible to obtain an effect that the phase vector and the frequency of the fundamental wave component accompanied by the fluctuation can be obtained by a very light calculation. Moreover, unlike the detection system shown in FIG. 1, the detection system of FIG. 12 does not need to configure a PLL that is a kind of feedback loop. Naturally, it is not necessary to detect a phase deviation equivalent value for PLL stabilization and to design and configure a phase controller using the phase deviation equivalent value. As a result, according to the invention of claim 4, the system instability caused by the PLL can be reduced, and the system design can be simplified.

Next, a description will be given of an embodiment of a power conversion device for a single-phase AC power system interconnection utilizing a fundamental wave component detection system provided by the present invention. FIG. 14 shows an example of the configuration of this type of power conversion device. Reference numeral 10 denotes a power conversion device, which is composed of other main components 10-1 to 10-3 in addition to the fundamental wave component detection system 10-4 that can detect a phase by adapting to a varying frequency. . 10-1 is an inverter, 10-2 is a feedback current controller, and 10-3 is a current command generator. The purpose of this power converter is to link the inverter to the system through current control that takes into account the phase difference from the voltage of the single-phase AC power supply system, and these four devices bear the main functions. The inverter and the current controller constitute a feedback current control system. If the current control system can be designed and configured appropriately, the current according to the current command can be exchanged with the system side. The main problem with this type of power converter is the generation of a current command for the feedback current control system.

考慮の上、以下のように構成することになる。

（３３）式においては、時間とともに変化する時間関数に関しては、これを明示するように時間変数ｔを付している。上の電流指令は、以下のように再構成することができる。

図１４における電流指令生成器１０−３は、（３４）〜（３６）式に従って構築されている。図

Actual measurement voltage of the voltage of the single-phase AC power supply system is to be (1) of [nu (t), detected is the frequency omega _alpha and phase vector of the fundamental wave component. This frequency is assumed to vary, although an approximate value (for example, an average value) is known. The current command i ^* (t) for current control is the current peak value,

The following configuration is taken into consideration.

In the equation (33), a time variable t is attached so as to clearly indicate a time function that changes with time. The above current command can be reconfigured as follows.

The current command generator 10-3 in FIG. 14 is constructed according to the equations (34) to (36). Figure

As the equation (34) clearly shows, detection of the phase or phase vector of the fundamental component of the system voltage is indispensable for generating a current command for system interconnection. Detection of a phase or a phase vector in the case of accompanying frequency fluctuations requires simultaneous detection of fluctuating frequencies as already described in detail with reference to FIGS. If it is considered that the current control is performed instantaneously, the phase or phase vector at this time must be detected instantaneously without time delay. In the power conversion device of FIG. 14, the fundamental wave component detection system according to the present invention as illustrated in FIGS. 1 and 12 is used to instantaneously detect the phase or phase vector while instantaneously detecting the frequency. The function of the period is realized.

Next, an example of a power conversion device for a single-phase AC power supply system interconnection utilizing a fundamental wave component detection system realized in discrete time will be described. FIG. 15 shows an example of this. The difference between FIG. 15 and FIG. 15 is that the fundamental wave component detection system 10-4 is realized in discrete time from the beginning, and in accordance with this, a continuous time signal is sampled before the input end of the fundamental wave component detection system 10-4 and discrete. A sampler that generates a time signal is installed, and a zero-order hold circuit that converts a discrete-time signal into a continuous-time signal is installed at the output end. Except for this point, the inverter 10-1, the feedback current controller 10-2, and the current command generator 10-3 constituting the power converter are not substantially different from those in FIG. Therefore, these descriptions are omitted.

1 to 15, the fundamental wave component detection method for a single-phase AC signal according to the present invention, and further, the same detection method as an example of a power converter for a single-phase AC power system interconnection Explained in detail how to use. The use of the fundamental wave component detection system according to the present invention is not limited to the power converters shown in FIGS. 14 and 15, uninterruptible power supply, power harmonic suppressor, single-phase transformer inrush current prevention device, special It should be pointed out that there are various other devices such as a charger and a power supply synchronization detection device.

Effect of the invention

As is clear from the above description, the present invention has the following effects. In particular, according to the first aspect of the present invention, the stability of the fundamental wave component detection system with respect to a single-phase AC signal with frequency fluctuation, which is a kind of adaptive system, can be improved from the viewpoint of a two-phase signal generator. The action to say was obtained. As a result of this action, according to the first aspect of the present invention, even when the frequency of the fundamental wave component of the single-phase AC signal fluctuates greatly, the frequency, phase, and amplitude of the fundamental wave component can be more stably increased. The effect that it can detect is acquired. In particular, for a single-phase AC signal having a constant frequency, an effect that a frequency detection value without pulsation can be obtained is obtained.

In particular, according to the second aspect of the present invention, it is possible to obtain the effect that the tracking performance with respect to the frequency fluctuation can be achieved while ensuring the stability of the fundamental wave component detection system. As a result of this action, according to the invention of claim 2, it is possible to satisfy the contradictory characteristics of system stability and adaptability to frequency fluctuations at the same time, but it is stable and truly adaptive. An effect that frequency phase detection is possible is obtained.

In particular, according to the third aspect of the invention, it is possible to design and use a broadband high-order phase controller that provides high followability with respect to frequency fluctuation and phase fluctuation, and the design can be easily performed. was gotten. As a result of this action, according to the invention of claim 3, there is obtained an effect that the frequency phase detection that achieves high followability and adaptability to frequency fluctuation and phase fluctuation can be achieved without impairing stability.

In particular, according to the invention of claim 4, without constituting a PLL which is a kind of feedback loop, in other words, with a very light operation in a form that reduces the instability of the system caused by the PLL. The phase vector and the frequency of the fundamental wave component accompanying the fluctuation can be obtained. In addition, the system design can be simplified. As a result of these actions, according to the invention of claim 4, it is possible to obtain an effect that adaptive frequency phase detection can be easily performed with a further improved stability.

In particular, according to the invention of claim 5, an effect that the adaptive function can be easily realized is obtained. As a result of this action, according to the invention of claim 5, the effect that the provided fundamental wave component detection method can be easily realized, that is, the fundamental wave component detection system which is an adaptive system can be easily realized. The effect to say is acquired.

The effect of the invention was experimentally verified through detailed and numerous experimental data. That is, even when frequency fluctuation, phase jump, amplitude fluctuation, signal distortion, noise mixing, etc. are present at a high level, it is possible to adaptively detect not only the phase and frequency of the fundamental wave component but also the amplitude. We have experimentally demonstrated the performance and effects. These experimental data show that the fundamental wave component detection system according to the present invention achieves performance that is impossible or difficult to achieve by conventional methods such as documents (3) to (9). This demonstrates that it has a very high effect.

The block diagram which shows the structure of the fundamental wave component detection system in 1 example of embodiment. Example of frequency response of band-pass filter in one embodiment Realization example of 1-input 2-output filter for two-phase signal generator in one embodiment 1 is a block diagram showing a configuration of an amplitude / phase deviation detector in an embodiment. The block diagram which shows the structure of the phase synchronizer in 1 example of embodiment. Response example of fundamental wave component detection system in one embodiment Response example of fundamental wave component detection system in one embodiment Response example of fundamental wave component detection system in one embodiment Response example of fundamental wave component detection system in one embodiment Response example of fundamental wave component detection system in one embodiment Response example of fundamental wave component detection system in one embodiment The block diagram which shows the structure of the fundamental wave component detection system in 1 example of embodiment. 1 is a block diagram showing a configuration of an amplitude / phase detector in an embodiment. The block diagram which shows one structural example of the power converter device using a fundamental wave component detection system The block diagram which shows one structural example of the power converter device using a fundamental wave component detection system

Explanation of symbols

DESCRIPTION OF SYMBOLS 1 Two-phase signal generator 2 Amplitude / phase deviation detector 3 Phase synchronizer 3-1 Phase controller 3-2 Phase integrator 4 Multi-rate sample holder 5 Amplitude / phase detector 5-1 Band pass filter 6 Frequency detector DESCRIPTION OF SYMBOLS 10 Power converter 10-1 Inverter 10-2 Feedback current controller 10-3 Current command generator 10-4 Fundamental wave component detection system

Claims (5)

Unknown π / 2 (rad) phase to the fundamental wave component advances or lag quadrature phase signals of the single-phase AC signal with a frequency variation, unknown variation frequency using a feedback adaptive filter having a stable variable filter coefficients The phase cosine sine value corresponding to the fluctuation frequency and fluctuation frequency of the fundamental wave component or the phase corresponding to the fluctuation frequency and fluctuation frequency of the fundamental wave component is generated using at least the generated quadrature signal. A method of detecting a fundamental wave component of a single-phase AC signal having an unknown variation frequency at least detected,
The characteristic of the stable filter for generating a quadrature signal is a characteristic obtained by adding a differential characteristic or an integral characteristic to a bandpass characteristic, and the detected detected fundamental wave frequency is used to make the corresponding phase detection value equal to the true value or Only the variable filter coefficient corresponding to the center frequency of the bandpass characteristic is adaptively adjusted so that the corresponding phase cosine sine detection value converges to the same true value, and the coefficient corresponding to the passband width is held constant. The fundamental wave component detection method of the single phase alternating current signal of the unknown fluctuation frequency characterized by these. Unknown π / 2 (rad) phase to the fundamental wave component advances or lag quadrature phase signals of the single-phase AC signal with a frequency variation, unknown variation frequency using a feedback adaptive filter having a stable variable filter coefficients The phase cosine sine value corresponding to the fluctuation frequency and fluctuation frequency of the fundamental wave component or the phase corresponding to the fluctuation frequency and fluctuation frequency of the fundamental wave component is generated using at least the generated quadrature signal. A method of detecting a fundamental wave component of a single-phase AC signal having an unknown variation frequency at least detected,
Using the fundamental wave component frequency detected from the single-phase AC signal with variable frequency, adaptive adjustment is performed while keeping the variable filter coefficient governing the characteristics of the stable filter for generating the quadrature signal constant for a period longer than the frequency detection period. A fundamental wave component detection method for a single-phase AC signal having an unknown variation frequency , characterized by comprising: A method for detecting a fundamental component of a single-phase AC signal having an unknown variation frequency according to any one of claims 1 and 2,
First, a phase deviation equivalent value, which is an estimated deviation between the phase true value and the phase detection value, is determined using feedback of the fundamental wave component phase detected from the variable frequency single-phase AC signal, and the phase deviation equivalent value is used. then determining a frequency detected value of the fundamental wave component, followed by claim 1, characterized in that to detect the fundamental wave component phase through integration equivalent processing detection fluctuation frequency of the fundamental wave component Or the fundamental wave component detection method of the single phase alternating current signal of the unknown fluctuation frequency as described in any one of Claim 2 . Unknown π / 2 (rad) phase to the fundamental wave component advances or lag quadrature phase signals of the single-phase AC signal with a frequency variation, unknown variation frequency using a feedback adaptive filter having a stable variable filter coefficients the generated from the single-phase AC signals, using the generated rectangular phase signals at least, a single-phase AC signals of unknown variation frequency to detect the phase cosine and sine value corresponding to the variation frequency and the variation frequency of the fundamental wave component A method of detecting a fundamental wave component,
First, the phase cosine sine value of the fundamental wave component of the variable frequency single-phase AC signal is detected, and then processing corresponding to differentiation of the detected phase cosine sine value is performed to generate a phase cosine sine differential equivalent value, A method of detecting a fundamental wave component of a single-phase alternating current signal having an unknown variation frequency , wherein the frequency of the fundamental wave component is detected through an inner product calculation process of a phase cosine sine value and a phase cosine sine differential equivalent value. . The fundamental component of the variable frequency single-phase AC signal according to any one of claims 1, 2, 3, and 4 , wherein the stable filter is realized as a digital filter in discrete time. Detection method.

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