JP5304883B2 - Partial structure of electric parts and electric circuits - Google Patents

Abstract

An electric device (2100) provided with a first transmission line (2180b) for carrying a first current, at least one second transmission line (2190b) parallel to the first transmission line and for carrying a second current, and metamaterials (2110a, 2112a, 2140, 2112b, 2110b, 2122, 2124a, 2150, 2130, 2160, 2124b) which exhibit negative permittivity and negative permeability with respect to the resonance wavelength component of an electromagnetic field. The metamaterials are arranged in predetermined positions and directions so that negative permittivity and negative permeability are exhibited with respect to the resonance wavelength component of the electromagnetic field produced by the first current, and so that the negative permittivity and negative permeability affect the second transmission line electromagnetically, thereby causing the second current to flow. Due to this, the electric device can have a small size and achieve strong coupling.

Description

  The present invention relates to an electric component and a partial structure of an electric circuit, and more particularly to an electric component suitable for taking out a part of electric power propagating on a transmission line to another port and the partial structure of the electric circuit.

  2. Description of the Related Art Conventionally, a directional coupler, which is an electrical component for taking out a part of power propagating on a transmission line of a high-frequency signal in a predetermined direction to another port, has been used.

  Among such directional couplers, in which the wavelength of the center frequency is λ, there is one in which two parallel lines having a length of λ / 4 are used as a coupling portion (for example, Japanese Patent Laid-Open No. 9-9 / 1990). No. 246818 (see “Patent Document 1”). In this case, for example, if the center frequency is 1 GHz, λ / 4 = 7.5 cm when the relative dielectric constant = 1.

  In addition, in order to reduce the size compared to the case where the lines are linearly parallel, there is a method in which a substrate on which the meandering parallel lines are formed is laminated to secure a parallel portion having a length of λ / 4. (For example, refer to Japanese Patent Laid-Open No. 5-160614 (hereinafter referred to as “Patent Document 2”)).

  In addition, in order to obtain strong coupling with a shorter parallel line length, an HPF (High-Pass Filter) type left-handed transmission line is used in a coupled line type coupler which is a directional coupler having two parallel lines. (For example, Akimichi Hirota, Shihiro Tahara, Naofumi Yoneda, "Coupled line type forward coupler using a right / left-handed composite line" (MW2008-28), IEICE technical report, incorporated association The Institute of Electronics, Information and Communication Engineers, May 2008, Vol.108, No.63, p.77-82 (hereinafter referred to as “Non-Patent Document 1”).

  Japanese Patent Laid-Open No. 2008-147737 (hereinafter referred to as “Patent Document 3”) describes that, for example, paragraph 0036 can be used as a strong coupling backward coupler as an application example of a left-handed transmission line. ing.

JP-A-9-246818 Japanese Patent Laid-Open No. 5-160614 JP 2008-147737 A

Akita Hamada, Shihiro Tahara, Naofumi Yoneda, "Coupled line type forward coupler using right / left-handed composite line" (MW2008-28), IEICE technical report, IEICE, 2008 5 Moon, Vol.108, No.63, p.77-82

  The directional couplers according to Patent Document 1 and Patent Document 2 basically have a coupled line having a length of λ / 4. Even if the length is shorter than λ / 4, the coupling is coupled. However, in order to obtain the strongest coupling, the length of the coupled line needs to be λ / 4.

  However, even if the length of the coupled line is λ / 4, the parallel coupling cannot increase the degree of electromagnetic coupling because the capacitive coupling and the magnetic coupling between the lines are not strong. For example, the degree of coupling of the directional coupler of Patent Document 1 is about 40 dB.

  In order to increase the degree of coupling, as in Patent Document 2, it is necessary to meander the parallel lines to increase the magnetic coupling, or to adjoin the lines in the stacking direction to increase the capacitive coupling. In any case, it is necessary to make the length of the coupled line close to λ / 4, which causes a problem that the size of the directional coupler increases.

  Further, when the line width is reduced in order to reduce the size of the directional coupler, there arises a problem that loss increases.

  In order to obtain strong coupling that does not depend on the length of the coupled line being λ / 4, it is conceivable to use a left-handed transmission line as in Non-Patent Document 1 described above. However, the transmission line type directional coupler requires a capacitor for the series and an inductor for the shunt. In order to reduce the size, it is necessary to shorten the pitch of the inductor.

  However, if the pitch of the inductor is shortened, an equivalent inductor will be included in the series due to coupling. For this reason, since the inductor becomes a right-handed component, there arises a problem that the operation of the left-handed system is suppressed.

  Further, since the self-inductance L and the capacitance C per unit length need to be constant, it is necessary to increase L and C as the size is reduced. For this reason, the left-handed transmission line has a structure that is difficult to reduce in size.

  Left-handed metamaterials have a resonance type, but only large ones. For this reason, there is nothing that can be used for the stripline, and application to a small directional coupler has not been proposed.

  The present invention has been made to solve the above-described problems, and one of the objects of the present invention is to provide an electric component capable of realizing small size and strong coupling, and a partial structure of an electric circuit. That is.

  In order to achieve the above-described object, according to one aspect of the present invention, an electrical component generates a first transmission line for passing a first current and a second current parallel to the first transmission line. At least one second transmission line for flowing, and a metamaterial exhibiting a negative dielectric constant and a negative magnetic permeability with respect to a resonance wavelength component of the electromagnetic field, wherein the metamaterial is an electromagnetic field generated by the first current By exhibiting a negative dielectric constant and a negative magnetic permeability with respect to the resonance wavelength component of the second and the negative dielectric constant and the negative magnetic permeability electromagnetically affect the second transmission line, The position and direction are determined and arranged so that current flows.

  Preferably, the metamaterial includes a first resonator that exhibits a negative dielectric constant with respect to an electromagnetic wave having a resonance wavelength, and the first resonator includes a half-wavelength line having a length that is approximately ½ of the resonance wavelength. The metamaterial further includes a second resonator that exhibits a negative permeability with respect to an electromagnetic wave having a resonance wavelength, and a support member that fixes positions of the first resonator and the second resonator, The support member positions the first resonator and the second resonator so that the magnetic field due to the resonance of the second resonator is concentrated in a region different from the region where the electric field due to the resonance of the first resonator is concentrated. To fix.

  Preferably, the support member fixes the positions of the first resonator and the second resonator so that both ends of the half-wavelength line are located outside the second resonator.

  Preferably, the support member has a position of the first resonator and the second resonator so that charges of the same polarity generated in the first resonator and the second resonator due to resonance are non-interfering with each other. To fix.

  More preferably, the support member fixes the first resonator so that the distances from the first transmission line and the second transmission line at both ends of the half-wavelength line are different.

  More preferably, the second resonator is an LC resonator, and the support member fixes the position of the LC resonator so that the magnetic field generated by the first current passes through the resonance loop of the LC resonator.

  More preferably, the support member fixes the first end of the half-wave line between the second resonator and a surface including the first transmission line and the second transmission line.

  More preferably, the second resonator includes a first outermost electrode and a second outermost electrode having a polarity different from that of the first outermost electrode, and the support member includes the first outermost electrode of the half-wavelength line. The end is fixed between the first outermost electrode and the surface including the first transmission line and the second transmission line.

  More preferably, the support member fixes the first resonator so that potentials at both ends of the half-wavelength line generated by the first current are different.

  More preferably, the support member fixes the position of the second resonator so that the second resonator is magnetically coupled to the magnetic field generated by the first current.

  More preferably, the second resonator includes a first electrode and a second electrode facing the first electrode, and the support member is a resonance formed by the first electrode and the second electrode. The first electrode and the second electrode are fixed so that the loop is substantially parallel to the direction of the electric field generated by the first current.

  Preferably, the metamaterial includes a first resonator that exhibits a negative dielectric constant with respect to an electromagnetic wave having a resonance wavelength, and the first resonator includes a half-wavelength line having a length that is approximately ½ of the resonance wavelength. The metamaterial further includes a second resonator that exhibits a negative permeability with respect to an electromagnetic wave having a resonance wavelength. The second resonator includes a plurality of plate-like electrodes, and the plate-like electrodes include a plurality of plate-like electrodes. Each of the first plate-like electrodes and a plurality of second plate-like electrodes disposed opposite to the first plate-like electrodes, and the second resonator further includes a plurality of first plate-like electrodes. 1st connection part electrically connected, and 2nd connection part which electrically connects a some 2nd plate-like electrode, The 1st arranged on the outermost part among a plurality of plate-like electrodes The outermost electrode and the second outermost electrode are the first plate-like electrode and the second plate-like electrode, respectively, and the metamaterial further includes the first plate-like electrode and the second plate-like electrode. A support member for fixing the position of the resonator and the second resonator, wherein the support member has a first outermost electrode adjacent to the first end of the half-wavelength line, and a second outermost electrode; The positions of the first resonator and the second resonator are fixed so as to be close to the second end of the half-wavelength line.

  More preferably, the first resonator further includes a first conductive plate connected to the first end, and a second conductive plate connected to the second end, and the support member is The first conductive plate is fixed to a position outside the second resonator and facing the first outermost electrode, and facing the second outermost electrode outside the second resonator. The second conductive plate is fixed at the position.

  According to another aspect of the present invention, the electrical component includes a metamaterial exhibiting a negative dielectric constant and a negative permeability with respect to the resonance wavelength component of the electromagnetic field, and the metamaterial is attached to the substrate. A negative dielectric constant and a negative magnetic permeability are exhibited with respect to the resonant wavelength component of the electromagnetic field by the first current flowing through the first transmission line on the substrate, and the negative dielectric constant and the negative magnetic permeability are the substrate By being electromagnetically affected by the second transmission line on the substrate when attached to the substrate, the position and the direction are determined and arranged so that the second current flows through the second transmission line.

  Preferably, the electrical component further includes a ground plane disposed so as to be opposite to the plane including the first transmission line and the second transmission line with the metamaterial interposed therebetween when attached to the substrate. The ground surface has a ground connection portion for electrically connecting to a ground line on the substrate when attached to the substrate.

  According to still another aspect of the present invention, the partial structure of the electric circuit includes at least a first transmission line for passing the first current and a second current parallel to the first transmission line. One second transmission line and a metamaterial exhibiting a negative dielectric constant and a negative permeability with respect to the resonance wavelength component of the electromagnetic field, and the metamaterial is a resonance wavelength component of the electromagnetic field due to the first current And a negative current permittivity and a negative permeability, and the negative permittivity and the negative permeability affect the second transmission line electromagnetically, so that the second current flows. The position and direction are determined and arranged.

  The metamaterial included in the partial structure of the electrical component and the electrical circuit according to the present invention includes a first resonator having a line having a length of approximately ½ of the resonance wavelength and exhibiting a negative dielectric constant at the resonance wavelength; And a second resonator exhibiting negative permeability at the resonance wavelength. These resonators are arranged so that the magnetic field due to the resonance of the second resonator is concentrated in a region different from the region where the electric field due to the resonance of the first resonator is concentrated.

  Further, according to an aspect of the present invention, one outermost electrode is close to one end of a λ / 2 long metal wire, and the other outermost electrode is close to the other end of the metal wire. An arranged capacitor type resonator is used to develop negative magnetic permeability. Here, as the capacitor-type resonator, one having the opposite signs of the charges accumulated in the two outermost electrodes is used. With the above configuration, according to the present invention, it is possible to realize a metamaterial that uses a λ / 2 length metal wire and that simultaneously develops a negative dielectric constant and a negative magnetic permeability. For this reason, the electrical component provided with the left-handed metamaterial which can implement | achieve small coupling | bonding and strong coupling | bonding, and the partial structure of an electrical circuit can be provided.

1 is a schematic external view of a capacitor-type resonator 300. FIG. It is the II-II sectional view taken on the line shown in FIG. It is a figure for demonstrating the resonant circuit formed with the capacitor | condenser type | mold resonator 300 in a resonant frequency. 6 is a diagram illustrating an example of frequency characteristics of relative permeability generated in the capacitor-type resonator 300. FIG. 3 is a diagram showing a metamaterial having a negative dielectric constant using a coiled resonator 100. FIG. It is a figure which shows the relative magnetic permeability of the metamaterial shown in FIG. It is a figure which shows the dielectric constant of the metamaterial shown in FIG. 3 is a diagram illustrating a metamaterial having a negative magnetic permeability using a coiled resonator 100. FIG. It is a figure which shows the relative magnetic permeability of the metamaterial shown in FIG. It is a figure which shows the dielectric constant of the metamaterial shown in FIG. It is a figure which shows the capacitor | condenser type | mold resonator and coil type | mold resonator to which the outermost internal electrode is directly connected. It is a figure which shows the dielectric constant of the resonator group shown in FIG. It is a figure which shows the relative magnetic permeability of the resonator group shown in FIG. It is a figure which shows the metamaterial which concerns on 1st Embodiment. It is a figure which shows the dielectric constant of the resonator group shown in FIG. It is a figure which shows the relative magnetic permeability of the resonator group shown in FIG. It is a figure which shows the structure which changed the structure of the capacitor | condenser type | mold resonator in the metamaterial of 2nd Embodiment. It is the schematic of 2nd Embodiment metamaterial. It is a figure which shows the structure of the metamaterial which concerns on 2nd Embodiment. 3 is a perspective view of a unit 600. FIG. It is the side view which looked at the unit 600 from the y direction. 3 is a perspective view of a unit 700. FIG. 3 is a side view of a unit 700. FIG. 4 is a perspective view of a unit 800. FIG. 3 is a side view of a unit 800. FIG. 4 is a top view of a unit 800. FIG. 2 is a perspective view of a unit 900. FIG. 3 is a front view of a unit 900. FIG. 2 is a side view of a unit 900. FIG. It is a figure for demonstrating the production method of the unit 900 which concerns on 5th Embodiment. It is a figure which shows the structure of the unit 1000 which concerns on 6th Embodiment. It is the figure which showed typically the positional relationship of the metamaterial which combined the split ring type | mold resonator 1210, and the half wavelength resonator 1220, the signal track | line 200, and the ground 220. FIG. It is a figure which shows typically the mode of an electric charge and an electric field when the metamaterial shown in FIG. 32 shows a negative dielectric constant. It is a figure which shows typically the mode of a magnetic field when the metamaterial shown in FIG. 32 shows a negative magnetic permeability. It is the figure which showed typically the positional relationship of the metamaterial from which the arrangement | positioning of a resonator differs from the metamaterial of FIG. 34, the signal track | line 200, and the ground 220. FIG. It is a figure for demonstrating the area | region where an electric field concentrates when the metamaterial shown in FIG. 35 shows a negative dielectric constant. It is a figure for demonstrating the area | region where a magnetic field concentrates when the metamaterial shown in FIG. 35 shows a negative magnetic permeability. 5 is a perspective view of a directional coupler 2100. FIG. 2 is a front view of a directional coupler 2100. FIG. 5 is a side view of a directional coupler 2100. FIG. 3 is a plan view of a directional coupler 2100. FIG. FIG. 10 is a perspective view of a directional coupler 2200. It is a perspective view of the directional coupler part of a multilayer substrate. It is a graph which shows the measurement result of the characteristic of the directional coupler part using a metamaterial. It is a perspective view of the directional coupler part of the multilayer substrate used for a comparative measurement. It is a graph which shows the measurement result of the characteristic of the directional coupler part which does not use a metamaterial.

[Challenges for realizing left-handed metamaterials]
In recent years, devices called metamaterials have attracted attention. This metamaterial is an artificial material having electromagnetic or optical characteristics that a substance existing in nature does not have. Typical properties of such metamaterials include negative permeability (μ <0), negative dielectric constant (ε <0), or negative refractive index (when both permeability and dielectric constant are negative) Is mentioned. The region of μ <0 and ε> 0, or the region of μ> 0 and ε <0 is also referred to as “evanescent solution region”, and the region of μ <0 and ε <0 is also referred to as “left-handed region”. The

  Left-handed metamaterials with μ <0 and ε <0 have a periodic arrangement of elements with negative permittivity and elements with negative permeability in order to simultaneously realize negative permittivity and negative permeability. Made.

  Left-handed metamaterials are broadly classified into circuit systems and resonant systems. As a means for realizing negative μ in the resonance system, for example, there is a split ring resonator (SRR: Split Ring Resonator) (for example, “left-handed metamaterial” (Nikkei Electronics January 2 issue, Nikkei BP) , January 2, 2006, pages 75-81)).

  On the other hand, as means for realizing negative ε, there is a fine metal wire that is sufficiently long with respect to the wavelength of electromagnetic waves. According to this thin metal wire, the plasma frequency is lowered and negative ε is realized. "Low Frequency Plasmons in thin-wire structures" (JB Pendry et al., J. Phys .: Condens. Matter Vol. 10 (1998) 4785-4809) describes that negative ε can be realized by an array of fine metal wires. ing. In Japanese translation of PCT publication No. 2008-507733, there is a description that the wire of the periodic grating has a negative dielectric constant.

  It is also known that a thin metal wire having a length that is half the wavelength λ of an electromagnetic wave generates a negative dielectric constant due to resonance with the electromagnetic wave.

  The metamaterial cannot be miniaturized by a method using a thin metal wire that is sufficiently long with respect to the wavelength of the electromagnetic wave to realize negative ε. Therefore, it is conceivable to use a metal wire having a length that is half the wavelength λ of the electromagnetic wave.

  However, when a left-handed metamaterial is realized by combining a λ / 2 long metal wire with a resonator for realizing negative μ, the λ / 2 long metal wire is a kind of resonator. There is a risk of causing interference with the resonator for realizing negative μ. As a result, the combination of the metal wire and the resonator may not exhibit negative ε and negative μ simultaneously.

  An embodiment of a metamaterial capable of simultaneously expressing a negative dielectric constant and a negative magnetic permeability for solving the above-described problem will be described below.

[About resonators]
The left-handed metamaterial according to the present invention is a resonant system in which resonators are combined. Therefore, first, a resonator constituting the left-handed metamaterial of the present invention will be described.

(Multilayer capacitor type resonator)
One of the resonators used in the present embodiment is a multilayer capacitor type resonator including a plurality of electrodes. In this resonator, a resonance circuit mainly composed of electrostatic capacitance (capacitance) generated between the electrodes is formed. This resonant circuit is sensitive to a specific frequency component of the electromagnetic wave generated by the alternating current flowing in the signal line arranged around the resonator, and generates an electrical resonance phenomenon by receiving the electromagnetic wave of this frequency component. obtain. Due to this resonance phenomenon, negative magnetic permeability appears.

  Here, in order to generate the resonance of the magnetic permeability, which is a function as a metamaterial, the length of each resonator in the propagation direction of the current is at least λ with respect to the wavelength λ of the electromagnetic wave at the frequency to be targeted. Must be shorter than / 4. Furthermore, the length of each resonator in the current propagation direction is preferably λ / 20 or less.

  As the resonator, a multilayer capacitor formed by laminating a plurality of plate electrodes with an insulator (dielectric) can be used. Below, the structure which implement | achieves a resonator using a multilayer capacitor is illustrated. According to this configuration, the resonator can be easily configured using a multilayer capacitor such as a commercially available multilayer ceramic capacitor. However, you may use the electrode member designed exclusively for comprising the resonator which concerns on this invention.

  FIG. 1 is a schematic external view of a capacitor-type resonator 300. Referring to FIG. 1, a capacitor resonator 300 is covered with an exterior part 10 that is a nonmagnetic material. As the exterior portion 10, a resin material such as Teflon (registered trademark) is suitable. The capacitor-type resonator 300 is disposed close to the signal line 200 through which a current including a predetermined frequency component flows, so that it receives a specific frequency component (resonance frequency) of an electromagnetic wave generated by the current and resonates. Arise. A ground 220 is disposed on the surface of the capacitor type resonator 300 opposite to the surface in contact with the signal line 200.

  Resonance in the capacitor-type resonator 300 generates a magnetic flux in the capacitor-type resonator 300 and develops a negative magnetic permeability.

  In order for the capacitor type resonator 300 to exhibit a negative magnetic permeability, that is, to exhibit a negative magnetic permeability that is a function as a metamaterial, in the current propagation direction in the signal line 200 of the capacitor type resonator 300. The length l ′ needs to be at least shorter than λ / 4 with respect to the wavelength λ of the electromagnetic wave at the resonance frequency. Furthermore, the length l of the capacitor resonator 300 is preferably λ / 20 or less.

  Hereinafter, as an example of the capacitor-type resonator 300, a case where a multilayer capacitor having eight layers of internal electrodes having a length l ′ = 1.6 mm, a width W = 0.8 mm, and a height H = 1.2 mm is used is illustrated. To do. The distance h between the signal line 200 and the multilayer capacitor is 0.2 mm, and the distance between the multilayer capacitor and the ground h ′ is 0.2 mm.

  Here, if λ / 4 = length l ′ = 1.6 mm, λ = 6.4 mm, which corresponds to a frequency fmax = 46.875 GHz in the air. Therefore, if this capacitor type resonator 300 is arranged at a pitch of λ / 4 or less, it can be used as a metamaterial in the gigahertz band. As a matter of course, the length l of the resonator can be appropriately designed according to the frequency region to be applied.

  Next, the structure of the capacitor-type resonator 300 will be described with reference to FIGS. 1 and 2. 2 is a cross-sectional view taken along line II-II shown in FIG.

  Referring to FIG. 1, when a current flows through signal line 200, an alternating magnetic field is generated in the circumferential direction around signal line 200. That is, the magnetic field lines of the magnetic field are concentric circles with the signal line 200 as the center. Further, since an electric potential is generated when a current flows through the signal line 200, an alternating electric field is generated between the signal line 200 and the ground 220.

  Referring to FIG. 2, capacitor type resonator 300 includes a plurality of first internal electrodes 4 and a plurality of second internal electrodes 5 that face each other with spacers 6 each being an insulator having a high relative dielectric constant. The plurality of first internal electrodes 4 are electrically connected to the first external electrode 2, and the plurality of second internal electrodes 5 are electrically connected to the second external electrode 3. As described above, in the capacitor-type resonator 300, the plurality of plate-like internal electrodes 4 and 5 are laminated, and the area of the electrode is between the adjacent first internal electrode 4 and second internal electrode 5. Then, a capacitance (capacitance) whose value is determined by the distance between the electrodes, the relative dielectric constant of the spacer 6 and the like is generated.

  The electrode surfaces of the first internal electrode 4 and the second internal electrode 5 constituting the capacitor resonator 300 are arranged so as to be substantially parallel to the magnetic field lines of the magnetic field. At the same time, the electrode surfaces of the first external electrode 2 and the second external electrode 3 are substantially different from the magnetic field lines on the surfaces different from the electrode surfaces of the first external electrode 2 and the second external electrode 3. It arrange | positions so that it may become parallel. That is, as shown in FIG. 2, when the magnetic field lines of the magnetic field generated by the current flowing through the signal line 200 are generated in the front-rear direction of the paper, the capacitor-type resonator 300 includes the first internal electrode 4 and the second internal electrode 5. The electrode cross-section longitudinal direction of the first external electrode 2 and the second external electrode 3 is arranged so that the longitudinal direction of the electrode cross-section coincides with the vertical direction of the paper.

  By arranging the capacitor-type resonator 300 while maintaining the positional relationship as shown in FIG. 2, a resonance circuit as shown in FIG. 3 is formed with respect to a predetermined frequency component. Magnetic susceptibility develops.

  FIG. 3 is a diagram for explaining a resonance circuit formed by the capacitor-type resonator 300 at the resonance frequency.

  Referring to FIG. 3, the first internal electrode 4 and the second internal electrode 5, and the first external electrode 2 and the second external electrode, which are arranged so that the electrode surfaces thereof are substantially parallel to the magnetic field lines of the magnetic field. The electrode 3 acts as a coil (inductor) according to the path length.

  In the capacitor-type resonator 300, the uppermost electrode 4a of the first internal electrodes, the first external electrode 2, and the lowermost electrode 4b of the first internal electrodes are electrically connected to each other. Is formed. Similarly, the uppermost electrode 5a, the second outer electrode 3, and the lowermost electrode 5b of the second internal electrodes are electrically connected to each other, and a current path including these is connected. It is formed. Here, both current paths are electrically connected to each other via the electrostatic capacitance (capacitance C1) between the electrode 4a and the electrode 5a and the electrostatic capacitance (capacitance C2) between the electrode 4b and the electrode 5b. A resonance circuit is formed which is connected and includes capacitances C1 and C2 and inductances L1 to L6 generated by the respective electrodes. Therefore, the capacitor-type resonator 300 according to the present embodiment has a resonance frequency determined by the capacitance (C1 + C2) and the inductance (L1 + L2 + L3 + L4 + L5 + L6), and permeability resonance occurs when an electromagnetic wave having this resonance frequency is incident.

  In the capacitor-type resonator 300, a capacitance is generated between the adjacent internal electrodes. The other capacitances except the uppermost capacitance and the lowest capacitance are the same. The influence on the formation of the resonant circuit is small. This is because current concentrates on the outermost layer of the circulation path causing resonance.

  FIG. 4 is a diagram illustrating an example of frequency characteristics of relative permeability generated in the capacitor-type resonator 300. The change characteristics shown in FIG. 4 are calculated by simulation. Here, the relative magnetic permeability represents a ratio of magnetic permeability to vacuum magnetic permeability.

  Referring to FIG. 4, it can be seen that the capacitor type resonator 300 has about 4.9 GHz as one resonance frequency, and the relative permeability largely fluctuates before and after the resonance frequency, resulting in a negative permeability.

  In the above description, the electrode surfaces of the first internal electrode 4 and the second internal electrode 5, and the first external electrode 2 and the second external electrode 3 are arranged so as to be substantially parallel to the magnetic field lines of the magnetic field. It was described that negative permeability, which is a function as a metamaterial, can be expressed. Here, “substantially parallel” means to exclude the state in which each electrode surface is orthogonal to the magnetic field lines of magnetic force, and in addition to the state in which each electrode surface is completely parallel to the magnetic field lines of magnetic field, Including a state having a predetermined angle. Practically, if the magnitude of the negative magnetic permeability developed in the capacitor-type resonator 300 is a value that can satisfy the requirements of the application, etc., it can be regarded as “substantially parallel”.

(Coil type resonator)
Next, a coil type resonator, which is another type of resonator used in the metamaterial of the present embodiment, will be described. Whereas the capacitor type resonator has a negative magnetic permeability, the coil type resonator is arranged so that the central axis is parallel to the electric field direction (perpendicular to the magnetic field). A negative dielectric constant can be realized. In addition, the coiled resonator arranged so that the central axis is perpendicular to the electric field direction (parallel to the magnetic field direction) can achieve negative magnetic permeability.

  First, the configuration of a metamaterial that develops a negative dielectric constant using a coil-type resonator will be described with reference to FIG. FIG. 5 is a diagram for explaining a configuration of a metamaterial that develops a negative dielectric constant using a coil-type resonator.

  Referring to FIG. 5, the metamaterial includes a coiled resonator 100 and an exterior part 10. The coiled resonator 100 is covered with an exterior part 10 that is a non-magnetic material. The coiled resonator 100 is disposed between the signal line 200 and the ground 220. The ground 220 is disposed on the surface of the exterior portion 10 on the surface opposite to the surface in contact with the signal line 200 of the coiled resonator 100.

  A current including a predetermined frequency component flows through the signal line 200. In the present embodiment, it is assumed that the signal line 200 is a strip line. However, the signal line 200 is an example of a conductor through which a current flows, and the form of the conductor is not limited to this.

  The coil-type resonator 100 is a circuit around a metal wire. The total length of the coiled resonator 100 (the total length of the metal wire) is about half of the wavelength of the current flowing through the signal line 200. Here, the frequency of the current flowing through the signal line 200 is in the GHz band, and the length of the coiled resonator 100 is 28 mm.

  In FIG. 5, the coiled resonator 100 that is wound around the central axis 110, that is, has a spring shape is shown. However, the shape of the coil-type resonator 100 is not limited to that shown in FIG. For example, the coiled resonator 100 may have a shape that is wound along a quadrangular prism. Alternatively, the coiled resonator 100 may have a shape wound along a spherical surface.

  The coiled resonator 100 only needs to have the length and shape as described above. As the coil type resonator 100, a coil wound with a metal wire or the like can be used. As the coil-type resonator 100, a pre-made one (for example, a pre-made coil) may be used, or a dedicated one may be used.

  The exterior part 10 fixes the position of the coiled resonator 100. As the exterior portion 10, a resin material such as Teflon (registered trademark) is suitable. However, the exterior part 10 is an example of a support member that fixes the position of the coiled resonator 100, and the coiled resonator 100 may be fixed by another member.

  The central axis 110 of the coiled resonator 100 is parallel to the electric field generated by the current flowing through the signal line 200, more specifically, the electric field generated between the signal line 200 and the ground 220. That is, the exterior part 10 fixes the coiled resonator 100 so that the central axis 110 is parallel to the electric field. In other words, the coiled resonator 100 is arranged so that there is a difference in potential between both ends of the coil along the gradient of the electric field.

  In the example shown in FIG. 5, the central axis 110 is in the direction from the signal line 200 toward the ground 220. That is, the central axis 110 is orthogonal to the ground 220 plane and penetrates the signal line 200. With this arrangement, the central axis 110 is parallel to the electric field generated by the current flowing through the signal line 200 (perpendicular to the magnetic field generated by the current flowing through the signal line 200).

  With respect to the signal line 200, the coiled resonator 100 receives a specific frequency (resonance frequency) component of the electric field generated by the current flowing through the signal line 200, and causes resonance.

  The electromagnetic properties of the coiled resonator 100 are shown in FIGS. The relative permeability and relative permittivity of the metamaterial shown in FIG. 5 are shown in FIGS. 6 and 7, respectively. Here, the relative dielectric constant represents the ratio of the dielectric constant to the vacuum dielectric constant, and the relative magnetic permeability represents the ratio of the magnetic permeability to the vacuum magnetic permeability. As shown in FIG. 7, the metamaterial of FIG. 5 exhibits a negative dielectric constant near 2.6 GHz. On the other hand, the relative magnetic permeability is always positive as shown in FIG.

  As described above, it can be seen that a negative dielectric constant is exhibited by the coiled metal wire having a length of ½ of the wavelength. Thus, a metamaterial using a coiled metal wire can be made smaller than a metamaterial that achieves a negative dielectric constant using a straight metal wire.

  Next, an example of realizing a metamaterial having a negative magnetic permeability (μ) using a spring-like metal wire will be described. The metamaterial having negative μ is realized by placing the coil type resonator 100 having the same length and shape as the coil type resonator 100 shown in FIG. 5 so that the central axis 110 is parallel to the magnetic field. Is done. The fact that the coiled resonator 100 arranged in this manner exhibits a negative magnetic permeability will be described below with reference to FIGS.

  FIG. 8 is a diagram for explaining a configuration of a metamaterial that develops a negative dielectric constant using a coil-type resonator. The metamaterial shown in FIG. 8 rotates the coiled resonator 100 shown in FIG. 6 90 degrees around the Y axis, and the central axis of the coiled resonator 100 is parallel to the magnetic field generated by the current flowing through the signal line 200 ( It is arranged so as to be perpendicular to the electric field generated by the current flowing through the signal line 200.

  The relative permeability and relative permittivity of the metamaterial shown in FIG. 8 are shown in FIGS. 9 and 10, respectively. As shown in FIG. 9, the metamaterial of FIG. 8 exhibits a negative permeability near 2.6 GHz. On the other hand, as shown in FIG. 10, the relative dielectric constant is always positive.

  By changing the direction of the central axis in this way, it can be seen that the coiled resonator 100 having the same structure may exhibit a negative dielectric constant or a negative magnetic permeability. Coiled resonator 100 arranged so that the central axis direction is non-orthogonal with respect to the magnetic field direction and the electric field direction simultaneously exhibits a negative dielectric constant and a magnetic permeability.

[First Embodiment]
The metamaterial according to the first embodiment of the present invention will be described in which a coil type resonator and a capacitor type resonator are arranged side by side.

  In order for a combination of these resonators to become a left-handed metamaterial, that is, to simultaneously exhibit a negative magnetic permeability and a negative dielectric constant, the arrangement and structure of each resonator are important. First, each resonator must be arranged so that the coil-type resonator exhibits a negative dielectric constant and the capacitor-type resonator exhibits a negative magnetic permeability. Furthermore, it is necessary to consider the structure of the resonator so that the resonators do not cause inappropriate interference.

  In order for the coil type resonator to exhibit a negative dielectric constant, the coil type resonator may be arranged so that its axis is parallel to the electric field direction (the z direction). On the other hand, with respect to the capacitor-type resonator, the inner plate is parallel to the magnetic field direction, that is, a plane (xy plane) normal to the magnetic field direction so that the capacitor-type resonator exhibits a negative magnetic permeability. ) So as to be parallel to each other.

  In addition to the above arrangement conditions, the capacitor-type resonator preferably satisfies the condition that the outermost two internal electrodes are in reverse phase, that is, the signs of charges stored in the internal electrodes are opposite. This is to avoid interference between the capacitor-type resonator and the coil-type resonator. Hereinafter, this will be described in more detail with reference to FIGS.

  FIG. 11 is a diagram showing a capacitor-type resonator and a coil-type resonator to which the outermost internal electrodes are directly connected. These resonators are arranged close to each other. However, the coil type resonator and the capacitor type resonator are not in electrical contact with each other. Since the coiled resonator is placed in an electric field, different signs of charge appear at both ends. FIG. 11 shows a situation where a positive charge (+ in FIG. 11) appears at the upper end and a negative charge (− in FIG. 11) appears at the lower end. At the anti-resonance frequency, the sign of the charge at both ends is reversed, an electric field vector in the opposite direction is generated, and a negative dielectric constant is expressed.

  On the other hand, the uppermost electrode and the lowermost electrode in FIG. 11 of the capacitor-type resonator are electrically connected directly by the uppermost electrode by the external electrode, and therefore store the electric charges having the same sign. FIG. 11 shows a case where the uppermost electrode and the lowermost electrode are negatively charged.

  In the situation shown in FIG. 11, negative charges stored in the adjacent lowermost electrode and the lower end of the coiled resonator interfere with each other. Therefore, negative dielectric constant and negative magnetic permeability do not occur at the same time. That is, the anti-resonance frequency having a negative dielectric constant and the anti-resonance frequency having a negative magnetic permeability do not match.

  This will be specifically described with reference to FIGS. FIG. 12 is a diagram showing the relative dielectric constant of the resonator group shown in FIG. FIG. 13 is a diagram showing the relative permeability of the resonator group shown in FIG.

  FIG. 12 shows the relative dielectric constant characteristics of the entire resonator group when the shape (length, etc.) of the coil-type resonator is changed. According to the shape change of the coil type resonator, the resonance frequency of the dielectric constant changes, and thus the frequency at which the negative dielectric constant is generated changes.

  FIG. 13 shows the relative permeability characteristics of the entire resonator group when the shape (length, etc.) of the coil-type resonator is changed. According to the shape change of the coil type resonator, the resonance frequency of the magnetic permeability changes, and therefore the frequency at which the negative magnetic permeability is generated changes. The change in the resonance frequency of the magnetic permeability despite the fact that the shape of the capacitor type resonator is not changed is due to the interference of the charges at the end of each resonator.

  When the shape of the coiled resonator is changed in this way, both a band where a negative dielectric constant occurs and a band where a negative permeability occurs change. Therefore, the negative dielectric constant and the negative magnetic permeability cannot be expressed at the same frequency. When the frequency indicating the negative dielectric constant (permeability) is increased, the frequency indicating the negative magnetic permeability (dielectric constant) also increases. Conversely, if the frequency indicating the negative dielectric constant (permeability) is decreased, the frequency indicating the negative magnetic permeability (dielectric constant) is also decreased. As described above, a phenomenon occurs in which the resonance frequency of the magnetic permeability (dielectric constant) is separated from the resonance frequency of the dielectric constant (permeability), so that the negative dielectric constant and the negative magnetic permeability are expressed at the same frequency. It is difficult to design a resonator.

  Therefore, in the metamaterial according to the present embodiment, two types of resonators are arranged as shown in FIG. The metamaterial according to the present embodiment includes a coil-type resonator 100, a capacitor-type resonator 300, and an exterior part 10 (not shown in FIG. 14). As in the case shown in FIG. 11, the exterior portion 10 fixes the capacitor-type resonator and the coil-type resonator at positions close to each other. Similar to the above description, other support members may be used instead of the exterior portion 10.

  Since the coil type resonator is placed in an electric field as in the case of FIG. 11, charges having different signs appear at both ends. FIG. 14 also shows a situation where a positive charge (+ in FIG. 14) appears at the upper end and a negative charge (− in FIG. 14) appears at the lower end, as in FIG. At the anti-resonance frequency, the sign of the charge at both ends is reversed, an electric field vector in the opposite direction is generated, and a negative dielectric constant is expressed.

  On the other hand, the capacitor type resonator is different from that shown in FIG. The uppermost electrode and the lowermost electrode in FIG. 14 of the capacitor-type resonator are not electrically directly connected by an external electrode, but are connected via an electric capacity. Therefore, the uppermost electrode and the lowermost electrode are in opposite phases (stores charges with opposite signs). FIG. 14 shows a case where the uppermost electrode has a negative charge and the lowermost electrode has a positive charge.

  In the situation shown in FIG. 14, unlike the situation shown in FIG. 11, interference between charges stored in the adjacent lowermost (or uppermost) electrode and the lower end (or upper end) of the coil resonator is suppressed. Can do. Therefore, a negative dielectric constant and a negative magnetic permeability can be generated simultaneously. That is, the antiresonance frequency having a negative dielectric constant can be matched with the antiresonance frequency having a negative permeability.

  This will be described with reference to FIG. 15 and FIG. FIG. 15 shows the relative dielectric constant characteristics of the entire resonator group when the shape of the coiled resonator is changed. According to the shape change of the coil type resonator, the resonance frequency of the dielectric constant changes, and thus the frequency at which the negative dielectric constant is generated changes.

  FIG. 16 shows the relative permeability characteristics of the entire resonator group when the shape of the coil-type resonator is changed. Even if the shape of the coil-type resonator is changed, the resonance frequency of the magnetic permeability does not substantially change. This is because charge interference at the end of each resonator is suppressed, and the resonance characteristics of the capacitor-type resonator do not change.

  As described above, the metamaterial according to the present embodiment can generate a negative dielectric constant and a negative magnetic permeability at the same time, and becomes a left-handed system.

  14 shows a set of one coil type resonator and one capacitor type resonator, the metamaterial may include a plurality of sets. In this case, for example, the set is fixed by a support member at a one-dimensional or two-dimensional continuous position.

[Second Embodiment]
In the first embodiment, an example is shown in which a coil-type resonator is used as a resonator having a negative ε. However, in the present invention, the resonator having a negative ε is not limited to a coil-type resonator, and a resonator including a line having a length of approximately λ / 2 that resonates with an electromagnetic wave can be used.

  Further, as described in the first embodiment, the resonator having negative ε and the resonator having negative μ (capacitor-type resonator in the first embodiment) are not necessarily arranged side by side. Absent.

  In the second embodiment, as a resonator having negative ε, a resonator including a λ / 2 length line and two conductive plates connected to both ends of the line is used, and a resonator having negative ε. And a configuration in which a capacitor-type resonator having a negative μ is combined in a common space.

  An outline of the configuration of the metamaterial according to the second embodiment will be described with reference to FIGS. 17 and 18. FIG. 18 is a schematic diagram of a metamaterial according to the second embodiment. FIG. 17 shows the metamaterial of the second embodiment in which the configuration of the capacitor type resonator is changed.

  In both FIG. 17 and FIG. 18, two conductive plates are arranged outside the two outermost electrodes of the capacitor-type resonator so as to face each outermost electrode. The conductive plates are connected by a wound line. The line is designed so that its length is approximately λ / 2 of the resonance wavelength.

  Since the track is wound, its length can be secured in a small space. However, the line may not be wound depending on the resonance wavelength or when downsizing is not necessary. 17 and 18 show the line wound in a coil shape, but downsizing is not limited to the method of winding the line, and can be realized by bending the line. For example, a meander line may be used.

  Each conductive plate increases the capacitance between the conductive line and the absolute value of the negative dielectric constant at the resonance frequency. In addition, the substantial length of λ / 2 can be shortened by the wavelength shortening effect due to the capacitance. Depending on the required negative dielectric constant, each conductive plate may not be installed. Further, the conductive plate may be connected to only one end of the line for design reasons.

  The difference between FIG. 17 and FIG. 18 is that in FIG. 17, the two outermost electrodes of the capacitor-type resonator are directly connected, whereas in FIG. In that point. Since the metamaterial according to the present embodiment shown in FIG. 18 can suppress the interference of electric charges similarly to the metamaterial according to the first embodiment, the negative permittivity and the negative permeability can be expressed simultaneously. Can do. In the structure shown in FIG. 17, it is difficult to simultaneously develop a negative dielectric constant and a negative magnetic permeability.

  FIG. 19 shows a specific configuration of the metamaterial according to the present embodiment schematically shown in FIG. Referring to FIG. 19, the metamaterial according to the present embodiment includes a plurality of units 600 in which a negative dielectric constant resonator and a negative magnetic permeability resonator are formed in a substrate material. In this unit, a negative dielectric constant resonator and a negative magnetic permeability resonator are formed in one chip by using a technique such as a multilayer substrate. In this configuration, the substrate material corresponds to the support member.

  Each unit 600 is disposed immediately below the signal line 200 and between the signal line 200 and the ground 220. Each unit 600 is arranged spatially continuously. Although FIG. 19 shows an example in which four units 600 are arranged in a direction along the signal line 200, the arrangement of the units 600 is not limited to this. It is also possible to arrange the one-dimensionally arranged resonators in the same plane to form a planar metamaterial. Furthermore, a planar metamaterial can be stacked to form a three-dimensional metamaterial.

  The structure of the unit 600 will be described with reference to FIGS. FIG. 20 is a perspective view of the unit 600. FIG. 21 is a side view of the unit 600 as viewed from the y direction.

  As shown in FIG. 20, the unit 600 includes an uppermost electrode 610a, a lowermost electrode 610b, a first internal electrode 622, a second internal electrode 624, a third internal electrode 632, and a fourth An internal electrode 634 and a line 640 are provided. As shown in FIG. 21, the unit 600 further includes a first external electrode 650 and a second external electrode 660.

  The uppermost electrode 610a is disposed above the first internal electrode 622, the second internal electrode 624, the third internal electrode 632, and the fourth internal electrode 634 (at a position where the z coordinate is large). The lowermost electrode 610b is disposed below the first internal electrode 622, the second internal electrode 624, the third internal electrode 632, and the fourth internal electrode 634 (where the z coordinate is small). The uppermost electrode 610a has a side surface portion extending in the −z direction. The lowermost electrode 610b has a side surface portion extending in the + z direction. Further, the uppermost electrode 610 a is disposed directly below the signal line 200.

  The line 640 connects the side surface portion extending in the −z direction of the uppermost electrode 610a and the side surface portion extending in the + z direction of the lowermost electrode 610b. The line 640 functions as a part of a λ / 2 line that realizes a negative dielectric constant by connecting the uppermost electrode 610a and the lowermost electrode 610b to each side surface portion.

  The length of the line constituted by the line 640 and each side surface portion is designed according to the resonance frequency. Here, in order to take the length of λ / 2, the line 640 is a meander line drawn in the center layer. However, the shape of the line 640 is not limited to this, and may be helical or spiral, for example.

  The uppermost electrode 610a and the lowermost electrode 610b are provided for increasing the absolute value of the negative dielectric constant and shortening the resonance wavelength. The resonance wavelength is shortened by the wavelength shortening effect due to the capacitance between the uppermost electrode 610a and the signal line. The uppermost electrode 610a and the lowermost electrode 610b can be omitted depending on the required negative dielectric constant and resonance wavelength.

  The first internal electrode 622 and the second internal electrode 624 are disposed in close proximity to each other. In addition, the third internal electrode 632 and the fourth internal electrode 634 are disposed close to and opposed to each other. A pair of first internal electrode 622 and second internal electrode 624 (referred to as an upper electrode pair) is disposed on the uppermost electrode 610a side. A pair of the third internal electrode 632 and the fourth internal electrode 634 (referred to as a lower electrode pair) is disposed on the lowermost electrode 610b side. Each internal electrode surface is disposed in parallel to the direction of the magnetic field generated by the current flowing through the signal line 200 (perpendicular to the electric field direction).

  As shown in FIG. 21, the first external electrode 650 connects the first internal electrode 622 and the third internal electrode 632. As shown in FIG. 21, the second external electrode 660 connects the second internal electrode 624 and the fourth internal electrode 634. Each external electrode surface is disposed parallel to the direction of the magnetic field generated by the current flowing through the signal line 200 (perpendicular to the electric field direction).

  The above-described line 640, the uppermost electrode 610a, and the lowermost electrode 610b realize a negative dielectric constant. The first to fourth internal electrodes 622, 624, 632, 634, the first external electrode 650, and the second external electrode 660 form a capacitor-type resonator having two upper and lower electrodes, and are negative. Realize permeability. Of course, the λ / 2 line that realizes the negative dielectric constant and the capacitor-type resonator that realizes the negative magnetic permeability are not directly electrically connected to each other. Further, the λ / 2 line and the capacitor type resonator are not electrically connected to the signal line 200 and the ground 220, and are in a floating state. Further, the units 600 are not in contact with each other.

  By disposing the units 600 as described above continuously spatially, the metamaterial according to the present embodiment functions as a left-handed metamaterial. Note that the arrangement of the units 600 is not limited to the above. For example, it may be arranged two-dimensionally in a plane.

  Since the metamaterial according to the present embodiment is created by creating a negative dielectric constant resonator and a negative magnetic permeability resonator in the unit, industrial manufacture is easy.

[Third Embodiment]
In the third embodiment, a metamaterial using a split ring type resonator instead of the capacitor type resonator in the second embodiment will be described.

  The structure of one unit 700 of the metamaterial according to the third embodiment is shown in FIGS. FIG. 22 is a perspective view of the unit 700. FIG. 23 is a side view of the unit 700.

  Referring to FIG. 22, unit 700 includes an uppermost electrode 710a, a lowermost electrode 710b, a first internal electrode 722, a second internal electrode 724a, a third internal electrode 724b, and a fourth An internal electrode 730 and a line 740 are provided. Referring to FIG. 23, unit 700 further includes a first external electrode 750 and a second external electrode 760.

  The uppermost electrode 710a and the lowermost electrode 710b have the same structure as the uppermost electrode 610a and the lowermost electrode 610b according to the second embodiment, and are arranged outside the internal electrodes.

  The line 740 connects the uppermost electrode 710a and the lowermost electrode 710b. The line 740 functions as a part of the λ / 2 line and realizes a negative dielectric constant, like the line 640 of the second embodiment. In the present embodiment, the line 740 has a helical structure that makes a half turn in the horizontal plane.

  The second internal electrode 724a and the third internal electrode 724b are arranged apart from each other in the same plane. The first external electrode 750 connects the second internal electrode 724 a and the fourth internal electrode 730. The second external electrode 760 connects the third internal electrode 724 b and the fourth internal electrode 730. That is, the second internal electrode 724a, the first external electrode 750, the third internal electrode 724b, the second external electrode 760, and the third internal electrode 730 have a structure similar to that of the split ring resonator. . Therefore, these electrodes develop a negative magnetic permeability.

  The first internal electrode 722 is disposed so as to face the second internal electrode 724a and the third internal electrode 724b so as not to be in electrical contact with the second internal electrode 724a and the third internal electrode 724b. The The first internal electrode 722 supplements the capacitance at the break between the second internal electrode 724a and the third internal electrode 724b, and serves to lower the resonance frequency.

[Fourth Embodiment]
As another example of a metamaterial in which a resonator for a negative dielectric constant and a resonator for a negative magnetic permeability are formed in one chip, a resonator for a negative magnetic permeability is provided in a coil arranged in the periphery. You can also make things that you place. In the fourth embodiment, an example of such a metamaterial is shown.

  A structure of one metamaterial unit 800 according to the fourth embodiment will be described with reference to FIGS. 24, 25, and 26. FIG. 24 is a perspective view of the unit 800. FIG. 25 is a side view of the unit 800. FIG. 26 is a top view of the unit 800.

  The unit 800 includes a coiled conductor 810, a first electrode 822, a second electrode 824, a third electrode 832, a fourth electrode 834, a first via 842, and a second via 844. With.

  The coiled conductor 810 circulates a plurality of regions (eight times in the example shown here) near the surface of the unit 800. The coiled conductor 810 is disposed so as to surround the first electrode 822, the second electrode 824, the third electrode 832, the fourth electrode 834, the first via 842, and the second via 844.

  The first electrode 822 and the second electrode 824 are disposed in close proximity to each other. Further, the first electrode 822 and the second electrode 824 are arranged with their positions in the horizontal plane being shifted from each other.

  The third electrode 832 and the fourth electrode 834 are disposed in close proximity to each other. In addition, the third electrode 832 and the fourth electrode 834 are arranged with their positions in the horizontal plane shifted from each other.

  The pair of the first electrode 822 and the second electrode 824 is formed in the upper part in the unit 800. The pair of the third electrode 832 and the fourth electrode 834 is formed in the lower part in the unit 800. In addition, the upper part and the lower part here are based on FIG. 24 and FIG.

  The first via 842 connects the first electrode 822 and the third electrode 832. The second via 844 connects the second electrode 824 and the fourth electrode 834.

  With the above structure, the first to fourth electrodes 822, 824, 832, 834, the first via 842, and the second via 844 function as a capacitor-type resonator and exhibit negative magnetic permeability.

  According to the configuration of the present embodiment, the length of the line (coil) can be increased while maintaining the size of the unit as compared with the second and third embodiments. Therefore, a low resonance frequency can be obtained.

[Fifth Embodiment]
In the unit for creating the metamaterial according to the third embodiment or the fourth embodiment (metamaterial unit), the negative magnetic permeability resonator is an external electrode for connecting the internal electrode. Had. On the other hand, in the negative permeability resonator according to the present embodiment, the conductive portion for connecting the internal electrode is realized by a via.

  The structure of one metamaterial unit 900 according to the fifth embodiment is shown in FIGS. FIG. 27 is a perspective view of the unit 900. FIG. 28 is a front view of the unit 900. FIG. 29 is a side view of the unit 900.

  27 to 29, the unit 900 includes an uppermost electrode 910a, a first via 912a, a second via 912b, a lowermost electrode 910b, a first internal electrode 922, and a second The internal electrode 924a, the third internal electrode 924b, the fourth internal electrode 930, the line 940, the third via 950, and the fourth via 960 are provided.

  The first via 912a, the line 940, and the second via 912b connect the uppermost electrode 910a and the lowermost electrode 910b.

  The total length of the first via 912a, the line 940, and the second via 912b is approximately half the resonance wavelength. The first via 912a, the line 940, and the second via 912b function as part of the λ / 2 line and realize a negative dielectric constant. The shape of the line 940 is not limited to the meander line shown in the figure, and may be helical or spiral, for example.

  The uppermost electrode 910a and the lowermost electrode 910b exhibit the functions of increasing the absolute value of the negative dielectric constant and shortening the resonance wavelength, like the uppermost electrode 610a and the lowermost electrode 610b shown in FIG. However, the uppermost electrode 910a and the lowermost electrode 910b can be omitted.

  The outer end of the first via 912a (the end not connected to the line 940) and the outer end of the second via 912b (the end not connected to the line 940) are Regardless of the presence or absence of the upper electrode 910a and the lowermost electrode 910b, it is preferable to be outside the negative permeability resonator so that charges are accumulated at both ends of the λ / 2 line.

  The third via 950 connects the second internal electrode 924 a and the third internal electrode 930. The fourth via 960 connects the third internal electrode 924 b and the third internal electrode 930. The second internal electrode 924a, the third via 950, the third internal electrode 924b, the fourth via 960, and the third internal electrode 930 have the same structure as the split ring type resonator, and are negative. It functions as a resonator that exhibits magnetic permeability. The first internal electrode 922 compensates for the capacitance of the cut portion between the second internal electrode 924a and the third internal electrode 924b, similarly to the first internal electrode 722 of the fourth embodiment. It plays a role of lowering the resonance frequency.

  Unit 900 according to the present embodiment does not require an external electrode. This unit is therefore easy to manufacture. When a unit including an external electrode is created, usually, after a portion other than the external electrode is laminated, the external electrode is attached to the laminated part. On the other hand, the unit 900 according to the present embodiment can be created only by stacking.

  The unit 900 is suitable for creating a metamaterial in which a plurality of units are arranged. When units having external electrodes come into contact with each other, the current flowing through the external electrode of one unit also flows through the external electrode of the other unit, and electromagnetic wave resonance does not occur appropriately. Therefore, it is necessary to perform unit processing such as arranging the units apart from each other or covering the external electrode with an insulator. Since the units 900 according to the present embodiment can be arranged adjacent to each other, the metamaterial can be further reduced. Further, since no processing is required, creation of a metamaterial using the unit 900 is easy.

  A method of creating the unit 900 will be described with reference to FIG. FIG. 30 is a diagram for explaining a method of creating the unit 900 according to the sixth embodiment.

  Referring to FIG. 30, unit 900 is created by sequentially stacking a plurality of layers. In FIG. 30, layers L1 to L6 including main components of the unit 900 are shown. The material (substrate material) of each layer is an insulating material such as a resin. Metal parts are formed on several layers of substrate material. Further, vias are formed in some layers of the substrate material so as to penetrate the substrate material. FIG. 30 shows a part of the layers L1 to L6. Actually, the layers L1 to L6 further extend in the lateral direction in FIG.

  In each of the layers L1 to L6, a plurality of (3 × 3 in FIG. 30) unit components arranged periodically are arranged. The layer L1 includes a plurality of bottom electrodes 910b. The layer L2 includes a plurality of fourth internal electrodes 930. The layer L3 includes a plurality of lines 940. The layer L4 includes a plurality of pairs of the second internal electrode 924a and the third internal electrode 924b. The layer L5 includes a plurality of first internal electrodes 922. Layer L6 includes a plurality of top electrodes 910a.

  In each layer, vias are formed in regions corresponding to the first via 912a, the second via 912b, the third via 950, and the fourth via 960. In FIG. 27, vias are indicated by vertical thin lines.

  After the layers are stacked to form a stacked body, the stacked body is cut to create a unit 900. Nine units 900 are formed from the portion shown in FIG. In addition, instead of separating the laminated body into each unit 900, several units 900 may be cut out from the laminated body as a group.

  In this embodiment, the structure in which the conductive portion of the split resonator shown in the third embodiment is a via is shown, but the conductive portion of another type of resonator can be a via. . For example, the external electrode of the multilayer capacitor type resonator shown in the second embodiment may be a via.

[Sixth Embodiment]
In the metamaterial unit according to the second, third, and fifth embodiments, a line for expressing a negative dielectric constant is connected to an LC resonator (specifically, a multilayer capacitor type resonator and a split type resonator). ). However, the line does not necessarily have to be inside the LC resonator. In the sixth embodiment, a unit 1000 in which a λ / 2 line is disposed outside the LC resonator will be described.

  FIG. 31 shows the structure of a unit 1000 according to the sixth embodiment. FIG. 31 is a diagram showing a structure of a unit 1000 according to the sixth embodiment.

  Referring to FIG. 31, unit 1000 includes an uppermost electrode 1010a, a first via 1012, a lowermost electrode 1010b, a first internal electrode 1022, a second internal electrode 1024a, and a third internal electrode. An electrode 1024b, a fourth internal electrode 1030, a second via 1050, and a third via 1060 are provided.

  The first via 1012 connects the uppermost electrode 1010a and the lowermost electrode 1010b. The length of the first via 1012 is approximately ½ of the resonance wavelength. Therefore, the first via 1012 exhibits a negative dielectric constant with respect to the electromagnetic wave having the resonance wavelength.

  In the present embodiment, the uppermost electrode 1010a and the lowermost electrode 1010b are connected by a straight first via 1012. However, a λ / 2 line may be realized by combining a plurality of vias and a line in a horizontal plane as in the structure shown in FIG. In order to reduce the size of the unit, the line in this case is preferably a bent one such as a meander line as described in other embodiments.

  The top electrode 1010a and the bottom electrode 1010b, like the top electrode 910a and the bottom electrode 910b in the fifth embodiment, increase the absolute value of the negative dielectric constant and reduce the resonance frequency. To do.

  The second internal electrode 1024a, the first via 1050, the third internal electrode 1024b, the third internal electrode 1030, the second via 1060, and the third internal electrode 1024b are formed of a split ring resonator. It has the same structure and functions as a resonator that develops negative magnetic permeability. Similar to the first internal electrode 722 of the fourth embodiment, the first internal electrode 1022 compensates for the capacitance of the cut portion between the second internal electrode 1024a and the third internal electrode 1024b, It plays a role of lowering the resonance frequency.

  The first internal electrode 1022, the second internal electrode 1024 a, the first via 1050, the third internal electrode 1024 b, the second via 1060, and the third internal electrode 1030 are the top electrode 1010 a and the bottom part It arrange | positions in the space pinched | interposed into the electrode 1010b. That is, in the unit according to the present embodiment, a resonator that expresses a negative magnetic permeability is formed in a resonator that develops a negative dielectric constant.

  Similar to the unit 900 according to the fifth embodiment, the unit 1000 according to the present embodiment can be easily created because the internal electrodes are connected by vias. Moreover, since the unit 1000 does not have an electrode on the surface of the unit, it is suitable for creating a metamaterial.

[Supplement]
The positional relationship of the resonators for allowing the metamaterial to simultaneously exhibit a negative dielectric constant and a negative magnetic permeability at a certain resonance frequency will be summarized. Here, a metamaterial (or metamaterial unit) in which a split ring type resonator and a half-wavelength resonator are combined as described in the fifth embodiment will be described as an example.

  FIG. 32 is a diagram schematically showing the positional relationship between a metamaterial that combines the split ring resonator 1210 and the half-wave resonator 1220, the signal line 200, and the ground 220. As described in the fifth embodiment, this metamaterial simultaneously exhibits a negative magnetic permeability and a negative dielectric constant. This is because the region where the electric field concentrates when the metamaterial resonates with the electromagnetic field does not overlap the region where the magnetic field concentrates.

  A region where the electric field concentrates will be described with reference to FIG. FIG. 33 is a diagram schematically showing the state of electric charge and electric field when the metamaterial shown in FIG. 32 shows a negative dielectric constant. Referring to FIG. 33, half-wave resonator 1220 includes a first outermost electrode 1222, a second outermost electrode 1224, and a line 1226. The first outermost electrode 1222 is disposed on the signal line 200 side. The second outermost electrode 1244 is disposed on the ground 220 side.

  FIG. 33 shows a situation where a current flows through the signal line 200 and an electric field from the signal line 200 toward the ground 220 is generated. When a current having a resonance frequency flows, negative charge is accumulated in the first outermost electrode 1222 and positive charge is accumulated in the second outermost electrode 1224. A large electric field is generated in a region 1230 between the first outermost electrode 1222 and the signal line 200 and a region 1240 between the second outermost electrode 1224 and the ground 220.

  That is, the region sandwiched between the end portion of the half-wave resonator 1220 where charges are accumulated by the half-wave resonance and the signal line 200 or the ground is a region where the resonance electric field is concentrated. Here, the electrodes connected to both ends of the half-wavelength line correspond to the ends of the half-wave resonator 1220. However, when the half-wave resonator 1220 does not include an electrode, both ends of the half-wave line correspond to end portions of the half-wave resonator 1220.

  The region where the magnetic field is concentrated will be described with reference to FIG. FIG. 34 is a diagram schematically illustrating the state of the magnetic field when the metamaterial illustrated in FIG. 32 exhibits negative magnetic permeability. Referring to FIG. 34, split ring resonator 1210 includes a first conductor 1212 and a second conductor 1214.

  FIG. 34 shows a situation where a current flows through the signal line 200 and a magnetic field is generated from the split ring resonator 1210. When a current having a resonance frequency flows, the current and the split ring resonator 1210 LC resonate, and a large magnetic field cancels out the magnetic field generated by the current flowing through the signal line 200 in the region 1250 inside the second conductor 1214. Occur. The generated magnetic field is mainly orthogonal to the paper surface.

  That is, the internal region of the loop where LC resonance occurs is a region where the magnetic field due to resonance concentrates. In other words, the space surrounded by the electrode pair that forms the capacitance and the conductive portion that forms the inductance is the region where the magnetic field due to resonance is concentrated.

  33 and FIG. 34, the region where the electric field concentrates (region 1230 and region 1240) and the region where the magnetic field concentrates (region 1250) are separated from each other. Therefore, the electric field generated by the resonance of the half-wave resonator 1220 hardly affects the resonance of the split ring resonator 1210. The reverse is also true. Therefore, the metamaterial shown in FIG. 32 can simultaneously exhibit a negative dielectric constant and a negative magnetic permeability. In the metamaterial having the structure shown in FIG. 32, the magnetic field generated by the magnetic permeability resonance is concentrated in a region different from the region where the electric field generated by the dielectric resonance is concentrated.

  For comparison, a metamaterial in which the positional relationship between the split ring resonator and the half-wave resonator is changed will be described with reference to FIGS.

  FIG. 35 is a diagram schematically showing the positional relationship between a metamaterial having a different resonator arrangement from the metamaterial of FIG. 34, the signal line 200, and the ground 220.

  The metamaterial shown in FIG. 35 includes a split ring resonator 1310 and a half-wave resonator 1320. The split ring type resonator 1310 includes a first conductor 1312 and a second conductor 1314. The half-wave resonator 1320 is entirely disposed in the second conductor 1314.

  In this metamaterial, there is an overlap between a region where the electric field concentrates and a region where the magnetic field concentrates when the metamaterial resonates with the electromagnetic field. For this reason, it is somewhat difficult to stably express negative magnetic permeability and negative dielectric constant at the same time.

  A region where the electric field is concentrated is shown in FIG. FIG. 36 is a diagram for explaining a region where an electric field concentrates when the metamaterial shown in FIG. 35 exhibits a negative dielectric constant. Referring to FIG. 36, half-wave resonator 1320 includes a first outermost electrode 1322, a second outermost electrode 1324, and a line 1326. The first outermost electrode 1322 is disposed on the signal line 200 side. The second outermost electrode 1344 is disposed on the ground 220 side.

  When a negative dielectric constant is generated, a large electric field is generated in a region 1330 between the first outermost electrode 1322 and the signal line 200 and a region 1340 between the second outermost electrode 1324 and the ground 220. .

  The region where the magnetic field is concentrated will be described with reference to FIG. FIG. 37 is a diagram for explaining a region where a magnetic field concentrates when the metamaterial shown in FIG. 35 exhibits negative magnetic permeability. When the negative magnetic permeability is developed, a large magnetic field is generated in the region 1350 inside the second conductor 1314 in a direction that cancels the magnetic field generated by the current flowing through the signal line 200.

  36 and 37, a part of the region where the electric field concentrates (region 1330 and region 1340) and a part of the region where the magnetic field concentrates (region 1350) overlap. Therefore, the electric field generated by the resonance of the half-wave resonator 1220 affects the resonance of the split ring resonator 1210. The reverse is also true. Therefore, it is somewhat difficult for the metamaterial shown in FIG. 35 to develop a negative dielectric constant and a negative magnetic permeability at the same time.

  The above description also applies to metamaterials having other types of resonators. For example, the above description also applies to a metamaterial in which a split resonator is replaced with a multilayer capacitor resonator.

  However, when a multilayer capacitor type resonator is used, it is preferable that charges having the same polarity are non-interfering as described in the first embodiment and the second embodiment. That is, it is preferable that the resonator is configured so that charges of the same polarity are generated so far as not to affect each other's expression. Specifically, it is preferable that the polarity of the outermost two outermost electrodes among the plurality of electrodes forming the electrostatic capacitance is opposite.

[Seventh Embodiment]
In the first embodiment to the sixth embodiment, a single metamaterial has been described. In the seventh embodiment, a directional coupler 2100 that is an electrical component using a metamaterial will be described.

  The structure of the directional coupler 2100 using the metamaterial according to the seventh embodiment is shown in FIGS. FIG. 38 is a perspective view of the directional coupler 2100. FIG. 39 is a front view of the directional coupler 2100. FIG. 40 is a side view of the directional coupler 2100. FIG. 41 is a plan view of the directional coupler 2100. FIG.

  Referring to FIGS. 38 to 41, directional coupler 2100 includes a first transmission line 2180, a second transmission line 2190, and a metamaterial portion. The first transmission line 2180 is configured by electrically connecting first transmission lines 2180a, 2b, and 2c in order. The second transmission line 2190 is configured by electrically connecting second transmission lines 2190a, 2190, and 2190c in order.

  The first transmission line 2180b and the second transmission line 2190b are opposite surfaces across the metamaterial portion with respect to the attachment surface of the directional coupler 2100 to the substrate (surface in the z-axis positive direction with respect to the metamaterial portion). In this embodiment, for convenience, they are referred to as “metamaterial upper surface”) in parallel.

  When the directional coupler 2100 is attached to the substrate, the first transmission line 2180a is electrically connected to a line on the substrate for inputting an input current to the directional coupler 2100. With respect to the side surface in the y-axis negative direction.

  When the directional coupler 2100 is attached to the substrate, the first transmission line 2190c is electrically connected to a line on the substrate for outputting a passing current from the directional coupler 2100. With respect to the side surface in the positive y-axis direction.

  Thereby, the input current input from the line on the substrate for inputting the input current is in the order of the first transmission line 2180a, the first transmission line 2180b, and the first transmission line 2180c in the order of the directional coupler 2100. Is output to a line on the substrate for outputting a passing current.

  When the directional coupler 2100 is attached to the substrate, the second transmission line 2190a can be electrically connected to a line on the substrate for outputting a backward-coupled output current from the directional coupler 2100. The metamaterial portion is disposed on the side surface in the y-axis negative direction in parallel with the first transmission line 2180a.

  When the directional coupler 2100 is attached to the substrate, the second transmission line 2180c can be electrically connected to a line on the substrate for outputting a forward-coupled output current from the directional coupler 2100. It arrange | positions in parallel with the 1st transmission line 2180c on the side surface of a y-axis positive direction with respect to a metamaterial part.

  Thereby, the output current of the backward coupling is output to the line on the substrate for outputting the output current of the backward coupling in the order of the second transmission line 2190b and the second transmission line 2190a. The forward-coupled output current is output to the line on the substrate for outputting the forward-coupled output current in the order of the second transmission line 2190b and the second transmission line 2190c.

  The metamaterial portion is basically the same as the structure of the metamaterial unit 900 described in the fifth embodiment. The metamaterial portion includes an uppermost electrode 2110a, a first via 2112a, a second via 2112b, a lowermost electrode 2110b, a first internal electrode 2122, a second internal electrode 2124a, and a third An internal electrode 2124b, a fourth internal electrode 2130, a line 2140, a third via 2150, and a fourth via 2160 are provided, and their functions and structures are the same as those of the metamaterial of the fifth embodiment. In the unit 900, the uppermost electrode 910a, the first via 912a, the second via 912b, the lowermost electrode 910b, the first internal electrode 922, the second internal electrode 924a, the third internal electrode 924b, the fourth This is the same as the internal electrode 930, the line 940, the third via 950, and the fourth via 960.

  The structure in which the uppermost electrode 2110a, the first via 2112a, the line 2140, the second via 2112b, and the lowermost electrode 2110b are electrically connected in this order forms a half-wave resonator.

  The first internal electrode 2122, the second internal electrode 2124a, the third via 2150, the fourth internal electrode 2130, the fourth via 2160, the third internal electrode 2124a, and the first internal electrode 2122 in this order A structure equivalent to an LC resonance circuit configured to make a circuit in the above constitutes an LC resonator.

  Note that the first transmission line 2180, the second transmission line 2190, and the metamaterial portion are not in electrical contact with each other.

  The first transmission line 2180 and the second transmission line 2190 on the upper surface of the metamaterial described above have a width between the outer sides of the respective transmission lines that is substantially parallel to the uppermost electrode 2110a of the half-wave resonator. Are arranged so as to be narrower than the width in the x-axis direction of the uppermost electrode 2110a when projected from the negative z-axis direction.

  The positional relationship between the first transmission line 2180 and the metamaterial portion is such that the negative dielectric constant and negative with respect to a component having substantially the same wavelength as the resonance wavelength of the metamaterial of the electromagnetic field due to the current flowing through the first transmission line 2180b. It is determined to indicate magnetic permeability.

  The positional relationship between the second transmission line 2190 and the metamaterial portion is determined such that the negative dielectric constant and the negative magnetic permeability expressed by the metamaterial portion have an electromagnetic influence on the second transmission line 2190b. .

  The positional relationship between the first transmission line 2180 and the metamaterial portion is such that each of both ends of the λ / 2 line constituted by the first via 2112a, the line 2140, and the second via 2112b of the half-wave resonator, The distance from the first transmission line 2180b is determined to be different.

  The positional relationship between the second transmission line 2190 and the metamaterial portion is determined so that the distances from the second transmission line 2190b at both ends of the λ / 2 line of the half-wave resonator are different.

  The direction of the first transmission line 2180 is determined so that the magnetic field lines of the magnetic field generated by the current flowing through the first transmission line 2180b pass through the LC resonance circuit equivalent to the LC resonator.

  The positional relationship between the first transmission line 2180 and the second transmission line 2190 and the metamaterial portion is such that the end of the above-mentioned metamaterial upper surface side of the λ / 2 line is closest to the metamaterial upper surface side of the LC resonator. It is determined to be between the first inner electrode 2122 which is an outer electrode and the upper surface of the metamaterial on which the first transmission line 2180b and the second transmission line 2190b are arranged.

  The positional relationship between the first transmission line 2180 and the metamaterial portion is such that the potentials at both ends of the λ / 2 line of the half-wave resonator are different based on the electric field generated by the current flowing through the first transmission line 2180b. It is determined as follows.

  The positional relationship between the first transmission line 2180 and the metamaterial portion is determined so that the LC resonator is magnetically coupled to the magnetic field generated by the current flowing through the first transmission line 2180b.

  The positional relationship between the first transmission line 2180 and the metamaterial part is the first internal electrode 2122, the second internal electrode 2124a, the third internal electrode 2124b, and the fourth internal electrode 2130 of the LC resonator. The formed LC resonance circuit surface is determined so as to be substantially parallel to the direction of the electric field generated by the current flowing through the first transmission line 2180b.

  In the present embodiment, the first transmission line 2180 and the second transmission line 2190 are not only on the upper surface of the metamaterial but also on the side surface so as to be electrically connected to the line on the substrate. Is extended to. However, the present invention is not limited to this, and when the upper surface side of the metamaterial is an attachment surface, it is not necessary to extend the first transmission line 2180 and the second transmission line 2190 to the side surface.

  As for the manufacturing method, after the metamaterial part is manufactured by the manufacturing method described with reference to FIG. 30, the first transmission line 2180 and the second transmission line 2190 are formed on the surface of the metamaterial part. It can be manufactured by covering the surface with an insulator or the like so as to shield the portions other than the connection portion between the transmission line 2180 and the second transmission line 2190 and the line on the substrate.

  The directional coupler performs backward coupling by the difference in impedance between the even mode and the odd mode. Since the difference is limited in the coupling line of a normal directional coupler, coupling does not increase.

  However, since the impedance becomes an imaginary number by using the left-handed metamaterial, a large difference can be made, so that a small and strong coupling directional coupler can be realized.

  In order to realize a left-handed system, there are a circuit type and a resonance type with an HPF structure, and both are the same in that the impedance can be made an imaginary number. Therefore, a strong coupling directional coupler can be realized. However, since the resonance type has an advantage that it is easy to downsize, it is possible to realize a directional coupler that is smaller than the circuit type of the HPF structure.

  In FIGS. 38 to 41, the first transmission line 2180 and the second transmission line 2190 are depicted as being exposed to the outside for convenience of explanation. A part other than the part connected to the line on the substrate when attached is shielded electrically from the outside by an insulator.

  Moreover, it is preferable that a ground line is provided on the mounting surface of the mounting board to which the directional coupler 2100 is attached.

  In the present embodiment, the metamaterial unit 900 described in the fifth embodiment is basically used in the metamaterial portion having the same structure. However, the present invention is not limited to this, and metamaterials having other structures described in other embodiments may be used.

  In this embodiment, the metamaterial portion is composed of one metamaterial unit. However, the metamaterial portion is composed of a plurality of metamaterial units having the same or different resonance wavelengths. May be.

  In the present embodiment, the number of second transmission lines 2190 is one. However, it is not limited to this and may be two or more.

  In the present embodiment, the electrical component using the metamaterial is a directional coupler. However, in this directional coupler, since the coupling is close to 0 dB, the electrical component using the metamaterial may be a diplexer. That is, when used as a diplexer, a current having a frequency component corresponding to the resonance wavelength among currents entering the first transmission line 2180 can be output to one end of the second transmission line 2190, and the remaining frequency components Can be output from the other end of the first transmission line 2180.

[Eighth Embodiment]
In the seventh embodiment, the directional coupler 2100 using a metamaterial including a transmission line has been described. In the eighth embodiment, a directional coupler 2200 using a metamaterial that does not include a transmission line will be described.

  The structure of the directional coupler 2200 using the metamaterial according to the eighth embodiment is shown in FIG. FIG. 42 is a perspective view of the directional coupler 2200.

  Referring to FIG. 42, directional coupler 2200 includes a metamaterial portion and a ground plane 2201. The ground surface 2201 is configured by electrically connecting the ground surfaces 2201a, b, and c in order.

  Since the metamaterial part of directional coupler 2200 of the present embodiment is the same as the metamaterial part of directional coupler 2100 described in the seventh embodiment, the overlapping description will not be repeated.

  The ground surface 2201b is formed on an opposite surface (referred to as “metamaterial upper surface” for the sake of convenience in this embodiment) across the metamaterial portion with respect to the mounting surface of the directional coupler 2200 to the substrate 2300.

  The ground planes 2201a and 220c are parallel to an LC resonance circuit equivalent to the LC resonator of the metamaterial portion so that when the directional coupler 2200 is attached to the substrate, it can be electrically connected to the ground line 2301 on the substrate. Placed on the side.

  The substrate 2300 to which the directional coupler 2200 is attached is provided with a ground line 2301 so that any one of the ground surfaces 2201a and c of the directional coupler 2200 can be connected, and in the seventh embodiment. The metamaterial of the directional coupler 2200 of the present embodiment so as to have the same positional relationship as the positional relationship between the metamaterial portion of the directional coupler 2100 and the first transmission line 2180 and the second transmission line 2190. It is necessary to provide the first transmission line 2380 and the second transmission line 2390 so that the positional relationship between the portion and the first transmission line 2380 and the second transmission line 2390 on the substrate 2300 is determined. .

  In addition, it is preferable not to provide a ground portion on the back side of the attachment portion of the directional coupler 2200 of the substrate 2300 in order to suppress coupling with the transmission line on the substrate.

[Ninth Embodiment]
In the seventh and eighth embodiments, the directional couplers 2100 and 2200 configured as electrical components have been described. In the ninth embodiment, a directional coupler unit configured as a partial structure of an electric circuit will be described.

  The structure of the multilayer substrate in which the circuit containing the directional coupler part using the metamaterial which concerns on 9th Embodiment was formed is shown in FIG. FIG. 43 is a perspective view of the directional coupler portion of the multilayer substrate.

  Referring to FIG. 43, the directional coupler unit includes a first transmission line 2580, a second transmission line 2590, and a metamaterial portion 2400.

  Since metamaterial portion 2400 of the directional coupler portion of the present embodiment is similar to the metamaterial portion of directional coupler 2100 described in the seventh embodiment, the overlapping description will not be repeated.

  The metamaterial portion 2400 is provided inside the first layer substrate 2501 of the multilayer substrate. The first transmission line 2580 and the second transmission line 2590 are provided on the surface of the first layer substrate 2501. Second layer substrate 2502 is provided to cover first transmission line 2580 and second transmission line 2590.

  The positional relationship between the first transmission line 2580 and the second transmission line 2590 and the metamaterial part 2400 is the same as that of the first transmission line 2180 and the second transmission line 2190 in the seventh embodiment, and the metamaterial part. It is provided so as to have a positional relationship similar to that of.

  In order to measure the characteristics of the directional coupler portion of the present embodiment, a multilayer substrate on which a circuit including a directional coupler portion using a metamaterial was formed was prototyped. The size of the metamaterial portion is 2.4 mm in the x-axis direction, 2.0 mm, y-axis direction, and 1.8 mm in the z-axis direction using the coordinate axes described in FIGS. 38 to 41.

  Further, the portions other than the electrodes, vias, and lines of the metamaterial portion are occupied by dielectrics to fix the electrodes, vias, and lines, and the dielectric constant ε = 9 of the dielectrics. The size of the multilayer substrate is 5 mm square, and the dielectric constant ε = 4.

  In measurement, a high frequency input current of several GHz is input from port (1) in FIG. 45, a passing current is output from port (2), and an output current of backward coupling is output from port (3). , A forward-coupled output current is output from the port (4).

  FIG. 44 is a graph showing measurement results of the characteristics of the directional coupler unit using the metamaterial. Referring to FIG. 44, it can be seen that the forward coupling from port (1) to port (4) appears strongly at -2 dB around 3 GHz.

  FIG. 45 is a perspective view of a directional coupler portion of a multilayer substrate used for comparative measurement. Referring to FIG. 45, the multilayer substrate on which the circuit including the directional coupler unit not using the metamaterial used for the comparative measurement is formed has the directional coupler unit using the metamaterial described in FIG. The metamaterial portion 2400 in the multi-layer substrate on which the circuit including it is formed is replaced with a dielectric portion 2600 composed only of a dielectric having a dielectric constant ε = 9.

  The first transmission line 2780, the second transmission line 2790, the first layer substrate 2701, and the second layer substrate 2702 are respectively the first transmission line 2580, the second transmission line 2590, described with reference to FIG. This is the same as the first layer substrate 2501 and the second layer substrate 2502.

  FIG. 46 is a graph showing the measurement results of the characteristics of the directional coupler portion not using the metamaterial. Referring to FIG. 46, in this case, since the length of the coupled line is 2.4 mm, coupling is performed in air at a frequency of 12 GHz corresponding to a wavelength λ of λ / 4 = 2.4 mm. Therefore, the coupling appears in the vicinity of 6 GHz, but the attenuation is about −15 dB, which is lower than that of the directional coupler unit using the metamaterial.

  Thus, the directional coupler, which is an electrical component using the metamaterial described in the seventh to ninth embodiments, is a coupler close to 0 dB, and thus is limited to the directional coupler. Instead, it can be used as a diplexer which is another electrical component. For example, in the signal input from the port (1) in FIG. 45, the 3 GHz component can be separated into the port (4), and the other components can be separated into the port (2).

  Also, by combining multiple diplexers using metamaterials that can separate multiple frequency components, for example, by mounting them on a mobile phone, the frequency signal for communication and the frequency signal for GPS (Global Positioning System) are separated. Can be used to

[Others]
The embodiment disclosed this time should be considered as illustrative in all points and not restrictive. The scope of the present invention is defined by the terms of the claims, rather than the description above, and is intended to include any modifications within the scope and meaning equivalent to the terms of the claims.

  2 External electrode, 3 External electrode, 4 Internal electrode, 4a electrode, 4b electrode, 5 Internal electrode, 5a electrode, 5b electrode, 6 Spacer, 10 Exterior part, 100 Coil type resonator, 110 Central axis, 200 Signal line, 220 Ground, 300 capacitor type resonator, 600 units, 610a top electrode, 610b bottom electrode, 622, 624, 632, 634 internal electrode, 640 line, 650,660 external electrode, 700 units, 710a top electrode, 710b top Lower electrode, 722, 724a, 724b, 730 Internal electrode, 740 Line, 750, 760 External electrode, 800 units, 810 Coiled conductor, 822, 824, 832, 834 Electrode, 842, 844 Via, 2100, 2200 Directional coupling 2110a top electrode, 2 10b bottom electrode, 2112a first via, 2112b second via, 2122 first internal electrode, 2124a second internal electrode, 2124b third internal electrode, 2130 fourth internal electrode, 2140 line, 2150 second 3 vias, 2160 fourth via, 2180, 2380, 2580, 2780 first transmission line, 2190, 2390, 2590, 2790 second transmission line, 2201 ground plane, 2300 substrate, 2301 ground line, 2400 metamaterial Part, 2501, 2701 First layer substrate, 2502, 2702 Second layer substrate, 2600 Dielectric part.

Claims (16)

A first transmission line (2180b) for passing a first current;
At least one second transmission line (2190b) for flowing a second current parallel to the first transmission line;
A metamaterial (2110a, 2112a, 2140, 2112b, 2110b, 2122, 2124a, 2150, 2130, 2160, 2124b) showing a negative dielectric constant and a negative magnetic permeability with respect to the resonance wavelength component of the electromagnetic field,
The metamaterial exhibits a negative permittivity and a negative permeability with respect to the resonance wavelength component of the electromagnetic field due to the first current, and the negative permittivity and the negative permeability are the second An electrical component (2100) arranged and positioned so as to cause the second current to flow by electromagnetically affecting the transmission line. The metamaterial is
A first resonator (2110a, 2112a, 2140, 2112b, 2110b) having a negative dielectric constant with respect to an electromagnetic wave having a resonance wavelength;
The first resonator includes a half-wavelength line (2110a, 2112a, 2140, 2112b, 2110b) having a length approximately half of the resonance wavelength,
The metamaterial further comprises:
A second resonator (2122, 2124a, 2150, 2130, 2160, 2124b) exhibiting a negative permeability with respect to the electromagnetic wave having the resonance wavelength;
A support member for fixing positions of the first resonator and the second resonator;
The support member includes the first resonator and the second resonator so that a magnetic field due to resonance of the second resonator is concentrated in a region different from a region where an electric field due to resonance of the first resonator is concentrated. The electrical component according to claim 1, wherein the position of said resonator is fixed.   The support member fixes positions of the first resonator and the second resonator so that both ends (2110a, 2110b) of the half-wave line are located outside the second resonator; The electrical component according to claim 2.   The support member includes the first resonator and the second resonator so that charges of the same polarity generated in the first resonator and the second resonator by resonance do not interfere with each other. The electrical component according to claim 2, wherein the position of said is fixed.   The said support member fixes the said 1st resonator so that the distance from the said 1st transmission line and the said 2nd transmission line of the both ends (2110a, 2110b) of the said half-wavelength line may differ. 2. The electrical component according to 2. The second resonator is an LC resonator,
The electrical component according to claim 5, wherein the support member fixes a position of the LC resonator so that a magnetic field generated by the first current passes through a resonance loop of the LC resonator.   The support member fixes a first end (2110a) of the half-wave line between the second resonator and a surface including the first transmission line and the second transmission line. The electrical component according to 5 above. The second resonator is
A first outermost electrode (2122);
A second outermost electrode (2130) having a polarity different from that of the first outermost electrode;
The support member fixes the first end of the half-wavelength line between the first outermost electrode and a surface including the first transmission line and the second transmission line. The electrical component according to 7.   The electrical component according to claim 5, wherein the support member fixes the first resonator so that potentials at both ends (2110a, 2110b) of the half-wavelength line generated by the first current are different.   The electrical component according to claim 5, wherein the support member fixes the position of the second resonator so that the second resonator is magnetically coupled to a magnetic field generated by the first current. The second resonator is
A first electrode (2122);
A second electrode (2124a, 2124b) facing the first electrode,
The support member includes the first electrode and the second electrode so that a resonance loop formed by the first electrode and the second electrode is substantially parallel to a direction of an electric field generated by the first current. The electrical component according to claim 5, wherein the electrode is fixed. The metamaterial is
A first resonator (610a, 640, 610b) having a negative dielectric constant with respect to the electromagnetic wave having the resonance wavelength;
The first resonator includes a half-wavelength line (610a, 640, 610b) having a length approximately half of the resonance wavelength.
The metamaterial further comprises:
A second resonator (622, 624, 650, 632, 634, 660) exhibiting a negative permeability with respect to the electromagnetic wave having the resonance wavelength;
The second resonator is
A plurality of plate electrodes (622, 624, 632, 634),
The plate electrode includes a plurality of first plate electrodes (622, 632) and a plurality of second plate electrodes (624, 634) arranged to face the first plate electrodes. ,
The second resonator further includes:
A first connection part (650) for electrically connecting the plurality of first plate electrodes;
A second connection portion (660) for electrically connecting the plurality of second plate electrodes,
The first outermost electrode (622) and the second outermost electrode (634) arranged on the outermost side among the plurality of plate-like electrodes are the first plate-like electrode and the second plate-like electrode, respectively. And
The metamaterial further comprises:
A support member for fixing positions of the first resonator and the second resonator;
In the supporting member, the first outermost electrode is close to the first end (610a) of the half-wave line, and the second outermost electrode is the second end of the half-wave line. The electrical component according to claim 1, wherein positions of the first resonator and the second resonator are fixed so as to be close to (610b). The first resonator further includes:
A first conductive plate (610a) connected to the first end;
A second conductive plate (610b) connected to the second end,
The support member fixes the first conductive plate at a position outside the second resonator and facing the first outermost electrode, and outside the second resonator, The electrical component according to claim 12, wherein the second conductive plate is fixed at a position facing the second outermost electrode. A metamaterial (2110a, 2112a, 2140, 2112b, 2110b, 2122, 2124a, 2150, 2130, 2160, 2124b) showing a negative dielectric constant and a negative magnetic permeability with respect to the resonance wavelength component of the electromagnetic field,
The metamaterial has a negative dielectric constant and a negative dielectric constant with respect to the resonant wavelength component of the electromagnetic field due to the first current flowing through the first transmission line (2380) on the substrate when attached to the substrate (2300). And exhibiting an electromagnetic influence on the second transmission line (2390) on the substrate when the negative dielectric constant and the negative permeability are attached to the substrate, An electrical component (2200) arranged and positioned so that a second current flows through the second transmission line. A ground plane (2201b) disposed so as to be on the opposite side of the plane including the first transmission line and the second transmission line across the metamaterial when attached to the substrate;
The electrical component according to claim 14, wherein the ground plane has ground connection portions (2201a, 2201c) for electrically connecting to a ground line (2301) on the substrate when attached to the substrate. . A first transmission line (2580) for passing a first current;
At least one second transmission line (2590) for passing a second current parallel to the first transmission line;
A metamaterial (2400) exhibiting a negative dielectric constant and a negative magnetic permeability with respect to a resonance wavelength component of an electromagnetic field,
The metamaterial exhibits a negative permittivity and a negative permeability with respect to the resonance wavelength component of the electromagnetic field due to the first current, and the negative permittivity and the negative permeability are the second A partial structure (2501) of an electric circuit arranged and positioned so that the second current flows by electromagnetically affecting the transmission line.

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