JP5004759B2 - Synchronous machine control device and synchronous machine control method - Google Patents

Description

  The present invention relates to a synchronous machine control device and a synchronous machine control method that can be started without using a position sensor even when the synchronous machine is idling.

  In a control device for a synchronous machine, an opportunity to use position sensorless control for driving the synchronous machine without detecting the rotational position of the synchronous machine is increasing for cost reduction. In general synchronous machine position sensorless control, the rotational position is estimated based on the voltage and current of the synchronous machine. The voltage of the synchronous machine can be detected by using a voltage detector, but the synchronous machine is often directly connected to the power conversion means (inverter), and the voltage of the synchronous machine is the output voltage of the power conversion means. You can think that they are equal. Therefore, when the output voltage value of the power conversion means can be regarded as the command value, the rotational position of the synchronous machine can be estimated by replacing the output voltage command value to the power conversion means with the voltage of the synchronous machine. For this reason, a voltage detector for terminal voltage detection is unnecessary, and the required amount of detection is only the armature current of the synchronous machine.

  However, when the power conversion means is stopped, that is, when all the semiconductor switching elements of the power conversion means are off, there is no voltage command for the synchronous machine, so no information on the rotational position is obtained. For this reason, when the power conversion means is stopped and the synchronous machine is idling, the rotational position cannot be known, so that the synchronous machine cannot be restarted via the power conversion means. Therefore, in order to start with position sensorless control in a state where the power conversion means is stopped and the synchronous machine is idling, for example, restarting from a momentary power failure or starting from a state where the fan is idling due to outside wind, For example, it was very inconvenient to wait until the wind stopped and the rotation of the synchronous machine stopped.

In order to solve this problem, for example, a conventional control device for a synchronous machine described in Patent Document 1 detects the voltage of the synchronous machine, generates a voltage having the same phase as this voltage, and applies it to the synchronous machine. The synchronous machine is activated while being positionless.
Further, the conventional control device for a synchronous machine described in Patent Document 2 is such that when the synchronous machine is idling, at least one of the semiconductor switching elements of the power conversion means is turned on to short-circuit the winding of the rotary machine. The winding current that flows due to the idling of the synchronous machine is measured, the rotational position of the synchronous machine is estimated based on this winding current, and the synchronous machine is restarted.

Japanese Patent Laid-Open No. 5-83965 (paragraph 0004, FIG. 2) Japanese Patent No. 3636340 (paragraphs 0009, 0022, 0023, 0024 to 0043, FIGS. 1 to 3)

In the control device for a synchronous machine as in Patent Document 1, it is necessary to provide a detection circuit for detecting the voltage of the synchronous machine, which requires the cost of the detection circuit, and the problem of securing the installation space for the detection circuit. As a result, there has been a problem that the scale of the apparatus becomes large.
Further, in the synchronous machine control device as in Patent Document 2, since the overcurrent due to the short circuit flows to the semiconductor element over a long period of time, when the rotational speed of the synchronous machine idling due to strong wind is high, the semiconductor element is There was a problem of deterioration.
Furthermore, in the control device for a synchronous machine such as Patent Document 2, depending on the electrical constant of the synchronous machine, in order to prevent the semiconductor element from being damaged when idling at the maximum rotation speed, the short circuit time is It had to be set to tens of microseconds or less. As a result, there has been a problem that it is not possible to ensure a sufficient number of samplings sufficient to accurately calculate the rotational position. In order to remove noise at the time of current detection, a certain period of detection is secured and filters such as first order lag and moving average are often used. However, if the rotational position is estimated with a short-circuit current of tens of microseconds or less, the number of sampling 1 to 2 times, the filter cannot be used, and the rotational position estimation is easily affected by current detection noise.

  The present invention has been made to solve the above-described problems, and it is possible to detect at the time of current detection without using voltage detection means or estimating the position using a winding short circuit of a synchronous machine. An object of the present invention is to provide a control device for a synchronous machine and a control method for the synchronous machine that have resistance against noise and can be started without using a position sensor even when the synchronous machine is idling.

A control device for a synchronous machine according to the present invention stores current detection means for detecting a current of the synchronous machine, and a value obtained by maximizing the current amplitude of the synchronous machine obtained from the current detection means as a current amplitude maximum value. Current amplitude storage means, voltage command calculation means for outputting a voltage command to be applied to the synchronous machine, cutoff signal generating means for outputting a cutoff signal for blocking voltage application to the synchronous machine, and the cutoff signal Power conversion means for cutting off the voltage application to the synchronous machine when the power is on, and applying a voltage to the synchronous machine based on the voltage command when the cut-off signal is off. The signal generating means turns off the cutoff signal from the start time to the first time, turns on the cutoff signal from the first time to the second time, and obtains it from the current amplitude storage means. Predict the maximum current amplitude. Compared with a set reference value, when the current amplitude maximum value is smaller than the reference value, during the period from the second time to the third time, the cutoff signal is turned off, the voltage command calculation means, From the start time to the first time, based on the shutoff signal from the shutoff signal generating means, at least once, a voltage command is output so that at least one phase of the synchronous machine is short-circuited, and the power conversion The current amplitude maximum value is stored in the current amplitude storage means, and the cutoff signal from the cutoff signal generating means is off during the period from the second time to the third time, The power conversion means is controlled so as to start the synchronous machine by outputting a voltage command such that the current of the synchronous machine obtained from the current detecting means becomes zero .

  According to the present invention, even when the synchronous machine is idling, a voltage command is output so that the current of the synchronous machine becomes zero, so that the synchronous machine can be reliably started without overcurrent. There is a remarkable effect such as the above.

Embodiment 1 FIG.
FIG. 1 is a block diagram showing an overall configuration including a synchronous machine control apparatus according to Embodiment 1 of the present invention. A power conversion means (inverter) 2 is connected to the synchronous machine 1, and a current detection means 3 is attached so that a current flowing through the wiring connecting the synchronous machine 1 and the power conversion means 2 can be detected.
When defining (start-up time: 0) <(first time: t1) <(second time: t2) <(third time: t3), the current amplitude storage means 4 includes the current detection means 3. As for the current amplitude obtained from the above, the maximum value between the start time and the first time t1 is stored as the current amplitude maximum value.
The shut-off signal generating means 5 outputs a shut-off signal for shutting off voltage application to the synchronous machine 1.
The voltage command calculation means 6 outputs a voltage command that causes at least one phase of the synchronous machine to be short-circuited at least once from the start time to the first time t1, and from the second time t2 to the third time. Until time t3, a voltage command is output so that the current of the synchronous machine 1 becomes zero based on the current obtained from the current detection unit 3, and the power conversion unit 2 is controlled. Further, based on the voltage command Estimate the rotational position of the synchronous machine.

The detailed contents of each block will be described below.
The synchronous machine 1 has U-phase, V-phase, and W-phase three-phase windings. Although the synchronous machine in this Embodiment demonstrates the synchronous machine provided with the permanent magnet in the rotor, it can implement with the same structure also about the synchronous machine provided with the field winding in the rotor instead of the permanent magnet. Is possible.

  The power conversion means 2 cuts off the voltage application to the synchronous machine 1 when the cut-off signal output by the cut-off signal generating means 5 is on, and outputs the voltage command calculation means 6 when the cut-off signal is off. A voltage is applied to the synchronous machine 1 based on the three-phase voltage commands vu0 *, vv0 *, and vw0 *.

  The current detection means 3 detects the U-phase current and the V-phase current of the synchronous machine 1. In addition to the method of directly detecting the U-phase current and the V-phase current as shown in FIG. 1, the current detection means 3 is based on the DC link current of the power conversion means 2, which is a known technique, from the U-phase current and V-phase current (For example, Y. Murai et al., “Three-Phase Current-Waveform-Detection on PWM Invertes from DC Link Current-Steps”, Proceedings of IPEC-Yokohama 1995, pp.271-275, Yokohama, Japan April 1995).

In the current amplitude storage means 4, the subtractor 10 calculates the W phase current by the calculation of the equation (1) based on the U phase current and the V phase current obtained from the current detection means 3.

iw = -iu-iv (1)
However, iu: U-phase current, iv: V-phase current, iw: W-phase current

The absolute value of the U-phase current iu, the absolute value of the V-phase current iv, and the absolute value of the W-phase current iw are calculated by the absolute value calculator 11 and input to the maximum value calculator 12. The output of the maximum value calculator 12 and the output of the delay circuit 15 are input to the switch 13. The timer 14 outputs the current time with the start time set to zero, and the switch 13 outputs either “output of the maximum value calculator 12” or “output of the delay circuit 15” as an output based on the time obtained from the timer 14. Choose. The delay circuit 15 delays and holds the input by one sampling interval, and outputs the value to the maximum value calculator 12, the switch 13, and the cutoff signal selector 21. Note that the initial value of the delay circuit 15 is zero. The maximum value calculator 12 calculates a maximum value from “absolute value of U-phase current iu”, “absolute value of V-phase current iv”, “absolute value of W-phase current iw”, and “output of delay circuit 15”. Output. Based on the time obtained from the timer 14, the switch 13 selects “output of the maximum value calculator 12” as an output during the period from (start-up time) to (first time), and (first time) In the subsequent period, “output of delay circuit 15” is output.
By this series of operations, the current amplitude storage means 4 holds the “maximum current amplitude” during the period from the start time 0 to the first time t1, and outputs the result in the period after the first time t1. Can do.

In the shut-off signal generating means 5, the timer 20 outputs the current time with the start time set to zero, and the shut-off signal selector 21 generates a shut-off signal based on the time of the timer 20 and the "maximum current amplitude". Either one of outputting the cutoff signal (hereinafter referred to as “on”) or not outputting it (hereinafter referred to as “off”) is selected. The operation of the cutoff signal selector 21 will be described in detail. The cutoff signal is turned off during the period from the start time 0 to the first time t1 when the time obtained from the timer 20 is from the first time t1 to the second time t2. During the period, the cut-off signal is turned on. During the period from the second time t2 to the third time t3, if the magnitude of the “maximum current amplitude” is larger than a predetermined value, the on-output of the cutoff signal is continued and the start of the synchronous machine is stopped. If the “maximum current amplitude” is smaller than a predetermined value, the cutoff signal is turned off. The “maximum current amplitude” is zero when the synchronous machine 1 is stopped, and has a value proportional to the rotational speed when the synchronous machine 1 is idling. Accordingly, when the magnitude of the “maximum current amplitude” is larger than a predetermined value (upper limit value), the shut-off signal output from the shut-off signal generating means 5 to the power converting means 2 is turned on, so that the synchronous machine 1 It is possible to protect the power conversion means 2 from overcurrent and overvoltage that occur when the engine is idling at an excessive rotational speed due to strong winds or the like.
When the synchronous machine is stopped and then restarted, the shut-off signal is turned off again during the period from the start time 0 to the first time t1, and the shut-off is performed during the period from the first time t1 to the second time t2. The process is performed in the order of turning on the signal, checking the magnitude of the “maximum current amplitude” during the period from the second time t2 to the third time t3.

  In the voltage command calculation means 6, the coordinate converter 30 converts the current obtained from the current detection means 3 into rotating biaxial coordinates (dq axes) that rotate in synchronization with the armature phase θ, and d-axis The current id and the q-axis current iq are output. The timer 31 outputs the current time t with the activation time set to zero, and the current command generator 32 outputs the d-axis current command id * on the rotating biaxial coordinates (dq axes) according to the time obtained from the timer 31. q-axis current command iq * is output.

As an example of the operation of the current command generator 32, when the current time t obtained from the timer 31 is before the (third time: t3), zero is output as id * and iq * and the timer 31 When the obtained current time t is after the (third time: t3), the id * may be output with a predetermined value while iq * is kept at zero.
When the current time t obtained from the timer 31 is before the (third time: t3), zero is output as id * and iq *, and the current time t is the (third time: In the case after t3), each of id * and iq * may be output as an independent predetermined value.

When the current time obtained from the timer 31 is after the starting time, the current controller 33 matches the d-axis current command id * and the q-axis current command iq * with the d-axis current command id * and the q-axis current command iq *, respectively. As described above, the d-axis voltage command vd * and the q-axis voltage command vq * on the rotating biaxial coordinates (dq axes) are output.
Here, the current controller 33 will be described in detail.
The configuration of the current controller 33 is shown in FIG. In FIG. 2, the subtractor 80 calculates the deviation between the d-axis current command id * and the d-axis current id, and the subtractor 81 calculates the deviation between the q-axis current command iq * and the q-axis current iq. The switch 82 selects 0 as a signal to be output to the amplifier 83 and the amplifier 84 during a period in which the time t obtained from the timer 31 is the second time t2 from the activation time. When the time t obtained from the timer 31 is after time t2, the output of the subtractor 80 is selected as the output to the amplifier 83, and the output of the subtractor 81 is selected as the output to the amplifier 84. The amplifier 83 amplifies the signal obtained from the switch 82 and outputs it as a d-axis voltage command vd *. Here, the amplifier 83 may amplify the input by a proportional calculation or amplify the input by a proportional integration calculation. The amplifier 84 amplifies the signal obtained from the switch 82 and outputs it as a q-axis voltage command vq *. The amplifier 84 may also amplify the input by proportional calculation, or may amplify the input by proportional integration calculation.

The phase calculator 34 outputs the phase θ based on the d-axis voltage command vd *, the q-axis voltage command vq * and the time obtained from the timer 31.
The coordinate converter 35 performs coordinate conversion based on the d-axis voltage command vd *, the q-axis voltage command vq *, and the phase θ estimated by the phase calculator 34, and outputs the three-phase voltage commands vu *, vv *, and vw *. Output.
The coordinate converter 35 is described in a non-patent document “Actual and Design of AC Servo System” Second Edition, Sugimoto, Koyama, Tamai, 1991, published by General Electronic Publishing Co., Ltd. (page 123, FIG. 5.24). Has been.
The PWM modulator 36 PWM-modulates each of the three-phase voltage commands vu *, vv *, and vw *, and outputs it as a logic signal for selecting each phase of the power conversion means 2 as Hi or Low.

  The short-circuit vector generator 37 outputs a logic signal with a combination of “Hi for all three phases” or “Low for all three phases” in order to select each phase of the power conversion means 2. Based on the time obtained from the timer 31, the switch 38 selects whether the logic signal to be output to the power conversion means 2 is the output of the short-circuit vector generator 37 or the output of the PWM modulator 36. In particular, when the short-circuit vector generator 37 outputs a logic signal in a combination of “low for all three phases”, the negative side of the DC power supply in the two switching elements provided for each of the three phases of the power conversion means 2 The switching element is short-circuited, and a current is generated by a counter electromotive force induced by idling. This current is detected by the current detection means 3.

  Although the timers 14, 20, and 31 are described separately, they can be realized by one timer.

Here, the phase calculator 34 will be described in detail.
FIG. 3 is a block diagram showing the internal configuration of the phase calculator 34. The first-order lag calculator 40 performs first-order lag calculation of the cutoff angular frequency ωc with the d-axis voltage command vd * as an input, and outputs the result as a d-axis magnetic flux φd. The divider 41 divides the q-axis voltage command vq * by the d-axis magnetic flux φd and outputs it as an angular frequency ω1.
The signal generator 42 outputs a preset angular frequency ω *. Here, the angular frequency ω * is a preset value, but the angular frequency ω * may be generated based on factors such as the set temperature and the outside air temperature. The subtractor 43 subtracts the output of the integrator 45 indicating the current speed from the frequency ω * that is the target speed, and outputs the result to the gain calculator 44. The gain calculator 44 outputs the result obtained by multiplying the output of the subtractor 43 by 1 / T0 to the integrator 45. If the time t obtained from the timer 31 is before the third time t3, the integrator 45 holds the ω1 as an integral speed as the speed during idling, and calculates the gain if the time t is after the third time t3. Each frequency ω2 is output using the integral calculation value of the output of the unit 44 as the speed at the time of activation. The switch 46 outputs the angular frequency ω1 obtained from the divider 41 if the time t obtained from the timer 31 is before the third time t3, and the time t obtained from the timer 31 is after the third time t3. If so, the angular frequency ω2 obtained from the integrator 45 is output. The integrator 47 integrates the angular frequency ω1 or ω2 output from the switch 46 and outputs it as a phase θ.
Accordingly, the initial speed at the start is the idling speed, and the initial phase at the start is the idling phase.

Here, the operation principle of the phase calculator 34 in the period from the second time t2 to the third time t3 will be described. The magnetic flux generated in the synchronous machine 1 on the rotation orthogonal coordinates (dq axes) rotating at an arbitrary angular frequency ω has the relationship of the expressions (2) and (3).
φd = ∫ (vd−R × id + ω × φq) dt (2)
φq = ∫ (vq−R × iq−ω × φd) dt (3)
Where φd: d-axis magnetic flux induced in the armature, φq: q-axis magnetic flux induced in the armature, R: armature resistance, id: d-axis current flowing through the armature, iq: q flowing through the armature Axis current, ω × φd: d-axis counter electromotive force induced in the armature, ω × φq: q-axis counter electromotive force induced in the armature

When the magnetic flux phase of the synchronous machine and the d-axis of the dq axis coincide with each other, the q-axis magnetic flux φq is zero, and if φq = 0 is substituted into the equations (2) and (3), (4), (5 ) Formula holds.

φd = ∫ (vd−R × id) dt (4)
ω = (vq−R × iq) ÷ φd (5)

In particular, when the current of the synchronous machine 1 is zero, id = iq = 0 holds. Therefore, if this relationship is substituted into the equations (4) and (5), the equations (6) and (7) are obtained.
φd = ∫ (vd) dt (6)
ω = vq ÷ φd (7)

  In the present embodiment, the angular frequency obtained by the calculation of the equation (7) for dividing the q-axis voltage command vq * which is the amplitude of the voltage by the magnetic flux φd of the synchronous machine is the initial speed at the start, that is, the rotational angular speed at the start And If an attempt is made to obtain the rotation angle frequency at the start-up using the rotation angle change of the voltage command vector, it is necessary to differentiate the phase of the voltage command in order to obtain the rotation angle change of the voltage command vector. Alternatively, if the voltage amplitude is divided by the magnetic flux to obtain the rotation angular frequency at the start-up as in equation (7), the differential operation becomes unnecessary. In general, differential calculations are known to be vulnerable to disturbances, and measurement noise and other noise can reduce the accuracy significantly. However, the voltage amplitude, which does not require differential calculations, is divided by the magnetic flux and rotated at startup. By obtaining the angular frequency, there is an effect that high estimation accuracy can be maintained even if noise such as measurement noise is mixed.

The phase calculator 34 shown in FIG. 3 gives voltage commands vd * and vq * instead of the voltages vd and vq in the equations (6) and (7), and a first-order lag calculator 40 instead of the integrator of (6). The first-order lag calculation is performed at the cutoff frequency ωc, and the calculation result of the angular frequency ω is obtained as ω1 by performing the division of the equation (7) by the divider 41.
The reason for using the first-order lag calculator without using the integrator is as follows. The function of the integrator is expressed by 1 / s when the Laplace operator is s, and the Laplace operator s is replaced with jω (j is an imaginary number and ω is an angular velocity). Therefore, the value of ω is still close to zero at the extremely low rotation speed immediately after the start of the synchronous machine, so that even if there is a slight error in the input signal, the error is greatly amplified and output by the integrator. . As a result, the control may be adversely affected and may be hindered. On the other hand, in the case of the first-order lag calculator, although some time lag occurs, the use of the cut-off frequency ωc can prevent the generation of unnecessary error output at an extremely low rotational speed. The above is the reason why the first-order lag calculator is used without using the integrator. Further, when the time t is after the third time t3, the initial value at the third time t3 is ω1, and the final value is ω *. The first-order lag calculation of the time constant T0 is performed by the subtractor 43, the gain calculator 44, and the integrator 45.
With the above configuration, the phase calculator 34 outputs a phase θ in which the magnetic flux phase of the synchronous machine 1 coincides with the d-axis of the dq axis during the time t from the second time t2 to the third time t3.

  In the conventional synchronous machine control device, the armature winding of the synchronous machine is short-circuited, the position of the rotor is estimated based on the current flowing at that time, and the power conversion means is restarted. The synchronous machine is controlled while outputting the voltage command so that the current flowing through the synchronous machine 1 becomes zero without estimating the position using the current flowing when the armature winding is short-circuited. Since the phase θ in which the magnetic flux phase of 1 coincides with the d-axis of the dq axis is calculated, there is an effect that it is not necessary to protect the power conversion means against overcurrent or overvoltage. Further, since there is no restriction such as a short circuit time that must be completed in a short time, there is an effect that it is easy to ensure a sufficient number of samplings sufficient to accurately calculate the phase θ.

  FIG. 4 is an example showing a series of operation waveforms in the first embodiment, and the operation of the first embodiment will be described with reference to this figure. The horizontal axis of FIG. 4 is time, the first stage is the cutoff signal output by the cutoff signal generating means 5, the second stage is the effective phase current value of the synchronous machine 1, and the third stage is output by the current command generator 32. The d-axis current command id * and the fourth stage are the angular frequency ω output from the switch 46 in the phase calculator 34. In FIG. 4, the activation time is set to zero.

○ (Starting time: 0) Before: The shut-off signal output by the shut-off signal generating means 5 is on, and the power conversion means 2 does not apply voltage to the synchronous machine 1 and maintains the shut-off state. In this example, it is assumed that the synchronous machine 1 is idling at 50 [rad / s].

○ From (starting time: 0) to (first time: t1): If the idling speed of the synchronous machine exceeds the startable speed of the synchronous machine due to strong winds, etc., the synchronous machine will be damaged by overcurrent etc. A problem occurs. Therefore, before starting the synchronous machine, it is necessary to check whether the idle speed of the synchronous machine is within the startable limit, and if it is out of the start range, it is necessary to stop the start and check again after a predetermined time. is there. For this investigation, the winding of the rotating machine is short-circuited during the period from the start time 0 to the first time t1, and at that time, the winding current flowing due to the idling of the synchronous machine is measured to calculate the rotational speed of the synchronous machine. To do.
That is, the switch 38 in the voltage command calculation means 6 outputs the output of the short-circuit vector generator 37 as a logic signal output to the power conversion means 2 during the period from the start time 0 to the first time t1 obtained from the timer 31. select. The shut-off signal output by the shut-off signal generating means 5 is turned off, and the power conversion means 2 applies a voltage at which the synchronous machine 1 is three-phase short-circuited based on the voltage command output by the voltage command calculating means 6. When the synchronous machine 1 is idling, a phase current effective value proportional to the magnitude of the rotational speed of the synchronous machine 1 is generated when the power conversion means 2 outputs a voltage that causes a three-phase short circuit. The current amplitude storage means 4 holds the “maximum current amplitude” during the period from the start time to the first time t1, and in the case of FIG. 4, the phase current effective value becomes the maximum at the first time t1. Therefore, the current held by the current amplitude storage unit 4 is also the value at the first time t1.
Although the phase can be calculated based on the rotation speed calculated at the time of the short circuit, the short circuit time is better from the viewpoint of dealing with overcurrent prevention. Accordingly, the measurement time is also shortened, so that the measurement accuracy is lowered. Therefore, the accuracy of the information measured during this period is only enough to provide a guide for checking whether the rotational speed is suitable for starting the synchronous machine. Therefore, it is preferable to set a reference value for determining whether or not an overcurrent is slightly low in consideration of safety. Higher-precision measurement is performed in a period from (second time: t2) to (third time: t3).

○ (First time: t1) to (Second time: t2) period: The shut-off signal output by the shut-off signal generating means 5 is turned on, and the power converting means 2 applies voltage to the synchronous machine 1. It will be in the interruption state. When the synchronous machine 1 is idling, a phase current effective value proportional to the magnitude of the rotational speed is generated in the synchronous machine 1 at the first time t1, but the phase current effective value converges to zero when the state is cut off. . Since the current of the synchronous machine 1 becomes 0 due to this zero convergence, the consistency with the start-up of the synchronous machine 1 with the current 0 in the next (second time: t2) to (third time: t3) period. Will be improved and quick start-up will be possible.

○ (second time: t2) to (third time: t3) period: In the cut-off signal generating means 5, the cut-off signal selector 21 determines that the “maximum current amplitude” is larger than a predetermined value. In this case, the shutoff signal is kept on and the synchronous machine 1 is stopped. Further, when the “maximum current amplitude” is smaller than a predetermined value, the cutoff signal is turned off. The current command generator 32 outputs zero as the d-axis current command id * and the q-axis current command iq *. The current controller 33 includes a d-axis voltage command vd * and a q-axis voltage command vq such that the d-axis current id and the q-axis current iq of the synchronous machine 1 coincide with the d-axis current command id * and the q-axis current command iq *. * Is output. The initial voltage values of the d-axis voltage command vd * and the q-axis voltage command vq * output from the current controller 33 at time t3 may be set to zero to start control, or given a predetermined value. Control may be started. At this time, the initial value may be selected in a range that is several percent or less of the maximum induced voltage of the synchronous machine 1. The phase calculator 34 calculates the phase θ based on the d-axis voltage command vd * and the q-axis voltage command vq *, and the coordinate converter 35 outputs the d-axis voltage command vd *, the q-axis voltage command vq * and the phase. Based on θ, three-phase voltage commands vu *, vv *, and vw * are output. At this time, the switch 46 in the phase calculator 34 outputs an angular frequency ω1 at which the magnetic flux phase of the synchronous machine 1 coincides with the d-q d-axis. In the example of FIG. 4, the idling rotational angular velocity is 50 [rad / s], and the switch 46 in the phase calculator 34 is in the period from (second time: t2) to (third time: t3). The output ω also matches 50 [rad / s]. The PWM modulator 36 PWM-modulates each of the three-phase voltage commands vu *, vv *, and vw *, and outputs it as a logic signal for selecting each phase of the power conversion means 2 as Hi or Low. The switch 38 selects the output of the PWM modulator 36 and outputs it to the power conversion means 2.
When the magnitude of the “maximum current amplitude” is smaller than a predetermined value, the shut-off signal is off, so that the power conversion means 2 determines the three-phase voltage commands vu *, vv *, A voltage that matches vw * is applied to the synchronous machine 1. Here, the d-axis current command id * and the q-axis current command iq * are zero, and the current controller 33 controls the d-axis current id to match the d-axis current command id * (= 0). The d-axis current id of the machine 1 becomes zero, and the current controller 33 controls the q-axis current iq so as to coincide with the q-axis current command iq * (= 0). Since it becomes zero, the synchronous machine 1 does not generate torque, and thereby the idling rotational speed does not change.

Period after (third time: t3): If the time t is before the third time t3, the integrator 45 in the phase calculator 34 holds the ω1 as an integral value, and the time t is the third time. If it is after time t3, the result of integrating the output of the gain calculator 44 is output as the angular frequency ω2. The gain calculator 44 outputs the result obtained by multiplying the output of the subtractor 43 by 1 / T0 to the integrator 45. The switch 46 outputs the angular frequency ω2 obtained from the integrator 45 if the time t obtained from the timer 31 is after the third time t3. In the example of FIG. 4, the target angular frequency ω * is set to 10 [rad / s] and T0 is set to 2 [seconds], and the angular frequency ω is changed from 50 [rad / s] at time t3 to ω * (= 10 [rad / s]) with time constant T0 (= 2) seconds. In FIG. 4, the current command generator 32 sets the d-axis current command id * to a predetermined value (3 [A] while keeping the q-axis current command iq * at zero when the time t is after the third time t3. ]). When the angular frequency ω changes from 50 [rad / s] at time t3 to ω * (= 10 [rad / s]), the d-axis d-axis is shifted from the magnetic flux phase of the synchronous machine 1. To do. At this time, torque is generated in that direction so that the magnetic flux of the synchronous machine 1 coincides with the d-axis in accordance with the axis deviation of the d-axis current. As a result, the rotational speed of the synchronous machine 1 is also 50 [rad at time t3. / s] to ω * (= 10 [rad / s]).

As described above, the phase calculator calculates the first-order delay of the d-axis voltage command output from the current controller and outputs the d-axis magnetic flux from the second time to the third time. A first-order lag calculator and a first angular frequency divided by the q-axis voltage command output from the output of the first-order lag calculator and the current controller between the second time and the third time. A divider that outputs
A selection switch for selecting the first angular frequency output from the divider from the second time to the third time, and a first output for integrating the output of the selection switch to output a phase. 1 integrator, a second integrator that stores the first angular frequency output from the divider, and a preset angular frequency in a predetermined period after the third time. A signal generator, and a first-order lag calculation subtractor that outputs a deviation between the output of the signal generator and the first angular frequency stored in the second integrator in a predetermined period after the third time; A gain calculator that multiplies the output of the first-order lag calculation subtracter by a predetermined time constant in a predetermined period after the third time, and the second integrator has the third time In the subsequent predetermined period, the first angular frequency is output. Instead, the multiplication result by the gain calculator is integrated and the integration result is output as a second angular frequency, and the selection switch is connected to the second integrator in a predetermined period after the third time. By selecting the second angular frequency to be output, the synchronous machine 1 is changed from the idling state (= 50 [rad / s]) to the state of rotating at a predetermined rotational speed ω * (= 10 [ra / s]). Can be activated.
As described above, according to the configuration of the first embodiment, even when the synchronous machine is in the idling state, the voltage command calculation means 6 determines the current of the synchronous machine 1 based on the current obtained from the current detection means 3. Since the voltage conversion command that outputs zero is output to drive the power conversion means, there is an effect that the synchronous machine can be reliably started without overcurrent.

  Further, during the period from the second time to the third time, a voltage command is output so that the current becomes zero, and the phase of the synchronous machine 1 is calculated based on this voltage command. The phase calculation can take a longer time than the device that estimates the rotational position, and the resistance to current detection noise is increased by using a filter that removes noise caused by current detection by ensuring a sufficient number of samplings. There is an effect that can.

  Further, when the synchronous machine 1 is in the idling state, and the current signal maximum value obtained from the current amplitude memory means 4 is larger than a predetermined value, the shut-off signal generating means 5 has a predetermined period after the second time. Since the interruption signal is turned on, there is an effect of preventing the power conversion means from becoming overcurrent or overvoltage.

Embodiment 2. FIG.
In the first embodiment, the phase calculator 34 in the voltage command calculation means 6 is based on a voltage command that causes the current of the synchronous machine 1 to become zero from the second time t2 to the third time t3. Thus, the phase θ in which the magnetic flux phase of the synchronous machine 1 coincides with the d-axis of the dq axis is output.
This phase calculator calculates the magnetic flux phase of the synchronous machine 1 and the dq axis based on the current flowing through the synchronous machine 1 from the second time to the third time and the voltage command so that the current becomes zero. You may output phase (theta) in which a d-axis corresponds. In the second embodiment, this aspect will be described.

  FIG. 5 is a block diagram showing the overall configuration including the synchronous machine control apparatus according to Embodiment 2 of the present invention, which is different from FIG. 1 in that the phase calculator 34 is replaced with a phase calculator 34a. The phase calculator 34 a outputs the phase θ based on the d-axis current id, the q-axis current iq, the d-axis voltage command vd *, the q-axis voltage command vq *, and the time obtained from the timer 31. Other configurations are the same as those of the first embodiment shown in FIG.

FIG. 6 is a block diagram showing the internal configuration of the phase calculator 34a. The gain calculator 50 multiplies the d-axis current id by the armature resistance R, and the gain calculator 51 multiplies the q-axis current iq by the armature resistance R. The subtractor 52 subtracts the output of the gain calculator 50 from the d-axis voltage command vd * and outputs the value to the first-order lag calculator 40. The subtractor 53 subtracts the output of the gain calculator 51 from the q-axis voltage command vq * and outputs the value to the divider 41.
When the magnetic flux phase of the synchronous machine 1 matches the d-axis of the dq axis, equations (4) and (5) are established. In the first embodiment, id = iq = 0 holds when the current of the synchronous machine 1 is zero. Therefore, this relationship is substituted into the equations (4) and (5) (6) and (7) The phase calculator 34 is configured based on the above.
The phase calculator 34a shown in FIG. 6 can calculate the accurate phase θ even when id = iq = 0 does not hold transiently, instead of the equations (6) and (7) (4), The phase θ is calculated based on the equation (5). That is, the voltage commands vd * and vq * are given instead of the voltages vd and vq in the equations (4) and (5), the first-order lag calculator 40 is used instead of the integrator in the equation (4), The calculation result of the angular frequency ω is obtained as ω1 by dividing the equation (5) by the divider 41.

  With the above configuration, the phase calculator 34a outputs the phase θ based on the voltage command and the detected current so that the current of the synchronous machine 1 becomes zero, so that id = transient due to the control delay of the current controller 33 or the like. Even if iq = 0 does not hold, there is an effect that the magnetic flux phase of the synchronous machine 1 and the d-axis of the dq axis can be matched between the second time and the third time. As a result, there is an effect that the control device of the synchronous machine can be started more reliably.

Embodiment 3 FIG.
In the first embodiment, the current amplitude storage unit 4 sets the current amplitude obtained from the current detection unit 3 to a maximum current amplitude value between the starting time and the first time. It was memorized as a value.
However, by replacing the current amplitude storage means 4 with the current amplitude storage means 4b, the maximum value of the phase current effective value in the period from the start time to the first time may be stored and output as the current amplitude maximum value. . In this case, since there is a difference of √2 between the current amplitude value and the phase current effective value, the predetermined value for the determination that the cutoff signal selector 21 turns on / off the cutoff signal is the current amplitude value. And take into account the difference in effective value of the phase current. In the third embodiment, this aspect will be described.

  FIG. 7 is a diagram showing the internal configuration of the current amplitude storage means 4b according to the third embodiment of the present invention. The square value calculator 60 calculates the square of the U-phase current iu, the square of the V-phase current iv, and the W-phase current. The squares of iw are respectively calculated, added by the adder 61, and further raised by the 1/2 power by the 1/2 power calculator 62, and a value proportional to the phase current effective value is output to the gain calculator 63. The gain calculator 63 multiplies a predetermined coefficient to output a phase current effective value. Specifically, the gain calculator 63 halves the output of the adder 61 by a 1/2 power calculator and multiplies the output of the 1/2 power calculator 62 by 1 / √3. The maximum value calculator 12b receives the phase current effective value instead of the absolute value of each phase current of the maximum value calculator 12. In this case, since there is a difference of √2 between the current amplitude value and the phase current effective value, the predetermined value for the determination that the cutoff signal selector 21 turns on / off the cutoff signal is the current amplitude value. And take into account the difference in effective value of the phase current. Other configurations are the same as those of the first embodiment shown in FIG.

  Through this series of operations, the current amplitude storage means 4b holds the maximum value of the effective value of the phase current in the period from (starting time) to (first time) as “maximum current amplitude”, and the result is (first Can be output in the period after (time). When the synchronous machine 1 is idling, if the maximum value of each phase current is held as “maximum current amplitude” as in the above embodiment, the value may differ depending on the rotational position even at the same rotational speed. However, the relationship between the rotational speed and the “maximum current amplitude” when the synchronous machine 1 is idling by the configuration of the third embodiment is uniquely determined without depending on the rotational position. There is an effect that it is possible to more accurately determine a voltage command output in which the current of the synchronous machine becomes zero only when the speed is smaller than the speed of the motor.

Embodiment 4 FIG.
In the first embodiment, when the shut-off signal output from the shut-off signal generating means 5 is off, the synchronous machine 1 is controlled based on the three-phase voltage commands vu0 *, vv0 *, vw0 * output from the voltage command calculating means 6. By applying a voltage and setting the angular frequency at this time to ω *, the d-axis d-axis tends to deviate from the magnetic flux phase of the synchronous machine 1. At this time, the magnetic flux of the synchronous machine 1 is controlled so as to keep the rotational speed of the synchronous machine 1 at ω * by generating torque in the direction so that the magnetic flux of the synchronous machine 1 coincides with the d-axis according to the axis deviation of the d-axis current. Was.
However, once the rotation speed of the synchronous machine 1 is maintained at ω *, the synchronous machine 1 may be controlled with high stability and responsiveness using a known position sensorless control method. In the fourth embodiment, this aspect will be described.

FIG. 8 is a block diagram showing a synchronous machine control apparatus according to Embodiment 4 of the present invention. A speed command generator 70 generates a rotational speed command according to the time output by the timer 31. Based on the phase currents iu and iv obtained from the current detection means 3 and the rotational speed command obtained from the speed command generator 70, the sensorless controller 71 is configured so that the rotational speed of the synchronous machine 1 matches the rotational speed command. Outputs phase voltage command. The sensorless controller 71 can be configured by a known method described in Japanese Patent Application No. 2001-518922 and Japanese Patent Application No. 2002-565151. In these methods, torque is generated in the direction so that the magnetic flux of the synchronous machine 1 coincides with the d-axis by the amount of the axis deviation of the d-axis current, which is more stable than the control for maintaining the rotational speed of the synchronous machine at ω *. Control with high performance and responsiveness can be performed. The switch 72 is either a three-phase voltage command obtained from the coordinate converter 35 or a three-phase voltage obtained from the sensorless controller 71 as a three-phase voltage command vu *, vv *, vw * according to the time output by the timer 31. One of the voltage commands is selected and output to the PWM modulator 36. Specifically, when the fourth time t4 is defined as a predetermined time after the third time t3, the switch 72 is configured such that when the time t output by the timer 31 is before the fourth time t4, the coordinate converter When the three-phase voltage command obtained from 35 is selected and output to the PWM modulator 36 as the three-phase voltage commands vu *, vv *, vw *, and the time t output by the timer 31 is after the fourth time t4 The three-phase voltage command obtained from the sensorless controller 71 is selected and output to the PWM modulator 36 as the three-phase voltage commands vu *, vv *, vw *.
Although the speed command generator 70 in the present embodiment has been described as generating a rotational speed command in accordance with the time output by the timer 31, the rotational speed command is based on factors other than the time such as the set temperature and the outside air temperature. It goes without saying that the same applies to those that generate.
With the above configuration, since a known position sensorless control method is used for the synchronous machine 1 after the fourth time t4, it is possible to perform control with high stability and responsiveness.

Embodiment 5 FIG.
For example, as disclosed in Japanese Patent Laid-Open No. 5-137349, the power conversion means 2 connects a semiconductor switching element having an insulated gate input, such as a MOSFET and an IGBT, in a bridge shape with respect to a DC power supply, and the semiconductor switching element And a capacitor serving as a power source for the driving circuit of the semiconductor switching element connected to the positive side of the DC power supply while the semiconductor switching element connected to the negative side of the DC power supply is in an ON state. A power conversion unit having a charge pump circuit may be used. In this fifth embodiment, this aspect will be described.

  FIG. 9 is a diagram showing an internal configuration of the power conversion means 2d. In the figure, the power conversion means 2d converts the DC voltage of the DC power supply 90 into U-phase, V-phase, and W-phase AC voltages. The DC power supply 91 is a power supply for the drive circuit of the semiconductor switching elements 93, 95, and 97 connected to the negative electrode side among the semiconductor switching elements 92 to 97 connected in a bridge shape to the DC power supply 90. Further, capacitors 98, 99, and 100 are used as power sources for the drive circuits of the semiconductor switching elements 92, 94, and 96 connected to the positive electrode side of the DC power source 90, respectively. The U-phase charge pump circuit includes a DC power supply 91, a diode 101, a capacitor 98, and a semiconductor switching element 93. Similarly, the V-phase charge pump circuit includes a DC power supply 91, a diode 102, a capacitor 99, and a semiconductor switching element 95, and the W-phase charge pump circuit includes a DC power supply 91, a diode 103, a capacitor 100, and a semiconductor switching element 97. The The NOR circuit 104 outputs Hi when the cutoff signal, which is a logic signal, is OFF (Low) and the three-phase voltage command vu0 *, which is a logic signal, is Low, and otherwise outputs Low. Similarly, the NOR circuit 105 outputs Hi when the cutoff signal, which is a logic signal, is off (Low) and the three-phase voltage command vv0 *, which is a logic signal, is Low, otherwise, the NOR circuit 106 outputs Low. When the cutoff signal, which is a logic signal, is OFF (Low) and the three-phase voltage command vw0 *, which is a logic signal, is Low, Hi is output, and otherwise, Low is output. The AND circuit 107 outputs Hi when the cutoff signal, which is a logical signal, is off (Low) and the three-phase voltage command vu0 *, which is a logical signal, is Hi, and otherwise outputs Low. Similarly, the AND circuit 108 outputs Hi when the cutoff signal, which is a logic signal, is off (Low) and the three-phase voltage command vv0 *, which is a logic signal, is Hi, and otherwise outputs Low, and the AND circuit 109 When the cutoff signal, which is a logical signal, is OFF (Low) and the three-phase voltage command vw0 *, which is a logical signal, is Hi, Hi is output, and otherwise, Low is output. With this configuration, when the cutoff signal is on (Hi), all the logic signals input to the semiconductor switching elements 92 to 97 are turned off. The semiconductor switching elements 92 to 97 are turned on when the input logic signal is Hi and turned off when it is Low. The U-phase charge pump circuit can charge the capacitor 98 from the DC power supply 91 when the semiconductor switching element 93 is turned on. Similarly, the V-phase charge pump circuit can charge the capacitor 99 from the DC power supply 91 when the semiconductor switching element 95 is turned on, and the W-phase charge pump circuit is connected to the DC power supply 91 when the semiconductor switching element 97 is turned on. From this, the capacitor 100 can be charged. If this configuration is used, the power source of the drive circuit for the switching element connected to the positive electrode side of the DC power source can be realized by a capacitor, so that the cost of the power conversion means can be reduced.

  Here, a voltage that causes the voltage command calculation means to short-circuit the semiconductor switching elements 93, 95, and 97 connected to the negative electrode side of the DC power supply 90 at least once from the start time to the first time. When the commands vu0 *, vv0 *, and vw0 * are output, the capacitors 98, 99, and 100 are charged by the charge pump circuits of each phase, and when the waveform output starts, the lower arm (semiconductor switching elements 93, 95, and 97) or the upper arm (semiconductor) Even if any of the ON signals of the switching elements 92, 94, 96) is given first, the power conversion means 2d operates in accordance with the given voltage command, and the semiconductor switching elements can be turned on / off. Even after time t2, an effect of outputting a voltage waveform without disturbance is obtained. In particular, when the semiconductor switching elements 93, 95, and 97 are simultaneously turned on, the U-phase, V-phase, and W-phase of the synchronous machine 1 are short-circuited and the capacitors 98, 99, and 100 of each phase charge pump circuit are charged. be able to. As described in the above embodiment, the voltage command calculation means outputs a voltage command such that the semiconductor switching elements 93, 95, and 97 are simultaneously turned on at least once from the start time to the first time. Since the operation of short-circuiting the synchronous machine 1 can also serve as the operation of charging the capacitors 98, 99, 100 of each phase charge pump circuit, it can be started up efficiently.

  FIG. 10 is a flowchart when the power conversion means 2d configured as described above is applied to the fourth embodiment. In the fifth embodiment, the power conversion means 2 in FIG. 8 is replaced with the power conversion means 2d. In this configuration, each function of the voltage command calculation means 6c can be realized by a microcomputer. In this case, a CPU (not shown) installs software corresponding to each function installed in a ROM (not shown). Each function is realized at a predetermined timing by reading it onto a memory (not shown) and executing it individually. The fifth embodiment will be described below with reference to FIGS. FIG. 10 starts the description from the state where the synchronous machine 1 is idling (S101). The activation starts from the activation time (time 0) (S102). The shut-off signal generating means 5 turns off the shut-off signal, the voltage command calculating means 6c outputs the output of the short-circuit vector generator 37 as a voltage command, and the power conversion means 2d releases the shut-off state and is connected to the negative side of the DC power supply. The formed semiconductor switching element is short-circuited on (S103). By the operation of S103, the capacitor of the charge pump circuit of the power conversion means 2d can be charged (S104). At this time, the current amplitude storage means 4b calculates the phase current effective value from the detected current obtained from the current detection means 3, and holds the current amplitude maximum value (S105).

  When the time t has not reached the first time t1 (S106), the shut-off signal generating means 5 turns on the shut-off signal for a predetermined time and puts the power conversion means 2d in the shut-off state, thereby once the synchronous machine 1 (S107), after that, the power conversion means 2d repeats the operation of releasing the cutoff state and short-circuiting (S103).

  When the time t has reached the first time t1 (S106), the cutoff signal generating means 5 turns on the cutoff signal and puts the power conversion means 2d in the cutoff state (S108). When the maximum current amplitude value held by the current amplitude storage unit 4b is larger than a predetermined value (S109), the start-up process is stopped in order to protect the power conversion unit 2d from overcurrent and overvoltage (S110). . If the predetermined time has passed after entering the activation processing state, the operation may be started from the processing of S102.

When the current amplitude maximum value held by the current amplitude storage means 4b is smaller than a predetermined value (S109), when the time t reaches the second time t2 (S111), the cutoff signal of the cutoff signal generating means 5 is Turn off (S112). When the cut-off signal is turned off, the power conversion means 2d generates the initial value voltage until the voltage command output from the voltage command calculation means 6c is updated. This initial value voltage may be zero, or may be a predetermined value as long as it is in a sufficiently small range with respect to the maximum induced voltage. For example, when the maximum induced voltage of the synchronous machine 1 is 200V, the initial value voltage for each phase may be selected in a range of −2 to + 2V. The current detection means 3 detects the current (S113), the voltage command calculation means 6c outputs a voltage command so that the current becomes zero (S114), and the phase calculator 34 detects the magnetic flux phase of the synchronous machine 1. And the phase θ where the d-axis of the dq axis coincides with each other (S115).
When the time t has not reached the third time t3 (S116), the voltage command calculation means 6c continues to output the voltage command so that the current becomes zero and calculates the phase θ.

  When the time t reaches the third time t3 (S116), the current command generator 32 changes the d-axis current command id * from zero to a predetermined value while keeping the q-axis current command iq * at zero (S117). ) When the angular frequency ω output from the switch 46 in the phase calculator 34 is changed to the preset angular frequency ω * with a time constant T0 (S118), the rotational speed of the idler 1 is also synchronized with this. And rotate at an angular frequency ω *. When the time t reaches the fourth time t4 (S119), the voltage command calculation means 6c outputs a three-phase voltage command calculated by the sensorless control means 71 (S120).

  As shown in this series of operations, "charge pump circuit capacitor charging" and "determination of whether the synchronous machine is idling and greater than a predetermined speed" from the start time to the first time. Since it can be performed simultaneously by a short-circuit operation, a short-circuit for “charge pump circuit capacitor charging” and a short-circuit for “determination of whether the synchronous machine is in a free-run state and is greater than a predetermined speed” are performed. There is an effect that the start-up processing time can be shortened rather than separately.

  Further, if the configuration of the power conversion means 2d is used, the power source of the drive circuit of the semiconductor switching element connected to the positive electrode side of the DC power supply can be realized with a capacitor, so that the cost of the power conversion means can be reduced. is there.

  Further, the voltage command calculation means 6c outputs a voltage command that short-circuits the plurality of semiconductor switching elements connected to the negative electrode side of the DC power supply at least once from the start time to the first time. As a result, the capacitors of the charge pump circuit are sequentially charged, and the power conversion means 2 according to the given voltage command regardless of whether the lower arm or the upper arm is turned on at the start of waveform output after time t2. The semiconductor switching element can be turned on / off even after the second time t2, and an undistorted voltage waveform can be output after the second time t2.

Embodiment 6 FIG.
In the fifth embodiment, the semiconductor switching element connected to the negative electrode side of the DC power supply 90 is turned on at least once from the start time to the first time by the charge pump circuit provided in the power conversion means. During the state, the capacitor serving as the power source of the driving circuit of the semiconductor switching element connected to the positive electrode side of the DC power source 90 is charged. At this time, since the three semiconductor switching elements 93, 95, and 97 connected to the negative electrode side of the DC power supply 90 were simultaneously turned on, the DC power supply 91 simultaneously connected the three capacitors 98, 99, and 100. A large amount of current is generated at that time. As a result, the wiring connecting the positive electrode side of the DC power supply 91 and each phase charge pump circuit has to be made sufficiently thick. Further, when the wiring cannot be made sufficiently thick, the wiring resistance increases, and there is a problem that loss occurs due to current when the capacitors 98, 99, and 100 are charged simultaneously. Further, the DC power supply 91 needs to have a power capacity sufficient to charge the capacitors 98, 99, and 100 simultaneously. Alternatively, it is necessary to insert a resistor for preventing an inrush current into the wiring so that the current capacity of the DC power supply 91 does not increase, and there is a problem regarding the cost for installing the resistor, the space, and the loss consumed by the resistor. .

  Therefore, a voltage command is output at least three times so that only one of the three semiconductor switching elements connected to the negative electrode side of the DC power supply 90 is turned on from the start time to the first time. The capacitors 98, 99, and 100 respectively connected to the respective phase charge pump circuits may be charged separately one by one. Therefore, in the sixth embodiment, the interruption signal generating means in the above embodiment is replaced with an interruption signal generating means that outputs an interruption signal for each of the U phase, the V phase, and the W phase, and the power conversion means is changed. The capacitor 98 is configured such that each of the U phase, the V phase, and the W phase can be independently blocked according to the cutoff signal of the cutoff signal generating means obtained for each of the U phase, the V phase, and the W phase. , 99, 100 are charged separately one by one.

FIG. 11 is a block diagram showing an overall configuration including a control device for a synchronous machine in the present embodiment. The cutoff signal generating means 5e outputs cutoff signals xu, xv, xw for the U phase, V phase, and W phase, respectively. In the cutoff signal generating means 5e, the timer 20 outputs the current time with the start time set to zero, and the cutoff signal selector 21e is based on the time of the timer 20 and the “maximum current amplitude” obtained from the current amplitude storage means 4b. Then, on or off is selected for each of the cutoff signals xu, xv, xw and output.
The power conversion means 2e independently shuts off the U phase, the V phase, and the W phase according to the shut-off signals xu, xv, and xw. FIG. 12 is a diagram showing the internal configuration of the power conversion means 2e. The logic circuit 104e allows the semiconductor switching element 93 to turn off regardless of the value of the U-phase voltage command vu0 * when the cutoff signal xu is on. When the cutoff signal xu is off, a logical negation of vu0 * is output. Similarly, when the interruption signal xv is on, the logic circuit 105e outputs a signal that turns off the semiconductor switching element 95 regardless of the value of the V-phase voltage command vv0 *, and the interruption signal xv is off. Output a logical negation of vv0 *.
The logic circuit 106e outputs a signal that turns off the semiconductor switching element 97 regardless of the value of the W-phase voltage command vw0 * when the cutoff signal xw is on, and vw0 when the cutoff signal xw is off. Output a logical negation of *. The logic circuit 107e outputs a signal that turns off the semiconductor switching element 92 regardless of the value of the U-phase voltage command vu0 * when the cutoff signal xu is on, and vu0 when the cutoff signal xu is off. Outputs the value of *. Similarly, when the cutoff signal xv is on, the logic circuit 108e outputs a signal that turns off the semiconductor switching element 94 regardless of the value of the V-phase voltage command vv0 *, and the cutoff signal xv is off. Output the value of vv0 *. The logic circuit 109e outputs a signal that turns off the semiconductor switching element 96 regardless of the value of the W-phase voltage command vw0 * when the cutoff signal xw is on, and vw0 when the cutoff signal xw is off. Outputs the value of *. Moreover, what attached | subjected the code | symbol same as FIG. 9 is the same or it corresponds to this.

  FIG. 13 shows the cutoff signals xu, xv, xw output from the cutoff signal selector 21e during the period from the start time to the first time t1 from the start time, and the three-phase currents iu, iv, It is a figure which shows the relationship of iw. The operation of the cutoff signal selector 21e will be described in detail with reference to this figure. In FIG. 13, times t10 to t18 are times from the start time to the first time t1, and during the period from the start time to the first time t1, the short-circuit vector generator 37 is connected to each phase of the power conversion means 2e. Therefore, the three-phase voltage commands vu0 *, vv0 *, and vw0 * are output in the combination of “Low for all three phases”. When the cutoff signal xu is turned off and xv and xw are turned on for a period of 100 μs from time t10, only the semiconductor switching element 93 of the power conversion means 2e is turned on, and the other semiconductor switching elements are turned off. When the synchronous machine 1 is stopped, the three-phase currents iu, iv and iw are not generated even if only the semiconductor switching element 93 is turned on. Further, even when the synchronous machine 1 is idling, the three-phase currents iu, iv, iw may be generated or may not be generated. FIG. 13 shows an example in which the synchronous machine 1 is in the idling state, but the three-phase currents iu, iv, iw are not generated even if only the semiconductor switching element 93 is turned on. When 100 μs elapses from time t10, the cutoff signal selector 21e turns on all of the cutoff signals xu, xv, xw.

Subsequently, when the cutoff signal xv is turned off and xu and xw are turned on for a period of 100 μs from time t11, only the semiconductor switching element 95 of the power conversion means 2e is turned on, and the other semiconductor switching elements are turned off. Similarly to the time t10, when only the semiconductor switching element 95 is turned on, the three-phase currents iu, iv, iw may or may not be generated even when the synchronous machine 1 is idle. In this example, although only the semiconductor switching element 95 is turned on, current is generated in each of the three phases iu, iv, and iw. At this time, the current amplitude output from the gain calculator 63 in the current amplitude storage means 4b is as shown in the lower part of FIG. When 100 μs elapses from time t11, the cutoff signal selector 21e turns on all of the cutoff signals xu, xv, xw.
Subsequently, when the cutoff signal xw is turned off and xu and xv are turned on for a period of 100 μs from time t12, only the semiconductor switching element 97 of the power conversion means 2e is turned on, and the other semiconductor switching elements are turned off. Similarly to the time t10, when only the semiconductor switching element 97 is turned on, the three-phase currents iu, iv, iw may or may not be generated even when the synchronous machine 1 is idling. In this example, although only the semiconductor switching element 97 is turned on, current is generated in each of the three phases iu, iv, and iw. At this time, the current amplitude output from the gain calculator 63 in the current amplitude storage means 4b is as shown in the lower part of FIG. 13, and the current amplitude is smaller than when only the semiconductor switching element 95 is turned on. When 100 μs elapses from time t12, the cutoff signal selector 21e turns on all of the cutoff signals xu, xv, xw. This series of operations is repeated from t13 to t18. Since the current amplitude storage means 4b outputs the maximum value of current amplitude in the period from the start time to the first time t1, in the case of FIG. 13, the value after 100 μs has elapsed from any of the times t11, t14, and t17. become.

  FIG. 14 is a diagram showing the relationship between the phase voltage of the synchronous machine 1 and the current amplitude output from the gain calculator 63 in the current amplitude storage means 4b when the operations at the times t10, t11, and t12 are repeatedly performed. In the figure, the upper part represents the phase voltage, the lower part represents the current amplitude, and the horizontal axis represents the same time. FIG. 14 shows a state in which the synchronous machine 1 is idling at a certain speed. However, if the idling speed is different, the period and size of the waveform in FIG. As can be seen from FIG. 14, the maximum value of the current amplitude output by the gain calculator 63 may decrease from the maximum of 0.2 A from time 1.0 ms to time 2.2 ms. While the absolute value of the minimum phase voltage is larger than the absolute value of the maximum phase voltage, the maximum value of the current amplitude is less than 0.2A. Exists every 1/6 cycle. In other words, if the operation at the times t10, t11, t12 is repeated for a period of 1/6 times or more with respect to one cycle of the phase voltage, the current amplitude is uniquely determined by the idling speed regardless of the phase of the phase voltage. A fixed current amplitude can be obtained. The current amplitude obtained by this method is proportional to the idling speed, and the value thereof is the same as the value output by the current amplitude storage means 4b in the fifth embodiment.

  The synchronous machine control apparatus according to the sixth embodiment operates based on the flowchart shown in FIG. FIG. 15 starts the description from a state where the synchronous machine 1 is idling (S201). Start-up starts from the start time (S202). A value obtained by adding 100 μsec to the current time t is stored as a variable tx (S203). In the present embodiment, the variable tx is a value obtained by adding 100 μsec to the time t, but this value of 100 μsec is a value that takes into account the electrical constant and rated speed of the synchronous machine 1 or the rated capacity of the power conversion means 2e. There may be. The same applies to the values of 100 μsec and 200 μsec described in FIG. The cutoff signal generator 5e turns off the cutoff signal xu, and the switch 38 selects the output of the short-circuit vector generator 37 based on the time obtained from the timer 31. By this operation, only the semiconductor switching element 93 of the power conversion means 2e is turned on, and the other semiconductor switching elements are turned off. As a result, the U phase of the power conversion means 2e is released from the cutoff, and the DC power supply negative electrode side U phase semiconductor switching element is short-circuited (S204). Thereby, the capacitor 98 is charged, and the U-phase charge pump charging operation is performed (S205). At this time, the current amplitude storage means 4b calculates the phase current effective value from the detected current obtained from the current detection means 3, and holds the current amplitude maximum value (S206). If the current time is smaller than the variable tx at this stage (No in S207), a series of operations from S204 to S206 is repeated. At this stage, if the current time t is greater than the variable tx (Yes in S207), the cutoff signal generation means 5e turns on the cutoff signal xu, thereby turning off the semiconductor switching element 93 of the power conversion means 2e. The semiconductor switching elements 92 to 97 of the power conversion means 2e are all turned off (S208). This state is maintained until the current time becomes larger than the value obtained by adding 200 μsec to the variable tx (S209).

  When the current time becomes larger than the value obtained by adding 100 μsec to the variable tx, the value obtained by adding 100 μsec to the current time t is updated (S210). The cutoff signal generating means 5e turns off the cutoff signal xv. At this time, the switch 38 maintains the output selection of the short-circuit vector generator 37 based on the time obtained from the timer 31. By this operation, only the semiconductor switching element 95 of the power conversion means 2e is turned on, and the other semiconductor switching elements are turned off. As a result, the V phase of the power conversion means 2e is released from the cutoff, and the DC power source negative side V phase semiconductor switching element is short-circuited (S211). Thereby, the capacitor 99 is charged, and the V-phase charge pump charging operation is performed (S212). At this time, the current amplitude storage means 4b calculates the phase current effective value from the detected current obtained from the current detection means 3, and holds the current amplitude maximum value (S212). If the current time is smaller than the variable tx at this stage (No in S214), a series of operations from S211 to S213 is repeated. If the current time t is greater than the variable tx at this stage (Yes in S214), the cutoff signal generating means 5e turns on the cutoff signal xv, thereby turning off the semiconductor switching element 95 of the power conversion means 2e. The semiconductor switching elements 92 to 97 of the power conversion means 2e are all turned off (S215). This state is maintained until the current time becomes larger than the value obtained by adding 200 μsec to the variable tx (S216).

When the current time becomes larger than the value obtained by adding 100 μsec to the variable tx, the value obtained by adding 100 μsec to the current time t is updated (S217). The cutoff signal generating means 5e turns off the cutoff signal xw. At this time, the switch 38 maintains the output selection of the short-circuit vector generator 37 based on the time obtained from the timer 31. By this operation, only the semiconductor switching element 97 of the power conversion means 2e is turned on, and the other semiconductor switching elements are turned off. As a result, the W phase of the power conversion means 2e is released from cutoff, and the DC power source negative electrode side W phase semiconductor switching element is short-circuited (S218). Thereby, the capacitor 100 is charged, and the W-phase charge pump charging operation is performed (S219). At this time, the current amplitude storage means 4b calculates the effective value of the phase current from the detected current obtained from the current detection means 3, and holds the maximum current amplitude value (S220). If the current time is smaller than the variable tx at this stage (No in S221), a series of operations from S218 to S220 is repeated. At this stage, if the current time t is larger than the variable tx (Yes in S221), the cutoff signal generating means 5e turns on the cutoff signal xw, thereby turning off the semiconductor switching element 97 of the power conversion means 2e. The semiconductor switching elements 92 to 97 of the power conversion means 2e are all turned off (S222). This state is maintained until the current time becomes larger than the value obtained by adding 200 μsec to the variable tx (S223).
When the current time becomes larger than the value obtained by adding 200 μsec to the variable tx, if the time t is smaller than the first time t1, the steps from S203 are repeated (S224). If the time t is greater than the first time t1 at the time of S224, the same processing as that after S109 in FIG. 8 is performed.

  As shown in this series of operations, “capacitor charging of the charge pump circuit” is performed for each phase of the U phase, V phase, and W phase. The start-up processing time can be shortened compared to the case where the short circuit for determining whether the synchronous machine is in a free-running state and is faster than a predetermined speed is separately performed, and also due to “capacitor charging of the charge pump circuit” There exists an effect which can suppress generation | occurrence | production of a big electric current 1/3 times. As a result, there is an effect that the loss of the wiring connecting the positive electrode side of the DC power supply 91 and each phase charge pump circuit can be suppressed. Further, the DC power source 91 does not need a power source capacity for charging the three capacitors 98, 99, and 100 at the same time, and only needs a power source capacity that can charge any one of the capacitors 98, 99, and 100. effective. Alternatively, it is possible to omit or reduce the resistance inserted in order to prevent inrush current so that the current capacity of the DC power supply 91 does not increase, thereby suppressing the cost, space and resistance loss for installing the resistor. There is an effect that can be done.

Embodiment 7 FIG.
In the sixth embodiment, at least 3 voltage commands are issued so that only one of the three semiconductor switching elements connected to the negative electrode side of the DC power supply 90 is turned on from the start time to the first time. The capacitors 98, 99, and 100 connected to the respective phase charge pump circuits are separately charged one by one so that they are output once, but during the period from the start time to the first time, Capacitors 98 respectively connected to the respective phase charge pump circuits so as to output a voltage command such that only two of the three semiconductor switching elements connected to the negative electrode side of the DC power supply 90 are turned on at least three times. You may make it charge separately 99 and 100 2 each.

  FIG. 16 shows the cutoff signals xu, xv, xw output by the cutoff signal selector 21e during the period from the start time to the first time t1 obtained from the timer 20 in the seventh embodiment, and the synchronous machine 1. It is a figure which shows the relationship between phase current iu, iv, iw. The operation of the cutoff signal selector 21e will be described in detail with reference to this figure. In FIG. 16, times t20 to t22 are times from the start time to the first time t1, and during the period from the start time to the first time t1, the short-circuit vector generator 37 has each phase of the power conversion means. In order to select, the three-phase voltage commands vu0 *, vv0 *, and vw0 * are output in the combination of “Low for all three phases”. During a period of 100 μs from time t20, when the cutoff signals xu and xv are turned off and xw is turned on, the semiconductor switching elements 93 and 95 of the power conversion means 2e are turned on, and the other semiconductor switching elements are turned off. When the synchronous machine 1 is stopped, the three-phase currents iu, iv, iw are not generated even when the semiconductor switching elements 93 and 95 are turned on. Further, if the synchronous machine 1 is idling, at least two of the three-phase currents iu, iv, iw are generated. FIG. 16 shows an example where the synchronous machine 1 is in the idling state, and iu and iv of the three-phase current are generated as a result of turning on the semiconductor switching elements 93 and 95. When 100 μs elapses from time t20, the cutoff signal selector 21e turns on all of the cutoff signals xu, xv, xw. At this time, the current amplitude output from the gain calculator 63 in the current amplitude storage means 4b is as shown in the lower part of FIG.

  Subsequently, when the cutoff signals xv and xw are turned off and xu is turned on for a period of 100 μs from time t21, the semiconductor switching elements 95 and 97 of the power conversion means 2e are turned on, and the other semiconductor switching elements are turned off. Similarly to the time t20, when the semiconductor switching elements 95 and 97 are turned on, at least two of the three-phase currents iu, iv, and iw are generated if the synchronous machine 1 is idle. In this example, although only the semiconductor switching elements 95 and 97 are turned on, current is generated in each of the three phases iu, iv, and iw. At this time, the current amplitude output from the gain calculator 63 in the current amplitude storage means 4b is as shown in the lower part of FIG. 16, and the current amplitude is larger than when the semiconductor switching elements 93 and 95 are turned on. The value of the maximum current amplitude stored in the means 4b is updated. When 100 μs elapses from time t21, the cutoff signal selector 21e turns on all of the cutoff signals xu, xv, xw.

  Subsequently, when the cutoff signals xu and xw are turned off and xv is turned on for a period of 100 μs from time t22, the semiconductor switching elements 93 and 97 of the power conversion means 2e are turned on, and the other semiconductor switching elements are turned off. Similarly to the time t20, when the semiconductor switching elements 93 and 97 are turned on, at least two of the three-phase currents iu, iv, and iw are generated if the synchronous machine 1 is idle. In this example, the synchronous machine 1 is in the idling state, but as a result of turning on the semiconductor switching elements 93 and 97, current is generated in each of the three phases iu, iv, and iw. At this time, the current amplitude output from the gain calculator 63 in the current amplitude storage means 4b is as shown in the lower part of FIG. 16, and the current amplitude is the same as when the semiconductor switching elements 95 and 97 are turned on. When 100 μs elapses from time t22, the cutoff signal selector 21e turns on all of the cutoff signals xu, xv, xw.

FIG. 17 is a diagram showing the relationship between the phase voltage of the synchronous machine 1 and the current amplitude output from the gain calculator 63 in the current amplitude storage means 4b when a series of operations at the times t20, t21, and t22 are repeatedly performed. . FIG. 17 shows a state in which the synchronous machine 1 is idling at a certain speed. However, if the idling speed is different, the period and size of the waveform in FIG. As can be seen from FIG. 17, it can be seen that the pulsed current amplitude output by the gain calculator 63 has a predetermined value at least once out of three times. In other words, once the series of operations at the times t20, t21, and t22 is performed, the maximum current amplitude value of the three pulsed current amplitudes becomes a predetermined value.
In the case of the sixth embodiment, a predetermined value is obtained by repeatedly performing a series of operations at the times t10, t11, and t12 to obtain a maximum current amplitude value. It is not necessary to repeat a series of operations at t20, t21, and t22.

  In the synchronous machine control apparatus according to the seventh embodiment, the operation is performed based on the flowchart shown in FIG. FIG. 18 starts the description from the state where the synchronous machine 1 is idling (S301). Start-up is started from the start time (S302). A value obtained by adding 100 μsec to the current time t is stored as a variable tx (S303). In the present embodiment, the variable tx is a value obtained by adding 100 μsec to the time t, but this value of 100 μsec is a value that takes into account the electrical constant and rated speed of the synchronous machine 1 or the rated capacity of the power conversion means 2e. There may be. The same applies to the values of 100 μsec and 200 μsec shown in FIG. The cutoff signal generator 5e turns off the cutoff signals xu and xv, and the switch 38 selects the output of the short-circuit vector generator 37 based on the time obtained from the timer 31. By this operation, the semiconductor switching elements 93 and 95 of the power conversion means 2e are turned on, and the other semiconductor switching elements are turned off. As a result, the U phase and V phase of the power conversion means 2e are released from the cutoff, and the DC power source negative electrode side U phase semiconductor switching element and the V phase semiconductor switching element are short-circuited (S304). Thereby, the capacitors 98 and 99 are charged, and the charge pump charging operation is performed in the U phase and the V phase (S305). At this time, the current amplitude storage means 4b calculates the effective value of the phase current from the detected current obtained from the current detection means 3, and holds the maximum current amplitude value (S306). If the current time is smaller than the variable tx at this stage (No in S307), a series of operations from S304 to S306 are repeated. At this stage, if the current time t is larger than the variable tx (Yes in S307), the cutoff signal generating means 5e turns on the cutoff signals xu and xv, so that the semiconductor switching element 93 of the power conversion means 2e, 95 is turned off, and the semiconductor switching elements 92 to 97 of the power conversion means 2e are all turned off (S308). This state is maintained until the current time becomes larger than the value obtained by adding 200 μsec to the variable tx (S309).

  When the current time becomes larger than the value obtained by adding 100 μsec to the variable tx, the value obtained by adding 100 μsec to the current time t is updated (S310). The shut-off signal generating means 5e turns off the shut-off signals xv and xw. At this time, the switch 38 maintains the output selection of the short-circuit vector generator 37 based on the time obtained from the timer 31. By this operation, the semiconductor switching elements 95 and 97 of the power conversion means 2e are turned on, and the other semiconductor switching elements are turned off. As a result, the V phase and the W phase of the power conversion means 2e are released from the cutoff, and the DC power source negative electrode side V phase semiconductor switching element and the W phase semiconductor switching element are short-circuited (S311). Thereby, the capacitors 99 and 100 are charged, and the charge pump charging operation is performed in the V phase and the W phase (S312). At this time, the current amplitude storage unit 4b calculates the effective value of the phase current from the detected current obtained from the current detection unit 3, and holds the maximum value of current amplitude (S313). If the current time is smaller than the variable tx at this stage (No in S314), a series of operations from S311 to S313 are repeated. At this stage, if the current time t is larger than the variable tx (Yes in S314), the cutoff signal generating means 5e turns on the cutoff signals xv and xw, so that the semiconductor switching element 95 of the power conversion means 2e, 97 is turned off, and the semiconductor switching elements 92 to 97 of the power conversion means 2e are all turned off (S315). This state is maintained until the current time becomes larger than the value obtained by adding 200 μsec to the variable tx (S316).

  When the current time becomes larger than the value obtained by adding 100 μsec to the variable tx, the value obtained by adding 100 μsec to the current time t is updated (S317). The cutoff signal generating means 5e turns off the cutoff signals xu and xw. At this time, the switch 38 maintains the output selection of the short-circuit vector generator 37 based on the time obtained from the timer 31. By this operation, the semiconductor switching elements 93 and 97 of the power conversion means 2e are turned on, and the other semiconductor switching elements are turned off. As a result, the U phase and the W phase of the power conversion means 2e are released from the cutoff, and the DC power source negative electrode side U phase semiconductor switching element and the W phase semiconductor switching element are short-circuited (S318). As a result, the capacitors 98 and 100 are charged, and the U-phase and W-phase charge pump charging operations are performed (S319). At this time, the current amplitude storage means 4b calculates the effective value of the phase current from the detected current obtained from the current detection means 3, and holds the maximum current amplitude value (S320). If the current time is smaller than the variable tx at this stage (No in S321), a series of operations from S318 to S320 are repeated. At this stage, if the current time t is larger than the variable tx (Yes in S321), the cutoff signal generating means 5e turns on the cutoff signals xu and xw, so that the semiconductor switching element 93 of the power conversion means 2e, 97 is turned off, and the semiconductor switching elements 92 to 97 of the power conversion means 2e are all turned off (S322). This state is maintained until the current time t becomes larger than the value obtained by adding 200 μsec to the variable tx, and when the current time t becomes larger than the value obtained by adding 200 μsec to the variable tx (S323), The same processing as S109 and after in FIG. 8 is performed. In the present embodiment, the time obtained by adding 200 μsec to the time in step S323 corresponds to the first time.

  As shown in this series of operations, “capacitor charging of the charge pump circuit” and “determination of whether the synchronous machine is idling and greater than a predetermined speed” from the start time to the first time In addition to simultaneous charging by short-circuit operation, “charging capacitor of charge pump circuit” is performed every two phases of U phase, V phase and W phase. Start-up processing time can be shortened compared to separate short-circuiting for “determination of whether the synchronous machine is in a free-running state and is faster than a predetermined speed”, and also due to “charge pump circuit capacitor charging” It is possible to suppress the generation of a large current to 2/3 times. As a result, there is an effect that the loss of the wiring connecting the positive electrode side of the DC power supply 91 and each phase charge pump circuit can be suppressed. Further, the DC power supply 91 does not need a power supply capacity for charging the three capacitors 98, 99, and 100 at the same time, and the power supply capacity that can charge two of the capacitors 98, 99, and 100 is sufficient. There is. Alternatively, it is possible to omit or reduce the resistance inserted in order to prevent inrush current so that the current capacity of the DC power supply 91 does not increase, thereby suppressing the cost, space and resistance loss for installing the resistor. There is an effect that can be done.

It is a block diagram which shows the whole structure of the control apparatus of the synchronous machine in Embodiment 1 of this invention. It is a block diagram which shows the internal structure of the current controller 33 in Embodiment 1 of this invention. It is a block diagram which shows the internal structure of the phase calculator 34 in Embodiment 1 of this invention. It is an example which shows a series of operation | movement waveforms in Embodiment 1 of this invention. It is a block diagram which shows the control apparatus of the synchronous machine in Embodiment 2 of this invention. It is a block diagram which shows the internal structure of the phase calculator 34a in Embodiment 2 of this invention. It is a block diagram which shows the internal structure of the current amplitude memory | storage means 4b in Embodiment 3 of this invention. It is a block diagram which shows the control apparatus of the synchronous machine in Embodiment 4 of this invention. It is a circuit diagram which shows the internal structure of the power conversion means 2d in Embodiment 5 of this invention. It is a flowchart of the control apparatus of a synchronous machine when the power conversion means in Embodiment 5 of this invention is applied to Embodiment 4. It is a block diagram which shows the whole structure of the control apparatus of the synchronous machine in Embodiment 6 of this invention. It is a circuit diagram which shows the internal structure of the power conversion means in Embodiment 6 of this invention. It is a figure which shows the relationship between the interruption | blocking signal which the interruption | blocking signal selector outputs in the period of the 1st time from the starting time in Embodiment 6 of this invention, and the three-phase current of a synchronous machine. It is a figure which shows the relationship between the phase voltage of a synchronous machine when the operation | movement in 1st time in Embodiment 6 of this invention is repeatedly implemented, and the current amplitude which the gain calculator inside a current amplitude memory means outputs. It is a flowchart of the control apparatus of the synchronous machine in Embodiment 6 of this invention. It is a figure which shows the relationship between the interruption | blocking signal which the interruption | blocking signal selector outputs in the period of the 1st time from the starting time in Embodiment 7 of this invention, and the three-phase current of a synchronous machine. It is a figure which shows the relationship between the phase voltage of a synchronous machine when the operation | movement at the 1st time in Embodiment 7 of this invention is repeatedly implemented, and the current amplitude which the gain calculator inside a current amplitude memory means outputs. It is a flowchart of the control apparatus of the synchronous machine in Embodiment 7 of this invention.

Explanation of symbols

  DESCRIPTION OF SYMBOLS 1 Synchronous machine, 2, 2d, 2e Power conversion means, 3 Current detection means, 4, 4b Current amplitude memory means, 5, 5e Breaking signal generation means, 6, 6c Voltage command calculation means, 10 Subtractor, 11 Absolute value calculation , 12 maximum value calculator, 13 switch, 14 timer, 15 delay circuit, 20 timer, 21, 21e cutoff signal selector, 30 coordinate converter, 31 timer, 32 current command generator, 33 current controller, 34, 34a, 34b Phase calculator, 35 coordinate converter, 36 PWM modulator, 37 short-circuit vector generator, 38 switch, 40 first-order lag calculator, 41 divider, 42 signal generator, 43 subtractor, 44 gain calculator, 45 integrator, 46 switch, 47 integrator, 50 gain calculator, 51 gain calculator, 52 subtractor, 53 subtractor, 60 square Calculator, 61 adder, 62 1/2 power calculator, 63 gain calculator, 70 speed command generator, 71 sensorless controller, 72 switch, 80 subtractor, 81 subtractor, 82 switch, 83 amplifier, 90, 91 DC power supply, 92-97 semiconductor switching element, 98-100 capacitor, 101-103 diode, 104-106, 104e-106e NOR circuit, 107-109, 107e-109e AND circuit.

Claims (12)

Current detection means for detecting the current of the synchronous machine;
Current amplitude storage means for storing, as a current amplitude maximum value, a value at which the current amplitude of the synchronous machine obtained from the current detection means is maximum;
Voltage command calculation means for outputting a voltage command to be applied to the synchronous machine;
Shut-off signal generating means for outputting a shut-off signal for shutting off voltage application to the synchronous machine;
Power conversion means for cutting off voltage application to the synchronous machine when the cut-off signal is on, and applying voltage to the synchronous machine based on the voltage command when the cut-off signal is off. ,
The shut-off signal generating means turns off the shut-off signal from the start time to the first time,
During the period from the first time to the second time, the cut-off signal is turned on, the current amplitude maximum value obtained from the current amplitude storage means is compared with a preset reference value, and the current amplitude maximum value is When it is smaller than the reference value, the cutoff signal is turned off during the period from the second time to the third time,
The voltage command calculation means is a voltage command that causes at least one phase of the synchronous machine to be short-circuited at least once based on the shut-off signal from the shut-off signal generating means from the start time to the first time. To control the power conversion means, to store the current amplitude maximum value in the current amplitude storage means,
A voltage command such that the current of the synchronous machine obtained from the current detection means becomes zero when the interruption signal from the interruption signal generating means is OFF during the period from the second time to the third time. To control the power conversion means so as to start the synchronous machine. The voltage command calculation means, for each phase, outputs a voltage command that causes one phase of the synchronous machine to be short-circuited based on the cutoff signal off from the cutoff signal generation means between the start time and the first time. The power conversion means is controlled by outputting at least once, and the current amplitude storage means stores a current amplitude that is maximum among the amplitudes in a short circuit for each phase as the current amplitude maximum value. The synchronous machine control device according to claim 1 . The voltage command calculation means outputs a voltage command that causes the two phases of the synchronous machine to be short-circuited for each line based on the shut-off signal from the shut-off signal generating means from the start time to the first time. The power conversion means is controlled by outputting at least once, and the current amplitude storage means stores a current amplitude that is maximum among the amplitudes in a short circuit between each line as the current amplitude maximum value. The synchronous machine control device according to claim 1 . The voltage command calculation means calculates the phase of the synchronous machine based on a voltage command that causes an output current to become zero during the period from the second time to the third time. The control device for a synchronous machine according to any one of claims 1 to 3 . The voltage command calculation means is
A short-circuit vector generator that outputs a voltage command such that at least one phase is short-circuited;
A changeover switch that selects the output of the short-circuit vector generator and outputs it to the power conversion means from the start-up time to the first time;
A first coordinate converter that converts the detection result of the current detection means onto dq axis coordinates that rotate in synchronization with the rotation of the armature of the synchronous machine, and outputs a d axis current and a q axis current;
A current command generator that outputs a zero current as a d-axis current command and a q-axis current command on the dq-axis coordinate system from the start time to the third time;
Current control for outputting the d-axis voltage command and the q-axis voltage command on the dq-axis coordinate so as to control the output from the first coordinate converter so as to coincide with the output from the current command generator. And
A phase calculator that calculates a rotational phase in which a magnetic flux phase of the synchronous machine and a d-axis on the dq-axis coordinate coincide with each other based on an output from the current controller;
A second coordinate converter for outputting a three-phase voltage command based on the output of the phase calculator and the output of the current controller;
A PWM modulator that performs PWM modulation based on the output of the second coordinate converter,
The changeover switch, until the third time from the second time, any one of claims 1 to 4, selects the output of the PWM modulator and outputs to the power converter The control device of the synchronous machine as described in 1. The phase calculator is
A first-order lag calculator for calculating a first-order lag for the d-axis voltage command output from the current controller and outputting a d-axis magnetic flux from the second time to the third time;
A divider for dividing the q-axis voltage command output from the current controller by the output of the first-order lag calculator to output an angular frequency;
An integrator that integrates the angular frequency output from the divider and outputs a phase;
The control device for a synchronous machine according to claim 5, further comprising: A first multiplication circuit for multiplying a d-axis current output from the first coordinate converter by a resistance value of the armature;
A second multiplication circuit that multiplies the q-axis current output from the first coordinate converter by the resistance value of the armature;
First subtraction means for outputting a deviation between a d-axis voltage command output from the current controller and a multiplication result of the first multiplication circuit;
Second subtracting means for outputting a deviation between the q-axis voltage command output from the current controller and the multiplication result of the second multiplication circuit;
Instead of outputting the d-axis magnetic flux by calculating the first-order lag of the d-axis voltage command output from the current controller during the period from the second time to the third time, the first-order lag calculator
During the period from the second time to the third time, the output of the first subtracting means is subjected to first order lag calculation to output a d-axis magnetic flux,
The divider divides the d-axis voltage command output from the current controller by the output of the first-order lag calculator, and outputs an angular frequency.
7. The control apparatus for a synchronous machine according to claim 6 , wherein the output of the second subtracter is divided by the output of the first-order lag calculator to output an angular frequency. A speed command generator for generating a rotational speed command according to time,
Based on the output of the speed command generator and the output of the current detection means, a sensorless sensor that outputs a three-phase voltage command so that the rotational speed of the synchronous machine matches the rotational speed command output by the speed command generator. A controller;
Phase / speed for selecting the output of the second coordinate converter from the second time to the fourth time, and selecting the output of the sensorless controller in a predetermined period after the fourth time. A switch, and
The changeover switch, instead of selecting the output of the PWM modulator and outputting it to the power conversion means during the period from the second time to the third time,
Until the third time from the second time, and selects the output of the phase-speed switching device according to any one of claims 5-7, characterized in that the output to the power conversion means Control device for synchronous machine. The blocking signal generating means, according to claim 1 wherein the current when the current amplitude maximum value obtained from the amplitude memory means is greater than the predetermined value, characterized in that on the predetermined period shutdown signal even after the second time control system for a synchronous machine according to any of the 1-8. Instead of the current amplitude storage means, the phase current effective value is calculated based on the current value obtained from the current detection means from the start time to the first time, and this phase current effective value becomes the maximum. control system for a synchronous machine according to any of claims 1 to 9, characterized in that with a current amplitude storage means for storing the value as a current amplitude maximum value. The power conversion means includes
A driving circuit for connecting the semiconductor switching element to a DC power source in a bridge shape and driving the semiconductor switching element;
A charge pump circuit that charges a capacitor serving as a power source for a drive circuit of the semiconductor switching element connected to the positive electrode side of the DC power supply while the semiconductor switching element connected to the negative electrode side of the DC power supply is on;
The voltage command calculation means is configured such that at least one phase of the semiconductor switching element connected to the negative electrode side of the DC power source of the power conversion means is short-circuited at least once from the start time to the first time. The control device for a synchronous machine according to any one of claims 1 to 10, wherein a voltage command is output. A first step of turning off the shut-off signal by the shut-off signal generating means between the start time and the first time;
Based on the shutoff signal off in the first step, a voltage command that causes at least one phase of the synchronous machine to be short-circuited at least once by the voltage command calculation means from the start time to the first time. A second step of outputting and controlling the power conversion means;
Between the start time and the first time, the current of the synchronous machine is detected by current detection means, and the value at which the detected current amplitude is maximum is stored as the current amplitude maximum value by the current amplitude storage means. A third step;
Between the first time and the second time, the cutoff signal generating means turns on the cutoff signal and compares the current amplitude maximum value stored in the third step with a preset reference value, A fourth step of turning off the cutoff signal during the period from the second time to the third time when the current amplitude maximum value is smaller than the reference value;
When the shut-off signal is turned off in the fourth step, the current of the synchronous machine is detected by the current detection means from the second time to the third time, and the voltage command calculation means And a step of controlling the power conversion means so as to start up the synchronous machine by outputting a voltage command so that the current becomes zero.

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