JP4563144B2 - Leakage current detection method and leak current detection device - Google Patents

Description

  The present invention relates to a leakage current detection method and a leakage current detection device for detecting a resistive leakage current in various electrical equipment management fields or electrical work fields.

  As a connection configuration of a transformer for voltage conversion in various power supply systems, for example, there is a ΔΔ connection shown in FIG. 40, and VCA, VBC, and VAB are phases between the A phase, B phase, and C phase on the primary side. Voltage, IA, IB, IC are currents of each phase, EU, EV, EW are voltages of each phase, Eu, Ev, Ew are voltages of each phase on the secondary side, Ia, Ib, Ic are currents of each phase, Vca, Vbc, and Vab indicate interphase voltages.

  The primary side voltages VCA, VBC, and VAB are typically 6.6 kV, for example, and the secondary side voltages Vca, Vbc, and Vab are typically 200 V, for example. FIG. 41 shows the configuration of YY connection, and the same reference numerals as those in FIG. 40 indicate the same names. FIG. 42 shows the case of secondary side neutral point extraction in the YY connection configuration. The same reference numerals as those in FIGS. 40 and 41 denote the same names, and Vag, Vbg and Vcg are the secondary side. The voltage between each phase and the neutral point is shown.

  FIG. 43 shows a configuration of YΔ connection in which the primary side is Y-connected and the secondary side is Δ-connected, and the same reference numerals as those in FIGS. 40 and 42 denote the same name portions. FIG. 44 shows the case where the primary side is Δ-connected and the secondary side is Y-connected, contrary to FIG. FIG. 45 shows a configuration of VV connection in which the primary side and the secondary side are V-connected. As a secondary side connection configuration, there is a single-phase three-wire configuration, and power can be supplied as 200V and 100V between phases. Besides the above-described connection configuration, there are a staggered connection, a Scott connection, a Wood bridge connection, a modified Wood Bridge connection, and the like. Further, there are configurations such as a combination of three phases and a single phase, a combination of two wires, three wires and four wires.

  In each of the connection configurations described above, a method of measuring insulation resistance in a non-live line state is common in order to prevent a failure due to a secondary side insulation failure or the like. However, it does not necessarily reflect the insulation state of the live line state. Therefore, various methods for detecting leakage current in a live line state have been proposed. The leakage current includes capacitive leakage current due to ground-to-ground capacitance and various capacitor connections, and resistive leakage current due to leakage resistance. Conventional leakage current detection methods for detecting resistive leakage current are I0 (zero) Phase current) detection method and Igr (resistive leakage current) detection method.

In the I0 detection method, a ZCT sensor having a current transformer configuration for detecting a zero-phase current flowing in a ground line connected between a neutral point and the ground is provided, or a ground line connected between an arbitrary phase and the ground. A leakage current is detected by providing a ZCT sensor having a current transformer configuration that detects a current flowing through the current transformer. In the Igr detection method, an injection transformer for injecting a signal of a predetermined frequency is provided, and the Igr1 method for detecting the injected signal and the zero-phase current detected by the ZCT sensor are determined using the reference voltage phase. The Igr2 method is known (see, for example, Patent Document 1 to Patent Document 16).
Japanese Examined Patent Publication No. 6-105276 JP-A-6-43196 JP 2001-242205 A Japanese Patent Laid-Open No. 5-180885 Japanese Utility Model Publication No. 6-57037 JP 2000-74979 A JP 2002-131362 A JP 2001-215247 A JP 2001-165971 A JP-A-8-182179 JP-A-8-182180 Japanese Patent Laid-Open No. 10-10184 Japanese Patent Laid-Open No. 10-78462 JP-A-10-339757 Japanese Utility Model Publication No. 7-29477 JP 2002-125313 A

  In the power supply system, as described above, various connection configurations are applied as the connection configuration of the transformer. In any of these configurations, there is a leakage current due to an insulation failure or a ground fault. When it occurs, it is necessary to quickly detect the leakage current and cut off the power supply to avoid the occurrence of a fire or the like. Therefore, as described above, various means have been proposed. However, it is possible to install a leakage current detection device without a power failure with respect to the conventional detection means for leakage current detection, making it unnecessary to take in a reference voltage and the like, and solving the following first to third problems. It is necessary.

The first problem is to increase the accuracy of detection of the resistive leakage current.
In the conventional I0 system, since the total of the capacitive leakage current and the resistive leakage current is viewed, it is difficult to accurately detect the resistive leakage current. The conventional Igr1 method is a method for injecting a signal and does not detect an actual leakage current, so that the detection accuracy is low. Further, in the conventional Igr2 method, since the reference voltage phase is taken from the outside, it is difficult to accurately detect the resistive leakage current due to the deviation of the reference voltage phase accompanying the slight deterioration of the ground phase. Furthermore, most of the conventional Igr2 systems are designed on the assumption that capacitive leakage current is balanced. Therefore, the capacitive leakage current is unbalanced and the capacity varies with load fluctuations. In an environment where the leakage current is unbalanced, the detection accuracy has deteriorated.

  The background of the increase in unbalanced capacitive leakage current is the inverterization of various devices due to the progress of energy saving. By making these various devices into inverters, the generation of high-frequency noise components from various devices increases. Therefore, equipment manufacturers add a noise prevention capacitor between the equipment and the ground for noise countermeasures. As a result, since the high-frequency current flows in the ground phase, the capacitive leakage current increases, and the unbalance due to the connection state of the load increases.

The second problem is speeding up the detection of resistive leakage current.
When detecting electric leakage, a time guard called a detection time limit is generally provided. This is to prevent inadvertent reporting of unnecessary electrical leakage and to ensure that necessary information can be reported. Since these temporal guards differ depending on the customer system, the detection device is optimized by setting in advance. Specific detection time limit setting values include, for example, 10 seconds / 30 seconds / 1 minute / 3 minutes / 5 minutes / 10 minutes. For example, when the detection time limit is set to 10 seconds, notification is not made unless the leakage current exceeds a certain value for 10 seconds continuously. The detection time limit accuracy is about ± 10%. For this reason, as the processing time required for detection, for example, when the detection time limit setting is 10 seconds, high-speed leakage current detection processing of about ± 1 second (within 2 seconds in width) is required. In general, when the target electric circuit system is expanded and further high accuracy is pursued, the processing time tends to increase, and speeding up of these processing times becomes a second problem.

The third problem is automatic switching between single phase and three phases.
There are single-phase and three-phase power supply systems subject to leakage current detection. In that case, in order to improve operability, it is easy to handle as a configuration that does not require a phase switching operation. It is requested. That is, the pursuit of simplicity of the detection device is a third problem.

  An object of the present invention is to solve the above first to third problems by using only a detection signal by ZCT.

The leakage current detection method of the present invention is a leakage current detection method for detecting a resistive leakage current by detecting a current flowing through a ground line in a power supply system by using ZCT, wherein the power supply system is detected from a ZCT detection signal. Of the leakage current waveform parameters including the amplitude and phase parameters of the fundamental wave of the ZCT detection signal and its n-order harmonic component based on the frequency information . An error between an output parameter including the amplitude and phase parameters of the fundamental wave and its n-th harmonic component defined as an output and the leakage waveform parameter is extracted, and the output parameter is corrected so that the error is minimized. was subjected to identification of the leakage system performed by the identification convergence of該漏electric system, viewed including the step of detecting resistive leakage current, the process is divided fundamental wave The k-th and n-th harmonic of the phase angle of the component theta, determined using the tan ^-1 function, the n next side multiplied by k / 2 integer fraction, k is the next side multiplied by n / 2 Then, the difference value is obtained (the denominator 2 with the n and k as the numerator can be any other integer), and a predetermined modulo operation is performed on the difference value to obtain the sin, cos function And outputting the output parameter not related to the reference phase and the phase parameter of the leakage current waveform parameter .

In addition, the method includes a step of decomposing each of an amplitude error and a phase error of a difference between the leakage waveform parameter and the output parameter into a resistive component and a capacitive component, and correcting a coefficient for leakage system identification.

An amplitude error that is a difference between the leakage waveform parameter and the output parameter for the k-order harmonic component, and an amplitude error that is a difference between the leakage waveform parameter and the output parameter for the n-order harmonic component. In the case of different polarities, the processing related to the coefficient correction for the leaked system identification is performed based on the difference between the two amplitude errors, and when the two amplitude errors are the same polarity, the processing related to the coefficient correction for the system identification is performed as being correlated. It includes the process of performing .

  This includes a process of performing a plurality of types of leakage system identification and detecting a resistive leakage current based on the leakage system identification result that minimizes each error.

The leakage current detection apparatus of the present invention is a leakage current detection apparatus for detecting and processing a resistive leakage current by inputting only a ZCT detection signal for detecting a current flowing in a ground line in a power supply system. The detection signal is extracted, the frequency information of the detection signal is extracted, and the leakage waveform parameter including the amplitude and phase parameters for the n-th harmonic component of the detection signal according to the frequency information is extracted. An error extraction means for extracting an error between the parameter extraction means and the output parameter of the leakage system identified with the leakage waveform parameter;
A system identification means for estimating and detecting a resistive leakage current by performing a leakage system identification process including a leakage path by correcting the output parameter so that the error by the error extraction means approaches zero ,
Each of the leakage waveform parameter extraction means and the system identification means obtains the phase angle θ of the k-th order and n-th order harmonic components excluding the fundamental wave using a tan ⁻¹ function, and k / 2 is multiplied by n / 2 on the k-th order side to obtain the difference value (the denominator 2 with n and k as the numerator can be any other integer), and A configuration in which the phase parameter of the leakage current waveform parameter not related to a reference phase is output or the output parameter is output by performing a predetermined modulo operation on the difference value and outputting it as a sin, cos function signal It comes to have.

In addition, the error extraction unit decomposes each of the difference between the amplitude error and the phase error between the leakage waveform parameter and the output parameter into a resistive component and a capacitive component, and as a coefficient correction of the system identification unit It has a configuration for inputting.

In addition, the error extraction unit may include an amplitude error that is a difference between the leakage waveform parameter for the k-order harmonic component and the output parameter, and a difference between the leakage waveform parameter for the n-order harmonic component and the output parameter. If the amplitude error is different in polarity, a signal based on the difference between both amplitude errors is input to the system identification means, and if both amplitude errors are the same polarity, a signal indicating that there is a correlation is input to the system identification means. It has a configuration for inputting .

  Further, the system identification means has a plurality of identification units for performing leakage system identification corresponding to a plurality of types of power supply systems, and the leakage by the identification unit that minimizes the error between the output parameter of the plurality of identification units and the leakage waveform parameter. Means for detecting a resistive leakage current based on the system identification result are provided.

  Without inputting configuration information such as three-phase or single-phase power supply system, frequency information, and reference phase information, only a ZCT detection signal that detects current flowing in the ground line is input to detect resistive leakage current Therefore, when installing a leakage current detection device, it does not require power outage work, and even if the capacitive leakage current is unbalanced and the unbalanced state changes due to load fluctuations, To improve the detection accuracy of resistive leakage current by decomposing the amplitude error and phase error corresponding to the error between the leakage waveform parameter and the output parameter into a resistive component and a capacitive component and identifying the leakage system. Is possible. Further, the convergence of the system identification can be speeded up by changing the control power for coefficient correction according to the error between the leakage waveform parameter and the output parameter. Also, the phase switching operation is performed by identifying the leakage system for multiple types of power supply systems, for example, three-phase and single-phase, and determining the one with the smaller error as the power supply system for detecting the resistive leakage current. It can be unnecessary.

  Referring to FIG. 1, the leakage current detection method of the present invention is a leakage current detection method for detecting a resistive leakage current by detecting a current flowing through a ground line in a power supply system by using ZCT1. The signal is input to the leakage waveform parameter extraction unit 2 to extract the frequency information of the power supply system. Based on this frequency information, the amplitude and phase of the fundamental wave of the ZCT detection signal and its n-th harmonic component are extracted. The leakage waveform parameter including the parameter is extracted, and the error extraction unit 4 extracts an error between the output parameter including the amplitude and phase parameters of the fundamental wave and its n-th harmonic component and the leakage waveform parameter. The system identification circuit unit 3 corrects the output parameter to identify the leakage system so that the leakage current is minimized. It is intended to include a process of detecting the resistive leakage current.

  The leakage current detection apparatus of the present invention is a leakage current detection apparatus for detecting a resistive leakage current by inputting only a ZCT detection signal for detecting a current flowing through a ground line in a power supply system. The detection signal is extracted, the frequency information of the detection signal is extracted, and the leakage waveform parameter including the amplitude and phase parameters for the n-th harmonic component of the detection signal according to the frequency information is extracted. Parameter extraction means (leakage waveform parameter extraction unit 2), error extraction means (error extraction unit 4) for extracting an error between the leakage waveform parameter and the output parameter, and an error caused by this error extraction means so as to approach zero The system identification means (system identification means for estimating and detecting the resistive leakage current by correcting the output parameter and performing the leakage system identification process including the leakage path) And a identification circuit portion 3) and.

  FIG. 1 is an explanatory diagram of the principle of the present invention, wherein 1 is a ZCT unit having a single or a plurality of ZCT sensors ZCT1 to ZCTm, and 2 is a leakage waveform parameter extracting means for extracting leakage waveform parameters such as amplitude and phase information. 3 is a system identification circuit unit as a system identification unit, 4 is an error extraction unit as an error extraction unit that extracts an error between the leakage waveform parameter and the output parameter in the system identification process, Indicates various setting / display control units. ZCT1 to ZCTm of the ZCT unit 1 have a known configuration provided so as to be able to detect currents flowing through m transformer-corresponding ground lines of the power supply system. The detection signal of the ZCT unit 1 is input to the leakage waveform parameter extraction unit 2, and the amplitude / phase / frequency information of the n-th harmonic contained in the detection signal of the ZCT unit 1 is obtained for system identification of leakage current. Necessary leakage waveform parameters (amplitude and phase parameters of the fundamental wave and its n-th harmonic) are extracted. When the ZCT unit 1 includes m ZCT1 to ZCTm, the leakage waveform parameter extraction unit 2 includes means for extracting a leakage waveform parameter in accordance with a ZCT-compatible detection signal by time division processing.

  The system identification circuit unit 3 includes a configuration for performing leakage system identification corresponding to a plurality of types of power supply systems such as three-phase and single-phase, for example, and the signals detected by the ZCT 1 to ZCTm of the ZCT unit 1 are a plurality of types. It determines which power supply system, and simulates a leakage current system including an actual leakage current path corresponding to ZCT1 to ZCTm by time division processing corresponding to ZCT1 to ZCTm. The system identification is performed by repeating and converging the error by feeding back the error to the system identification circuit unit 3 so that the output parameter identified in step 3 matches (the output extracted by the error extraction unit 4 is zero). Detects the resistive leakage current due to the identified leakage system, and based on the error in the system identification, It determines for example, a single-phase or three-phase supply system. The various setting / display control unit 5 performs setting such as setting of a threshold for the detection output of the resistive leakage current, setting of a duration exceeding the detection output threshold, and the like. Corresponding to the setting, detection signals such as resistive leakage current Igr output / caution / warning are output.

  FIG. 2 is an explanatory diagram of an alarm system to which the present invention is applied. An alarm detection transmission device 12 is provided in a power receiving facility (cubicle) 11 of a power consumer 13 such as a factory, office building, school, hospital or the like. In the detection transmission device 12, when leakage detection is performed as an abnormality detection, this detection signal is sent to, for example, an alarm reception notification device in a security room or office 15 via a 100 V light line (power line carrier) or communication line. 14, and a leakage notification is sent to the monitoring center 16 via the telephone network or the like automatically or by a security guard. In the case of a guard, it is also possible to send a leakage notice to the monitoring center 16 by facsimile machine FAX or telephone. In the monitoring center 16, maintenance personnel can be dispatched by the emergency dispatch vehicle 17 or the like to repair the location where the abnormality has occurred.

  FIG. 3 is an explanatory diagram of ZCT connection. For example, in order to detect the current flowing through the ground line by grounding the b phase among the a, b, and c phases on the secondary side of the ΔΔ connection transformer. This shows a case where a ZCT having a current transformer configuration is provided. As a three-phase power supply system, when the secondary side of the transformer is Δ-connected, a b-phase grounding configuration is generally used. Further, ra, rb, and rc denote ground equivalent resistances, and ca, cb, and cc denote ground equivalent capacitances. Under normal conditions, the ground-to-ground equivalent resistances ra, rb, and rc show large values. Therefore, the resistive leakage current is a negligible value. The ground-to-ground equivalent capacities ca, cb, and cc include power factor improving capacitors and the like that are not shown. Furthermore, since there are many harmonic components due to inverter devices, etc., the capacitive leakage current is relatively low. A large value will be shown. Then, since the current of the vector sum of the current obtained by synthesizing the vector of the resistive leakage current of each phase and the current obtained by synthesizing the vector of the capacitive leakage current of each phase flows to the ground line, this is detected by ZCT. By inputting this ZCT detection signal to the leakage current detection device, the leakage system identification that simulates the leakage path is performed, and the resistive leakage current is estimated and detected with high accuracy and speed.

  FIG. 4 shows a leakage detection system in which the configuration of the present invention shown in FIG. 1 is applied to the configuration shown in FIG. 3. As an example, the b phase of the three phases a, b, and c is grounded by a ground line. A case where a ground fault occurs in the c phase in the configuration in which the ZCT is provided so that the current flowing through the ground line can be detected will be described. Therefore, the c-phase is connected to the ground equivalent resistance through which the resistive leakage current Igr flows and the ground equivalent capacitance through which the capacitive leakage current Igc flows, and the a-phase has a negligible magnitude between the ground equivalent resistance. Therefore, the illustration is omitted, and only the equivalent ground-to-ground capacity through which the capacitive leakage current Igc flows is illustrated. In addition, as shown in FIG. 1, the leakage current detection device for inputting a signal from the ZCT for detecting the current flowing through the grounding line includes a leakage waveform parameter extraction unit 2 connected to the ZCT, a system identification circuit unit 3, and an error. The system identification circuit unit 3 has a configuration including an extraction unit 4 and various setting / display control units 5, and the system identification circuit unit 3 performs correction processing so that the error amount approaches zero by feedback of the error amount from the error extraction unit 4. Then, the leakage system identification including the leakage path is performed, and the resistive leakage current Igr is detected.

  In addition, a case where a single ZCT is connected to the leakage current detection device is shown, but as shown in FIG. 1, it is also possible to connect a plurality of ZCTs corresponding to the power supply system. Although the case where the leakage current detection device is arranged at a position close to the ZCT is shown, this leakage current detection device may be arranged at a remote location and connected to the ZCT via networks known for various transmission methods. Is possible. It is also possible to connect via a wireless network as well as a wired network. When signals from ZCT are transmitted via each network, they are transmitted to the leakage current detection device according to the format according to the transmission method by ZCT compatible addressing, etc., and the leakage current detection device identifies each ZCT. Thus, it is possible to detect the resistive leakage current of the ZCT-compliant power supply system.

  FIG. 5 shows a case where the leakage current waveform in the case of a single phase in the case of the ratio of the resistive leakage current of 2 and the capacitive leakage current of 2 is obtained by simulation. There are many components, and the waveform is greatly distorted from the sine wave of the fundamental frequency.

  FIG. 6 is an explanatory diagram of a leakage current spectrum, in which the horizontal axis indicates frequency [Hz], the vertical axis indicates power [dBm], and the spectrum for 0 to 500 Hz in a 50 Hz distribution area. That is, it can be seen that a harmonic component of an integral multiple of 50 Hz is included. Depending on the configuration of the power supply system, the third harmonic component may be significantly less than the fifth harmonic component and the seventh harmonic component. For example, when the secondary winding of the transformer is Δ-connected, the third harmonic component may be in phase with each phase, resulting in a current circulating in the Δ-connection.

  FIG. 7 shows an example of the ground fault pattern corresponding to the spectrum of the first, third, fifth and seventh harmonic components. (A) ('0200) is a single-phase capacitive leakage current. (B) ('1200) is a single-phase capacitive leakage current plus a resistive leakage current, and (c) (' 0202) is a three-phase three-wire system with only a capacitive leakage current In the case of (d) ('1202), when a resistive leakage current is applied to the a phase of the three-phase three-wire system, (e) (' 0212) is a three-phase three-wire system and the capacitive leakage current is The cases where the a leakage current occurs in the a phase and the c phase and the resistive leakage current occurs in the c phase are respectively shown. The vertical axis represents the power of the primary / third / fifth / seventh harmonics with the combined power normalized to 1.0. That is, the leakage current waveform is slightly different depending on various leakage patterns, and the spectrum is slightly different. Therefore, it is also possible to determine whether or not a resistive leakage current is included based on the power pattern of the nth harmonic component included in the signal from the ZCT.

  FIG. 8 is an explanatory diagram of the normalized amplitude distribution of the third, fifth, and seventh harmonic components, and the third, fifth, and seventh harmonics of the same leakage pattern as that in FIG. The amplitude distribution when the power of the wave component is normalized to 1.0 is shown.

  FIG. 9 is an explanatory diagram of a combined waveform of n-order harmonic components, and shows examples of leakage waveforms when the n-order harmonic component is large and small. In the case of b-phase grounding in a three-phase three-wire system, capacitive leakage current occurs in both the a-phase and c-phase, and resistive leakage current also occurs in both the a-phase and c-phase, The left side shows the case where the nth order harmonic component is extremely large and the waveform is greatly distorted, and the other (right side) shows the case where the nth order harmonic component is relatively small and the waveform is not distorted so much. Yes. When this one waveform is compared with the other waveform, the two waveforms are greatly different, but the resistive leakage current has the same value. FIG. 6 described above shows an actual measurement waveform in the actual field, and the level of the nth harmonic is a waveform that is reduced by about 18 dB from the fundamental wave.

  FIG. 10 is an explanatory diagram of amplitude distribution of the third and seventh harmonics when the fifth harmonic is normalized. For example, in the case where the level of the fifth harmonic is normalized to 1.0, The power values of the third and seventh orders are shown in a two-dimensional graph, and various types of assumed leakage patterns are plotted. This indicates that the third and seventh amplitude coordinate positions can be specified by the leakage patterns. ing. The same result was obtained in the simulation for one and the other waveform shown in FIG. Although it is the power of the n-th harmonic, even if the amount of leakage is the same, the combined power value is greatly different for each leakage system. However, the same deterioration pattern is observed when the power is normalized. Therefore, it can be understood that some normalization means is effective in order to perform stable leakage detection.

  FIG. 11 is an explanatory diagram of an embodiment of the present invention, in which 1 is a ZCT unit, 2 is a leakage waveform parameter extraction unit, 3 is a system identification circuit unit, 4 is an error extraction unit, 5 is various setting / display control units, 21 is a filter unit, 22 is a data acquisition unit, 23 is a reference value extraction unit, 24 is a frequency information extraction unit, 25 is an I0 detection unit, 31 is a three-phase voltage generation unit, 32 is a single-phase voltage generation unit, and 33 is A three-phase identification unit, 34 is a single-phase identification unit, 35 is an Igr calculation / selection unit, and 36 is an Igr determination / timer monitoring unit. The arithmetic processing function of each part can also be realized by the arithmetic processing function of the processor.

  The filter unit 21 of the leakage waveform parameter extraction unit 2 includes a termination circuit unit corresponding to ZCT1 to ZCTm of the ZCT unit 1, a selection circuit SEL for processing in a time division manner, a gain switching unit GSW, and a low-pass filter LPF. Each of the ZCT1 to ZCTm of the ZCT unit 1 is terminated with a predetermined impedance by the termination circuit 1 to the termination circuit m, and is input to the selection circuit SEL as a voltage value. The selection circuit SEL selects a ZCT that is a target for detecting a leakage current. For example, when selecting three ZCTs, the selection circuit SEL can be sequentially selected in units of 0.6 seconds, for example. In the case of one ZCT, the selection circuit SEL can be omitted or fixedly selected. Further, selection information by the selection circuit SEL can be output together with an Igr output from the Igr determination / timer monitoring unit 36 so that it can be identified which one is ZCT1 to ZCTm. That is, it is possible to output an Igr output caution / alarm together with information on the power supply system.

  The gain switching unit GSW corresponds to a variable gain amplifier that switches the amplification gain for the ZCT output signal selected by the selection circuit SEL. Since the ZCT output signal corresponds to a wide range of, for example, about 50 mA to 800 mA, the amplification gain for the ZCT output signal sequentially selected by the selection circuit SEL is switched in order to ensure a predetermined dynamic range. . The selection circuit SEL and the gain switching unit GSW are controlled by the analog control unit of the data capturing unit 22.

  The data acquisition unit 22 includes an AD converter A / D, an offset removal circuit Offset, a buffer BUFF, and an analog control unit, and the frequency information extraction unit 24 includes a carrier generation unit CRR0. , A demodulator DEMO, a low-pass filter LPF0, a complex conjugate circuit, a frequency converter, and a carrier generator CRRn. The I0 detection unit 25 includes a power calculation unit PWR and a determination unit, and the reference value extraction unit 23 includes demodulation units DEM1 to demn, low-pass filters LPF1 to LPFn, an amplitude phase correction circuit, an amplitude / Phase difference extraction circuit.

  The offset removal circuit Offset of the data capturing unit 22 calculates the DC offset component because each of the digital signals corresponding to ZCT1 to ZCTm converted by the AD converter A / D includes a DC offset component. Processing is performed so that the offset component becomes zero, and the offset component is temporarily stored in the buffer BUFF. Thereby, it is possible to further improve the accuracy of detecting the resistive leakage current by digital arithmetic processing. Then, the data is read from the buffer BUFF and input to the analog control unit, the demodulation units DEM1 to DEMn of the reference value extraction unit 23, and the demodulation unit DEM0 of the frequency information extraction unit 25.

  The analog control unit increases the gain of the gain switching unit GSW when the signal level input to the buffer BUFF is lower than the lower limit value of the predetermined range with respect to the signal level from the ZCT selected by the selection circuit SEL. When the upper limit of the predetermined range is exceeded, gain switching control is performed so as to decrease the gain of the gain switching unit GSW. When the signal level input to the buffer BUFF is always within a predetermined range, the control structure for automatic gain switching can be omitted by setting the gain of the gain switching unit GSW as a preset value. The same applies when the AD converter A / D has a wide dynamic range.

  FIG. 12 is an explanatory diagram of the carrier generation unit CRR0 and the demodulation units DEM0 to DEMn of the frequency information extraction unit 24 in FIG. 11. The carrier generation unit CRR0 of the frequency information extraction unit 24 is a fundamental wave of a signal from ZCT. However, since the fundamental frequency in the power supply system is generally 50 Hz or 60 Hz, for example, data for generating a carrier having a frequency of 55 Hz in the middle is stored in ROM (read). (Only memory). The ROM stored data in this case can be set to (cos (2π55 (Hz) t) −jsin (2π55 (Hz) t)) indicating vector rotation at 55 Hz with a radius of 1.0.

  The demodulator DEM0 of the frequency information extractor 24 and the demodulator DEM0 to DEMn of the reference value extractor 23 multiply the input signal by the order of the fundamental wave and its harmonics and multiply by cos (nω). The frequency information extraction unit 24 includes a multiplier that obtains a demodulated output (DEM output) of the part and a multiplier that multiplies -sin (nω) to obtain a demodulated output (DEM output) of the imaginary part. , The signal from the buffer BUFF becomes a DEM input to the demodulator DEM0, and the carrier cos (2π55 (Hz) t) −jsin (2π55 (Hz) t) cos (2π55 (Hz) t) from the carrier generator CRR0, sin (2π55 (Hz) t) is input to each multiplier through a path indicated by a dotted arrow, and the demodulated output signal is input to an analog control unit and a low-pass filter. A complex conjugate circuit via PF0, input to the power calculating unit PWR of I0 detection unit 25.

  For the demodulating units DEM1 to DEMn of the reference value extracting unit 23, the signals from the buffer BUFF become the respective DEM inputs, and the carrier corresponding to the order from the carrier generating unit CRRn of the frequency information extracting unit 24 (extracted as described later). The first-order harmonic signal including the primary synchronized with the power source frequency; cos (nω), −sin (nω)) is input to the multiplier for demodulation. As a result, the demodulated output signal corresponding to the nth-order harmonic signal indicates the nth-order harmonic component contained in the ZCT detection signal as in the case of the synchronous detection, and the amplitude and phase correction is performed via the low-pass filters LPF1 to LPFn, respectively. Input to the circuit.

  FIG. 13 shows an example of the configuration of the low-pass filter LPF0 of the frequency information extraction unit 22 and the low-pass filters LPF1 to LPFn of the reference value extraction unit 23. The unit time delay circuit T, the input signal and the delay circuit T are shown in FIG. A case is shown in which a transversal FIR filter configuration is applied, which includes a multiplier for multiplying the intervening signal by coefficients ω0 to ωk, respectively, and an adder Σ. For example, since the low-pass filter LPF0 of the frequency information extraction unit 24 wants to remove unnecessary components other than the vicinity of 55 Hz, the bandwidth is about 55 Hz ± 25 Hz. Similarly, the other low-pass filters LPF1 to LPFn are set to a band corresponding to the nth-order harmonic, and the cutoff frequency is set to, for example, about ± 25 Hz with respect to the nth-order harmonic frequency, and unnecessary harmonic signals are removed. By using the carrier generation unit CRR0, the demodulation unit DEM0, and the low-pass filter LPF0 in the frequency information extraction unit 24, it is possible to extract a frequency between 30 Hz and 80 Hz. Therefore, the leakage signal can be extracted even before the frequency synchronization of 50 Hz / 60 Hz is established.

  FIG. 14 is an explanatory diagram of the I0 detection unit 25, which includes a power calculation unit PWR and a determination circuit, inputs a demodulated signal through the low-pass filter LPF0, and squares the demodulated signal by the power calculation unit PWR. The power is obtained, the difference between the power and the preset value REF is obtained by the calculation unit of the judgment circuit, and if the polarity is negative in the polarity judgment unit, it is judged that there is a leakage current (I0DEC = 1). If the polarity is positive, it is determined that there is no leakage current (I0DEC = 0), and the detection signal I0DEC is output and input to the LPF denormalization unit of the Igr determination / timer monitoring unit 36. In this case, in the case of the detection signal I0DEC having no leakage current, the resistance leakage current detection processing after the Igr determination / timer monitoring unit 36 is not performed in order to prevent malfunction such as sending of an alarm.

FIG. 15 is an explanatory diagram of the complex conjugate circuit and the frequency conversion unit in the frequency information extracting unit 24. The complex conjugate circuit of the frequency information extracting unit 24 includes a complex circuit including a delay circuit of unit time T and a multiplier. A conjugate circuit and a low-pass filter LPF are provided, and the output signal of the low-pass filter LPF0 is input to the multiplier and the delay circuit as a complex conjugate extraction input. In this case, the sampling interval signal converted by the AD converter A / D is input to the complex conjugate circuit via the buffer BUFF and further to the complex conjugate circuit via the demodulator DEM0 and the low-pass filter LPF0. Enter as shown. When signals having this time difference are LPF01 and LPF02, respectively, the complex conjugate extraction output Y is
Y = LPF02 × (LPF01) * (1)
It can be expressed as. Note that * indicates a complex conjugate operation.

  The complex conjugate extraction output Y from which the signal in the unnecessary band is removed by the low-pass filter LPF is a vector that shifts counterclockwise when the frequency of the signal input to the AD converter A / D is higher than 55 Hz. If it is lower, the vector is shifted in the clockwise direction. This vector signal is input to the frequency conversion unit as frequency information extraction input indicated by a dotted arrow. This frequency conversion unit includes a frequency information extraction circuit 61 and a carrier generation unit (CRRn) 62, and the frequency information extraction circuit 61 has a configuration including a vector information → Δθ conversion circuit 63 and a Δθ + 55 Hz addition MOD circuit 64.

When the frequency of the captured leakage current is f _AC , the arbitrary demodulation frequency is f _DEM , and the deviation between the captured leakage current frequency and the arbitrary demodulation frequency is Δf,
f _AC = f _DEM + Δf (2)
It becomes.

A plurality of frequencies for demodulation are generated based on two pieces of frequency information of an arbitrarily determined demodulation frequency f _DEM and Δf obtained by preprocessing. When the primary frequency f _DEM1 , the tertiary frequency f _DEM3 , the quintic frequency f _DEM5 , and the seventh frequency f _DEM7 are obtained, the following equation is obtained.
f _DEM1 = f _DEM + Δf
f _DEM3 = 3 × (f _DEM + Δf)
f _DEM5 = 5 × (f _DEM + Δf)
f _DEM7 = 7 × (f _DEM + Δf)
Therefore, the general formula for the frequency of the nth harmonic is:
_{f DEMn = n × (f DEM} + Δf) ··· (3)
It can be expressed as.

Further, the complex conjugate extraction output from the complex conjugate circuit is input to the frequency information extraction circuit 61 of the frequency conversion unit as the frequency information extraction input, and the complex vector information (X + jY) is input to the vector information → Δθ conversion circuit, and tan ^{− Using one} function, it is converted into angle information Δθ (proportional to the frequency information of Δf). Then, it is added (frequency addition) to the 55 Hz angle information generated by the carrier generation unit CRR0, and rotation angle information for each sample is obtained (± 180 degree mod addition). The carrier from the carrier generation unit CRRn A frequency information extraction output (rotation vector signal of CRRn = (cos (nωt) −jsin (nωt))) can be obtained.

  The frequency information extraction circuit 61 can be realized by various configurations in addition to the above-described configuration. For example, the complex conjugate signal (x + jy) is converted into an address (for example, upper x + lower y), and the ROM is determined by the converted address. To obtain a desired frequency (51.1 Hz / 60.3 Hz, etc.). Alternatively, it is possible to convert the output of the complex conjugate circuit into vector information having a radius of 1.0 and use only the imaginary component as a ROM address to convert it into desired frequency information. Alternatively, it is possible to adopt a configuration in which frequency extraction is directly performed using a PLL circuit (phase synchronization circuit).

FIG. 16 is an explanatory diagram of the amplitude phase correction circuit of the reference value extraction unit 23, and various amplitude characteristics / phase characteristics in the processing configuration from the ZCT unit 1 are not flat. As described above, if the amplitude phase characteristic is not flat, it leads to a detection error of leakage current. Therefore, by correcting this, the detection accuracy can be improved. The correction means various exist, for example, as shown, to store the (Ae (jcθ _n) indicating the exponentiation multiplier e as (jcθ _n)) ROM in advance correction value, the multiplier of this correction value This shows a case where the correction is made by inputting to. For this correction value, a known resistive leakage current is input, and an error from the value corresponding to the input resistive leakage current is obtained for the outputs of the low-pass filters LPF1 to LPFn, and this is stored in advance in the ROM as a correction value. Can be stored. Alternatively, it is possible to apply a phase difference extraction means described later.

  FIG. 17 is an explanatory diagram of an amplitude extraction circuit in the amplitude / phase difference extraction circuit of the reference value extraction unit 23. Reference numerals 71, 74, 81, 82 and 85 denote square circuits for obtaining power, 72, 76, 83, 87 is a 1 / a circuit, 73, 75, 84 and 86 are square root circuits, and 77, 78, 79 and 80 are multipliers. The output signals of the amplitude and phase correction circuits corresponding to the low-pass filters LPF1 to LPFn are indicated as LPF (1) to LPF (n), and the square circuit 71 outputs a signal SynLPFP indicating power to the primary signal LPF (1). Further, a primary amplitude normalized signal LPFN (1) is output by arithmetic processing by the square root circuit 73, the 1 / a circuit 74, the multiplication circuit 77, the square circuit 74, and the square root circuit 75, and 1 / a A primary signal LPFE (1) is output by arithmetic processing including the circuit 76 and the multiplier circuit 78.

  Also, the n-th harmonic signals LPF (k) to LPF (n) excluding the first-order harmonic signal LPF (1) are squared by the square circuits 81 and 82 to determine the power, and are synthesized and combined with the square root circuit 84 and 1 / a. By the arithmetic processing by the circuit 83, the multiplier circuit 79, the square circuit 85, and the square root circuit 86, the amplitude normalization signal LPFN (n) is output, and further, by the arithmetic processing including the 1 / a circuit 87 and the multiplier circuit 80, The signal LPFE (n) is output.

  The important earth leakage waveform parameters in the system identification of earth leakage are explained. The leakage waveform is a very complicated waveform as shown in FIGS. 5 to 9, but it is clear that it is a repetitive waveform based on the power supply frequency. The reference voltage phase is extremely important for the detection of the resistive leakage current, but the reference phase cannot be specified only from the leakage waveform input to the A / D converter. In practice, it is very easy to identify a leakage system assuming that the reference phase can be specified, but it is not practical. For this reason, it is indispensable to create an algorithm that does not depend on the reference phase in the leakage system identification. In response to the question of what is the leakage waveform parameter that is fundamental to the leakage system identification from the signal captured by the A / D converter of the data capture unit 22 and what is the parameter that is not swung to the reference phase? One answer is an autocorrelation sequence.

  When the input signal is f (t), the autocorrelation sequence A (τ) is A (τ) = Σ (f (t) × (f (t + τ)) *) (where * indicates a complex conjugate operation) For example, the autocorrelation series of resistive leakage, capacitive leakage, and combined leakage (when resistive leakage and capacitive leakage occur) are as shown in FIGS. 18A, 18B, and 18C. become. That is, the autocorrelation sequence differs depending on the leakage condition, but the autocorrelation sequence has a constant value regardless of the extraction phase of the extracted signal f (t). Therefore, if system identification is performed using an autocorrelation sequence, system identification independent of the reference phase is possible.

  The problem is the integration period of the autocorrelation calculation of the waveform, but it is desirable that it is one cycle of the power supply frequency. In the waveform extracted by A / D conversion, it is difficult to cut out one period from the quantization of sampling, but in synchronization with the input signal, it is demodulated by the demodulation circuit demn, and unnecessary band is obtained by the low-pass filter LPFn. If the baseband signal is removed, integration for one period is extremely easy and can be realized accurately.

  The autocorrelation sequence calculation has an extremely large amount of calculation, and when this calculation is introduced, the amount of processing increases dramatically. On the other hand, it is well known that the autocorrelation sequence represents the power spectrum of the input waveform. In fact, the power spectrum is not affected by the phase change. Actually, even if arbitrary phase rotation is performed on the vector signal of the low-pass filter LPFn, the autocorrelation sequence before the phase rotation and the autocorrelation sequence after the phase rotation match. This is because the autocorrelation calculation itself calculates a complex conjugate vector, and the phase component disappears. Therefore, the power of the output of the low-pass filter LPFn is seen to indicate that the autocorrelation calculation need not be performed.

  That is, the output of the low-pass filter LPFn of the reference value extraction unit 23 is multiplied by each nth-order harmonic vector signal as a complex conjugate vector having a radius of 1.0 to obtain a signal independent of the phase, which is identified as a leakage system identification As a reference signal. At the same time, a similar phase normalization circuit is also introduced to the EQL output in the system identification circuit unit 3 to obtain an output independent of the phase, which is used as the output of the system identification circuit unit 3, and is used as a reference by the error extraction unit 4. An error with the value is obtained, and the leakage system is identified so that this error is minimized. As a result, the amount of calculation can be drastically reduced.

FIG. 19 is an explanatory diagram of the phase difference extraction circuit of the amplitude / phase difference extraction circuit in the reference value extraction unit 23 (see FIG. 11). The nth and kth orders of the output of the amplitude extraction circuit of FIG. LPFE (n) and LPFE (k) are input, and the angle extraction unit obtains the phase angle θ using the tan ⁻¹ function, the nth order side is multiplied by k / 2, and the kth order side is n / The difference is obtained by multiplying by 2, and the difference output is subjected to, for example, a modulo operation of 180 degrees by the modulo circuit MOD, and output as a signal PHLPA of sin and cos functions. The denominator 2 with n and k as numerators can be any other integer.

  With respect to the captured leakage waveform, the waveform extraction phase is indefinite, so it is necessary to extract parameters of the leakage waveform independent of the extraction phase. In particular, this is a shift between the reference phase and the cut-out phase. In the case of the nth harmonic, if the reference phase is shifted by 10 degrees, the phase is 50 degrees for the fifth harmonic and 70 degrees for the seventh harmonic. Rotation will occur. In other words, if the fifth-order angle is multiplied by 7 and the seventh-order angle is multiplied by 5 to obtain the difference, the angle of deviation from the reference phase will disappear. Therefore, stable leakage waveform parameter extraction independent of the reference phase can be performed.

  In addition, even if the phase of the fundamental wave of the power line does not change, both the a-phase and c-phase in the case of three-phase b-phase grounding are applied to the harmonic components within the load after the load is supplied with power. Distortion occurs, and this distortion is attenuated by a noise removal filter formed between the load and the power line, and is rotated in phase to return to the power line. On the other hand, since the secondary side and the primary side of the high-voltage transformer are basically connected by a passive circuit, the total total distortion of the consumer finally appears as a voltage effect on the high-voltage side. It will appear as distortion on the next side. Accordingly, stable strain is observed in both the a phase and the c phase, but since the load conditions are different between the a phase and the c phase, the phases finally differ slightly. For this reason, as for the phase difference information, extracting a phase difference signal only from an nth-order harmonic signal without using a primary signal at least becomes a key point for high-accuracy leakage detection.

  For example, as described above, when the reference phase of the first harmonic is shifted by a degrees, the reference phase of the third harmonic is 3a degrees, the reference phase of the fifth harmonic is 5a degrees, and the reference phase of the seventh harmonic is Is 7a degrees, and the reference phase of the nth harmonic is shifted by na degrees. Therefore, by calculating a phase difference signal that is a multiple of each nth harmonic and calculating the difference, a phase difference signal that is not related to the reference phase. Can be extracted. Specifically, it is as follows.

If the primary waveform phase is θ1 + a, the fifth-order waveform phase is θ5 + 5a, and the seventh-order waveform phase is θ7 + 7a,
(Seventh-fifth)-(twice the primary) is
= (Θ7 + 7a) − (θ5 + 5a) −2 (θ1 + a)
= (Θ7-θ5-2θ1) + (7a-5a-2a)
= (Θ7-θ5-2θ1)
Thus, the reference phase a disappears.
Similarly, (5th order-5 times the first order) is
= (Θ5 + 5a) −5 (θ1 + a)
= (Θ5-5θ1) + (5a-5a)
= (Θ5-5θ1)
In the same manner, higher harmonics can be calculated.
(Seventh-seven times the primary) is
= (Θ7 + 7a) −7 (θ1 + a)
= (Θ7-7θ1) + (7a-7a)
= (Θ7-7θ1)
Thus, a value obtained by eliminating the reference phase a is obtained.

  When the transformer is Δ-connected, the third harmonic is in phase, and the third-harmonic component is reduced by circulating in the Δ connection. Therefore, in FIG. 19, it is possible to make n = 7 and k = 5 so that the third harmonic component of n = 3 is not used. As described above, it can be seen that, even when the cutout phase of the leakage waveform is cut out in a state where the reference phase is indefinite, the leakage waveform parameter irrelevant to the reference phase can be extracted by calculating the phase difference between the plurality of harmonics.

  Until now, if the reference phase is not taken from the outside, the detection of the resistive leakage current based on the reference phase is not common sense, but it can be accurately converted to the reference phase without taking in the reference phase from the outside. Corresponding information can be obtained. In addition, since the reference phase has been acquired from the outside in the past, if the grounding line condition deteriorates, the reference phase of the acquisition will be shifted as it is, and the leakage current cannot be detected accurately. Since the detection process of the resistive leakage current can be executed using the actual detection signal based only on the detection signal, the accurate resistive leakage current can be detected regardless of the deterioration of the ground resistance of the ground line.

  In addition, although three types of equations can be established from the three types of primary, fifth, and seventh harmonics that do not include third harmonics, mathematically, if two of these equations are determined, the remaining Since only one equation is determined, only two equations are meaningful as information. In this case, if the multiple of the primary phase (θ1 + a) is increased, the amount of phase rotation increases and the leakage waveform parameter becomes unusable. For this reason, it is desirable to suppress this multiple to about twice as much as possible.

  FIG. 20 is an explanatory diagram of phase error, where the horizontal axis indicates the angle (0 to 90 degrees), the vertical axis indicates the phase angle difference, and the case where the fifth and seventh harmonics are used, When the phase θ1 of the leakage waveform is 0 degree, 30 degrees, 60 degrees, and 90 degrees, the angle difference is shown when the estimated phase in the system identification circuit unit 3 is 0 to 90 degrees. This indicates that the phase θ1 of the leakage waveform and the estimated phase of the system identification circuit unit 3 coincide with each other.

  The system identification circuit unit 3 (see FIG. 11) includes a three-phase voltage generation unit 31, a single-phase voltage generation unit 32, a three-phase identification unit 33, a single-phase identification unit 34, an Igr calculation / selection unit 35, , The Igr determination / timer monitoring unit 36, the three-phase identification unit 33 and the single-phase identification unit 34 are respectively an EQLn unit (leakage current simulation circuit), an amplitude / phase difference calculation circuit, and an EQL coefficient correction circuit. It has the composition containing. The Igr calculation / selection unit 35 includes a phase determination unit, an Igr calculation unit, and an Igr selection unit, and the Igr determination / timer monitoring unit 36 includes an LPF inverse normalization unit and an Igr determination unit. And a timer monitoring unit. The error extracting unit 4 has a configuration including an error calculating unit, an error synthesizing unit, and an error decomposing unit, and various setting / display control units 5 The Igr determination / timer monitoring unit 36 has a configuration including various setting display control units that perform setting control on the Igr determination unit and the timer monitoring unit.

FIG. 21 is an explanatory diagram of the reference voltage generation unit. In the three-phase voltage generation unit 31 that generates the reference voltage, the b-phase grounding in the three phases of a phase, b phase, and c phase of 120 degrees phase difference, respectively. In this case, the primary reference voltages VGa (1), VGc (1) to n-order reference voltages VGa (n), VGc (n) of the a phase and the c phase having a phase difference of 120 degrees are shown. The case where it comprises with ROM to generate is shown. The single-phase voltage generator 32 can also be realized with the same ROM configuration. However, in the case of the single-phase voltage generator 32, a reference voltage with a phase difference of 180 degrees between the a phase and the c phase is generated. The configuration. In the case of the primary to n-order three-phase reference voltages VGa (1) to VGc (1) to VGa (n) to VGc (n) of the a-phase, b-phase, and c-phase, the a-phase reference voltage phase is set to 0 degree. Then, the primary voltage phase is represented by the equations (4) to (6), and the n-order voltage phase is represented by the equations (7) to (9).

  FIG. 22 is an explanatory diagram of the EQL unit, and shows an EQLn (leakage current simulation circuit) unit of the three-phase identification unit 33 and the single-phase identification unit 34. The a-phase reference voltage VGa (1) and the c-phase reference voltage VGc (1) input from the three-phase voltage generation unit 31 to the three-phase identification unit 33 have a phase difference of 120 degrees. As described above, the a-phase reference voltage VGa (1) and the c-phase reference voltage VGc (1) input from the single-phase voltage generation unit 32 to the single-phase identification unit 34 have a phase difference of 180 degrees. It is. Also, the parameters EQLRa (1), EQLRc (1), EQLCa (1), EQLCc (1), EQLRa (k), EQLRc (k), EQLCa (k), EQLCc (k) of the resistance and capacitance corresponding to the order. ) To EQLRa (n), EQLRc (n), EQLCa (n), and EQLCc (n).

  In the primary correspondence configuration, the parameters EQLRa (1), EQLRc (1), EQLCa (1), and EQLCc (1) are multiplied and added (Σ) to the reference voltages VGa (1) and VGc (1), respectively. The primary parameter EQL (1) is output. For the kth order and the nth order, the resistance parameters EQLRa (k) and EQLRc (k) are multiplied by 1 / k and 1 / n, and for the c phase, (jθ) of e, respectively. The parameters EQL (k) and EQL (n) are output by multiplying by multiplication and giving a phase rotation of θ degrees and adding (Σ).

Assuming that the voltage source of the nth harmonic is V, the impedance of the load existing between each phase and the ground is Z, and the current flowing through the ZCT is I, I = V / Z. On the other hand, the load impedance Z is a parallel connection of a capacitive load existing between each phase and the ground and a resistive load. When the frequency is ω, the capacitance is C, and the resistance is r, the capacitive load The current Ic flowing through
Ic = V / (1 / jωC) = jωCV (10)
The current Ir flowing through the resistive load is
Ir = V / r (11)
It becomes. Therefore, the current I finally flowing through the ZCT is
I = V (1 / r + jωC) (12)
It becomes. Actually, since the voltage V is the voltage of the nth-order harmonic reference voltage source and each phase (a / b / c phase) exists, all these combined vectors are obtained.

  In order to obtain the resistive leakage current that is the extraction target, it is necessary to measure the resistive leakage current component by separating the captured zero-phase current component into a resistive leakage current component and a capacitive leakage current component. . The capacitive leakage current is a phase advanced by 90 degrees of the resistive leakage current.

The capacitive load and the resistive load that are actually constructed in the leakage system are defined not by impedance but by admittance from the viewpoint of ease of system identification. The zero-phase current input from the ZCT is estimated by multiplying and combining the admittance vector and the reference n-order harmonic reference voltage source. As an equalization coefficient parameter of EQL, for each phase (PH = a, b, c),
EQL (PH) = EQLR (PH) + jEQLC (PH) (13)
It can be expressed as.

  As the EQL correction means, an automatic equalization technique applied to a modem or the like can be applied. That is, the error signal of the reference value and the estimated value is calculated by the complex conjugate of the phase normalization signal, further multiplied by the inverse of the amplitude correction, and multiplied by a certain control force. The resistive component can be multiplied by a complex conjugate of the error and the reference voltage (acting so as to eliminate the correlation between the reference voltage and the error), and the system identification can be corrected for the resistive component using the least square method.

に示すものとなる。又抵抗性成分については、基準電圧発生部からの基準電圧の次数に応じて１／ｎに低下する為、１／ｎの定数を乗算して対応することができる。又容量性成分については、次数の増加に伴う振幅の低下に対して、インピーダンスの低下により相殺されるので、そのままとする。 For capacitive components,

It will be shown in Further, the resistance component is reduced to 1 / n according to the order of the reference voltage from the reference voltage generator, and therefore can be handled by multiplying by a constant of 1 / n. Further, the capacitive component is left as it is because the decrease in the amplitude accompanying the increase in the order is offset by the decrease in the impedance.

The detailed EQL correction algorithm will be described based on the following equations (15) to (17).

  However, the estimated zero-phase current is based solely on the nth harmonic reference voltage from the reference voltage generator. On the other hand, the reference voltage phase and amplitude of the leakage system actually connected to the ZCT are different from the reference phase and amplitude, and it is necessary to correct this amplitude difference / phase difference. For this reason, each of the three-phase identification unit 33 and the single-phase identification unit 34 is provided with an amplitude / phase difference calculation circuit.

  FIG. 23 shows a part of the amplitude extraction circuit of the above-described amplitude / phase difference calculation circuit, and FIG. 24 shows the phase difference extraction circuit. In FIG. 23, the primary, k-order to n-order outputs EQL (1), EQL (k) to EQL (n) from the EQL section shown in FIG. 22 are inputted, and the same as the amplitude extraction circuit of FIG. Through such an arithmetic processing, EQL (1), EQLN (1), EQLE (n), EQLN (n), and AMPI (n) are output. This AMPI (n) is a parameter corresponding to the combined power of the nth-order harmonic for correcting the loop gain of EQL.

  FIG. 24 is an explanatory diagram of the error extraction unit, and has the same configuration as the phase difference extraction unit shown in FIG. 19, but the nth and kth harmonics from the amplitude extraction circuit shown in FIG. EQLE (n) and EQLE (k) corresponding to are input, and a phase difference parameter PHEQA is output.

  FIG. 25 shows an error calculation unit that constitutes a part of the error extraction unit 4, and includes an amplitude error extraction unit and a phase error extraction unit. The amplitude error extraction unit includes an LPFN from the amplitude extraction circuit shown in FIG. (N) and AMP (n) (inverse number of AMPI (n)) from the amplitude extraction circuit shown in FIG. 23 are input, and an amplitude error AE (n) corresponding to the difference is output. Further, the phase error extraction circuit receives PHLPA from the phase extraction circuit shown in FIG. 19 and PHEQA from the phase difference extraction unit shown in FIG. 24, and performs PDEA as a phase error and −1 by complex conjugate calculation. , EQLE (1) multiplication, and α multiplication error signal E are output.

  That is, the system identification is performed using, for example, the maximum gradient method or the least square method algorithm applied in the technical field of the modem so that the extracted leakage waveform parameter matches the parameter extracted by the system identification circuit unit. Specifically, the amplitude is obtained by extracting the difference signal AE (n) between the respective amplitudes AMP (n) and LPFN (n), and regarding the phase difference, the complex between PHEQA and PHLPA. The phase difference signal PDEA is calculated by conjugate operation, and −1 is added, multiplied by EQLE (1), multiplied by the coefficient α, and output as an error signal E.

  These amplitude / phase error signals are, for example, a three-phase, a-phase / c-phase, and moreover, a complicated combination of a resistive leakage current and a capacitive leakage current. Therefore, it is necessary to resolve the error very accurately. Since the amplitude error is not so sensitive, the amplitude error can be separated into error signals of respective phases by a method of correlating the data signal used in the modem and the error signal. The most important is the separation of the phase error signal.

  FIG. 26 is an explanatory diagram of the leakage current vector. In the power supply system in which the b phase among the a phase, the b phase, and the c phase is grounded, with reference to the a phase, (a) When the phase is rotated by +15 degrees, (b) shows a vector when the phase of the c phase is not rotated, (c) shows a vector when the phase of the c phase is rotated by -15 degrees, I0 is a leakage current, Ra and Rc indicate resistive leakage currents between the a phase and the c phase, and Ca and Cc indicate capacitive leakage currents between the a phase and the c phase. With respect to the leakage current I0 obtained by vector synthesis of the combined vector R of the resistive leakage current of the a phase and the c phase and the combined vector C of the capacitive leakage current of the a phase and the c phase, the phase shift of the c phase You can see that it changes. By feeding back the component corresponding to this change, both the phase error signal and the amplitude error signal can be converged to zero.

  FIG. 27 is an explanatory diagram of the error vector, showing the error E as a combined vector of the resistive Er and the capacitive Ec, the phase of the error E being θE, more than 90 degrees and less than 180 degrees and less than 90 degrees. The cases of exceeding 270 degrees and 360 degrees or less and exceeding 180 degrees and 270 degrees or less are shown as part 1 to part 4, respectively. If the phase of the resistive component R and the capacitive component C of the leakage current I0 is θR and θC, the resistive component ΔR of the error E corresponding to part1 to part4 can be obtained by the following arithmetic processing.

  28 and 29 are explanatory diagrams of an amplitude error decomposing unit that constitutes a part of the error decomposing unit of the error extracting unit 4 (see FIG. 11), and a phase and c in the case of three-phase b-phase grounding. FIG. 25 shows a configuration for a phase, and primary to n-order amplitude errors AE (1) to AE (n) from the amplitude error extraction circuit shown in FIG. 25 and AMPI ( n), a reference voltage corresponding to each phase from the reference voltage generator, VGa (1) to VGa (n) for the a phase, and VGc (1) to VGc (n for the c phase. ) And e (jθ) (indicating eθ raised to the power of jθ), and adding real part r by complex conjugate calculation (Σ) to output resistive amplitude errors AERa and AERc. Add part i (Σ) to obtain capacitive amplitude error AECa, AE And it outputs the c.

  The amplitude error decomposing unit in FIG. 29 inputs k-th and n-th order amplitude errors AE (k) and AE (n) and multiplies the value as a. When b = 1 and a ≧ 0, the signal AEPH is output by multiplying the determination output signal b of b = 0 by the difference between the amplitude errors AE (k) and AE (n). That is, an in-phase component having a large correlation of amplitude error is added and used for feedback correction. When AE (k) and AE (n) have different polarities, an inverse correlation relationship is shown, and addition (Σ) The amplitude error component is reduced by the processing. On the other hand, in the case of an inverse correlation state with different polarities, the determination unit feeds back the difference between AE (k) and AE (n) as AEPH to the EQL coefficient correction circuit. If the polarities are the same, it is determined that there is a correlation and AEPH = 0.

FIG. 30 is an explanatory diagram of the phase error decomposing unit. In the case of b-phase grounding, feedback is performed by decomposing the respective parameters Ra, Rc, Ca, and Cc of the a-phase and c-phase resistances and capacities. There is a need to. 27 is decomposed into ΔRb, ΔCb, ΔRa, ΔRc, ΔCa, and ΔCc by the arithmetic processing according to the mathematical expression based on the error vector of FIG. For example, for the error vector E in FIG. 27, if E = Er + Ec, the phase of _R is θ _R , the phase of _C is θ _C, and the magnitudes of the vectors Er, Ec are ΔR, ΔC, respectively.
E = ΔRejθ _R + ΔCejθ _C
This can be obtained by separating the real part and the imaginary part and performing arithmetic processing.

  FIG. 31 is an explanatory diagram of an error synthesis unit of the error extraction unit 4 (see FIG. 11), showing three phases a and c, and Σ showing an adder. AERa, AERc, AECa, AECc and ΔRa, ΔCa, ΔRc, ΔCc from the amplitude error decomposing unit (see FIG. 28) and the phase error decomposing unit (see FIG. 29) are input and synthesized error ERa, ECa, ERc, and ECc are output. This synthesized error is input to the three-phase identification unit 33 and the single-phase identification unit 34 to identify the leakage system.

  32 and 33 are explanatory diagrams of the EQL coefficient correction circuit of the three-phase identification unit 33 (see FIG. 11), and the EQL coefficient correction circuit of the single-phase identification unit 34 has the same configuration. 111 and 112 are condition determination units, 113 is an adder, 114 is a limiter (LM), 115 is a unit time delay circuit (T), 116 is a coefficient generation circuit (ROM), 117 is a multiplier, and 118 is an adder. Reference numeral 119 denotes a limiter (LM), and 120 denotes a unit time delay circuit (T), which has the same configuration corresponding to each phase.

ERa, ECa, ERc, and ECc from the error synthesis unit (see FIG. 31) are input, and the condition determination unit 111 outputs +1 for output OutE when the input input has a positive polarity greater than 0, and outputs OutE for a negative polarity. Is -1. The condition determination unit 112 outputs +1 for the control value ContAdj when the input input has the same polarity as the previous time, and −2 when the polarity is inverted. This control value ContAdj is accumulated by the adder 113, the limiter 114, and the delay circuit 115, and changes within a limit range by the limiter 114. The coefficient generation circuit 116
The output of the limiter 114 can be used as an address, and the ROM configuration can store a coefficient to be input to the multiplier. The read coefficient is multiplied by the output OutE of the condition determination unit 111, and an adder 118, a limiter 119, and a delay. An accumulation process is performed by a configuration including the circuit 120, and EQLRa, EQLCa, EQLRc, and EQLCc are output.

  In this case, when the loop gain is less than 1.0 and a stable system is configured, if there is an error correlation, the error polarity is maintained at a constant value of positive or negative. Therefore, if the error polarity changes, it is determined that the loop gain has exceeded 1.0, the control force is reduced by half, for example, and if the error polarity continues to be the same, there is an error correlation, The feedback is determined to be effective, and the control force is multiplied by √2, for example. In FIG. 32, the aforementioned control force is changed by processing a route including the condition determination unit 112 and the coefficient generation unit 116. As a result, even when the magnitude of the amplitude error changes according to the leakage pattern, the nonlinear feedback configuration of the EQL coefficient including the coefficient generation circuit 116 enables stable and high-speed convergence.

  Further, the EQL coefficient correction circuit shown in FIG. 33 receives the phase error signal AEPH, multiplies the coefficient α, integrates by the integration function of the adder, the modulo circuit MOD, the limiter LM, and the delay circuit T, and the integration value is limited. The phase correction signal e (jθ) is output by COS / SIN vector conversion.

  FIG. 34 is an explanatory diagram of EQL coefficient convergence characteristics, where the vertical axis of (A) and (B) indicates the EQL coefficient, the horizontal axis indicates the number of corrections, and (A) is capacitive in a phase and c phase. When there is a leakage and there is a resistive leakage in the c-phase, (B) shows a case where there is a single-phase leakage in both resistance and capacitance. In any case, it can be seen that convergence is achieved with about six corrections. The EQL coefficients in (A) Ra and Ca start from about 1 instead of 0, and in (B), Rc starts from about 0.5 and converges. It shows that speeding up is possible.

  FIG. 35 is an explanatory diagram of the Igr calculation / selection unit 35, in which 121 is a three-phase processing unit, 122 is a single-phase processing unit, 123 and 124 are median filters, and 125 is a selector (SEL). EQLRa, EQLRb, and EQLRc indicating the values of the resistive leakage current from the EQL coefficient correction circuit are input, and the three-phase processing unit 121 has different phases, so that the reference voltages VGb (1), VGc (1) is multiplied by EQLRb and EQLRc, respectively, and separated into a real part r and an imaginary part i, and the real part is added and squared. Also add imaginary part and square. These are added and input to the median filter 123. In the single-phase processing unit 122, RQLRa is squared to determine the power and input to the median filter 124. The selector 125 performs a selection operation according to a phase determination signal of three phases or a single phase, and outputs a resistive leakage current Igr.

  FIG. 36 is an explanatory diagram of the median filter. The outputs Md (0), Md (1), and Md (2) of the three-phase processing unit 121 or the single-phase processing unit 122 delayed by the delay circuit T of the sampling period are shown in FIG. It inputs into the comparison judgment part, and outputs the median value in Md (0), Md (1), Md (2). The output of the median filter is input to the selector 125 (see FIG. 35). As a result, the operation can be stabilized except for abnormal values due to noise.

  FIG. 37 is an explanatory diagram of the phase determination unit, showing the phase determination unit in the Igr calculation / selection unit 35 (see FIG. 11), 131 and 132 are synthesis processing units, 133 is an adder, and 134 is a phase selection unit. , 135 indicates a majority circuit, 136 indicates an adder (Σ), 137 indicates an adder, and 138 indicates a determination unit. The synthesis processing units 131 and 132 square the amplitude errors AE (1) to AE (n) and the phase errors PDEA and PDB, respectively, and synthesize them (Σ), obtain the difference a1 in the adder 123, and select the phase. In the unit 134, when a1 ≧ 0, the single-phase selection a2 = 0, and when a1 <0, the three-phase selection a2 = 1 is output. The majority circuit 135 adds the output a2 of the phase selection unit 134 through the unit time delay circuit T by the adder 136, obtains the difference a4 from the coefficient a3 in the adder 137, and determines in the determination unit 138. When a4 ≧ 0, three-phase determination is input, and when a4 <0, single-phase determination phase determination output is input to the Igr selection unit (see FIG. 11).

  FIG. 38 is an explanatory diagram of the Igr determination / timer monitoring unit. 141, 142, 146, and 147 are adders, 143 is an IGR determination unit, 144 is a timer monitoring unit, 145 is a setting unit, and 148 and 149 are continuous times. Indicates a monitoring unit. The detection signal I0DEC indicating the presence or absence of leakage current from the determination unit (see FIG. 11) of the I0 detection unit 25, the Igr determination output from the Igr selection unit of the Igr calculation / selection unit 35, and the amplitude / When SynLPFP from the amplitude extraction circuit (see FIG. 17) of the phase difference extraction unit is input and there is no leakage current, since I0DEC = 0, the output signal of the multiplier 142 is also 0, and the Igr determination process is performed. Absent. Thereby, detection malfunction is prevented. When there is a leakage current, I0DEC = 1, and the output of the multiplier 141 is input to the IGR determination unit 143, the caution threshold value of the setting unit 145 is input to the adder 146, and the warning threshold value is input to the adder 147. According to the set time limit, the continuous time monitoring unit 148 monitors the presence / absence of a continuous time exceeding the attention threshold value, and the continuous time monitoring unit 149 determines the presence / absence of the continuous time exceeding the warning threshold value. Outputs a caution signal or a warning signal when the set time limit is exceeded.

  FIG. 39 is a diagram for explaining the comparison between the present invention and the conventional example, and compares the conventional I0 method, Igr method 1, Igr method 2, and the present invention in terms of installation, accuracy, and totality. A circle mark and a triangle mark indicate superiority or inferiority. Even if the present invention belongs to the Igr system, ancillary equipment is unnecessary, uninterruptible installation is possible, reference voltage is not required, electric shock is small, installation space is small, single-phase / three-phase automatic switching is possible by system identification, capacitive leakage It can be seen that it is advantageous for all items because it can cope with balanced and unbalanced, can cope with load fluctuations, can cope with ground phase deterioration, and can be speeded up as others.

It is a principle explanatory view of the present invention. It is explanatory drawing of an alarm system. It is connection explanatory drawing of ZCT. It is explanatory drawing of a leak detection system. It is a simulation waveform explanatory drawing of the leakage current of a single phase. It is explanatory drawing of a leakage current spectrum. It is a pattern explanatory drawing of a spectrum. It is normalization amplitude distribution explanatory drawing. It is a synthetic waveform explanatory view of the nth harmonic component. It is nth harmonic amplitude distribution explanatory drawing. It is explanatory drawing of the Example of this invention. It is explanatory drawing of a carrier generation part and a demodulation part. It is explanatory drawing of a low-pass filter. It is explanatory drawing of an I0 detection part. It is explanatory drawing of a complex conjugate circuit and a frequency conversion part. It is explanatory drawing of an amplitude phase correction circuit. It is explanatory drawing of an amplitude extraction circuit. It is explanatory drawing of an autocorrelation calculation result. It is explanatory drawing of a phase difference extraction circuit. It is phase error explanatory drawing. It is explanatory drawing of a reference voltage generation part. It is explanatory drawing of an EQL part. It is explanatory drawing of an amplitude extraction circuit. It is explanatory drawing of a phase extraction part. It is explanatory drawing of an error calculation part. It is explanatory drawing of a leakage current vector. It is explanatory drawing of an error vector. It is explanatory drawing of an amplitude error decomposition | disassembly part. It is explanatory drawing of an amplitude error decomposition | disassembly part. It is explanatory drawing of a phase error decomposition | disassembly part. It is explanatory drawing of an error synthetic | combination part. It is explanatory drawing of an EQL coefficient correction circuit. It is explanatory drawing of an EQL coefficient correction circuit. It is EQL coefficient convergence characteristic explanatory drawing. It is explanatory drawing of an Igr calculation / selection part. It is explanatory drawing of a median value filter. It is explanatory drawing of a phase determination part. It is explanatory drawing of an Igr determination / timer monitoring part. It is comparison explanatory drawing of this invention and a prior art example. It is explanatory drawing of (DELTA) (DELTA) connection. It is explanatory drawing of a YY connection. It is explanatory drawing of YY connection (neutral point extraction). It is explanatory drawing of a Ydelta connection. It is explanatory drawing of (DELTA) Y connection. It is explanatory drawing of VV connection.

Explanation of symbols

DESCRIPTION OF SYMBOLS 1 ZCT part 2 Earth leakage waveform parameter extraction part 3 System identification circuit part 4 Error extraction part 5 Various setting / display control part 21 Filter part 22 Data acquisition part 23 Reference value extraction part 24 Frequency information extraction part 25 I0 detection part 31 Three-phase voltage Generator 32 Single-phase voltage generator 33 Three-phase identification unit 34 Single-phase identification unit 35 Igr calculation / selection unit 36 Igr judgment / timer monitoring unit

Claims (8)

In a leakage current detection method for detecting a resistive leakage current by detecting a current flowing through a ground line in a power supply system by ZCT,
A leakage waveform parameter including the amplitude and phase parameters of the fundamental wave of the ZCT detection signal and its n-th harmonic component based on the frequency information, extracting frequency information of the power supply system from the ZCT detection signal And the error between the leakage waveform parameter and the output parameter including the amplitude and phase parameters of the fundamental wave and its n-th harmonic component defined as the output of the identified leakage system is extracted, and the error is minimized. performing correction processing of the output parameters so as to perform identification of leakage system, the identification convergence of該漏electric system, viewed including the step of detecting resistive leakage current,
In this process, the phase angle θ of the components of the k-th order and n-th order harmonics excluding the fundamental wave is obtained by using a tan ⁻¹ function, multiplied by k / 2 on the n-order side, and n on the k-order side. Multiply / 2 to find the difference value (the denominator 2 with n and k as numerators can be any other integer), and perform a predetermined modulo operation on the difference value A leakage current detection method comprising: outputting the output parameter not related to a reference phase and the phase parameter of the leakage current waveform parameter by outputting the signal as a sin and cos function signal . Including a step of decomposing each of an amplitude error and a phase error of a difference between the leakage waveform parameter and the output parameter into a resistive component and a capacitive component, and correcting a coefficient of leakage system identification. The leakage current detection method according to claim 1. Amplitude error that is the difference between the leakage waveform parameter and the output parameter for the k-order harmonic component, and an amplitude error that is the difference between the leakage waveform parameter and the output parameter for the n-order harmonic component are different. In the case of performing the processing related to the coefficient correction for the leaked system identification based on the difference between the two amplitude errors, and performing the processing related to the coefficient correction for the system identification as correlated if the two amplitude errors are of the same polarity the leak current detecting method according to claim 1 or 2, wherein the containing.   The leakage current detection method according to claim 1, further comprising a step of performing a plurality of types of leakage system identification and detecting a resistive leakage current based on a leakage system identification result that minimizes each error. In a leakage current detection device for detecting and processing a resistive leakage current by inputting only a ZCT detection signal for detecting a current flowing in a ground line in a power supply system,
The ZCT detection signal is input to extract frequency information of the detection signal, and a leakage waveform parameter including amplitude and phase parameters for the nth harmonic component of the detection signal according to the frequency information is extracted. A leakage waveform parameter extracting means;
An error extraction means for extracting an error between the leakage waveform parameter and the output parameter of the leakage system identified ;
A system identification means for estimating and detecting a resistive leakage current by performing a leakage system identification process including a leakage path by correcting the output parameter so that the error by the error extraction means approaches zero ,
Each of the leakage waveform parameter extraction means and the system identification means obtains the phase angle θ of the k-th order and n-th order harmonic components excluding the fundamental wave using a tan ⁻¹ function, and k / 2 is multiplied by n / 2 on the k-th order side to obtain the difference value (the denominator 2 with n and k as the numerator can be any other integer), and A configuration in which the phase parameter of the leakage current waveform parameter not related to a reference phase is output or the output parameter is output by performing a predetermined modulo operation on the difference value and outputting it as a sin, cos function signal A leakage current detection device comprising: The error extraction means decomposes each of an amplitude error and a phase error of a difference between the leakage waveform parameter and the output parameter into a resistive component and a capacitive component, and inputs them as a coefficient correction of the system identification means 6. The leakage current detection device according to claim 5, wherein The error extraction means is an amplitude error that is a difference between the leakage waveform parameter for the k-order harmonic component and the output parameter, and a difference between the leakage waveform parameter for the n-order harmonic component and the output parameter. When the polarity is different from the amplitude error, a signal based on the difference between both amplitude errors is input to the system identification means, and when the both amplitude errors are the same polarity, a signal indicating a correlation is input to the system identification means. The leakage current detection apparatus according to claim 5 . The system identification means includes a plurality of identification units for performing leakage system identification corresponding to a plurality of types of power supply systems, and an identification unit that minimizes an error between an output parameter of the plurality of identification units and the leakage waveform parameter 6. The leakage current detection apparatus according to claim 5, further comprising means for detecting a resistive leakage current based on a leakage system identification result.

Images