JP4537802B2 - Power converter - Google Patents

Description

The present invention relates to a power conversion device.

In a conventional AC train system, single-phase AC power applied to an overhead wire is converted into DC power by a converter 5, and power is supplied to an inverter and a main motor that is a load thereof. As a control method of the converter 5, a PWM control method that performs pulse width modulation control by comparing a triangular wave carrier having a constant frequency and a modulated wave is widely applied. In particular, in an AC train system, there is a track circuit that controls the signal system due to current harmonics flowing out from the converter 5 to the overhead line, and a component that is an integral multiple (synchronization) of the power supply frequency is acceptable, but a non-integer A constant carrier frequency has been selected that is a frequency (integer multiple of the power supply frequency) that is synchronized with the power supply frequency (a constraint that the allowable value of the double (asynchronous) component is small).
Japanese Patent Application Laid-Open No. 08-116674 Japanese Patent Laid-Open No. 09-140165

However, in the conventional AC train system, the converter 5 needs to select a certain carrier frequency that is synchronized with the power supply frequency, so that the harmonic component of the specific frequency is superimposed on the secondary current, Noise was generated from the transformer. In particular, since it has a constant frequency, it can be heard as a pure tone called keen, which is very harsh and unpleasant.

  Patent Document 1 describes a converter 5 control device in which the carrier frequency is set to two values and has an effect of reducing noise (the purpose is to reduce loss). However, there is a strong demand for noise reduction in recent years, and a converter control device that can further reduce noise is desired.

  Patent Document 2 describes a technique that does not cause problems such as demagnetization and beat current while reducing the noise of the converter 5. However, there is no specific description about the setting of the carrier frequency that reduces noise and is suitable for an AC train system.

Accordingly, an object of the present invention is to provide a power conversion device that can prevent direct current magnetization and increase in loss and can improve noise reduction performance.

  The above-described problems include a converter that converts alternating current into direct current, a carrier frequency calculation unit that calculates a carrier frequency, and a PWM control unit that performs pulse width modulation control on the converter by comparing a triangular wave carrier calculated from the carrier frequency and a modulation wave The carrier frequency calculation unit can achieve this by calculating a continuously changing carrier frequency based on the absolute value of the power supply voltage.

  According to the present invention, it is possible to provide a power conversion device that can prevent a DC bias and an increase in loss and improve noise reduction performance.

(First embodiment)
A power converter according to a first embodiment of the present invention will be described in detail with reference to the drawings. FIG. 1 is a block diagram of a converter control device according to a first embodiment of the present invention.

In the train system equipped with the power conversion device according to the first embodiment of the present invention, the pantograph 1 is connected to the main transformer 11. The main transformer 11 is connected to the AC side of the converter 5, and further, a smoothing filter capacitor 7 and a VVVF inverter 8 that drives the main motor 9 are connected to the DC side of the converter 5. Here, the load of the converter 5 is an inverter 8 and a main motor 9. The converter control device 10 that controls the converter 5 calculates the AC output voltage command Vc * and controls the converter 5 so that the voltage Vdc of the filter capacitor 7 detected by the voltage detector 6 becomes a predetermined value. is there.

The input to the converter control device 10 is an output current Ic that is an AC side current of the converter 5 detected by the current detector 4, an output voltage Vc that is an AC side voltage, and a voltage Vdc of the filter capacitor 7.

ただし、Ｋｐｄｃ、Ｋｉｄｃは直流電圧制御の比例ゲイン、積分ゲインである。Ｓはラプラス演算子である。 A voltage control unit 13 provided in the converter control device 10 is inputted with a difference voltage between the voltage Vdc of the filter capacitor 7 which is an output of the subtractor 12 and a DC voltage command Vdc * which is a target value thereof, and its deviation. For example, the amplitude command value IPA * of the effective current of the converter 5 is calculated as shown in Equation 1 so that.

However, Kpdc and Kidc are a proportional gain and an integral gain of DC voltage control. S is a Laplace operator.

  The phase estimation unit 21 calculates the phase θs of the power supply voltage based on the overhead line voltage V1 detected by the voltage detector 23 by a well-known single-phase PLL technique. In the converter control device of the present embodiment, the zero point of θs is defined as the zero cross point at which the power supply voltage changes from negative to positive.

電流制御部１７では、コンバータ５の出力電流指令Ｉｃ*に、電流検出器４によって検出された出力電流Ｉｃが一致するように、数３のように出力電圧指令Ｖｃ*を算出する。

ただし、Ｋｐは比例ゲインである。 The current command calculation unit 15 receives the effective current amplitude command IPA * and the power supply voltage phase θs, and calculates the converter output current command Ic * as shown in Equation 2. However, here, it is assumed that the power factor at the punter point = 1.

The current control unit 17 calculates the output voltage command Vc * as shown in Equation 3 so that the output current command Ic * of the converter 5 matches the output current Ic detected by the current detector 4.

However, Kp is a proportional gain.

  The carrier frequency calculation unit 19 calculates a carrier frequency fc * based on the phase θs of the power supply voltage. The integrator 27 calculates the carrier phase θcar based on the carrier frequency fc * calculated by the carrier frequency calculation unit 19.

In the PWM control 18, a triangular wave carrier is generated based on the carrier phase θcar, and a gate to the converter is generated by triangular wave comparison PWM control so that an output voltage that matches the output voltage command value Vc of the converter 5 is obtained. Since this triangular wave comparison PWM control is a well-known technique, a detailed description thereof will be omitted.

The converter control device configured as described above controls the output current command Ic * of the converter 5 so that the DC voltage Vdc becomes the target value Vdc *, and the output current Ic matches the output current command Ic *. Thus, the output voltage command Vc * of the converter 5 is controlled.

  Next, the carrier frequency calculation unit 19 will be described in detail with reference to the drawings. FIG. 2 is a configuration diagram of the carrier frequency calculation unit 19.

ここに、ｆｌｏｏｒ（）は、小数以下を切り捨て整数化する関数とする。また、電源電圧θｓは、0[ｄｅｇ]以上360[ｄｅｇ]未満の領域に存在するものとする。 The carrier frequency calculation unit 19 includes a carrier count calculation unit 25 and a carrier frequency pattern table 24. The carrier count calculation unit 25 divides the phase θs of the power supply voltage calculated by the phase estimation unit 21 into predetermined regions, and generates and outputs a carrier count N for identifying the region. For example, if one power supply cycle is divided into 30 regions so that the power supply phase is equally divided, the carrier count N can be calculated as shown in Equation 4.

Here, floor () is a function that rounds down decimals to an integer. Further, it is assumed that the power supply voltage θs exists in an area of 0 [deg] or more and less than 360 [deg].

The carrier frequency pattern table 24 stores a carrier frequency corresponding to the carrier count N. The carrier pattern table 24 outputs the carrier frequency data corresponding to the carrier count N generated by the carrier count calculation unit 25 as the carrier frequency fc * at that time.

The converter control device configured as described above calculates in advance a carrier frequency fc * for the phase θs of the power supply voltage and a value corresponding thereto (referred to as carrier count in this embodiment), and stores it in a table. It takes the form of referencing each time during actual driving.

The power conversion device according to the first embodiment of the present invention is characterized in that the carrier frequency continuously changes according to the magnitude of the power supply voltage absolute value as shown in FIG. According to the magnitude of the absolute value of the power supply voltage, the carrier frequency calculation unit 19 according to the present embodiment increases the carrier frequency when the power supply voltage absolute value is high and sets the carrier frequency when the absolute value of the power supply voltage is low. And a continuously changing carrier frequency is set. Noise is caused by current harmonics, but large current harmonics occur in regions where the absolute value of the power supply voltage is large. Conversely, in regions where the absolute value of the power supply voltage is small, the current harmonics are relatively small. Value. Therefore, the effect of reducing the magnitude of the current harmonics of the converter output current can be expected by increasing the carrier frequency in the vicinity of the region where the absolute value of the power supply voltage is large, that is, increasing the switching frequency. Unlike Patent Document 1, the dispersion effect of current harmonics can be further enhanced by setting a carrier frequency that changes continuously so that a plurality of carrier frequencies are mixed. Due to these two synergistic effects, a significant noise reduction effect can be expected.

ただし、ｎは正の整数、Ｔは電源電圧の周期[ｓｅｃ]、ｔ０は任意の時刻[ｓｅｃ]である。ｔ０は任意であるので、例えば、電源電圧がゼロクロスする時刻[ｓｅｃ]として考えてもよい。 The carrier frequency calculation unit 19 of the power conversion device configured as described above has the same carrier frequency pattern in the positive interval (0 deg <= θs <180 deg) and the negative interval (180 deg <= θs <360 deg). Set. In addition, the carrier frequency calculation unit 19 integrates the carrier frequency fc * into one cycle of the power supply voltage (strictly, it is an integration obtained by converting fc * × 2π [rad / s]). The carrier frequency fc * [Hz] is set so as to satisfy the condition (equation 5) that is equal to an integer multiple of [deg].

However, n is a positive integer, T is a period [sec] of the power supply voltage, and t0 is an arbitrary time [sec]. Since t0 is arbitrary, for example, it may be considered as time [sec] when the power supply voltage crosses zero.

  The phase of the carrier frequency calculated based on Equation 5 returns to the initial value in any one cycle period. For example, the carrier phase α [deg] at the zero crossing of the power supply voltage means that the carrier phase is α [deg] even when the power supply voltage zero crosses again. That is, although the carrier phase changes irregularly within one period of the power supply voltage, the power supply voltage is synchronized when one period is observed. Therefore, there is an effect that the asynchronous component of the current harmonic component included in the output current of the converter 5 is not increased.

In the AC train system, an allowable value for the asynchronous component of the power supply voltage is set small in the current harmonics flowing out from the converter 5 to the overhead line for signal system control. If a carrier frequency pattern that is not synchronized with the power supply voltage is used, the asynchronous component of the current harmonic component increases, which may adversely affect the signal system. Therefore, by setting the carrier frequency pattern to be synchronized with the power supply voltage, an increase in the asynchronous component of the current harmonic is suppressed, and there is an effect that the signal control system is not affected. (Note that Patent Document 1 clearly states that the carrier frequency is switched in synchronization with the power supply voltage, but does not mention how the carrier phase should be obtained by integrating the carrier frequency.) The converter control device according to the embodiment has an effect that the increase in the asynchronous component of the current harmonic can be suppressed by setting the carrier frequency so that the carrier phase is continuous every cycle, that is, in synchronization. )
Further, in the power conversion device of the present embodiment, the carrier frequency uses the same carrier frequency pattern for the positive half cycle and the negative half cycle of the power supply voltage. It is possible to suppress. There are minute individual differences in circuit characteristics (including semiconductor characteristics) of the U-phase and V-phase of the converter 5. If different carrier frequencies are used for the positive half cycle and the negative half cycle of the power supply voltage, a DC component may be generated on the AC side due to the asymmetry due to the individual difference. This DC voltage may cause the main transformer to demagnetize, cause noise and vibration, or cause protection to stop due to overcurrent. Therefore, by setting the carrier frequency pattern to be the same between the positive half cycle and the negative half cycle of the power supply voltage, the effect of suppressing the asymmetry of the output voltage and suppressing the bias of the main transformer can be expected.

  It was confirmed by simulation that the harmonics of the output current of the converter 5 are dispersed. FIG. 4 shows the analysis result in the case of the conventional constant carrier frequency. FIG. 5A shows the case of a continuously changing carrier frequency, which is a converter of a two-frequency switching system between a low carrier frequency and a high carrier frequency, which is the known technique of FIG. 5B. FIG. 5A shows that the harmonic component of the output current is dispersed best.

  With this configuration, the carrier frequency changes according to the phase θs of the power supply voltage. For this reason, the frequency spectrum of the ripple of the output current of the converter 5 is dispersed, and an unpleasant pure tone (sound having a specific frequency component) generated from the main transformer can be suppressed, and noise can be reduced.

The power conversion device configured as described above can prevent DC bias and loss increase, and can improve noise reduction performance.

In the power conversion device according to the present embodiment, the carrier frequency fc * is described as output based on the carrier frequency pattern table. However, the carrier frequency fc * is calculated using the carrier frequency pattern table as in this embodiment. Even if it is referred to or directly calculated, the same operation and effect can be obtained.

(Second Embodiment)
A power converter according to a second embodiment of the present invention will be described in detail with reference to the drawings. FIG. 6 is a calculation pattern diagram of the carrier frequency by the carrier frequency calculation unit of the power conversion device according to the second embodiment of the present invention. The same structural elements as those shown in FIGS. 1 to 5 are designated by the same reference numerals and the description thereof is omitted.

  The carrier frequency calculation unit 19 of the power conversion device according to the second embodiment of the present invention sets a low carrier frequency when the absolute value of the power supply voltage is large, that is, when the power supply phase is around 90 deg or 270 deg. In addition, a high carrier frequency is set in a region where the absolute value of the power supply voltage is small, that is, in the vicinity of 0 deg or 180 deg.

  The carrier frequency calculation unit 19 of the power conversion device configured as described above has the same carrier frequency pattern in the positive interval (0 deg <= θs <180 deg) and the negative interval (180 deg <= θs <360 deg). Set. In addition, the carrier frequency calculation unit 19 integrates the carrier frequency fc * into one cycle of the power supply voltage (strictly, it is the integration of the one converted into fc * × 2π [rad / s]). The carrier frequency fc * [Hz] is set so as to satisfy the condition of being equal to an integral multiple of [deg] (see (Equation 5)).

  In the power conversion device configured as described above, the carrier frequency is set low when the absolute value of the power supply voltage is high, and the carrier frequency is set high when the absolute value of the power supply voltage is low.

  When the high carrier frequency is set in the region where the absolute value of the power supply voltage is high and the low carrier frequency is set in the region where the absolute value of the power supply voltage is low, as in the power conversion device of the first embodiment, the current is large ( Usually, since the power factor is 1 operation, the switching frequency in the region where the absolute value of the power supply voltage is large (the absolute value of the current is also large) increases, so the loss of the converter increases. As a result, the cooling capacity is inevitably increased, which may increase the weight and physique of the converter. Therefore, the power conversion device of the second embodiment sets the carrier frequency low when the absolute value of the power supply voltage is high, and sets the carrier frequency high when the absolute value of the power supply voltage is low. Suppress the increase.

The power conversion device according to the present embodiment is more efficient than the system of the constant carrier frequency employed in the current system, even if the noise reduction effect is not obtained as much as the power conversion device according to the first embodiment. There is an advantage as a system because it does not cause physique and weight and the effect of noise reduction is obtained. (For current systems where the carrier frequency is constant, it can be expected that the switching frequency will be lowered and noise and loss will be reduced only in the region where the absolute value of the power supply voltage is low, as in Patent Document 1. If this happens, the average frequency will be lower than that of the existing system, and the resulting current harmonic level will be higher than that of the existing system. It is practically effective to set a low area)

  FIG. 7 shows an analysis result of the power conversion device according to the second embodiment when the carrier frequency is set to 1650 Hz near the zero cross of the power supply voltage and the carrier frequency is set to 1250 Hz near the peak of the power supply voltage. By comparison with FIG. 4 (conventional converter control device), it can be seen that the harmonic components are dispersed and the effect of noise reduction can be expected.

  With this configuration, since the carrier frequency changes according to the phase θs of the power supply voltage, the frequency spectrum of the ripple of the output current of the converter 5 is dispersed, and the annoying pure tone (specificity) generated from the main transformer (Sound having frequency components) can be suppressed, and noise can be reduced.

  Moreover, since the power conversion device of the present embodiment also uses the same carrier frequency pattern in the positive half cycle and the negative half cycle of the power supply voltage, the asymmetry of the output voltage is suppressed, and the main transformer The effect of suppressing the magnetic demagnetization can be expected.

  The power conversion device configured as described above can prevent DC bias and loss increase, and can improve noise reduction performance.

(Third embodiment)
A power converter according to a third embodiment of the present invention will be described in detail with reference to the drawings. FIG. 8 is a calculation pattern diagram of the carrier frequency by the carrier frequency calculation unit of the power conversion device according to the third embodiment of the present invention.

  The carrier frequency calculation unit 19 of the power conversion device according to the second embodiment of the present invention randomly sets carrier frequencies so that adjacent carrier frequencies have no regularity.

  The carrier frequency calculation unit 19 of the power conversion device configured as described above has the same carrier frequency pattern in the positive interval (0 deg <= θs <180 deg) and the negative interval (180 deg <= θs <360 deg). Set. In addition, the carrier frequency calculation unit 19 integrates the carrier frequency fc * in one period of the power supply voltage (strictly, it is the integration of the one converted into fc * × 2π [rad / s]). The carrier frequency fc * [Hz] is set so as to satisfy the condition of being equal to an integral multiple of [deg] (see (Equation 5)).

  With this configuration, the carrier frequency changes according to the phase θs of the power supply voltage. For this reason, the frequency spectrum of the ripple of the output current of the converter 5 is dispersed, and an unpleasant pure tone (sound having a specific frequency component) generated from the main transformer can be suppressed, and noise can be reduced.

  The power conversion device configured as described above can uniformly disperse current harmonics by changing adjacent carrier frequencies randomly without regularity. If the carrier frequency is set so as to have a specific frequency as in the converter control device of the first embodiment or the second embodiment, there is a concern that the frequency component may be newly heard as noise.

  Therefore, by uniformly changing the carrier frequency so as not to have a specific frequency as in the converter control device of the present embodiment, a uniformly distributed current harmonic distribution can be obtained. As a result, it is possible to make the characteristic of not causing an irritating specific frequency, which is an aim of dispersing carriers, more remarkable.

  Moreover, since the power conversion device of the present embodiment also uses the same carrier frequency pattern in the positive half cycle and the negative half cycle of the power supply voltage, the asymmetry of the output voltage is suppressed, and the main transformer The effect of suppressing the magnetic demagnetization can be expected.

  The power conversion device configured as described above can prevent DC bias and loss increase, and can improve noise reduction performance.

(Fourth embodiment)
A power converter according to a fourth embodiment of the present invention will be described in detail with reference to the drawings. FIG. 9 is a block diagram of the carrier frequency calculation unit of the power conversion device according to the fourth embodiment of the present invention. A part of the configuration of the carrier frequency calculation unit 39 is different from the power conversion devices of the first to third embodiments.

In the power conversion device according to the fourth embodiment, the cycle count calculation unit 26 generates and outputs a cycle counter NT indicating the current cycle based on the power supply voltage phase θs. FIG. 9 is a relationship diagram showing an example of the power supply voltage V1 and the period counter NT. In this example, the period counter 26 is set to increase to 0, 1, 2 every power supply period and to return to 0 again.

In the carrier frequency calculation unit 39, three carrier frequency pattern tables 24 corresponding to the period counter NT are prepared. The switch 31 selects and outputs one corresponding from the three carrier frequency pattern tables 24 based on the period counter NT. The power conversion device configured as described above can set a different carrier frequency pattern for each cycle of the power supply voltage. Rather than using a specific carrier frequency pattern, by changing the pattern for each period, it can be expected that the current harmonic spectrum is further dispersed and the effect of noise reduction becomes remarkable. Further, as in the power conversion device of the present embodiment, by selecting a new pattern for each cycle, the output voltage asymmetry, that is, a phenomenon such as DC bias is suppressed, and control anxiety is suppressed. It can be expected to suppress qualitative properties as much as possible.

The power conversion device configured as described above can prevent DC bias and loss increase, and can improve noise reduction performance.

(Fifth embodiment)
A power converter according to a fifth embodiment of the present invention will be described in detail with reference to the drawings. FIG. 11 is a block diagram of a power conversion device according to a fifth embodiment of the present invention.

The power conversion device according to the fifth embodiment of the present invention will be described with respect to a configuration in which a plurality of converters are provided in one train of an AC train. Note that the same components as those shown in FIGS. 1 to 10 are denoted by the same reference numerals and description thereof is omitted.

  In the power conversion device according to the fifth embodiment of the present invention, first carrier frequency calculation unit 49A generates carrier counter N corresponding to power supply voltage phase θs and outputs the carrier counter N to other carrier frequency calculation unit 49. . The other carrier frequency calculation unit 49 refers to the carrier frequency pattern table 24 using this carrier counter N.

  The output of each carrier frequency calculation unit 49 is the carrier frequency fc *, and the result obtained by integrating this is the phase θcar of the triangular wave carrier. In the AC train system, when a plurality of converters exist in one train as in the converter control device of the present embodiment, the phase difference operation that cancels out the current harmonics flowing in the overhead line by shifting the carrier phases of each other is performed. Since it is essential, the phase difference offset 28 of each unit is added after the triangular wave carrier phase θcar.

  The above configuration is characterized in that the carrier counter N of each unit is shared. Thereby, the carrier frequency set in each carrier frequency calculation part 49 becomes the same setting at the same time in all the units. That is, even when the carrier frequency is variable, it is guaranteed that all units set the same carrier frequency at the same time, so that it is possible to maintain the effect of suppressing the current harmonics flowing in the overhead wire. Become. An increase in current harmonics flowing through the overhead wire may affect the signal circuit and may cause a serious accident such as inability to operate. According to the present invention, it is possible to maintain the reliability of the system.

  In recent years, control has been digitally controlled, and individual differences between controllers are small. Therefore, as in this embodiment, if one individual carrier counter N is not clearly shared but is configured by digital control, it is equivalent to sharing the carrier counter N. A working effect can be obtained.

(Sixth embodiment)
A power converter according to a sixth embodiment of the present invention will be described in detail with reference to the drawings. FIG. 12 is a block diagram of a power conversion device according to the fifth embodiment of the present invention.

  In the power conversion device according to the sixth embodiment of the present invention, the switching mode setting unit 22 is input with the speed of the vehicle, the output power of the converter or inverter, or the main motor as its load, and the like. In response to this, a switching signal for making the carrier frequency variable or fixed is output.

  For example, as a first setting example, when the absolute value of the speed is lower than a predetermined value, the carrier frequency is made variable, and when the absolute value of the speed is higher than the predetermined value, the carrier frequency is fixed. For example, as the second setting, when the absolute value of the RMS of the output current is lower than a predetermined value, the carrier frequency is made variable, and when the absolute value of the RMS of the output current is higher than the predetermined value, the carrier frequency Can be set according to the driving situation, such as fixing.

  Two carrier frequency pattern tables 24 are prepared. One is to change the carrier frequency, and for example, it can be the one shown in the first embodiment. The other is to fix the carrier frequency. That is, it is a pattern in which a constant carrier frequency is written regardless of the carrier count N.

  The switch 32 outputs a value referenced from the corresponding table as a carrier frequency set value fc * according to the switch signal.

  The power conversion device configured as described above can obtain a noise reduction effect by changing the carrier frequency only under predetermined operating conditions. As a means for reducing the noise by making the carrier frequency variable, there is a method of setting the carrier frequency high where the absolute value of the power supply voltage is large, as in the converter control device of the first embodiment. However, since the converter 5 normally operates at a power factor of 1, a large current value as a whole may be cut off due to the above setting, that is, the loss may increase. If low noise is given the highest priority, it is possible to improve the cooling capacity of the converter 5 to cope with it, but this is not preferable because it increases the size and weight of the equipment.

  On the other hand, in the low speed region or directly in the low output region, since the output current of the converter 5 is small, it is an operating condition that has sufficient capacity for the cooling capacity of the converter 5. Therefore, only in this case, by making the carrier frequency variable and reducing noise, the effect of reducing noise can be limited to some operating conditions within a range that does not increase the size and weight of the equipment. Can also be expected.

  Here, if a stop to the station and departure are assumed, noise for passengers waiting at the station is a problem. Further, in such low speed traveling, other noises associated with traveling are small, and it is an operating condition in which electromagnetic noise from the main transformer is conspicuous. Therefore, as described above, even if the noise is reduced only in the low-speed or low-power region, a very beneficial effect can be obtained as an AC train system.

It is a block diagram of the power converter device of a 1st embodiment based on the present invention. It is a block diagram of the carrier frequency calculating part 19 of the power converter device of 1st Embodiment based on this invention. It is a calculation pattern figure of the carrier frequency by the carrier frequency calculating part of the power converter device of 1st Embodiment based on this invention. It is a simulation result of the conventional power converter. (A) It is a simulation result of the power converter device of 1st Embodiment based on this invention. (B) It is the simulation result of the power converter device of patent document 1. FIG. It is a calculation pattern figure of the carrier frequency by the carrier frequency calculating part of the power converter device of 2nd Embodiment based on this invention. It is a calculation pattern figure of the carrier frequency by the carrier frequency calculating part of the power converter device of 3rd Embodiment based on this invention. It is a simulation result of the power converter device of 3rd Embodiment based on this invention. It is a block diagram of the carrier frequency calculating part of the power converter device of 4th Embodiment based on this invention. It is the relationship figure which showed an example of the power supply voltage V1 and the period counter NT. It is a block diagram of the power converter device of 5th Embodiment based on this invention. It is a block diagram of the power converter device of 5th Embodiment based on this invention.

Explanation of symbols

DESCRIPTION OF SYMBOLS 1 Pantograph 2 Wheel 3 Converter input voltage detector 4 Converter input current detector 5 Converter 6 Voltage detector 7 of filter capacitor 7 Filter capacitor 8 Inverter 9 Electric motor 10 Converter control device 11 Main transformer 12 Subtractor 13 Voltage control unit 14 Addition 15 Current command calculation unit 16 Subtractor 17 Current control unit 18 PWM control unit 19 Carrier frequency calculation unit 20 Power supply voltage FF calculation unit 21 Phase estimation unit 22 Switching mode setting unit 23 Wire voltage detector 24 Carrier frequency pattern 25 Carrier count calculation Unit 26 period count calculation unit 27 integrator 28 adder 29 divider 31 switch 32 operation mode changeover switch 39 carrier frequency calculation unit 49 carrier frequency calculation unit 59 carrier frequency calculation unit

Claims (2)

A converter that converts alternating current to direct current,
A carrier frequency calculator for calculating the carrier frequency;
A PWM controller that performs pulse width modulation control on the converter by comparing a triangular wave carrier calculated from a carrier frequency and a modulated wave;
The carrier frequency calculating unit calculates a continuously changing carrier frequency based on an absolute value of a voltage on an AC input side of the converter. In the converter control device according to claim 1,
When there are a plurality of the carrier frequency calculation units, all the carrier frequency calculation units use the same carrier frequency pattern.

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