JP4052653B2 - Radio correction clock - Google Patents
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Description
本発明は、金属外装部を有する電波修正時計がその時計ケースの内部に有し、受信コイルによって標準電波を受信する高性能なアンテナの構造とそれを用いた最適な受信手段を有する電波修正時計に関する。 The present invention provides a radio-controlled timepiece having a high-performance antenna structure having a radio-controlled timepiece having a metal exterior part and receiving a standard radio wave by a receiving coil, and an optimal receiving means using the same. About.
近年、タイムコードを有する長波の標準電波を受信して、使用中の時計の時刻を当該標準時の時刻に自動的に合わせる電波修正時計が商品化されているが、腕時計においては、小型と、薄型と、特に、高級感が重要な問題であって、それを実現するためには、少なくとも、磁心にマグネットワイヤーを巻回すことによって形成された受信コイルを有し、長波を受信するバーアンテナを、高級感を出すことができる金属外装部を有する時計ケースに内臓する必要があるが、そうすると、主に長波の金属外装部で生じる渦流損失によって該アンテナの受信性能が低下してしまい、長波を受信できないという問題が発生する。 In recent years, radio-controlled timepieces that receive long-wave standard radio waves with time codes and automatically adjust the time of the clock in use to the standard time have been commercialized. However, wristwatches are small and thin. In particular, luxury is an important issue, and in order to realize it, at least a bar antenna having a receiving coil formed by winding a magnet wire around a magnetic core and receiving a long wave, It is necessary to incorporate a watch case with a metal exterior that can give a sense of quality, but if this is done, the reception performance of the antenna will be degraded due to eddy current loss that occurs mainly in the metal exterior of the long wave, and long waves will be received. The problem of not being able to occur.
その問題を解決するために、図９に示す従来のアンテナ９０は磁心９１からなり、該磁心９１はマグネットワイヤーを巻回すことによって受信コイル９２を形成した受信コイル形成部９１ａとギャップ９３を有する非受信コイル形成部９１ｂからなっている（受信コイル９２の両端に直列に接続されたＬＣ共振回路を形成する共振用のコンデンサは図では省略してある）。 In order to solve the problem, the conventional antenna 90 shown in FIG. 9 includes a magnetic core 91, and the magnetic core 91 has a receiving coil forming portion 91 a in which a receiving coil 92 is formed by winding a magnet wire and a non-magnetic gap 91. A reception coil forming portion 91b is formed (resonance capacitors that form LC resonance circuits connected in series to both ends of the reception coil 92 are omitted in the figure).
まず、アンテナ９０に対して、以下に示す数１からす数５の関係式が成り立つ。数１は受信コイル９２のインダクタンスＬとコンデンサの容量ＣからなるＬＣ共振回路のＱ値の、長波の角周波数ωと、インダクタンスＬと、長波の渦流損失抵抗を含む受信コイル９２の抵抗Ｒの関係式であって、数２はインダクタンスＬの受信コイル９２の巻数ｎと磁束９７の閉磁路９６の磁気抵抗Ｒｍの関係式であって、数３は該磁気抵抗Ｒｍの受信コイル形成部９１ａの磁気抵抗Ｒｍａとギャップ９３を含む非受信コイル形成部９１ｂの磁気抵抗Ｒｍｂの和で表されることを示しており、数４は磁気抵抗Ｒｍａの交流透磁率μａと、磁路長ｌｍａと、磁路断面積Ｓｍａの関係式であって、数５は磁気抵抗Ｒｍｂの交流透磁率μｂと、磁路長ｌｍｂと、磁路断面積Ｓｍｂと、ギャップ長ｌｍｇと、ギャップ断面積Ｓｍｇと、実効交流透磁率μｂｅの関係式である。 First, for the antenna 90, the following relational expression of Formula 1 to Formula 5 is established. Equation 1 shows the relationship between the long-wave angular frequency ω, the inductance L, and the resistance R of the reception coil 92 including the long-wave eddy current loss resistance, of the Q value of the LC resonance circuit composed of the inductance L of the reception coil 92 and the capacitance C of the capacitor. a formula, the number 2 is a relational expression of the magnetoresistance R m of closed magnetic circuit 96 turns n and the magnetic flux 97 of the receiving coil 92 of the inductance L, the number 3 is the receive coil forming portion 91a of the magnetoresistive R m and number 4 is an alternating magnetic permeability mu a magnetoresistive R ma indicates that represented by the sum of the reluctance R mb the non-receiving coil forming part 91b that includes a magnetoresistive R ma and the gap 93, the magnetic path The relational expression between the length l ma and the magnetic path cross-sectional area S ma , where Equation 5 is the AC permeability μ b of the magnetic resistance R mb , the magnetic path length l mb , the magnetic path cross-sectional area S mb, and the gap length and l mg, and the gap cross-sectional area S mg, effective NagareToru is a relational expression of the permeability μ be.
上記の数１から数５の関係式を使って、４０ｋＨｚの長波９４がアンテナ９０に到来した時の前記共振用のコンデンサの両極間に生じる検出電圧Ｖを説明する。 The detected voltage V generated between the two poles of the resonance capacitor when the 40 kHz long wave 94 arrives at the antenna 90 will be described using the above relational expressions 1 to 5.
前記長波９４は磁心９１の通路９５ａと９５ｂを通過するが、通路９５ｂにはギャップ９３があってそれによって通路９５ｂの実効交流透磁率μｂｅは通路９５ａの交流透磁率μａに比べ小さくなり、該長波９４の大部分は通路９５ａを通過し、受信コイル９２には電磁誘導によって受信コイル誘起起電力ｖが発生する。 The long wave 94 passes through the passages 95a and 95b of the magnetic core 91, but the passage 95b has a gap 93 so that the effective AC permeability μ be of the passage 95b is smaller than the AC permeability μ a of the passage 95a. Most of the long wave 94 passes through the passage 95a, and a reception coil induced electromotive force v is generated in the reception coil 92 by electromagnetic induction.
その後、その受信コイル誘起起電力ｖによってＬＣ共振回路に生じる電流が発生する磁束９７は閉磁路９６を回るが、その時、インダクタンスＬが数３から数５の関係式から求まる磁気抵抗Ｒｍを使って数２から求まり、そのインダクタンスＬにより、数１に示すＱ値が求まるが、磁路９６ｂに存在するギャップ９３による磁気抵抗Ｒｍｂの増大は若干であり（ギャップ９３における磁束９７の外部への漏れは少なく、受信コイル形成部９１ａ側にある金属外装部９８での渦流損失は小さい）、この時のＱ値は比較的大きな値となるので、長波を受信するのに必要である、前記受信コイル９２に直列に接続する共振用のコンデンサ（容量Ｃ）の両極間に発生する検出電圧Ｖは、前記受信コイル誘起起電力ｖのＱ倍、すなわち、Ｑ・ｖとなって、前記アンテナ９０を金属外装部９８を有する時計に内臓することが可能となった。
しかしながら、基本技術に関わる改良すべき２つの問題がある。１つの問題は以下のようである。図９に示すアンテナ９０において、該アンテナ９０の受信コイル９２に発生する受信コイル誘起起電力ｖを増大するには通路９５ａの交流透磁率μａを通路９５ｂの実効交流透磁率μｂｅに比べより高くする必要があり、つまり、ギャップ９３のギャップ長９３ａを長くする必要があり、一方、前記検出電圧Ｖ大きくするために、前記Ｑ値を大きく取ろうとすると、数１の関係式からインダクタンスＬを大きくする必要があるが、数２から数５の関係式より、磁心９１の閉磁路９６の磁気抵抗Ｒｍをできるだけ小さくする必要があり、磁心９１のギャップ９３を含む磁路９６ｂの磁気抵抗Ｒｍｂを小さくするために、例えば、ギャップ長９３ａを短くする必要があり、一方ではギャップ９３のギャップ長９３ａを長くする必要がある、一方では該ギャップ長９３ａを短くする必要があるという、相反する要求のため両方の要求を共に満たすことができないという問題があった。 However, there are two problems related to the basic technology that should be improved. One problem is as follows. In the antenna 90 shown in FIG. 9, than to increase the receive coil induced electromotive force v generated in the reception coil 92 of the antenna 90 than the AC magnetic permeability mu a passage 95a in the effective AC permeability mu BE passage 95b In other words, the gap length 93a of the gap 93 needs to be increased. On the other hand, in order to increase the detection voltage V, if the Q value is increased, the inductance L is calculated from the relational expression (1). it is necessary to increase, but from a few 2 number 5 relations, it is necessary to minimize the magnetic resistance Rm of the closed magnetic path 96 of the magnetic core 91, the magnetic resistance of the magnetic path 96b including gaps 93 of the magnetic core 91 R mb For example, it is necessary to shorten the gap length 93a, and on the other hand, it is necessary to increase the gap length 93a of the gap 93. However, there is a problem that it is not possible to satisfy both requirements because of conflicting requirements that the gap length 93a needs to be shortened.
もう１つの問題は磁心９１の加工組み立てに関する問題であって、長波９４の受信においてアンテナ９０の受信性能を安定化させるためには、つまり、前記検出電圧Ｖを安定化させるためには、１つには、前記長波９４が通過する磁心９１の通路９５ａと９５ｂのそれぞれの交流透磁率μａと実効交流透磁率μｂｅを安定化させる必要があって、２つには、前記ＬＣ共振回路の前記Ｑ値を安定化させる必要があって、該実効交流透磁率μｂｅと該Ｑ値に関わるギャップ９３のギャップ長９３ａのばらつきを量産上でコントロールする必要があるが、そのばらつきのコントロールは特に組み立てにおいて困難であった。 Another problem is related to the processing and assembling of the magnetic core 91. In order to stabilize the reception performance of the antenna 90 in the reception of the long wave 94, that is, to stabilize the detection voltage V, there is one problem. It is necessary to stabilize the AC permeability μ a and the effective AC permeability μ be of the passages 95a and 95b of the magnetic core 91 through which the long wave 94 passes. It is necessary to stabilize the Q value, and it is necessary to control the variation of the effective AC magnetic permeability μ be and the gap length 93a of the gap 93 related to the Q value in mass production. It was difficult to assemble.
基準信号を出力する基準信号発生手段と、該基準信号に基づき計時情報を出力する計時手段と、該計時情報をもとに時刻を表示する表示手段と、基準時刻情報を持つ標準電波を受信する、受信コイルと、さらに、バイアス磁界を発生するバイアス磁界発生コイルが形成された断面積が大きい受信コイル形成部と該受信コイル形成部より断面積が小さい非受信コイル形成部からなる磁心から構成されるアンテナと、該アンテナに接続する受信手段と、該受信手段からの受信情報に基づき前記計時手段の出力時刻情報を修正する時刻情報修正手段を有し、金属外装部を有する時計ケースからなる電波修正時計において、該時計ケースの内部にある前記アンテナはリング状の一体の磁心からなり、該受信コイルに直列に接続する共振コンデンサとの共振時に該受信コイルが発生する磁束が該磁心から外部に漏れない閉磁路上を回り、さらに、ダンピング制御コンデンサが該バイアス磁界発生コイルに並列に接続されたＬＣバイアス磁界発生回路はスイッチとバイアス発生電流制限抵抗を介して電源とグランドに接続され、前記受信手段はパルス生成手段を有し、該パルス生成手段から、受信する標準電波の周波数より高い周波数を有するバイアス磁界発生パルスを前記スイッチに入力することによって、該スイッチはオンされ、バイアス磁界発生電流がバイアス磁界発生コイルに供給されて、前記磁心にバイアス磁界が印加され、標準電波の受信時において、前記磁心の受信コイル形成部の交流透磁率が最大付近にあるように、また、前記非受信コイル形成部の交流透磁率が該受信コイル形成部の交流透磁率に比べ十分小さくなるように、前記パルス生成手段のバイアス磁界発生パルスにより、前記磁心にバイアス磁界が印加され、その後、共振時には受信コイル形成部と前記非受信コイル形成部のＢ−Ｈカーブ上の動作点が原点付近になるように前記バイアス磁界は減衰振動してゼロにされる。 Reference signal generating means for outputting a reference signal, timing means for outputting time information based on the reference signal, display means for displaying time based on the time information, and receiving a standard radio wave having reference time information A magnetic core comprising a receiving coil, a receiving coil forming part having a large cross-sectional area on which a bias magnetic field generating coil for generating a bias magnetic field is formed, and a non-receiving coil forming part having a smaller cross-sectional area than the receiving coil forming part. that antenna and a receiving means for connecting to the antenna, have a time information correction means for correcting the output time information of the clock means based on the received information from said receiving means, radio wave comprising a watch case having a metal outer portion in timepiece, the antenna on the inside of said time meter casing consists magnetic core of the ring-shaped integral, the resonant capacitor connected in series to the receiving coil Futoki flux which the receiving coil is generated, Ri turn the magnetic sincerely closed magnetic path that does not leak to the outside, further, LC bias field generation circuit damping control capacitor connected in parallel to the bias magnetic field generating coil switch and the bias generator Connected to the power supply and ground via a current limiting resistor, the receiving means has a pulse generating means, from which a bias magnetic field generating pulse having a frequency higher than the frequency of the standard radio wave to be received is input to the switch Thus, the switch is turned on, the bias magnetic field generation current is supplied to the bias magnetic field generation coil, the bias magnetic field is applied to the magnetic core, and the AC transmission of the reception coil forming unit of the magnetic core is received when the standard radio wave is received. The AC permeability of the non-receiving coil forming section is such that the magnetic permeability is near the maximum, and the receiving coil A bias magnetic field is applied to the magnetic core by a bias magnetic field generation pulse of the pulse generating means so that the magnetic permeability is sufficiently smaller than the AC permeability of the component, and then, at resonance, the receiving coil forming unit and the non-receiving coil forming unit The bias magnetic field is damped and zeroed so that the operating point on the BH curve is near the origin .
前記標準電波の受信に入る前に、前記磁心全体を初期化するために、前記パルス生成手段の出力する磁心初期化磁界発生パルスにより、減衰振動を有する、前記バイアス磁界に比べ十分大きな磁心初期化磁界が前記バイアス磁界発生コイルによって前記磁心に印加される。 Prior to the reception of the standard radio wave, in order to initialize the entire magnetic core, the magnetic core initialization magnetic field initialization pulse generated by the pulse generation means outputs a sufficiently large magnetic core initialization compared to the bias magnetic field. A magnetic field is applied to the magnetic core by the bias magnetic field generating coil.
現在あるアンテナ９０より高性能なアンテナとそれを用いた受信手段を使うことによってより小型、薄型のアンテナが可能であり、それを内臓した、より小型、薄型の金属外装部を有する電波修正時計が可能である。 By using an antenna with higher performance than the existing antenna 90 and a receiving means using the antenna, a smaller and thinner antenna is possible, and a radio-controlled timepiece having a smaller and thinner metal exterior portion incorporating the antenna is provided. Is possible.
以下、本発明の実施の形態を図面に基づいて詳述する。 Hereinafter, embodiments of the present invention will be described in detail with reference to the drawings.
図１に本発明の第１のアンテナの平面構成図を示す。４０ｋＨｚの長波４を受信するアンテナ１０はリング状の一体の磁心１からなり、該磁心１はマグネットワイヤーを巻回すことによって長波４を受信するための受信コイル２と受信時にバイアス磁界を発生するバイアス磁界発生コイル３を形成した、断面積が大きい受信コイル形成部１ａと該受信コイル形成部１ａに比べ十分断面積が小さい非受信コイル形成部１ｂからなっており、共振時（受信コイル２に直列に接続する共振用のコンデンサは省略してある）に前記受信コイル２が発生する磁束７が該磁心１から外部に漏れない閉磁路６上を回る構造となっている。 FIG. 1 shows a plan view of a first antenna of the present invention. An antenna 10 that receives a long wave 4 of 40 kHz comprises a ring-shaped integral magnetic core 1, and the magnetic core 1 is wound around a magnet coil and a receiving coil 2 for receiving the long wave 4 and a bias that generates a bias magnetic field at the time of reception. The magnetic field generating coil 3 is formed of a receiving coil forming portion 1a having a large cross-sectional area and a non-receiving coil forming portion 1b having a sufficiently small cross-sectional area compared to the receiving coil forming portion 1a, and at resonance (in series with the receiving coil 2). The magnetic flux 7 generated by the receiving coil 2 travels on a closed magnetic path 6 that does not leak to the outside from the magnetic core 1.
以下、図２に示す本発明のアンテナを用いた電波受信のフローチャートと図３に示す受信手段のブロック図に従って、本発明のアンテナ１０を用いた電波受信方法を説明する。 Hereinafter, a radio wave receiving method using the antenna 10 of the present invention will be described with reference to a flowchart of radio wave reception using the antenna of the present invention shown in FIG. 2 and a block diagram of the receiving means shown in FIG.
まず、図４に示す本発明にかかわる電波修正時計のブロック図を説明する。電波修正時計４０は基準信号を出力する基準信号発生手段４１と、該基準信号に基づき計時情報を出力する計時手段４２と、該計時情報をもとに時刻を表示する表示手段４３と、前記基準時刻情報を持つ標準電波を受信するアンテナ１０と、該アンテナ１０に接続する受信手段４４と、該受信手段４４からの受信情報に基づき前記計時手段４２の出力時刻情報を修正する時刻情報修正手段４５を有している。 First, a block diagram of the radio-controlled timepiece according to the present invention shown in FIG. 4 will be described. The radio-controlled timepiece 40 includes a reference signal generating unit 41 that outputs a reference signal, a time measuring unit 42 that outputs time information based on the reference signal, a display unit 43 that displays time based on the time information, and the reference An antenna 10 for receiving a standard radio wave having time information, a receiving means 44 connected to the antenna 10, and a time information correcting means 45 for correcting the output time information of the time measuring means 42 based on the received information from the receiving means 44. have.
次に、図３に示す受信手段のブロック図を説明する。アンテナ１０の受信コイル３０ａ（図１に示す受信コイル２に相当する）とそれに直列に接続する共振用のコンデンサ３０ｂ（該コンデンサ３０ｂの容量Ｃは受信コイル３０ａのインダクタンスＬと、長波の角周波数ωが１／√ＬＣになるように合わせる）からなるＬＣ共振回路３０のコンデンサ３０ｂの両極を電圧検出手段３８に接続し、該電圧検出手段３８は検出電圧３８ａをコード復調手段３９に出力し、該コード復調手段３９は該検出電圧３８ａからコードを復調し、該復調コード信号３９ａを図４に示す時刻情報修正手段４５に出力する。 Next, a block diagram of the receiving means shown in FIG. 3 will be described. A receiving coil 30a of the antenna 10 (corresponding to the receiving coil 2 shown in FIG. 1) and a resonance capacitor 30b connected in series thereto (the capacitance C of the capacitor 30b is an inductance L of the receiving coil 30a and an angular frequency ω of a long wave) Are connected to the voltage detection means 38, and the voltage detection means 38 outputs the detection voltage 38a to the code demodulation means 39. The code demodulating means 39 demodulates the code from the detected voltage 38a and outputs the demodulated code signal 39a to the time information correcting means 45 shown in FIG.
パルス生成手段３６は、受信用基準信号発生手段３５からの基準信号３５ａを入力して電圧検出手段３８に電圧検出パルス３６ａを出力し、また、前記磁心１にバイアス磁界を印加するためのバイアス磁界発生パルス３６ｂをスイッチ３７に出力する。 The pulse generation means 36 receives the reference signal 35 a from the reception reference signal generation means 35 and outputs a voltage detection pulse 36 a to the voltage detection means 38, and a bias magnetic field for applying a bias magnetic field to the magnetic core 1. The generated pulse 36b is output to the switch 37 .
アンテナ１０のバイアス磁界発生コイル３１ａ（図１に示すバイアス磁界発生コイル３に相当する）にダンピング制御コンデンサ３１ｂを並列に接続したＬＣバイアス磁界発生回路３１はスイッチ３７とバイアス磁界発生電流制限抵抗３３を介して電源３２とグランド３４に接続されている。 An LC bias magnetic field generation circuit 31 in which a damping control capacitor 31b is connected in parallel to a bias magnetic field generation coil 31a (corresponding to the bias magnetic field generation coil 3 shown in FIG. 1) of the antenna 10 includes a switch 37 and a bias magnetic field generation current limiting resistor 33. The power source 32 and the ground 34 are connected to each other.
次に、図２に示す本発明のアンテナを用いた電波受信のフローチャートを使って４０ｋＨｚの長波の受信方法を説明する。 Next, a method for receiving a long wave of 40 kHz will be described with reference to a flowchart of radio wave reception using the antenna of the present invention shown in FIG.
図２に示すように、図３に示すパルス生成手段３６から受信する標準電波の周波数より高い周波数（例えば、長波の８倍の周波数）を有するバイアス磁界発生パルス３６ｂ（図２おいてバイアス磁界発生パルス２１に相当する）をスイッチ３７に入力することによって、該スイッチ３７はオンされ、パルス状のバイアス磁界発生電流２２がバイアス磁界発生コイル３１ａに供給され、前記磁心１にバイアス磁界が印加される。該バイアス磁界発生電流２２は、図５のバイアス磁界発生電流の波形図に示すように、立上がり部２２ａと、飽和部２２ｂと、立下り部２２ｃと、減衰振動部２２ｄからなっており、該飽和部２２ｂの時間において、図６に示す電波受信時のＢ−Ｈカーブ上の動作図で、図１に示す磁心１の受信コイル形成部１ａは磁界Ｈ１で磁束密度Ｂ１の可逆磁化範囲の動作点Ｐ１に、非受信コイル形成部１ｂは磁界Ｈ２で磁束密度Ｂ２の動作点Ｐ２位置にあって、図７に示す交流透磁率μの磁束密度Ｂに対する変化図で、受信コイル形成部１ａは交流透磁率μが最大付近の交流透磁率μ１である動作点Ｐ１（Ｂ１、μ１）に、非受信コイル形成部１ｂは交流透磁率μが１付近の交流透磁率μ２である動作点Ｐ２（Ｂ２、μ２）になっており、交流透磁率μ２は交流透磁率μ１にくらべ十分に小さいので、アンテナ１０に到来した長波はほとんど受信コイル２の通路５ａを通り、受信コイル２に受信コイル誘起起電力２０を発生させる。なお、図２に示す受信コイル誘起起電力２０は見易くするためにバイアス磁界発生パルス２１でなく一定のバイアス磁界発生電圧がスイッチ３７に入力され、スイッチ３７が常時オンした場合の受信コイル誘起起電力２０になっている。ところで、受信コイル誘起起電力２０の位相とバイアス磁界発生パルス２１の位相の関係は電波受信の度に変わるが、バイアス磁界発生パルス２１の周波数に少なくとも長波の８倍の周波数を使えば、長波の波形を捕らえるには問題ない。次に、該受信コイル誘起起電力２０によって図３に示すＬＣ共振回路３０に生じる電流によってコンデンサ３０ｂの電極間に生じる電圧を検出する方法を説明する。 As shown in FIG. 2, a bias magnetic field generation pulse 36b ( a bias magnetic field generation in FIG. 2 ) having a frequency higher than the frequency of the standard radio wave received from the pulse generation means 36 shown in FIG. by entering corresponding to the pulse 21) to the switch 37, the switch 37 is turned on, pulsed bias magnetic field generating current 22 is supplied to the bias magnetic field generating coils 31a, a bias magnetic field Ru is applied to the magnetic core 1 . As shown in the waveform diagram of the bias magnetic field generation current in FIG. 5, the bias magnetic field generation current 22 includes a rising portion 22a, a saturation portion 22b, a falling portion 22c, and a damped oscillation portion 22d. FIG. 6 is an operation diagram on the BH curve at the time of radio wave reception shown in FIG. 6 at the time of the part 22b, and the receiving coil forming part 1a of the magnetic core 1 shown in FIG. In P1, the non-receiving coil forming unit 1b is located at the operating point P2 of the magnetic flux density B2 in the magnetic field H2, and is a variation diagram of the AC permeability μ with respect to the magnetic flux density B shown in FIG. In the operating point P1 (B1, μ1) where the magnetic permeability μ is the AC permeability μ1 near the maximum, the non-receiving coil forming unit 1b operates at the operating point P2 (B2, μ2) where the AC permeability μ is the AC permeability μ2 near 1. The AC permeability μ2 is Since it is sufficiently smaller than the AC permeability μ1, most of the long waves that have arrived at the antenna 10 pass through the path 5a of the receiving coil 2 and generate a receiving coil induced electromotive force 20 in the receiving coil 2. In order to make the receiving coil induced electromotive force 20 shown in FIG. 2 easier to see, the receiving coil induced electromotive force when the constant bias magnetic field generating voltage is input to the switch 37 instead of the bias magnetic field generating pulse 21 and the switch 37 is always turned on. It is 20. By the way, the relationship between the phase of the receiving coil induced electromotive force 20 and the phase of the bias magnetic field generation pulse 21 changes every time radio waves are received, but if the frequency of the bias magnetic field generation pulse 21 is at least eight times longer than the long wave, There is no problem in capturing the waveform. Next, a method for detecting the voltage generated between the electrodes of the capacitor 30b by the current generated in the LC resonance circuit 30 shown in FIG.
図５に示すように、バイアス磁界発生コイル３１ａに供給されたバイアス磁界発生電流２２は立下り部２２ｃで急激に立下り、その後減衰振動部２２ｄを有しゼロになる。図６に示すＢ−Ｈカーブ上ではどうなるかというと、動作点Ｐ１は磁束密度Ｂがゼロの動作点Ｐ０（Ｈ０，Ｂ０）に向かって可逆磁化カーブ上を減衰振動しながらもどり、一方、動作点Ｐ２は同様に磁束密度Ｂがゼロの動作点Ｐ０（Ｈ０，Ｂ０）に向かって経路Ｌｂ上を減衰振動しながらもどり、図７では動作点Ｐ０（Ｂ０，μ０）で、その時の交流透磁率は磁束密度Ｂ０がゼロに対応する最大交流透磁率μ０になる。 As shown in FIG. 5, the bias magnetic field generating current 22 supplied to the bias magnetic field generating coil 31a falls sharply at the falling part 22c, and then has a damping vibration part 22d and becomes zero. What happens on the BH curve shown in FIG. 6 is that the operating point P1 returns to the operating point P0 (H0, B0) where the magnetic flux density B is zero while oscillating and oscillating on the reversible magnetization curve. Similarly, the point P2 returns to the operating point P0 (H0, B0) where the magnetic flux density B is zero while oscillating damped on the path Lb. In FIG. 7, the operating point P0 (B0, μ0) is the AC magnetic permeability at that time. Becomes the maximum AC permeability μ0 corresponding to the magnetic flux density B0 being zero.
図２に示すように、バイアス磁界発生電流２２が減衰振動部２２ｄを通ってゼロになった直後にパルス生成手段３６は電圧検出手段３８に電圧検出パルス３６ａ（図２においては電圧検出パルス２３に相当する）を入力すると、受信コイル３０ａのインダクタンスＬとコンデンサ３０ｂの容量Ｃは長波の角周波数ωが１／√ＬＣに等しくなる共振の条件を満たして、電圧検出手段３８は前記受信コイル誘起起電力２０の振幅ｖの減衰率αに受信コイル３０ａのＱ値（数１に示すＱ値の関係式が適用できる）を掛けたα・Ｑ・ｖとなる振幅Ｖの検出電圧２４（３８ａ）をコード復調手段３９に次の電圧検出パルス３６ａの立ち上がりまで保持出力する。ただし、前記受信コイル誘起起電力２０がＬＣ共振回路３０に生じる電流によって発生する磁束７が磁心１の外部に漏れない閉磁路６上を回るが、該閉磁路６の磁路６ｂにギャップはないのでその磁気抵抗Ｒｍｂは数６のようになる。 As shown in FIG. 2, immediately after the bias magnetic field generating current 22 becomes zero through the damped oscillation part 22d, the pulse generating means 36 sends the voltage detecting pulse 38a to the voltage detecting pulse 36a (in FIG. Are equivalent to each other), the inductance L of the receiving coil 30a and the capacitance C of the capacitor 30b satisfy the resonance condition in which the long-wave angular frequency ω is equal to 1 / √LC. A detection voltage 24 (38a) of amplitude V, which is α · Q · v, obtained by multiplying the attenuation rate α of the amplitude v of the power 20 by the Q value of the receiving coil 30a (a relational expression of the Q value shown in Equation 1 can be applied). The code demodulation means 39 is held and output until the next rise of the voltage detection pulse 36a. However, the magnetic flux 7 generated by the current generated in the LC resonance circuit 30 by the receiving coil induced electromotive force 20 travels on the closed magnetic path 6 where it does not leak to the outside of the magnetic core 1, but there is no gap in the magnetic path 6 b of the closed magnetic path 6. Therefore, the magnetoresistance R mb is as shown in Equation 6.
この減衰率αはバイアス磁界発生電流２２が立下る直前から電圧検出手段３８が検出電圧２４を検出するまでの時間（主にバイアス磁界発生電流２２の減衰振動部２２ｄの時間）に関係するので、バイアス磁界発生電流制限抵抗３３とダンピング制御コンデンサ３１ｂの容量を最適化してその時間を短くすることによって１に近い問題ない値にすることが望ましい。なお、バイアス磁界発生コイル３に印加されたバイアス磁界発生電流２２の立下り２２ｃと振動減衰部２２ｄは受信コイル２とバイアス磁界発生コイル３の電磁結合により前記検出電圧２４の波形に影響を及ぼすが、その周波数は該検出電圧２４の周波数に比べかなり高いので、その影響は電圧検出手段３８にローパスフィルターを設けることによって除去できる。 Since the attenuation rate α is related to the time from the time immediately before the bias magnetic field generation current 22 falls to the time when the voltage detection means 38 detects the detection voltage 24 (mainly, the time of the damping vibration part 22d of the bias magnetic field generation current 22). It is desirable to optimize the capacitance of the bias magnetic field generation current limiting resistor 33 and the damping control capacitor 31b and shorten the time so as to have a value close to 1 with no problem. The falling 22c of the bias magnetic field generating current 22 applied to the bias magnetic field generating coil 3 and the vibration attenuating unit 22d affect the waveform of the detection voltage 24 by electromagnetic coupling between the receiving coil 2 and the bias magnetic field generating coil 3. Since the frequency is considerably higher than the frequency of the detection voltage 24, the influence can be eliminated by providing the voltage detection means 38 with a low-pass filter.
さらに、図１０に従って、本発明の第２の受信手段を説明する。該受信手段１４４は図４に示す本発明にかかわる電波修正時計のブロック図で、図３に示す本発明の第１の受信手段４４に置き換わることができ、受信手段１４４の受信手段４４と異なる点は、電源３２と、バイアス磁界発生アンテナ１０のバイアス磁界発生コイル３１ａ（図１に示すバイアス磁界発生コイル３に相当する）にダンピング制御コンデンサ３１ｂを並列に接続したＬＣバイアス磁界発生回路３１に接続するスイッチ３７とグランド３４間に接続するバイアス磁界電流制限抵抗３３を、初期化スイッチ１０８とバイアス磁界電流制限抵抗１０３ｂの並列接続の磁心初期化磁界電流制限抵抗１０３ａとの直列接続に置き換えた点である。 Further, the second receiving means of the present invention will be described with reference to FIG. The receiving means 144 is a block diagram of the radio-controlled timepiece according to the present invention shown in FIG. 4, and can be replaced with the first receiving means 44 of the present invention shown in FIG. 3, and is different from the receiving means 44 of the receiving means 144. Is connected to an LC bias magnetic field generation circuit 31 in which a damping control capacitor 31b is connected in parallel to a power source 32 and a bias magnetic field generation coil 31a of the bias magnetic field generation antenna 10 (corresponding to the bias magnetic field generation coil 3 shown in FIG. 1). The bias magnetic field current limiting resistor 33 connected between the switch 37 and the ground 34 is replaced with a series connection of a parallel connection of the initialization switch 108 and the bias magnetic field current limiting resistor 103b. .
長波の受信を開始する前に、パルス生成手段１０６が出力する磁心初期化磁界発生信号１０６ｃによって初期化スイッチ１０８がオンされ、パルス生成手段１０６が出力する磁心初期化磁界発生パルス１０６ｂ（この時は、バイアス磁界発生パルスではなく、磁心初期化磁界を発生するためのパルス）でスイッチ３７がオンされると、磁心初期化磁界発生電流制限抵抗１０３ａに従って磁心初期化磁界電流がバイアス磁界発生コイル３１ａに供給されその後、スイッチ３７はオフされ、ダンピング制御コンデンサ３１ｂにより該磁心初期化磁界電流は減衰振動しながらゼロにされる（該磁心初期化磁界発生電流の電流波形は図５に示すバイアス磁界発生電流の波形と同様な波形となる）。 Before starting the reception of the long wave, the initialization switch 108 is turned on by the magnetic core initialization magnetic field generation signal 106c output from the pulse generation means 106, and the magnetic core initialization magnetic field generation pulse 106b (at this time) output from the pulse generation means 106 When the switch 37 is turned on with a pulse for generating a magnetic core initialization magnetic field instead of a bias magnetic field generation pulse ), the magnetic core initialization magnetic field current is applied to the bias magnetic field generation coil 31a according to the magnetic core initialization magnetic field generation current limiting resistor 103a. After that, the switch 37 is turned off, and the magnetic core initialization magnetic field current is made zero while being damped and oscillated by the damping control capacitor 31b (the current waveform of the magnetic core initialization magnetic field generation current is the bias magnetic field generation current shown in FIG. It will be the same waveform as
図７に示す電波受信におけるＢ−Ｈカーブ上の動作図で説明すると、前記磁心初期化磁界発生電流は図１に示すアンテナ１０の磁心１の受信コイル形成部１ａと非受信コイル形成部１ｂを十分に飽和させる磁心初期化磁界を発生し、受信コイル形成部１ａではＢ−Ｈカーブ上の動作点Ｐ３（Ｈ３、Ｂ３）から経路Ｌｉ上を減衰振動しながら動作点Ｐ０（Ｈ０，Ｂ０）に達し、同様に、非受信コイル形成部１ｂもＢ−Ｈカーブ上のさらに高い飽和磁束密度の動作点（図示せず）から経路Ｌｉ上を減衰振動しながら動作点Ｐ０（Ｈ０，Ｂ０）に達し、何らかの原因によって磁心１が帯磁していたとしても、電波受信の前に消磁されるので、受信時には、初期化スイッチ１０８はオフされ、バイアス磁界発生電流制限抵抗１０３ｂと磁心初期化磁界発生電流制限抵抗１０３ａの合成抵抗によって決まる、受信コイル形成部１ａと非受信コイル形成部１ｂにそれぞれ、常に一定のバイアス磁界Ｈ１とＨ２を印加できるので安定な検出電圧を取得することができ、電波受信性能がより安定化する。 Referring to the operation diagram on the BH curve in radio wave reception shown in FIG. 7, the magnetic core initialization magnetic field generation current is generated by the receiving coil forming portion 1a and the non-receiving coil forming portion 1b of the magnetic core 1 of the antenna 10 shown in FIG. A magnetic core initializing magnetic field that sufficiently saturates is generated, and the receiving coil forming unit 1a moves from the operating point P3 (H3, B3) on the BH curve to the operating point P0 (H0, B0) while performing damped oscillation on the path Li. Similarly, the non-receiving coil forming portion 1b also reaches the operating point P0 (H0, B0) from the operating point (not shown) of the higher saturation magnetic flux density on the BH curve while oscillating damped on the path Li. Even if the magnetic core 1 is magnetized for some reason, it is demagnetized before radio wave reception. Therefore, at the time of reception, the initialization switch 108 is turned off, and the bias magnetic field generation current limiting resistor 103b and the magnetic core initialization magnetic field are turned off. Since constant bias magnetic fields H1 and H2 can always be applied to the receiving coil forming unit 1a and the non-receiving coil forming unit 1b determined by the combined resistance of the raw current limiting resistor 103a, a stable detection voltage can be obtained. Receive performance is more stable.
図８に本発明の第２のアンテナの平面構成図を示す。長波８４を受信するアンテナ８０はリング状の一体の磁心８１からなり、該磁心８１はマグネットワイヤーを巻回すことによって長波８４を受信するための受信コイル８２と受信時にバイアス磁界を発生するバイアス磁界発生コイル８３を形成した、断面積が大きい受信コイル形成部８１ａと該受信コイル形成部８１ａに比べ十分断面積が小さい非受信コイル形成部８１ｂからなっており、基本的に共振時（受信コイル８２に直列に接続する共振用のコンデンサは省略してある）に前記受信コイル８２が発生する磁束８７が該磁心８１から外部に漏れない閉磁路８６上を回る構造となっている。図１に示す本発明の第１のアンテナ１０と異なる点は、磁心８１が受信コイル８２とバイアス磁界発生コイル８３を形成した受信コイル形成部８１ａに紙面の表側から非受信コイル形成部８１ｂを重ね合わせることによって一体化した構造である点であり、アンテナ８０は非受信コイル形成部８１ｂを受信コイル形成部８１ａに重ね合わせる前に、受信コイル形成部８１ａにマグネットワイヤーを巻回すことができる構造となっている。他の点はアンテナ１０と同様であり説明を省略する。 FIG. 8 is a plan view of the second antenna of the present invention. The antenna 80 for receiving the long wave 84 is composed of a ring-shaped integral magnetic core 81. The magnetic core 81 is wound around a magnet wire to generate a bias magnetic field for generating a bias magnetic field when receiving the reception coil 82 for receiving the long wave 84. The coil 83 is formed of a receiving coil forming part 81a having a large cross-sectional area and a non-receiving coil forming part 81b having a sufficiently small cross-sectional area compared to the receiving coil forming part 81a. A resonance capacitor connected in series is omitted), and the magnetic flux 87 generated by the receiving coil 82 circulates on a closed magnetic path 86 that does not leak from the magnetic core 81 to the outside. 1 differs from the first antenna 10 of the present invention shown in FIG. 1 in that a magnetic core 81 overlaps a receiving coil forming portion 81a in which a receiving coil 82 and a bias magnetic field generating coil 83 are formed with a non-receiving coil forming portion 81b from the front side of the drawing. The antenna 80 has an integrated structure, and the antenna 80 has a structure in which a magnet wire can be wound around the receiving coil forming portion 81a before the non-receiving coil forming portion 81b is superimposed on the receiving coil forming portion 81a. It has become. The other points are the same as those of the antenna 10 and will not be described.
以上の説明により、本発明のアンテナ１０あるいはアンテナ８０は、従来のアンテナ９０に比べアンテナ１０に到来した長波はほとんど受信コイル２の通路５ａを通るので、受信コイル２により大きな受信コイル誘起起電力２０を発生し、また、ＬＣ共振回路の共振時に該受信コイル誘起起電力２０による電流によって発生する磁束７は閉磁路６を基本的に外部に漏れることなく回るので、図１に示すように、非受信コイル形成部１ｂ側にある金属外装部８での渦流損失はなく（受信コイル形成部１ａ側に金属外装部８があっても、同様にそれによる渦流損失はなく、また、図において省略された、その他の金属製の電子部品による渦流損失もない）、従来のアンテナ９０に比べより大きなＱ値、つまり、より大きな検出電圧２４を出力する高感度で高性能なアンテナであって、小型化、薄型化に適していることが分かる。 According to the above description, the antenna 10 or the antenna 80 of the present invention has a larger reception coil induced electromotive force 20 than the reception coil 2 because the long wave arriving at the antenna 10 almost passes through the path 5a of the reception coil 2 as compared with the conventional antenna 90. In addition, the magnetic flux 7 generated by the current generated by the receiving coil induced electromotive force 20 at the time of resonance of the LC resonance circuit rotates basically without leaking to the outside through the closed magnetic path 6, and therefore, as shown in FIG. There is no eddy current loss in the metal sheathing portion 8 on the receiving coil forming portion 1b side (even if the metal sheathing portion 8 is on the receiving coil forming portion 1a side, there is no eddy current loss due to this, and it is omitted in the figure) In addition, there is no eddy current loss due to other metal electronic parts), and a larger Q value than the conventional antenna 90, that is, a larger detection voltage 24 is output. A high-performance antenna sensitivity, compact, to be suitable for thinning seen.
以上の説明により、本発明のアンテナ１０あるいはアンテナ８０は、従来のアンテナ９０に対し、それぞれの磁心１あるいは８０はその加工組み立てにおいて受信性能のばらつきの発生の原因となるギャップを有しない一体構造であるので大量生産に適している。 From the above description, the antenna 10 or the antenna 80 of the present invention is different from the conventional antenna 90 in that each magnetic core 1 or 80 has an integrated structure that does not have a gap that causes a variation in reception performance in processing and assembly. It is suitable for mass production.
タイムコードを有する４０ｋＨｚの長波の標準電波に対して説明してきたが、６０ｋＨｚ等の他の長波やさらに高い周波数であるＶＨＦ帯（１００ＭＨｚ付近）の超短波まで本発明のアンテナとそれを用いた電波受信方法が適用できることは言うまでもない。 The 40 kHz long wave standard radio wave having a time code has been described. However, other long waves such as 60 kHz and even higher frequency VHF band (near 100 MHz) ultra short wave and the radio wave reception using the antenna of the present invention. It goes without saying that the method is applicable.
以上の詳細な説明により示されたように、本発明のアンテナとそれを用いた受信手段を使用することによって、小型、薄型の金属外装部を有する電波修正時計、例えば、女性用電波修正時計を提供できる。 As shown in the above detailed description, by using the antenna of the present invention and the receiving means using the antenna, a radio-controlled timepiece having a small and thin metal exterior part, for example, a radio-controlled timepiece for women Can be provided.
１０ ８０ ９０ アンテナ
１ ８１ ９１ 磁心
１ａ ８１ａ ９１ａ 受信コイル形成部
１ｂ ８１ｂ ９１ｂ 非受信コイル形成部
２ ８２ ９２ ３０ａ 受信コイル
３ ８３ バイアス磁界発生コイル
２０ 受信コイル誘起起電力
２１ ３６ｂ １０６ｂ バイアス磁界発生パルス
２２ バイアス磁界発生電流
２２ｄ 減衰振動部
２３ 電圧検出パルス
２４ ３８ａ 検出電圧
３０ ＬＣ共振回路
３０ｂ 共振用コンデンサ
３１ ＬＣバイアス磁界発生回路
３１ａ バイアス磁界発生コイル
３１ｂ ダンピング制御コンデンサ
３３ １０３ｂ バイアス磁界発生電流制限抵抗
３５ １０５ 受信用基準信号発生手段
３６ １０６ パルス生成手段
３７ スイッチ
３８ 電圧検出手段
４ ８４ ９４ 長波
４４ １４４ 受信手段
５ａ ５ｂ ８５ａ ８５ｂ ９５ａ ９５ｂ 電波通路
６ ８６ ９６ 閉磁路
７ ８７ ９７ 磁束
８ ８８ ９８ 金属外装部
１０３ａ 初期化磁界発生電流制限抵抗
１０８ 初期化スイッチ
10 80 90 Antenna 1 81 91 Magnetic core 1a 81a 91a Receiving coil forming unit 1b 81b 91b Non-receiving coil forming unit 2 82 92 30a Receiving coil 3 83 Bias magnetic field generating coil 20 Receiving coil induced electromotive force 21 36b 106b Bias magnetic field generating pulse 22 Bias Magnetic field generation current 22d Attenuation oscillation unit 23 Voltage detection pulse 24 38a Detection voltage 30 LC resonance circuit 30b Resonance capacitor 31 LC bias magnetic field generation circuit 31a Bias magnetic field generation coil 31b Damping control capacitor 33 103b Bias magnetic field generation current limiting resistor 35 105 For reception Reference signal generating means 36 106 Pulse generating means 37 Switch 38 Voltage detecting means 4 84 94 Long wave 44 144 Receiving means 5a 5b 85a 85b 95a 95b Radio wave path 6 86 96 Closed magnetic path 87 97 flux 8 88 98 metal outer section 103a initialization magnetic field generating current limiting resistor 108 initialization switch
Claims (2)
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2004189137A JP4052653B2 (en) | 2004-06-28 | 2004-06-28 | Radio correction clock |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2004189137A JP4052653B2 (en) | 2004-06-28 | 2004-06-28 | Radio correction clock |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JP2006010542A JP2006010542A (en) | 2006-01-12 |
| JP4052653B2 true JP4052653B2 (en) | 2008-02-27 |
Family
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| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP2004189137A Expired - Fee Related JP4052653B2 (en) | 2004-06-28 | 2004-06-28 | Radio correction clock |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JP4052653B2 (en) |
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP2014165740A (en) * | 2013-02-26 | 2014-09-08 | Norio Miyauchi | Antenna |
Families Citing this family (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US7848180B2 (en) | 2005-10-28 | 2010-12-07 | Casio Computer Co., Ltd. | Antenna apparatus, receiving apparatus and watch using magnetic sensor |
| JP4687585B2 (en) * | 2006-06-28 | 2011-05-25 | カシオ計算機株式会社 | Antenna circuit and clock |
| JP5041610B2 (en) * | 2010-11-01 | 2012-10-03 | 則雄 宮内 | Wireless charging apparatus and wireless charging method thereof |
| CN114864235A (en) * | 2021-02-04 | 2022-08-05 | 中车株洲电力机车研究所有限公司 | Iron core magnetic circuit multiplexing method |
-
2004
- 2004-06-28 JP JP2004189137A patent/JP4052653B2/en not_active Expired - Fee Related
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP2014165740A (en) * | 2013-02-26 | 2014-09-08 | Norio Miyauchi | Antenna |
Also Published As
| Publication number | Publication date |
|---|---|
| JP2006010542A (en) | 2006-01-12 |
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