JP3788051B2 - Resonator, filter, duplexer, and communication device - Google Patents

Description

[0001]
BACKGROUND OF THE INVENTION
The present invention relates to a resonator, a filter, a duplexer, and a communication device.
[0002]
[Prior art]
As a resonator used in the microwave band and the millimeter wave band, a hairpin resonator described in JP-A-62-193302 is known. This hairpin resonator is provided with a line having a curved portion on a dielectric substrate, and is characterized in that it can be downsized as compared with a resonator having a linear line. Further, as another resonator that can be miniaturized, a resonator in which a spiral line is provided on a dielectric substrate as described in JP-A-2-96402 is known.
[0003]
[Problems to be solved by the invention]
By the way, the conventional resonator comprises one resonator by one half wavelength line. Therefore, in the conventional resonator, a region where electric energy is concentrated and accumulated and a region where magnetic energy is concentrated and accumulated are separated into specific regions of the dielectric substrate, respectively, so-called lumped constants. It was handled as an element. Specifically, the region where electric energy is stored is near the open end of the half-wave line, and the region where magnetic energy is stored is near the center of the half-wave line.
[0004]
Here, the magnetic energy is accumulated by the current flowing in the half-wave line according to Ampere's law. In other words, the concentration of the magnetic energy storage area at a specific location means that the current is concentrated at that location. However, in the high frequency band of the microwave band and the millimeter wave band, current concentrates on the edge of the half-wavelength line due to the so-called edge effect, and the conductor loss at the edge increases. For this reason, the concentration of the current at a specific location significantly increases the conductor loss due to the edge effect.
[0005]
When the resonator is downsized, it is necessary to reduce the size of the dielectric substrate and increase the dielectric constant of the dielectric substrate. When the length of the half-wavelength line is shortened as the size of the dielectric substrate is reduced, the resonance frequency is increased (for example, 10 GHz). Therefore, the dielectric constant of the dielectric substrate is increased to lower the resonance frequency to reduce the original desired frequency. This is because the resonance frequency (for example, 2 GHz) must be set. However, since there is a limit that a dielectric constant of a dielectric substrate having a low loss in practice cannot be used as much as possible, there is a limit to miniaturization of the resonator.
[0006]
SUMMARY OF THE INVENTION An object of the present invention is to provide a resonator, a filter, a duplexer, and a communication device that have an excellent loss characteristic while achieving a reduction in size and weight.
[0007]
[Means and Actions for Solving the Problems]
In order to achieve the above object, a resonator according to the present invention includes:
(A) an insulating member;
(B) a plurality of conductor lines provided on the insulating member and having a curved portion and electromagnetically coupled to each other;
(C) Both ends of the conductor line are open ends, and the open ends are in the same plane. so Placed in different positions The conductor line has a substantially ring shape with a cut portion. thing,
It is characterized by. More specifically, Conductor track Are disposed at positions different from each other by, for example, 180 degrees or 90 degrees between adjacent conductor lines.
[0008]
With the above configuration, the region in which electrical energy is stored and the region in which magnetic energy is stored are dispersed in the insulating member, and the deviation of the electric field and magnetic field distribution is reduced. Therefore, the density of current flowing in the conductor line is made uniform. In other words, the current distribution in the longitudinal direction of the conductor line is transformed from a sinusoidal curve into a group of curves having a more uniform shape and a smaller amplitude. As described above, since the current distribution is made uniform, the conductor loss due to the edge effect and the skin effect is reduced.
[0009]
In the resonator according to the present invention, at least one gap is provided at the edge of the conductor line along the edge, and the conductor pattern width and the gap width of the edge are substantially equal to the skin depth of the current. It is characterized in that it is set to a size. Alternatively, a plurality of linear conductors are arranged with a gap to form a conductor line, and the conductor pattern width of the linear conductor and the width of the gap are set to substantially the skin depth dimension. .
[0010]
With the above configuration, the current flowing through the conductor line is shunted to the conductor having the pattern width of the skin depth dimension. Therefore, the edge effect and the skin effect are alleviated and the conductor loss is further reduced.
[0011]
In the resonator according to the present invention, the conductor lines are stacked via a thin film dielectric, and the thickness of the remaining conductor line and the thickness of the thin film dielectric are determined with the skin depth remaining, leaving the uppermost conductor line. It is characterized by being set to the following dimension. Here, all the conductor lines may have the same shape pattern.
[0012]
With the above configuration, the current is shunted to the plurality of stacked conductor lines. Accordingly, the edge effect and skin effect of the current are alleviated in the film thickness direction of the conductor line, and the conductor loss is further reduced.
[0013]
Also, by filling the gap between adjacent conductor lines in the same plane with a dielectric material, the distance between conductor lines can be changed according to the dielectric constant of the dielectric material, and the degree of freedom in designing the resonator Becomes larger.
[0014]
In addition, since current concentration is reduced in each part of the conductor line, even for conductor lines with a narrow pattern width (small cross-sectional area), the current density is less than the critical current density required to maintain a superconducting state. Can be. Therefore, a conductor line made of a superconductor can easily maintain a superconducting state.
[0015]
Furthermore, the filter, the duplexer, and the communication device according to the present invention include the resonator having the above-described characteristics, so that the insertion loss can be reduced and the size can be reduced.
[0016]
DETAILED DESCRIPTION OF THE INVENTION
DESCRIPTION OF EMBODIMENTS Hereinafter, embodiments of a resonator, a filter, a duplexer, and a communication device according to the present invention will be described with reference to the accompanying drawings.
[0017]
[Principle, FIGS. 1 to 5]
It will be described with reference to FIG. 1 and FIG. 2 that the conductor loss of the resonator can be reduced by configuring the resonator with a plurality of conductor lines. FIG. 1 and FIG. 2 are electromagnetic field distribution diagrams of the resonator when one resonator is constituted by one and two conductor lines, respectively.
[0018]
As shown in FIG. 1, the conductor line 1 has a substantially ring shape having a cut portion C, and the length thereof is λ / 2 (λ: wavelength of the resonance frequency of the resonator). When the current i flows through the conductor line 1 in the direction indicated by the arrow, for example, electric energy is concentrated and accumulated in the vicinity of the open ends 1a and 1b of the line 1, and little magnetic energy is accumulated. Therefore, a maximum potential difference is obtained between the open ends 1a and 1b. On the other hand, when the current i flows in the line 1, a magnetic field H is generated around the line 1 according to Ampere's law, and magnetic energy is concentrated and accumulated in the vicinity of the central portion 1 c of the line 1, and electric energy Will only accumulate a little. Therefore, in the resonator R1 configured by one conductor line 1, a region where electric energy is concentrated and accumulated is separated from a region where magnetic energy is concentrated and accumulated, so-called lumped element. Are treated as
[0019]
In the resonator R1, the current distribution in the longitudinal direction of the conductor line 1 is a sinusoidal curve, the amplitude is minimum (node) at the open ends 1a and 1b of the line 1, and the amplitude is maximum (antinode) at the center 1c. ) That is, the current density is maximized at the central portion 1c, and the conductor loss due to the edge effect is remarkably increased. In FIGS. 1 and 2, the density of current density is indicated by the length of the arrow of current i. That is, if the arrow is short, the current density is low, and if the arrow is long, the current density is high. In addition, the strength of the magnetic field strength is indicated by the size of the diameter of the direction symbol of the Z component of the magnetic field H. That is, if the diameter of the direction symbol is small, the magnetic field strength is weak, and if the diameter of the direction symbol is large, the magnetic field strength is high.
[0020]
On the other hand, next, as shown in FIG. 2, a resonator R2 constituted by two conductor lines 2 and 3 will be described. Each of the conductor lines 2 and 3 has a substantially ring shape having a cut portion C. The line 3 is arranged in parallel inside the line 2 with a predetermined interval, and the cut portion C of the line 3 is disposed at a position that is 180 degrees different from the cut C of the line 2. When the resonator R2 is resonating, the directions of the currents i flowing in the adjacent lines 2 and 3 are the same direction.
[0021]
When the current i flows through the lines 2 and 3 in the directions indicated by arrows, for example, electric energy is concentrated and accumulated near the open ends 2a, 2b, 3a, and 3b of the lines 2 and 3, and the central portion 2c. , 3c, magnetic energy is concentrated and accumulated. That is, in the resonator R2 configured by the two conductor lines 2 and 3, the region where electric energy is concentrated and accumulated and the region where magnetic energy is concentrated and accumulated are adjacently arranged and dispersed. . Thereby, the deviation of the magnetic field distribution is reduced, the effective inductance of the lines 2 and 3 can be increased, and the unloaded Q of the resonator R2 can be improved.
[0022]
In other words, each of the conductor lines 2 and 3 has a sinusoidal current distribution in the longitudinal direction, and the amplitude is minimum (node) at the open ends 2a, 2b, 3a, and 3b, and the amplitude at the central portions 2c and 3c. Is the maximum (belly). However, since the open ends 2a and 2b of the line 2 and the central part 3c of the line 3 are disposed adjacent to each other, mutual induction occurs between them. Similarly, since the central portion 2c of the line 2 and the open ends 3a and 3b of the line 3 are adjacently disposed, mutual induction occurs between them. As a result, the mutual current distribution is transformed from a sinusoidal curve to a curve having a more uniform and smaller amplitude. As a result, the density of the current i flowing in the conductor lines 2 and 3 is made uniform, and the conductor loss due to the edge effect and the skin effect can be reduced.
[0023]
Next, it will be described based on the planar circuit simulation analysis that the resonance frequency of the resonator can be lowered by configuring the resonator with a plurality of conductor lines.
[0024]
3A to 3D respectively show resonators R3 to R6 used for analysis. A resonator R3 illustrated in FIG. 3A includes a substantially ring-shaped conductor line 4 having a cut portion C. The pattern width of the line 4 was set to 400 μm. The resonator R4 shown in FIG. 3B includes substantially ring-shaped conductor lines 5 and 6 each having a cut portion C. The line 6 is arranged inside the line 5 with a predetermined interval, and the cutting part C of the line 6 is disposed adjacent to the cutting part C of the line 5. The pattern width of the lines 5 and 6 was set to 190 μm, and the interval between the lines 5 and 6 was set to 20 μm. A resonator R5 shown in FIG. 3C includes substantially ring-shaped conductor lines 7 and 8 each having a cut portion C. The line 8 is arranged inside the line 7 with a predetermined interval, and the cut portion C of the line 8 is disposed at a position 90 degrees different from the cut portion C of the line 7. The pattern width of the lines 7 and 8 was set to 190 μm, and the distance between the lines 7 and 8 was set to 20 μm. A resonator R6 shown in FIG. 3D includes substantially ring-shaped conductor lines 9 and 10 each having a cut portion C. The line 10 is arranged in parallel with a predetermined interval inside the line 9, and the cut part C of the line 10 is disposed at a position 180 degrees different from the cut part C of the line 9. The pattern width of the lines 9 and 10 was set to 190 μm, and the distance between the lines 9 and 10 was set to 20 μm.
[0025]
FIG. 4 is a graph showing simulation analysis results of the resonators R3 to R6. The resonance characteristic of the resonator R3 is indicated by a dotted line. The resonance frequency (fundamental mode) of the resonator R3 is 3.33 GHz, and a spurious mode (secondary mode) having a higher frequency than the fundamental mode is generated at a frequency of 6.64 GHz. The resonance characteristic of the resonator R4 is indicated by a two-dot chain line. The resonance frequency (fundamental mode) of the resonator R4 is 2.95 GHz, and the spurious modes (secondary, third and fourth modes) are generated at frequencies of 3.52 GHz, 4.74 GHz and 6.92 GHz, respectively. Since the resonator R4 is composed of the two conductor lines 5 and 6, the resonance frequency is lower than that of the resonator R3 due to the influence of the capacitance generated between the lines 5 and 6. However, there is a problem that the secondary spurious mode occurs close to the resonance frequency (fundamental mode) and is difficult to use as a filter.
[0026]
The resonance characteristic of the resonator R5 is indicated by a one-dot chain line. The resonance frequency (fundamental mode) of the resonator R5 is 2.20 GHz, and spurious modes (second-order and third-order) are generated at frequencies of 4.06 GHz and 5.60 GHz, respectively. The resonator R5 is composed of two conductor lines 7 and 8, and the mutual cut portions C are arranged at positions different by 90 degrees. As a result, in addition to the influence of the capacitance generated between the lines 7 and 8, it is considered that the mutual induction amount is increased. If the resonators have the same size, the resonance frequency is reduced to about 2/3 of the resonator R3. Lower. Moreover, since the secondary and tertiary spurious modes move to the high frequency side and away from the resonance frequency (fundamental mode) compared to the resonator R4, they are suitable for use as a filter.
[0027]
The resonance characteristic of the resonator R6 is indicated by a solid line. The resonance frequency (fundamental mode) of the resonator R6 is 2.15 GHz, and spurious modes (secondary and third order) are generated at 4.86 GHz and 6.18 GHz, respectively. The resonator R6 is composed of two conductor lines 9 and 10, and the mutual cut portions C are arranged at positions different by 180 degrees. Thereby, in addition to the influence of the capacitance generated between the lines 9 and 10, it is considered that the mutual induction amount increases, and the resonance frequency is lowered to about 2/3 of the resonator R3. Moreover, since the secondary and tertiary spurious modes move further to the higher frequency side than the resonator R5 and away from the resonance frequency (fundamental mode), they are suitable for use as a filter. As a result, by configuring the resonator with a plurality of conductor lines, the size of the insulating substrate can be reduced and the resonator can be downsized without increasing the dielectric constant of the insulating substrate.
[0028]
Furthermore, as shown in FIGS. 5A and 5B, the resonance frequency of the resonator in the case where the resonator is constituted by three and four conductor lines will be described based on a planar circuit simulation analysis.
[0029]
The resonator R7 shown in FIG. 5A includes substantially ring-shaped conductor lines 11 to 13 each having a cut portion C. The lines 11 to 13 are arranged in parallel with a predetermined interval, and the cut portions C of the adjacent lines 11 to 13 are arranged at positions different from each other by 180 degrees. The pattern width of the lines 11 to 13 was set to 120 μm, and the interval between the lines 11 to 13 was set to 20 μm. As a result of simulating the resonator R7 having the above configuration, the resonance frequency (fundamental mode) was 1.78 GHz.
[0030]
The resonator R8 illustrated in FIG. 5B includes substantially ring-shaped conductor lines 14 to 17 each having a cut portion C. The lines 14 to 17 are arranged side by side with a predetermined interval, and the cut portions C of the adjacent lines 14 to 17 are arranged at positions different from each other by 180 degrees. The pattern width of the lines 14 to 17 was set to 85 μm, and the interval between the lines 14 to 17 was set to 20 μm. As a result of simulating the resonator R8 having the above configuration, the resonance frequency (fundamental mode) was 1.57 GHz.
[0031]
As a result, it can be seen that by increasing the number of conductor lines constituting the resonator, the resonance frequency of the resonator is reduced, and the resonator can be further reduced in size (area).
[0032]
[First Embodiment, FIGS. 6 to 18]
As shown in FIG. 6, the resonator R <b> 9 is provided on the insulating substrate 21, the two conductor lines 22 and 23 provided on the upper surface of the insulating substrate 21, and the lower surface and the outer peripheral end of the insulating substrate 21. The ground conductor 25 is composed of an input terminal 28 and an output terminal 29 provided at the end of the insulating substrate 21. As a material for the insulating substrate 21, a dielectric, an insulator, or the like is used.
[0033]
Each of the conductor lines 22 and 23 has bent portions bent at right angles at three locations, and both end portions 22a, 22b, 23a, and 23b are open ends. The open ends 22a and 22b of the line 22 are close to each other, and the central portion 23c of the line 23 is disposed between the open ends 22a and 22b. Similarly, the open ends 23a and 23b of the line 23 are close to each other, and the central portion 22c of the line 22 is disposed between the open ends 23a and 23b. The open ends 22a and 22b are disposed at positions different from the open ends 23a and 23b by 180 degrees. Further, the lines 22 and 23 are arranged in parallel with a predetermined gap D. Thus, the lines 22 and 23 are mutually inductively and capacitively coupled on the upper surface of the insulating substrate 21. The input terminal 28 and the output terminal 29 are adjacent to the open ends 22a and 23b of the lines 22 and 23 with a predetermined gap, respectively, and are capacitively coupled to the open ends 22a and 23b.
[0034]
The conductor lines 22 and 23, the ground conductor 25, and the input / output terminals 28 and 29 are formed into a film shape on the surface of the insulating substrate 21 by a conductive material such as Ag, Ag-Pd, or Cu by printing, sputtering, vapor deposition, or the like. Then, it is formed using a known photolithography technique (resist film coating, exposure, resist film development, conductive material etching, resist film peeling) or the like.
[0035]
When a high frequency signal is supplied from the input terminal 28 and the resonator R9 is resonating, the directions of currents flowing in the adjacent lines 22 and 23 are the same. When current flows through the lines 22 and 23, electric energy is concentrated and accumulated near the open ends 22a, 22b, 23a, and 23b of the lines 22 and 23, and magnetic energy is accumulated near the center parts 22c and 23c. Is concentrated and accumulated. That is, in the resonator R9 configured by the two conductor lines 22 and 23, the region where electric energy is concentrated and accumulated and the region where magnetic energy is concentrated and accumulated are adjacently arranged and dispersed. . Thereby, the deviation of the magnetic field distribution is reduced, the effective inductance of the lines 22 and 23 can be increased, and the unloaded Q of the resonator R9 can be improved.
[0036]
In other words, each of the conductor lines 22 and 23 has a sinusoidal current distribution in the longitudinal direction, the amplitude is minimum (node) at the open ends 22a, 22b, 23a, and 23b, and the amplitude at the central portions 22c and 23c. Is the maximum (belly). However, since the open ends 22a and 22b of the line 22 and the central part 23c of the line 23 are adjacently arranged, mutual induction occurs between them. Similarly, since the central portion 22c of the line 22 and the open end portions 23a and 23b of the line 23 are disposed adjacent to each other, mutual induction occurs between them. As a result, the mutual current distribution is transformed from a sinusoidal curve to a curve having a more uniform and smaller amplitude. As a result, the density of the current flowing in the conductor lines 22 and 23 is made uniform, and the conductor loss due to the edge effect and the skin effect can be reduced.
[0037]
Furthermore, by configuring the resonator R9 with the two conductor lines 22 and 23, the resonance frequency can be lowered as compared with the conventional resonator. As a result, the resonator R9 can be downsized by reducing the size of the insulating substrate 21 without increasing the dielectric constant of the insulating substrate 21.
[0038]
The conductor lines 22 and 23 are usually one conductor pattern as shown in FIG. 7A. By the way, in the case of the resonator R9 used in the microwave band or the millimeter wave high frequency band, the conductor lines 22 and 23 having the conductor pattern as shown in FIG. Current tends to concentrate. Therefore, as shown in FIG. 7B, in order to alleviate the current concentration at the edge portion, two gaps 31 are formed along the edge portions at both edge portions of the lines 22 and 23, respectively. And the conductor pattern width and the gap width at the edge may be set to substantially the skin depth of the current. As a result, a thin conductor pattern is formed at the edge portions of the conductor lines 22 and 23, and current is divided between the thin conductor pattern and the main conductor pattern. As a result, the edge effect and skin effect of the current are alleviated, and the conductor loss can be further reduced.
[0039]
Further, in FIG. 7B, the gap 31 provided at the edge of the lines 22 and 23 and the gap D between the lines 22 and 23 are filled with a dielectric material 33 to increase the coupling capacitance between the lines 22 and 23. It is getting bigger. Thereby, the dimension of the gap D between the lines 22 and 23 can be changed according to the dielectric constant of the dielectric material 33, and the degree of freedom in designing the resonator R9 is increased.
[0040]
The resonator R9 may be constituted by the conductor lines shown in FIGS. 8 to 18 in addition to the two conductor lines 22 and 23. FIG. 8 is composed of four conductor lines 41 to 44. The cut portions C of the lines 41 to 44 are arranged at positions different by 90 degrees between the adjacent lines 41 to 44. 9 and 10 are configured by substantially ring-shaped conductor lines 45 to 48 and 49 to 52 each having a cut portion C at a square corner. In FIG. 9, the cut portions C are disposed at positions that differ by 90 degrees between the adjacent lines 45 to 48. In FIG. 10, the cut portions C are disposed at positions that differ by 180 degrees between the adjacent lines 49 to 52.
[0041]
FIG. 11 is composed of conductor lines 53 to 56. A gap between the conductor lines 53 to 56 is filled with a dielectric material 33. FIGS. 12 and 13 are each composed of two spiral conductor lines 57 and 58 and conductor lines 59 and 60. The gap between the lines 57 and 58 and the gap between the lines 59 and 60 are filled with a dielectric material 33. FIG. 14 is composed of two U-shaped conductor lines 61 and 62. FIG. 15 shows a further arrangement of a conductor line 63 inside the lines 61 and 62 shown in FIG. A gap between the lines 61 to 63 is filled with a dielectric material 33. FIG. 16 is composed of four substantially annular conductor lines 64 to 67. The cut portions C of the lines 64 to 67 are arranged at positions different by 180 degrees between the adjacent lines 64 to 67. FIG. 17 shows that the pattern cross-sectional area of the central portion where the current density is maximized is increased by making the pattern width of the central portion of each of the conductor lines 68 to 71 wider than the pattern width of the open end portion. Loss is reduced.
[0042]
In FIG. 18, ten substantially ring-shaped conductor lines 72 to 81 having a constant pattern width W are arranged side by side in a region surrounded by a dotted line 82 while maintaining a constant gap width D1. The cut portions C of the lines 72 to 81 are disposed at positions different by 180 degrees between the adjacent lines 72 to 81. The pattern width W and the gap width D1 of the lines 72 to 81 are set to the skin depth dimension. Thereby, a current is shunted to the lines 72 to 81, the edge effect and skin effect of the current are alleviated, and the conductor loss can be further reduced.
[0043]
[Second Embodiment, FIGS. 19 to 26]
In the second embodiment, a resonator having a structure in which a conductor line and a dielectric are stacked on an insulating substrate will be described.
[0044]
As shown in FIG. 19, a U-shaped conductor line 102 is provided on the upper surface of the insulating substrate 101, a ground conductor 106 is provided on the lower surface and the outer peripheral end, and an input terminal 108 and an output terminal 109 are provided on the end. Both end portions 102a and 102b of the line 102 are open ends, and are close to the input terminal 108 and the output terminal 109 with a predetermined gap, respectively, and are capacitively coupled. Further, as shown in FIGS. 20 and 21, a conductor line 103 having the same shape as the line 102 is laminated on the line 102 through a dielectric 104 while being rotated 180 degrees with respect to the line 102.
[0045]
Between the open ends 102a and 102b of the line 102, the central part 103C of the line 103 is disposed. Similarly, a central portion 102 c of the line 102 is disposed between the open ends 103 a and 103 b of the line 103. The open ends 102a and 102b are disposed at positions different from the open ends 103a and 103b by 180 degrees.
[0046]
Thus, the obtained lines 102 and 103 of the resonator R10 are mutually inductively and capacitively coupled in the film thickness direction via the dielectric 104. When a high frequency signal is supplied from the input terminal 108 and the resonator R10 is resonating, the directions of currents flowing in the adjacent lines 102 and 103 are the same. When a current flows in the line 102, electric energy is concentrated and accumulated in the vicinity of the open ends 102a and 102b of the line 102 and the portion sandwiched between the open ends 102a and 102b, and in the vicinity of the central part 102c. Magnetic energy is concentrated and stored. Similarly, when a current flows in the line 103, electric energy is concentrated and accumulated in the vicinity of the open ends 103a and 103b of the line 103 and the portion sandwiched between the open ends 103a and 103b, and the central portion 103c. Magnetic energy is concentrated and accumulated in the vicinity. That is, in the resonator 10 constituted by the two conductor lines 102 and 103, a region where electric energy is concentrated and accumulated and a region where magnetic energy is concentrated are arranged adjacent to each other and dispersed. This reduces the deviation of the magnetic field distribution.
[0047]
In other words, each of the conductor lines 102 and 103 has a sinusoidal current distribution in the longitudinal direction, the amplitude is minimum (node) at the open ends 102a, 102b, 103a, and 103b, and the amplitude at the central portions 102c and 103c. Is the maximum (belly). However, since the open ends 102a and 102b of the line 102 and the central part 103c of the line 103 are adjacently arranged, mutual induction occurs between them. Similarly, since the center portion 102c of the line 102 and the open end portions 103a and 103b of the line 103 are adjacently arranged, mutual induction occurs between them. As a result, the mutual current distribution is transformed from a sinusoidal curve to a curve having a more uniform and smaller amplitude. As a result, the density of the current flowing through the conductor lines 102 and 103 is made uniform, and the conductor loss due to the edge effect and the skin effect can be reduced.
[0048]
Furthermore, by configuring the resonator R10 with the two conductor lines 102 and 103, the resonance frequency can be lowered as compared with the conventional resonator. As a result, the resonator R10 can be downsized by reducing the size of the insulating substrate 101 without increasing the dielectric constant of the insulating substrate 101.
[0049]
Further, as shown in FIG. 22, three gaps 111 are provided at both edge ends of each of the conductor lines 102 and 103 along the edge edges, and the conductor pattern width and gap width of the edge edges are defined as the skin. You may make it set to the dimension below the depth. As a result, a thin conductor pattern is formed at the edge portions of the lines 102 and 103, and current is divided between the thin conductor pattern and the main conductor pattern. As a result, the edge effect and skin effect of the current are alleviated, and the conductor loss can be further reduced.
[0050]
Further, the resonator R10 is constituted by the two conductor lines 102 and 103, in addition to those shown in FIGS. 26 It may be configured by a conductor line shown in FIG. In FIG. 23, the conductor lines 112a and 112b and the conductor lines 113a and 113b are alternately stacked via the dielectrics 104 to form lines 102 and 103 having a multilayer structure (four-layer structure in the case of FIG. 23). . At this time, the film thickness t1 of the lines 112a, 112b, and 113a other than the uppermost line 113b and the film thickness t2 of the dielectric 104 are set to dimensions equal to or less than the skin depth. Thus, by multilayering the lines 102 and 103, the current is divided into the lines 112a and 112b and the lines 113a and 113b. Therefore, the edge effect and skin effect of the current are relaxed also in the film thickness direction of the lines 102 and 103, and the conductor loss can be further reduced.
[0051]
FIG. 24 shows a conductor line 116 having the same shape as the line 115 (see (B) and (C)) on a rectangular substantially annular conductor line 115 (see (A)) having a cut portion C via a dielectric. Are laminated. FIG. 24B shows a case where the cut portion C is disposed at a position that is 90 degrees different between the adjacent lines 115 and 116. FIG. 24C shows a case where the cut portion C is disposed at a position different by 180 degrees between the adjacent lines 115 and 116. In FIG. 24, the cut portions C of the conductor lines 115 and 116 may be formed at square corners, and the shape of the conductor lines 115 and 116 is a substantially circular ring having the cut portions C. There may be.
[0052]
Also, the resonator R11 shown in FIGS. 25 and 26 is the same as the resonator R9 shown in FIG. 6 except that the conductor lines 122a and 122b and the conductor lines 123a and 123b are stacked via the dielectric 124, respectively. In the case of FIG. 26, the lines 22 and 23 have a two-layer structure). The lines 122a and 122b have the same shape pattern, and the lines 123a and 123b also have the same shape pattern. At this time, the film thickness t1 of the lines 122a and 123a other than the uppermost lines 122b and 123b and the film thickness t2 of the dielectric 124 are set to dimensions equal to or smaller than the skin depth. Thus, by making the conductor lines 22 and 23 multilayer, the current is shunted to the lines 122a and 122b and the lines 123a and 123b. Therefore, the edge effect and skin effect of the current are also reduced in the film thickness direction of the lines 22 and 23, and the conductor loss can be further reduced.
[0053]
[Third Embodiment, FIGS. 27 and 28]
The third embodiment shows an embodiment of a filter according to the present invention, and will be described by taking a three-stage bandpass filter as an example.
[0054]
As shown in FIGS. 27 and 28, the band-pass filter 131 has three resonators R8 shown in FIG. 5B arranged in parallel on the upper surface of the insulating substrate 132. Further, an input terminal 135 is provided at the left end portion of the insulating substrate 132, and the input terminal 135 is brought close to the open end portion of the conductor line 14 of the resonator R8 disposed on the left side of the substrate 132 to be capacitively coupled. Similarly, an output terminal 136 is provided at the right end portion of the substrate 132, and this output terminal 136 is brought close to the open end portion of the conductor line 14 of the resonator R 8 disposed on the right side of the substrate 132 to be capacitively coupled. The insulating substrate 132 is accommodated in the shielding case 137. The bandpass filter 131 obtained in this way has a small insertion loss and can be miniaturized.
[0055]
[Fourth Embodiment, FIG. 29]
The fourth embodiment shows an embodiment of a duplexer (antenna duplexer) according to the present invention. As shown in FIG. 29, in the duplexer 141, the transmission filter 142 is electrically connected between the transmission terminal Tx and the antenna terminal ANT, and the reception filter 143 is electrically connected between the reception terminal Rx and the antenna terminal ANT. ing. Here, as the transmission filter 142 and the reception filter 143, the filter 131 of the third embodiment can be used. By mounting this filter 131, it is possible to realize a duplexer 141 that has a small insertion loss and can be miniaturized.
[0056]
[Fifth Embodiment, FIG. 30]
5th Embodiment shows one Embodiment of the communication apparatus which concerns on this invention, and demonstrates it taking a mobile phone as an example.
[0057]
FIG. 30 is an electric circuit block diagram of an RF transmission / reception portion of the mobile phone 150. In FIG. 30, 151 is an antenna element, 152 is an antenna duplexer, 153 is a receiving circuit, and 154 is a transmitting circuit. Here, the duplexer 141 of the fourth embodiment can be used as the antenna duplexer 152. By mounting the duplexer 141, the insertion loss of the RF transmission / reception portion is reduced, and the communication quality such as the noise characteristics and transmission speed of the mobile phone 150 can be improved.
[0058]
[Other Embodiments]
The resonator, the filter, the duplexer, and the communication device according to the present invention are not limited to the above embodiment, and can be variously modified within the scope of the gist.
[0059]
In the above-described embodiment, the cut portions C are disposed at positions that are different by 90 degrees or 180 degrees between adjacent conductor lines. However, the present invention is not limited to this, and the cut portions C are positions at different angles. Can be arranged.
[0060]
Furthermore, at least one of the conductor lines may be made of a superconductor. In the present invention, since current concentration is reduced in each part of the line, the critical current density required to maintain the current density in a superconducting state even for a line with a narrow pattern width (small cross-sectional area). The conductor line made of a superconductor can be easily kept in a superconducting state. The superconductor is preferably a high-temperature superconductor such as yttrium or bismuth.
[0061]
In addition to the microstrip line, the conductor line according to the present invention is a well-known coplanar guide, slot guide, planar dielectric line (see JP-A-8-265007), suspended strip, fin line, strip line, asymmetrical. Includes stripline, triplate line, parallel stripline, etc.
[0062]
【The invention's effect】
As is apparent from the above description, according to the present invention, a resonator is composed of an insulating member and a plurality of conductor lines each having open ends, and the open ends of the conductor lines are arranged at different positions. Thus, the region where electrical energy is stored and the region where magnetic energy is stored are dispersed in the insulating member, and the deviation of the magnetic field distribution is reduced. Therefore, the density of the current flowing in the conductor line is made uniform, and the conductor loss due to the edge effect and the skin effect can be reduced. Furthermore, by configuring the resonator with a plurality of conductor lines, the resonance frequency of the resonator can be lowered, and the size of the insulating member can be reduced without increasing the dielectric constant of the insulating member. The size of the resonator can be reduced.
[Brief description of the drawings]
FIG. 1 is a current and magnetic field distribution diagram for explaining the principle of a resonator according to the present invention.
FIG. 2 is a current and magnetic field distribution diagram for explaining the principle of the resonator according to the present invention.
FIG. 3 is a plan view of a resonator provided with different conductor lines for explaining the principle of the resonator according to the present invention, wherein (A), (B), (C), and (D) are different from each other.
4 is a graph showing a resonance frequency characteristic of each resonator shown in FIG. 3;
FIGS. 5A and 5B are plan views of a resonator provided with another conductor line for explaining the principle of the resonator according to the present invention. FIGS.
FIG. 6 is a perspective view showing a first embodiment of a resonator according to the invention.
7A is an enlarged longitudinal sectional view of a conductor line of the resonator shown in FIG. 6, and FIG. 7B is an enlarged longitudinal sectional view of another conductor line.
8 is a plan view of still another conductor line of the resonator shown in FIG. 6. FIG.
9 is a plan view of still another conductor line of the resonator shown in FIG. 6. FIG.
10 is a plan view of still another conductor line of the resonator shown in FIG. 6. FIG.
11 is a plan view of still another conductor line of the resonator shown in FIG. 6. FIG.
12 is a plan view of still another conductor line of the resonator shown in FIG. 6. FIG.
13 is a plan view of still another conductor line of the resonator shown in FIG. 6. FIG.
14 is a plan view of still another conductor line of the resonator shown in FIG. 6. FIG.
15 is a plan view of still another conductor line of the resonator shown in FIG. 6;
16 is a plan view of still another conductor line of the resonator shown in FIG. 6;
17 is a plan view of still another conductor line of the resonator shown in FIG. 6;
18 is a plan view of still another conductor line of the resonator shown in FIG. 6;
FIG. 19 is a perspective view showing a second embodiment of a resonator according to the invention.
20 is a perspective view showing a manufacturing procedure following FIG. 19. FIG.
21 is an enlarged longitudinal sectional view of a conductor line of the resonator shown in FIG.
22 is an enlarged longitudinal sectional view of another conductor line of the resonator shown in FIG. 20;
FIG. 23 is an enlarged vertical sectional view of still another conductor line of the resonator shown in FIG. 20;
24 is a plan view of still another conductor line of the resonator shown in FIG. 20. FIG.
FIG. 25 is a perspective view showing still another embodiment of the resonator according to the invention.
26 is an enlarged longitudinal sectional view of a conductor line of the resonator shown in FIG. 25. FIG.
FIG. 27 is an internal plan view showing one embodiment of a filter according to the present invention.
FIG. 28 is a longitudinal sectional view of the filter shown in FIG.
FIG. 29 is an electric circuit block diagram showing an embodiment of a duplexer according to the present invention.
FIG. 30 is an electric circuit block diagram showing an embodiment of a communication device according to the present invention.
[Explanation of symbols]
2, 3 ... Conductor line
2a, 2b, 3a, 3b ... open end
7-14 ... conductor line
21 ... Insulating substrate
22, 23 ... Conductor line
22a, 22b, 23a, 23b ... open end
25 ... Ground conductor
28 ... Input terminal
29 ... Output terminal
31 ... Gap
33 ... Dielectric material
41-81 ... Conductor line
101 ... Insulating substrate
102, 103 ... Conductor line
102a, 102b, 103a, 103b ... open end
104: Dielectric
106: Ground conductor
108: Input terminal
109 ... Output terminal
111 ... Gap
112a, 112b, 113a, 113b ... conductor line
115, 116 ... Conductor line
122a, 122b, 123a, 123b ... conductor lines
33 ... Dielectric material
131 ... Filter
132. Insulating substrate
135: Input terminal
136 ... Output terminal
137 ... Shielding case
141 ... Duplexer
142 ... transmission filter
143: Reception filter
150 ... mobile phone
151. Antenna element
152 ... Antenna duplexer
153 ... Receiving circuit
154: Transmitter circuit
R2, R5-R11 ... Resonator
C ... Cutting part
D ... Gap
W: Pattern width
D1 ... Gap width
t1: Conductor line thickness
t2: Dielectric film thickness
ANT ... antenna terminal
Tx: Transmission terminal
Rx: Receive terminal

Claims (11)

An insulating member;
A plurality of conductor lines provided on the insulating member and having a curved portion and electromagnetically coupled to each other;
Both ends of the conductor line are open ends, the open ends are disposed at different positions in the same plane, and the shape of the conductor line is a substantially ring shape having a cut portion ,
A resonator characterized by. Resonator according to claim 1, wherein the cutting portion, characterized in that disposed 180 degrees different positions between adjacent conductor lines mutually of the conductor line. The edge portion of the conductor line is provided with at least one gap along the edge portion, and the conductor pattern width and the gap width of the edge portion are set to substantially the skin depth dimension. The resonator according to claim 1 or 2 . The conductor line is configured by arranging a plurality of linear conductors with a gap, and a conductor pattern width of the linear conductor and a width of the gap are set to approximately a skin depth dimension. The resonator according to claim 1 or 2 . The conductor lines are stacked through a thin film dielectric, the uppermost conductor line is left, and the film thickness of the remaining conductor lines and the film thickness of the thin film dielectric are set to dimensions of the skin depth or less. The resonator according to any one of claims 1 to 4, characterized in that: 6. The resonator according to claim 5, wherein all the conductor lines have the same shape pattern. The resonator according to any one of claims 1 to 6, characterized in that filled with dielectric material in the gap between the conductor line adjacent in the same plane. The resonator according to any of claims 1 to claim 7, characterized in that at least one of said conductor line is a superconductor. Filter, characterized in that it comprises at least one of claims 1 to resonator according to claim 8. A duplexer comprising the filter according to claim 9 . A communication apparatus comprising at least one of the filter according to claim 9 or the duplexer according to claim 10 .

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