JP3567928B2 - Noise suppression device - Google Patents

Description

[0001]
TECHNICAL FIELD OF THE INVENTION
The present invention relates to an FM receiver that suppresses pulse noise (hereinafter, referred to as pulse noise) due to electromagnetic wave noise such as electric mirror noise generated at the time of FM reception and obtains a good output audio signal.
[0002]
[Prior art]
In an automobile environment, pulsed electromagnetic wave noise such as ignition noise and mirror noise is generated. Since the pulsed electromagnetic wave noise is mixed into the antenna of the car radio, the pulsed noise is also generated in the audio signal obtained by demodulating the FM signal. For this reason, a pulse noise suppression device is generally used in a car radio.
[0003]
FIG. 13 is a block diagram of a pulse noise suppressing device in a conventional FM receiver described in, for example, JP-A-63-87026. In the figure, 1 is an FM demodulation circuit, 2 is a delay circuit, 3 is a gate circuit, 4 is a level hold circuit, 5 is a stereo demodulation circuit, 6 is an HPF (high-pass filter) for noise detection, 7 is a noise amplifier, and 8 is a noise amplifier. A noise detection circuit, 9 is a waveform shaping circuit, 10 is an integration circuit, 11 is a noise detection circuit, and 14 is a previous value holding type correction circuit.
[0004]
When the FM intermediate frequency signal of the FM receiver is input to the FM demodulation circuit 1, an FM demodulated signal is output. This FM demodulated signal is supplied to a delay circuit 2 composed of an LPF (low-pass filter) and is delayed. The output of the delay circuit 2 is supplied to a stereo demodulation circuit 5 via a gate circuit 3 and a level hold circuit 4, and the Lch and The Rch audio signal is separated and output. The delay circuit 2 is provided to compensate for the time from when the pulse noise described later is supplied to the HPF 6 to when the gate circuit 3 is turned off.
[0005]
The FM demodulated signal is supplied to a noise detection HPF 6, and a noise component signal extracted by the HPF 6 is amplified by a noise amplifier 7 and supplied to a noise detection circuit 8. The noise detection circuit 8 is composed of a rectifier circuit that rectifies the output signal of the noise amplifier 7, and this noise detection output is supplied to a waveform shaping circuit 9 and an integration circuit 10. The waveform shaping circuit 9 converts the noise detection output into a correction period signal having a pulse width of a predetermined time and supplies the signal to the gate circuit 3. The gate circuit 3 is driven by the correction period signal supplied from the waveform shaping circuit 9 to the gate circuit 3 to be in a signal cutoff state. In the signal cutoff state, the delay output level before the signal cutoff is held by the level hold circuit 4 for stereo. The signal is supplied to the demodulation circuit 5.
[0006]
As described above, the noise period t1 portion of the demodulated signal as shown in FIG. 14A is interpolated by the correction value signal shown in FIG. 14B by the preceding value as shown in FIG. The occurrence of a spike due to a sudden change in is prevented. When the noise detection pulse is not supplied from the waveform shaping circuit 9, the gate circuit 3 and the level hold circuit 4 enter a through state.
[0007]
In addition, the noise detection output is smoothed by the integration circuit 10 to obtain a DC signal corresponding to the noise level, and the DC signal is fed back to the noise amplifier 7 to form an AGC loop. I try to lower the gain.
[0008]
[Problems to be solved by the invention]
In the above configuration, the correction error becomes large because the previous value hold is used for the correction of the pulse noise. Therefore, it is conceivable to perform a linear interpolation as shown in FIG. 14D on the signal after the stereo demodulation to reduce the correction error.
[0009]
However, in the generation of the noise detection pulse by the noise detection circuit 11 having the above-described configuration, when the period of the generated pulse noise is long, the output signal of the integration circuit 10 increases and the gain of the noise amplifier 7 decreases. Go. Therefore, the amplitude of the pulse noise at the output of the noise amplifier 7 becomes smaller, and the pulse noise is no longer detected. Therefore, when the pulse noise generation period is long, the pulse noise detection period is shorter than the actual noise generation period. That is, the noise detection pulse obtained from the waveform shaping circuit 9 may be shorter than the actual noise generation period.
[0010]
FIG. 15 shows an example in which the FM demodulation signal is corrected by linear interpolation using a noise detection pulse shorter than the actual noise generation period as described above. As shown in FIG. 15C, the value at the end of the correction period used for linear interpolation includes pulse noise, so that not only a sufficient correction cannot be performed, but also a large correction error may occur.
[0011]
The present invention has been made in view of the above, and has as its object to reduce a correction error when a pulse noise generation period is long.
[0012]
[Means for Solving the Problems]
2. The noise suppression device according to claim 1, wherein the noise detection unit detects a noise generation period from the FM demodulation signal and outputs a correction period signal, and based on the correction period signal, the FM demodulation signal in the noise generation period. Value correction method using a signal immediately before the noise occurrence period, and an interpolation correction of the FM demodulation signal in the noise occurrence period using signals before and after the noise occurrence period based on the correction period signal. Interpolation method correcting means, a correction method determining means for determining selection of the previous value holding method when it is determined that the correction period signal is shorter than an actual noise occurrence period, and an output of the correction method determining means. And a correction method selection means for selecting one of the preceding value holding method correction means and the interpolation method correction means in response.
[0013]
According to a second aspect of the present invention, in the noise suppression apparatus according to the first aspect, the correction method determining unit determines that an absolute value of a difference between the FM demodulated signal corresponding to the start end and the end of the correction period signal is the FM demodulated signal. Is determined to be shorter than the actual noise occurrence period when the average amplitude is larger than the average amplitude of the noise.
[0014]
According to a third aspect of the present invention, there is provided the noise suppressing apparatus according to the second aspect, wherein the correction method determining unit determines an absolute value of a difference between a high-frequency component of the FM demodulated signal corresponding to a start end and an end of the correction period signal. Is larger than the average amplitude of the high frequency component of the FM demodulated signal, it is determined that the correction period signal is shorter than the actual noise generation period.
[0015]
According to a fourth aspect of the present invention, there is provided the noise suppression apparatus according to the second aspect, wherein the correction method determination unit performs correction in any one of high-frequency components of the FM demodulated signal divided into a plurality of bands. When the absolute value of the difference between the high frequency components of the FM demodulated signal corresponding to the start and end of the period signal is larger than the average amplitude of the high frequency component of the FM demodulated signal, the correction period signal is shorter than the actual noise generation period. Is determined.
[0016]
The noise suppression device according to claim 5, further comprising: noise detection means for detecting a noise generation period from the FM demodulated signal to output a correction period signal; an FM demodulation signal corresponding to a start end of the correction period signal; When the absolute value of the difference between the FM demodulated signals after the end of the period becomes smaller than the average amplitude of the FM demodulated signal, a correction period determining means for outputting a determination signal indicating the end of the noise generation period; Until the determination signal is output, the correction period correction unit that extends the correction period signal to output a correction correction period signal, and, based on the correction correction period signal, converts the FM demodulation signal of the noise occurrence period into the correction period signal. An interpolation method correcting means for performing interpolation correction using signals before and after the noise occurrence period is provided.
[0017]
According to a sixth aspect of the present invention, in the noise suppressor according to the fifth aspect, the correction period determination unit determines an absolute value of a difference between a high-frequency component of the FM demodulated signal corresponding to a start end and an end of the correction period signal. At the time when the amplitude becomes smaller than the average amplitude of the high frequency component of the FM demodulated signal, a determination signal for ending the noise generation period is output.
[0018]
According to a seventh aspect of the present invention, in the noise suppression apparatus according to the fifth aspect, the correction period determination unit performs correction in any one of high-frequency components of the FM demodulated signal divided into a plurality of bands. When the absolute value of the difference between the high-frequency components of the FM demodulated signal corresponding to the beginning and the end of the period signal becomes smaller than the average amplitude of the high-frequency components of the FM demodulated signal, a determination signal of the end of the noise generation period is output. It is characterized by doing.
[0019]
BEST MODE FOR CARRYING OUT THE INVENTION
Hereinafter, the present invention will be specifically described with reference to the drawings showing the embodiments.
[0020]
Embodiment 1 FIG.
FIG. 1 is a block diagram of a pulse noise suppression device in an FM receiver according to a first embodiment of the present invention. In FIG. 1, reference numeral 1 denotes an FM demodulation circuit, 5 denotes a stereo demodulation circuit, and 14 denotes a correction of a previous value holding system. Reference numeral 21 denotes a noise detection circuit, 22 denotes a correction method determination circuit, 23 denotes a linear interpolation method correction circuit, and 24 denotes a switch circuit. The same parts as those in FIG. 13 will not be described repeatedly.
[0021]
FIG. 2 is a block diagram showing an example of the detection circuit 21. In the drawing, 26 is an HPF, 27 is an absolute value circuit, 28 is an LPF, 29 is a multiplication circuit, 30 is a comparison circuit, and 31 is a correction period generation circuit. It is.
[0022]
The component of the pulse noise included in the FM demodulated signal is distributed over a wide range, and the component of the pulse noise is outside the band in which the frequency component necessary for the FM demodulated signal or the output audio signal is distributed. Exists. Therefore, the HPF 26 extracts a high-frequency component of the FM demodulated signal as a noise component including a pulse noise component. FIG. 3A shows an FM demodulated signal input to the HPF 26, and FIG. 3B shows an output signal of the HPF 26. In FIG. 3A, pulse noise is generated during a period t1. FIG. 3B shows a state in which the pulse noise is extracted.
[0023]
Next, the absolute value circuit 27 obtains the absolute value of the output signal of the HPF 26. FIG. 3C shows an output signal of the absolute value circuit 27. When the output signal of the absolute value circuit 27 is larger than the threshold value output from the multiplication circuit 29, the comparison circuit 30 determines that pulse noise has occurred and sends a correction period signal to the correction period generation circuit 31.
[0024]
Here, the threshold value output from the multiplication circuit 29 will be described. The FM-demodulated signal contains background noise and circuit noise (hereinafter referred to as floor noise) in addition to pulse noise. Since the automobile usually moves, the reception state of the FM broadcast signal changes every moment, and the level of the floor noise also changes every moment.
[0025]
If the pulse noise is smaller than the floor noise, the noise is masked by the floor noise and is difficult to hear. If a threshold smaller than the floor noise is set, the floor noise is erroneously determined as pulse noise. Therefore, a threshold is generally determined based on floor noise. Since floor noise is so-called random noise, it does not have a strong high-frequency component and is widely distributed in all bands. Therefore, a signal obtained by extracting a low-frequency component from the output of the absolute value circuit 27 by the LPF 28 is set as a signal proportional to the magnitude of the floor noise, and the output signal of the LPF 28 is multiplied by a coefficient by the multiplication circuit 29 to be a threshold.
[0026]
The comparison circuit 30 compares the output signal of the absolute value circuit 27 with the threshold value output from the multiplication circuit 29, and determines that pulse noise has occurred when the output signal of the absolute value circuit 27 is larger. However, since the pulse noise may be momentarily smaller than the threshold value, the output signal of the comparison circuit 30 may not be continuous in the period t1 in which the pulse noise occurs as shown in FIG.
[0027]
Since pulse noise is generated in the period t1, it is necessary to correct the entire period of the period t1. Therefore, when the detection interval of the pulse noise is short as in the period t1 in FIG. 3D, the correction period generating circuit 31 outputs the continuous correction period signal as in the period t1 in FIG. I'm doing a get. By this processing, a correction period signal that is continuous in the pulse noise generation period t1 is obtained as shown in FIG. The above is the operation of the noise detection circuit 21.
[0028]
Next, the correction period signal may be shorter than the pulse noise generation period t1, which will be described. As described above, the absolute value of the output signal of the HPF 26 is obtained by the absolute value circuit 27 to obtain a signal as shown in FIG. 3 (c). Further, when the signal passes through the LPF 28, the output of the LPF 28 becomes as shown in FIG. To gradually increase. That is, if the period of occurrence of the pulse noise is long, the output signal of the LPF 28 gradually increases due to the pulse noise instead of the floor noise, and the threshold value gradually increases. Therefore, the pulse noise is not detected on the side near the end point of the pulse noise generation period t1, and the correction period signal may be shorter than the pulse noise generation period t1 as shown in FIG.
[0029]
FIG. 15 shows an example in which the pulse noise portion is linearly interpolated in a state where the correction period signal is shorter than the pulse noise generation period t1 (hereinafter, referred to as a short correction period signal). When the FM demodulation signal including the pulse noise shown in FIG. 15A is linearly interpolated with the short correction period signal shown in FIG. 15B, the end of the linear interpolation part ends with the pulse noise as shown in FIG. Therefore, the correction error increases, and further, after the end of the short correction period signal, pulse noise is output without any processing.
[0030]
FIGS. 4A and 4B show an example of correction by the linear interpolation method and the previous value holding method when the correction period signal is shorter than the pulse noise generation period. However, there is little adverse effect due to the correction. For this purpose, the correction method determination circuit 22 determines the magnitude relationship between the pulse noise generation period and the correction period signal, and selects the previous value holding method when the correction period signal is shorter, and selects the linear interpolation method when the correction period signal is longer. Outputs the system selection signal.
[0031]
Hereinafter, the operation of the correction method determination circuit 22 will be described. When the correction period signal is shorter than the pulse noise generation period as shown in FIG. 5C with respect to the FM demodulation signal shown in FIG. 5A, the FM demodulation signal at the end of the correction period signal has a pulse. Sexual noise is present. For this reason, there is a problem that the difference (| S−E1 |) between the FM demodulated signal values at the start point and the end point of the correction period becomes large. Conversely, if the correction period signal correctly corresponds to the pulse noise generation period, the difference (| S−E2 |) between the values of the FM demodulation signal at the start point and the end point of the correction period is equal to the average FM demodulation signal. Should be less than the amplitude level. Therefore, if the difference | SE | between the FM demodulated signal at the end point and the start point is larger than the average FM demodulated signal (| S-E1 | in the figure), the correction width is short and pulse noise is generated. You may have. That is, it is determined that the correction period signal is shorter than the pulse noise generation period.
[0032]
FIG. 6 is a diagram showing a configuration example of the correction method determination circuit 22, and its operation will be described with reference to FIG. In the figure, 32 and 33 are hold circuits, 34 is a subtraction circuit, 35 is an absolute value circuit, 36 is a level detection circuit composed of an absolute value circuit 37 and an LPF 38, and 39 is a judgment circuit.
[0033]
Hereinafter, the operation will be described. 6, the FM demodulation signal and the correction period signal are input to the hold circuits 32 and 33, the value S of the FM demodulation signal at the rising portion of the correction period signal is input to the hold circuit 32, and the falling portion is input to the hold circuit 33. (E1 or E2 in FIG. 5A) is held. Next, (SE) is calculated by the subtraction circuit 34, and the magnitude of (SE) is obtained by the absolute value circuit 35.
[0034]
In the level detection circuit 36, an FM demodulation signal indicating an average amplitude of the FM demodulation signal from which the pulse noise component is removed as shown in FIG. The level detection signal P is obtained.
[0035]
Next, a case where the correction period signal is shorter than the pulse noise generation period t1 as shown in FIG. Due to the pulse noise, the value of the FM demodulation signal at the start point of the correction period is S, and the value at the end point is E1. In this case, the difference (S-E1) between the values of the FM demodulated signal may be larger than the value P of the FM demodulated signal level detection signal.
[0036]
Next, the judgment circuit 39 compares the output | S-E1 | of the subtraction circuit obtained by the absolute value circuit 35 with the level detection signal output P of the level detection circuit 36. If (S-E1)> P, the correction period signal Is shorter than the pulse noise generation period t1.
[0037]
When the correction period signal is not shorter than the pulse noise generation period as shown in FIG. 5D, the value P of the FM demodulated signal level detection signal is larger than the output signal | S−E2 | of the absolute value circuit 35. Therefore, the determination circuit 39 does not determine that the correction period signal is shorter than the pulse noise generation period t1 if (SE2) <P.
[0038]
As described above, the correction method determination circuit 22 shown in FIG. 6 can detect a case where the correction period signal is shorter than the pulse noise generation period.
[0039]
Therefore, as shown in FIG. 4, when the correction period signal is shorter than the pulse noise generation period, the correction error is smaller in the previous value holding method than in the linear interpolation method. If it is determined that the signal is shorter than the pulse noise generation period, a correction method selection signal for selecting the previous value holding method is output, and the FM demodulated signal containing the pulse noise is corrected by the previous value holding method correction circuit 14. I do.
[0040]
Embodiment 2 FIG.
FIG. 7 is a block diagram of a noise suppressing apparatus according to Embodiment 2 of the present invention. In the figure, 1 is an FM demodulation circuit, 5 is a stereo demodulation circuit, 14 is a previous value holding type correction circuit, 21 is a noise detection circuit, 22 is a correction type determination circuit, 23 is a linear interpolation type correction circuit, 24 is a switch circuit, 40 is a filter. The same parts as those in FIG. 1 will not be described repeatedly.
[0041]
In FIG. 7, the low frequency component of the FM demodulated signal is suppressed by using a high pass filter (HPF) as the filter 40, and then input to the correction method determination circuit 22. Since the pulse noise contains many high-frequency components, the attenuation of the pulse noise by the filter 40 is small. Further, since the floor noise component is widely distributed in the entire band, a signal mainly including the high frequency component of the floor noise and the pulse noise is input to the correction method determination circuit 22.
[0042]
FIGS. 8A and 8B show examples of the input signal and the output signal waveform of the filter 40 (HPF) when the pulse noise occurs during the period of t1, and the ratio of the pulse noise becomes large in the output signal. It can be seen that the low frequency component is attenuated. When this output signal is input to the correction method determination circuit 22, the output level P of the level detection circuit 36 in FIG. 6 is mainly an average level of floor noise. The level P is used to prevent erroneous determination of the floor noise as pulse noise when the floor noise is large. On the other hand, since the suppression of the pulse noise by the filter 40 is small, when the correction period signal is short, the hold circuit 32 holds the level of a portion having no pulse noise and having a small amplitude mainly composed of floor noise. 33 holds the level of the pulse noise portion, the output | SE− | of the absolute value circuit 35 is larger than the output of the level detection circuit 36.
[0043]
As described above, since the signal obtained by attenuating the low-frequency component (mainly the regular audio signal) of the FM demodulated signal is used as the input of the correction method determination circuit 22, the two input signals | S of the determination circuit 39 are used. -E | and P contain almost no audio signal. For this reason, the determination of the magnitude relationship between the pulse noise generation period and the correction period signal is less likely to be affected by the audio signal, thereby improving the accuracy of the correction method determination.
[0044]
Further, the signal is divided into a plurality of bands by the filter 40, and the magnitude relation between the pulse noise generation period and the correction period signal is determined for each band in the correction method determination circuit 22. When it is determined that the period is shorter than the period of occurrence of the pulse noise, the correction by the previous value holding method may be selected. This processing increases the possibility of detecting even when the pulse noise is biased to a specific frequency component, and improves the accuracy of the determination of the correction method selection.
[0045]
Embodiment 3 FIG.
In the third embodiment, when the correction period signal is shorter than the pulse noise generation period included in the input signal, the correction is performed such that the correction period signal matches the pulse noise generation period (hereinafter, the correction period signal generation period). Correction) is performed so that no pulse noise remains in the corrected FM demodulated signal.
[0046]
FIG. 9 shows a block diagram of the third embodiment. In the figure, 1 is an FM demodulation circuit, 5 is a stereo demodulation circuit, 21 is a noise detection circuit, 23 is a linear interpolation type correction circuit, 25 is a correction period determination circuit for determining the validity of a correction period signal, and 41 is a correction period correction Circuit. 1 and FIG. 7 will not be described repeatedly.
[0047]
The noise detection circuit 21 detects pulse noise included in the FM demodulated signal and outputs a correction period signal. As described above, when the pulse noise generation period is long, the pulse noise is detected and obtained. The correction period signal may be shorter than the actual pulse noise. In FIG. 9, the state of the pulse noise is continuously monitored by the correction period determination circuit 25 even after the end of the correction period signal by the noise detection circuit 21, and a determination signal about the presence or absence of the pulse noise is output. To correct the correction period signal.
[0048]
The correction period correction circuit 41 sets a correction period signal for controlling the linear interpolation type correction circuit 23 based on the correction period signal output from the noise detection circuit 21, and ends the correction period signal output from the correction period determination circuit 25. An operation is performed to reset the correction correction period signal in accordance with a subsequent determination signal indicating no pulse noise.
[0049]
FIG. 10 shows a configuration example of the correction period determination circuit 25. The FM demodulated signal input to FIG. 10 is digitized by the A / D converter 42. The memory 43 discards the oldest data every time the A / D converter 42 samples new data and accumulates new data, and the control circuit 44 stores the data immediately before the rising of the correction correction period signal output from the correction period correction circuit 41. Is stored in the memory 43 as data S. Further, data during the duration of the correction correction period signal is stored in the memory 43 one by one as data E. Further, | SE | is calculated by the subtraction circuit 45 and the absolute value circuit 46.
[0050]
The level detection circuit 47 includes an absolute value circuit 47a and an LPF 47b, and obtains an average amplitude P of the FM demodulated signal. The judging circuit 48 compares the output signal | SE | of the absolute value circuit 46 with the output P of the level detecting circuit 47. If | SE |> P, the pulse noise generation period has not ended. Is output as a signal indicating pulse noise (for example, “1”). If | SE | <= P, a determination signal (for example, “0”) indicating no pulse noise is output as a signal indicating that the pulse noise generation period has ended.
[0051]
Since the correction period determination circuit 25 operates as described above, it is possible to make the correction correction period signal output from the correction period correction circuit 41 coincide with the pulse noise generation period.
[0052]
The linear interpolation type correction circuit 23 corrects a pulse noise generation portion in the FM demodulated signal by linear interpolation using the correction correction period signal.
[0053]
FIG. 11 shows an example of a correction waveform by linear interpolation. In the figure, (a) shows a correction period signal shorter than the pulse noise generation period, and (b) shows a correction waveform using the correction correction period signal. It can be seen that good linear interpolation has been realized.
[0054]
As described above, after detecting the pulse noise generation period, a change in the FM demodulation signal is detected based on the value of the FM demodulation signal at the start point of the correction period, and the change value is an average FM demodulation signal in the vicinity thereof. The range exceeding the amplitude is determined as the pulse noise generation period, and the FM demodulation signal is corrected by obtaining the correction correction period signal that matches the pulse noise generation period, so that the pulse noise generation portion can be corrected correctly. .
[0055]
Embodiment 4 FIG.
FIG. 12 is a block diagram of a noise suppressing apparatus according to Embodiment 4 of the present invention. In the figure, 1 is an FM demodulation circuit, 5 is a stereo demodulation circuit, 21 is a noise detection circuit, 23 is a linear interpolation type correction circuit, 25 is a correction period determination circuit, 40 is a filter, and 41 is a correction period correction circuit. The same parts as those in FIGS. 7 and 9 will not be described.
[0056]
12, the low frequency component of the FM demodulated signal is suppressed using an HPF (high pass filter) as the filter 40 and then input to the correction period determination circuit 25. Since the pulse noise contains many high-frequency components, the attenuation of the pulse noise by the filter 40 is small. Therefore, a signal mainly including pulse noise is input to the correction period determination circuit 25.
[0057]
FIG. 8 shows the input signal and output signal waveform of the filter 40 when the pulse noise occurs during the period of t1. In FIG. 8B, the ratio of the pulse noise is large, and the low-frequency component is attenuated. When the output signal of the filter 40 is input to the correction period determination circuit 25, the output level P of the level detection circuit 47 in FIG.
[0058]
On the other hand, since the suppression of the pulse noise by the filter 40 is small, the data S at the start point of the correction period stored in the memory 43 is a value of a portion where there is no pulse noise and the amplitude is extremely small. The value of the output | SE | of the absolute value circuit 46 greatly differs depending on whether or not it is the value of the pulse noise portion during the lifetime of the signal. This makes it extremely easy for the correction period determination circuit 25 to determine the validity of the correction period signal.
[0059]
As described above, since the signal obtained by attenuating the low-frequency component (mainly the normal audio signal) of the FM demodulated signal is used as the input of the correction period determination circuit 25, the two input signals | S of the determination circuit 48 are used. -E | and P contain almost no audio signal. For this reason, the determination of the magnitude relationship between the pulse noise generation period and the correction period signal is less likely to be affected by the audio signal, thereby improving the accuracy of the correction method determination.
[0060]
Further, the signal is divided into a plurality of bands by the filter 40, and the presence or absence of the pulse noise is detected for each band in the correction period determination circuit 25, and the correction period signal is detected in a range where the pulse noise is continuously detected in any band. May be extended to obtain a correction correction period signal. This processing increases the possibility that the validity of the correction period signal can be correctly determined even when the pulse noise is biased to a specific frequency component, and improves the correction accuracy of the correction period signal.
[0061]
It is needless to say that the circuits described in the first to fourth embodiments may be incorporated in an integrated circuit or may be realized by software of a microprocessor.
[0062]
【The invention's effect】
As described above, according to the present invention, the following effects can be obtained.
[0063]
According to the first aspect of the present invention, when it is determined that the correction period signal obtained by the noise detection unit is shorter than the actual noise generation period, the correction period signal is shorter than the actual noise generation period. Since the FM demodulated signal in the noise generation period is corrected by the previous value holding method in which the occurrence of the correction error is small, the FM demodulated signal with the small correction error can be obtained.
[0064]
3. The noise suppression device according to claim 2, wherein the correction period signal has an actual noise generation period when the absolute value of the difference between the FM demodulation signal corresponding to the start and end of the correction period signal is larger than the average amplitude of the FM demodulation signal. Since it is determined to be shorter, it is easy to determine the validity of the correction period signal.
[0065]
4. The noise suppression device according to claim 3, wherein the absolute value of the difference between the high frequency components of the FM demodulated signal corresponding to the start and end of the correction period signal is larger than the average amplitude of the high frequency components of the FM demodulated signal. Since it is determined that the period signal is shorter than the actual noise generation period, the accuracy of determining the validity of the correction period signal is improved without being affected by the FM demodulated signal.
[0066]
According to a fourth aspect of the present invention, in any one of the high-frequency components of the FM demodulated signal divided into a plurality of bands, the difference between the high-frequency component of the FM demodulated signal corresponding to the start and end of the correction period signal is determined. If the absolute value is larger than the average amplitude of the high frequency component of the FM demodulated signal, the correction period signal is determined to be shorter than the actual noise generation period. Accurate determination of the validity of the signal can be obtained.
[0067]
The absolute value of the difference between the FM demodulation signal corresponding to the beginning of the correction period signal and the FM demodulation signal after the end of the correction period signal is smaller than the average amplitude of the FM demodulation signal. Since the interpolation correction is performed using the corrected correction period signal obtained by extending the correction period signal up to the point in time, excellent interpolation correction of the FM demodulated signal can be performed.
[0068]
7. The noise suppression device according to claim 6, wherein the absolute value of the difference between the high-frequency components of the FM demodulated signal corresponding to the start and end of the correction period signal becomes smaller than the average amplitude of the high-frequency components of the FM demodulated signal. Since the interpolation correction is performed using the corrected correction period signal obtained by extending the correction period signal up to this point, it is possible to perform more excellent interpolation correction of the FM demodulated signal.
[0069]
The noise suppression device according to claim 7, wherein in any one of the high-frequency components of the FM demodulated signal divided into a plurality of bands, the difference between the high-frequency component of the FM demodulated signal corresponding to the start end and the end of the correction period signal. Interpolation correction is performed using the corrected correction period signal obtained by extending the correction period signal until the absolute value becomes smaller than the average amplitude of the high frequency component of the FM demodulated signal. , Good interpolation correction of the FM demodulated signal is possible.
[Brief description of the drawings]
FIG. 1 is a block diagram illustrating a configuration of a noise suppression device according to a first embodiment.
FIG. 2 is a block diagram illustrating a configuration of a noise detection circuit according to the first embodiment.
FIG. 3 is a diagram illustrating an operation of the noise detection circuit according to the first embodiment.
FIG. 4 is a diagram illustrating correction of a linear interpolation method and correction of a previous value holding method using a short correction period signal.
FIG. 5 is a diagram illustrating the operation of the correction method determination circuit according to the first embodiment.
FIG. 6 is a block diagram illustrating a configuration of a correction method determination circuit according to the first embodiment.
FIG. 7 is a block diagram illustrating a configuration of a noise suppression device according to a second embodiment.
FIG. 8 is a diagram illustrating an operation of a filter 40 according to the second embodiment.
FIG. 9 is a block diagram showing a configuration of a noise suppression device according to a third embodiment.
FIG. 10 is a block diagram showing a configuration of a correction method determination circuit according to a third embodiment.
FIG. 11 is a diagram illustrating linear interpolation using a short correction period signal and a corrected correction period signal.
FIG. 12 is a block diagram showing a configuration of a noise suppression device according to a fourth embodiment.
FIG. 13 is a block diagram illustrating a configuration of a conventional pulse noise suppression device.
FIG. 14 is a view for explaining correction of a previous value holding method and a linear interpolation method of a pulse noise portion by a correction period signal.
FIG. 15 is a diagram illustrating linear interpolation correction of a pulse noise portion by a short correction period signal.
[Explanation of symbols]
1 FM demodulation circuit, 5 stereo demodulation circuit, 11 noise detection circuit, 14 pre-value holding method correction circuit, 21 noise detection circuit, 22 correction method determination circuit, 23 linear interpolation method correction circuit, 24 switch circuit, 25 period determination circuit, 40 filter, 41 is a correction period correction circuit.

Claims (7)

Noise detection means for detecting a noise generation period from the FM demodulated signal and outputting a correction period signal;
Based on the correction period signal, a previous value holding method correction unit that corrects the FM demodulation signal in the noise generation period using a signal immediately before the noise generation period;
Interpolation method correction means for interpolating and correcting the FM demodulation signal in the noise generation period using signals before and after the noise generation period based on the correction period signal,
When the correction period signal is determined to be shorter than the actual noise generation period, a correction method determination unit that determines selection of the previous value holding method,
A noise suppression device comprising: a correction method selection unit that selects one of the preceding value holding method correction unit and the interpolation method correction unit in accordance with an output of the correction method determination unit. When the absolute value of the difference between the FM demodulated signal corresponding to the start end and the end of the corrected period signal is larger than the average amplitude of the FM demodulated signal, the correction method determining means determines that the corrected period signal is shorter than the actual noise generation period. The noise suppression device according to claim 1, wherein the determination is performed. When the absolute value of the difference between the high-frequency components of the FM demodulated signal corresponding to the start and end of the correction period signal is larger than the average amplitude of the high-frequency components of the FM demodulated signal, The noise suppression device according to claim 1, wherein it is determined that the period is shorter than an actual noise generation period. The correction method determining means determines that the absolute value of the difference between the high-frequency component of the FM demodulated signal corresponding to the beginning and the end of the correction period signal in any of the high-frequency components of the FM demodulated signal divided into a plurality of bands. 2. The noise suppression device according to claim 1, wherein when the amplitude is larger than the average amplitude of the high frequency component of the FM demodulated signal, the correction period signal is determined to be shorter than the actual noise generation period. Noise detection means for detecting a noise generation period from the FM demodulated signal and outputting a correction period signal;
When the absolute value of the difference between the FM demodulation signal corresponding to the start end of the correction period signal and the FM demodulation signal after the end of the correction period signal becomes smaller than the average amplitude of the FM demodulation signal, the end of the noise generation period Correction period determination means for outputting a determination signal,
From the end of the correction period signal until the determination signal is output, a correction period correction unit that extends the correction period signal and outputs a correction correction period signal,
A noise suppression device, comprising: an interpolation method correction unit that performs interpolation correction of an FM demodulation signal in the noise generation period using signals before and after the noise generation period based on the correction correction period signal. When the correction period determining means determines that the absolute value of the difference between the high frequency components of the FM demodulated signal corresponding to the start and end of the correction period signal becomes smaller than the average amplitude of the high frequency components of the FM demodulated signal, The noise suppression device according to claim 5, wherein a determination signal for terminating the period is output. The correction period determination means determines that the absolute value of the difference between the high frequency components of the FM demodulated signal corresponding to the start and end of the correction period signal in any of the high frequency components of the FM demodulated signal divided into a plurality of bands. 6. The noise suppression device according to claim 5, wherein a determination signal for ending the noise occurrence period is output when the amplitude of the FM demodulated signal becomes smaller than the average amplitude of the high frequency component.

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