JP3546861B2 - Drive control device for magnet type synchronous motor - Google Patents

Description

[0001]
TECHNICAL FIELD OF THE INVENTION
The present invention relates to a drive control device for a magnet type synchronous motor .
[0002]
[Conventional technology and problems to be solved]
As a starting control method of the electric motor, as in Japanese Patent Application Laid-Open No. 9-74790, a time interval of an angle signal for every 60 electrical degrees is measured based on a signal indicating a rotation angle of the electric motor, and the rotation angle is interpolated based on the time interval. There is known a method of creating an estimated rotation angle and calculating a current flowing through the stator winding or a voltage applied to the stator winding based on the estimated rotation angle. According to this method, even if the angle interval of the rotation position signal is large, the angle information between the rotation position signals can be supplemented by the interpolation calculation, so that the configuration of the sensors for detecting the rotation position is simplified and the desired detection accuracy is maintained. Is possible.
[0003]
However, according to such a conventional start control method, only the angle can be detected every 60 degrees at the time of start. Therefore, if the actual phase of the rotor is shifted with respect to the rotation sensor, a control error due to the phase shift causes There is a problem that the starting torque and the maximum torque at the extremely low speed are greatly reduced.
[0004]
The present invention has been made in view of such conventional problems, and enables the electric motor to reliably exhibit the maximum torque even at the time of starting or at extremely low speed without complicating the configuration of the rotation sensor. It is an object of the present invention to provide an electric motor control device.
[0005]
[Means for Solving the Problems]
A first invention is a drive control device for a magnet-type synchronous motor that drives a magnet-type synchronous motor with a rotor phase detection system that can detect a signal only at a predetermined rotor phase, wherein the rotor phase detection system is A plurality of control modes having different types of phase correction for each speed range of the magnet type synchronous motor, and when the rotation speed of the rotor is equal to or less than a predetermined rotation speed, a correction angle determined in advance by the detected phase value of the rotor. Is selected from among the plurality of control modes, and the control in the correction mode is continued until the rotation speed of the rotor exceeds the predetermined rotation speed. The predetermined rotation speed is a rotation speed at which the detection value of the rotor phase by the rotor phase detection system is such that the drive torque of the electric motor becomes insufficient with respect to the target drive torque due to a decrease in control accuracy of the drive control device. is there.
[0006]
A second invention is a drive control device for a magnet-type synchronous motor that drives a magnet-type synchronous motor with a rotor phase detection system capable of detecting a signal only at a predetermined rotor phase, wherein the rotor phase detection system is It has a plurality of control modes in which the type of phase correction is different for each speed range of the magnet type synchronous motor, and when the rotation speed of the rotor is equal to or lower than a predetermined rotation speed, the control current supplied to the magnet type synchronous motor is A correction mode for outputting a control signal obtained by adding a predetermined correction angle to the phase as needed is selected from among the plurality of control modes, and the control in the correction mode is performed until the rotation speed of the rotor exceeds the predetermined rotation speed. It was to be continued. The predetermined rotation speed is a rotation speed at which the detection value of the rotor phase by the rotor phase detection system is such that the drive torque of the electric motor becomes insufficient with respect to the target drive torque due to a decrease in control accuracy of the drive control device. is there.
[0007]
According to a third aspect, in the first or second aspect, as one of the control modes different from the correction mode , when the rotor rotation speed is in a high-speed rotation speed region exceeding a predetermined value, the detected phase is not changed. It has a normal mode for supplying a control current so that the current phase advances by a predetermined phase β.
[0008]
In a fourth aspect based on the first or second aspect, in the correction mode , the rotor phase detection is performed even when the torque command to the electric motor or a representative parameter thereof is equal to or more than the reference value for a set time. The system is configured to be selected when a phase signal from the system is not detected.
[0009]
In a fifth aspect based on the first or second aspect, the correction angle to be added at any time is set to be equal to or less than a speed calculated from a maximum load and a maximum torque assumed in design.
[0010]
In a sixth aspect based on the first or second aspect , when the phase signal from the rotor phase detection system is not detected even when the phase signal in the correction mode reaches a maximum value, It was configured to repeat.
[0011]
A seventh invention is the in the first or second aspect, upon detection of a phase signal from the rotor phase detection system in the current control in the correction mode, the addition of the correction angle the detection phase as an initial value Was configured to continue.
[0012]
Advantageously, in the invention of the sixth, when the phase signal in the correction mode has reached a maximum value it was constructed the phase signal so as to gradually return to the minimum value.
[0013]
A ninth aspect of the invention of the sixth and configured to reduce the correction angle number of repetitions of the correction mode is the adding enough to increase.
[0014]
[Action / Effect]
According to the first or second aspect, there is provided a correction mode for variably setting a pseudo detection phase set in place of an actual rotation phase of the motor or a phase of an output current to the motor in a predetermined phase unit. Thus, the electric motor can be driven with the current vector phase that ensures the maximum torque in the process of the variable setting. For this reason, when a rotation sensor having a low resolution of, for example, a phase angle of 60 degrees is used, a torque shortage or a torque shock generated at the start or in a very low speed rotation region where the phase estimation calculation is difficult is eliminated, and the electric motor or the motor is used. Drivability of the vehicle used can be greatly improved.
[0015]
In addition, at the time of a low load where it is not necessary to select the correction mode or in an operation range where the rotation speed is relatively high, as shown in the third invention, the current phase is shifted by a predetermined phase β (generally 2 (rad)), control in the normal mode for supplying a control current may be performed. In this case, sufficient control accuracy can be obtained even by a method of estimating and outputting the current phase of the motor by interpolation processing.
[0016]
According to the fourth aspect, when the motor is actually determined to be insufficient in torque, the correction mode in which the maximum torque is obtained is selected, so that it is possible to efficiently start the motor with a large load. Become.
[0017]
According to the fifth aspect, the unit of the phase setting is set to be equal to or less than the speed calculated from the maximum load and the maximum torque assumed in the design, so that the rotation angle can be maintained while maintaining the high torque output state. This makes it difficult for the rotor of the electric motor to lose synchronism with the control current vector, so that the starting performance is more reliably improved. Further, in the vehicle to which the electric motor according to the present invention is applied, by determining the unit of the phase setting from the vehicle weight and the maximum torque, for example, in a stopped state or an extremely low-speed running state such as when a wheel runs over a step. Step-out of the motor when an extremely large load is applied can be suppressed.
[0018]
According to the sixth aspect, even if the set phase reaches the maximum value within the set range, if no phase signal is detected from the rotation sensor, control in the correction mode is repeated again from the minimum value. Therefore, the subsequent abnormal operation when the motor loses synchronism with the rotor magnetic field can be prevented, and the start control can be reliably performed again, or the start can be repeated even if the start fails.
[0019]
According to the seventh aspect, when the phase signal from the rotation sensor is detected during the control in the correction mode, the correction mode is continued with the detected phase as an initial value, so that the high load state is maintained. During this period, a high torque is continuously obtained, so that the starting under a high load can be performed smoothly and reliably.
[0020]
According to the eighth aspect, the speed of returning the phase to the minimum value within the phase setting range in the sixth aspect is reduced, so that it is possible to suppress a torque shock due to a sudden change in the current vector phase.
[0021]
According to the ninth aspect, when the control of the correction mode is repeated in the sixth aspect, the set unit of the phase is reduced as the number of repetitions increases, so that the starting operation is repeated. The angular velocity of the current vector phase can be reduced to a level that does not cause loss of synchronism, and the load range in which starting can be performed can be expanded.
[0022]
BEST MODE FOR CARRYING OUT THE INVENTION
Hereinafter, embodiments of the present invention will be described with reference to the drawings. FIG. 1 schematically shows a mechanical configuration of an embodiment of the present invention. In the figure, 1 is an internal magnet type synchronous motor, and 2 is a phase detector for detecting its rotor phase. The phase detector comprises a first Hall element 2a, a second Hall element 2b, a third Hall element 2c, and a disk 2d attached to the rotor of the motor 1 and magnetized to have the same magnetic pole as the rotor magnetic pole. The rotation sensor according to the invention is configured. 3 is a motor control unit, 4 is an inverter driver, 5 is an inverter, and 6 is a battery. The control unit 3 includes a microcomputer and its peripheral devices, and functions as control means of the present invention.
[0023]
The first to third Hall elements 2a to 2c of the phase detector 2 output on / off signals as shown in FIG. From the combination of the signals, the rotor phase can be detected with a resolution of 60 electrical degrees. For example, when 2a = on, 2b = on, and 2c = off, it can be seen that the rotor phase is in a section from 120 degrees to 180 degrees.
[0024]
FIG. 3 shows the torque characteristics of the electric motor 1. When the rotor phase coincides with the phase of the rotating magnetic field generated by the stator, the torque generated in the rotor becomes zero (point A). As the phase of the rotating magnetic field advances from point A, the torque increases, and point B After the maximum value is reached, the torque decreases when the phase of the rotating magnetic field is further advanced. Such a torque characteristic (torque curve) is basically determined according to the specifications of the electric motor, and changes according to the operating conditions (such as the rotation speed) of the electric motor.
[0025]
In general, the maximum torque can be obtained when the rotating magnetic field phase is advanced by π / 2 (rad) from the rotor phase. Therefore, the basic condition is that the rotating magnetic field phase is advanced by π / 2 from the rotor phase. Generally, the rotating magnetic field phase is expressed by the angle of deviation from the state, and this is also followed in this description. Hereinafter, this shift angle is referred to as a beta angle β.
[0026]
This beta angle corresponds to the angle formed by the current vector with the q-axis when the current supplied to the stator coil is divided into a field component current (d-axis current) and a torque component current (q-axis current). (See FIG. 4). When the motor control is performed, the beta angle β and the length I of the current vector (corresponding to the amplitude of the alternating current supplied to the stator coil) are determined in accordance with the rotation speed of the rotor and the target torque. A d-axis current tId and a target q-axis current tIq are obtained, an inverter command value is obtained from the tId, tIq, and the rotor phase θ, and the inverter 5 is driven based on the command value to control a current flowing through the stator coil.
[0027]
Although the phase detector 2 has an angular resolution of only 60 degrees as described above, it is possible to obtain a relatively accurate rotor phase θ by a known estimation operation when the rotor is rotating at a certain speed. Also in the present embodiment, when the rotor rotation speed is equal to or higher than the predetermined speed VO, the estimation calculation of the rotor phase θ is performed (normal mode).
[0028]
When the rotor is not rotating or rotating at an extremely low speed, the rotor phase θ cannot be accurately estimated. Therefore, when the rotor rotation speed is lower than the predetermined speed VO, a certain fixed value in the determined section is set as the rotor phase θ (fixed mode). For example, when it is known that the rotor phase is in the section from 120 degrees to 180 degrees, the current control is performed after fixing the rotor phase θ to an intermediate value of 150 degrees. In this case, since the true phase of the rotor and the rotor phase θ used for current control are shifted by a maximum of 30 degrees , a state occurs in which the actual torque generated by the electric motor 1 becomes smaller than the target torque. However, if a certain amount of torque is obtained and the rotor rotation speed increases, the mode can be shifted to the normal mode, so that there is no problem.
[0029]
The rotor may not rotate, and the rotor may not rotate even if the motor 1 generates a certain amount of torque. For example, the above-described state occurs when the electric motor 1 is driving the driving wheels of a vehicle and the driving wheels are going over a step. Even if the motor 1 generates the maximum torque, the current control in the fixed mode may not be able to get over the step, even if the step is such that the motor 1 generates the maximum torque. Therefore, when such a state occurs, the rotor phase change control for gradually changing the rotor phase θ within the determined section is executed (correction mode). In the process of gradually changing the rotor phase θ, there is always a time when the rotor phase θ coincides with the rotor phase at which the maximum torque occurs, so that the maximum torque can be obtained even temporarily.
[0030]
Next, the details of the control will be described with reference to flowcharts shown in FIG. 5 and the following flowcharts show a control routine that is executed by the control unit 3 periodically or at a predetermined timing, and reference characters S in the figure and in the following description represent respective processing steps.
[0031]
FIG. 5 shows a rotor rotation speed calculation routine, which is executed every time the output of any of the three Hall elements 2a to 2c changes (off → on, on → off), that is, every time the rotor rotates by 60 electrical degrees. Is done.
S1:
The current count value is obtained from a timer counter that is counted up every fixed minute time, and the value is set as t0.
S2:
The value of t1 is substituted into t2, and the value of t0 acquired in S1 is substituted into t1. t1 represents the current time, and t2 represents the time when this routine was executed last time.
S3:
The rotor rotation speed V is calculated by dividing 60 degrees by the time (t1-t2) required for the rotor to rotate 60 degrees.
[0032]
FIG. 6 shows a main control routine. The command value calculated in this routine is sent to the inverter driver 4, and the inverter driver 4 generates a PWM signal based on the command value, and the switching element of the inverter 5 outputs the PWM signal. , The current flowing through the stator coil of the electric motor 1 is controlled.
S10:
The rotor phase θ is calculated.
S20:
Β is calculated based on the rotor rotation speed V and a target torque tT given from the outside. That is, for example, a value is looked up from a control map in which β is stored in advance in correspondence with V and tT.
S30:
A current amplitude I is calculated based on the rotor rotation speed V and a target torque tT given from outside. In this case, for example, a value is looked up from a control map in which I is stored in advance in correspondence with V and tT.
S40:
A target d-axis current tId and a target q-axis current tIq are calculated based on β and I. S50:
A command value is calculated based on the target d-axis current tId, the target q-axis current tIq, and the rotor phase θ.
[0033]
FIG. 7 shows a rotor phase calculation subroutine, which shows details of the processing performed in S10 of the main control routine.
S100:
The section of the rotor phase is determined from the combination of the on / off signals of the first to third Hall elements 2a to 2c of the rotor phase detector 2, and the first rotor phase of the determined section is set as the section leading phase θ1. For example, when 2a = on, 2b = on, and 2c = off, it can be determined that the rotor phase is between 120 degrees and 180 degrees. In this case, θ1 is set to 120 degrees.
S110-150:
The rotor phase θ is calculated according to the mode indicated by the mode selection flag fm. The mode selection flag fm is a flag set in a mode selection routine (FIG. 12) to be described later. When the mode selection flag fm is 3, the estimation mode is selected, the fixed mode is set at 2, and the correction mode is set at 1 and 0. To do.
[0034]
FIG. 8 shows an estimation mode rotor phase calculation subroutine, which shows details of the processing performed in S120 of the rotor phase calculation subroutine.
S121:
The current count value is obtained from the timer counter (same as that of S1 in FIG. 5), and the value is set as ti.
S122:
The rotor phase θ is calculated by the phase estimation calculation. Specifically, the difference between the time t1 at which the rotor phase has just become the section leading phase θ1 (same as t1 in S2 in FIG. 5) and the current time ti is multiplied by the rotor rotation speed V, and θ1 is multiplied by this. The added value is defined as the rotor phase θ.
[0035]
FIG. 9 shows a fixed mode rotor phase calculation subroutine, which shows details of the processing performed in S140 of the rotor phase calculation subroutine.
S141:
The rotor phase θ is calculated by adding a fixed value (here, 30 degrees) to the section leading phase θ1.
[0036]
FIG. 10 shows a correction mode rotor phase calculation subroutine, which shows details of the processing performed in S150 of the rotor phase calculation subroutine.
S151:
It is determined whether or not the mode selection flag fm is 1. When the correction mode is selected, fm is 1 or 0. In particular, when fm = 1, it indicates that it is immediately after shifting from another mode to the correction mode. When the mode selection flag fm is 1, the process proceeds to S152, and an initial process immediately after the shift to the correction mode is performed. Specifically, the value of the counter n is reset to 0, and the initial value of the rotor phase θ is set to the section leading phase θ1. Before the shift to the correction mode, the fixed mode should have been selected, and the rotor phase at this time is θ1 + 30 degrees. If the rotor phase θ is changed stepwise to θ1, a slight torque shock may occur. When this torque shock becomes a problem, it is preferable to gradually return the rotor phase θ from θ1 + 30 degrees to θ1. The counter n is a counter that counts up the number of execution sets of the rotor phase change control (the number of times θ has been changed from the minimum value to the maximum value of the section).
S153:
When it is determined that the mode selection flag fm is not 1 (fm = 0), the process proceeds to S153, and the section head phase θ1 set in S100 of FIG. 7 is different from the section head phase θ1z when this routine was executed last time. That is, it is determined whether or not the section has shifted during the correction mode. If a section transition has occurred, the process proceeds to S154, in which the rotor phase θ is set to the section leading phase θ1 as a process at the time of the section transition, and the process proceeds to S155 and subsequent steps. Note that the occurrence of the section transition indicates that the rotor has rotated to some extent, and therefore the correction mode may be temporarily terminated. If it is determined in S153 that no section shift has occurred, the process directly proceeds to S155 and subsequent steps.
S155:
The phase change width dθ for the rotor phase change control is calculated based on the counter n. Specifically, as illustrated in FIG. 11, a value is looked up from a control table preset to give dθ according to n. In this control table, as shown in the drawing, dθ is set smaller as n increases. When dθ is large, one set of control can be completed in a short time, but the time during which the maximum torque is obtained also becomes short. Therefore, first, the phase change control is performed using a large dθ, and when the transition to the estimation mode cannot be achieved by the control (corresponding to a state in which riding on a step cannot be achieved in the above-described example of the vehicle), dθ is gradually increased. The rotor phase change control is repeatedly executed while decreasing the value. Note that the initial value (maximum value) of dθ is the rotor when the maximum torque is generated at the time of the maximum load operation assumed in the design (in the above-described example of the vehicle, at the time of the operation on the maximum step that guarantees the ride). It is set to a value at which the change speed of the rotor phase does not become faster than the rotation speed.
S156:
The new phase θ is calculated by adding the phase change width dθ to the current θ.
S157:
It is determined whether or not the rotor phase θ calculated in S156 exceeds the section maximum phase (θ1 + 60 degrees). If θ> θ1 + 60 degrees, the process proceeds to S158, where the counter n is counted up, and the rotor phase θ is returned to the section leading phase θ1. If the rotor phase θ is returned stepwise from θ1 + 60 degrees to θ1, some torque shock may occur. If this torque shock becomes a problem, the rotor phase θ may be gradually returned to θ1. If θ ≦ θ1 + 60 degrees, the process directly proceeds to S159 and subsequent steps.
S159:
The mode selection flag fm is set to 0 (that is, the correction mode is being executed and the rotor phase change control is being executed), and the current section head phase θ1 is stored as θ1z.
[0037]
FIG. 12 shows a mode selection routine, which is executed at predetermined intervals independently of the main control routine.
S181:
It is determined whether the rotor rotation speed V is higher than a predetermined speed VO. If V> VO, the process proceeds to S182, where the counter C is reset to 0, and then the mode selection flag fm is set to 3 (estimation mode) in S183. If it is determined in S181 that V ≦ VO, the process proceeds to S184, and it is determined whether the target torque tT is smaller than the predetermined torque TO. Even when V ≦ VO, such a determination is made because it is not necessary to select the special mode when the motor driver does not request a large torque.
S184:
If tT <TO, the process proceeds to S185 to reset the counter C to 0, and then sets the mode selection flag fm to 2 (fixed mode) in S186. When it is determined that tT ≧ TO, the process proceeds to S187, where the counter C is counted up by a predetermined step value dC, and then it is determined in S188 whether the counter C is smaller than a predetermined value ts.
S189:
If C <ts, the process proceeds to S189, and the mode selection flag fm is set to 2 (fixed mode). That is, even if a state occurs in which the rotor hardly rotates despite the driver requesting a large torque, the fixed mode is selected until the state continues for a predetermined time. When it is determined that C ≧ ts, the correction mode is selected by the processing of S190 and thereafter.
S190:
The current mode selection flag fm is set to 0 in order to discriminate whether the mode is a shift from another mode to the correction mode, or whether the correction mode is already selected and the rotor phase change control is being reselected. Determine if it is greater than. If fm> 0, it is determined that a transition from another mode has been made, and the flow advances to S191 to set the mode selection flag fm to 1 (special mode and immediately after the mode transition). If fm = 0, the process proceeds to S192, and the value of fm is maintained at 0 as it is.
[0038]
FIG. 13 shows a second embodiment of the motor control according to the present invention. In the first embodiment, control for generating the maximum torque is performed by variably setting the detection phase in the correction mode, whereas in this embodiment, the beta angle β of the control current is variably set. The points are different. That is, in this embodiment, when the mode selection flag fm is 3 when the rotor phase is calculated in S10 of the main control routine of FIG. 6, the rotor phase is calculated in the estimation mode (FIG. 8), and the mode selection flag fm is set to 2 , 1, 0, the rotor phase is calculated in the fixed mode (FIG. 9). The operation of the rotor phase in the correction mode is not performed. On the other hand, when the mode selection flag fm is 3 or 2 during the beta angle calculation performed in S20 of the main control routine (FIG. 6), the value βm looked up from the control map is directly set as the beta angle β, while the mode selection flag is set. When fm is 1, 0, the beta angle is calculated using the correction mode beta angle calculation subroutine described below with reference to FIG.
S201:
It is determined whether or not the mode selection flag fm is 1. If fm = 1, the process proceeds to S202, where an initial process immediately after the shift to the correction mode is performed. Specifically, the value of the counter n is reset to 0, and the initial value of the beta angle β is set to a value obtained by subtracting 30 degrees from the map value βm.
S203:
An angle change width dβ for beta angle change control is calculated based on the counter n. This is determined, for example, by referring to a control table set in advance so as to give dβ according to n. This control table is configured such that dβ is set smaller as n increases.
S204:
A new beta angle β is calculated by adding the angle change width dβ to the current β.
S205:
It is determined whether the beta angle β calculated in S204 exceeds βm + 30 degrees. If the beta angle β exceeds βm + 30 degrees, the process proceeds to S206, where the counter n is counted up, and the beta angle β is returned to βm 30 degrees.
S207:
The mode selection flag fm is set to 0.
[Brief description of the drawings]
FIG. 1 is a schematic diagram showing a mechanical configuration of an embodiment of the present invention.
FIG. 2 is an output timing chart of a phase detector.
FIG. 3 is a characteristic diagram illustrating a relationship between a phase angle (β) of a control current and a generated torque.
FIG. 4 is a flowchart showing a first embodiment of the motor control according to the present invention.
FIG. 5 is a flowchart showing a first embodiment of motor control according to the present invention.
FIG. 6 is a flowchart showing a first embodiment of motor control according to the present invention.
FIG. 7 is a flowchart showing a first embodiment of motor control according to the present invention.
FIG. 8 is a flowchart showing a first embodiment of motor control according to the present invention.
FIG. 9 is a flowchart showing a first embodiment of motor control according to the present invention.
FIG. 10 is a flowchart showing a first embodiment of motor control according to the present invention.
FIG. 11 is an explanatory diagram of a control table used in the processing of FIG. 10;
FIG. 12 is a flowchart showing a first embodiment of motor control according to the present invention.
FIG. 13 is a flowchart showing a first embodiment of motor control according to the present invention.
[Explanation of symbols]
DESCRIPTION OF SYMBOLS 1 Motor 2 Phase detector 2a, 2b, 2c Hall element 2d Disk 3 Control unit 4 Inverter driver 5 Inverter 6 Battery

Claims (9)

A drive control device for a magnet-type synchronous motor that drives a magnet-type synchronous motor with a rotor phase detection system that can detect a signal only at a predetermined rotor phase,
The rotor phase detection system has a plurality of control modes with different types of phase correction for each speed range of the magnet type synchronous motor,
When the rotation speed of the rotor is equal to or less than a predetermined rotation speed,
A correction mode for outputting a phase signal obtained by adding a predetermined correction angle to the detected phase value of the rotor as needed is selected from among the plurality of control modes,
Control in the correction mode is continued until the rotation speed of the rotor exceeds the predetermined rotation speed,
The predetermined rotation speed is a rotation speed at which the detection value of the rotor phase by the rotor phase detection system is such that the drive torque of the electric motor becomes insufficient with respect to the target drive torque due to a decrease in control accuracy of the drive control device. A drive control device for a magnet-type synchronous motor, comprising: A drive control device for a magnet-type synchronous motor that drives a magnet-type synchronous motor with a rotor phase detection system that can detect a signal only at a predetermined rotor phase,
The rotor phase detection system has a plurality of control modes with different types of phase correction for each speed range of the magnet type synchronous motor,
When the rotation speed of the rotor is equal to or less than a predetermined rotation speed,
A correction mode for outputting a control signal obtained by adding a predetermined correction angle to the phase of the control current supplied to the magnet type synchronous motor as needed is selected from among the plurality of control modes,
Control in the correction mode is continued until the rotation speed of the rotor exceeds the predetermined rotation speed,
The predetermined rotation speed is a rotation speed at which the detection value of the rotor phase by the rotor phase detection system is such that the drive torque of the electric motor becomes insufficient with respect to the target drive torque due to a decrease in control accuracy of the drive control device. A drive control device for a magnet-type synchronous motor, wherein: As one of the control modes different from the correction mode , when the rotor rotation speed is in a high-speed rotation region exceeding a predetermined value , a control current is supplied so that the current phase advances by a predetermined phase β with respect to the detected phase. 3. The drive control device for a magnet type synchronous motor according to claim 1 , wherein the drive control device has a mode. The correction mode, so that the torque command or a representative parameter of the motor state which is equal to or greater than the reference value is selected when the phase signal from the rotor phase detection system be continued setting time is not detected The drive control device for a magnet type synchronous motor according to claim 1 or 2, wherein 3. The drive control device for a magnet type synchronous motor according to claim 1, wherein the correction angle to be added as needed is set to be equal to or less than a speed calculated from a maximum load and a maximum torque assumed in design. 3. The magnet type synchronous motor according to claim 1, wherein the correction mode is repeated when the phase signal from the rotor phase detection system is not detected even when the phase signal in the correction mode reaches the maximum value . Drive control device . The magnet type synchronization according to claim 1 or 2, wherein when a phase signal from a rotor phase detection system is detected during current control in the correction mode, addition of the correction angle is continued with the detected phase as an initial value. Drive control device for electric motor . When said phase signal by the correction mode has reached the maximum value, magnet synchronous motor drive control apparatus according to claim 6 back and the phase signal to gradually minimum. The motor start control device according to claim 6, wherein the correction angle to be added is reduced as the number of repetitions of the correction mode increases.

Images