JP3539464B2 - Power supply and discharge lamp lighting device - Google Patents

Description

[0001]
TECHNICAL FIELD OF THE INVENTION
The present invention relates to a power supply device and a discharge lamp lighting device that reduce harmonics of an input current.
[0002]
[Prior art]
Conventionally, as a discharge lamp lighting device of this type, for example, a configuration described in Japanese Patent Application Laid-Open No. H5-211774 is known. In the discharge lamp lighting device described in Japanese Patent Application Laid-Open No. 5-217774, a full-wave rectifier circuit is connected to a commercial AC power supply, and a first capacitor and a second capacitor are connected to output terminals of the full-wave rectifier circuit. ing. Further, a partial smoothing circuit having a charging capacitor and an inductor is connected to the second capacitor, and a parallel resonant circuit and a transistor of the capacitor and the inductor are connected in series to the partial smoothing circuit. Is connected to a fluorescent lamp.
[0003]
Then, by the high-frequency switching operation of the transistor, resonance occurs in the parallel resonance circuit, a resonance voltage is generated, and the fluorescent lamp is lit at high frequency.
[0004]
[Problems to be solved by the invention]
However, the discharge lamp lighting device described in JP-A-5-212774 has a slight problem in crest factor because the voltage from the second capacitor and the partial smoothing circuit is not sufficient.
[0005]
The present invention has been made in view of the above problems, and has as its object to provide a power supply device and a discharge lamp lighting device in which harmonic components are reduced and a crest factor is improved.
[0006]
[Means for Solving the Problems]
According to a first aspect of the present invention, there is provided a power supply device comprising: a rectifier for rectifying an alternating current from an AC power supply; a first capacitor connected in parallel to an output terminal of the rectifier; It has a diode connected in series, a second capacitor connected in parallel to the first capacitor via the diode, an inductance element and a charging capacitor, and the output of the rectifier means is connected to the charging capacitor. A partial smoothing circuit connected in parallel to the second capacitor that is charged with a voltage lower than the maximum instantaneous voltage value, a parallel resonance circuit having a first resonance capacitor and a resonance inductor, and a parallel resonance circuit in series with the parallel resonance circuit. Connected switching element, connected in parallel to this switching element Improve crest factor An inverter circuit that has a second resonance capacitor, is connected in parallel to the partial smoothing circuit, and generates a high-frequency voltage by a switching operation of the switching element. The inverter circuit supplies the input current from the first capacitor and the second capacitor when the output level of the rectifier is equal to or higher than the charge level of the charging capacitor, and the output level of the rectifier is lower than the charge level of the charging capacitor. In some cases, the input current is supplied from the partial smoothing circuit, the parallel resonance circuit and the second resonance capacitor are caused to perform a resonance operation by the switching operation of the switching element to reduce harmonics, and the wave height is increased by flowing the resonance current into the second capacitor. High frequency output with improved rate.
[0007]
According to a second aspect of the present invention, there is provided a power supply device comprising: a first capacitor connected to an AC power supply; a rectifier connected to the first capacitor; a second capacitor connected to the rectifier; A partial smoothing circuit connected in parallel to the second capacitor, which has a charging capacitor and charges the charging capacitor with a voltage lower than the maximum instantaneous voltage value of the output of the rectifier; A parallel resonance circuit having a capacitor and a resonance inductor, a switching element connected in series to the parallel resonance circuit, and a switching element connected in parallel to the switching element Improve crest factor An inverter circuit that has a second resonance capacitor, is connected in parallel to the partial smoothing circuit, and generates a high-frequency voltage by a switching operation of the switching element. The inverter circuit supplies the input current from the first capacitor and the second capacitor when the output level of the rectifier is equal to or higher than the charge level of the charging capacitor, and the output level of the rectifier is lower than the charge level of the charging capacitor. In some cases, the input current is supplied from the partial smoothing circuit, the parallel resonance circuit and the second resonance capacitor are caused to perform a resonance operation by the switching operation of the switching element to reduce harmonics, and the wave height is increased by flowing the resonance current into the second capacitor. High frequency output with improved rate.
[0008]
According to a third aspect of the present invention, there is provided a power supply device comprising: a rectifier for rectifying an AC from an AC power supply; a first capacitor connected in parallel to an output terminal of the rectifier; and a diode connected to the first capacitor. A second capacitor connected in parallel to the diode, an inductance element and a charging capacitor, and charging the charging capacitor with a voltage lower than the maximum instantaneous voltage value of the output of the rectifier. A partial smoothing circuit connected in parallel to the first capacitor via a capacitor and a diode, a parallel resonance circuit having a first resonance capacitor and a resonance inductor, a switching element connected in series to the parallel resonance circuit, Connected in parallel to this switching element Improve crest factor An inverter circuit that has a second resonance capacitor, is connected in parallel to the partial smoothing circuit, and generates a high-frequency voltage by a switching operation of the switching element. The inverter circuit supplies the input current from the first capacitor and the second capacitor when the output level of the rectifier is equal to or higher than the charge level of the charging capacitor, and the output level of the rectifier is lower than the charge level of the charging capacitor. In some cases, the input current is supplied from the partial smoothing circuit, the parallel resonance circuit and the second resonance capacitor are caused to perform a resonance operation by the switching operation of the switching element to reduce harmonics, and the wave height is increased by flowing the resonance current into the second capacitor. High frequency output with improved rate.
[0009]
According to a fourth aspect of the present invention, there is provided the power supply device according to the first or third aspect, further comprising a short-circuit means for short-circuiting a diode in accordance with an output level of the rectifying means. The burden on the element is reduced.
[0010]
According to a fifth aspect of the present invention, there is provided the power supply device according to any one of the first to fourth aspects, further comprising a capacitance changing unit that changes a capacitance of the second capacitor. In the state where the voltage of the second capacitor is low, the voltage value is reduced to 0 to further reduce harmonics.
[0011]
The power supply device according to claim 6 is the power supply device according to any one of claims 1 to 5, wherein the first resonance capacitor and the second resonance capacitor have substantially equal capacities, thereby further improving the waveform.
[0012]
A discharge lamp lighting device according to a seventh aspect includes the power supply device according to any one of the first to sixth aspects and a discharge lamp connected to the power supply device, and has respective functions.
[0013]
BEST MODE FOR CARRYING OUT THE INVENTION
Hereinafter, a discharge lamp lighting device according to an embodiment of the power supply device of the present invention will be described with reference to the drawings.
[0014]
As shown in FIG. 1, an input terminal of a full-wave rectifier circuit 1 as a rectifier of a diode bridge is connected to a commercial AC power supply e, and a first capacitor C1 having a large capacity is connected to an output terminal of the full-wave rectifier circuit 1. The first capacitor C1 is connected to a series circuit of a diode D1 and a second capacitor C2 having a smaller capacity than the first capacitor C1.
[0015]
Further, the partial smoothing circuit 2 is connected to the second capacitor C2. The partial smoothing circuit 2 is connected to a series circuit of a charging capacitor C3, an inductor L1, and a diode D2, and is connected between the inductor L1 and the diode D2. , A diode D3 is connected.
[0016]
Further, an inverter circuit 3 is connected to the partial smoothing circuit 2. In the inverter circuit 3, a primary winding Tr1a of a leakage flux type inverter transformer Tr1 as a resonance inductor, a parallel resonance circuit 4 of a first resonance capacitor C4, and a collector and an emitter of a transistor Q1 serving as a switching element are connected. . Further, a second resonance capacitor C5 is connected between the emitter and the collector of the transistor Q1.
[0017]
The control circuit 5 is connected to the base of the transistor Q1.
[0018]
Further, filaments FL1 and FL2 of a fluorescent lamp FL as a discharge lamp are connected to the secondary winding Tr1b of the inverter transformer Tr1, and a starting capacitor C6 is connected to these filaments FL1 and FL2.
[0019]
The load circuit 6 is constituted by the fluorescent lamp FL or the like.
[0020]
Next, the operation of the above embodiment will be described.
[0021]
First, when the inverter circuit 3 oscillates by the switching operation of the transistor Q1 by the control circuit 5, a high-frequency voltage is generated by the resonance between the primary winding Tr1a of the inverter transformer Tr1 and the charging capacitor C3, and the secondary winding Tr1b Also, a high-frequency voltage is induced.
[0022]
When the transistor Q1 is turned on, a current flows through the primary winding Tr1a of the inverter transformer Tr1, and a current flows through the charging capacitor C3, the inductor L1, and the diode D3 to charge the charging capacitor C3. Then, a DC voltage lower than the peak value of the pulsating voltage from the full-wave rectifier circuit 1 can be stored in the charging capacitor C3.
[0023]
Here, a description will be given of a section where the pulsating voltage of the full-wave rectifier circuit 1 is higher than the charging voltage of the charging capacitor C3 and a section where the pulsating voltage is lower than the charging voltage.
[0024]
First, when the transistor Q1 of the inverter circuit 3 is turned on at an arbitrary time in a section in which the pulsating voltage of the full-wave rectifier circuit 1 is higher than the charging voltage of the charging capacitor C3, the current to the primary winding Tr1a of the inverter transformer Tr1 is turned on. Is supplied mostly from the first capacitor C1 and partly from the second capacitor C2. The combined capacitance of the first capacitor C1 and the second capacitor C2 is sufficient to provide the energy required by the inverter circuit 3. In accordance with the current supply from the first capacitor C1 and the second capacitor C2, energy flows from the commercial AC power supply e side as an input current. In response to the change in the pulsating voltage, an operation is performed so as to accompany the switching operation of the transistor Q1, and the small and equal amplitude of the high frequency of the inverter operation of the inverter circuit 3 along the sine wave value of the AC voltage becomes full-wave. The voltage value of the rectifier circuit 1 is superimposed on all high sections.
[0025]
That is, in the section where the voltage value of the full-wave rectifier circuit 1 is high, the combined value of the first capacitor C1 and the second capacitor C2 is determined by the energy provided by the supplied pulsating voltage being the energy required by the inverter circuit 3. It is a value that is satisfied.
[0026]
Therefore, both the first capacitor C1 and the second capacitor C2 have a small ripple component, a small amount of heat generation, and can enhance the operation reliability.
[0027]
Then, in a section where the voltage value of the full-wave rectifier circuit 1 is high, the charging capacitor C3 is charged when the transistor Q1 is turned on. Note that, in a section where the voltage value of the full-wave rectifier circuit 1 is high, the charge is not discharged from the charging capacitor C3 to the inverter circuit 3 side.
[0028]
Next, in a section where the voltage value of the full-wave rectifier circuit 1 is low, the transistor Q1 is turned on when the pulsating sine wave voltage of the full-wave rectifier circuit 1 starts to decrease with respect to the charging voltage of the charging capacitor C3. Then, the current to the primary winding Tr1a of the inverter transformer Tr1 is first supplied from the second capacitor C2. Since the capacity of the second capacitor C2 is not sufficient to provide the energy required by the inverter circuit 3, the current flowing through the primary winding Tr1a after the transistor Q1 is turned on increases as the current of the second capacitor C2 increases. The voltage drops. Then, from the time when the voltage of the second capacitor C2 drops to the voltage of the first capacitor C1, the first capacitor C1 supplies energy to the inverter circuit 3 which is insufficient in the second capacitor C2.
[0029]
Then, the voltage is supplied until the transistor Q1 is turned off. However, the decrease in the voltage of the second capacitor C2 after the start of the energy supply from the first capacitor C1 is reduced. When the energy is supplied from the first capacitor C1 to the inverter circuit 3, an amount of energy corresponding thereto is supplied as an input current from the commercial AC power supply e side.
[0030]
On the other hand, in the charging voltage of the charging capacitor C3, the release of energy is delayed due to the transient impedance of the inductor L1, and the energy is released immediately before the transistor Q1 is turned off. Then, when the transistor Q1 is turned off, the charging voltage of the charging capacitor C3 becomes a voltage supply source to the series circuit of the inductor L1, the diode D2, and the second capacitor C2. Here, since the inductor L1 and the second capacitor C2 are set so as to obtain an oscillating resonance, the charging of the second capacitor C2 is performed in a sine wave shape. This charging is increased in the inverter circuit 3 to a voltage at which the energy supply does not become insufficient when the transistor Q1 is turned on next time. When the transistor Q1 is turned off, the first resonance capacitor C4 and the second resonance capacitor C5 resonate with the primary winding Tr1a of the inverter transformer Tr1. Then, this resonance current flows through the path of the second resonance capacitor C5, the primary winding Tr1a of the inverter transformer Tr1, the second capacitor C2, and the second resonance capacitor C5, and the second capacitor C2 is charged. An oscillating voltage is generated. At this time, as shown in FIG. 2, the voltage between both ends of the second capacitor C2 is almost equal to the DC voltage at the highest instantaneous voltage portion and the lowest instantaneous voltage portion of the commercial AC power supply e.
[0031]
Then, as the voltage of the first capacitor C1 decreases with respect to the charging voltage of the charging capacitor C3, the voltage of the second capacitor C2 decreases, and the amplitude of the inductor L1 and the second capacitor C2 increases. Further, although the input current decreases, the current flows continuously.
[0032]
As described above, the continuous flow of the input current from the commercial AC power supply e prevents the harmonic component from intervening in the input current.
[0033]
Further, by increasing the fluctuation of the voltage value of the second capacitor C2, as shown in FIG. 3, the crest factor of the lamp current waveform of the fluorescent lamp FL is improved, and the crest factor is improved.
[0034]
Next, another embodiment will be described with reference to FIG.
[0035]
The embodiment shown in FIG. 4 differs from the embodiment shown in FIG. 1 in that the diode D1 is removed and the full-wave rectifier circuit 1 is connected between the first capacitor C1 and the second capacitor C2.
[0036]
As described above, by eliminating the diode D1, the circuit configuration can be simplified while the basic operation is substantially the same.
[0037]
Another embodiment will be described with reference to FIG.
[0038]
The embodiment shown in FIG. 5 differs from the embodiment shown in FIG. 1 in that a second capacitor C2 is connected in parallel to a diode D1.
[0039]
Even in such a configuration, the basic operation is the same as that of the embodiment shown in FIG.
[0040]
Further, another embodiment will be described with reference to FIG.
[0041]
The embodiment shown in FIG. 6 is different from the embodiment shown in FIG. 1 in that a series circuit of a capacitor C11 and a field effect transistor Q2 is connected in parallel with the second capacitor C2, and the field effect transistor Q2 is connected to the second capacitor C2. The control circuit 11 is connected.
[0042]
By controlling the field effect transistor Q2 by the control circuit 11, the substantial combined capacitance with the second capacitor C2 is changed. For example, when the output of the inverter circuit 3 changes due to a temperature change or the like, By changing the combined capacitance of the second capacitor C2 and the capacitor C11, the voltage value surely drops to 0 in the portion where the voltage of the second capacitor C2 is low, and the input current is continued, so that harmonics can be more reliably detected. To prevent.
[0043]
The same effect can be obtained by adding this configuration to the embodiment shown in FIG.
[0044]
Still another embodiment will be described with reference to FIG.
[0045]
The embodiment shown in FIG. 7 differs from the embodiment shown in FIG. 1 in that a thyristor Q3 as a short-circuit means is connected in anti-parallel to the diode D1, and a control circuit 12 is connected to the gate of the thyristor Q3. It is.
[0046]
Normally, the inverter circuit 3 is operated by boosting the voltage due to resonance between the inverter transformer Tr1 of the inverter circuit 3 and the second capacitor C2. For example, when the lamp current of the fluorescent lamp FL increases, the thyristor Q3 Is turned on, a current flows in a direction opposite to that of the diode D1, and the voltage is reduced by resonance between the inverter transformer Tr1 and the first capacitor C1 and the second capacitor C2, and the resonance point is changed from that of the second capacitor C2. To reduce the load on the transistor Q1.
[0047]
Similar effects can be obtained by adding this configuration to the embodiment shown in FIGS.
[0048]
Further, another embodiment will be described with reference to FIGS.
[0049]
The embodiment shown in FIGS. 8 to 10 is different from the embodiment shown in FIGS. 1, 4 and 5 in that a diode is connected in parallel with the series circuit of the charging capacitor C3 and the inductor L1 of the partial smoothing circuit 2. D6 is connected.
[0050]
Then, when charging the charging capacitor C3, the magnetic energy of the inductor L1 is supplied to the charging capacitor C3 via the diode D6, whereby the charging capacitor C3 can be charged. Also, by passing a current through the diode D3, the current flows through the diode D2 only when charging the charging capacitor C3, and the voltage of the transistor Q1 is applied to the diode D3 while the transistor Q1 is off. The voltage applied to the inductor L1 and the diode D2 is reduced, and the size of the element can be reduced.
[0051]
Further, another embodiment will be described with reference to FIG.
[0052]
The embodiment shown in FIG. 11 differs from the embodiment shown in FIG. 8 in that a series circuit of a capacitor C11 and a field-effect transistor Q2 in parallel with the second capacitor C2, similarly to the embodiment shown in FIG. And the control circuit 11 is connected to the field effect transistor Q2.
[0053]
The same effect can be obtained by adding this configuration to the embodiment shown in FIGS. 9 and 10.
[0054]
Still another embodiment will be described with reference to FIG.
[0055]
In the embodiment shown in FIG. 12, a thyristor Q3 as a short-circuit means is connected to the diode D1 in anti-parallel to the embodiment shown in FIG. 8, similarly to the embodiment shown in FIG. The control circuit 12 is connected to the gate of Q3.
[0056]
Note that the same effect can be obtained by adding this configuration to the embodiment shown in FIG.
[0057]
Further, another embodiment will be described with reference to FIGS.
[0058]
The embodiment shown in FIGS. 13 to 15 differs from the embodiment shown in FIGS. 1, 4 and 5 in that a leakage flux type inverter transformer Tr1 is replaced by a parallel connection to a first resonance capacitor C4. Connect the resonance inductor L3, connect the series circuit of the ballast L4 and the primary winding Tr2a of the insulation type transformer Tr2 in parallel with this resonance inductor L3, and connect the fluorescent lamp to the secondary winding Tr2b of the transformer Tr2. FL connected.
[0059]
The function of the inverter transformer Tr1 is distributed to the resonance inductor L3, the ballast L4, and the insulating transformer Tr2, and basically operates in the same manner as in FIGS. 1, 4, and 5.
[0060]
Further, another embodiment will be described with reference to FIG.
[0061]
The embodiment shown in FIG. 16 is different from the embodiment shown in FIG. 13 in that a series circuit of a capacitor C11 and a field-effect transistor Q2 is connected in parallel with the second capacitor C2, similarly to the embodiment shown in FIG. And the control circuit 11 is connected to the field effect transistor Q2.
[0062]
The same effect can be obtained by adding this configuration to the embodiment shown in FIGS. 14 and 15.
[0063]
Still another embodiment will be described with reference to FIG.
[0064]
In the embodiment shown in FIG. 17, a thyristor Q3 as a short-circuit means is connected to the diode D1 in anti-parallel to the embodiment shown in FIG. 13, similarly to the embodiment shown in FIG. The control circuit 12 is connected to the gate of Q3.
[0065]
Note that the same effect can be obtained even if this configuration is added to the embodiment shown in FIG.
[0066]
Another embodiment will be described with reference to FIGS.
[0067]
The embodiment shown in FIGS. 18 to 20 is different from the embodiment shown in FIGS. 13 to 15 in that the charging capacitor C3 and the inductor of the partial smoothing circuit 2 are similar to the embodiment shown in FIGS. A diode D6 is connected in parallel with the series circuit of L1.
[0068]
Further, another embodiment will be described with reference to FIG.
[0069]
The embodiment shown in FIG. 21 is different from the embodiment shown in FIG. 18 in that a series circuit of a capacitor C11 and a field-effect transistor Q2 is provided in parallel with the second capacitor C2, similarly to the embodiment shown in FIG. And the control circuit 11 is connected to the field effect transistor Q2.
[0070]
Even if this configuration is added to the embodiment shown in FIGS. 19 and 20, the same effect can be obtained.
[0071]
Still another embodiment will be described with reference to FIG.
[0072]
In the embodiment shown in FIG. 22, a thyristor Q3 as a short-circuit means is connected to the diode D1 in antiparallel to the embodiment shown in FIG. 18, similarly to the embodiment shown in FIG. The control circuit 12 is connected to the gate of Q3.
[0073]
The same effect can be obtained even if this configuration is added to the embodiment shown in FIG.
[0074]
Another embodiment will be described with reference to FIGS.
[0075]
In the embodiments shown in FIGS. 23 to 25, the insulating transformer Tr2 is eliminated from the embodiment shown in FIGS. 18 to 20, and the capacitor C6 at the other end of the filaments FL1 and FL2 of the fluorescent lamp FL is eliminated. In addition, a starting capacitor C12 is connected to one end side to simplify the configuration.
[0076]
Although the filaments FL1 and FL2 cannot be preheated, the basic operation is the same as in the embodiment shown in FIGS.
[0077]
Further, another embodiment will be described with reference to FIG.
[0078]
The embodiment shown in FIG. 26 differs from the embodiment shown in FIG. 23 in that a series circuit of a capacitor C11 and a field-effect transistor Q2 is connected in parallel to the second capacitor C2, similarly to the embodiment shown in FIG. And the control circuit 11 is connected to the field effect transistor Q2.
[0079]
The same effect can be obtained by adding this configuration to the embodiment shown in FIGS. 24 and 25.
[0080]
Still another embodiment will be described with reference to FIG.
[0081]
In the embodiment shown in FIG. 27, a thyristor Q3 as a short-circuit means is connected to the diode D1 in anti-parallel to the embodiment shown in FIG. 23 in the same manner as the embodiment shown in FIG. The control circuit 12 is connected to the gate of Q3.
[0082]
A similar effect can be obtained even if this configuration is added to the embodiment shown in FIG.
[0083]
Another embodiment will be described with reference to FIGS.
[0084]
The embodiment shown in FIGS. 28 to 30 is different from the embodiment shown in FIGS. 23 to 25 in that the charging capacitor C3 and the inductor of the partial smoothing circuit 2 are similar to the embodiment shown in FIGS. A diode D6 is connected in parallel with the series circuit of L1.
[0085]
Further, another embodiment will be described with reference to FIG.
[0086]
The embodiment shown in FIG. 31 is different from the embodiment shown in FIG. 28 in that a series circuit of a capacitor C11 and a field-effect transistor Q2 is connected in parallel with the second capacitor C2, similarly to the embodiment shown in FIG. And the control circuit 11 is connected to the field effect transistor Q2.
[0087]
The same effect can be obtained by adding this configuration to the embodiment shown in FIGS. 29 and 30.
[0088]
Still another embodiment will be described with reference to FIG.
[0089]
In the embodiment shown in FIG. 31, a thyristor Q3 as a short-circuit means is connected to the diode D1 in anti-parallel to the embodiment shown in FIG. 28 in the same manner as the embodiment shown in FIG. The control circuit 12 is connected to the gate of Q3.
[0090]
The same effect can be obtained by adding this configuration to the embodiment shown in FIG.
[0091]
Next, a load circuit 6 according to another embodiment will be described with reference to FIGS. The load circuit 6 shown in FIGS. 32 to 42 can be used in any of the discharge lamp lighting devices shown in FIGS. 1 and 3 to 31.
[0092]
First, in the load circuit 6 shown in FIG. 33, a starting capacitor C12 and one end of filaments FL1, FL2 of a fluorescent lamp FL are connected to a secondary winding Tr1b of a leakage flux type inverter transformer Tr1.
[0093]
In the load circuit 6 shown in FIG. 34, a preheating capacitor C6 is connected to the other ends of the filaments FL1 and FL2 of the fluorescent lamp FL of the load circuit 6 shown in FIG.
[0094]
Further, the load circuit 6 shown in FIG. 35 connects the primary winding Tr2a of the insulation type transformer Tr2 via the ballast L3, and connects one end of the filaments FL1 and FL2 of the fluorescent lamp FL to the secondary winding Tr2b of the transformer Tr2. And a capacitor C6 is connected to the other end.
[0095]
Further, the load circuit 6 shown in FIG. 36 has a configuration in which the capacitor C12 is connected to the secondary winding Tr2b of the transformer Tr2 of the load circuit 6 shown in FIG. 35, and the capacitor C6 is deleted.
[0096]
The load circuit 6 shown in FIG. 37 has a configuration in which a capacitor C6 is connected between the other ends of the filaments FL1 and FL2 of the fluorescent lamp FL of the load circuit 6 shown in FIG.
[0097]
In the load circuit 6 shown in FIG. 38, the secondary winding Tr2b of the insulating transformer Tr2 is connected to one end of the filaments FL1 and FL2 of the fluorescent lamp FL via the ballast L4, and the other end is connected to the capacitor C6. Things.
[0098]
Further, in the load circuit 6 shown in FIG. 39, a capacitor C12 is connected to one end of the filaments FL1, FL2 instead of the capacitor C6 of the load circuit 6 shown in FIG.
[0099]
Further, the load circuit 6 shown in FIG. 40 has a configuration in which a capacitor C6 is connected to the other ends of the filaments FL1 and FL2 of the load circuit 6 shown in FIG.
[0100]
Further, the load circuit 6 shown in FIG. 41 connects the ballast L4 and the primary winding Tr2a of the insulating transformer Tr2 to the resonance inductor L3, and connects the capacitor C12 and the filaments FL1 and FL1 of the fluorescent lamp FL to the secondary winding Tr2a. One end of FL2 is connected.
[0101]
The load circuit 6 shown in FIG. 42 has a configuration in which a capacitor C6 is connected to the other ends of the filaments FL1 and FL2 of the fluorescent lamp FL of the load circuit 6 shown in FIG.
[0102]
【The invention's effect】
According to the power supply device of the first aspect, the inverter circuit supplies the input current from the first capacitor and the second capacitor when the output level of the rectifier is equal to or higher than the charge level of the charging capacitor, and the output level of the rectifier is Is lower than the charge level of the charging capacitor, an input current is supplied from the partial smoothing circuit, and the switching operation of the switching element causes the parallel resonance circuit and the second resonance capacitor to perform a resonance operation to reduce harmonics and reduce the resonance current. A high frequency output with an improved crest factor can be obtained by pouring into the second capacitor.
[0103]
According to the power supply device of the second aspect, when the output level of the rectifier is equal to or higher than the charge level of the charging capacitor, the inverter circuit supplies the input current from the first capacitor and the second capacitor, and outputs the output level of the rectifier. Is lower than the charge level of the charging capacitor, an input current is supplied from the partial smoothing circuit, and the switching operation of the switching element causes the parallel resonance circuit and the second resonance capacitor to perform a resonance operation to reduce harmonics and reduce the resonance current. A high frequency output with an improved crest factor can be obtained by pouring into the second capacitor.
[0104]
According to the power supply device of the third aspect, the inverter circuit supplies the input current from the first capacitor and the second capacitor when the output level of the rectifying means is equal to or higher than the charging level of the charging capacitor. Is lower than the charge level of the charging capacitor, an input current is supplied from the partial smoothing circuit, and the switching operation of the switching element causes the parallel resonance circuit and the second resonance capacitor to perform a resonance operation to reduce harmonics and reduce the resonance current. A high frequency output with an improved crest factor can be obtained by pouring into the second capacitor.
[0105]
According to the power supply device of the fourth aspect, in addition to the power supply device of the first or third aspect, the power supply device further includes a short-circuit means for short-circuiting the diode in accordance with the output level of the rectifying means. Thus, it is possible to reduce the burden on the switching element.
[0106]
According to the power supply device of the fifth aspect, in addition to the power supply device of any one of the first to fourth aspects, the power supply device further includes a capacitance varying unit that varies the capacitance of the second capacitor. Then, when the voltage of the second capacitor is low, the voltage value is reduced to 0, so that harmonics can be further reduced.
[0107]
According to the power supply device of the sixth aspect, in addition to the power supply device of any one of the first to fifth aspects, since the first resonance capacitor and the second resonance capacitor have substantially the same capacitance, the waveform can be further improved.
[0108]
According to the discharge lamp lighting device of the seventh aspect, since the discharge lamp is provided with the discharge lamp connected to the power supply device of any one of the first to sixth aspects, respective effects can be obtained.
[Brief description of the drawings]
FIG. 1 is a circuit diagram showing one embodiment of a discharge lamp lighting device according to the present invention.
FIG. 2 is a waveform chart showing a voltage of a second capacitor according to the first embodiment;
FIG. 3 is a waveform chart showing a lamp current of the fluorescent lamp.
FIG. 4 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.
FIG. 5 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.
FIG. 6 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.
FIG. 7 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.
FIG. 8 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.
FIG. 9 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.
FIG. 10 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.
FIG. 11 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.
FIG. 12 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.
FIG. 13 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.
FIG. 14 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.
FIG. 15 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.
FIG. 16 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.
FIG. 17 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.
FIG. 18 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.
FIG. 19 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.
FIG. 20 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.
FIG. 21 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.
FIG. 22 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.
FIG. 23 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.
FIG. 24 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.
FIG. 25 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.
FIG. 26 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.
FIG. 27 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.
FIG. 28 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.
FIG. 29 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.
FIG. 30 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.
FIG. 31 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.
FIG. 32 is a circuit diagram showing a discharge lamp lighting device according to another embodiment of the present invention.
FIG. 33 is a circuit diagram showing a load circuit according to another embodiment of the present invention;
FIG. 34 is a circuit diagram showing a load circuit according to another embodiment of the present invention;
FIG. 35 is a circuit diagram showing a load circuit according to another embodiment of the present invention;
FIG. 36 is a circuit diagram showing a load circuit according to another embodiment of the present invention;
FIG. 37 is a circuit diagram showing a load circuit according to another embodiment of the present invention;
FIG. 38 is a circuit diagram showing a load circuit according to another embodiment of the present invention;
FIG. 39 is a circuit diagram showing a load circuit according to another embodiment of the present invention;
FIG. 40 is a circuit diagram showing a load circuit according to another embodiment of the present invention.
FIG. 41 is a circuit diagram showing a load circuit according to another embodiment of the present invention;
FIG. 42 is a circuit diagram showing a load circuit according to another embodiment of the present invention;
[Explanation of symbols]
1 Full-wave rectifier circuit as rectifier
2 Partial smoothing circuit
3 Inverter circuit
4 Parallel resonance circuit
C1 First capacitor
C2 Second capacitor
C3 Charging capacitor
C4 First resonance capacitor
C5 Second resonance capacitor
D1 diode
e Commercial AC power supply
Fluorescent lamp as FL discharge lamp
L1 inductor
Q1 Transistor as switching element
Q3 Thyristor as short-circuit means
Tr Inverter transformer as resonant inductor

Claims (7)

Rectifying means for rectifying alternating current from an alternating current power supply;
A first capacitor connected in parallel to an output terminal of the rectifier,
A diode connected in series with a forward polarity to one end of the first capacitor;
A second capacitor connected in parallel to the first capacitor via the diode;
A partial smoothing circuit having an inductance element and a charging capacitor, connected in parallel to the second capacitor that charges the charging capacitor with a voltage lower than the maximum instantaneous voltage value of the output of the rectifier,
A parallel resonance circuit having a first resonance capacitor and a resonance inductor, a switching element connected in series to the parallel resonance circuit, and a second resonance capacitor connected in parallel to the switching element and improving the crest factor And a inverter circuit connected in parallel with the partial smoothing circuit and generating a high-frequency voltage by the switching operation of the switching element. A first capacitor connected to an AC power supply;
Rectifying means connected to the first capacitor;
A second capacitor connected to the rectifier,
A partial smoothing circuit having an inductance element and a charging capacitor, connected in parallel to the second capacitor that charges the charging capacitor with a voltage lower than the maximum instantaneous voltage value of the output of the rectifier,
A parallel resonance circuit having a first resonance capacitor and a resonance inductor, a switching element connected in series to the parallel resonance circuit, and a second resonance capacitor connected in parallel to the switching element and improving the crest factor And a inverter circuit connected in parallel with the partial smoothing circuit and generating a high-frequency voltage by the switching operation of the switching element. Rectifying means for rectifying alternating current from an alternating current power supply;
A first capacitor connected in parallel to an output terminal of the rectifier,
A diode connected to the first capacitor;
A second capacitor connected in parallel with the diode;
In parallel with the first capacitor via the second capacitor and the diode having an inductance element and a charging capacitor, and charging the charging capacitor with a voltage lower than the maximum instantaneous voltage value of the output of the rectifier. A connected partial smoothing circuit,
A parallel resonance circuit having a first resonance capacitor and a resonance inductor, a switching element connected in series to the parallel resonance circuit, and a second resonance capacitor connected in parallel to the switching element and improving the crest factor And a inverter circuit connected in parallel with the partial smoothing circuit and generating a high-frequency voltage by the switching operation of the switching element. 4. The power supply device according to claim 1, further comprising a short-circuit means for short-circuiting a diode in accordance with an output level of the rectifier. The power supply device according to any one of claims 1 to 4, further comprising capacitance changing means for changing the capacitance of the second capacitor. 6. The power supply device according to claim 1, wherein the first resonance capacitor and the second resonance capacitor have substantially the same capacitance. A power supply device according to any one of claims 1 to 6,
A discharge lamp lighting device, comprising: a discharge lamp connected to the power supply device.

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