JP3480259B2 - Power supply - Google Patents

Description

Detailed Description of the Invention

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a power supply device in which a switching circuit that performs a plurality of power conversions shares a switching element, and more specifically, a chopper circuit improves input distortion from an AC power supply and a load circuit. Relates to a power supply device including an inverter circuit that supplies a low frequency output synchronized with an AC power supply.

[0002]

[Prior art]

(Conventional Example 1) FIG. 24 shows a conventional power supply device (Japanese Patent Application No. 1-10).
5181 and JP-A-2-282809). This circuit includes a step-up chopper circuit for improving input current distortion by switching elements Q1 and Q2, an inductor L1 and diodes D5 and D6, and a step-down chopper circuit for load current limiting by switching elements Q1 to Q4 and an inductor L2. There is. The circuit configuration will be described below.

In parallel with the smoothing capacitor C, a diode D
1, D2 series circuit, diodes D3, D4 series circuit, diodes D5, D6 series circuit, switching elements Q1, Q2 series circuit, switching elements Q3, Q4
The series circuit of is connected. Switching element Q1,
The connection point of Q2 and the connection points of the diodes D1 and D2 are connected. Further, the connection point of the switching elements Q3 and Q4 and the connection point of the diodes D3 and D4 are connected. A series circuit of the inductor L2 and the load circuit Z is connected between the connection point of the switching elements Q1 and Q2 and the connection point of the switching elements Q3 and Q4. Diode D5,
Between the connection point of D6 and the connection point of the switching elements Q1 and Q2, an AC power supply P connected via a filter circuit F and an inductor L1 are connected in a series circuit.

Here, a control circuit (not shown) outputs an ON / OFF signal to the gate electrodes of the switching elements Q1 to Q4 to control the ON / OFF of the switching elements Q1 to Q4, and the AC power source is a positive half. In the cycle, the switching element Q1 is alternately turned on / off, the switching elements Q2 and Q3 are turned off, and the switching element Q4 is turned on. On the other hand, in the negative half cycle of the AC power supply, the switching element Q2 is alternately turned on / off, the switching elements Q1 and Q4 are turned off, and the switching element Q3 is turned on.

The operation of the conventional circuit shown in FIG. 24 will be described with reference to FIG. First, in a positive half cycle of the AC power supply P, when the switching elements Q1 and Q4 are on and the switching elements Q2 and Q3 are off, as shown in FIG. 25 (a), the AC power supply P, the filter circuit F, and the diode D.
5, current flows through the path of the switching element Q1 and the inductor L1, and energy is stored in the inductor L1. In addition, the smoothing capacitor C to the switching element Q
1, inductor L2, load circuit Z, switching element Q
A current flows through the path of No. 4, the voltage of the smoothing capacitor C is stepped down by the inductor L2, and is supplied to the load circuit Z. Energy is stored in the inductor L2 due to the current flowing through the inductor L2.

Next, when only the switching element Q1 is turned off, a voltage is generated across the inductor L1 due to the energy stored in the inductor L1, and this voltage is generated by the AC power source P.
Is superposed on the voltage of and the smoothing capacitor C is charged through the diode D2. That is, as shown in FIG. 25B, the AC power supply P, the filter circuit F, and the diode D.
5, smoothing capacitor C, diode D2, inductor L
A current flows through the path of No. 1, and the energy of the inductor L1 is released. As a result, a high-frequency current constantly flows from the AC power supply P, and the input circuit distortion is improved by shaping the waveform of the high-frequency current by the filter circuit F. Further, the smoothing capacitor C can obtain a voltage higher than the peak value of the AC power source P. Furthermore, the regenerative current due to the energy stored in the inductor L2 is
2, load circuit Z, switching element Q4, diode D
It flows in the route of 2. Thereafter, the switching element Q1 is turned on and off at a high frequency to repeat the operations of FIGS. 25A and 25B, and the load circuit Z is supplied with a unidirectional DC voltage.

Next, in the negative half cycle of the AC power supply P, when the switching elements Q1 and Q4 are off and the switching elements Q2 and Q3 are on, as shown in FIG. 25 (c), the AC power supply P and the filter circuit. F, inductor L
1, a current flows through the path of the switching element Q2 and the diode D6, and energy is stored in the inductor L1. In addition, the smoothing capacitor C to the switching element Q
3, load circuit Z, inductor L2, switching element Q
A current flows through the second path, the voltage of the smoothing capacitor C is stepped down by the inductor L2 and is supplied to the load circuit Z. Energy is stored in the inductor L2 due to the current flowing through the inductor L2.

Next, when only the switching element Q2 is turned off, a voltage is generated across the inductor L1 due to the energy stored in the inductor L1, and this voltage is applied to the AC power source P.
Is superposed on the voltage of and is charged in the smoothing capacitor C via the diode D1. That is, as shown in FIG. 25D, the AC power supply P, the filter circuit F, the inductor L1,
A current flows through the path of the diode D1, the smoothing capacitor C, and the diode D6, and the energy of the inductor L1 is released. As a result, a high-frequency current is always flowing from the AC power supply P, and this is filtered by the filter circuit F.
The input current distortion is improved by performing the waveform shaping by. Further, the smoothing capacitor C can obtain a voltage higher than the peak value of the AC power source P. Furthermore, inductor L
The regenerative current due to the stored energy of 2 is inductor L2,
It flows in the path of the diode D1, the switching element Q3, and the load circuit Z. Thereafter, the switching element Q2 is turned on and off at a high frequency to repeat the operations shown in FIGS. By the above operation, the load circuit Z is connected to the AC power source P
A rectangular wave voltage whose polarity is inverted is supplied in synchronization with each half cycle of.

As described above, in the positive half cycle of the AC power supply, the switching element Q1 operates as both the switching element of the chopper circuit and the switching element of the inverter circuit. On the other hand, in the half cycle when the AC power supply is negative,
The switching element Q2 operates as both the switching element of the chopper circuit and the switching element of the inverter circuit.

(Conventional Example 2) The conventional example of FIG. 24 is provided with a step-up chopper circuit for improving the input distortion and a step-down chopper for limiting the load current, whereas as shown in FIG. 19, switching elements Q1 and Q2 are provided. Inductor L1 and diode D
As a conventional example, a power supply device including a step-up / down chopper circuit for improving input distortion by 1, D2, D5 to D10 and a step-down chopper circuit for limiting a load current by switching elements Q1 to Q4 and an inductor L2 can be considered. The circuit configuration will be described below. In the conventional example of FIG. 19, a series circuit of diodes D1 and D2 and a series circuit of diodes D3 and D4 are connected in antiparallel with a smoothing capacitor C, and a series circuit of switching elements Q3 and Q4 is connected in parallel with a smoothing capacitor C. ing. The series circuit of the diodes D5 and D6 and the series circuit of the switching elements Q1 and Q2 are connected in antiparallel, and the diode D7 and the switching elements Q1 and Q2 are connected.
2. The circuit in which the diode D8 is connected in series in this order and the series circuit of the diodes D9 and D10 are the smoothing capacitor C.
Are connected in anti-parallel with. Also, the diodes D1 and D
The connection point of 2 and the connection points of the switching elements Q1 and Q2 are connected, and the connection point of the diodes D3 and D4 and the connection point of the switching elements Q3 and Q4 are connected. The inductor L1 is connected between the connection point of the switching elements Q1 and Q2 and the connection point of the diodes D9 and D10, and between the connection point of the switching elements Q1 and Q2 and the connection point of the switching elements Q3 and Q4. A series circuit including an inductor L2 and a load circuit Z is connected, and an AC power supply P is connected between a connection point of the diodes D5 and D6 and a connection point of the diodes D9 and D10.

The operation of the conventional circuit shown in FIG. 19 is shown in FIGS.
7 will be described. First, in the positive half cycle of the AC power supply P, when the switching elements Q1 and Q4 are on and the switching elements Q2 and Q3 are off, FIG.
As shown in, a current flows through the path of the AC power supply P, the filter circuit F, the diode D5, the switching element Q1, and the inductor L1, and energy is stored in the inductor L1. Further, a current flows from the smoothing capacitor C through the path of the diode D7, the switching element Q1, the inductor L2, the load circuit Z, and the switching element Q4, and the voltage of the smoothing capacitor C is stepped down by the inductor L2 and supplied to the load circuit Z. . Energy is stored in the inductor L2 due to the current flowing through the inductor L2.
Next, when only the switching element Q1 is turned off, a voltage is generated across the inductor L1 due to the energy stored in the inductor L1, and the smoothing capacitor C is charged via the diode D9. That is, as shown in FIG. 26B, a current flows through the path of the inductor L1, the diode D9, the smoothing capacitor C, the diode D2, and the inductor L1, and the energy of the inductor L1 is released. As a result, the current from the AC power source P does not flow directly into the smoothing capacitor C, but the current that once flows in the inductor L1 is accumulated as energy, and the regenerative current due to the accumulated energy flows into the smoothing capacitor C. Inrush current when P is turned on can be prevented. Further, the smoothing capacitor C can also obtain a voltage lower than the peak value of the AC power source P. Furthermore, the regenerative current due to the energy stored in the inductor L2 flows through the route of the inductor L2, the load circuit Z, the switching element Q4, and the diode D2. Thereafter, the switching element Q1 is turned on and off at a high frequency to repeat the operations shown in FIGS. 26A and 26B, and the load circuit Z is supplied with a unidirectional DC voltage.

Next, in the negative half cycle of the AC power supply P, when the switching elements Q1 and Q4 are off and the switching elements Q2 and Q3 are on, as shown in FIG. 27 (c), the AC power supply P and the filter circuit. F, inductor L
1, a current flows through the path of the switching element Q2 and the diode D6, and energy is stored in the inductor L1. In addition, the smoothing capacitor C to the switching element Q
3, load circuit Z, inductor L2, switching element Q
2. A current flows through the path of the diode D8, the voltage of the smoothing capacitor C is stepped down by the inductor L2, and is supplied to the load circuit Z. Energy is stored in the inductor L2 due to the current flowing through the inductor L2.

Next, when only the switching element Q2 is turned off, a voltage is generated across the inductor L1 due to the energy stored in the inductor L1, and the smoothing capacitor C is charged via the diode D1. That is, FIG.
As shown in (d), inductor L1 and diode D
1, a current flows through the path of the smoothing capacitor C and the diode D10, and the energy of the inductor L1 is released.
As a result, the current from the AC power source P does not flow directly into the smoothing capacitor C, but the current that once flows in the inductor L1 is accumulated as energy, and the regenerative current due to the accumulated energy flows into the smoothing capacitor C. Inrush current when P is turned on can be prevented. Further, the smoothing capacitor C can also obtain a voltage lower than the peak value of the AC power source P. Furthermore, the regenerative current due to the energy stored in the inductor L2 causes the inductor L2, the diode D1,
It flows in the path of the switching element Q3 and the load circuit Z. Thereafter, the switching element Q2 is turned on and off at a high frequency to repeat the operations shown in FIGS. Through the above operation, the load circuit Z is supplied with the rectangular wave voltage whose polarity is inverted in synchronization with each half cycle of the AC power supply P.

[0014]

In the above-mentioned conventional example 1,
The switching element is shared between the boost chopper circuit and the step-down chopper circuit.However, since the current of the boost chopper circuit and the current of the step-down chopper circuit are superimposed and flow in the switching element that has a dual function, the current withstand amount increases. The cost reduction effect is diminished due to the decrease in the number of elements due to the dual use. In addition, since the control signal of the switching element is also used, the independence of control for each circuit is lost. For example, when controlling to keep the output power constant, the input power is larger than the output power. Or
Alternatively, it may be too small. When the input power becomes excessive with respect to the output power, excess energy is stored in the smoothing capacitor, the voltage across the smoothing capacitor rises, the voltage applied to the component increases, and stress is added to the component in some cases. It will be.

Such a phenomenon is caused, for example, when the conventional circuit is applied to a lighting device for a high pressure discharge lamp, the impedance of the load is low in the starting process of the high pressure discharge lamp,
In addition, a large current needs to flow to the load, which is particularly remarkable. That is, a constant on-duty must be provided in order to pass the output current, but the output impedance is low because the load impedance is low. On the other hand, since the input power is an amount according to the on-duty, the input power becomes excessive.

On the other hand, in the conventional example 2, since the switching element is shared by the step-up / step-down chopper circuit and the step-down chopper circuit, the voltage of the smoothing capacitor can be set lower than the power supply voltage, and further, when the power is turned on. There is an advantage that inrush current can be prevented. However, since the current withstanding capability of the dual-purpose element increases, which is also a drawback of Conventional Example 1, cost reduction cannot be achieved, and independence of control for each circuit cannot be achieved.

The present invention is intended to solve such a problem, and an object thereof is to increase a switching current flowing in a switching element which is also used as two power supply circuits such as a chopper circuit and an inverter circuit. Another object of the present invention is to provide a power supply device in which the control of the chopper circuit and the inverter circuit is maintained independent of each other. Also,
By using a buck-boost chopper circuit and a step-down chopper circuit that also function as switching elements, it is possible to increase the degree of freedom in setting the smoothing capacitor voltage with respect to the power supply voltage and prevent not only the inrush current at power-on, but also each. The present invention provides a power supply device that has an independence from the circuit of (1) and operates to cancel the current of the step-up / down chopper circuit and the current of the step-down chopper circuit to reduce the current withstanding capacity of the switching element.

[0018]

In order to achieve the above object, the present invention has at least two power conversion circuits each having at least one switching element or rectifying element. At least one of the rectifying elements is also used as an element constituting at least two different power converting circuits, and at least one of the currents from the different power converting circuits flowing into the combined switching element or rectifying element is at least one power converting element. The present invention is characterized by comprising a control means having at least a period in which a current flowing in from a circuit has a polarity opposite to that of a current flowing in from at least one other power conversion circuit and flows in directions canceling each other. This allows
According to the present invention, it is possible to reduce the current flowing through the switching element that is also used for the plurality of switching circuits. In addition, control of a plurality of switching circuits can be made independent.

[0019]

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS FIG. 1 shows a preferred embodiment of the present invention, in which the first and second switching elements Q1 and Q2, which are respectively equipped with reverse conducting elements in parallel, are arranged in the same forward direction. A circuit connected in series and a circuit in which third and fourth switching elements Q3 and Q4 each having a reverse-direction energization element in parallel are connected in series so that their forward directions match with each other are connected in parallel with the capacitor EC. connection,
A first rectifying element D1 having the same polarity as an energizing element provided with a circuit in which first and second rectifying elements D5 and D6 are connected in series with the first to fourth switching elements Q1 to Q4 in parallel.
Is connected in parallel to the capacitor EC such that one end of the two rectifiers matches one end of the first and third switching elements Q1 and Q3, and the connection point of the two rectifying elements D5 and D6 and the first and second switching elements. Between the connection points Q1 and Q2 of
An AC power supply AC via a filter (not shown) and a series circuit of the first inductor L1 are connected to each other, and the connection point of the first and second switching elements Q1 and Q2 and the third and fourth switching elements Q3 and Q4 are connected. A circuit configuration is provided in which a series circuit of the load circuit L and the second inductor L2 is connected between the connection point and the connection point. AC power supply AC and first inductor L1
Is connected to the connection point of the first and second switching elements Q1 and Q2 on the AC power supply AC side, and the load circuit L
In the series circuit of the second inductor L2 and the second inductor L2, the load circuit L side is connected to the connection point of the first and second switching elements Q1 and Q2, which stabilizes the potential of the load circuit L at high frequencies. The operation may be reversed.

FIG. 11 shows another embodiment of the present invention, in which first and second switching elements Q1 and Q2 each having a reverse current-carrying element in parallel are connected in series so that their forward directions coincide with each other. And the third and fourth switching elements Q3, which are provided with the reverse-direction energizing element in parallel, respectively.
A circuit in which Q4 is connected in series so that the forward directions match,
A circuit in which fifth and sixth switching elements Q5 and Q6, each of which has a reverse current-carrying element in parallel, are connected in series so that their forward directions coincide with each other, is connected in parallel to the capacitor EC with the same polarity, Second switching element Q
Connection point of 1, Q2 and fifth and sixth switching elements Q
A series circuit of an AC power supply AC and a first inductor L1 is connected between the connection point of the third and fourth switching elements Q3 and Q4, and the connection point of the first and second switching elements Q1 and Q2 and the third and fourth switching elements. A circuit configuration is provided in which a series circuit of the load circuit L and the second inductor L2 is connected between the connection point of the elements Q3 and Q4.

Regardless of which circuit configuration is adopted, it is preferable that the switching elements having the reverse-direction energization elements arranged in parallel are field-effect transistors each having a reverse-direction parasitic diode.
Further, a diode may be connected in antiparallel to the bipolar transistor. Preferred embodiments of the current loops in these circuit configurations will be listed below.
Before that, the period during which a general-purpose current loop that repeatedly appears in the future occurs will be defined in advance.

A1) The current of the first power conversion circuit is the first
Of a closed loop composed of the inductor, the fifth rectifying element, the capacitor, the second field effect transistor, and the power supply, and the current of the second power conversion circuit is the capacitor, the third field effect transistor, and the third field effect transistor. 2 inductors,
A period in which at least a period in which a closed circuit including the load circuit and the second field effect transistor is formed is satisfied at the same time. In the following description, this period is simply referred to as [A1].

A2) The current of the first power conversion circuit is the first
Forming a closed loop composed of the inductor, the power supply, the first field effect transistor, the capacitor, and the sixth rectifying element, and the current of the second power conversion circuit, the capacitor, the first field effect transistor, and the load. A period having at least a period in which a closed loop including the circuit, the second inductor, and the fourth field effect transistor is simultaneously established. In the following description, this period is simply described as [A2].

B1) A state in which the current of the first power conversion circuit forms a closed loop composed of a power supply, a first inductor, a fifth rectifying element, and a first field effect transistor, and a second power conversion circuit. Current of the second inductor,
A period having at least a period in which a closed loop including the load circuit, the first field effect transistor, and the third field effect transistor is simultaneously established. In the following description, this period will be simply referred to as [B1].

B2) A state in which the current of the first power conversion circuit forms a closed loop composed of a power supply, a second field effect transistor, a sixth rectifying element, and a first inductor, and a second power conversion. The current in the circuit is the second inductor,
A period having at least a period in which a closed loop including the fourth field-effect transistor, the second field-effect transistor, and the load circuit is simultaneously established. In the following description, this period is simply described as [B2].

C1) The current of the first power conversion circuit is the first
Inductor, fifth rectifying element, capacitor, and second
Forming a closed loop composed of a field effect transistor and a power source, and a current in the second power conversion circuit is a closed loop composed of a second inductor, a load circuit, a second field effect transistor, and a fourth field effect transistor. And a state that constitutes a period that has at least a period that is satisfied at the same time. In the following description, this period is simply described as [C1].

C2) The current of the first power conversion circuit is the first
Of the second power conversion circuit, a state of forming a closed loop including the inductor, the power supply, the l-th field effect transistor, the capacitor, the sixth rectifying element, and the first inductor, A period having at least a period in which a closed loop including the third field effect transistor, the first field effect transistor, and the load circuit is simultaneously established. In the following description, this period is simply described as [C2].

D1) A state in which the current of the first power conversion circuit forms a certain closed loop from the power supply, the first inductor, the fifth rectifying element, and the first field effect transistor, and the second power conversion. The current in the circuit is the second inductor,
Load circuit, first field effect transistor, capacitor,
And a state that forms a closed loop including the fourth field effect transistor at least simultaneously. In the following description, this period will be simply referred to as [D1].

D2) A state in which the current of the first power conversion circuit forms a closed loop consisting of a power supply, a second field effect transistor, a sixth rectifying element, and a first inductor, and a second power conversion. The current in the circuit is the second inductor,
A period having at least a period in which a state forming a certain closed loop from the third field effect transistor, the capacitor, the second field effect transistor, and the load circuit is simultaneously established. In the following description, this period is simply described as [D2].

Based on the above definition, each of the following embodiments (α1) to (α3) and (β1) to (β6)
In the current loop of FIG. 12, (γ1) to (γ6),
1) to (δ6) correspond to the current loops of FIG. 13, respectively. In the following description, "when the polarity of the power supply is negative" means "the first and second SW elements Q1 and Q2 of the power supply".
When the polarity of the connection point side of the power source is positive, the phrase "when the polarity of the power source is positive" means that the polarity of the connection point side of the first and second SW elements Q1 and Q2 of the power source is positive. "When". The embodiment including the following control devices can be applied to the circuit of FIG. 1 and the circuit of FIG. 11.

(Α1) When the polarity of the power source is negative, [A1]
→ Operates in the order of [B1], and when the polarity of the power supply is positive, [A
2] → [B2] An embodiment including a control device configured to operate in this order. (Α2) When the polarity of the power source is negative, the operation is performed in the order of [A1] → [C1], and when the polarity of the power source is positive, [A2] → [C2]
2] An embodiment including a control device configured to operate in the order of [2]. (Α3) When the polarity of the power source is negative, the operation is performed in the order of [A1] → [D1], and when the polarity of the power source is positive, [A2] → [D
2] An embodiment including a control device configured to operate in the order of [2].

(Β1) When the polarity of the power source is negative, [A1]
An embodiment provided with a control device configured to operate in the order of [B1] → [C1] and to operate in the order of [A2] → [B2] → [C2] when the polarity of the power source is positive. (Β2) When the polarity of the power source is negative, [A1] → [B1] →
It operates in the order of [D1], and when the polarity of the power source is positive, [A
2] → [B2] → [D2] in this order, an embodiment including a control device configured to operate. (Β3) When the polarity of the power source is negative, [A1] → [C1] →
It operates in the order of [B1], and when the polarity of the power source is positive, [A
2]->[C2]-> [B2]. (Β4) When the polarity of the power supply is negative, [A1] → [C1] →
It operates in the order of [D1], and when the polarity of the power source is positive, [A
2]->[C2]-> [D2]. (Β5) When the polarity of the power source is negative, [A1] → [D1] →
It operates in the order of [B1], and when the polarity of the power source is positive, [A
2]->[D2]-> [B2]. (Β6) When the polarity of the power source is negative, [A1] → [D1] →
It operates in the order of [C1], and when the polarity of the power supply is positive, [A
2]->[D2]-> [C2].

(Γ1) When the polarity of the power source is negative, [A1]
→ [B1] → [C1] → [D1], and when the power supply polarity is positive, [A2] → [B2] → [C2] → [D
2] An embodiment including a control device configured to operate in the order of [2]. (Γ2) When the polarity of the power source is negative, [A1] → [B1] →
An embodiment provided with a controller configured to operate in the order of [D1] → [C1] and to operate in the order of [A2] → [B2] → [D2] → [C2] when the polarity of the power source is positive. Form. (Γ3) When the polarity of the power source is negative, [A1] → [C1] →
[B1] → [D1] in order, and when the polarity of the power source is positive, [A2] → [C2] → [B2] → [D2] Form. (Γ4) When the polarity of the power source is negative, [A1] → [C1] →
An embodiment provided with a controller configured to operate in the order of [D1] → [B1] and to operate in the order of [A2] → [C2] → [D2] → [B2] when the polarity of the power source is positive. Form. (Γ5) When the polarity of the power source is negative, [A1] → [D1] →
An embodiment provided with a controller configured to operate in the order of [B1] → [C1] and to operate in the order of [A2] → [D2] → [B2] → [C2] when the polarity of the power source is positive. Form. (Γ6) When the polarity of the power source is negative, [A1] → [D1] →
An embodiment provided with a control device configured to operate in the order of [C1] → [B1] and to operate in the order of [A2] → [D2] → [C2] → [B2] when the polarity of the power source is positive. Form.

(Δ1) When the polarity of the power source is negative, [A1]
→ [B1] → [C1] → [B2] operates in this order, and when the polarity of the power source is positive, [A2] → [B2] → [C2] → [B
2] An embodiment including a control device configured to operate in the order of [2]. (Δ2) When the polarity of the power source is negative, [A1] → [B1] →
An embodiment provided with a control device configured to operate in the order of [D1] → [B1] and to operate in the order of [A2] → [B2] → [D2] → [B2] when the polarity of the power source is positive. Form. (Δ3) When the polarity of the power source is negative, [A1] → [C1] →
[B1] → [C1] in order, and when the polarity of the power source is positive, [A2] → [C2] → [B2] → [C2] Form. (Δ4) When the power supply polarity is negative, [A1] → [C1] →
An embodiment provided with a control device configured to operate in the order of [D1] → [C1] and to operate in the order of [A2] → [C2] → [D2] → [C2] when the polarity of the power source is positive. Form. (Δ5) When the polarity of the power source is negative, [A1] → [D1] →
[B1] → [D1] in order, and when the polarity of the power source is positive, [A2] → [D2] → [B2] → [D2] Form. (Δ6) When the polarity of the power supply is negative, [A1] → [D1] →
An embodiment provided with a control device configured to operate in the order of [C1] → [D1] and to operate in the order of [A2] → [D2] → [C2] → [D2] when the polarity of the power source is positive. Form.

Next, preferred embodiments of the specific switching procedure will be listed below, but before that, a general-purpose switching period that will repeatedly appear in the future will be defined in advance. a1) A period in which the second field effect transistor Q1 and the third field effect transistor Q3 are turned on. In the following description, this period is simply described as [a1]. a2) A period in which the first field effect transistor Q1 and the fourth field effect transistor Q4 are turned on. In the following description, this period is simply described as [a2]. b1) A period in which the first field effect transistor Q1 and the third field effect transistor Q3 are turned on. In the following description, this period will be simply referred to as [b1]. b2) A period in which the second field effect transistor Q2 and the fourth field effect transistor Q4 are turned on. In the following description, this period is simply described as [b2]. c1) A period in which the first field effect transistor Q1 is turned on. In the following description, this period is simply referred to as [c1]. c2) A period in which the second field effect transistor Q2 is turned on. In the following description, this period is simply described as [c2]. d1) A period in which the second field effect transistor Q2 is turned on. In the following description, this period is simply described as [d1]. d2) A period in which the first field effect transistor Q1 is turned on. In the following description, this period is simply described as [d2]. e1) A period during which the third field effect transistor Q3 is turned on. In the following description, this period is simply described as [e1]. e2) A period in which the fourth field effect transistor Q4 is turned on. In the following description, this period is simply referred to as [e2]. f) A period in which the first to fourth field effect transistors Q1 to Q4 are turned off. In the following description, this period is simply referred to as [f].

On the premise of the above definitions, the respective embodiments listed below correspond to FIGS. 14 to 18. Also,
In the following description, "when the polarity of the power source is negative" means "when the polarity of the connection point side of the first and second SW elements Q1 and Q2 of the power source is negative". "When the polarity of is positive" means "when the polarity of the connection point side of the first and second SW elements Q1 and Q2 of the power source is positive". The embodiment including the following control devices can be applied to the circuit of FIG. 1 and the circuit of FIG. 11.

(3A) When the polarity of the power source is negative, [a1]
→ Operates in the order of [e1], and when the polarity of the power supply is positive, [a
2] → [e2] Embodiment provided with the control device comprised so that it may operate | move in order. (3B) When the polarity of the power source is negative, the operation proceeds in the order of [a1] → [b1], and when the polarity of the power source is positive, [a2] → [b
2] An embodiment including a control device configured to operate in the order of [2].

(4C) When the polarity of the power source is negative, [a1]
An embodiment provided with a control device configured to operate in the order of [b1] → [e1] and to operate in the order of [a2] → [b2] → [e2] when the polarity of the power source is positive. (4J) When the polarity of the power supply is negative, [a1] → [e1] →
It operates in the order of [b1], and when the polarity of the power supply is positive, [a
2]->[e2]-> [b2].

(1) When the polarity of the power source is negative, [a1] →
Operates in the order of [f], and when the polarity of the power source is positive, [a2]
-> Embodiment provided with the control device comprised so that it may operate | move in order of [f]. (3C) When the polarity of the power source is negative, the operation proceeds in the order of [a1] → [c1], and when the polarity of the power source is positive, [a2] → [c
2] An embodiment including a control device configured to operate in the order of [2].

(3C ') When the polarity of the power source is negative, [a
1] → [c1] → [f], and when the polarity of the power source is positive, the controller is configured to operate in the order of [a2] → [c2] → [f] . (3C ") When the polarity of the power supply is negative, [a1] → [f] →
It operates in the order of [c1], and when the polarity of the power source is positive, [a
2]->[f]-> [c2] Embodiment which equips with a control device comprised so that it may operate | move in order.

(4B) When the polarity of the power source is negative, [a1]
An embodiment provided with a control device configured to operate in the order of [b1] → [d1] and to operate in the order of [a2] → [b2] → [d2] when the polarity of the power source is positive. (4K) When the polarity of the power supply is negative, [a1] → [e1] →
It operates in the order of [d1], and when the polarity of the power source is positive, [a
2]->[e2]-> [d2].

(3A ') When the polarity of the power source is negative, [a
1] → [e1] → [f], and when the polarity of the power source is positive, the controller is configured to operate in the order of [a2] → [e2] → [f] . (3B ') [a1] → [b1] when the polarity of the power supply is negative
→ Operates in the order of [f], and when the polarity of the power supply is positive, [a
2] → [b2] → [f] An embodiment including a control device configured to operate in this order.

(4A) [a1] when the polarity of the power supply is negative
An embodiment including a control device configured to operate in the order of [b1] → [c1] and to operate in the order of [a2] → [b2] → [c2] when the polarity of the power source is positive. (4L) When the polarity of the power supply is negative, [a1] → [e1] →
It operates in the order of [c1], and when the polarity of the power source is positive, [a
2] → [e2] → [c2] An embodiment including a control device configured to operate in this order.

(4A1) When the polarity of the power supply is negative, [a
1] → [b1] → [c1] → [f], and when the power supply polarity is positive, [a2] → [b2] → [c2] →
An embodiment including a control device configured to operate in the order of [f]. (4A2) [a1] → [b1] when the polarity of the power supply is negative
→ [f] → [c1] in order, and when the polarity of the power source is positive, [a2] → [b2] → [f] → [c2] Form of.

(4C1) When the polarity of the power source is negative, [a
1] → [b1] → [e1] → [f], and when the power supply polarity is positive, [a2] → [b2] → [e2] →
An embodiment including a control device configured to operate in the order of [f]. (4J1) [a1] → [e1] when the polarity of the power supply is negative
->[B1]-> [f] operates in this order, and a control device configured to operate in the order of [a2]->[e2]->[b2]-> [f] when the polarity of the power supply is positive Form of.

(4L1) When the polarity of the power source is negative, [a
1] → [e1] → [c1] → [f], and when the power supply polarity is positive, [a2] → [e2] → [c2] →
An embodiment including a control device configured to operate in the order of [f]. (4L2) [a1] → [e1] when the polarity of the power supply is negative
->[F]-> [c1] are operated in this order, and when the polarity of the power source is positive, a control device configured to operate in the order of [a2]->[e2]->[f]-> [c2] is implemented. Form of.

(4D) When the polarity of the power source is negative, [a1]
An embodiment comprising a control device configured to operate in the order of [d1] → [e1], and to operate in the order of [a2] → [d2] → [e2] when the polarity of the power source is positive. (4F) When the polarity of the power source is negative, [a1] → [d1] →
It operates in the order of [b1], and when the polarity of the power supply is positive, [a
2]->[d2]-> [b2].

(2A) When the polarity of the power source is negative, [a1]
An embodiment provided with a control device configured to operate in the order of [d1] → [f] and to operate in the order of [a2] → [d2] → [f] when the power supply polarity is positive. (4E) When the polarity of the power source is negative, [a1] → [d1] →
It operates in the order of [c1], and when the polarity of the power source is positive, [a
2]->[d2]-> [c2].

(4E1) When the polarity of the power source is negative, [a
1] → [d1] → [c1] → [f], and when the power supply polarity is positive, [a2] → [d2] → [c2] →
An embodiment including a control device configured to operate in the order of [f]. (4E2) [a1] → [d1] when the polarity of the power supply is negative
->[F]-> [c1] are operated in this order, and when the polarity of the power supply is positive, a control device configured to operate in the order of [a2]->[d2]->[f]-> [c2] is implemented. Form of.

(3A ") When the polarity of the power source is negative, [a
1] → [f] → [e1], and a control device configured to operate in the order of [a2] → [f] → [e2] when the polarity of the power source is positive. . (3B ") When the polarity of the power supply is negative, [a1] → [f] →
It operates in the order of [b1], and when the polarity of the power supply is positive, [a
2]->[f]-> [b2].

(4G) When the polarity of the power source is negative, [a1]
An embodiment provided with a control device configured to operate in the order of [c1] → [e1] and to operate in the order of [a2] → [c2] → [e2] when the polarity of the power source is positive. (4I) When the polarity of the power source is negative, [a1] → [c1] →
It operates in the order of [b1], and when the polarity of the power supply is positive, [a
2]->[c2]-> [b2].

(4C3) When the polarity of the power source is negative, [a
1] → [f] → [b1] → [e1], and when the power supply polarity is positive, [a2] → [f] → [b2] → [e
2] An embodiment including a control device configured to operate in the order of [2]. (4G2) [a1] → [c1] when the polarity of the power supply is negative
→ [f] → [e1] in order, and when the polarity of the power source is positive, a control device is configured to operate in the order of [a2] → [c2] → [f] → [e2]. Form of.

(4G3) When the polarity of the power source is negative, [a
1] → [f] → [c1] → [e1], and when the power supply polarity is positive, [a2] → [f] → [c2] → [e
2] An embodiment including a control device configured to operate in the order of [2]. (4I2) [a1] → [c1] when the power supply polarity is negative
->[F]-> [b1] in order, and when the polarity of the power source is positive, [a2]->[c2]->[f]-> [b2] Form of.

(4I3) When the polarity of the power source is negative, [a
1] → [f] → [c1] → [b1], and when the power supply polarity is positive, [a2] → [f] → [c2] → [b
2] An embodiment including a control device configured to operate in the order of [2]. (4J3) When the power supply polarity is negative, [a1] → [f] →
An embodiment provided with a control device configured to operate in the order of [e1] → [b1] and to operate in the order of [a2] → [f] → [e2] → [b2] when the polarity of the power source is positive. Form.

(2B) When the polarity of the power source is negative, [a1]
An embodiment including a control device configured to operate in the order of [f] → [d1] and to operate in the order of [a2] → [f] → [d2] when the polarity of the power source is positive. (4H) When the polarity of the power source is negative, [a1] → [c1] →
It operates in the order of [d1], and when the polarity of the power source is positive, [a
2]->[c2]-> [d2].

(4H2) When the polarity of the power supply is negative, [a
1] → [c1] → [f] → [d1], and when the power supply polarity is positive, [a2] → [c2] → [f] → [d
2] An embodiment including a control device configured to operate in the order of [2]. (4H3) When the polarity of the power source is negative, [a1] → [f] →
An embodiment provided with a control device configured to operate in the order of [c1] → [d1] and to operate in the order of [a2] → [f] → [c2] → [d2] when the polarity of the power source is positive. Form.

(4B1) When the polarity of the power source is negative, [a
1] → [b1] → [d1] → [f], and when the power supply polarity is positive, [a2] → [b2] → [d2] →
An embodiment including a control device configured to operate in the order of [f]. (4K1) [a1] → [e1] when the polarity of the power supply is negative
->[D1]-> [f] is operated in order, and a control device configured to operate in the order of [a2]->[e2]->[d2]-> [f] when the polarity of the power supply is positive is provided. Form of.

(4B2) When the polarity of the power source is negative, [a
1] → [b1] → [f] → [d1], and when the power supply polarity is positive, [a2] → [b2] → [f] → [d
2] An embodiment including a control device configured to operate in the order of [2]. (4K2) [a1] → [e1] when the polarity of the power supply is negative
->[F]-> [d1] in order, and when the polarity of the power source is positive, [a2]->[e2]->[f]-> [d2] Form of.

(4D1) When the polarity of the power supply is negative, [a
1] → [d1] → [e1] → [f], and when the power supply polarity is positive, [a2] → [d2] → [e2] →
An embodiment including a control device configured to operate in the order of [f]. (4F1) [a1] → [d1] when the polarity of the power supply is negative
->[B1]-> [f] are operated in this order, and a control device configured to operate in the order of [a2]->[d2]->[b2]-> [f] when the polarity of the power supply is positive. Form of.

(4D2) When the polarity of the power source is negative, [a
1] → [d1] → [f] → [e1], and when the power supply polarity is positive, [a2] → [d2] → [f] → [e
2] An embodiment including a control device configured to operate in the order of [2]. (4F2) [a1] → [d1] when the polarity of the power supply is negative
->[F]-> [b1] are operated in this order, and a control device configured to operate in the order of [a2]->[d2]->[f]-> [b2] when the polarity of the power supply is positive Form of.

(4B3) When the polarity of the power supply is negative, [a
1] → [f] → [b1] → [d1], and when the power supply polarity is positive, [a2] → [f] → [b2] → [d
2] An embodiment including a control device configured to operate in the order of [2]. (4K3) When the power supply polarity is negative, [a1] → [f] →
An embodiment provided with a control device configured to operate in the order of [e1] → [d1] and to operate in the order of [a2] → [f] → [e2] → [d2] when the polarity of the power source is positive. Form.

(4D3) When the polarity of the power source is negative, [a
1] → [f] → [d1] → [e1], and when the power supply polarity is positive, [a2] → [f] → [d2] → [e
2] An embodiment including a control device configured to operate in the order of [2]. (4F3) When the polarity of the power supply is negative, [a1] → [f] →
An embodiment provided with a control device configured to operate in the order of [d1] → [b1] and to operate in the order of [a2] → [f] → [d2] → [b2] when the polarity of the power source is positive. Form.

(4C2) When the polarity of the power source is negative, [a
1] → [b1] → [f] → [e1], and when the polarity of the power source is positive, [a2] → [b2] → [f] → [e
2] An embodiment including a control device configured to operate in the order of [2]. (4J2) [a1] → [e1] when the polarity of the power supply is negative
→ [f] → [b1] in order, and when the polarity of the power source is positive, [a2] → [e2] → [f] → [b2] Form of.

(4A3) When the polarity of the power source is negative, [a
1] → [f] → [b1] → [c1], and when the power supply polarity is positive, [a2] → [f] → [b2] → [c
2] An embodiment including a control device configured to operate in the order of [2]. (4G1) [a1] → [c1] when the polarity of the power supply is negative
->[E1]-> [f] are operated in this order, and a control device configured to operate in the order of [a2]->[c2]->[e2]-> [f] when the power supply polarity is positive is implemented. Form of.

(4I1) When the polarity of the power source is negative, [a
1] → [c1] → [b1] → [f], and when the power supply polarity is positive, [a2] → [c2] → [b2] →
An embodiment including a control device configured to operate in the order of [f]. (4L3) When the power supply polarity is negative, [a1] → [f] →
An embodiment provided with a control device configured to operate in the order of [e1] → [c1] and to operate in the order of [a2] → [f] → [e2] → [c2] when the polarity of the power source is positive. Form.

(4E3) When the polarity of the power source is negative, [a
1] → [f] → [d1] → [c1], and when the power supply polarity is positive, [a2] → [f] → [d2] → [c
2] An embodiment including a control device configured to operate in the order of [2]. (4H1) [a1] → [c1] when the power supply polarity is negative
->[D1]-> [f] is operated in this order, and when the polarity of the power supply is positive, a control device configured to operate in the order of [a2]->[c2]->[d2]-> [f] is implemented. Form of. Further, the gate / source of the element during the period when current flows through the parasitic diode of the switching element Q4 when the polarity of the power source is negative and during the period when current flows through the parasitic diode of the switching element Q3 when the polarity of the power source is positive. A voltage may be applied between them.

In each of the above embodiments, the output to the load is preferably a low frequency rectangular wave synchronized with the power supply. A discharge lamp can be used as the load, but the load is not limited to this.

[0068]

【Example】

(First Embodiment) FIG. 1 shows a first embodiment. This power supply device includes first and second field effect transistors Q1 and Q2.
Series circuit and third and fourth field effect transistors Q
A series circuit of 1 and Q2 and a series circuit of two rectifying elements D5 and D6 are connected in parallel with the capacitor C1, and the first and second
A series circuit composed of a power supply AC and a first inductor L1 connected via a filter (not shown) is connected between the connection point of the field effect transistors Q1 and Q2 and the connection point of the two rectifying elements D5 and D6. A load circuit L and a second inductor L2 are provided between the connection point of the first and second field effect transistors Q1 and Q2 and the connection point of the third and fourth field effect transistors Q3 and Q4. A series circuit is connected. One end of the power supply AC is connected so as to coincide with the connection point of the first and second field effect transistors Q1 and Q2, and one end of the load circuit L is connected to the first and second field effect transistors Q1 and Q2. Connected to match the points.

Each of the field effect transistors Q1 to Q4 is switching-driven as follows by an on / off signal given from the control device. First, as shown in FIG. 2, the polarity of the power supply AC is the first and second field effect transistors Q.
When the connection point side of 1 and Q2 is negative, the period during which the second and third field effect transistors Q2 and Q3 are turned on (see FIG. 2).
(See (a)), first and third field effect transistors Q
1 and Q3 are turned on (see FIG. 2B), first, second, third and fourth field effect transistors Q1 and Q
2, Q3, Q4 are turned off (see FIG. 2 (c)) in this order, and the polarity of the power supply AC is as shown in FIG. 3 for the first and second field effect transistors Q1, Q2. When the connection point side is positive, the period during which the first and fourth field effect transistors Q1 and Q4 are turned on (see FIG. 3A),
Turning on the second and fourth field effect transistors Q2 and Q4
During the period (see FIG. 3B), the period during which the first, second, third, and fourth field effect transistors Q1, Q2, Q3, and Q4 are turned off (see FIG. 3C). The controller CNT configured as described above is provided.

This power supply device is composed of a first power conversion circuit which constitutes a step-up chopper circuit and a second power conversion circuit which constitutes a step-down chopper circuit.
The field effect transistors Q1 and Q2 are also used for the first and second power conversion circuits. The polarity of the power supply AC is
, The first and second field effect transistors Q
The operation when the connection point side of 1 and Q2 is negative will be described with respect to the first power conversion circuit forming the step-up chopper circuit and the second power conversion circuit forming the step-down chopper circuit.

First, with respect to the first power conversion circuit that constitutes the boost chopper circuit, a period during which the first and third field effect transistors Q1 and Q3 are turned on (see FIG. 2B).
Is a period for charging the first inductor L1 with energy, which acts as a choke of the boost chopper, and includes the first, second, third, and fourth field-effect transistors Q.
A period in which 1, Q2, Q3, and Q4 are turned off (see FIG. 2C), and second and third field effect transistors Q2,
The period in which Q3 is turned on (see FIG. 2A) is a period in which the energy stored in the first inductor L1 is discharged.

Next, regarding the second power conversion circuit which constitutes the step-down chopper circuit, the period during which the second and third field effect transistors Q2 and Q3 are turned on (see FIG. 2A).
Is a period during which the second inductor L2, which acts as the choke of the step-down chopper, is charged with energy.
And a period in which the third field effect transistors Q1 and Q3 are turned on (see FIG. 2B), and the first, second, third, and fourth field effect transistors Q1, Q2, Q3, and Q4 are turned off. The period (see FIG. 2C) is a period for discharging the energy stored in the second inductor L2.

The current loop of the first power conversion circuit CNV1 will be described during the period in which the second and third field effect transistors Q2 and Q3 are turned on (see FIG. 2A). Is a closed loop composed of the first inductor L1, the first rectifying element D5, the capacitor EC, the second field effect transistor Q2, and the power supply AC, and the current of the second power conversion circuit CNV2 is In a period in which the EC, the third field effect transistor Q3, the second inductor L2, the load circuit L, and the state forming the closed loop including the second field effect transistor Q2 are simultaneously established (this period is referred to as T1). is there. In addition, during the period in which the first and third field effect transistors Q1 and Q3 are turned on (see FIG. 2B), the first power conversion circuit CN
The current of V1 is the power supply AC, the first inductor L1, the first
Rectifying element D5 and first field effect transistor Q1
And a current of the second power conversion circuit CNV2 causes a closed loop composed of the second inductor L2, the load circuit L, the first field effect transistor Q1 and the third field effect transistor Q3. This is a period in which the constituent states are simultaneously established (this period is referred to as T2). Furthermore, during the period in which the first, second, third, and fourth field effect transistors Q1, Q2, Q3, and Q4 are turned off (see FIG. 2C), the current of the first power conversion circuit CNV1 is A first inductor L1, a first rectifying element D5,
Capacitor EC and second field effect transistor Q
2. a state of forming a closed loop composed of a power supply AC, and a second
Current of the power conversion circuit CNV2 of the second inductor L
2, a load circuit L, a second field effect transistor Q2 and a fourth field effect transistor Q4 and a state forming a closed loop at the same time (this period is T3
It is).

During the period of T1, the forward current due to the second power conversion circuit CNV2 flowing into the second field effect transistor Q2 and the reverse current due to the first power conversion circuit CNV1 are superposed. , The current flowing through the second field effect transistor Q2 is reduced, and the switching loss is reduced. In the period of T2 above,
By superimposing the current in the positive direction by the first power conversion circuit CNV1 flowing into the first field effect transistor Q1 and the current in the reverse direction by the second power conversion circuit CNV2, the first field effect transistor Q1 is The flowing current is reduced, and the switching loss is reduced. During the period of T3, the current in the positive direction by the second power conversion circuit CNV2 flowing into the second field effect transistor Q2 and the current in the reverse direction by the first power conversion circuit CNV1 are superposed, so that the second current is generated. Field effect transistor Q
The current flowing through 2 is reduced, and switching loss is reduced.

The operation when the polarity of the power supply AC is opposite is shown in FIG. The waveform of each part is shown in FIG. IL in the figure
1 is the current flowing through the first inductor L1 and IL2 is the second
Current flowing in the inductor L2, IL2-IL1 is the second
Current flowing in the inductor L2 of the first inductor L1
Of the current flowing through the first field effect transistor Q1, IQ2 is the current flowing through the second field effect transistor Q2, IQ3 is the current flowing through the third field effect transistor Q3, and IQ4 is the fourth current flowing through the third field effect transistor Q3. Currents flowing in the field effect transistor Q4 and VQ1GS to VQ4GS are respectively the first to fourth field effect transistors Q1 to Q4.
Is a drive signal supplied between the gate and source of the.
Figure 8 shows the waveform for one cycle of switching.
The period from t0 to t1 is T1, the period from t1 to t2 is T2, t
The period of 2 to t3 (= t0) corresponds to T3.

(Second Embodiment) As a second embodiment, the operation when the power supply voltage is low or when the first inductor L1 is large will be described. The circuit configuration and the switching operation are the same as those in the first embodiment, but the current loop is partially different. The polarity of the power supply AC is, as shown in FIG.
The current loop when the connection point side of the first and second field effect transistors Q1 and Q2 is negative will be described. First, during the period in which the second and third field effect transistors Q2 and Q3 are turned on (see FIG. 4A), the second power conversion circuit CN is
A period in which the current of V2 forms a closed loop composed of the capacitor EC, the third field effect transistor Q3, the second inductor L2, the load circuit L, and the second field effect transistor Q2 (this period is T1. It is). Next, the first and third field effect transistors Q
During the period in which 1 and Q3 are turned on (see FIG. 4B), the current of the first power conversion circuit is the power supply AC and the first inductor L.
1, the first rectifying element D5 and the first field effect transistor Q1 form a closed loop, and the current of the second power conversion circuit changes the second inductor L2, the load circuit L, and the first electric field. This is a period (this period is referred to as T2) in which a state forming a closed loop including the effect transistor Q1 and the third field effect transistor Q3 is simultaneously established. Further, during the period in which the first, second, third, and fourth field effect transistors Q1, Q2, Q3, Q4 are turned off (see FIG. 4 (c) or (d)), the current flows through the first inductor L1. There are the following two states depending on the magnitude relation between the current and the current flowing through the second inductor L2.

The absolute value of the current of the first inductor L1 is
When it is smaller than the absolute value of the current of the second inductor L2 (see FIG. 4C), the first power conversion circuit CNV1
Current of the power supply AC, the first inductor L1, the first rectifying element D5, and the first field effect transistor Q1 to form a closed loop, and the second power conversion circuit C
The current of NV2 is the second inductor L2, the load circuit L,
A period in which a closed loop including the first field effect transistor Q1, the capacitor EC, and the fourth field effect transistor Q4 is simultaneously established (this period is referred to as T3
And). Further, when the absolute value of the current of the first inductor L1 matches the absolute value of the current of the second inductor L2 (see FIG. 4D), the first power conversion circuit CNV
As a result of the currents from the first and second power conversion circuits CNV2 being canceled by each other, the sum of the currents flowing into the dual-purpose SW elements becomes 0, and the above-mentioned dual-purpose is actually used in each power conversion circuit. The closed loop of the current passing through the SW element is not formed, and the first inductor L1 and the first rectifying element D
5, capacitor EC, fourth field effect transistor Q
4, second inductor L2, load circuit L, and power supply AC
Is a period (this period is referred to as T4) in which the state forming the closed loop consisting of is established.

Each of the above periods T1 to T4 will be described with respect to the first power conversion circuit forming the step-up chopper circuit and the second power conversion circuit forming the step-down chopper circuit.
Regarding the first power conversion circuit that constitutes the step-up chopper circuit, the period of T2 and T3 is the period of charging the energy in the first inductor L1 that acts as the choke of the step-up chopper, and the period of T4 is the first period. Inductor L
It is a period for releasing the energy stored in 1. Further, regarding the second power conversion circuit that constitutes the step-down chopper circuit, the period T1 is a period in which the second inductor L2 that acts as a choke of the step-down chopper is charged with energy, and the periods T2, T3, and T4 are , The period during which the energy stored in the second inductor L2 is released.

During the period of T2, the forward current due to the first power conversion circuit CNV1 flowing into the first field effect transistor Q1 and the reverse current due to the second power conversion circuit CNV2 are superposed, so that The current flowing through the first field effect transistor Q1 is reduced, and the power loss is reduced. During the period of T3, the second power conversion circuit CNV2 flowing into the second field effect transistor Q2.
By superimposing the current in the positive direction and the current in the reverse direction by the first power conversion circuit CNV1, the current flowing through the second field effect transistor Q2 is reduced, and the power loss is reduced. During the period of T4, the currents from the first power conversion circuit CNV1 and the second power conversion circuit CNV2 are canceled by each other, and as a result, the sum of the currents flowing into the dual-purpose SW element becomes 0, and in fact, Since the closed loop of the current passing through the dual-purpose SW element is not formed inside the power conversion circuit, the first field effect transistor Q1 and the second electric field are generated even though the power conversion circuit is operating. Since no current flows through the effect transistor Q2, there is an effect that no power loss occurs.

FIG. 5 shows the operation when the polarity of the power supply AC is opposite. Further, the waveform of each part is shown in FIG. IL in the figure
1 is the current flowing through the first inductor L1 and IL2 is the second
Current flowing in the inductor L2, IL2-IL1 is the second
Current flowing in the inductor L2 of the first inductor L1
Of the current flowing through the first field effect transistor Q1, IQ2 is the current flowing through the second field effect transistor Q2, IQ3 is the current flowing through the third field effect transistor Q3, and IQ4 is the fourth current flowing through the third field effect transistor Q3. Currents flowing in the field effect transistor Q4 and VQ1GS to VQ4GS are respectively the first to fourth field effect transistors Q1 to Q4.
Is a drive signal supplied between the gate and source of the.
Figure 9 shows the waveform for one cycle of switching.
The period from t0 to t1 is T1, the period from t1 to t2 is T2, t
The period from 2 to t3 corresponds to T3, and the period from t3 to t4 (= t0) corresponds to T4.

(Third Embodiment) FIG. 11 shows the circuit configuration of the third embodiment. In terms of circuit configuration, what is different from the first embodiment is that instead of a series circuit of two rectifying elements D5 and D6 connected in parallel with a capacitor C1, fifth and sixth field effect transistors Q5 and Q6 are used. It has a series circuit of. Each of the field effect transistors Q1 to Q6 is switching-driven as follows by an on / off signal given from the control device.

First, when the polarity of the power supply AC is negative on the connection point side of the first and second field effect transistors Q1 and Q2, as shown in FIG. 6, the second, third and sixth field effect transistors are formed. The period during which Q2, Q3, and Q6 are turned on (Fig. 6
(See (a)), the third field effect transistor Q3 is turned on.
Period (see FIG. 6 (b) or (c)), first, second,
Third, fourth, fifth and sixth field effect transistors Q
1, Q2, Q3, Q4, Q5, and Q6 operate in the order of the OFF period (see FIG. 6D), and the polarity of the power supply AC is
As shown in FIG. 7, when the connection point side of the first and second field effect transistors Q1 and Q2 is positive, the period during which the first, fourth and fifth field effect transistors Q1, Q4 and Q5 are turned on (see FIG. 7 (a)), a period during which the second and fourth field effect transistors Q2, Q4 are turned on (see FIG. 7 (b) or (c)), first, second, third, fourth, fifth , And a sixth field effect transistor Q1, Q2, Q3, Q4, Q
5 and Q6 are turned off in this order (see FIG. 7D).

Similar to the first and second embodiments, the operation when the polarity of the power supply AC is negative on the connection point side of the first and second field effect transistors Q1 and Q2 will be described by focusing on the current loop. Then, first, during the period in which the second, third, and sixth field effect transistors Q2, Q3, and Q6 are turned on (see FIG. 6A), the current of the first power conversion circuit CNV1 changes to the power supply A.
C, a first inductor L1, a sixth field effect transistor Q6, and a second field effect transistor Q2, and a state forming a closed loop, and a second power conversion circuit CNV.
A period in which the current of No. 2 and the state of forming the closed loop including the capacitor EC, the third field effect transistor Q3, the second inductor L2, the load circuit L, and the second field effect transistor Q2 are simultaneously established (this period Is T1). Next, during the period in which the third field effect transistor Q3 is turned on (see FIG. 6B or 6C), the current flowing through the first inductor L1 and the second inductor L2
There are two states, depending on the magnitude relationship with the current flowing through.

When the absolute value of the current of the first inductor L1 is smaller than the absolute value of the current of the second inductor L2 (see FIG. 6 (b)), the current of the first power conversion circuit CNV1 is the power source. AC, the first inductor L1, the fifth field effect transistor Q5, and the state of forming a certain closed loop from the first field effect transistor Q1 and the current of the second power conversion circuit CNV2, the second inductor L2 , Load circuit L, first field effect transistor Q1, and third
And a state of forming a closed loop composed of the field effect transistor Q3 is simultaneously established (this period is referred to as T2). Further, when the absolute value of the current of the first inductor L1 matches the absolute value of the current of the second inductor L2 (see FIG. 6C), the first power conversion circuit CNV1 and the second power conversion circuit As a result of the currents from the CNV2 being canceled each other, the total sum of the currents flowing into the dual-purpose SW elements becomes 0, and in fact, the closed loop of the currents passing through the dual-purpose SW elements is internally generated in each power conversion circuit. A period in which a closed loop including the first inductor L1, the fifth field effect transistor Q5, the third field effect transistor Q3, the second inductor L2, the load circuit L, and the power supply AC is formed without being configured. (This period is T3).

Further, the first, second, third, fourth, fifth and sixth field effect transistors Q1, Q2, Q3, Q.
Period for turning off Q4, Q5, and Q6 (see FIG. 6 (d))
Is a result of the currents from the first power conversion circuit CNV1 and the second power conversion circuit CNV2 being canceled each other, and as a result, the sum of the currents flowing into the dual-purpose SW elements is 0, and in fact, each power conversion circuit Internally, the combined SW
The closed loop of the current passing through the element is not formed, and the first inductor L1, the fifth field effect transistor Q5, the capacitor EC, the fourth field effect transistor Q4, the second inductor L2, the load circuit L, and the power supply AC are connected. Is a period (this period is referred to as T4) in which the state forming the closed loop is established.

The operation in each of the periods T1 to T4 will be described with respect to the first power conversion circuit forming the step-up chopper circuit and the second power conversion circuit forming the step-down chopper circuit.
First, regarding the first power conversion circuit forming the step-up chopper circuit, the periods T1 and T2 are the periods for charging the energy in the first inductor L1, which acts as the choke of the step-up chopper, and the periods T3 and T4. Is the first
Is a period during which the energy stored in the inductor L1 is released. Further, regarding the second power conversion circuit that constitutes the step-down chopper circuit, the period T1 is a period in which the second inductor L2 that acts as a choke of the step-down chopper is charged with energy, and the periods T2, T3, and T4 are , The period during which the energy stored in the second inductor L2 is released.

During the period of T1, the forward current flowing into the second field effect transistor Q2 by the second power conversion circuit CNV2 and the reverse current flowing by the first power conversion circuit CNV1 are superimposed, so that The current flowing through the second field effect transistor Q2 is reduced, and the switching loss is reduced. In the period of T2, the current in the positive direction by the first power conversion circuit CNV1 flowing into the first field effect transistor Q1 and the second power conversion circuit CNV
Due to the superposition of currents in the opposite direction due to V2, the first
Current flowing through the field effect transistor Q1 of
This has the effect of reducing switching loss.

In the period of T3, the first power conversion circuit CN
As a result of the currents from V1 and the second power conversion circuit CNV2 canceling each other out, the sum of the currents flowing into the combined SW elements becomes 0, and in practice, the above-mentioned combined use is made inside each power conversion circuit. Since a closed loop of the current passing through the SW element is not formed, no current flows through the first field effect transistor Q1 and the second field effect transistor Q2 even though the power conversion circuit is operating. This has the effect that no power loss occurs.

In the period of T4, the first power conversion circuit CN
As a result of the currents from V1 and the second power conversion circuit CNV2 canceling each other out, the sum of the currents flowing into the dual-purpose SW elements becomes 0, and the above-mentioned dual-purpose is practically used inside each power conversion circuit. Since the closed loop of the current passing through the SW element is not configured, the first field effect transistor Q1 and the second field effect transistor Q1 are activated even though the power conversion circuit is operating.
Since no current flows through the field effect transistor Q2, the power loss does not occur.

FIG. 7 shows the operation when the polarity of the power supply AC is opposite. Further, the waveform of each part is shown in FIG. In the figure, I
L1 is a current flowing through the first inductor L1, IL2 is a current flowing through the second inductor L2, and IL2-IL1 is a current flowing through the second inductor L2 and the first inductor L.
1 to IQ6 are the first to the sixth differences, respectively.
The currents flowing through the sixth field effect transistors Q1 to Q6 and VQ1GS to VQ6GS are drive signals supplied between the gates and sources of the first to sixth field effect transistors Q1 to Q6, respectively. FIG. 10 shows a waveform for one cycle of switching. The period from t0 to t1 is T1, the period from t1 to t2 is T2, and the period from t2 to t3 is T.
3, the period from t3 to t4 (= t0) corresponds to T4.

(Fourth Embodiment) The fourth embodiment is claim 2
Corresponds to 2. The circuit configuration of this embodiment is as described in the second conventional example. Specific examples of the circuit operation of FIG. 19 are shown in FIGS. 20 (a) to 20 (c) and FIGS.
It is shown and described in (f). In the positive half cycle of the AC power supply P, when the switching elements Q1 and Q3 are on and the switching elements Q2 and Q4 are off, as shown in FIG.
5, current flows through the path of the switching element Q1 and the inductor L1, and energy is stored in the inductor L1. In addition, the regenerative current due to the stored energy of the inductor L2 uses the inductor L2 as a current source to generate the diode D.
1, a current flows through the path of the switching element Q3 and the load circuit Z.

Next, when the switching elements Q2 and Q3 are on and the switching elements Q1 and Q4 are off, the regenerative current due to the energy stored in the inductor L1 flows through the inductor L1, and the current using the smoothing capacitor C as a current source is the inductor L2. Flowing through. Here, when the current value flowing through the inductor L1 is larger than the current value flowing through the inductor L2, as shown in FIG.
As a current source, a current flows through the path of the diode D9, the smoothing capacitor C, and the diode D2, and the smoothing capacitor C
Is charged. In addition, due to the characteristics of the diode D2, a current flows in the reverse direction while a forward current flows in the diode D2 due to the current loop using the inductor L1 as a current source. As switching element Q3, load circuit Z, inductor L2,
A current flows through the path of the diode D2, the voltage of the smoothing capacitor C is stepped down by the inductor L2, and the voltage is supplied to the load circuit Z. At this time, in the diode D2,
The current in the current loop using the inductor L1 as the current source and the current in the current loop using the smoothing capacitor C as the current source flow in opposite directions to cancel each other, and the current value flowing in the diode D2 becomes small.

On the other hand, the value of the current flowing through the inductor L1 is
If the current value is smaller than the value of the current flowing through the inductor L2, FIG.
As shown in (c), current flows through the path of the diode D9, the smoothing capacitor C, the diode D8, and the switching element Q2 using the inductor L1 as a current source, and the smoothing capacitor C is charged. In addition, current flows through the path of the switching element Q3, the load circuit Z, the inductor L2, the switching element Q2, and the diode D8 with the smoothing capacitor C as a current source, and the voltage of the smoothing capacitor C changes to the inductor L.
It is stepped down by 2 and supplied to the load circuit Z. At this time, in the switching element Q2 and the diode D8,
The current of the current loop having the inductor L1 as the current source and the current of the current loop having the smoothing capacitor C as the current source flow in opposite directions to cancel each other, and the switching element Q
2 and the current value flowing through the diode D8 becomes smaller. Hereinafter, when the switching elements Q1 and Q3 are on and the switching elements Q2 and Q4 are off at a high frequency, and when the switching elements Q2 and Q3 are on and the switching elements Q1 and Q4 are off (FIGS. 20A and 20B). Alternatively, FIG.
By repeating (a) and (c), a unidirectional DC voltage is supplied to the load circuit Z.

Next, in the negative half cycle of the AC power supply P, when the switching elements Q2 and Q4 are on and the switching elements Q1 and Q3 are off, as shown in FIG. As a result, a current flows through the path of the inductor L1, the switching element Q2, and the diode D6, and energy is stored in the inductor L1. Further, the regenerative current due to the energy stored in the inductor L2 flows through the route of the load circuit Z, the switching element Q4, and the diode D2 with the inductor L2 as the current source.

Next, when the switching elements Q1 and Q4 are on and the switching elements Q2 and Q3 are off, the regenerative current due to the energy stored in the inductor L1 flows through the inductor L1, and the current using the smoothing capacitor C as the current source is the inductor L2. Flowing through. Here, when the value of the current flowing through the inductor L1 is larger than the value of the current flowing through the inductor L2, as shown in FIG.
As a current source, a current flows through the path of the diode D1, the smoothing capacitor C, and the diode D10 to charge the smoothing capacitor C. A current flows through the path of the diode D1, the inductor L2, the load circuit Z, and the switching element Q4 with the smoothing capacitor C as a current source, and the voltage of the smoothing capacitor C is stepped down by the inductor L2 and supplied to the load circuit Z. At this time, in the diode D1, the current of the current loop having the inductor L1 as the current source and the current of the current loop having the smoothing capacitor C as the current source flow in opposite directions to cancel each other, and the diode D1
The value of the current flowing through 1 becomes smaller.

On the other hand, the value of the current flowing through the inductor L1 is
If the current value is smaller than the value of the current flowing through the inductor L2, FIG.
As shown in (f), current flows through the path of the switching element Q1, the diode D7, the smoothing capacitor C, and the diode D10 using the inductor L1 as a current source, and the smoothing capacitor C is charged. In addition, current flows through the path of the diode D7, the switching element Q1, the inductor L2, the load circuit Z, and the switching element Q4 using the smoothing capacitor C as a current source, and the voltage of the smoothing capacitor C is stepped down by the inductor L2 to the load circuit Z. Supplied. At this time, in the diode D7 and the switching element Q1, the current of the current loop having the inductor L1 as the current source and the current of the current loop having the smoothing capacitor C as the current source flow in opposite directions to cancel each other, and the diode D7
7 and the current value flowing through the switching element Q1 become smaller. Hereinafter, when the switching elements Q2 and Q4 are turned on and the switching elements Q1 and Q3 are turned off at a high frequency, and when the switching elements Q1 and Q4 are turned on and the switching element Q is turned on.
2 and Q3 are off (FIG. 21 (d), (e) or FIG. 21 (d), (f)), the load circuit Z is supplied with a reverse DC voltage. Through the above operation, the load circuit Z is supplied with the rectangular wave voltage whose polarity is inverted in synchronization with each half cycle of the AC power supply P.

That is, in this embodiment, the switching element Q1, the diode D7, the diode D1 or the switching element Q2, the diode D8, and the diode D, which also function as the buck-boost chopper circuit and the step-down chopper circuit, are used.
2, regardless of the magnitude of each of the current value flowing through the inductor L1 and the current value flowing through the inductor L2,
0 (b), (c), and FIGS. 21 (e) and (f), the current in the current loop on the inductor L1 side and the current on the inductor L2 side flow in opposite directions to cancel each other, so Since it is possible to reduce the breakdown voltage, it is possible to reduce the breakdown voltage of the dual-purpose switching element and diode, and there is an advantage that the cost can be reduced. Further, since the step-up / step-down chopper operation and the step-down chopper operation can be performed independently, there is an advantage that the input power can be controlled according to the output power when the output power is controlled to be constant. As a result, when the present embodiment is applied to a high pressure discharge lamp lighting device,
In the starting process of the high-pressure discharge lamp, even if the impedance of the load is low, a large current can flow through the load without making the input power excessive with respect to the output power.

When the control method of this embodiment is used, the current on the step-down chopper circuit side does not return to the smoothing capacitor side even when the load impedance is low, as shown in FIGS. Energy is load circuit Z
Since it is consumed by, it is possible to prevent over-boosting of the voltage across the smoothing capacitor, and it is possible to effectively use energy on the load side.

(Fifth Embodiment) The fifth embodiment is claim 2
Corresponds to 2. The circuit configuration of this embodiment is as described in the second conventional example. 22 (a) to 22 (c) and 23 (d) to 23 (d).
It is shown and described in (f). In the positive half cycle of the AC power supply P, when the switching element Q1 is on and the switching elements Q2, Q3, Q4 are off, as shown in FIG.
5, current flows through the path of the switching element Q1 and the inductor L1, and energy is stored in the inductor L1. In addition, the regenerative current due to the stored energy of the inductor L2 uses the inductor L2 as a current source to generate the diode D.
1, a current flows through the path of the smoothing capacitor C, the diode D4, and the load circuit Z.

Next, when the switching elements Q2 and Q3 are on and the switching elements Q1 and Q4 are off, the regenerative current due to the energy stored in the inductor L1 flows through the inductor L1, and the current using the smoothing capacitor C as a current source is the inductor L2. Flowing through. Here, when the current value flowing through the inductor L1 is larger than the current value flowing through the inductor L2, as shown in FIG.
As a current source, a current flows through the path of the diode D9, the smoothing capacitor C, and the diode D2, and the smoothing capacitor C
Is charged. Further, with the smoothing capacitor C as a current source, the switching element Q3, the load circuit Z, the inductor L2,
A current flows through the path of the diode D2, the voltage of the smoothing capacitor C is stepped down by the inductor L2, and the voltage is supplied to the load circuit Z. At this time, in the diode D2,
The current in the current loop using the inductor L1 as the current source and the current in the current loop using the smoothing capacitor C as the current source flow in opposite directions to cancel each other, and the current value flowing in the diode D2 becomes small. On the other hand, when the value of the current flowing through the inductor L1 is smaller than the value of the current flowing through the inductor L2, as shown in FIG. 22C, the inductor L1 is used as a current source for the diode D9, the smoothing capacitor C, the diode D8, and the switching element Q2. A current flows through the path and the smoothing capacitor C is charged. In addition, a current flows through the path of the switching element Q3, the load circuit Z, the inductor L2, the switching element Q2, and the diode D8 using the smoothing capacitor C as a current source, and the voltage of the smoothing capacitor C is stepped down by the inductor L2 to the load circuit Z. Supplied. At this time, in the switching element Q2 and the diode D8, the current of the current loop having the inductor L1 as the current source and the current of the current loop having the smoothing capacitor C as the current source flow in opposite directions to cancel each other, and the switching element Q2 And the value of the current flowing through the diode D8 becomes smaller. Hereinafter, when the switching element Q1 is on and the switching elements Q2, Q3, and Q4 are off at high frequency, and when the switching elements Q2 and Q3 are on and the switching elements Q1 and Q4 are off (FIGS. 22A and 22B). 22 (a) and 22 (c)) are repeated, and the load circuit Z
Is supplied with a unidirectional DC voltage.

Next, in the negative half cycle of the AC power supply P, the switching element Q2 is turned on and the switching element Q2 is turned on.
When 1, Q3 and Q4 are off, as shown in FIG. 23 (d), a current flows through the path of the inductor L1, the switching element Q2 and the diode D6 using the AC power source P as a current source, and energy is accumulated in the inductor L1. To be done. In addition, a regenerative current due to the energy stored in the inductor L2 flows through the load circuit Z, the diode D3, the smoothing capacitor C, and the switching element Q2 with the inductor L2 as a current source.

Next, when the switching elements Q1 and Q4 are on and the switching elements Q2 and Q3 are off, a regenerative current due to the energy stored in the inductor L1 flows through the inductor L1, and a current using the smoothing capacitor C as a current source is the inductor L2. Flowing through. Here, when the value of the current flowing through the inductor L1 is larger than the value of the current flowing through the inductor L2, as shown in FIG.
As a current source, a current flows through the path of the diode D1, the smoothing capacitor C, and the diode D10 to charge the smoothing capacitor C. A current flows through the path of the diode D1, the inductor L2, the load circuit Z, and the switching element Q4 with the smoothing capacitor C as a current source, and the voltage of the smoothing capacitor C is stepped down by the inductor L2 and supplied to the load circuit Z. At this time, in the diode D1, the current of the current loop having the inductor L1 as the current source and the current of the current loop having the smoothing capacitor C as the current source flow in opposite directions to cancel each other, and the diode D1
The value of the current flowing through 1 becomes smaller.

On the other hand, the value of the current flowing through the inductor L1 is
If the current value is smaller than the current value flowing through the inductor L2, FIG.
As shown in (f), current flows through the path of the switching element Q1, the diode D7, the smoothing capacitor C, and the diode D10 using the inductor L1 as a current source, and the smoothing capacitor C is charged. In addition, current flows through the path of the diode D7, the switching element Q1, the inductor L2, the load circuit Z, and the switching element Q4 using the smoothing capacitor C as a current source, and the voltage of the smoothing capacitor C is stepped down by the inductor L2 to the load circuit Z. Supplied. At this time, in the diode D7 and the switching element Q1, the current of the current loop having the inductor L1 as the current source and the current of the current loop having the smoothing capacitor C as the current source flow in opposite directions to cancel each other, and the diode D7
7 and the current value flowing through the switching element Q1 become smaller. Hereinafter, when the switching element Q2 is on and the switching elements Q1, Q3, Q4 are off at high frequency, and when the switching elements Q1, Q4 are on, the switching element Q2,
When Q3 is off (Fig. 23 (d), (e) or Fig. 2)
By repeating 3 (d) and (f), the DC voltage in the reverse direction is supplied to the load circuit Z. By the above operation, the load circuit Z
Is supplied with a rectangular wave voltage whose polarity is inverted in synchronization with each half cycle of the AC power supply P.

In this embodiment, as in the fourth embodiment,
Switching element Q1, diode D7, and diode D that also function as a buck-boost chopper circuit and a step-down chopper circuit
1, or switching element Q2, diode D8,
In the diode D2, there are advantages that the current withstand amount can be reduced and that the buck-boost chopper operation and the step-down chopper operation can be performed independently.

[0105]

According to the present invention, a current flowing from the first power conversion circuit to a switching element or a rectifying element that is also used as an element forming the first power conversion circuit and the second power conversion circuit is provided. , The current flowing from the second power conversion circuit is controlled so as to flow in a direction to cancel each other, thereby reducing the current withstanding amount of the switching element or the rectifying element while having independence to each circuit. There is an effect that can be. Also, the first
By using the step-up / step-down chopper circuit for the power converter circuit, it is possible to increase the degree of freedom in setting the smoothing capacitor voltage with respect to the power supply voltage, and to prevent an inrush current when the power is turned on.

[Brief description of drawings]

FIG. 1 is a circuit diagram showing a preferred embodiment of the present invention.

FIG. 2 is a circuit diagram showing an operation of the first embodiment of the present invention when one power source has a polarity.

FIG. 3 is a circuit diagram showing an operation of the first embodiment of the present invention when the other power source is polarized.

FIG. 4 is a circuit diagram showing an operation of the second embodiment of the present invention when one power source has a polarity.

FIG. 5 is a circuit diagram showing an operation of the second embodiment of the present invention when the other power source is polarized.

FIG. 6 is a circuit diagram showing an operation of the third embodiment of the present invention when one power source has a polarity.

FIG. 7 is a circuit diagram showing an operation of the third embodiment of the present invention when the other power source is polarized.

FIG. 8 is a waveform diagram showing operation waveforms of various parts of the first embodiment of the present invention.

FIG. 9 is a waveform diagram showing operation waveforms of various parts of the second embodiment of the present invention.

FIG. 10 is a waveform diagram showing operation waveforms of various parts of the third embodiment of the present invention.

FIG. 11 is a circuit diagram showing another embodiment of the present invention.

FIG. 12 is an explanatory diagram showing an embodiment of a first group focusing on the current loop of the present invention.

FIG. 13 is an explanatory diagram showing an embodiment of a second group focusing on the current loop of the present invention.

FIG. 14 is an explanatory diagram showing a first group of embodiments relating to a switch operation of the present invention.

FIG. 15 is an explanatory diagram showing a second group of embodiments relating to the switch operation of the present invention.

FIG. 16 is an explanatory diagram showing an embodiment of a third group relating to the switch operation of the present invention.

FIG. 17 is an explanatory diagram showing a fourth group of embodiments relating to the switch operation of the present invention.

FIG. 18 is an explanatory diagram showing an embodiment of a fifth group relating to the switch operation of the present invention.

FIG. 19 is a circuit diagram showing a configuration of a power supply device according to claim 22.

FIG. 20 is a circuit diagram showing an operation of the fourth embodiment of the present invention when one power source has a polarity.

FIG. 21 is a circuit diagram showing an operation of the fourth embodiment of the present invention when the other power source is polarized.

FIG. 22 is a circuit diagram showing an operation of the fifth embodiment of the present invention when one power source has a polarity.

FIG. 23 is a circuit diagram showing an operation of the fifth embodiment of the present invention when the other power source is polarized.

FIG. 24 is a circuit diagram showing a configuration of a power supply device of Conventional Example 1.

FIG. 25 is a circuit diagram showing an operation of Conventional Example 1.

FIG. 26 is a circuit diagram showing an operation of the conventional example 2 when one power source has a polarity.

FIG. 27 is a circuit diagram showing an operation when the other power supply polarity in Conventional Example 2 is changed.

[Explanation of symbols]

Q1-Q4 switching elements D5, D6 diode EC capacitor L1 First inductor L2 second inductor AC AC power supply L load circuit

─────────────────────────────────────────────────── ─── Continuation of the front page (72) Shinji Hizuma, 1048, Kadoma, Kadoma City, Osaka Prefecture, Matsushita Electric Works, Ltd. (72) Toshiro Nakamura, 1048, Kadoma, Kadoma City, Osaka Matsushita Electric Works, Ltd. (56) References JP-A-2-282809 (JP, A) JP-A-3-86084 (JP, A) (58) Fields investigated (Int.Cl. ⁷ , DB name) H02M 7/48 H02M 7 / 5387 H05B 41/24

Claims (25)

(57) [Claims] 1. At least two power conversion circuits each comprising at least one switching element or rectifying element, at least one of said switching elements or rectifying elements comprising at least two different power conversion circuits. Among the currents from different power conversion circuits that also serve as constituent elements and that flow into the dual-purpose switching element or rectifying element, the current that flows from at least one power conversion circuit is another at least one power conversion circuit. A power supply device comprising: a control unit configured to have at least a period in which the currents have a polarity opposite to that of the currents that flow in and the currents flow in directions to cancel each other. 2. The at least two different power conversion circuits according to claim 1, wherein the first power conversion circuit is the switching element or the rectifying element that also functions as the above-mentioned.
A second power conversion circuit configured to have at least a closed loop including at least a power supply and an inductor, and the switching element or the rectifying element that also serves as the above
A power supply device comprising at least a closed loop including at least a load circuit, an inductor and a capacitor. 3. The power supply device according to claim 2, wherein the first power conversion circuit is configured as a step-up chopper circuit or a step-up / step-down chopper circuit, and the second power conversion circuit is configured as a step-down chopper circuit. . 4. The booster chopper circuit or the step-up / down chopper circuit of the first power conversion circuit according to claim 3, wherein the power supply is an input and the capacitor of the second power conversion circuit is an output. A power supply device characterized in that the step-down chopper circuit of the circuit is configured with the capacitor of the second power conversion circuit as an input and the load circuit as an output. 5. The method according to claim 2, wherein
The current flowing from the first power conversion circuit into the dual-purpose switching element or rectifying element uses the energy of the power source as a supply source, and the current flowing from the second power conversion circuit into the dual-purpose switching element is A power supply device having at least a period in which the energy of the inductor in the second power conversion circuit is used as a supply source. 6. The method according to any one of claims 2 to 4,
The current flowing from the first power conversion circuit to the dual-purpose switching element uses the energy of the power source as a supply source, and the current flowing from the second power conversion circuit to the dual-purpose switching element is the capacitor. A power supply device having at least a period in which energy is used as a supply source. 7. The method according to any one of claims 2 to 4,
The current flowing from the first power conversion circuit to the dual-purpose switching element uses the energy of the power source and the inductor in the first power conversion circuit as a supply source, and the second power conversion circuit also performs the dual function. The power supply device, wherein the current flowing into the switching element has at least a period in which the energy of the capacitor is used as a supply source. 8. The method according to claim 2, wherein
The current flowing from the first power conversion circuit to the dual-purpose switching element uses the energy of the power source and the inductor in the first power conversion circuit as a supply source, and the second power conversion circuit also performs the dual function. The power supply device, wherein the current flowing into the switching element has at least a period in which the energy of the inductor in the second power conversion circuit is used as a supply source. 9. The method according to claim 1, wherein
As a result of the currents from the respective power conversion circuits being canceled by each other, the total sum of the currents flowing into the dual-purpose switching elements becomes 0, and, in effect, the dual-purpose switching elements are passed through in the respective power conversion circuits. A power supply device characterized by having a period in which a closed loop of current is not configured and a closed loop of current extending to a plurality of power conversion circuits is configured. 10. The circuit according to claim 1, wherein the first and second switching elements, each having a reverse-direction energization element in parallel, are connected in series so that their forward directions coincide with each other, and a reverse-direction energization. A circuit in which third and fourth switching elements each having elements in parallel are connected in series so that their forward directions are matched is connected in parallel with a capacitor with the same polarity, and first and second rectifying elements are connected in series. In order that one end of the first rectifying element matches one end of the first and third switching elements with the same polarity as the energizing element provided with the connected circuit in parallel with the first to fourth switching elements,
Connected in parallel to the capacitor, between the connection point of the two rectifying elements and the connection point of the first and second switching elements, connect a series circuit of an AC power source and a first inductor via a filter, A circuit configuration in which a load circuit and a series circuit of a second inductor are connected between the connection point of the first and second switching elements and the connection point of the third and fourth switching elements. Power supply. 11. The first to fourth switching elements according to claim 10, wherein the first to fourth switching elements are respectively provided with the reverse-direction conducting elements in parallel, and the first to fourth switching elements respectively include reverse-direction parasitic diodes.
To a fourth field effect transistor, the power supply device. 12. The series circuit of an AC power supply and a first inductor according to claim 10, wherein the AC power supply side is connected to a connection point of the first and second switching elements, and the load circuit and the second inductor are connected. The power supply device is characterized in that the load circuit side is connected to the connection point of the first and second switching elements. 13. The circuit according to claim 1, wherein the first and second switching elements, each having a reverse-direction energization element in parallel, are connected in series so that the forward directions coincide with each other, and the reverse-direction energization. A circuit in which third and fourth switching elements each including elements in parallel are connected in series so that their forward directions match, and fifth and sixth switching elements each including reverse-direction energization elements in parallel are connected in the forward direction. A circuit connected in series so as to be coincident with each other is connected in parallel with a capacitor with the same polarity, and between the connection point of the first and second switching elements and the connection point of the fifth and sixth switching elements, A series circuit of an AC power supply and a first inductor is connected, and between the connection point of the first and second switching elements and the connection point of the third and fourth switching elements, the load circuit and the second circuit are connected. A power supply device comprising a circuit configuration in which a series circuit of inductors is connected. 14. The first to sixth switching elements according to claim 13, wherein the reverse-direction energization elements are respectively provided in parallel, and the first to sixth switching elements each have a reverse-direction parasitic diode.
To a sixth field effect transistor, a power supply device. 15. The current according to claim 10, wherein when the polarity of the connection point side of the first and second switching elements of the power supply is negative, the current of the first power conversion circuit is Of the inductor, the first rectifying element or the reverse current-carrying element of the fifth switching element, and the state of forming a closed loop composed of the first switching element, and the current of the second power conversion circuit is the second inductor, The load circuit, the first switching element, and the third switching element constitute a closed loop at least at the same time, and the polarity of the connection side of the first and second switching elements of the power supply is positive. When the current of the first power conversion circuit is
Of the switching element, the second rectifying element or the reverse current-carrying element of the sixth switching element, and the state in which a closed loop is formed, and the current of the second power conversion circuit is the second inductor, A power supply device characterized by having at least a period in which a state forming a closed loop composed of a fourth switching element, a second switching element, and a load circuit is simultaneously established. 16. The current according to claim 10, wherein when the polarity of the connection point side of the first and second switching elements of the power supply is negative, the current of the first power conversion circuit is the power supply, the first Of the inductor, the first rectifying element or the reverse current-carrying element of the fifth switching element, and the state of forming a closed loop composed of the first switching element, and the current of the second power conversion circuit is the second inductor, A load circuit, a first switching element, a capacitor, and a state forming a closed loop composed of a fourth switching element are at least simultaneously established, and the connection point side of the first and second switching elements of the power supply When the polarity is positive, the current of the first power conversion circuit is the power source, the second switching element, the reverse rectifying element of the second rectifying element or the sixth switching element, and the first switching element. A closed loop composed of a inductor and a state in which the current of the second power conversion circuit forms a closed loop composed of a second inductor, a third switching element, a capacitor, a second switching element, and a load circuit. The power supply device is characterized in that it has at least a period in which both are established at the same time. 17. The method according to claim 13, wherein when the polarity of the connection point side of the first and second switching elements of the power source is negative, the current of the first power conversion circuit is the power source, the first A closed loop composed of the inductor, the sixth switching element, and the second switching element,
The current of the second power conversion circuit changes to the capacitor, the third switching element, the second inductor, the load circuit, and the second
Current of the first power conversion circuit when the polarity of the connection point side of the first and second switching elements of the power source is positive, which has at least a period in which a closed loop state of the switching elements of , Power supply, first switching element, fifth switching element, first
The state of forming a closed loop composed of the inductor of
The electric current of the power conversion circuit has at least a period in which a state forming a closed loop including a capacitor, a first switching element, a load circuit, a second inductor, and a fourth switching element is simultaneously established. Power supply. 18. The current of the first power conversion circuit according to claim 10, when the polarity of the connection point side of the first and second switching elements of the power supply is negative. A state forming a closed loop including a reverse current-carrying element of the first rectifying element or the fifth switching element, a capacitor, a second switching element, and a power source;
The power converter circuit current has at least a period in which a current forming a closed loop including the second inductor, the load circuit, the second switching element, and the fourth switching element is simultaneously established, And the polarity of the connection point side of the second switching element is positive, the current of the first power conversion circuit causes the first inductor, the power supply, the first switching element, the capacitor, the second rectifying element or the sixth A state forming a closed loop composed of the reverse current-carrying element of the switching element and the first inductor, and the current of the second power conversion circuit is the second inductor, the third switching element, the first switching element, A power supply device having at least a period in which a closed loop including a load circuit and a state forming a closed circuit are simultaneously established. 19. The current according to claim 10, wherein when the polarity of the connection point side of the first and second switching elements of the power source is negative, the current of the first power conversion circuit is the first inductor. A state forming a closed loop including a reverse current-carrying element of the first rectifying element or the fifth switching element, a capacitor, a second switching element, and a power supply;
The current of the power conversion circuit of at least has a period in which at least a state of forming a closed loop composed of a capacitor, a third switching element, a second inductor, a load circuit, and a second switching element is satisfied, When the polarity of the connection point side of the first and second switching elements is positive, the current of the first power conversion circuit causes the first inductor, the power supply, the first switching element, the capacitor, and the second rectifying element. Alternatively, the state of forming a closed loop including the reverse-direction energization element of the sixth switching element and the current of the second power conversion circuit causes the capacitor, the first switching element, the load circuit, the second inductor, and the fourth A power supply device having at least a period in which a state forming a closed loop including switching elements is simultaneously established. 20. The first inductor, the first rectifying element, or the fifth rectifier according to claim 10, wherein when the polarity of the connection point side of the first and second switching elements of the power source is negative. The first and second switching elements of the power source have at least a period during which a state forming a closed loop including the reverse-direction energization element of the switching element, the third switching element, the second inductor, the load circuit, and the power source is established. When the polarity of the connection point side of is positive, from the first inductor, the power supply, the load circuit, the second inductor, the fourth switching element, and the reverse directional element of the second rectifying element or the sixth switching element. A power supply device having at least a period during which a state forming a closed loop is formed. 21. The first inductor, the first rectifying element, or the fifth rectifier according to claim 10, wherein when the polarity of the connection point side of the first and second switching elements of the power source is negative. There is at least a period during which a state forming a closed loop consisting of the reverse-direction energizing element of the switching element, the capacitor, the fourth switching element, the second inductor, the load circuit, and the power supply is established, and the first and second power supplies When the polarity on the connection point side of the switching element is positive, the first inductor, the power supply, the load circuit, the second inductor, the third switching element, the capacitor, and the reverse of the second rectifying element or the sixth switching element. A power supply device characterized in that it has at least a period during which a state forming a closed loop composed of directional energization elements is established. 22. The series circuit according to claim 1, wherein the series circuit of the first and second rectifying elements and the series circuit of the third and fourth rectifying elements are connected in antiparallel with a capacitor, and a third circuit is provided. A series circuit of the fourth switching element is connected in parallel with the capacitor, a series circuit of the fifth and sixth rectifying elements and a series circuit of the first and second switching elements are connected in antiparallel, Rectifying element, first and second switching elements,
A circuit in which the eighth rectifying element is connected in series in this order and a series circuit of the ninth and tenth rectifying elements are connected in antiparallel with the capacitor, and a connection point of the first and second rectifying elements and a first rectifying element are connected. , Second
Connected to the connection point of the switching element, the connection point of the third and fourth rectifying elements and the connection point of the third and fourth switching elements, and the connection of the first and second switching elements. The first inductor is connected between the connection point and the connection point of the ninth and tenth rectifying elements, and the connection point of the first and second switching elements and the connection of the third and fourth switching elements. A series circuit including a second inductor and a load circuit is connected between the connection point and the point, and between the connection point of the fifth and sixth rectifying elements and the connection point of the ninth and tenth rectifying elements, A power supply device comprising a circuit configuration in which an AC power supply is connected via a filter circuit. 23. In any one of claims 10 to 21, when the polarity of the connection point side of the first and second switching elements of the power source is negative, the second and third switching elements are turned on.
During which the first and third switching elements are turned on, the first to fourth switching elements are turned off, and the polarity of the connection point side of the first and second switching elements of the power supply is positive. At this time, the first and fourth switching elements are turned on
The switching element is turned on, the second and fourth switching elements are turned on, and the first to fourth switching elements are turned off in this order, so that each switching element is switched at a frequency higher than the power supply frequency. A power supply device comprising the configured control means. 24. In any one of claims 10 to 21, when the polarity of the connection point side of the first and second switching elements of the power source is negative, the second and third switching elements are turned on.
During the period of turning on, the period of turning on only the second switching element, the period of turning off the first to fourth switching elements, when the polarity of the connection point side of the first and second switching elements of the power source is positive, Turn on the first and fourth switching elements
Is configured to have at least a state in which each switching element is switched at a frequency higher than the power supply frequency in the order of a period during which the switching element is turned on, a period during which only the first switching element is turned on, and a period during which the first to fourth switching elements are turned off. A power supply device comprising: 25. The power supply according to claim 2, wherein the load circuit is composed of a circuit including at least a discharge lamp, and the current output to the discharge lamp has a low-frequency substantially rectangular wave shape. apparatus.