JP3412113B2 - Acceleration power supply for gyrotron - Google Patents

Description

Detailed Description of the Invention

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a power supply device used in a gyrotron device, which includes a power supply device for acceleration for accelerating an electron beam and a power supply power supply device for supplying oscillation power. The present invention relates to a power supply device for acceleration used.

[0002]

2. Description of the Related Art For a gyrotron device including an acceleration power supply device for accelerating an electron beam and a power supply power supply device for supplying oscillating power for the purpose of achieving low capacity and high efficiency. An example of a conventional dual power supply type power supply system is disclosed, for example, in Japanese Patent Application Laid-Open No. 6-76748, "Power Supply Device for Gyrotron".

The structure of the dual power supply type power supply system for the gyrotron device described in the above publication will be briefly described with reference to FIG.

As shown in FIG. 12, the gyrotron device 102 is of a type having two collectors.
The cathode electrode 104 and the anode electrode 106 have a bipolar electron gun portion 108, a body portion 110 having a cavity resonator, a first collector 112 which is a bipolar collector portion, and a second collector 114. An acceleration power supply 120 for accelerating the electron beam 116 emitted from the cathode electrode 104 is connected between the cathode electrode 104 and the body portion 110. Electron beam 116 emitted from cathode electrode 104
In order to give an initial speed to the
And 128, and the voltage is divided and applied to the anode electrode 106. A first power supply power supply 122 is provided between the cathode electrode 104 and the first collector 112 and a second power supply power supply 124 is provided between the cathode electrode 104 and the second collector 114 to supply power necessary for gyrotron oscillation. But,
Each is connected. The strong magnetic field coil 118 generates a magnetic field for causing the electron beam 116 emitted from the cathode electrode 104 to cooperate with an electric field formed by the anode electrode 106 to cause a spiral motion. When the collector of the gyrotron device has one pole, the first collector 112 in FIG. 12 is eliminated and the first power supply source 122 is correspondingly eliminated (that is, only the second power supply source 124 is used as the power supply source). Of) configuration.

[0005]

An acceleration power supply 1 of a dual power supply type power supply system for a gyrotron device shown in FIG.
20, first power supply power supply 122 and second power supply power supply 1
The power supply configuration of 24 does not require a special configuration, and it has been considered that it is possible, for example, by using the method of "DC smoothing circuit not using LC filter" of Japanese Patent Laid-Open No. 3-1664068 of the present inventor. FIG. 13 shows the configuration of a DC smoothing circuit that does not use the LC filter. As shown in FIG. 13, LC
The DC smoothing circuit that does not use the filter is the primary side DC power supply 2
02, power supply DC power supply 224, secondary side DC power supply 20
4 and a DC voltage smoothing device 228. The primary side DC power source 202 includes a rectifier 220 and a smoothing capacitor 22.
3 and rectify the AC voltage 221 to generate a DC voltage as an output. The power supply DC power supply 224 includes a relatively low frequency inverter 225, a transformer 226, and a rectifier 22.
The output DC voltage of the primary side DC power supply 202 is received, converted into an AC voltage by the inverter 225, stepped up by the transformer 226 and rectified by the rectifier 227 to generate a DC voltage including ripples. The DC voltage smoothing device 228 includes a ripple compensation inverter 229, a high frequency transformer 230, and a rectifier 231, and receives the DC voltage of the primary side DC power supply 202 and converts it into an AC voltage having a frequency higher than the output AC voltage of the inverter 225. ,
The high-frequency transformer 230 boosts the voltage, and the rectifier 231 generates a voltage that compensates the ripple generated in the output of the power supply DC power supply 224. The secondary side DC power supply 204 has a configuration in which three rectifiers 227 and rectifiers 231 are connected in series to obtain a high voltage. Note that 232 is the load, 23
3 is the capacitance of the cable connecting the output of the secondary side DC power supply 204 and the load 232, which is generally small enough to be ignored.

By the way, the gyrotron uses a cavity resonator having a cylindrical shape. For this reason, the number of modes that generate high-frequency resonance is larger than that of a cavity having a rectangular shape or the like. When oscillating in a different mode different from the desired mode, the oscillation frequency shifts, and the radiation angle of the high frequency transmitted in the gyrotron also differs from that in the desired mode. On the other hand, the mode converter installed inside the gyrotron is designed assuming the conversion from a specific mode to a specific dissimilar mode, and when other modes are incident, it is reflected and causes a standing wave. Or, since the radiation angle is different from the desired radiation angle, high frequency is accumulated inside the gyrotron, which causes an abnormal electric field. Further, the high frequency output window outputs only a specific frequency, and generally the output frequency band is narrow. Therefore, when the oscillation frequency shifts due to the different mode oscillation of the gyrotron, it is reflected by the high frequency window and a standing wave is generated inside the gyrotron. When a standing wave is generated in this way and an abnormal electric field is formed in the gyrotron, a discharge is generated inside the gyrotron and destroys the gyrotron. Therefore, the gyrotron needs to be oscillated only in a predetermined mode at any time.

FIG. 14 shows the concept of mode characteristics related to oscillation of a gyrotron. As shown in FIG. 14, the gyrotron has a beam voltage region suitable for oscillating a predetermined mode, and when the beam voltage exceeds the upper limit beam voltage, it enters the abnormal mode region. Further, the oscillation efficiency is higher as the beam voltage is higher in a predetermined mode area, that is, the closer to the abnormal mode area. The gyrotron generally has lower oscillation efficiency than other electron tubes, and when it is attempted to perform operation with high oscillation efficiency, the gyrotron is in the vicinity of a boundary with another mode that is an abnormal mode (for example, V ₀ in FIG. 14). It is necessary to set the beam voltage to. Then, the beam voltage obtained and set becomes high due to fluctuations in the input voltage of the power supply, etc., and if the beam voltage exceeds the upper limit beam voltage of the predetermined mode area, the abnormal mode is entered, so that the oscillation efficiency in the predetermined mode is always stable. In order to obtain oscillation, the beam voltage is extremely stable, and it is necessary to prevent the beam voltage from exceeding the upper limit in the transient period after the power is turned on until the beam voltage reaches a steady state. Therefore, the gyrotron needs a beam accelerating power supply which has no ripple in the output voltage and no overshoot in the above transient period, and which has good stability. This point is remarkably different from the conditions of other oscillators such as electron tubes.

That is, the acceleration power source 120 shown in FIG.
Is not limited to any type of power supply, it has no overshoot, and empirically requires strict characteristics such as voltage fluctuations and ripples within ± 0.5% of the desired beam voltage. is there. As described above, when the power source having the configuration shown in FIG. 13 is applied to the acceleration power source 120,
Since there is no mechanism for controlling the output voltage so as to obtain a desired beam voltage, for example, it is not possible to absorb fluctuations in the input voltage and the voltage ripple can be suppressed within a desired range.
For example, it is difficult to stabilize within a desired beam voltage ± 0.5%.

Therefore, for example, a normal switching regulator system is applied to the power supply of FIG. 13 to detect an error between the output voltage and a desired voltage, and feedback control is performed to amplify the error by a predetermined number. In this case, an overshoot usually occurs, and the input impedance between the cathode and the body of the gyrotron device fluctuates considerably with respect to the nominal resistance when the gyrotron device starts operating.
In some cases, the output voltage may converge to a voltage value greatly different from the predetermined voltage, that is, so-called good settling cannot be stably obtained.

In other words, with the configuration shown in FIG. 13 or the above-mentioned modification, the regulator tube which is inefficient and requires protective equipment etc. is still required, and it is difficult to eliminate it. .

An object of the present invention is to provide an accelerating power supply for a gyrotron device which does not require a regulator tube, has no overshoot, and has high settability.

[0012]

In order to achieve the above object, the cathode part and the anode part which constitute an electron gun part for generating an electron beam, and the electron beam generated from the cathode part interact with each other to generate a large power. A gyrotron device having a body part including a cavity resonator that oscillates a high frequency, and a collector part that interacts and then traps an electron beam, wherein a voltage is applied between the cathode part and the body part. The accelerating power supply device for use in a gyrotron device that operates by receiving power from an accelerating power supply device for power supply and a power supply power supply device for applying a voltage between the cathode part and the collector part, A direct current chopper means for performing pulse width modulation of the rate D, which is a switching means for turning on / off an input direct current voltage, and an on / off state of the switching means. DC chopper means including a chopper control means for controlling ON / OFF, a smoothing means for smoothing an output voltage of the switching means, and an inverter means for converting an output DC voltage of the DC chopper means into a high frequency AC voltage. A high-frequency transformer for boosting the output AC voltage of the inverter, and a rectifier for rectifying the output AC voltage of the high-frequency transformer to obtain a high DC voltage used for applying between the cathode part and the body part. And means for detecting a voltage representing the output DC high voltage of the rectifying means and generating a signal representing the detected DC high voltage, and a DC reference voltage indicating a desired output DC voltage of the rectifying means. And a means for generating a signal, wherein the chopper control means subtracts the signal representing the detected DC high voltage from the signal representing the DC reference voltage. Means and, above and integral and the first predetermined factor k ₁ integrating-amplifier means for amplifying the output of the subtraction means, a signal representative of the detected DC high voltage second predetermined times f ₂ that amplifies the A means for detecting a current representative of the output direct current of the direct current chopper means and amplifying the signal representative of the detected direct current chopper output current by a third predetermined factor f _1; and a second predetermined factor f ₂ amplified. Means for adding a signal representing the detected DC chopper output current amplified by a third predetermined factor f ₁ to the signal representing the detected DC high voltage, and the addition from the output of the integrating / amplifying means. Subtracting means for subtracting the output of the means to generate the duty ratio D to control the on / off of the switching means, the transfer function of the transfer function between the input of the DC chopper means and the output of the rectifying means. The characteristic equation must have a negative real root. The features.

[0013]

The means for subtracting the detected DC high voltage signal from the DC reference voltage signal, and the integration / amplification means for integrating the output of the subtraction means and amplifying by a _first predetermined multiple k ₁ A means for amplifying the detected DC high voltage signal by a second predetermined factor f _2; and a current representing the output DC current of the DC chopper means is detected to represent the detected DC chopper output current. Means for amplifying the signal by a third predetermined factor f ₁ and the detected direct current amplified by a third predetermined factor f ₁ to the signal representing the detected DC high voltage amplified by a _second predetermined factor f ₂ Means for adding a signal representing a chopper output current, and subtraction for subtracting the output of the adding means from the output of the integrating / amplifying means to generate the conduction ratio D and controlling ON / OFF of the switching means. DC chopper control with means Since the characteristic equation of the transfer function between the input of the DC chopper means including the means and the output of the rectifying means has a negative real root, the accelerating power supply of the present invention has The output voltage rises without causing an overshoot in the transition period in which the output voltage becomes stable.

Further, the integration / amplification means integrates the difference obtained by subtracting the detected signal representing the DC high voltage from the signal representing the DC reference voltage by the subtraction means, and the first predetermined multiple k ₁ Since it is amplified, it has an extremely high settling property, a desired beam acceleration voltage can be obtained as an output voltage, and its fluctuation is extremely small and stable.

[0015]

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT A preferred embodiment of the present invention will be described below with reference to the drawings. Acceleration power supply unit 26 shown in the embodiment
Is particularly suitable for a gyrotron used for research and development of fusion plasma.

FIG. 1 shows an energy recovery gyrotron (Collector Potential Depr).
It is a figure showing the concept of an esed Gyrotron (henceforth "CPD gyrotron") and a power supply bias. In FIG. 1, reference numeral 10 denotes a gyrotron, which is a vacuum tube composed of an electron gun 12 mounted on a magnetic field of a high magnetic field, a body 16 including a cavity resonator 14, and a collector 18. The electron beam 20
In the cavity resonator 14 on the way, the energy of the electrons is partially converted into high-frequency energy by the principle of the electron cyclotron maser. Electron beam 20 after the end of oscillation
Is captured by the collector 18 and generates heat. In the conventional gyrotron and its power supply system, the efficiency of energy conversion into high frequencies is in the order of 30%, and most of them generate heat in the collector. Therefore, as described above, in the present embodiment, the insulator 22 is inserted between the body 16 and the collector 18 to insulate the body 16 and the collector 1.
A system for recovering the energy of electrons by applying a deceleration electric field between the eight. That is, the power supply system is connected to the cathode 24
Acceleration power supply unit 2 which gives an accelerating electric field to electrons between the body 16 and the body 16.
6 and a power supply unit 28 for supplying oscillation power,
Improves energy conversion efficiency.

Although the output voltage of the acceleration power supply unit 26 is higher than that of the power supply power supply unit 28, the current is much smaller and the power is low. However, since it directly affects the oscillation of the gyrotron, it is necessary to use a highly stabilized power supply.

FIG. 2 shows, in the form of a wiring diagram, an embodiment of the acceleration power supply unit 26 according to the present invention. FIG. 2 shows the configuration of the acceleration power supply unit 26 when a three-phase AC 420V 50Hz is used as the input power. The step-down transformer 30 steps down the AC 420V to 260V, and the diode rectifier 32 rectifies the AC 260V to obtain DC 350V. The smoothing reactor L ₁ and the capacitor C ₂ are for smoothing the rectified voltage. 34 is an insulated gate bipolar transistor (IGBT (Insulate)
d Gate Bipolar Transisto
r)) and the protective diode D1 thereof, and 36 is a chopper control unit 3 described in detail later.
It is 6. The IGBT TR1 (detailed configuration will be described later) of the switching unit 34 controlled by the chopper control unit 36 is the DC 3 obtained by the diode rectifier 32.
50V is turned on / off to adjust the current, and DC 250V is output. D2 acts as a so-called freewheeling diode. In order to obtain a DC voltage of the order of 100 kV required as an accelerating voltage, six inverters 38 are connected in parallel to the output of the switching unit 34 and each inverter 38
The DC voltage of 250V is converted into a rectangular wave of 5kHz by using the high frequency transformer 40 connected to the output of each inverter 38 to boost the voltage to approximately 16.7kV. Rectifier 42 using fast recovery diode for high voltage is used for each high frequency transformer 4
0 output and each output of the six rectifiers 42 are connected in series. Each rectifier 42 is 1
The rectangular wave voltage boosted to 6.7 kV is rectified, and DC 100 kV is applied to the output side of the six rectifiers 42 connected in series.
Outputs 00mA. Reference numeral 46 equivalently represents the input impedance between the cathode 24 and the body 16 of the gyrotron 10 of FIG. The smoothing reactor L ₂ and the capacitors C _{2 to} C ₇ are for smoothing the output voltage of the switching unit 34. The inverter 38, the high frequency transformer 40 and the rectifier 42 form a so-called DC-DC converter system. Since the inverter 38 having a high frequency of 5 kHz is used as described above, the capacitance on the extra high side can be reduced, so that the gyrotron 10 serving as the load of the acceleration power supply unit 26 can shut off the inverter 38 at high speed. It has the feature that

250V to 100kV (However, 6 units of D
This is the output voltage of a C-DC converter connected in series on the output side. ), The high-frequency transformer 40 needs to have a high transformation ratio while having a high frequency. Further, since the gyrotron needs a stable accelerating electric field, it dislikes voltage ripple and overshoot. Therefore, pulse width modulation (PWM) control is not performed for the control of the inverter 38, and a duty of 50% is basically used, PWM control is performed in the chopper control unit 36 to realize output voltage control.

First, a high-voltage transformer suitable for a gyrotron used for research and development of fusion plasma requires a particularly high voltage. In that case, a high-frequency transformer suitable for combination with the acceleration power source of the present invention will be described. To do.

An amorphous iron core is used for the iron core of the high frequency transformer 40. The high frequency transformer 40 has a Bm
The ax is 0.3T, the winding ratio is 33.6: 1, and the characteristic is that the frequency of 5 kHz (rectangular wave) is passed.
FIG. 3 shows the appearance of the high frequency transformer 40. The withstand voltage between the primary and secondary sides of the high-frequency transformer 40 needs to be as high as 100 kV, and therefore the insulating gap needs to be large. However, if the gap is large, the high frequency transformer 40
The voltage drop due to the impedance becomes large. Therefore, in order to suppress the impedance of the high frequency transformer 40 to a low level, a structure in which the secondary coil is sandwiched between the primary coils is taken as shown in FIG. As a result, the% impedance is set to 10%.

In order to operate the high frequency transformer 40 with a rectangular wave of 5 kHz, the frequency characteristic of the high frequency transformer 40 needs to have a sine wave with a margin of 5 kHz or more. FIG. 4 shows the frequency characteristics of the high frequency transformer 40. From FIG.
By adopting the structure described above and shown in FIG.
Gain flat characteristics up to kHz and phase 1
It can be seen that there is no noticeable delay up to 0 kHz. It should be noted that although the resonance point is at 20 kHz and the gain changes sharply, it has been confirmed that there is no problem in practical use.

FIG. 5 shows an output waveform when a 5 kHz rectangular wave is input to the high frequency transformer 40. From FIG. 5, it can be seen that the voltage is boosted while maintaining the shape of the rectangular wave. It should be noted that although the influence of the above-mentioned resonance point appears at the time of startup and overshoot occurs, it has been confirmed that there is no practical problem.

Next, the control of the inverter 38 will be described. In order to alleviate the commutation ripple, the control of the inverter 38 shifts the phase angle by 30 ° and performs ignition control. The PWM control is not performed in the inverter 38 for the purpose of suppressing ripple. Figure 6 shows 50V on the low voltage side
The measurement result of the output voltage waveform of each inverter 38 at the time of driving is shown. The INV. 1-INV. 6 corresponds to each of the six inverters 38 shown in FIG. 2 in order from the top. It can be seen from FIG. 6 that the result is good with no phase shift. The PWM control of the inverter 38 is not always necessary for the present invention, and the PWM control may be performed according to the application.

Finally, the chopper control peculiar to the present invention will be described in detail. The IGTBTR1 shown in FIG. 2 actually has a configuration in which four IGTBs are connected in parallel instead of one IGTB. Therefore, the chopper circuit is 600
V, 100A IGTB in 4 parallel configuration 10
It is composed of a smoothing reactor L ₂ of 0 μH and six capacitors C _{2 to} C ₇ having a total capacitance of 820 μF and each having the same capacitance. Under the control of the chopper control unit 36, the switching unit 34 performs PWM chopper control with a 10 kHz cycle.

The controlled object model of the chopper control is considered as a secondary system of the sum of the smoothing reactor L ₂ and the capacitors C _{2 to} C ₇ by switching the chopper, and the purpose of the servo system is to control the capacitor voltage. , Fig. 7
The equivalent circuit of the chopper control shown in Fig. 3 is analyzed.
In FIG. 7, L represents the smoothing reactor L ₂ and
C represents the sum of the capacitor C ₂ -C _7, S represents the TR1 in Figure 2, D represents D2 of FIG. 2, R is the load, in the case of the present embodiment six in FIG. 2 It is assumed that the nominal input resistance between the body 16 and the cathode 24 of the gyrotron 10 of FIG. 1 connected to the series connected output of the rectifier 42 is represented. 7A shows the state when the switch S is on, and FIG. 7B shows the state when the switch S is off.

The state equation when the switch S is on is shown in FIG.
From (a) of, it is expressed as the following equation.

[0028]

[Equation 1] Further, the state equation when the switch S is off is represented by the following equation from FIG. 7B.

[0029]

[Equation 2] When the state averaging method is used for these two equations, they can be summarized as the following equations.

[0030]

[Equation 3] However, D is the PWM duty ratio, that is, the duty ratio (0 <D <1).

On the other hand, the output equation can be expressed by the following equation.

[0032]

[Equation 4] FIG. 8 shows a capacitor voltage V _C (corresponding to the output voltage of the acceleration power supply unit 26, that is, the voltage applied between the body 16 and the cathode 24 of the gyrotron 10) in consideration of the settling property described later in the servo system of this system. FIG. 7 is a state variable diagram of chopper control in which an integral control for integrating and controlling an error e between a reference voltage V _reff representing a desired applied voltage and control is introduced. Since the symbols shown in FIG. 8 are used in general automatic control, description thereof will be omitted. In FIG. 8, the system in the broken line labeled as a plant corresponds to the equation (3), which corresponds to the gyrotron 10 through the rectifier 42 from the switching unit 34 at the conduction ratio D in the configuration shown in FIG.
Corresponding to the part between the body 16 and the cathode 24 (FIG. 1) up to the nominal input resistance R. In FIG. 8, components outside the broken line correspond to the chopper control unit 36 in FIG.

In the servo system shown in FIG. 8, f ₁ and f ₂
Considering the expanded system which is separated by the plant input (point D in the figure) except for the feedback system of, the state equation of the expanded system can be expressed as the following equation.

[0034]

[Equation 5] The feedback of this system is expressed as the following equation.

[0035]

[Equation 6] However, f ₁ , f ₂ and k represent respective gains of the reactor current i _L , the capacitor voltage v _C and the integral z. Expression (6) is obtained by amplifying the reactor current i _L by the f ₁ gain element (actually amplifier) 50 and amplifying the capacitor voltage V _C by the f ₂ gain element (actually amplifier) 52 shown in FIG. Then, these outputs are added by the adder 54, and this output is input as the input D of the plant by subtracting the output z of the integrator 56 from the output of the k gain element (actually amplifier) 58 by the subtractor 60. Corresponds to the part. In addition,
Each V _C and i _L shown in FIG. 8 is actually detected by the detecting means shown in FIG. 2 as follows. Rectifier 42
The first detection unit 70 which divides the voltage of the output connected in series by the resistor divider and detects the voltage of the differential type by the reference voltage V
_{It detects the} capacitor voltage V _C which is compared with _reff .
The second detection unit 72, which detects the input voltage of the inverter 38 by dividing it with a resistance divider, detects V _C input to the f ₂ gain element 52. i _L is the reactor current detector 74
Detected by. Moreover, 1 / CR in the plant of FIG.
And V _C input to the 1 / L element are the first detection unit 70.
It uses the one detected in.

By substituting the equation (6) into the equation (5) which is the state equation of the expansion system, the following equation is obtained.

[0037]

[Equation 7] From this, when the transfer function is obtained together with the equation (4) of the output equation, the following equation is obtained.

[0038]

[Equation 8] Since the gyrotron acceleration power supply dislikes overshoot, it is necessary that the characteristic equation of equation (8) has a negative real root and that the smoothing reactor L, that is, L ₂ in FIG. 2 does not become an overcurrent. Is. The values of the feedback gains f ₁ , f ₂ and k that satisfy this are determined.

In FIG. 9, f ₁ = 2.3 × 10 ⁻³ , f ₂ = 1.
The calculation result of the step response of the voltage applied to the low voltage output v _{c, that} is, the capacitors C _{2 to} C ₇ is shown by using the MATLAB simulation code when 5 × 10 ⁻³ and k = 1.3.

FIG. 10 shows the reactor current and the extra-high output voltage (that is, 6 in FIG. 2) when the load resistance R = 490 kΩ.
The step response measurement result of the serially connected output voltage of the rectifier 42 of the stand is shown.

It can be seen from FIGS. 9 and 10 that the response is about 20 ms, and the calculation result and the measurement result match (however, the measurement result is the extra-high-side output voltage).

A CPD with a frequency of 110 GHz jointly developed by the present applicant and Toshiba using the acceleration power supply unit 26 of this embodiment.
The result of an actual operation test using the gyrotron E3972 is shown in FIG. The voltage V _C between the cathode and collector of the CPD gyrotron is 43 kV, and the current I _c flowing through the collector is 17 A. On the other hand, the acceleration power supply voltage V _a
Is 77 kV, its output current I _a is 66 mA, and the stability and settling of the acceleration power supply voltage satisfy ± 0.5%.
The operation time of the CPD gyrotron oscillation is 5 seconds, which is far longer than the conventional operation time of 10 milliseconds. During this time, the oscillation power is 350
At kW, the energy conversion efficiency has dramatically increased from the conventional 30% level to 48%. As described above, this experiment is the first in the world to raise the energy conversion efficiency to 48% by the oscillation of several seconds and several hundred kW, thus demonstrating the usefulness of this embodiment.

[0043]

Since the present invention is constructed as described above, it has the following operational effects. That is, the integral control and the state feedback control are used in combination with the chopper control, and the characteristic equation of the transfer function of the system has a negative real root so that, for example, 2
High-speed startup of 0 ms is possible.

Further, due to the fluctuation of the input impedance during the operation between the cathode and the body of the gyrotron,
In the conventional feedback system using only proportional control, in some cases the desired voltage is not converged, and the settling property is poor. It is possible to achieve extremely high stability.

By using the accelerating power source of the present invention having no overshoot and having extremely high settling property, it becomes possible to operate the gyrotron near the upper limit voltage of the stable mode, and the energy conversion efficiency of the gyrotron is remarkably improved. It is possible to raise it. For example, CPD for improving the energy conversion efficiency of gyrotron
A long pulse gyrotron accelerating power source of the order of seconds required to drive the gyrotron is possible.

[Brief description of drawings]

FIG. 1 is a diagram illustrating the concept of energy recovery (CPD) gyrotron and power supply bias.

FIG. 2 is a connection diagram showing an embodiment of an acceleration power supply for a gyrotron according to the present invention.

FIG. 3 shows an appearance of a high frequency transformer 40 of the embodiment shown in FIG.

FIG. 4 shows frequency characteristics of a high frequency transformer 40.

FIG. 5 is a photograph of an oscilloscope waveform showing an output waveform when a 5 kHz rectangular wave is input to the high frequency transformer 40.

6 is a photograph of an oscilloscope waveform showing the measurement result of the output voltage waveform of each inverter 38 of FIG. 2 when the low voltage side is operated at 50V. INV. 1-INV. 6 corresponds to each of the six inverters 38 shown in FIG. 2 in order from the top.

FIG. 7 is a diagram showing an equivalent circuit of chopper control,
(A) shows the state when the switch S is on, and (b) shows the state when the switch S is off.

FIG. 8 is a state variable diagram of chopper control in which integral control according to the present invention is introduced.

FIG. 9: f ₁ = 2.3 × 10 ⁻³ , f ₂ = 1.5 × 10
Using MATLAB simulation code when the ^-3 and k = 1.3 is a diagram showing calculation results of the step response of the low-pressure output _{V c.}

FIG. 10 is a photograph of an oscilloscope waveform showing the step response measurement results of the reactor current and the extra-high output voltage when the load resistance R = 490 kΩ.

FIG. 11 is an oscillographic waveform photograph showing the results of an actual operation test using a CPD gyrotron E3972 with a frequency of 110 GHz, using the acceleration power supply unit 26 of the present embodiment.

FIG. 12 is a diagram showing a configuration of a conventional dual power supply type power supply system for a gyrotron device.

FIG. 13 is a diagram showing a configuration of a conventional DC smoothing circuit that does not use an LC filter.

FIG. 14 is a diagram showing a concept of mode characteristics related to oscillation of a gyrotron.

[Explanation of symbols]

26 Acceleration Power Supply Section 34 Switching Section 36 Chopper Control Section 38 Inverter 40 High Frequency Transformer 42 Rectifier 50 f ₁ Gain Element 52 f ₂ Gain Element 54 Adder 56 Integrator 58 k Gain Element 60 Subtractor 70 First Detection Section 72 Second Detector 74 Reactor current detector

─────────────────────────────────────────────────── ─── Continuation of the front page (72) Go Imai Tsuyoshi Imai 801 Mukaiyama, Naka-machi, Naka-gun, Naka-gun, Ibaraki Prefecture 1 In the Naka Institute of the Japan Atomic Energy Research Institute (72) Toshio Asaka 613-9 Namikicho, Sano-shi, Tochigi Prefecture ( 72) Inventor Toshimitsu Iiyama 195, Tanuma, Tanuma-cho, Anso-gun, Tochigi Prefecture (56) Reference JP 59-12544 (JP, A) JP 6-76748 (JP, A) JP 3-164068 (JP) , A) Japanese Unexamined Patent Publication No. 6-290880 (JP, A) SAI 61-90150 (JP, U) (58) Fields investigated (Int.Cl. ⁷ , DB name) H01J 23/34

Claims (2)

(57) [Claims] 1. A body including a cathode part and an anode part which constitute an electron gun part for generating an electron beam, and a cavity resonator which interacts with the electron beam generated from the cathode part and oscillates a high power high frequency. A gyrotron device having a collector part and a collector part for trapping an electron beam after interacting with each other, an acceleration power supply device for applying a voltage between the cathode part and the body part, the cathode part, and A DC chopper means for performing pulse width modulation of a conduction ratio D in an accelerating power supply device used in a gyrotron device which operates by receiving power from a power supply power supply device for applying a voltage between the collector parts. Switching means for turning on / off the input DC voltage, chopper control means for controlling on / off of the switching means, and DC chopper means including smoothing means for smoothing the output voltage of the switching means, inverter means for converting the output DC voltage of the DC chopper means into high frequency AC voltage, and boosting the output AC voltage of the inverter means. A high-frequency transformer, a rectifier that rectifies the output alternating voltage of the high-frequency transformer to obtain a direct current high voltage used for applying between the cathode part and the body part, and an output direct current high voltage of the rectifier. And a means for generating a signal representing the detected high DC voltage, and a means for generating a signal representing a DC reference voltage indicating a desired output DC voltage of the rectifying means, the chopper The control means subtracts a signal representing the detected DC high voltage from the signal representing the DC reference voltage, and an output of the subtraction means. A minute vital first predetermined factor k ₁ integrating-amplifier means for amplifying a signal representative of the detected DC high voltage second predetermined factor f
₂ means for amplifying, a means for detecting a current representing an output direct current of the direct current chopper means, and amplifying a signal representing the detected direct current chopper output current by a third predetermined multiple f _1, and a second predetermined multiple and means for adding a signal representative of a third predetermined times f ₁ amplified the detected DC chopper output current signal representing the f ₂ amplified the detected DC high voltage, the output of the integrator-amplifier means Between the input of the DC chopper means and the output of the rectifying means, the subtracting means controlling the ON / OFF of the switching means by generating the conduction ratio D by subtracting the output of the adding means from An accelerating power supply device for a gyrotron device, characterized in that the characteristic equation of the transfer function of has a negative real root. 2. The acceleration power supply device for a gyrotron device according to claim 1, wherein the smoothing means has an inductor whose one end is coupled to the output of the DC chopper means, and the other end of the inductor and the acceleration power supply device. An acceleration power supply device for a gyrotron device, comprising: a capacitor connected between common lines.