JP3389740B2 - AC generator - Google Patents

Description

Detailed Description of the Invention

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to an AC generator equipped with a full-wave rectifier circuit, which can be used as, for example, a battery charging generator installed in a vehicle or the like, a generator for an electric vehicle or a motor generator. Is.

[0002]

2. Description of the Related Art An AC power generator shown as an example is shown in FIG.
A rotor 110 having a field winding 100 as shown in FIG.
And a stator (not shown) having a three-phase armature winding 120, and the field winding 100 is excited by the excitation circuit 130 to rotate the rotor (field) 110. Each phase winding 120a, 120b of the wire 120,
An induced phase voltage is generated in each of 120c. The induced phase voltage is converted (rectified) into direct current by a full-wave rectifier composed of six diodes 140 and supplied to the battery 150 and the electric load 160.

This AC generator is required to have a high output (in particular, an output in the low engine speed range) as the electric load increases. Therefore, as a means for improving the power generation output, it is possible to increase the size of the generator, increase the field current, and select the number of windings of the armature winding according to the rotation speed range used in the generator. Can be mentioned.

[0004]

However, in recent years,
Since the mounting space in the engine room tends to be reduced, higher output and smaller size of the generator are required. However, although the above-mentioned method of increasing the physique can improve the output over the entire range from the low rotation speed range to the high rotation speed range as shown in FIG. 34, it is against the demand for miniaturization. In the method of increasing the field current, FIG.
As shown in, the output can be improved in the high speed range, but the output in the low speed range cannot be expected so much. In the method of changing the number of windings of the armature winding in the range of the number of rotations used, as shown in FIG. 36, when the number of windings is reduced, the output in the high rotation speed range is improved, but the output in the low rotation speed range is improved. This will result in a decline. Conversely, if a large number of windings are selected to improve the output in the low rotation speed range, the body size becomes large and the output in the high rotation speed range decreases. As described above, in the conventional power generation method, it is difficult to improve the power generation output particularly in the low rotation speed region where the amount of power generation is required without significantly expanding the size of the generator. Therefore, a completely new way of controlling the output of the generator is required.

Therefore, the inventor of the present application considered technical means for improving the output based on the power generation principle. The consideration process will be described below. FIG. 37 is a circuit diagram of a one-phase model showing the power generation principle. In this one phase model, armature resistance r _a, an armature inductance L, and the load resistance R is connected in series, to which an AC voltage source (induced phase voltage E0
) Has been added. Therefore, the voltage V applied across the load resistor R is delayed by the phase difference δ with respect to the induced phase voltage E ₀ as shown in FIGS. 38 and 39.

This phase difference δ is passively determined by the relationship between R and r _a and ωL, and is obtained by the following mathematical formula.

## EQU1 ## δ = tan ⁻¹ {ωL / (R + r _a )} ω: Electrical angular velocity [ω = (p / 2) × (n / 60) × 2
π] p: Number of magnetic poles n: Number of rotations (rpm) On the other hand, the phase current I flowing through the load resistance R can be obtained by the following mathematical formula.

## EQU2 ## I = (E ₀ −V cos δ) / Z _s Z _s : Synchronous impedance [= {(ωL) ² +
r _a ² }]

Here, since the frequency is low in the low rotation speed range, ω becomes small. Therefore, since ωL becomes smaller, δ becomes smaller than the above expression 1. That is, it can be said that the lower the rotational speed, the smaller the delay of the voltage V with respect to the induced phase voltage E ₀ . Therefore, the lower the rotational speed, that is, the smaller δ, the larger cos δ in the above equation 2, so the phase current I flowing through the load resistance R becomes smaller. As a result, the power generation output P also decreases (see FIG. 40).

From the above results, E can be obtained even at low speed rotation.
_The inventor has considered that if the phase difference δ between ₀ and V can be made large, I can be increased and the overall output current can be increased, so that the power generation output P can be improved. Therefore, the inventor applies an AC voltage delayed by an arbitrary electrical angle to the induced line voltage (or induced phase voltage) generated in the armature between adjacent phase windings (or phase windings). , It was noted that the phase difference δ between E ₀ and V can be increased by creating a combined voltage having a phase delayed with respect to the induced line voltage (or induced phase voltage). The present invention has been made based on the above circumstances.
An object of the present invention is to provide a new control method, and to provide an AC generator capable of improving the power generation output (particularly in the low rotation speed range) without expanding the physique.

[0009]

In order to achieve the above object, the present invention has a field winding according to claim 1, and a magnetic field is generated in the field winding to generate a magnetic flux. And an armature winding formed by connecting n phase windings to each other, and an armature in which an induced phase voltage is generated in the phase winding due to relative rotation with the field, A bridge-type full-wave rectification circuit including at least n switching elements connected to the armature winding, and at least these switching elements perform full-wave rectification of the induced phase voltage generated in the phase winding to supply the load. And a switching means for forming a voltage applying circuit for applying a part of the output voltage of the full-wave rectifier circuit to a part of the armature winding as an AC voltage, and the armature winding by the voltage applying circuit. The phase of the AC voltage applied to a part of the wire A phase advance having an arbitrary delay angle with respect to the phase of the induced line voltage generated between the adjacent phase windings and having a lead angle with respect to the phase of the applied AC voltage toward the armature winding. The technical means of including a drive circuit for driving the switching element so as to flow a current is adopted.

According to a second aspect of the present invention, in the AC generator according to the first aspect, field current control means for controlling the field current based on the output voltage of the full-wave rectifier circuit, and the power generation output are detected. Power generation output detection means, relative rotation speed detection means for detecting the relative rotation speed of the field and the armature,
At any given power generation output and at any relative rotation speed of the field and the armature, a control map in which the delay angle that is a combination of the field current with the minimum loss and the phase current is stored in advance, And a map circuit for setting the delay angle from the control map in correspondence with the information obtained by the power generation output detection means and the relative rotation speed detection means.

According to a third aspect of the present invention, in the alternating-current power generator according to the first aspect, field current control means for controlling the field current based on the output voltage of the full-wave rectifier circuit, and power generation load torque are detected. And a feedback circuit for setting the delay angle so that the power generation load torque is minimized based on the information obtained by the power generation load torque detection means.

According to a fourth aspect of the present invention, in the AC generator according to the first aspect, a part of the armature winding is a space between adjacent phase windings. According to a fifth aspect, in the alternating-current power generation device according to the first aspect,
A part of the armature winding is the phase winding.

According to a sixth aspect, in the AC generator according to the first aspect, the arbitrary delay angle is 30 to 120.
The angle is determined from within the range of °. According to a seventh aspect, in the alternating-current power generator according to the first aspect, the alternating voltage applied by the voltage applying circuit is a pseudo sine wave that changes stepwise.

According to an eighth aspect of the present invention, in the alternating-current power generator according to the first aspect, the alternating voltage applied by the voltage applying circuit is composed of a rectangular pulse group formed by PWM control. According to a ninth aspect, in the AC generator according to the first aspect, the switching element includes a switching element portion that constitutes the voltage application circuit and a switching element portion that constitutes the bridge type full-wave rectification circuit. Is characterized by.

According to a tenth aspect, in the AC generator according to the first aspect, the switching element portion forming the voltage application circuit is a transistor, and the switching element portion forming the bridge type full-wave rectification circuit. Is a diode. In the eleventh aspect, in the AC generator according to the first aspect, the switching element portion forming the voltage application circuit and the switching element portion forming the bridge type full-wave rectification circuit are integrated elements. Is characterized by.

According to a twelfth aspect, in the AC generator according to the first aspect, the switching element is an IGBT.
It is characterized by being T. In claim 13, claim 1
In the AC power generator described in paragraph 1, the switching element is a MOS-FET.

[0017]

With the configuration of the present invention, a composite voltage having a phase delayed with respect to the induced phase voltage or the induced line voltage is created and a current is caused to flow toward the armature winding. Therefore, it becomes possible to arbitrarily control the output of the AC generator. In particular, since the output current can be increased when the generator has a low rotation speed, the output of the generator can be improved. Further, since the output can be controlled in the direction of lowering it, the output can be controlled even when the magnetic flux of the field is constant. Further, depending on the control mode, it is possible to improve the output regardless of the number of revolutions, and it is possible to provide a power generation device having a small size for the output.

In this way, the full-wave rectifier circuit is
Instead of receiving the voltage from the generator completely passively, by generating an applied AC voltage that also interferes with the voltage from itself, it is possible to change the mode of the armature output that acts on itself, and the full wave The DC output of the rectifier circuit can be controlled.

According to the second aspect, the delay angle corresponding to the power generation output detected by the power generation output detection means and the relative rotation speed between the field and the armature detected by the relative rotation speed detection means is calculated from the control map. Is set. The delay angle set from this control map is a combination of the field current and the phase current with the minimum loss (that is, the maximum efficiency) at an arbitrary power generation output and an arbitrary relative rotation speed of the field and the armature. Since it is a delay angle, it is possible to always generate power with maximum efficiency by driving the switching element so as to have that delay angle.

According to the third aspect, the delay angle is set by the feedback circuit so that the power generation load torque is minimized, that is, the power generation efficiency is maximized. Therefore, by driving the switching element so as to have the delay angle, it is possible to always generate power with maximum efficiency.

In the sixth aspect, the delay angle is 30 to
By selecting the angle of 120 °, the phase difference between the voltage generated in the armature and the AC voltage applied to the armature by the voltage application circuit becomes large, and a large current flows in the generator and the input side of the full-wave rectification circuit. It comes to flow between and. As a result, the power generation output (DC output) obtained from the output side of the full-wave rectifier circuit can be improved.

[0022]

Next, a first embodiment of the present invention will be described with reference to FIGS. FIG. 1 is an overall configuration diagram of a vehicle power generator. The vehicle generator 1 of this embodiment includes a rotor 3 (field) having a field winding 2, a stator 5 having an armature winding 4, and an exciting circuit for exciting the field winding 2 ( (Described below), a full-wave rectification circuit for full-wave rectifying the AC voltage induced in the armature winding 4 (described below), and a part of the output voltage of this full-wave rectification circuit is used for the stator 5 (armature). Voltage applying circuit (described below), the magnetic flux direction of the field winding 2 and the armature winding 4
Magnetic sensors 6, 7 for detecting the relative rotational position with respect to
8, an amplifier circuit 9 that amplifies the outputs of the magnetic sensors 6 to 8, a phase control circuit 10 that controls the voltage application circuit based on the output of the amplifier circuit 9, and a control circuit 11 that controls the excitation circuit.
It is composed of

The rotor 3 functions as a field when the field winding 2 is excited by the excitation circuit, and is rotationally driven by the rotational power of an engine (not shown) (counterclockwise direction in FIG. 1).
To be done. The armature winding 4 is a three-phase winding 4 that is Y-connected.
a, 4b, and 4c, and an induced phase voltage having a phase difference of 120 ° in electrical angle is generated in the order of the phase windings 4a, 4b, and 4c as the rotor 3 rotates. The exciting circuit includes a transistor 12 for connecting and disconnecting the exciting current, and the transistor 1
2 and a diode 13 connected in series.

The full-wave rectifier circuit (switching means of the present invention) is constructed by connecting six diodes 14a to 14f (switching elements of the present invention) in a bridge shape, and the output voltage after rectification is the battery. 15 and electric load 16. The voltage application circuit (switching means of the present invention) is composed of the diodes 14a to 14 of the full-wave rectification circuit.
6 transistors 17 connected in parallel with f
a to 17f (switching element of the present invention). The transistors 17a to 17f are connected so that the conduction directions are opposite to the diodes 14a to 14f.

The magnetic sensors 6 to 8 (position detecting means of the present invention) are, for example, as shown in FIG.
8a is used, and a drive current is passed through the Hall elements 6a to 8a to generate a voltage according to the orthogonal component of the magnetic flux applied to the sensing surface. This magnetic sensor 6-8
Is 90 in electrical angle with respect to each of the phase windings 4a to 4c.
° Three are installed at the delayed position. The amplifier circuit 9 has three operation amplifier circuits 9a, 9b, and 9c for amplifying the outputs of the magnetic sensors 6 to 8, respectively, as shown in FIG.
It is composed of

Phase control circuit 10 (driving circuit of the present invention)
Are transistors 17a to 17 of the voltage applying circuit according to a control signal created by digitally converting the output of the amplifier circuit 9.
As shown in FIG. 4, three hysteresis circuits 10a, 10b, and 10c, which control f, and whose hysteresis width can be arbitrarily set, and this hysteresis circuit 1
It is composed of three NOT circuits 10d, 10e, and 10f that output signals opposite to the output signals of 0a to 10c. The control circuit 11 is made of a well-known one, and the battery 15
Terminal for detecting the voltage of the Ignition switch 18
There is provided an IG terminal connected to the battery 15 via the, and a D terminal connected to the transistor (base) 12 of the excitation circuit.

Next, the operation of this embodiment will be described. The control circuit 1 is turned on by turning on the ignition switch 18 in FIG.
When the IG terminal of No. 1 and the battery 15 are connected, the control circuit 11 detects the voltage of the battery 15 and duty-controls the transistor 12 of the excitation circuit so as to obtain a power generation output corresponding to the battery voltage. The field winding 2 is excited with an appropriate current.

When the rotor 3 having the field winding 2 is rotationally driven by the engine, the armature winding 4 of the stator 5 has the phase windings 4a, 4b, 4c arranged in the order of 120 °. Induced phase voltages Eu, Ev, and Ew having a phase difference are generated (see FIG. 5A). At this time, the adjacent phase windings 4a and 4
The induced line voltages Eu-v, Ev-w, Ew-u generated between b, 4b and 4c, 4c and 4a are induced phase voltages Eu, Ev, E.
The phase is advanced by an electrical angle of 30 ° with respect to w (see FIG. 5 (b)). Note that Eu-v = Eu-Ev, E
vw = Ev-Ew and Ew-u = Ew-Eu.

Further, as the rotor 3 rotates, sensor outputs u, v, w having a phase difference of 120 ° in electrical angle are generated in each magnetic sensor 6-8. Each magnetic sensor 6 to 8 has an electrical angle of 90 ° with respect to the phase windings 4a, 4b, and 4c.
Since they are installed at the delayed positions, the sensor outputs u, v, w have the same phase as the induced phase voltages Eu, Ev, Ew, respectively (see FIG. 5 (c)).

The respective sensor outputs u, v, w are amplified by the amplifier circuit 9 and taken into the phase control circuit 10. In the phase control circuit 10, the hysteresis circuits 10a to 10c cause a digital signal U delayed by 60 ° in electrical angle from the sensor outputs u, v, and w (output of the amplifier circuit 9).
0, U1, V0, V1, W0, W1 (see FIG. 6 (a))
Is created and these digital signals U0, U1, V0, V
By driving the transistors 17a to 17f of the voltage applying circuit based on 1, W0 and W1, an AC voltage V is applied between the adjacent phase windings 4a and 4b, 4b and 4c, 4c and 4a.
UV, Vv-w, and Vw-u are applied (see FIG. 6B).

This applied AC voltage (applied line voltage) Vu-v
, Vv-w and Vw-u are induced phase voltages Eu and Ev, respectively.
, Ew is delayed by 30 ° in terms of electrical angle.
With respect to the induced line voltages Eu-v, Ev-w, and Ew-u shown in (b), the electrical angles are delayed by 60 °. At this time, the applied phase voltages Vu, Vv, Vw obtained by the applied AC voltages Vu-v, Vv-w, Vw-u are also relative to the induced phase voltages Eu, Ev, Ew (see FIG. 5 (a)). Each is delayed by 60 ° in electrical angle (see FIG. 6 (c)).

The induced line voltages Eu-v, Ev-w, Ew-
The delay angles of the applied AC voltages Vu-v, Vv-w, and Vw-u with respect to u can be changed from 0 to 90 ° in electrical angle according to the hysteresis width set by the hysteresis circuits 10a to 10c. The delay angle can be set by changing the positions of the magnetic sensors 6 to 8.

Here, the effect of the power generation system of this embodiment will be described based on comparison with the conventional power generation system. In the conventional power generation method, as shown in FIG.
_a , an armature inductance L, and a load resistance R are connected in series, an AC voltage source (induced phase voltage E ₀ ) is applied to this, and the voltage V applied across the load resistance R is
The phase difference δ is delayed with respect to the induced phase voltage E ₀ .

Since the phase difference δ is passively determined by the relationship between R and r _a and ωL (see Formula 1) as described in the section of the prior art, when the rotational speed is low ( When ω is small and this ω can be ignored), δ = 0 ° is considered, and the phase current I is obtained by the following equation. However,
k and k'are proportional constants.

## EQU3 ## I = (E ₀ -V) / Z _S = (E ₀ -V) / r _a = (kω-V) / r _a

When the rotation speed is high (ω is large and the resistance r _a is negligible compared to ω), it is considered that δ = 90 °, and the phase current I is calculated by the following equation. Desired.

Equation 4] _{I = E 0 / Z S =} E 0 / ωL = k '/ L As a result, in the conventional power generation, with respect to the rotational speed, FIG. 7
The output current shown by the broken line graph is obtained.

On the other hand, in the power generation method of the present embodiment (a circuit diagram of the one-phase model is shown in FIG. 8), δ is set depending on the drive timing of each of the transistors 17a to 17f forming the voltage application circuit.
Can be set to any angle. Therefore, for example, as shown in FIGS. 9 and 10, the phase voltage E with respect to the voltage V is controlled to have a delay angle of δ, and for example, δ
= 90 °, the phase current I flows in a form having a lead angle of the electrical angle ψ, that is, as a phase advance current. When the rotation speed is low (ω = small), the phase current I is obtained by the following equation.

## EQU5 ## I = E ₀ / Z _S = E ₀ / r _a = kω / r _a

When the rotation speed is high (ω = large), the phase current I is obtained by the following equation.

## EQU6 ## I = E ₀ / Z _S = E ₀ / ωL = k '/ L As a result, as shown in FIG. 11, a one-phase output is periodically generated in an electrically driven state, Due to this region, the power generation of the generator is assisted. Therefore, in the power generation method of the present embodiment, the output current shown by the solid line graph in FIG. 7 is obtained with respect to the rotation speed, and the output in the low rotation speed range is improved compared to the conventional power generation method (see FIG. 11). ).

The induced line voltages Eu-v, Ev-w, Ew-
12 and 13 show the relationship between the delay angle (phase difference) δ of the applied AC voltages Vu-v, Vv-w, and Vw-u with respect to u and the generated current and generated efficiency. According to the power generation method of the present embodiment, the delay angle δ = 90 °, as shown by the one-dot chain line graph in FIG.
At this time, the generated current becomes maximum in almost all the rotation speed regions, and as shown by the solid line graph in FIG. 13, when the delay angle δ = 60 °, it is possible to generate power with maximum efficiency in substantially all the rotation speed regions. Therefore, if the delay angle is set to about 90 ° (75 to 110 °), high output is obtained, and the delay angle is set to about 60 ° (40 to 75 °).
High efficiency can be obtained by setting to.

Next, a second embodiment of the present invention will be described. FIG. 14 is an overall configuration diagram of the vehicular power generation device 1 according to the second embodiment. In the present embodiment, the three phase windings 4a to 4c are Δ-connected, and the induced phase voltage generated in each of the phase windings 4a to 4c is represented by an electrical angle, as shown in FIG. 16 (d). AC voltage (pseudo sine wave) delayed by 30 ° is applied to each phase winding 4a ...
4c shows an example of application to 4c.

Next, a third embodiment of the present invention will be described. FIG. 17 is an overall configuration diagram of the vehicular power generation device 1 according to the third embodiment. In this embodiment, a PWM generation circuit 19 is provided instead of the phase control circuit 10 described in the first embodiment. The PWM generation circuit 19 includes transistors 17 that form a voltage application circuit based on a pulse signal (see FIG. 19D) created based on a sensor output (see FIG. 18C).
Drive a to 17f. As a result, the AC voltage composed of the rectangular pulse group (see FIG. 19E) is adjacent to the phase windings 4a and 4b at a phase delayed by 60 ° in electrical angle with respect to the line voltage generated in the stator 5. 4b and 4c, 4c and 4a
Applied between.

Next, a fourth embodiment of the present invention will be described. FIG. 20 is an overall configuration diagram of the vehicular power generation device 1 according to the fourth embodiment. The vehicular power generation device 1 of the present embodiment includes a current sensor 20 for detecting a DC output current that is full-wave rectified by a full-wave rectification circuit, in addition to the components (explanation thereof) described in the first embodiment. (Power generation output detection means of the present invention), F / V conversion circuit 21 (relative rotation speed detection means of the present invention) that calculates an electrical angular velocity from the sensor output u of the magnetic sensor 6, and map circuit that controls the phase control circuit 10. 22 is provided.

The map circuit 22 maps a delay angle, which is a combination of the field current and the phase current with the minimum loss, to an arbitrary relative rotational speed between the rotor 3 and the stator 5 and an arbitrary power generation output ( Stored control map (not shown)
And the hysteresis setting value corresponding to the delay angle set by this control map is set to the phase control circuit 10 (see FIG. 21).
Output to.

Here, the principle of improving power generation efficiency will be described. The AC generator 1 of this embodiment can be represented by the one-phase model shown in FIG. 22 and the vector diagram shown in FIG. Further, the phase current I is calculated by the following formula.

[Equation 7]

The output P that can be taken out as DC
Is calculated by the following equation in the case of a three-phase generator.

[Equation 8] _{P = I DC V DC = 3VIcosψ} = 3 (VE 0 / Z s) sinδ ...... ( derivation of the formula will be omitted)

The symbols used in the above equations are shown below. P: Power Output I: phase current E _0: induced phase voltage (= field current I functions _f) V: terminal voltage (constant) Z _s: synchronous impedance [= {(ωL) ² +
r _a ^2}] L: synchronous inductance r _a: the armature resistance (phase resistance) [delta]: load angle (angle of lag) [psi: power factor angle ^{_{ψ s: = tan -1 (ωL}} / r a) ω: electrical angular velocity ( = number of poles / 2 × 2πn / 60) n : number of revolutions (rpm) I _DC: DC output current V _DC: DC voltage

Next, the state at the time of power generation will be considered using the circle diagram (FIG. 24) which is a schematic representation of the above formulas for calculating the phase current I and the output P. In the circle diagram of FIG. 24, the locus of point p at which the output is constant is as follows.

[Equation 9]

In general, since r _a << ω, ψ _s ≈π /
2 and substituting this into the above equation,

[Equation 10]

Therefore, if the output P is constant, bp (the distance between the points b and p) is constant, and bp is centered around the point b.
A circle having a radius of is a locus for a constant output P. This circle is called the output circle p _a . Now, consider a state in which the rotation speed n and the output P are constant (at this time, since the rotation speed n is constant, the synchronous impedance Z _s is also constant). Since the output P is constant, the point p moves on the output circle p _a . When the point p becomes equal to the point c, the induced phase voltage E ₀ becomes the minimum, that is, the field current _If becomes the minimum. The induced phase voltage E ₀ increases as the field current I _f increases, and the point p is the output circle p.
Since it moves clockwise on the circumference of _a , the phase current I decreases, and the phase current I becomes the minimum at the point d. This time,
The power factor angle ψ = 0 °, that is, the power factor becomes 100%.

In the normal power generation method using only the field current I _f control, the power factor is always 100%. The vector diagram and the circle diagram at that time are shown in FIGS. 25 and 26. By the way, the efficiency of the generator is expressed by the following equation.

Η = P / (P + P _c + P _f + P _i + P _m + P α) P: Power generation output P _c : Copper loss (armature copper loss) P _f : Field loss (field winding copper loss) P _i : Iron loss P _m : Mechanical loss Pα: Other loss

Here, P _i , P _m , and Pα are almost constant losses under the conditions of constant terminal voltage and constant rotation speed. Further, P _c and P _f are respectively represented by the following equations.

## EQU12 ## P _c = 3r _a I ² P _f = r _f I _f ²

[0051] In normal field current I _f control only by the power generation system, in order to control the output P by adjusting the induced phase voltage E _0, i.e. the field current I _f, once the field current I _f, Since the phase current I is naturally determined, the sum of copper loss and field loss (P _c + P _f ) cannot be minimized. But,
On the output circle p _a shown in FIG. 24, the loss (P _c +) corresponding to the phase voltage and the load voltage is controlled by controlling the load angle δ.
It is possible to control the point where P _f ) is the minimum, that is, the maximum efficiency.

[0052] This example finds the optimal phase current I and the field current I _f in the power generation state of the generator, but which aims to be a high-efficiency power generation. The operation of this embodiment will be described below. When the IG terminal of the control circuit 11 and the battery 15 are connected by turning on the ignition switch 18, the control circuit 11 detects the voltage of the battery 15 and the battery voltage is the target voltage (for example, 14
The duty of the transistor 12 of the exciting circuit is controlled so that V becomes V), and the field winding 2 is excited with an appropriate current.

When the rotor 3 having the field winding 2 is rotationally driven by the engine, the armature winding 4 of the stator 5 has the phase windings 4a, 4b and 4c arranged in the order of 120 °. Induced phase voltages Eu, Ev, Ew having a phase difference are generated (see FIG. 27A). At this time, the adjacent phase windings 4a and 4
The induced line voltages Eu-v, Ev-w, Ew-u generated between b, 4b and 4c, 4c and 4a are induced phase voltages Eu, Ev, E.
The phase is advanced by an electrical angle of 30 ° with respect to w (see FIG. 27 (b)). Note that Eu-v = Eu-Ev,
Ev-w = Ev-Ew and Ew-u = Ew-Eu.

Further, as the rotor 3 rotates, sensor outputs u, v, w having a phase difference of 120 ° in electrical angle are generated in each magnetic sensor 6-8. Each magnetic sensor 6 to 8 has an electrical angle of 90 ° with respect to the phase windings 4a, 4b, and 4c.
Since they are installed at the delayed positions, the sensor outputs u, v, w have the same phase as the induced phase voltages Eu, Ev, Ew, respectively (see FIG. 27 (c)). This is because the magnetic sensors 6 to 8 detect the magnetic flux φ itself, and the magnetic flux φ advances by 90 ° with respect to the induced phase voltage E = −dφ / dt.

The respective sensor outputs u, v, w are amplified by the amplifier circuit 9 and taken into the phase control circuit 10. The phase control circuit 10 uses the hysteresis set value from the map circuit 22 to set the hysteresis circuit 1
Sensor outputs u, v, w (amplifier circuit 9
Output), digital signals U0, U1, V0, V1, W0 delayed by an angle corresponding to the hysteresis set value,
W1 (see FIG. 28A) is created. Here, a digital signal delayed by 60 ° in electrical angle is obtained by the hysteresis setting value. These digital signals U0, U1, V0,
By driving the respective transistors 17a to 17f of the voltage applying circuit based on V1, W0 and W1, AC voltages Vu-v and Vv- are applied between the adjacent phase windings 4a and 4b, 4b and 4c, 4c and 4a. w and Vw-u are applied (see FIG. 28B).

This applied AC voltage (voltage between applied lines) Vu-v
, Vv-w and Vw-u are induced phase voltages Eu and Ev, respectively.
, Ew is delayed by an electrical angle of 30 °.
With respect to the induced line voltages Eu-v, Ev-w, and Ew-u shown in 7 (b), the electrical angles are delayed by 60 °.
At this time, the applied phase voltages Vu, Vv, Vw obtained by the applied AC voltages Vu-v, Vv-w, Vw-u are also relative to the induced phase voltages Eu, Ev, Ew (see FIG. 27A). Each is delayed by 60 ° in electrical angle (see FIG. 28 (c)).
That is, the load angle δ (delay angle) can be set to 60 ° by the hysteresis setting value from the map circuit 22.
The method of setting the load angle δ by the hysteresis setting value from the map circuit 22 has been described above.

Next, high efficiency power generation by the map circuit 22 will be described. Now, the load angle δ is set to 60 ° by the hysteresis setting value from the map circuit 22, and the battery voltage is set to the target voltage (for example, 14V) by the control circuit 11.
The duty of the transistor 12 of the exciting circuit is controlled so that the field winding is excited with an appropriate current (I _f ).

The map circuit 22 determines the direct current I _DC at this time.
Is calculated by the current sensor 20 to calculate the demand power P by the product of the target voltage of the control circuit 11 and the demand power P and the electrical angular velocity signal ω from the F / V conversion circuit 21
The load angle δ at which the loss (P _c + P _f ) is minimum, that is, the point of maximum efficiency (combination of I and E _{0, that} is, the field current _If ) is read from the control map, and the hysteresis setting value corresponding to the load angle δ is read. Is output to the phase control circuit 10.

As a result, as shown in FIG. 29, the generator can always generate power with maximum efficiency in the entire speed range from the low speed range to the high speed range, and as a result, the vehicle can be saved. Fuel efficiency can be realized.

Next, a fifth embodiment of the present invention will be described. FIG. 30 is an overall configuration diagram of the vehicular power generation device 1 according to the fifth embodiment. The vehicular power generation device 1 of the present embodiment includes, in addition to the constituent elements (explanation thereof omitted) described in the first embodiment, torque detection means 23 for detecting the axial torque of the rotor 3, and this torque detection means 23. A feedback circuit 24 that controls the phase control circuit 10 based on the signal

In this embodiment, the load angle δ is set by the hysteresis setting value from the feedback circuit 24, and the operation is the same as in the fourth embodiment except the operation of the feedback circuit 24. Therefore, the operation of the feedback circuit 24 will be described using the algorithm shown in FIG.
Now, the load angle δ ₀ is set to 60 ° by the hysteresis setting value from the feedback circuit 24, and the control circuit 11 duty-controls the transistor 12 of the exciting circuit so that the battery voltage becomes the target voltage (for example, 14 V). It is assumed that the field winding 2 is excited with an appropriate current ( _If ).

The feedback circuit 24 not only adjusts the load angle δ but also feeds back the axial torque τ of the rotor 3 detected by the torque detecting means 23 so that the axial torque τ becomes minimum (minimum loss, maximum efficiency). The load angle δ is obtained, and the hysteresis setting value corresponding to the load angle δ is output to the phase control circuit 10. As a result, similarly to the fourth embodiment, it is possible to always generate power with maximum efficiency in the entire rotational speed range, and as a result, it is possible to realize fuel saving of the vehicle.

Next, a sixth embodiment of the present invention will be described. FIG. 32 is an overall configuration diagram of the vehicle power generation device 1 according to the sixth embodiment. In this embodiment, the three phase windings 4a of the first embodiment are used.
To 4c, the detection device 25 for detecting the current is provided, and the induced phase voltage Eu is derived from the current generated in each of the phase windings 4a to 4c.
The phases of Ev and Ew are obtained. With such a structure, it is not necessary to provide an output sensor as in the first embodiment, and the structure is simplified. Also,
In the sixth embodiment, as a switching element, MOS-FETs (27a, 27b, 27c, 27d, 27e, 27f) are used as shown in FIG. In this case, since the diode elements (26a, 26b, 26c, 26d, 26e, 26f) are integrally formed in each MOS-FET, the same operation and control as the switching element in the first embodiment can be performed. It can be carried out.

[Modification] In the embodiment, the transistors 17a to 1 are used as switching elements constituting the voltage application circuit.
Although 7f was used, a thyristor can also be used. In addition, the diodes 14a to constitute the full-wave rectification circuit
14f and transistors 17a that form a voltage application circuit
It is also possible to form an IGBT in which 17f and one element are integrally configured. Further, the three phase windings 4a to 4c are Y-connected (first embodiment, third embodiment) or Δ-connected (second embodiment) as the three-phase armature winding 4, but the number of phases and connection are Is not limited.

As the magnetic sensors 6 to 8, Hall elements 6a to
Although 8a is shown, a photo sensor may be used. Alternatively, a rotation sensor such as an encoder or a resolver may be installed. An amplifier circuit 9 as a signal processing circuit for the magnetic sensors 6 to 8
Although the hysteresis circuits 10a to 10c are used, a Hall IC or the like in which these circuits are integrated may be used.
In the embodiment, the example in which the rotor 3 is provided with the field winding 2 and the exciting current is variably controlled by the external exciting circuit (transistor 12 and diode 13) has been described. However, a magnetic rotor is used as the field. You may use. At this time, the excitation circuit is not necessary and the output can be adjusted by the delay angle δ.

In the fourth embodiment, the electrical angular velocity is calculated by the F / V conversion circuit 21 based on the sensor output u of the magnetic sensor 6, but the sensor output v of the magnetic sensor 7 or the sensor output w of the magnetic sensor 8 is calculated. It goes without saying that it may be calculated based on the above.

[Brief description of drawings]

FIG. 1 is an overall configuration diagram of a vehicle power generation device according to a first embodiment.

FIG. 2 is a schematic diagram of a magnetic sensor used in the first embodiment.

FIG. 3 is a circuit diagram showing a configuration of an amplifier circuit used in the first embodiment.

FIG. 4 is a circuit diagram showing a configuration of a phase control circuit used in the first embodiment.

FIG. 5 is a waveform diagram of an induced phase voltage, an induced line voltage, and a sensor output in the first embodiment.

FIG. 6 is a waveform chart of a transistor input signal, an applied line voltage, and an applied phase voltage in the first embodiment.

FIG. 7 is a graph comparing the power generator of the first embodiment with a conventional power generator.

FIG. 8 is a circuit diagram showing the power generation principle of the one-phase model of the first embodiment.

FIG. 9 is a vector diagram illustrating the power generation method of the first embodiment.

FIG. 10 is a voltage / current waveform diagram of the first embodiment.

FIG. 11 is a graph showing a power generation output according to the first embodiment.

FIG. 12 is a graph showing the relationship between the rotation speed and the generated current in both the first example and the conventional example.

FIG. 13 is a graph showing the relationship between rotation speed and power generation efficiency, as in FIG.

FIG. 14 is an overall configuration diagram of a vehicle power generation device according to a second embodiment.

FIG. 15 is a waveform diagram (a) of each part according to the second embodiment.
It is (b).

FIG. 16 is a waveform chart (c) of each part according to the second embodiment.
It is (d).

FIG. 17 is an overall configuration diagram of a vehicle power generation device according to a third embodiment.

FIG. 18 is a waveform chart (a) of each part according to the third embodiment.
It is (c).

FIG. 19 is a waveform chart (d) of each part according to the third embodiment.
(E).

FIG. 20 is an overall configuration diagram of a vehicle power generation device according to a fourth embodiment.

FIG. 21 is a circuit diagram showing a configuration of a phase control circuit used in a fourth embodiment.

FIG. 22 is a circuit diagram showing the power generation principle of the one-phase model of the fourth embodiment.

FIG. 23 is a vector diagram showing a power generation state according to the present power generation method (fourth example).

FIG. 24 is a circle diagram showing a power generation state according to the present power generation method (fourth example).

FIG. 25 is a vector diagram showing a power generation state according to a conventional power generation method.

FIG. 26 is a circle diagram showing a power generation state according to a conventional power generation method.

FIG. 27 is a waveform chart of an induced phase voltage, an induced line voltage, and a sensor output in the fourth example.

FIG. 28 is a transistor input signal according to the fourth embodiment;
It is each waveform figure of an applied line voltage and an applied phase voltage.

FIG. 29 is a graph showing power generation efficiency according to the present power generation method (fourth example).

FIG. 30 is an overall configuration diagram of a vehicle power generation device according to a fifth embodiment.

FIG. 31 is an algorithm showing the operation of the feedback circuit (fifth embodiment).

FIG. 32 is an overall configuration diagram of a vehicle power generation device according to a sixth embodiment.

FIG. 33 is a circuit diagram of a vehicle generator (prior art).

FIG. 34 is a graph illustrating an improvement in power generation output (prior art).

FIG. 35 is a graph illustrating an improvement in power generation output (prior art).

FIG. 36 is a graph illustrating an improvement in power generation output (prior art).

FIG. 37 is a circuit diagram of a one-phase model showing the principle of power generation (prior art).

FIG. 38 is a vector diagram of a conventional power generation method.

FIG. 39 is a voltage-current waveform diagram of a conventional power generation method.

FIG. 40 is a graph showing a power generation output by the conventional power generation method.

[Explanation of symbols]

DESCRIPTION OF SYMBOLS 1 Vehicle generator 3 Rotor (field) 4 Armature windings 4a to 4c Phase winding 5 Stator (armature) 6 to 8 Magnetic sensor (position detecting means) 10 Phase control circuit (driving circuit, first) Example, 2nd Example) 11 control circuit (field current control means) 14a-14f diode (switching element) 17a-17f transistor (switching element) 19 PWM generation circuit (driving circuit / third example) 20 current sensor (Power generation output detection means) 21 F / V conversion circuit (relative rotation speed detection means) 22 Map circuit 23 Torque detection means (power generation load torque detection means) 24 Feedback circuit 25 Current detection devices 26a to 26f Diodes (switching elements) 27a to 27f MOS-FET (switching element)

Continuation of front page (56) Reference JP-A-3-207225 (JP, A) JP-A-4-210739 (JP, A) JP-A-8-116699 (JP, A) JP-A-5-252670 (JP , A) (58) Fields surveyed (Int.Cl. ⁷ , DB name) H02J ^7/ 14-7/24 H02P 9/30

Claims (17)

(57) [Claims] 1. A field winding which has a field winding and which generates magnetic flux when a field current flows through the field winding, and an armature winding formed by connecting n phase windings. And an armature in which an induced phase voltage is generated in the phase winding due to relative rotation with the field, and at least n switching elements connected to the armature winding, and at least these switching elements are provided. The element forms a bridge type full-wave rectifier circuit that full-wave rectifies the induced phase voltage generated in the phase winding and supplies the load to the load, and a part of the output voltage of the full-wave rectifier circuit is part of the armature winding. A switching means that forms a voltage application circuit that applies an AC voltage to a part of the wire; and a phase of the AC voltage that is applied to a part of the armature winding by the voltage application circuit between adjacent phase windings. To the phase of the induced line voltage generated in Re AC power generator and a drive circuit for driving the switching element to flow leading phase current having an angle advances to the phase of the AC voltage the applied toward the armature winding and having a corner. 2. A field current control means for limiting the field current based on an output voltage of the full-wave rectifier circuit, a power generation output detection means for detecting a power generation output, and the field and the armature. Relative rotation speed detection means for detecting the relative rotation speed, at a given power generation output and at any relative rotation speed of the field and the armature, a combination of a field current and a phase current with minimum loss And a map circuit for setting the delay angle from the control map in accordance with the information obtained by the power generation output detection means and the relative rotation speed detection means. The alternating-current power generator according to claim 1. 3. A field current control means for controlling the field current based on the output voltage of the full-wave rectification circuit, a power generation load torque detection means for detecting a power generation load torque, and a power generation load torque detection means. The AC generator according to claim 1, further comprising: a feedback circuit that sets the delay angle so that the power generation load torque is minimized based on the obtained information. 4. The AC generator according to claim 1, wherein a part of the armature winding is a line between adjacent phase windings. 5. The AC generator according to claim 1, wherein the part of the armature winding is the phase winding. 6. The arbitrary delay angle is 30 ° to 120 °.
The alternating-current power generator according to claim 1, wherein the angle is determined from within the range. 7. The AC power generator according to claim 1, wherein the AC voltage applied by the voltage applying circuit comprises a pseudo sine wave that changes stepwise. 8. The AC generator according to claim 1, wherein the AC voltage applied by the voltage applying circuit is composed of a rectangular pulse group formed by PWM control. 9. The AC generator according to claim 1, wherein the switching element includes a switching element portion that constitutes the voltage application circuit and a switching element portion that constitutes the bridge type full-wave rectifier circuit. . 10. The switching element portion forming the voltage application circuit is a transistor, and the switching element portion forming the bridge type full-wave rectification circuit is a diode. AC generator. 11. The alternating current according to claim 1, wherein the switching element portion forming the voltage application circuit and the switching element portion forming the bridge type full-wave rectifier circuit are integrated elements. Power generator. 12. The AC generator according to claim 1, wherein the switching element is an IGBT. 13. The switching element is a MOS-FE.
The AC generator according to claim 1, wherein the AC generator is T. 14. A switching device comprising position detecting means for detecting a relative rotational position of the magnetic flux direction of the field and the armature winding, wherein the delay angle is based on a detection value of the position detecting means. The AC power generation device according to claim 1, wherein the AC power generation device is controlled by driving the. 15. A current detecting means for detecting a phase current is provided,
2. The delay angle is controlled by driving the switching element based on a current value detected by the current detection means and a phase voltage corresponding to the current value. AC generator. 16. A field winding having a field winding, wherein a field current generating a magnetic flux when a field current flows through the field winding, and an armature winding formed by connecting n phase windings. And an armature in which an induced phase voltage is generated in the phase winding due to relative rotation with the field, and at least n switching elements connected to the armature winding, and at least these switching elements are provided. The element forms a bridge-type full-wave rectifier circuit that full-wave rectifies the induced phase voltage generated in the phase winding and supplies the load to the load, and a part of the output voltage of the full-wave rectifier circuit is used for the armature winding. Switching means forming a voltage application circuit for applying an AC voltage to a part of the wire, and the phase of each phase voltage of the AC voltage applied to a part of the armature winding by the voltage application circuit has a corresponding induction Has an arbitrary delay angle with respect to the phase of the phase voltage AC power generator and a drive circuit for driving the switching element to flow leading phase current having an angle proceeds to phase of the applied phase voltages towards the armature winding with. 17. A field magnet for generating a magnetic flux and an armature winding formed by connecting n phase winding wires, and an induced phase voltage is applied to the phase winding wire as the field magnet rotates relative to the field magnet wire. Is provided, and at least n switching elements connected to the armature winding. The induced phase voltage generated in the phase winding is full-wave rectified by at least these switching elements to load. A switching unit that forms a bridge-type full-wave rectifier circuit for supplying, and forms a voltage application circuit that applies a part of the output voltage of the full-wave rectifier circuit to a part of the armature winding as an AC voltage; The phase of the AC voltage applied to a part of the armature winding by the voltage applying circuit has an arbitrary delay angle with respect to the phase of the induced line voltage generated between the adjacent phase windings, and the electric machine Direct current to the child winding AC power generator and a drive circuit for driving the switching element in Suyo.