JP2022087290A - Transmission device and reception device - Google Patents

Abstract

PROBLEM TO BE SOLVED: To improve reception quality in environment in which a direct wave is dominant, in a transmission method for simultaneously transmitting a plurality of modulation signals from a plurality of antennas.

SOLUTION: A transmission method transmits a first modulation signal and a second modulation signal simultaneously at the same frequency. By performing pre-coding on both signals by using a fixed pre-coding matrix, and regularly switching a phase of at least one of the first modulation signal and the second modulation signal to transmit them, reception quality of data improves in a reception device.

SELECTED DRAWING: Figure 6

COPYRIGHT: (C)2022,JPO&INPIT

Description

The present invention particularly relates to a transmitting device and a receiving device that perform communication using a multi-antenna.

Conventionally, as a communication method using a multi-antenna, for example, there is a communication method called MIMO (Multiple-Input Multiple-Autoput). In multi-antenna communication represented by MIMO, the communication speed of data is increased by modulating each of a plurality of series of transmission data and simultaneously transmitting each modulation signal from different antennas.

FIG. 23 shows an example of the configuration of the transmission / reception device when the number of transmission antennas is 2, the number of reception antennas is 2, and the number of transmission modulation signals (transmission streams) is 2. In the transmitting device, the encoded data is interleaved, the interleaved data is modulated, frequency conversion or the like is performed to generate a transmission signal, and the transmission signal is transmitted from the antenna. At this time, the spatial multiplex MIMO method is a method in which different modulated signals are transmitted from the transmitting antenna to the same frequency at the same time.

At this time, Patent Document 1 proposes a transmitting device having a different interleaving pattern for each transmitting antenna. That is, in the transmission device of FIG. 23, the two interleaves (πa, πb) have different interleave patterns. Then, in the receiving device, as shown in Non-Patent Document 1 and Non-Patent Document 2, the reception quality is improved by repeatedly performing the detection method using soft values (MIMO detector in FIG. 23). Will be done.

By the way, as a model of the actual propagation environment in wireless communication, there are an NLOS (non-line of light) environment represented by a Rayleigh fading environment and a LOS (line of light) environment represented by a rice fading environment. When transmitting a single modulated signal in the transmitting device, performing maximum ratio synthesis on the signal received by multiple antennas in the receiving device, and demodulating and decoding the signal after maximum ratio synthesis, the LOS environment, In particular, in an environment where the rice factor indicating the magnitude of the received power of the direct wave with respect to the received power of the scattered wave is large, good reception quality can be obtained. However, depending on the transmission method (for example, spatial multiplex MIMO transmission method), there arises a problem that the reception quality deteriorates as the rice factor increases. (See Non-Patent Document 3)
In FIGS. 24A and 24B, LDPC (low-density party-check) -encoded data is 2 × 2 in a ray-fading environment and a rice-fading environment with rice factors K = 3, 10, and 16 dB. (2 antenna transmission, 2 antenna reception) An example of the simulation result of BER (Bit Error Rate) characteristics (vertical axis: BER, horizontal axis: SNR (signal-to-noise power ratio)) in the case of spatial multiplex MIMO transmission is shown. ing. (A) of FIG. 24 is a BER characteristic of Max-log-APP (see Non-Patent Document 1 and Non-Patent Document 2) without repeated detection (APP: a posterior probability), and FIG. 24 (B) is a repeat. It shows the BER characteristics of the detected Max-log-APP (see Non-Patent Document 1 and Non-Patent Document 2) (number of repetitions 5 times). As can be seen from FIGS. 24 (A) and 24 (B), it can be confirmed that the reception quality deteriorates as the rice factor increases in the spatial multiplex MIMO system regardless of whether or not the repeated detection is performed. From this, it is possible to have a problem peculiar to the spatial multiplex MIMO system, which is not found in the conventional single modulated signal transmission system, that "in the spatial multiplex MIMO system, the reception quality deteriorates when the propagation environment becomes stable". Recognize.

Broadcasting and multicast communication are services that must support various propagation environments, and it is naturally possible that the radio wave propagation environment between the receiver and the broadcasting station possessed by the user is the LOS environment. When a spatial multiplex MIMO system having the above-mentioned problems is used for broadcasting or multicast communication, a phenomenon occurs in which the receiver cannot receive services due to deterioration of reception quality, although the reception electric field strength of radio waves is high. there is a possibility. That is, in order to use the spatial multiplex MIMO system in broadcasting and multicast communication, it is desired to develop a MIMO transmission method that can obtain a certain level of reception quality in both the NLOS environment and the LOS environment.

Non-Patent Document 8 describes a method of selecting a codebook (precoding matrix (also referred to as precoding weight matrix)) to be used for precoding from feedback information from a communication partner. There is no description about how to perform precoding in a situation where feedback information from the communication partner cannot be obtained, such as multicast communication.

On the other hand, Non-Patent Document 4 describes a method of switching the precoding matrix over time, which can be applied even when there is no feedback information. In this document, it is described that a unitary matrix is used as a matrix used for precoding and that the unitary matrix is randomly switched. However, the application method for the deterioration of reception quality in the LOS environment shown above is described. It is not mentioned at all, only the random switching is mentioned. As a matter of course, there is no description about the precoding method for improving the deterioration of the reception quality of the LOS environment and the method of constructing the precoding matrix.

International Publication No. 2005/050885

"Achieving near-capacity on a multiple-antenna channel" IEEE Transition on communications, vol. 51, no. 3, pp. 389-399, March 2003. "Performance analysis and design optimization of LDPC-coded MIMO OFDM systems" IEEE Transfers. Signal Processing. , Vol. 52, no. 2, pp. 348-361, Feb. 2004. "BER performance evolution in 2x2 MIMO partial multiplexing systems under Rician fading channels," IEICE Transfers. Fundamentals, vol. E91-A, no. 10, pp. 2798-2807, Oct. 2008. "Turbo space-time codes with time timing linear transformations," IEEE Trans. Wireless communications, vol. 6, no. 2, pp. 486-493, Feb. 2007. "Likelihood function for QR-MLD suitedable for soft-decision turbo decoding and it performance," IEICE Transfer. Commun. , Vol. E88-B, no. 1, pp. 47-57, Jan. 2004. "Signpost to the Shannon Limits:" Parallel Concatenate (Turbo) Coding "," Turbo (iterative) decoding "and its Surroundings" Institute of Electronics, Information and Communication Engineers, Intellectual Techniques IT98-51 "Advanced signal processing for PLCs: Wavelet-OFDM," Proc. of IEEE International symposium on ISPLC 2008, pp. 187-192, 2008. D. J. Love, and R. W. heath, Jr. , "Limited feedback frequency precoding for spectral multiplexing systems," IEEE Trans. Inf. Theory, vol. 51, no. 8, pp. 2967-2976, Aug. 2005. DVB Document A122, Framing structure, channel coding and modulation for a second generation digital terrestrial terrestrial television system2T L. Vangelista, N.M. Benvenuto, and S. Tomasin, "Key technologies for next-generation terrestrial digital television standard DVB-T2," IEEE Commun. Magazine, vol. 47, no. 10, pp. 146-153, Oct. 2009. T. Ohgane, T.M. Nishimura, and Y. Ogawa, "Application of multiplexing multiplexing and those performance in a MIMO channel," IEICE Trans. Commun. , Vol. E88-B, no. 5, pp. 1843-1851, May 2005. R. G. Gallagger, "Low-density parity-check codes," IRE Trans. Information. Theory, IT-8, pp-21-28, 1962. D. J. C. Mackay, "Good error-correcting codes based on very sparse matrix," IEEE Trans. Information. Theory, vol. 45, no. 2, pp399-431, March 1999. ETSI EN 302 307, "Second generation framing structure, channel coding and modulation systems for broadband stering, interactivity servicing, interactivity servicing" 1.1.2, June 2006. Y. -L. Weng, and C.I. -C. Cheng, "a fast-convergence decoding method and memory-effective VLSI architect architecture for irregular LDPC codes in the IEEE200.EEE-802.16eStand. 1255-1259. S. M. Alamouti, "A single transmit technology technology for wireless communications," IEEE J. Select. Ares Commun. , Vol. 16, no. 8, pp. 1451-1458, Oct 1998. V. Tarok, H. et al. Jafrkhani, and A. R. Calderbank, "Space-time block coding for wireless communications: Performance responses," IEEE J. Select. Ares Commun. , Vol.17, no. 3, no.3, pp. 451-460, March 1999.

An object of the present invention is to provide a MIMO system capable of improving reception quality in a LOS environment.

The transmission device according to the present invention generates a first transmission signal and a second transmission signal from a first modulation signal and a second modulation signal composed of in-phase components and orthogonal components based on a modulation method, and has the same frequency band and the same. A transmission device that transmits from one or more different output ports at different timings, and is predetermined for a phase changing unit that regularly changes the phase of an input modulated signal and an input modulated signal. A weighted synthesis unit that performs weighted synthesis using a fixed precoding matrix, and a signal based on at least one of the first modulated signal and the second modulated signal are phase-changed by the phase changing unit, and the first It is characterized in that both the modulated signal and the signal based on the second modulated signal are provided with a transmission unit for transmitting the first transmission signal and the second transmission signal generated by weighted synthesis by the weighted synthesis unit. do.

Further, the receiving device according to the present invention receives from the transmitting device the first transmission signal and the second transmission signal transmitted by the first transmission signal and the second transmission signal in the same frequency band and at the same timing. At least one of the first transmission signal and the second transmission signal is generated by regularly changing the phase of at least one of the original first modulation signal and the second modulation signal, respectively. The receiving unit and the signal received by the receiving unit are demoted by a demodulation method according to the first modulation signal or the modulation method used for the second modulation signal, and the first modulation signal and the first modulation signal are used. It is characterized by including a demodulator for obtaining a logarithmic likelihood ratio of transmission data which is a source of a second modulated signal.

Here, the signal based on the first modulation signal may refer to the case where the first modulation signal itself is used, the case where the phase of the first modulation signal is changed, or the case where the signal is weighted (precoded). be. Similarly, the signal based on the second modulation signal may refer to the second modulation signal itself, the phase of the second modulation signal may be changed, or the signal may be weighted (precoded). ..

As described above, according to the present invention, it is possible to provide a transmission method, a reception method, a transmission device, and a reception device for improving the deterioration of reception quality in the LOS environment. , Can provide high quality service.

Example of configuration of transmitter / receiver in spatial multiplex MIMO transmission system An example of frame configuration Example of transmitter configuration when phase change method is applied Example of transmitter configuration when phase change method is applied Example of frame configuration Example of phase change method Receiver configuration example Configuration example of the signal processing unit of the receiving device Configuration example of the signal processing unit of the receiving device Decryption processing method Example of reception status Example of transmitter configuration when phase change method is applied Example of transmitter configuration when phase change method is applied Example of frame configuration Example of frame configuration Example of frame configuration Example of frame configuration Example of frame configuration An example of mapping method An example of mapping method Example of configuration of weighted composite unit An example of how to rearrange symbols Example of configuration of transmitter / receiver in spatial multiplex MIMO transmission system BER characteristic example Example of phase change method Example of phase change method Example of phase change method Example of phase change method Example of phase change method Example of symbol arrangement of modulated signal that can obtain high reception quality Example of frame configuration of modulated signal that can obtain high reception quality Example of symbol arrangement of modulated signal that can obtain high reception quality Example of symbol arrangement of modulated signal that can obtain high reception quality Example of change in the number of symbols and the number of slots required for one coded block when a block code is used. Example of change in the number of symbols and the number of slots required for the two coded blocks when the block code is used. Overall configuration diagram of the digital broadcasting system Block diagram showing a configuration example of a receiver Diagram showing the structure of multiplexed data A diagram schematically showing how each stream is multiplexed in the multiplexed data. A detailed diagram showing how a video stream is stored in a PES packet string. The figure which shows the structure of TS packet and source packet in multiplexed data The figure which shows the data structure of PMT Diagram showing the internal structure of multiplexed data information Diagram showing the internal structure of stream attribute information Configuration diagram of video display and audio output device An example of a communication system configuration Example of symbol arrangement of modulated signal that can obtain high reception quality Example of symbol arrangement of modulated signal that can obtain high reception quality Example of symbol arrangement of modulated signal that can obtain high reception quality Example of symbol arrangement of modulated signal that can obtain high reception quality Example of transmitter configuration Example of transmitter configuration Example of transmitter configuration Example of transmitter configuration The figure which shows the baseband signal exchange part

Hereinafter, embodiments of the present invention will be described in detail with reference to the drawings.
(Embodiment 1)
The transmission method, transmission device, reception method, and reception device of the present embodiment will be described in detail.

Before giving this description, the outline of the transmission method and the decoding method in the spatial multiplex MIMO transmission system which is a conventional system will be described.
The configuration of the N _t xN _r spatial multiplex MIMO system is shown in FIG. The information vector z is encoded and interleaved. Then, as the interleaved output, the vector u = (u ₁ , ..., U _Nt ) of the encoded bits is obtained. However, u _i = (ui ₁ , ..., u _iM ) (M: number of transmission bits per symbol). When the transmission vector s = (s ₁ , ..., s _Nt ) ^T , the transmission signal s _i = map ( _ui ) is expressed from the transmission antenna #i, and when the transmission energy is normalized, E {| s _i | ² } = Es. It is expressed as / Nt ( _Es : total energy per channel). Then, if the reception vector is y = (y ₁ , ..., y _Nr ) ^T , it is expressed as in Eq. (1).

At this time, H _NtNr is a channel matrix, n = (n ₁ , ..., n _Nr ) ^T is a noise vector, ni is an average value of ⁰ , and _i . i. d. Complex Gaussian noise. From the relationship between the transmission symbol and the reception symbol introduced by the receiver, the probability regarding the reception vector can be given by a multidimensional Gaussian distribution as in Eq. (2).

Here, consider a receiver consisting of an outer soft-in / soft-out decoder and MIMO detection, which performs iterative decoding as shown in FIG. 1. The vector (L-value) of the log-likelihood ratio in FIG. 1 is expressed by the equations (3)-(5).

<Repeat detection method>
Here, iterative detection of MIMO signals in an N _t xN _r spatial multiplex MIMO system will be described.
The log-likelihood ratio of u _mn is defined as in Eq. (6).

From Bayes' theorem, Eq. (6) can be expressed as Eq. (7).

However, U _{mn, ± 1} = {u | u _mn = ± 1}. And _lnΣaj ~ max
When approximated by ln a _j , equation (7) can be approximated as equation (8). The symbol "~" above means an approximation.

P (u | u _mn ) and ln P (u | u _mn ) in the formula (8) are expressed as follows.

By the way, the logarithmic probability of the equation defined in the equation (2) is expressed as in the equation (12).

Therefore, from the equations (7) and (13), in MAP or APP (a posteriori probability), the posterior L-value is expressed as follows.

Hereinafter, it is referred to as repeated APP decoding. Further, from the equations (8) and (12), in the log-likelihood ratio (Max-Log APP) based on the Max-Log approximation, the subsequent L-value is expressed as follows.

Hereinafter, it is referred to as repeated Max-log APP decoding. The external information required by the iterative decoding system can be obtained by subtracting the pre-input from the equation (13) or (14).
<System model>
FIG. 23 shows the basic configuration of the system leading to the following description. Here, a 2 × 2 spatial multiplex MIMO system is used, each of the streams A and B has an outer encoder, and the two outer encoders have the same LDPC code encoder (here, an LDPC code encoder is used as the outer encoder). However, the error correction code used by the outer encoder is not limited to the LDPC code, and other error correction codes such as a turbo code, a convolutional code, and an LDPC convolutional code may be used in the same manner. Further, the outer encoder is configured to be provided for each transmitting antenna, but the present invention is not limited to this, and a plurality of transmitting antennas may be used, or one outer encoder may be provided, and transmission may be performed. It may have more outer encoders than the number of antennas). Each of the streams A and B has an interleaver (π _a , π _b ). Here, the modulation method is 2 ^h -QAM (h bits are transmitted with one symbol).
The receiver shall perform repeated detection (repeated APP (or Max-log APP) decoding) of the above-mentioned MIMO signal. Then, as the decoding of the LDPC code, for example, sum-product decoding shall be performed.
FIG. 2 shows the frame configuration and describes the order of the symbols after interleaving. At this time, ( _{ia, ja), (ib, j b ) shall be} expressed as shown in the following equation.

At this time, ia, _ib : the order of symbols after interleaving, ja _a , j _b : bit position in the modulation method _{(ja, j b = 1} , ..., H), π _a , π _b : stream. ^A , ^B interleaver, Ω _{aia, ja} , Ω _{bib, jb} : Indicates the order of data before interleaving of streams A and B. However, _FIG . 2 shows the frame configuration when _ia = ib.
<Repetitive decoding>
Here, the sum-product decoding and the iterative detection algorithm of the MIMO signal used for decoding the LDPC code in the receiver will be described in detail.

The sum-produce decoding binary MxN matrix H = {H _mn } is used as the inspection matrix of the LDPC code to be decoded. The subsets A (m) and B (n) of the set [1, N] = {1, 2, ..., N} are defined as follows.

At this time, A (m) means a set of column indexes that are 1 in the mth row of the check matrix H, and B (n) is a set of row indexes that are 1 in the nth row of the check matrix H. .. The algorithm for sum-produce decoding is as follows.
Step A ・ 1 (Initialization): The prior value logarithmic ratio β _mn = 0 is set for all sets (m, n) satisfying H _mn = 1. The loop variable (number of iterations) is set to l _sum = 1, and the maximum number of loops is set to l _{sum, max} .
Step A ・ 2 (row processing): External value logarithm using the following update formula for all sets (m, n) that satisfy H _mn = 1 in the order of m = 1, 2, ..., M. The ratio α _mn is updated.

At this time, f is a function of Gallager. Then, how to obtain λ _n will be described in detail below.
Step A ・ 3 (column processing): External value logarithm using the following update formula for all pairs (m, n) that satisfy H _mn = 1 in the order of n = 1, 2, ..., N. Update the ratio β _mn .

Step A ・ 4 (Calculation of log-likelihood ratio): For n ∈ [1, N], the log-likelihood ratio L _n is calculated as follows.

Step A ・ 5 (counting the number of iterations): If l _sum <l _{sum, max} , increment l _sum and return to step A ・ 2. When l _sum = l _{sum, max} , this sum-produce decoding is completed.

The above is the operation of one sum-product decoding. After that, repeated detection of the MIMO signal is performed. In the variables m, n, α _mn , β _mn , λ _n , and L _n used in the above description of the operation of sum-produce decoding, the variables in the stream A are ^ma , n _a , α _{a mana} , β ^a _mana , Variables in λ _na , L _na , and stream ^{B are represented by mb, n b, α b mb nb, β b} _{mb nb ,} ^λ _{nb ,} and L _nb .
<Repeated detection of MIMO signal>
Here, a method of obtaining λ _n in the iterative detection of a MIMO signal will be described in detail.

From equation (1), the following equation holds.

From the frame configuration of FIG. 2, the following relational expressions are established from the equations (16) and (17).

At this time, n _a , n _b ∈ [1, N]. Hereinafter, λ _na , L _na , λ _nb , and L _nb are expressed as λ _{k, na} , L _{k, na} , λ _{k, nb} , L _k, and nb, respectively, when the number of repetitions of the repeated detection of the MIMO signal is k. And.

Step B ・ 1 (Initial detection; k = 0): At the time of initial detection, λ _{0, na} , λ _{0, nb} are obtained as follows.
For iterative APP decoding:

For iterative Max-log APP decoding:

However, it is assumed that X = a and b. Then, the number of iterations of the repeated detection of the MIMO signal is set to l _mimo = 0, and the maximum number of iterations is set to l _{mimo, max} .
Step B ・ 2 (repeated detection; number of repetitions k): λ _{k, na} , λ _{k, nb} when the number of repetitions k is from equations (11) (13)-(15) (16) (17). It is expressed as 31)-(34). However, (X, Y) = (a, b) (b, a).
For iterative APP decoding:

For iterative Max-log APP decoding:

Step B ・ 3 (counting the number of iterations, estimating the codeword): If l _mimo <l _{mimo, max} , increment l _mimo and return to step B ・ 2. In the case of l _mimo = l _{mimo, max} , the estimated codeword is determined as follows.

However, it is assumed that X = a and b.
FIG. 3 is an example of the configuration of the transmission device 300 according to the present embodiment. The coding unit 302A receives information (data) 301A and a frame configuration signal 313 as inputs, and has a frame configuration signal 313 (error correction method used by the coding unit 302A for error correction coding of data, a coding rate, a block length, etc.). The information of the above is included, and the method specified by the frame configuration signal 313 is used. Further, the error correction method may be switched.) According to, for example, a convolution code, an LDPC code, a turbo code, etc. Error correction coding is performed, and the encoded data 303A is output.

The interleaver 304A receives the encoded data 303A and the frame configuration signal 313 as inputs, performs interleaving, that is, rearranging the order, and outputs the interleaved data 305A. (The interleaving method may be switched based on the frame configuration signal 313.)
The mapping unit 306A receives the interleaved data 305A and the frame configuration signal 313 as inputs, and performs QPSK (Quadrature Phase Shift Keying), 16QAM (16 Quadrature Amplitude Modulation), 64QAM (64 Quadrature Modulation), 64QAM (64 Quadrature) band modulation, etc. Output signal 307A. (The modulation method may be switched based on the frame configuration signal 313.)
FIG. 19 is an example of a mapping method in the IQ plane of the common mode component I and the orthogonal component Q constituting the baseband signal in QPSK modulation. For example, as shown in FIG. 19A, when the input data is "00", I = 1.0 and Q = 1.0 are output, and similarly, when the input data is "01", I =. -1.0, Q = 1.0 is output, ..., Is output. 19 (B) is an example of a mapping method in the IQ plane of QPSK modulation different from FIG. 19 (A), and the point that FIG. 19 (B) is different from FIG. 19 (A) is in FIG. 19 (A). The signal point shown in FIG. 19B can be obtained by rotating the signal point around the origin. The method of rotating such a constellation is shown in Non-Patent Document 9 and Non-Patent Document 10, and even if the Cyclic Q Delay shown in Non-Patent Document 9 and Non-Patent Document 10 is applied. good. As another example from FIG. 19, FIG. 20 shows the signal point arrangement in the IQ plane at 16QAM, and the example corresponding to FIG. 19 (A) is FIG. 20 (A), FIG. 19 (B). An example corresponding to is shown in FIG. 20 (B).

The coding unit 302B receives information (data) 301B and a frame constituent signal 313 as inputs, and includes information such as a frame constituent signal 313 (error correction method to be used, a coding rate, a block length, etc.), and the frame constituent signal 313. The method specified by is used. Further, the error correction method may be switched.) For example, error correction coding such as a convolution code, LDPC code, turbo code, etc. is performed, and the data after encoding is performed. Output 303B.

The interleaver 304B receives the encoded data 303B and the frame configuration signal 313 as inputs, performs interleaving, that is, rearranging the order, and outputs the interleaved data 305B. (The interleaving method may be switched based on the frame configuration signal 313.)
The mapping unit 306B receives the interleaved data 305B and the frame configuration signal 313 as inputs, and performs QPSK (Quadrature Phase Shift Keying), 16QAM (16 Quadrature Amplitude Modulation), 64QAM (64 Quadrature Modulation), 64QAM (64 Quadrature) band modulation, etc. Output signal 307B. (The modulation method may be switched based on the frame configuration signal 313.)
The signal processing method information generation unit 314 receives the frame configuration signal 313 as an input, and outputs information 315 regarding the signal processing method based on the frame configuration signal 313. The information 315 regarding the signal processing method includes information for specifying which precoding matrix is used in a fixed manner and information for a phase change pattern for changing the phase.

The weighted synthesis unit 308A receives the baseband signal 307A, the baseband signal 307B, and the information 315 regarding the signal processing method as inputs, and weight-synthesizes the baseband signal 307A and the baseband signal 307B based on the information 315 regarding the signal processing method. The signal 309A after weighted synthesis is output. The details of the weighting synthesis method will be described in detail later.

The radio unit 310A receives the signal 309A after weighted synthesis as an input, performs processing such as orthogonal modulation, band limitation, frequency conversion, and amplification, outputs a transmission signal 311A, and outputs a transmission signal 511A as a radio wave from the antenna 312A. To.

The weighted synthesis unit 308B receives the baseband signal 307A, the baseband signal 307B, and the information 315 regarding the signal processing method as inputs, and weight-synthesizes the baseband signal 307A and the baseband signal 307B based on the information 315 regarding the signal processing method. The signal 316B after weighting synthesis is output.

FIG. 21 shows the configuration of the weighted synthesis unit (308A, 308B). The area surrounded by the dotted line in FIG. 21 is the weighted composition unit. The baseband signal 307A is multiplied by w11 to generate w11 · s1 (t) and multiplied by w21 to generate w21 · s1 (t). Similarly, the baseband signal 307B is multiplied by w12 to generate w12 · s2 (t) and multiplied by w22 to generate w22 · s2 (t). Next, z1 (t) = w11 · s1 (t) + w12 · s2 (t) and z2 (t) = w21 · s1 (t) + w22 · s2 (t) are obtained. At this time, s1 (t) and s2 (t) are BPSK (Binary) as can be seen from the above description.
Phase Shift Keying), QPSK, 8PSK (8 Phase Shift Keying), 16QAM,
It is a baseband signal of a modulation method such as 32QAM (32 Quadrature Amplitude Modulation), 64QAM, 256QAM, 16APSK (16 Amplitude Phase Shift Keying).

Here, both weighting and synthesizing units shall execute weighting using a fixed precoding matrix, and as an example of the precoding matrix, an equation (37) or an equation (38) is used as an example. There is a method using (36). However, this is an example, and the value of α is not limited to the formula (37) and the formula (38), and another value, for example, α may be 1.

The precoding matrix is

However, in the above formula (36), α is

Is.
Alternatively, in the above formula (36), α is

Is.
The precoding matrix is not limited to the equation (36), and the one shown in the equation (39) may be used.

In this equation (39), it may be expressed by a = Ae ^jδ11 , b = Be ^jδ12 , c = Ce ^jδ21 , d = De ^jδ22 . Further, any one of a, b, c and d may be "zero". For example, (1) a is zero, b, c, d are not zero, (2) b is zero, a, c, d are not zero, (3) c is zero, a, b. , D may be non-zero, (4) d may be zero, and a, b, and c may be non-zero.

When any one of the modulation method, the error correction code, and the coding rate thereof is changed, the precoding matrix to be used may be set or changed, and the precoding matrix may be used fixedly.

The phase changing unit 312 receives the signal 312B after the weighted synthesis and the information 315 regarding the signal processing method as inputs, and periodically changes the phase of the signal 312B and outputs the signal 312B. To change regularly means to change the phase in a predetermined period (for example, every n symbols (n is an integer of 1 or more) or every predetermined time) according to a predetermined phase change pattern. .. The details of the phase change pattern will be described in the fourth embodiment below.

The radio unit 310B receives the phase-changed signal 309B as an input, performs processing such as orthogonal modulation, band limitation, frequency conversion, and amplification, outputs a transmission signal 311B, and the transmission signal 311B is output as a radio wave from the antenna 312B. To.

FIG. 4 shows a configuration example of the transmission device 400 different from that of FIG. In FIG. 4, a part different from FIG. 3 will be described.
The coding unit 402 receives information (data) 401 and a frame configuration signal 313 as inputs, performs error correction coding based on the frame configuration signal 313, and outputs the encoded data 402.

The distribution unit 404 takes the encoded data 403 as an input, distributes the data, and outputs the data 405A and the data 405B. Note that FIG. 4 describes the case where there is only one coding unit, but the present invention is not limited to this, and the coding unit is m (m is an integer of 1 or more), and the code created by each coding unit is used. The present invention can be similarly carried out in the case where the distribution unit outputs the conversion data separately into two systems of data.

FIG. 5 shows an example of a frame configuration on the time axis of the transmission device according to the present embodiment. The symbol 500_1 is a symbol for notifying the receiving device of the transmission method, and is, for example, an error correction method used for transmitting a data symbol, information on its coding rate, and a modulation method used for transmitting the data symbol. Information etc. is transmitted.

Symbol 501_1 is a symbol for estimating the channel variation of the modulated signal z1 (t) {where t is time} transmitted by the transmitting device. Symbol 502_1 is a data symbol transmitted by the modulation signal z1 (t) to the symbol number u (on the time axis), and symbol 503_1 is a data symbol transmitted by the modulation signal z1 (t) to the symbol number u + 1.

Symbol 501_2 is a symbol for estimating the channel variation of the modulated signal z2 (t) {where t is time} transmitted by the transmitting device. The symbol 502_2 is a data symbol transmitted by the modulation signal z2 (t) to the symbol number u, and the symbol 503_2 is a data symbol transmitted by the modulation signal z2 (t) to the symbol number u + 1.

At this time, in the symbol at z1 (t) and the symbol at z2 (t), the symbols at the same time (same time) are transmitted from the transmitting antenna using the same (common) frequency.

The relationship between the modulated signal z1 (t) and the modulated signal z2 (t) transmitted by the transmitting device and the received signals r1 (t) and r2 (t) in the receiving device will be described.
In FIG. 5, 504 # 1 and 504 # 2 indicate a transmitting antenna in the transmitting device, 505 # 1 and 505 # 2 indicate a receiving antenna in the receiving device, and the transmitting device transmits the modulated signal z1 (t) to the transmitting antenna 504. # 1, the modulation signal z2 (t) is transmitted from the transmission antenna 504 # 2. At this time, it is assumed that the modulated signal z1 (t) and the modulated signal z2 (t) occupy the same (common) frequency (band). The channel fluctuations of each transmitting antenna of the transmitting device and each antenna of the receiving device are set to h11 (t), h12 (t), h21 (t), and h22 (t), respectively, and the reception antenna 505 # 1 of the receiving device receives. Assuming that the signal is r1 (t) and the received signal received by the receiving antenna 505 # 2 of the receiving device is r2 (t), the following relational expression is established.

FIG. 6 is a diagram related to the weighting method (precoding method) and the phase changing method in the present embodiment, and the weighting synthesis unit 600 integrates both the weighting synthesis units 308A and 308B of FIG. It is a weighted composition unit. As shown in FIG. 6, the streams s1 (t) and streams s2 (t) correspond to the baseband signals 307A and 307B of FIG. 3, that is, the base according to the mapping of the modulation scheme such as QPSK, 16QAM, 64QAM. It becomes the common mode I component and the quadrature Q component of the band signal. Then, as in the frame configuration of FIG. 6, the stream s1 (t) represents the signal of the symbol number u as s1 (u), the signal of the symbol number u + 1 as s1 (u + 1), and so on. Similarly, the stream s2 (t) represents the signal with the symbol number u as s2 (u), the signal with the symbol number u + 1 as s2 (u + 1), and so on. Then, the weighting synthesis unit 600 inputs the baseband signals 307A (s1 (t)) and 307B (s2 (t)) in FIG. 3 and the information 315 regarding the signal processing method, and weights according to the information 315 regarding the signal processing method. , And outputs the signals 309A (z1 (t)) and 309B (z2 (t)) after the weighted synthesis of FIG.

At this time, z1 (t) can be expressed by the following equation (41), where W1 = (w11, w12) is the vector of the first row in the fixed precoding matrix F.

On the other hand, in z2 (t), assuming that the vector of the second row in the fixed precoding matrix F is W2 = (w21, w22) and the phase changing equation by the phase changing unit is y (t), the following equation (42) is used. ) Can be expressed.

Here, y (t) is an equation for changing the phase according to a predetermined method. For example, assuming that the period is 4, the phase changing equation at time u is represented by, for example, the equation (43). be able to.

Similarly, the phase change equation at time u + 1 can be expressed by, for example, equation (44).

That is, the phase change equation at time u + k can be expressed by equation (45).

The regular phase change examples shown in the equations (43) to (45) are only examples.
The period of regular phase change is not limited to 4. As the number of cycles increases, it may be possible to promote improvement in the reception performance (more accurately, error correction performance) of the receiving device (although it does not mean that the cycle should be large, 2). It is likely that you should avoid small values such as).

Further, in the phase change examples shown in the above equations (43) to (45), a configuration is shown in which the phase is sequentially rotated by a predetermined phase (in the above equation, by π / 2), but the same amount of phase is rotated. Instead, the phase may be changed randomly. For example, the phase of y (t) to be multiplied in the order shown in the equation (46) or the equation (47) may be changed according to a predetermined period. What is important in the regular change of phase is that the phase of the modulated signal is changed regularly, and the degree of the changed phase is as uniform as possible, for example, from -π radian to π radian. On the other hand, although it is desirable to have a uniform distribution, it may be random.

As described above, the weighted synthesis unit 600 of FIG. 6 executes precoding using a predetermined fixed precoding weight, and the phase changing unit regularly changes the phase of the input signal and the degree of the change. Change while changing to.

In the LOS environment, the reception quality may be greatly improved by using a special precoding matrix, but depending on the situation of the direct wave, the special precoding matrix depends on the phase and amplitude component of the direct wave when it is received. different. However, there is a certain rule in the LOS environment, and if the phase of the transmission signal is regularly changed according to this rule, the data reception quality is greatly improved. The present invention proposes a signal processing method for improving the LOS environment.

FIG. 7 shows an example of the configuration of the receiving device 700 according to the present embodiment. The radio unit 703_X receives the received signal 702_X received by the antenna 701_X as an input, performs processing such as frequency conversion and orthogonal demodulation, and outputs the baseband signal 704_X.

The channel variation estimation unit 705_1 in the modulation signal z1 transmitted by the transmission device takes the baseband signal 704_X as an input, extracts the reference symbol 501_1 for channel estimation in FIG. 5, and obtains a value corresponding to h11 in the equation (40). Estimate and output the channel estimation signal 706_1.

The channel variation estimation unit 705_2 in the modulation signal z2 transmitted by the transmission device takes the baseband signal 704_X as an input, extracts the reference symbol 501_2 for channel estimation in FIG. 5, and obtains a value corresponding to h12 in the equation (40). Estimate and output the channel estimation signal 706_2.

The radio unit 703_Y receives the received signal 702_Y received by the antenna 701_Y as an input, performs processing such as frequency conversion and orthogonal demodulation, and outputs the baseband signal 704_Y.
The channel variation estimation unit 707_1 in the modulation signal z1 transmitted by the transmission device takes the baseband signal 704_Y as an input, extracts the reference symbol 501_1 for channel estimation in FIG. 5, and obtains a value corresponding to h21 in the equation (40). Estimate and output the channel estimation signal 708_1.

The channel variation estimation unit 707_2 in the modulation signal z2 transmitted by the transmission device takes the baseband signal 704_Y as an input, extracts the reference symbol 501_2 for channel estimation in FIG. 5, and obtains a value corresponding to h22 in the equation (40). Estimate and output the channel estimation signal 708_2.

The control information decoding unit 709 inputs the baseband signals 704_X and 704_Y, detects the symbol 500_1 for notifying the transmission method of FIG. 5, and outputs the signal 710 regarding the information of the transmission method notified by the transmission device.

The signal processing unit 711 receives the baseband signals 704_X, 704_Y, the channel estimation signals 706_1, 706_2, 708_1, 708_2, and the signal 710 related to the transmission method information notified by the transmission device as inputs, performs detection and decoding, and receives data. Outputs 712_1 and 712_2.

Next, the operation of the signal processing unit 711 of FIG. 7 will be described in detail. FIG. 8 shows an example of the configuration of the signal processing unit 711 according to the present embodiment. FIG. 8 mainly includes an INNER MIMO detection unit, a soft-in / soft-out decoder, and a coefficient generation unit. The method of iterative decoding in this configuration is described in detail in Non-Patent Document 2 and Non-Patent Document 3, but the MIMO transmission method described in Non-Patent Document 2 and Non-Patent Document 3 is spatial multiplex MIMO transmission. Although it is a method, the transmission method in the present embodiment is a MIMO transmission method in which the phase of the signal is regularly changed with time and a precoding matrix is used, which is non-Patent Document 2 and Non-Patent Document 2. This is a difference from Patent Document 3. The (channel) matrix in equation (36) is H (t), the precoding weight matrix in FIG. 6 is F (where the precoding matrix is a fixed one that does not change in the received signal of 1), and FIG. The matrix of the phase change equation by the phase change unit is Y (t) (where Y (t) changes depending on t), the receive vector is R (t) = (r1 (t), r2 (t)) ^T , and the stream. When the vector S (t) = (s1 (t), s2 (t)) ^T , the following relational expression holds.

At this time, the receiving device can apply the decoding methods of Non-Patent Document 2 and Non-Patent Document 3 to the reception vector R (t) by obtaining H (t) × Y (t) × F. ..
Therefore, the coefficient generation unit 819 of FIG. 8 is a signal 818 regarding the information of the transmission method notified by the transmission device (the fixed precoding matrix used and the information for specifying the phase change pattern when the phase is changed). (Corresponding to 710 in FIG. 7) is used as an input, and a signal 820 related to information on the signal processing method is output.

The INNER MIMO detection unit 803 receives a signal 820 related to information on the signal processing method as an input, and uses this signal to perform repeated detection / decoding by using the relationship of the equation (48). Will be explained.

In the signal processing unit having the configuration shown in FIG. 8, it is necessary to perform the processing method as shown in FIG. 10 in order to perform iterative decoding (repeated detection). First, one codeword (or one frame) of the modulated signal (stream) s1 and one codeword (or one frame) of the modulated signal (stream) s2 are decoded. As a result, from the soft-in / soft-out decoder, one codeword (or one frame) of the modulated signal (stream) s1 and one codeword (or one frame) of the modulated signal (stream) s2 are each. The log-likelihood ratio of bits (LLR: Log-Likelihood Ratio) is obtained. Then, the detection / decoding is performed again using the LLR. This operation is performed multiple times (this operation is called iterative decoding (repeated detection)). Hereinafter, a method of creating a log-likelihood ratio (LLR) of a symbol at a specific time in one frame will be mainly described.

In FIG. 8, the storage unit 815 includes a baseband signal 801X (corresponding to the baseband signal 704_X in FIG. 7), a channel estimation signal group 802X (corresponding to the channel estimation signals 706_1 and 706_2 in FIG. 7), and a baseband. To realize iterative decoding (repeated detection) by inputting the signal 801Y (corresponding to the baseband signal 704_Y in FIG. 7) and the channel estimation signal group 802Y (corresponding to the channel estimation signals 708_1 and 708_2 in FIG. 7). In addition, H (t) × Y (t) × F in the equation (48) is executed (calculated), and the calculated matrix is stored as a modified channel signal group. Then, the storage unit 815 outputs the above signals as a baseband signal 816X, a modified channel estimation signal group 817X, a baseband signal 816Y, and a modified channel estimation signal group 817Y when necessary.

Subsequent operations will be described separately for the case of initial detection and the case of iterative decoding (repeated detection).
<In the case of initial detection>
The INNER MIMO detection unit 803 inputs the baseband signal 801X, the channel estimation signal group 802X, the baseband signal 801Y, and the channel estimation signal group 802Y. Here, the modulation method of the modulation signal (stream) s1 and the modulation signal (stream) s2 will be described as 16QAM.

First, the INNER MIMO detection unit 803 executes H (t) × Y (t) × F from the channel estimation signal group 802X and the channel estimation signal group 802Y, and obtains a candidate signal point corresponding to the baseband signal 801X. The situation at that time is shown in FIG. In FIG. 11, ● (black circle) is a candidate signal point in the IQ plane, and since the modulation method is 16QAM, there are 256 candidate signal points. (However, since FIG. 11 shows an image diagram, not all 256 candidate signal points are shown.) Here, the 4 bits transmitted by the modulated signal s1 are b0, b1, b2, b3, and the modulated signal s2. Assuming that the 4 bits transmitted in 1 are b4, b5, b6, and b7, there are candidate signal points corresponding to (b0, b1, b2, b3, b4, b5, b6, b7) in FIG. Then, the square Euclidean distance between the received signal point 1101 (corresponding to the baseband signal 801X) and each of the candidate signal points is obtained. Then, each square Euclidean distance is divided by the noise variance σ ² . Therefore, (b0, b1,
b2, b3, b4, b5, b6, _b7 ) The value obtained by dividing the Euclidean distance between the candidate signal point and the received signal point squared by the noise variance is EX (b0, b1, b2, b3, b4, b5, b5). b
6, b7) will be obtained. The baseband signal and the modulated signals s1 and s2 are complex signals.

Similarly, H (t) × F × Y (t) is executed from the channel estimation signal group 802X and the channel estimation signal group 802Y to find the candidate signal point corresponding to the baseband signal 801Y, and the reception signal point (baseband signal). The squared Euclidean distance with (corresponding to 801Y) is obtained, and this squared Euclidean distance is divided by the noise dispersion σ ² . Therefore, the value obtained by dividing the candidate signal point corresponding to (b0, b1, b2, b3, b4, b5, b6, b7) and the Euclidean distance squared to the received signal point by the noise variance is _EY (b0, b1, b2). , B3, b4, b5, b6, b7).

Then, EX (b0, b1, b2, b3, b4, b5, b6, b7) + _EY (b0, b1, b2, b3, b4, b5, b6, _b7 ) = E (b0, b1, b2, b3). , B4, b5, b6, b7).

The INNER MIMO detection unit 803 outputs E (b0, b1, b2, b3, b4, b5, b6, b7) as a signal 804.
The log-likelihood calculation unit 805A takes the signal 804 as an input, calculates the log-likelihood of the bits b0 and b1 and b2 and b3, and outputs the log-likelihood signal 806A. However, in the calculation of the log-likelihood, the log-likelihood when it is "1" and the log-likelihood when it is "0" are calculated. The calculation method is as shown in the formula (28), the formula (29), and the formula (30), and the details are shown in Non-Patent Document 2 and Non-Patent Document 3.

Similarly, the log-likelihood calculation unit 805B takes the signal 804 as an input, calculates the log-likelihood of the bits b4 and b5 and b6 and b7, and outputs the log-likelihood signal 806B.
The deinterleaver (807A) receives the log-likelihood signal 806A as an input, performs deinterleave corresponding to the interleaver (interleaver (304A) in FIG. 3), and outputs the log-likelihood signal 808A after deinterleave.

Similarly, the deinterleaver (807B) takes the log-likelihood signal 806B as an input, performs deinterleave corresponding to the interleaver (interleaver (304B) in FIG. 3), and outputs the log-likelihood signal 808B after deinterleave.

The log-likelihood ratio calculation unit 809A takes the deinterleaved log-likelihood signal 808A as an input, and calculates the log-likelihood ratio (LLR: Log-Likelihood Ratio) of the bits encoded by the encoder 302A of FIG. Then, the log-likelihood ratio signal 810A is output.

Similarly, the log-likelihood ratio calculation unit 809B takes the deinterleaved log-likelihood signal 808B as an input, and the log-likelihood ratio (LLR: Log-) of the bits encoded by the encoder 302B of FIG.
Likelihood Ratio) is calculated, and the log-likelihood ratio signal 810B is output.

The Soft-in / soft-out decoder 811A receives the log-likelihood ratio signal 810A as an input, performs decoding, and outputs the log-likelihood ratio 812A after decoding.
Similarly, the Soft-in / soft-out decoder 811B receives the log-likelihood ratio signal 810B as an input, performs decoding, and outputs the log-likelihood ratio 812B after decoding.

<In the case of iterative decoding (repeated detection), the number of iterations k>
The interleaver (813A) inputs the log-likelihood ratio 812A after decoding obtained by the k-1st soft-in / soft-out decoding, performs interleaving, and outputs the log-likelihood ratio 814A after interleaving. .. At this time, the interleave pattern of the interleave (813A) is the same as the interleave pattern of the interleaver (304A) of FIG.

The interleaver (813B) inputs the log-likelihood ratio 812B after decoding obtained by the k-1st soft-in / soft-out decoding, performs interleaving, and outputs the log-likelihood ratio 814B after interleaving. .. At this time, the interleave pattern of the interleave (813B) is the same as the interleave pattern of the interleaver (304B) of FIG.

The INNER MIMO detection unit 803 inputs the baseband signal 816X, the modified channel estimation signal group 817X, the baseband signal 816Y, the modified channel estimation signal group 817Y, the logarithmic likelihood ratio 814A after interleaving, and the logarithmic likelihood ratio 814B after interleaving. And. Here, instead of the baseband signal 801X, the channel estimation signal group 802X, the baseband signal 801Y, and the channel estimation signal group 802Y, the baseband signal 816X, the modified channel estimation signal group 817X, the baseband signal 816Y, and the modified channel estimation signal group 817Y. Is used because there is a delay time due to repeated decoding.

The difference between the operation during repeated decoding of the INNER MIMO detection unit 803 and the operation during initial detection is that the log-likelihood ratio 814A after interleaving and the log-likelihood ratio 814B after interleaving are used for signal processing. Is. First, the INNER MIMO detection unit 803 obtains E (b0, b1, b2, b3, b4, b5, b6, b7) as in the case of the initial detection. In addition, the coefficients corresponding to the equations (11) and (32) are obtained from the log-likelihood ratio 814A after interleaving and the log-likelihood ratio 814B after interleaving. Then, the value of E (b0, b1, b2, b3, b4, b5, b6, b7) is corrected by using this obtained coefficient, and the value is corrected to E'.
(B0, b1, b2, b3, b4, b5, b6, b7) and output as a signal 804.

The log-likelihood calculation unit 805A takes the signal 804 as an input, calculates the log-likelihood of the bits b0 and b1 and b2 and b3, and outputs the log-likelihood signal 806A. However, in the calculation of the log-likelihood, the log-likelihood when it is "1" and the log-likelihood when it is "0" are calculated. The calculation method is as shown in the formula (31), the formula (32), the formula (33), the formula (34), and the formula (35), and is shown in Non-Patent Document 2 and Non-Patent Document 3. ..

Similarly, the log-likelihood calculation unit 805B takes the signal 804 as an input, calculates the log-likelihood of the bits b4 and b5 and b6 and b7, and outputs the log-likelihood signal 806B. The operation after the demodulator is the same as the initial detection.

Note that FIG. 8 shows the configuration of the signal processing unit when performing repeated detection, but repeated detection is not necessarily an essential configuration for obtaining good reception quality, and is a configuration portion required only for repeated detection. , The configuration may not have interleavers 813A and 813B. At this time, the INNER MIMO detection unit 803 does not perform repetitive detection.

Then, an important part in the present embodiment is to perform an operation of H (t) × Y (t) × F. As shown in Non-Patent Document 5 and the like, initial detection and repeated detection may be performed using QR decomposition.
Further, as shown in Non-Patent Document 11, MMSE (Minimum Mean Square Error) and ZF (Zero Forcing) are linearly calculated based on H (t) × Y (t) × F, and initial detection is performed. You may go.

FIG. 9 has a signal processing unit configuration different from that of FIG. 8, and is a signal processing unit for the modulated signal transmitted by the transmission device of FIG. The difference from FIG. 8 is the number of soft-in / soft-out decoders, and the soft-in / soft-out decoder 901 receives the log-likelihood ratio signals 810A and 810B as inputs, performs decoding, and after decoding. The log-likelihood ratio 902 is output. The distribution unit 903 receives the log-likelihood ratio 902 after decoding as an input and distributes. For the other parts, the operation is the same as in FIG.

As described above, as in the present embodiment, when the transmitting device of the MIMO transmission system transmits a plurality of modulated signals from a plurality of antennas, the precoding matrix is multiplied and the phase is changed with time, and the phase is changed. By making the changes regularly, it is possible to obtain the effect that the reception quality of data in the receiving device is improved as compared with the case of using the conventional spatial multiplex MIMO transmission in the LOS environment where the direct wave is dominant.

In the present embodiment, in particular, regarding the configuration of the receiving device, the operation is described by limiting the number of antennas, but the same can be performed even if the number of antennas increases. That is, the number of antennas in the receiving device does not affect the operation and effect of the present embodiment.

Further, in the present embodiment, the LDPC code has been described as an example, but the present invention is not limited to this, and the decoding method is also limited to sum-produce decoding as a soft-in / soft-out decoder. There are other soft-in / soft-out decoding methods such as BCJR algorithm, SOVA algorithm, Msx-log-MAP algorithm and the like. Details are shown in Non-Patent Document 6.

Further, in the present embodiment, the single carrier method has been described as an example, but the present invention is not limited to this, and the same can be performed even when multi-carrier transmission is performed. Therefore, for example, a spectrum diffusion communication method, an OFDM (Orthogonal Frequency-Division Multiplexing) method, an SC-FDMA (Single Carrier Frequency Division Access), SC-OFDM (Single Circuit, etc. The same can be performed when the wavelet OFDM method or the like shown in is used. Further, in the present embodiment, symbols other than the data symbols, for example, pilot symbols (preambles, unique words, etc.), symbols for transmitting control information, and the like may be arranged in the frame.

Hereinafter, as an example of the multi-carrier method, an example when the OFDM method is used will be described.
FIG. 12 shows the configuration of the transmission device when the OFDM method is used. In FIG. 12, the same reference numerals are given to those operating in the same manner as in FIG.

The OFDM system-related processing unit 1201A receives the weighted signal 309A as an input, performs OFDM system-related processing, and outputs a transmission signal 1202A. Similarly, the OFDM method-related processing unit 1201B takes the weighted signal 309B as an input and outputs a transmission signal 1202B.

FIG. 13 shows an example of the configuration of the OFDM system related processing units 1201A and 1201B and later in FIG. 12, and the parts related to 1201A to 312A in FIG. 12 are 1301A to 1310A and the parts related to 1201B to 312B. Is 1301B to 1310B.

The serial-parallel conversion unit 1302A performs serial-parallel conversion of the weighted signal 1301A (corresponding to the weighted signal 309A in FIG. 12), and outputs a parallel signal 1303A.

The rearrangement unit 1304A receives the parallel signal 1303A as an input, performs rearrangement, and outputs the rearranged signal 1305A. The rearrangement will be described in detail later.
The inverse fast Fourier transform unit 1306A takes the rearranged signal 1305A as an input, performs an inverse fast Fourier transform, and outputs the signal 1307A after the inverse Fourier transform.

The radio unit 1308A receives the signal 1307A after the inverse Fourier transform as an input, performs processing such as frequency conversion and amplification, outputs the modulated signal 1309A, and the modulated signal 1309A is output as a radio wave from the antenna 1310A.

The serial-parallel conversion unit 1302B performs serial-parallel conversion on the weighted and phase-changed signal 1301B (corresponding to the phase-changed signal 309B in FIG. 12), and outputs the parallel signal 1303B.

The rearrangement unit 1304B receives the parallel signal 1303B as an input, performs rearrangement, and outputs the rearranged signal 1305B. The rearrangement will be described in detail later.
The inverse fast Fourier transform unit 1306B takes the rearranged signal 1305B as an input, performs an inverse fast Fourier transform, and outputs the signal 1307B after the inverse Fourier transform.

The radio unit 1308B receives the signal 1307B after the inverse Fourier transform as an input, performs processing such as frequency conversion and amplification, outputs the modulated signal 1309B, and the modulated signal 1309B is output as a radio wave from the antenna 1310B.

Since the transmission device of FIG. 3 is not a transmission method using a multi-carrier, the phase is changed so as to have four cycles as shown in FIG. 6, and the phase-changed symbols are arranged in the time axis direction. When a multi-carrier transmission method such as the OFDM method as shown in FIG. 12 is used, naturally, the symbols after precoding and changing the phase are arranged in the time axis direction as shown in FIG. 3, and each of them is arranged. A method of performing for each (sub) carrier can be considered, but in the case of the multi-carrier transmission method, a method of arranging in the frequency axis direction or using both the frequency axis and the time axis can be considered. Hereinafter, this point will be described.

FIG. 14 shows an example of a method of rearranging symbols in the rearrangement units 1301A and 1301B of FIG. 13 in terms of frequency on the horizontal axis and time on the vertical axis, and the frequency axis is from (sub) carrier 0 to (sub) carrier 9. The modulated signals z1 and z2 use the same frequency band at the same time (time), and FIG. 14 (A) shows a method of rearranging the symbols of the modulated signal z1 and FIG. 14 (B). Shows a method of rearranging the symbols of the modulated signal z2. The symbols of the weighted signal 1301A input by the serial-parallel conversion unit 1302A are numbered in order as # 0, # 1, # 2, # 3, .... Here, since the case of cycle 4 is considered, # 0, # 1, # 2, and # 3 are for one cycle. Considering the same, # 4n, # 4n + 1, # 4n + 2, and # 4n + 3 (n is an integer of 0 or more) are for one cycle.

At this time, as shown in FIG. 14A, symbols # 0, # 1, # 2, # 3, ... Are arranged in order from carrier 0, and symbols # 0 to # 9 are arranged at time $ 1. After that, symbols # 10 to # 19 are arranged regularly, such as at time $ 2. The modulated signals z1 and z2 are complex signals.

Similarly, the symbols of the weighted and phase-changed signal 1301B input by the serial-parallel converter 1302B are numbered in order as # 0, # 1, # 2, # 3, .... .. Here, since the case of period 4 is considered, # 0, # 1, # 2, and # 3 have different phase changes, and # 0, # 1, # 2, and # 3 are one. It is for the cycle. Considering the same, # 4n, # 4n + 1, # 4n + 2, and # 4n + 3 (n is an integer of 0 or more) have different phase changes, and # 4n, # 4n + 1, # 4n + 2, and # 4n + 3 are one. It is for the cycle.

At this time, as shown in FIG. 14B, symbols # 0, # 1, # 2, # 3, ... Are arranged in order from carrier 0, and symbols # 0 to # 9 are arranged at time $ 1. After that, symbols # 10 to # 19 are arranged regularly, such as at time $ 2.

The symbol group 1402 shown in FIG. 14B is a symbol for one cycle when the phase changing method shown in FIG. 6 is used, and symbol # 0 is a symbol when the phase at time u in FIG. 6 is used. Symbol # 1 is a symbol when the phase of time u + 1 in FIG. 6 is used, symbol # 2 is a symbol when the phase of time u + 2 in FIG. 6 is used, and symbol # 3 is a symbol in FIG. 6. It is a symbol when the phase of time u + 3 is used. Therefore, in symbol # x, when x mod 4 is 0 (remainder when x is divided by 4, so mod: modulo), symbol # x is a symbol when the phase of time u in FIG. 6 is used. Yes, x mod
When 4 is 1, symbol # x is a symbol when the phase of time u + 1 in FIG. 6 is used, and when x mod 4 is 2, symbol # x is a symbol when the phase of time u + 2 in FIG. 6 is used. It is a symbol, and when x mod 4 is 3, symbol # x is a symbol when the phase of time u + 3 in FIG. 6 is used.

In the present embodiment, the phase of the modulated signal z1 shown in FIG. 14A is not changed.
As described above, when a multi-carrier transmission method such as an OFDM method is used, the symbols can be arranged in the frequency axis direction, unlike the case of single-carrier transmission. The arrangement of the symbols is not limited to the arrangement as shown in FIG. Another example will be described with reference to FIGS. 15 and 16.

FIG. 15 shows an example of a symbol rearrangement method in the rearrangement units 1301A and 1301B of FIG. 13 in the horizontal axis frequency and the vertical axis time, which are different from those in FIG. 14, and FIG. 15A shows the modulation signal z1. 15 (B) shows a method of rearranging the symbols of the modulation signal z2. 15 (A) and 15 (B) are different from FIG. 14, in that the method of rearranging the symbols of the modulated signal z1 and the method of rearranging the symbols of the modulated signal z2 are different. In FIG. 15 (B), the symbol # 0 to # 5 are placed on carriers 4 to 9, symbols # 6 to # 9 are placed on carriers 0 to 3, and then symbols # 10 to # 19 are placed on each carrier according to the same rules. At this time, similarly to FIG. 14 (B), the symbol group 1502 shown in FIG. 15 (B) is a symbol for one cycle when the phase changing method shown in FIG. 6 is used.

FIG. 16 shows an example of a symbol rearrangement method in the rearrangement units 1301A and 1301B of FIG. 13 in the horizontal axis frequency and the vertical axis time, which are different from those in FIG. 14, and FIG. 16A shows the modulation signal z1. A method of rearranging the symbols, FIG. 16B shows a method of rearranging the symbols of the modulated signal z2. The difference between FIGS. 16A and 16B is that the symbols are arranged in order on the carrier in FIG. 14, whereas the symbols are not arranged in order on the carrier in FIG. It is a point. As a matter of course, in FIG. 16, as in FIG. 15, the method of rearranging the symbols of the modulated signal z1 and the method of rearranging the modulated signal z2 may be different.

FIG. 17 shows an example of a symbol rearrangement method in the rearrangement portions 1301A and 1301B of FIG. 13 in the horizontal axis frequency and the vertical axis time, which are different from those in FIGS. 14 to 16, and FIG. 17 (A) shows modulation. A method of rearranging the symbols of the signal z1 and FIG. 17B show a method of rearranging the symbols of the modulated signal z2. In FIGS. 14 to 16, the symbols are arranged in the frequency axis direction, but in FIG. 17, the symbols are arranged using both the frequency and the time axis.

In FIG. 6, an example of switching the phase change in 4 slots has been described, but here, a case of switching in 8 slots will be described as an example. The symbol group 1702 shown in FIG. 17 is a symbol for one cycle (hence, 8 symbols) when the phase change method is used, and symbol # 0 is a symbol when the phase at time u is used, and the symbol # 1 is a symbol when the phase of time u + 1 is used, symbol # 2 is a symbol when the phase of time u + 2 is used, and symbol # 3 is a symbol when the phase of time u + 3 is used. # 4 is a symbol when the phase of time u + 4 is used, symbol # 5 is a symbol when the phase of time u + 5 is used, and symbol # 6 is a symbol when the phase of time u + 6 is used. Symbol # 7 is a symbol when the phase of time u + 7 is used. Therefore, in symbol # x, when x mod 8 is 0, symbol # x is a symbol when the phase of time u is used, and when x mod 8 is 1, symbol # x uses the phase of time u + 1. When x mod 8 is 2, symbol # x is a symbol when the phase of time u + 2 is used, and when x mod 8 is 3, symbol # x uses the phase of time u + 3. When x mod 8 is 4, symbol # x is a symbol when the phase of time u + 4 is used, and when x mod 8 is 5, symbol # x uses the phase of time u + 5. When x mod 8 is 6, symbol # x is a symbol when the phase of time u + 6 is used, and when x mod 8 is 7, symbol # x uses the phase of time u + 7. It is a symbol when I was there. In the arrangement of the symbols in FIG. 17, symbols for one cycle are arranged using a total of 4 × 2 = 8 slots, 4 slots in the time axis direction and 2 slots in the frequency axis direction. At this time, one cycle is arranged. The number of minute symbols is m × n symbols (that is, there are m × n types of phases to be multiplied). The frequency axis direction slot (number of carriers) used to arrange symbols for one cycle is n, and the time axis. Assuming that the slot used in the direction is m, it is preferable that m> n. This is because the phase of the direct wave, the fluctuation in the time axis direction is gradual as compared with the fluctuation in the frequency axis direction. Therefore, since the regular phase change of the present embodiment is performed in order to reduce the influence of the steady direct wave, it is desired to reduce the fluctuation of the direct wave in the period of performing the phase change. Therefore, it is preferable to set m> n. In consideration of the above points, it is better to rearrange the symbols using both the frequency axis and the time axis as shown in FIG. 17 rather than rearranging the symbols only in the frequency axis direction or only in the time axis direction. Is likely to be stationary, and the effect of the present invention can be easily obtained. However, when arranging in the direction of the frequency axis, the fluctuation of the frequency axis is steep, so there is a possibility that diversity gain can be obtained. It is not always the method.

FIG. 18 shows an example of a symbol rearrangement method in the rearrangement units 1301A and 1301B of FIG. 13 in the horizontal axis frequency and the vertical axis time, which are different from those in FIG. 17, and FIG. 18A shows the modulation signal z1. 18 (B) shows a method of rearranging the symbols of the modulation signal z2. In FIG. 18, the symbols are arranged using both the frequency and the time axis as in FIG. 17, but the difference from FIG. 17 is that in FIG. 17, the frequency direction is prioritized and then the time axis direction. Whereas the symbols are arranged, in FIG. 18, the time axis direction is prioritized, and then the symbols are arranged in the time axis direction. In FIG. 18, the symbol group 1802 is a symbol for one cycle when the phase changing method is used.

In addition, in FIGS. 17 and 18, similarly to FIG. 15, even if the arrangement method of the symbol of the modulation signal z1 and the symbol arrangement method of the modulation signal z2 are arranged differently, the same can be carried out, and the cost is high. The effect of being able to obtain reception quality can be obtained. Further, in FIGS. 17 and 18, even if the symbols are not arranged in order as in FIG. 16, the same can be performed, and the effect that high reception quality can be obtained can be obtained. can.

FIG. 22 shows an example of a symbol rearrangement method in the rearrangement units 1301A and 130B of FIG. 13 in the horizontal axis frequency and the vertical axis time, which are different from the above. Consider a case where the phase is regularly changed by using 4 slots such as the times u to u + 3 in FIG. The characteristic point in FIG. 22 is that the symbols are arranged in order in the frequency axis direction, but when the symbols are advanced in the time axis direction, the symbols are cyclically shifted by n (n = 1 in the example of FIG. 22). Is. In the four symbols shown in the symbol group 2210 in the frequency axis direction in FIG. 22, the phase of the time u to u + 3 in FIG. 6 shall be changed.

At this time, the # 0 symbol uses the phase change at time u, the # 1 uses the phase change at time u + 1, the # 2 uses the phase change at time u + 2, and the phase at time u + 3 is used. The phase change that has been performed shall be performed.

Similarly, for the symbol group 2220 in the frequency axis direction, the phase change using the phase of time u is used for the symbol of # 4, the phase change using the phase of time u + 1 is used for # 5, and the phase of time u + 2 is used for # 6. It is assumed that the phase is changed, and in # 7, the phase is changed using the phase at time u + 3.

The phase was changed as described above for the symbol of time $ 1, but the phase was changed as follows for the symbol groups 2201, 2202, 2203, and 2204 because of the cyclic shift in the time axis direction. Will be done.

In the symbol group 2201 in the time axis direction, the phase change using the phase of time u in the symbol # 0, the phase change using the phase of time u + 1 in # 9, and the phase change using the phase of time u + 2 in # 18. In # 27, it is assumed that the phase is changed using the phase at time u + 3.

In the symbol group 2202 in the time axis direction, the phase of the symbol of # 28 is changed using the phase of time u, the phase is changed by using the phase of time u + 1 in # 1, and the phase is changed by using the phase of time u + 2 in # 10. In # 19, it is assumed that the phase is changed using the phase at time u + 3.

In the symbol group 2203 in the time axis direction, the phase of the symbol of # 20 is changed using the phase of time u, the phase is changed by using the phase of time u + 1 in # 29, and the phase is changed by using the phase of time u + 2 in # 21. In # 11, it is assumed that the phase is changed using the phase at time u + 3.

In the symbol group 2204 in the time axis direction, the phase of the symbol of # 12 is changed by using the phase of time u, the phase of # 21 is changed by using the phase of time u + 1, and the phase of # 30 is changed by using the phase of time u + 2. In # 3, it is assumed that the phase is changed using the phase at time u + 3.

The feature in FIG. 22 is that, for example, when focusing on the symbol of # 11, the symbols (# 10 and # 12) on both sides in the frequency axis direction at the same time both change the phase using a phase different from that of # 11. At the same time, the symbols (# 2 and # 20) on both sides of the same carrier of the symbol of # 11 in the time axis direction change the phase using a phase different from that of # 11. And this is not limited to the symbol of # 11, and all the symbols having symbols on both sides in the frequency axis direction and the time axis direction have the same characteristics as the symbol of # 11. As a result, the phase is effectively changed, and it is less likely to be affected by the steady state of the direct wave, so that the data reception quality is likely to be improved.

In FIG. 22, the description is made with n = 1, but the present invention is not limited to this, and the same can be performed with n = 3. Further, in FIG. 22, the above characteristics are realized by arranging the symbols on the frequency axis and cyclically shifting the order of the arrangement of the symbols when the time advances in the axial direction, but the symbols are random. There is also a method of realizing the above-mentioned characteristics by arranging them (which may be regular).

(Embodiment 2)
In the first embodiment, the phase of the weighted and synthesized signal z (t) (precoded by a fixed precoding matrix) is changed. Here, various embodiments of the phase changing method that can obtain the same effect as that of the first embodiment will be disclosed.

In the above embodiment, as shown in FIGS. 3 and 6, the phase changing unit 317B is configured to execute the phase change only for one output from the weighting combining unit 600.
However, the timing for executing the phase change may be executed before the precoding by the weighting / combining unit 600, and the transmitting device replaces the configuration shown in FIG. 6 with the configuration shown in FIG. 6, as shown in FIG. 25. The phase changing unit 317B may be provided in front of the weighting / combining unit 600.

In this case, the phase change unit 317B executes a regular phase change for the baseband signal s2 (t) according to the mapping of the selected modulation method, and s2'(t) = s2 (t).
) Y (t) (where y (t) is changed by t) is output, and the weighting synthesizer 600 executes precoding on s2'(t) to z2 (t) (=). W2s2'(t)) (see equation (42)) may be output and transmitted.

Further, the phase change may be performed for both the modulated signals s1 (t) and s2 (t), and the transmitting device may change the phase as shown in FIG. 26 instead of the configuration shown in FIG. , A phase changing unit may be provided for both outputs of the weighting / combining unit 600.

The phase changing unit 317A regularly changes the phase of the input signal in the same manner as the phase changing unit 317B, and changes the phase of the precoded signal z1'(t) from the weighted synthesis unit. The phase-changed signal z1 (t) is output to the transmitter.

However, the phase changing unit 317A and the phase changing unit 317B change the phase as shown in FIG. 26 at the same timing to change the phase of each other. (However, the following is an example, and the method of changing the phase is not limited to this.) At time u, the phase changing unit 317A of FIG. 26 has z1 (t) = y ₁ (t) z1'. (T), and the phase changing unit 317B changes the phase so that z2 (t) = y ₂ (t) z2'(t). For example, as shown in FIG. 26, at time u, y ₁ (u) = e ^j0 , y ₂ (u).
= E ^-j π ^{/ 2} , at time u + 1, y ₁ (u + 1) = e ^j π ^{/ 4} , y ₂ (u + 1) = e ^-j3 π ^{/ 4} , ..., At time u + k, y ₁ (u + k) The phase is changed as = e ^jk π ^{/ 4} , y ₂ (u + k) = e ^{j (-k} π ^{/ 4-} π ^{/ 2)} . The period for regularly changing the phase may be the same or different between the phase changing unit 317A and the phase changing unit 317B.

Further, as described above, the timing for changing the phase may be before the execution of precoding by the weighting synthesis unit, and the transmission device may have the configuration shown in FIG. 27 instead of the configuration shown in FIG. 26.

When the phases of both modulated signals are changed regularly, it is assumed that each transmitted signal includes information on each phase change pattern as, for example, control information, and the receiving device obtains this control information. Then, the transmitting device can know the phase changing method, that is, the phase changing pattern, which is regularly switched, and thereby, the correct demodulation (detection) can be executed.

Next, a modified example of the configuration of FIGS. 6 and 25 will be described with reference to FIGS. 28 and 29. The difference between FIG. 28 and FIG. 6 is that the information 2800 regarding the phase change ON / OFF exists, and the phase change is performed to either z1'(t) or z2'(t) (at the same time). , Or, at the same frequency, the phase is changed to either z1'(t) or z2'(t).) Therefore, since the phase change is performed to either z1'(t) or z2'(t), the phase change unit 317A and the phase change unit 317B in FIG. 28 perform the phase change (ON). In some cases, the phase is not changed (OFF). The control information related to this ON / OFF becomes the information 2800 related to the phase change ON / OFF. The information 2800 regarding the phase change ON / OFF is output from the signal processing method information generation unit 314 shown in FIG.

The phase changing unit 317A of FIG. 28 has z1 (t) = y ₁ (t) z1'(t), and the phase changing unit 317B has z2 (t) = y ₂ (t) z2'(. The phase is changed so as to be t).

At this time, for example, z1'(t) is assumed to change the phase in the period 4. (At this time, z2'(t) does not change the phase.) Therefore, at time u, y ₁ (u) = e ^j0 , y ₂ (u) = 1, and at time u + 1, y ₁ (u + 1) = e ^j π ^{/ 2} , y ₂ (u + 1) = 1, at time u + 2, y ₁ (u + 2) = e ^j π, y ₂ (u + 2) = 1, at time u + 3, y ₁ (u + 3) = e ^j3 π ^{/ 2} , y ₂ (u + 3) = 1.

Next, for example, z2'(t) is assumed to change the phase in the period 4. (At this time, z
1'(t) does not change the phase. Therefore, at time u + 4, y ₁ (u + 4) = 1, y ₂ (u + 4) = e ^j0 , and at time u + 5, y ₁ (u + 5) = 1, y ₂ (u + 5) =
e ^j π ^{/ 2} , at time u + 6, y ₁ (u + 6) = 1, y ₂ (u + 6) = e ^j π, at time u + 7, y ₁ (u + 7) = 1, y ₂ (u + 7) = e ^j3 π ^/ It shall be ² .

Therefore, in the above example,
When the time is 8k, y ₁ (8k) = e ^j0 , y ₂ (8k) = 1,
When the time is 8k + 1, y ₁ (8k + 1) = e ^{jπ / 2} , y ₂ (8k + 1) = 1,
When the time is 8k + 2, y ₁ (8k + 2) = e ^jπ , y ₂ (8k + 2) = 1,
When the time is 8k + 3, y ₁ (8k + 3) = e ^{j3π / 2} , y ₂ (8k + 3) = 1,
When the time is 8k + 4, y ₁ (8k + 4) = 1, y ₂ (8k + 4) = e ^j0 ,
When the time is 8k + 5, y ₁ (8k + 5) = 1, y ₂ (8k + 5) = e ^{jπ / 2} ,
When the time is 8k + 6, y ₁ (8k + 6) = 1, y ₂ (8k + 6) = e ^jπ ,
When the time is 8k + 7, y ₁ (8k + 7) = 1, y ₂ (8k + 7) = e ^{j3π / 2}
Will be.

As described above, there is a time for changing the phase only for z1'(t) and a time for changing the phase only for z2'(t). Further, the phase change cycle is composed of the time for changing the phase only for z1'(t) and the time for changing the phase only for z2'(t). In the above description, the period when the phase is changed only for z1'(t) and the period when the phase is changed only for z2'(t) are the same, but the period is not limited to this, and z1'(. The period when the phase is changed only at t) and the period when the phase is changed only at z2'(t) may be different. Further, in the above example, it is described that the phase of z1'(t) is changed in 4 cycles and then the phase of z2'(t) is changed in 4 cycles, but the present invention is not limited to this. , The order of the phase change of z1'(t) and the phase change of z2'(t) may be arbitrary (for example, the phase change of z1'(t) and the phase change of z2'(t) are alternately performed. It may go, it may be in the order according to a certain rule, or the order may be random.)
The phase changing unit 317A of FIG. 29 has s1'(t) = y ₁ (t) s1 (t), and the phase changing unit 317B has s2'(t) = y ₂ (t) s2 (. The phase is changed so as to be t).

At this time, for example, s1 (t) is assumed to change the phase in the period 4. (At this time, s2 (t) does not change the phase.) Therefore, at time u, y ₁ (u) = e ^j0 ,
y ₂ (u) = 1, at time u + 1, y ₁ (u + 1) = e ^j π ^{/ 2} , y ₂ (u + 1) = 1, at time u + 2, y ₁ (u + 2) = e ^j π, y ₂ (u + 2) ) = 1, at time u + 3,
It is assumed that y ₁ (u + 3) = e ^j3 π ^{/ 2} and y ₂ (u + 3) = 1.

Next, for example, in s2 (t), it is assumed that the phase is changed in the period 4. (At this time, s1 (t) does not change the phase.) Therefore, at time u + 4, y ₁ (u + 4) = 1.
, Y ₂ (u + 4) = e ^j0 , at time u + 5, y ₁ (u + 5) = 1, y ₂ (u + 5) = e ^j π ^{/ 2} , at time u + 6, y ₁ (u + 6) = 1, y ₂ (u + 6) ) = E ^j π, at time u + 7, y ₁ (u + 7) = 1, y ₂ (u + 7) = e ^j3 π ^{/ 2} .

Therefore, in the above example,
When the time is 8k, y ₁ (8k) = e ^j0 , y ₂ (8k) = 1,
When the time is 8k + 1, y ₁ (8k + 1) = e ^{jπ / 2} , y ₂ (8k + 1) = 1,
When the time is 8k + 2, y ₁ (8k + 2) = e ^jπ , y ₂ (8k + 2) = 1,
When the time is 8k + 3, y ₁ (8k + 3) = e ^{j3π / 2} , y ₂ (8k + 3) = 1,
When the time is 8k + 4, y ₁ (8k + 4) = 1, y ₂ (8k + 4) = e ^j0 ,
When the time is 8k + 5, y ₁ (8k + 5) = 1, y ₂ (8k + 5) = e ^{jπ / 2} ,
When the time is 8k + 6, y ₁ (8k + 6) = 1, y ₂ (8k + 6) = e ^jπ ,
When the time is 8k + 7, y ₁ (8k + 7) = 1, y ₂ (8k + 7) = e ^{j3π / 2}
Will be.

As described above, there is a time for changing the phase only for s1 (t) and a time for changing the phase only for s2 (t). Further, the phase change cycle is composed of the time for changing the phase only for s1 (t) and the time for changing the phase only for s2 (t). In the above description, the period when only s1 (t) is changed in phase and the period when only s2 (t) is changed in phase are the same, but the period is not limited to this, and only s1 (t) is used. The period when the phase change is performed and the period when the phase change is performed only for s2 (t) may be different. Further, in the above example, it is described that the phase of s1 (t) is changed in 4 cycles and then the phase of s2 (t) is changed in 4 cycles, but the present invention is not limited to this. The order of the phase change of (t) and the phase change of s2 (t) may be arbitrary (for example, the phase change of s1 (t) and the phase change of s2 (t) may be alternately performed. The order may be according to a certain rule, or the order may be random.
)
As a result, it is possible to equalize the reception states when the transmission signals z1 (t) and z2 (t) are received on the receiving device side, and the received signals z1 (t) and z2 (t) are respectively. By periodically switching the phase in the symbol, the error correction capability after error correction and decoding can be improved, so that the reception quality in the LOS environment can be improved.

As described above, even with the configuration shown in the second embodiment, the same effect as that of the first embodiment can be obtained.
In the present embodiment, the case where the single carrier method is used as an example, that is, the case where the phase change is performed with respect to the time axis has been described, but the present invention is not limited to this, and the same may be performed even when multi-carrier transmission is performed. Can be done. Therefore, for example, a spectrum diffusion communication method, an OFDM (Orthogonal Frequency-Division Multiplexing) method, an SC-FDMA (Single Carrier Frequency Division Access), SC-OFDM (Single Circuit, etc. The same can be performed when the wavelet OFDM method or the like shown in is used. As described above, in the present embodiment, the case of performing the phase change in the time t-axis direction has been described as an explanation for performing the phase change, but the phase change is performed in the frequency axis direction as in the first embodiment. That is, in the present embodiment, in the description of the phase change in the t direction, t is replaced with f (f: frequency ((sub) carrier)), and the phase change method described in the present embodiment is considered. Can be applied to phase change in the frequency direction. Further, the phase change method of the present embodiment can be applied to the phase change in the time-frequency direction as in the description of the first embodiment.

Therefore, although the case of performing the phase change in the time axis direction is shown in FIGS. 6, 25, 26, and 27, in FIGS. 6, 25, 26, and 27, the time t is replaced with the carrier f. By thinking, it is equivalent to changing the phase in the frequency direction, and by substituting time t for time t and frequency f, that is, (t) for (t, f), phase change in the time frequency block. Is equivalent to doing.

Then, in the present embodiment, symbols other than the data symbols, for example, pilot symbols (preambles, unique words, etc.), symbols for transmitting control information, and the like may be arranged in the frame.

(Embodiment 3)
In the first and second embodiments, the phase is changed regularly. In the third embodiment, in the receiving devices scattered in various places when viewed from the transmitting device, the receiving devices can obtain good data reception quality regardless of where the receiving devices are arranged. The method will be disclosed.

In the third embodiment, the symbol arrangement of the signal obtained by changing the phase will be described.
FIG. 31 shows an example of a frame configuration of some symbols of a signal on the time-frequency axis when a multi-carrier method such as an OFDM method is used in a transmission method in which the phase is regularly changed.

First, of the two precoded baseband signals described in the first embodiment, a case where one of the baseband signals (see FIG. 6) is phase-changed will be described.
(Note that FIG. 6 shows a case where the phase is changed in the time axis direction, but in FIG. 6, it corresponds to performing the phase change in the frequency direction by replacing the time t with the carrier f. By substituting time t for time t and frequency f, that is, (t) for (t, f), it is equivalent to performing a phase change in a block of time frequency.)
FIG. 31 shows the frame configuration of the modulation signal z2'which is the input of the phase changing unit 317B shown in FIG. 12, and one square is a symbol (however, since precoding is performed, both s1 and s2 are used. It usually contains the signal of, but depending on the configuration of the precoding matrix, it may be only one signal of s1 and s2).

Here, attention is paid to the symbol 3100 of carrier 2 and time $ 2 in FIG. Although it is described as a carrier here, it may also be referred to as a subcarrier. In carrier 2, the symbol 3103 closest to time $ 2, that is, the symbol 3103 at time $ 1 of carrier 2 and the symbol 3101 at time $ 3 are in the respective channel states of carrier 2 and symbol 3100 at time $ 2. Very high correlation with channel state.

Similarly, at time $ 2, the channel state of the frequency symbol closest to carrier 2 in the frequency axis direction, that is, the symbol 3104 of carrier 1 and time $ 2 and the symbol 3104 of time $ 2 and carrier 3 is Both have a very high correlation with the channel state of the symbol 3100 of carrier 2 and time $ 2.

As described above, each channel state of the symbols 3101, 3102, 3103, and 3104 has a very high correlation with the channel state of the symbol 3100.
In the present specification, in the transmission method for regularly changing the phase, it is assumed that N kinds of phases (where N is an integer of 2 or more) are prepared as the phases to be multiplied. The symbol shown in FIG. 31 is, for example, attached with the description "e ^j0 ", which changes the phase by multiplying the signal z2'in FIG. 6 in this symbol by "e ^j0 ". It means that it was done. That is, the values described in each symbol of FIG. 31 are in y (t) in the formula (42) and in z2 (t) = y ₂ (t) z2'(t) described in the second embodiment. It is a value of y ₂ (t).

In the present embodiment, high data reception quality is obtained on the receiving device side by utilizing the high correlation between the channel states of the symbols adjacent to each other in the frequency axis direction and / or the symbols adjacent to each other in the time axis direction. Discloses the symbol arrangement of the phase-changed symbols obtained.

<Condition # 1> and <Condition # 2> can be considered as conditions for obtaining high data reception quality on the receiving side.
<Condition # 1>
As shown in FIG. 6, when a multi-carrier transmission method such as OFDM is used in a transmission method for regularly changing the phase of the precoded baseband signal z2', the time X and the carrier Y are data. Symbols for transmission (hereinafter referred to as data symbols), and adjacent symbols in the time axis direction, that is, time X-1 · carrier Y and time X + 1 · carrier Y are all data symbols, and these three The precoded baseband signal z2'corresponding to the data symbol, that is, the precoded baseband signal z2'at time X · carrier Y, time X-1 · carrier Y and time X + 1 · carrier Y, respectively. Both have different phase changes.

<Condition # 2>
As shown in FIG. 6, when a multi-carrier transmission method such as OFDM is used in a transmission method for regularly changing the phase of the precoded baseband signal z2'.
The time X carrier Y is a symbol for data transmission (hereinafter referred to as a data symbol), and the adjacent symbols in the frequency axis direction, that is, the time X carrier Y-1 and the time X carrier Y + 1 are both data. If it is a symbol, the precoded baseband signal z2'corresponding to these three data symbols, that is, after each precoding in time X · carrier Y, time X · carrier Y-1 and time X · carrier Y + 1. In the base band signal z2'of, different phase changes are performed in each case.

Then, it is preferable that there is a data symbol that satisfies <condition # 1>. Similarly, it is preferable that there is a data symbol that satisfies <Condition 2>.
The reason why this <condition # 1> and <condition # 2> is derived is as follows.

As described above, the channel state of each symbol having a certain symbol (hereinafter referred to as symbol A) in the transmission signal and temporally adjacent to the symbol A has a high correlation with the channel state of the symbol A.

Therefore, if different phases are used for three symbols that are adjacent in time, the symbol A has poor reception quality (although the reception quality is high as SNR, the phase relationship of the direct wave is poor) in the LOS environment. Even if the reception quality is poor due to the poor situation), it is very likely that good reception quality can be obtained with the two symbols adjacent to the remaining symbol A, and as a result, after error correction and decoding. Can obtain good reception quality.

Similarly, there is a certain symbol (hereinafter referred to as symbol A) in the transmission signal, and the channel state of each symbol frequency-adjacent to this symbol A has a high correlation with the channel state of symbol A as described above. ..

Therefore, if different phases are used for three symbols that are adjacent in frequency, the symbol A has poor reception quality (although the reception quality is high as SNR, the phase relationship of the direct wave is poor) in the LOS environment. Even if the reception quality is poor due to the poor situation), it is very likely that good reception quality can be obtained with the two symbols adjacent to the remaining symbol A, and as a result, after error correction and decoding. Can obtain good reception quality.

Further, by combining <Condition # 1> and <Condition # 2>, there is a possibility that the reception quality of data can be further improved in the receiving device. Therefore, the following <condition # 3> can be derived.

<Condition # 3>
As shown in FIG. 6, when a multi-carrier transmission method such as OFDM is used in a transmission method for regularly changing the phase of the precoded baseband signal z2', the time X and the carrier Y are data. It is a symbol for transmission (hereinafter referred to as a data symbol), and symbols adjacent in the time axis direction, that is, time X-1 · carrier Y and time X + 1 · carrier Y are both data symbols and frequencies. When the adjacent symbols in the axial direction, that is, the time X carrier Y-1 and the time X carrier Y + 1 are both data symbols, the precoded baseband signal z2'corresponding to these five data symbols, that is, , Time X · Carrier Y and Time X-1 · Carrier Y and Time X + 1 · Carrier Y and Time X · Carrier Y-1 and Time X · Carrier Y + 1 with their respective precoded baseband signals z2'. Different phase changes are made.

Here, a supplement is given regarding "different phase changes". The phase change will be defined from 0 radians to 2π radians. For example, in the time X and the carrier Y, the phase change applied to the baseband signal z2'after the precoding in FIG. 6 is performed at e ^{jθX, Y} and the time X-1.
-In the carrier Y, the phase change applied to the baseband signal z2'after the precoding of FIG. 6 is e ^{jθX-1, Y} , time X + 1.-In the carrier Y, the baseband signal z2' after the precoding of FIG. If the phase change applied to is e ^{jθX + 1, Y} , then 0 radian ≤ θ _{X, Y} <2π, 0 radian ≤ θ _{X-1, Y} <2π, 0 radian ≤ θ _{X + 1, Y} <2π. Therefore, under <condition # 1>, θ _{X, Y} ≠ θ _{X-1, Y} and θ _{X, Y} ≠ θ _{X + 1, Y} and θ _{X +.
1, Y} ≠ θ _{X-1, Y} is established. Similarly, in <condition # 2>, θ _{X, Y} ≠ θ _{X, Y-1} and θ _{X, Y} ≠ θ _{X, Y + 1} and θ _{X, Y-1} ≠ θ _{X-1, Y + 1} . So, <
In condition # 3>, θ _{X, Y} ≠ θ _{X-1, Y} and θ _{X, Y} ≠ θ _{X + 1, Y} and θ _{X, Y} ≠ θ _{X, Y-1} and θ _{X, Y} ≠ θ _{X, Y + 1} and θ _{X-1, Y} ≠ θ _{X + 1, Y} and θ _{X-1, Y} ≠ θ _{X, Y-1} and θ _{X-1, Y} ≠ θ _{X, Y + 1} and θ _{X + 1, Y} ≠ θ _{X, Y-1} θ _{X + 1, Y} ≠ θ _{X, Y + 1} and θ _{X, Y-1} ≠ θ _{X, Y + 1} .

Then, it is preferable that there is a data symbol that satisfies <condition # 3>.
FIG. 31 is an example of <condition # 3>, in which the phase multiplied by the precoded baseband signal z2'of FIG. 6 corresponding to the symbol 3100 corresponding to the symbol A and the symbol 3100 are temporally. Symbols that are frequency-adjacent to the phase multiplied by the precoded baseband signal z2'in FIG. 6 corresponding to the adjacent symbol 3101 and the precoded baseband signal z2' in FIG. 6 corresponding to 3103. The phases multiplied by the precoded baseband signal z2'in FIG. 6 corresponding to 3102 and the precoded baseband signal z2' in FIG. 6 corresponding to 3104 are arranged so as to be different from each other. Therefore, even if the reception quality of the symbol 3100 is poor on the receiving side, the reception quality of the adjacent symbol is very high, so that high reception quality after error correction and decoding can be ensured.

FIG. 32 shows an example of arranging symbols obtained by changing the phase under this condition.
As can be seen from FIG. 32, in any data symbol, the degree of phase change for the symbols whose phases are adjacent to each other in both the frequency axis direction and the time axis direction is different from each other. ing. By doing so, the error correction capability of the receiving device can be further improved.

That is, in FIG. 32, when the data symbols exist in the adjacent symbols in the time axis direction, <condition # 1> is satisfied for all X and all Y.
Similarly, in FIG. 32, when data symbols exist in adjacent symbols in the frequency direction, <condition # 2> is satisfied for all X and all Y.

Similarly, in FIG. 32, when the data symbol exists in the adjacent symbol in the frequency direction and the data symbol exists in the adjacent symbol in the time axis direction, <condition # 3> is all X, all. It is established by Y of.

Next, a case where the phase of the two precoded baseband signals described in the second embodiment is changed (see FIG. 26) will be described.
As shown in FIG. 26, when giving a phase change to both the precoded baseband signal z1'and the precoded baseband signal z2', there are several methods for changing the phase. This point will be explained in detail.

As a method 1, the phase of the baseband signal z2'after precoding is changed as shown in FIG. 32 as described above. In FIG. 32, the phase change of the baseband signal z2'after precoding has a period of 10. However, as described above, in order to satisfy <Condition # 1>, <Condition # 2>, and <Condition # 3>, the (sub) carrier 1 applies the precoded baseband signal z2'to the baseband signal z2'. The phase change is changing over time. (Although such a change is made in FIG. 32, a period of 10 may be used and another phase change method may be used.) Then, the phase change of the baseband signal z1'after precoding is as shown in FIG. 33. In addition, in the phase change of the baseband signal z2'after precoding, the phase change value for one cycle of the cycle 10 is constant. In FIG. 33, at time $ 1 including one cycle (of the phase change of the baseband signal z2'after precoding), the value of the phase change of the baseband signal z1'after precoding is e ^j0 . At time $ 2 including one cycle (of the phase change of the baseband signal z2'after precoding), the value of the phase change of the baseband signal z1'after precoding is e ^{jπ / 9} . ..., and.

The symbol shown in FIG. 33 has, for example, the description "e ^j0 ", which is the phase obtained by multiplying the signal z1'in FIG. 26 in this symbol by "e ^j0 ". Means that has changed. That is, the value described in each symbol of FIG. 33 is the value of y ₁ (t) in z1 (t) = y ₁ (t) z1'(t) described in the second embodiment.

As shown in FIG. 33, the phase change of the baseband signal z1'after precoding is performed by changing the phase of the baseband signal z2' after precoding by setting the phase change value for one cycle of the cycle 10 to be constant. The value should be changed together with the number for one cycle. (As described above, in FIG. 33, e ^j0 is set for the first cycle, and e ^{jπ / 9} , ... Is set for the second cycle.)
By doing so, the phase change of the baseband signal z2'after precoding has a period of 10, but the phase change of the baseband signal z1'after precoding and the baseband signal z2' after precoding It is possible to obtain the effect that the period when both of the phase changes are taken into consideration can be made larger than 10. This may improve the reception quality of the data of the receiving device.

As the method 2, the phase of the baseband signal z2'after precoding is changed as shown in FIG. 32 as described above. In FIG. 32, the phase change of the baseband signal z2'after precoding has a period of 10. However, as described above, in order to satisfy <Condition # 1>, <Condition # 2>, and <Condition # 3>, the (sub) carrier 1 applies the precoded baseband signal z2'to the baseband signal z2'. The phase change is changing over time. (Although such a change is made in FIG. 32, a period of 10 may be used and another phase change method may be used.) Then, the phase change of the baseband signal z1'after precoding is shown in FIG. As shown, the phase change of the baseband signal z2'after precoding performs the phase change in the period 3 different from the period 10.

The symbol shown in FIG. 30 is, for example, attached with the description "e ^j0 ", which is the phase obtained by multiplying the signal z1'in FIG. 26 in this symbol by "e ^j0 ". Means that has changed. That is, the value described in each symbol of FIG. 30 is the value of y ₁ (t) in z1 (t) = y ₁ (t) z1'(t) described in the second embodiment.

By doing so, the phase change of the baseband signal z2'after precoding has a period of 10, but the phase change of the baseband signal z1'after precoding and the baseband signal z2' after precoding The period when both phase changes are taken into consideration is 30, and the period when both the phase change of the baseband signal z1'after precoding and the phase change of the baseband signal z2' after precoding are taken into consideration is larger than 10. You can get the effect that you can. This may improve the reception quality of the data of the receiving device. As one effective method of the method 2, the phase change period of the baseband signal z1'after precoding is set to N, and the baseband signal z2 after precoding is set to N.
When the phase change period of'is M, especially when N and M are in an elementary relationship with each other, the phase change of the baseband signal z1'after precoding and the phase of the baseband signal z2' after precoding. There is an advantage that the period when both changes are taken into consideration can be easily set to a large period of N × M, but it is possible to increase the period even if N and M are in a prime relationship with each other.

The phase changing method of the third embodiment is an example and is not limited to this, and as described in the first and second embodiments, the phase may be changed in the frequency axis direction or the time may be changed. Even if the phase is changed in the axial direction or the phase is changed in the time-frequency block, the reception quality of the data in the receiving device can be improved in the same manner.

In addition to the frame configuration described above, it is conceivable that a pilot symbol (SP (Scattered Pilot)) or a symbol for transmitting control information may be inserted between the data symbols. The phase change in this case will be described in detail.

FIG. 47 shows the frame configuration of the modulated signal (baseband signal after precoding) z1 or z1'and the modulated signal (baseband signal after precoding) z2' on the time-frequency axis, and is shown in FIG. 47 (a). ) Is the time of the modulated signal (baseband signal after precoding) z1 or z1'-frame configuration on the frequency axis, and FIG. 47 (b) is the time of the modulated signal (baseband signal after precoding) z2'-. It is a frame configuration on the frequency axis. In FIG. 47, 4701 indicates a pilot symbol, 4702 indicates a data symbol, and the data symbol 4702 is a symbol that has undergone precoding or precoding and phase change.

FIG. 47 shows the symbol arrangement when the phase is changed for the baseband signal z2'after precoding as shown in FIG. 6 (the phase is not changed for the baseband signal z1 after precoding). ). (Note that FIG. 6 shows a case where the phase is changed in the time axis direction, but in FIG. 6, it corresponds to performing the phase change in the frequency direction by replacing the time t with the carrier f. By substituting time t for time t and frequency f, that is, (t) for (t, f), it is equivalent to performing a phase change in a block of time frequency.) Therefore, after precoding in FIG. 47. The numerical value described in the symbol of the baseband signal z2'indicates the phase change value. The symbol of the baseband signal z1'(z1) after precoding in FIG. 47 does not change the phase, so no numerical value is described.

The important point in FIG. 47 is that the phase change for the baseband signal z2'after precoding is applied to the data symbol, that is, the precoded symbol. (Here, although it is described as a symbol, since the symbol described here is precoded, it includes both the symbol of s1 and the symbol of s2.) Therefore. , The phase of the pilot symbol inserted in z2'is not changed.

FIG. 48 shows the frame configuration on the time-frequency axis of the modulated signal (baseband signal after precoding) z1 or z1'and the modulated signal (baseband signal after precoding) z2', FIG. 48 (a). ) Is the time of the modulated signal (baseband signal after precoding) z1 or z1'-frame configuration on the frequency axis, and FIG. 48 (b) is the time of the modulated signal (baseband signal after precoding) z2'-. It is a frame configuration on the frequency axis. In FIG. 48, 4701 indicates a pilot symbol, 4702 indicates a data symbol, and the data symbol 4702 is a symbol subjected to precoding and phase change.

FIG. 48 shows the symbol arrangement when the phase is changed with respect to the precoded baseband signal z1'and the precoded baseband signal z2', as shown in FIG. 26. (Note that FIG. 26 shows a case where the phase is changed in the time axis direction, but in FIG. 26, by substituting the time t with the carrier f, it corresponds to performing the phase change in the frequency direction. By substituting time t for time t and frequency f, that is, (t) for (t, f), it is equivalent to performing a phase change in a block of time frequency.) Therefore, after precoding in FIG. 48. The numerical values described in the symbols of the baseband signal z1'and the precoded baseband signal z2' indicate the phase change value.

The important point in FIG. 48 is that the phase change for the precoded baseband signal z1'is applied to the data symbol, that is, the precoded symbol, and the precoded baseband signal z2. The phase change for'is the point applied to the data symbol, that is, the precoded symbol. (Here, although it is described as a symbol, since the symbol described here is precoded, it includes both the symbol of s1 and the symbol of s2.) Therefore. , The phase change is not applied to the pilot symbol inserted in z1', and the phase change is not applied to the pilot symbol inserted in z2'.

FIG. 49 shows the frame configuration of the modulated signal (baseband signal after precoding) z1 or z1'and the modulated signal (baseband signal after precoding) z2' on the time-frequency axis, and is shown in FIG. 49 (a). ) Is the time of the modulated signal (baseband signal after precoding) z1 or z1'-frame configuration on the frequency axis, and FIG. 49 (b) is the time of the modulated signal (baseband signal after precoding) z2'-. It is a frame configuration on the frequency axis. In FIG. 49, 4701 is a pilot symbol, 4702 is a data symbol, 4901 is a null symbol, the in-phase component I = 0 of the baseband signal, and the orthogonal component Q = 0. At this time, the data symbol 4702 becomes a precoding or a symbol that has undergone phase change with precoding. The difference between FIGS. 49 and 47 is the method of constructing a symbol other than the data symbol, and the modulation signal z2'is a null symbol at the time and carrier in which the pilot symbol is inserted in the modulation signal z1', and vice versa. In addition, at the time and carrier in which the pilot symbol is inserted in the modulation signal z2', the modulation signal z1'is a null symbol.

FIG. 49 shows the symbol arrangement when the phase is changed for the baseband signal z2'after precoding as shown in FIG. 6 (the phase is not changed for the baseband signal z1 after precoding). ). (Note that FIG. 6 shows a case where the phase is changed in the time axis direction, but in FIG. 6, it corresponds to performing the phase change in the frequency direction by replacing the time t with the carrier f. By substituting time t for time t and frequency f, that is, (t) for (t, f), it is equivalent to performing a phase change in a block of time frequency.) Therefore, after precoding in FIG. 49. The numerical value described in the symbol of the baseband signal z2'indicates the phase change value. Since the phase of the symbol of the baseband signal z1'(z1) after precoding in FIG. 49 is not changed, the numerical value is not described.

The important point in FIG. 49 is that the phase change for the baseband signal z2'after precoding is applied to the data symbol, that is, the precoded symbol. (Here, although it is described as a symbol, since the symbol described here is precoded, it includes both the symbol of s1 and the symbol of s2.) Therefore. , The phase of the pilot symbol inserted in z2'is not changed.

FIG. 50 shows the frame configuration of the modulated signal (baseband signal after precoding) z1 or z1'and the modulated signal (baseband signal after precoding) z2' on the time-frequency axis, and is shown in FIG. 50 (a). ) Is the time of the modulated signal (baseband signal after precoding) z1 or z1'-frame configuration on the frequency axis, and FIG. 50 (b) is the time of the modulated signal (baseband signal after precoding) z2'-. It is a frame configuration on the frequency axis. In FIG. 50, 4701 is a pilot symbol, 4702 is a data symbol, 4901 is a null symbol, the in-phase component I = 0 of the baseband signal, and the orthogonal component Q = 0. At this time, the data symbol 4702 becomes a precoding or a symbol that has undergone phase change with precoding. The difference between FIGS. 50 and 48 is the method of constructing a symbol other than the data symbol, and the modulation signal z2'is a null symbol at the time and carrier in which the pilot symbol is inserted in the modulation signal z1', and vice versa. In addition, at the time and carrier in which the pilot symbol is inserted in the modulation signal z2', the modulation signal z1'is a null symbol.

FIG. 50 shows the symbol arrangement when the phase is changed with respect to the precoded baseband signal z1'and the precoded baseband signal z2', as shown in FIG. 26. (Note that FIG. 26 shows a case where the phase is changed in the time axis direction, but in FIG. 26, by substituting the time t with the carrier f, it corresponds to performing the phase change in the frequency direction. By substituting time t for time t and frequency f, that is, (t) for (t, f), it is equivalent to performing a phase change in a block of time frequency.) Therefore, after precoding in FIG. 50. The numerical values described in the symbols of the baseband signal z1'and the precoded baseband signal z2' indicate the phase change value.

The important point in FIG. 50 is that the phase change for the precoded baseband signal z1'is applied to the data symbol, that is, the precoded symbol, and the precoded baseband signal z2. The phase change for'is the point applied to the data symbol, that is, the precoded symbol. (Here, although it is described as a symbol, since the symbol described here is precoded, it includes both the symbol of s1 and the symbol of s2.) Therefore. , The phase change is not applied to the pilot symbol inserted in z1', and the phase change is not applied to the pilot symbol inserted in z2'.

FIG. 51 shows an example of the configuration of a transmission device that generates and transmits a modulated signal having the frame configuration of FIGS. 47 and 49, and the same reference numerals are given to those that operate in the same manner as in FIG. ..
In FIG. 51, the weighting synthesis units 308A and 308B and the phase change unit 317B are
It operates only when the frame configuration signal 313 indicates the timing which is a data symbol.

When the pilot symbol (which also serves as null symbol generation) generation unit 5101 of FIG. 51 indicates that the frame configuration signal 313 is a pilot symbol (and a null symbol), the baseband signal 5102A of the pilot symbol and Output 5102B.

Although not shown in the frame configurations of FIGS. 47 to 50, a method of transmitting a modulated signal from one antenna, for example, without precoding (and no phase rotation), (in this case, the other antenna). When the control information symbol is transmitted using a transmission method using a spatiotemporal code (particularly a spatiotemporal block code), the control information symbol 5104 is a control information 5103, a frame. When the configuration signal 313 is used as an input and the frame configuration signal 313 indicates that it is a control information symbol, the base band signals 5102A and 5102B of the control information symbol are output.

The radio units 310 and 310B of FIG. 51 select a desired baseband signal from the plurality of baseband signals based on the frame configuration signal 313 among the plurality of input baseband signals. Then, the OFDM-related signal processing is performed, and the modulated signals 311A and 311B according to the frame configuration are output, respectively.

FIG. 52 shows an example of the configuration of a transmission device that generates and transmits a modulated signal having the frame configuration of FIGS. 48 and 50, and the same reference numerals are given to those that operate in the same manner as those of FIGS. 4 and 51. is doing. The phase changing unit 317A added to FIG. 51 operates only when the frame configuration signal 313 indicates the timing of the data symbol. Other than that, the operation is the same as that in FIG. 51.

FIG. 53 is a method of configuring a transmission device different from that of FIG. 51. The differences will be described below. As shown in FIG. 53, the phase modulation unit 317B receives a plurality of baseband signals as inputs. When the frame configuration signal 313 indicates that it is a data symbol, the phase modulation unit 317B performs a phase change on the precoded baseband signal 316B. When the frame configuration signal 313 indicates that it is a pilot symbol (or null symbol) or a control information symbol, the phase modulation unit 317B stops the phase change operation and the baseband signal of each symbol. Is output as it is. (As an interpretation, it can be considered that the phase rotation corresponding to "e ^j0 " is forcibly performed.)
The selection unit 5301 takes a plurality of baseband signals as inputs, selects and outputs the baseband signals of the symbols indicated by the frame configuration signals 313.

FIG. 54 is a method of configuring a transmission device different from that of FIG. 52. The differences will be described below. As shown in FIG. 54, the phase modulation unit 317B receives a plurality of baseband signals as inputs. When the frame configuration signal 313 indicates that it is a data symbol, the phase modulation unit 317B performs a phase change on the precoded baseband signal 316B. When the frame configuration signal 313 indicates that it is a pilot symbol (or null symbol) or a control information symbol, the phase modulation unit 317B stops the phase change operation and the baseband signal of each symbol. Is output as it is. (As an interpretation, it can be considered that the phase rotation corresponding to "e ^j0 " is forcibly performed.)
Similarly, the phase modulation unit 5201 receives a plurality of baseband signals as inputs, as shown in FIG. 54. Then, when the frame constituent signal 313 indicates that it is a data symbol, the phase modulation unit 5201 performs a phase change on the precoded baseband signal 309A. When the frame configuration signal 313 indicates that it is a pilot symbol (or null symbol) or a control information symbol, the phase modulation unit 5201 stops the phase change operation and the baseband signal of each symbol. Is output as it is. (As an interpretation, it can be considered that the phase rotation corresponding to "e ^j0 " is forcibly performed.)
In the above description, pilot symbols, control symbols, and data symbols have been described as examples, but the present invention is not limited to this, and transmission methods different from precoding, such as one-antenna transmission and transmission using a spatiotemporal block code, are used. Similarly, if the symbol is transmitted using a method, etc., it is important not to give a phase change. On the contrary, for a symbol that has been precoded, the phase change should be performed. Is important in the present invention.

Therefore, it is a feature of the present invention that the phase change is not performed on all the symbols in the frame configuration on the time-frequency axis, and the phase change is given only to the precoded signal.

(Embodiment 4)
In the first and second embodiments, it is disclosed that the phase is changed regularly, and in the third embodiment, the degree of the phase change of the adjacent symbols is changed.

In the fourth embodiment, it is shown that the phase changing method may be different depending on the modulation method used by the transmission device and the coding rate of the error correction code.
Table 1 below shows an example of a phase changing method set according to various setting parameters set by the transmitting device.

In Table 1, # 1 is the modulation signal s1 of the first embodiment (baseband signal s1 of the modulation method set by the transmission device), and # 2 is the modulation signal s2 (baseband signal s2 of the modulation method set by the transmission device). Means. The sequence of coding rates in Table 1 shows the coding rates set by the error correction codes for the modulation methods of # 1 and # 2. As described in the first to third embodiments, the sequence of the phase change patterns in Table 1 is a phase change method applied to the precoded baseband signals z1 (z1') and z2 (z2'). The phase change pattern is defined as A, B, C, D, E, ..., But this is actually information indicating the degree of change in the degree of phase change. For example, it is assumed that a change pattern as shown in the above equation (46) or equation (47) is shown. In the example of the phase change pattern in Table 1, "-" is described, which means that the phase change is not performed.

The combination of the modulation method and the coding rate shown in Table 1 is an example, and the modulation method other than the modulation method shown in Table 1 (for example, 128QAM, 256QAM, etc.) and the coding rate (for example, 7/8) are examples. Etc.) may be included. Further, as shown in the first embodiment, the error correction code may be set separately for s1 and s2 (in the case of Table 1, as shown in FIG. 4, one error correction code is encoded. It is assumed that the above is applied.). Further, a plurality of different phase change patterns may be associated with the same modulation method and coding rate. The transmitting device transmits information indicating each phase change pattern to the receiving device, and the receiving device identifies the phase change pattern by referring to the information and Table 1, and performs demodulation and decoding. Become. When the phase change pattern is uniquely determined for the modulation method and the error correction method, the transmitting device transmits the information of the modulation method and the error correction method to the receiving device, and the receiving device receives the information. In this case, the information on the phase change pattern is not always necessary because the phase change pattern can be known by obtaining the information.

In the first to third embodiments, the case where the phase is changed with respect to the baseband signal after precoding has been described, but not only the phase but also the amplitude is regularly changed with a period like the phase change. It is also possible. Therefore, Table 1 may also correspond to an amplitude change pattern that regularly changes the amplitude of the modulated signal. In this case, the transmission device may be provided with an amplitude changing unit that changes the amplitude after the weighted composition unit 308A of FIGS. 3 and 4, and an amplitude changing unit that changes the amplitude after the weighted composition unit 308B. It should be noted that the amplitude of one of the precoded baseband signals z1 (t) and z2 (t) may be changed (in this case, the amplitude changing unit is placed after either the weighting synthesis unit 308A or 308B. It may be provided.) However, the amplitude may be changed for both.

Further, although not shown in Table 1 above, the mapping method may be changed regularly by the mapping unit instead of changing the phase regularly.
That is, the mapping method of the modulation signal s1 (t) is 16QAM, the mapping method of the modulation signal s2 (t) is 16QAM, and for example, the mapping method of applying the modulation signal s2 (t) to the modulation signal s2 (t) is regularly 16QAM. → 16APSK (16 Amplitude Phase Shift Keying)
→ The first mapping method that has a different signal point arrangement from 16QAM and 16APSK on the IQ plane → The second mapping method that has a different signal point arrangement from 16QAM and 16APSK on the IQ plane → ... Then, as in the case of regularly changing the phase as described above, the effect of improving the data reception quality can be obtained in the receiving device.

Further, the present invention may be a combination of any of a method of regularly changing the phase, a method of regularly changing the mapping method, and a method of changing the amplitude, and all of them are taken into consideration. It may be configured to transmit a transmission signal.

In this embodiment, it can be carried out in either the single carrier method or the multi-carrier transmission. Therefore, for example, a spectrum diffusion communication method, an OFDM (Orthogonal Frequency-Division Multiplexing) method, an SC-FDMA (Single Carrier Frequency Division Access), SC-OFDM (Single Circuit, etc. It can also be carried out when the wavelet OFDM method or the like shown in is used. As described above, in the present embodiment, as an explanation for performing the phase change, the amplitude change, and the mapping change, the case where the phase change, the amplitude change, and the mapping change are performed in the time t-axis direction has been described. Similarly, as in the case of performing the phase change in the frequency axis direction, that is, in the present embodiment, in the description of the phase change, the amplitude change, and the mapping change in the t direction, t is set to f (f: frequency ((sub). ) Carrier)), the phase change, the amplitude change, and the mapping change described in the present embodiment can be applied to the phase change, the amplitude change, and the mapping change in the frequency direction. Further, the phase change, amplitude change, and mapping change method of the present embodiment can be applied to the phase change, amplitude change, and mapping change in the time-frequency direction as in the description of the first embodiment. Is.

Then, in the present embodiment, symbols other than the data symbols, for example, pilot symbols (preambles, unique words, etc.), symbols for transmitting control information, and the like may be arranged in the frame.

(Embodiment A1)
In this embodiment, as shown in Non-Patent Documents 12 to 15, a QC (Quasi Cyclic) LDPC (Low-Density Prity-Check) code (not a QC-LDPC code, but an LDPC code). (May be good), LDPC code and BCH code (Bose-Chaudhuri-Hocquenghem code) concatenated code, turbo code using tail biting or block code such as Duo-Binary Turbo Code is used to change the phase regularly. I will explain in detail how to do it. Here, as an example, a case where two streams of s1 and s2 are transmitted will be described as an example. However, when the control information or the like is not required when encoding is performed using the block code, the number of bits constituting the coded block is the number of bits constituting the block code (however, among these, the following It may contain control information and the like as described.) When control information (for example, CRC (cyclic redundancy check), transmission parameter, etc.) is required when encoding is performed using a block code, the number of bits constituting the coded block is the block code. It may be the sum of the number of constituent bits and the number of bits such as control information.

FIG. 34 is a diagram showing changes in the number of symbols and the number of slots required for one coded block when a block code is used. FIG. 34 shows, for example, as shown in the transmitter of FIG. 4, a “block code” in the case where two streams s1 and s2 are transmitted and the transmitter has one encoder. It is a figure which showed the change of the number of symbols and the number of slots required for one coded block when used. " (At this time, as the transmission method, either single carrier transmission or multi-carrier transmission such as OFDM may be used.)
As shown in FIG. 34, it is assumed that the number of bits constituting one coded block in the block code is 6000 bits. In order to transmit these 6000 bits, 3000 symbols are required when the modulation method is QPSK, 1500 symbols are required when the modulation method is 16QAM, and 1000 symbols are required when the modulation method is 64QAM.

Since the transmitting device of FIG. 4 transmits two streams at the same time, when the modulation method is QPSK, the above-mentioned 3000 symbols are assigned 1500 symbols to s1 and 1500 symbols to s2. A 1500 slot (named "slot" here) is required to transmit the 1500 symbols transmitted in s1 and the 1500 symbols transmitted in s2.

Similarly, when the modulation scheme is 16QAM, 750 slots are required to transmit all the bits that make up one coded block, and when the modulation scheme is 64QAM, all the bits that make up one block. 500 slots are required to transmit the bits.

Next, in the method of changing the phase regularly, the relationship between the slot defined above and the phase to be multiplied will be described.
Here, the number of phase change values (or phase change sets) prepared for the method of regularly changing the phase is set to 5. That is, it is assumed that five phase change values (or phase change sets) are prepared for the phase change unit of the transmitter of FIG. 4 (which is the "period" in the first to fourth embodiments). (As shown in FIG. 6, when the phase change is performed only on the baseband signal z2'after precoding, five phase change values may be prepared in order to perform the phase change in the period 5. Further, FIG. 26. Baseband signal z1'after precoding, as in
When phase change is performed for both and z2', two phase change values are required for one slot. These two phase change values are called a phase change set. Therefore, in this case, in order to change the phase of the period 5, five phase change sets may be prepared). These five phase change values (or phase change sets) are represented as PHASE [0], PHASE [1], PHASE [2], PHASE [3], PHASE [4].

When the modulation method is QPSK, in the 1500 slots described above for transmitting 6000 bits constituting one coded block, 300 slots use phase PHASE [0] and phase PHASE [0]. There are 300 slots using 1], 300 slots using phase PHASE [2], 300 slots using phase PHASE [3], and 300 slots using phase PHASE [4]. There is a need. This is because if there is a deviation in the phase used, the influence of the phase using a large number is large, and the receiving quality of the data depends on this influence in the receiving device.

Similarly, when the modulation method is 16QAM, in the 750 slots described above for transmitting 6000 bits constituting one coded block, the slot using the phase PHASE [0] is 150 slots. There are 150 slots that use phase PHASE [1], 150 slots that use phase PHASE [2], 150 slots that use phase PHASE [3], and 150 slots that use phase PHASE [4]. Must be a slot.

Similarly, when the modulation method is 64QAM, in the 500 slots described above for transmitting 6000 bits constituting one coded block, 100 slots use the phase PHASE [0]. 100 slots use phase PHASE [1], 100 slots use phase PHASE [2], 100 slots use phase PHASE [3], 100 slots use phase PHASE [4] Must be a slot.

As described above, in the method of regularly changing the phase, N pieces of phase change values (or phase change sets) are prepared (N different phases are PHASE [0], PHASE [1], PHASE [2]. ], ..., PHASE [N-2], PHASE [N-1]), when transmitting all the bits that make up one coded block, the phase PHASE [ The number of slots using 0] is K ₀ , the number of slots using phase PHASE [1] is K _{1, and} the number of slots using phase PHASE [i] is K _i (i = 0,1,2, ... , N-1), when the number of slots using phase PHASE [N-1] is K _N-1

<Condition # A01>
K ₀ = K ₁ = ... = K _i = ... = K _N-1 , that is, K _a = K _b , (for ∀a, ∀b, but a, b = 0,1,2,・ ・ ・, N-1, a ≠ b)

It should be.

When the communication system supports a plurality of modulation methods and is used by selecting from the supported modulation methods, it is preferable that <condition # A01> is satisfied in the supported modulation methods. ..

However, when a plurality of modulation methods are supported, the number of bits that can be transmitted by one symbol is generally different for each modulation method (in some cases, they may be the same). In some cases, there may be a modulation method that cannot satisfy <Condition # A01>. In this case, the following conditions may be satisfied instead of <Condition # A01>.

<Condition # A02>
The difference between K _a and K _b is 0 or 1, that is, | K _a -K _b | is 0 or 1.
(For ∀a, ∀b, but a, b = 0,1,2, ..., N-1, a ≠ b)

FIG. 35 is a diagram showing changes in the number of symbols and the number of slots required for the two coded blocks when the block code is used. FIG. 35 shows the case where two streams of s1 and s2 are transmitted and the transmitting device has two encoders, as shown in the transmitting device of FIG. 3 and the transmitting device of FIG. "A diagram showing changes in the number of symbols and the number of slots required for one coded block when a block code is used". (At this time, as the transmission method, either single carrier transmission or multi-carrier transmission such as OFDM may be used.)
As shown in FIG. 35, it is assumed that the number of bits constituting one coded block in the block code is 6000 bits. In order to transmit these 6000 bits, 3000 symbols are required when the modulation method is QPSK, 1500 symbols are required when the modulation method is 16QAM, and 1000 symbols are required when the modulation method is 64QAM.

Then, in the transmission device of FIG. 3 and the transmission device of FIG. 12, two streams are transmitted at the same time, and since there are two encoders, different code blocks are transmitted in the two streams. become. Therefore, when the modulation method is QPSK, since the two coded blocks are transmitted in the same section by s1 and s2, for example, the first coded block is transmitted by s1 and the first coded block is transmitted by s2. Since the 2 coded blocks will be transmitted, 3000 slots are required to transmit the 1st and 2nd coded blocks.

Similarly, when the modulation method is 16QAM, 1500 slots are required to transmit all the bits constituting the two coded blocks, and when the modulation method is 64QAM, the two coded blocks are required. 1000 slots are required to transmit all the bits that make up the.

Next, in the method of changing the phase regularly, the relationship between the slot defined above and the phase to be multiplied will be described.
Here, the number of phase change values (or phase change sets) prepared for the method of regularly changing the phase is set to 5. That is, it is assumed that five phase change values (or phase change sets) are prepared for the phase change unit of the transmitters of FIGS. 3 and 12 (“period” in the first to fourth embodiments. (As shown in FIG. 6, when the phase change is performed only on the baseband signal z2'after precoding, five phase change values may be prepared in order to perform the phase change in the period 5. , As shown in FIG. 26, when the phase change is performed for both the baseband signals z1'and z2' after precoding, two phase change values are required for one slot. These two phase changes. The value is called a phase change set. Therefore, in this case, in order to perform the phase change in the period 5, five phase change sets may be prepared). These five phase change values (or phase change sets) are represented as PHASE [0], PHASE [1], PHASE [2], PHASE [3], PHASE [4].

When the modulation method is QPSK, in the 3000 slots described above for transmitting the number of bits 6000 × 2 bits constituting the two coded blocks, the slots using the phase PHASE [0] are 600 slots and the phase. 600 slots using PHASE [1], 600 slots using phase PHASE [2], 600 slots using phase PHASE [3], 600 slots using phase PHASE [4] Must be. This is because if there is a deviation in the phase used, the influence of the phase using a large number is large, and the receiving quality of the data depends on this influence in the receiving device.

Further, in order to transmit the first coded block, the slot using the phase PHASE [0] is 600 times, the slot using the phase PHASE [1] is 600 times, and the slot using the phase PHASE [2] is 600 times. There must be 600 slots using phase PHASE [3] 600 times, 600 slots using phase PHASE [4], and phase PHASE to transmit the second coded block. 600 slots using [0], 600 slots using phase PHASE [1], 600 slots using phase PHASE [2], 600 slots using phase PHASE [3], It is preferable that the number of slots using the phase PHASE [4] is 600.

Similarly, when the modulation method is 16QAM, in the 1500 slots described above for transmitting the number of bits 6000 × 2 bits constituting the two coded blocks, there are 300 slots using the phase PHASE [0]. Slots, 300 slots using phase PHASE [1], 300 slots using phase PHASE [2], 300 slots using phase PHASE [3], slots using phase PHASE [4] Must be 300 slots.

Further, in order to transmit the first coded block, the slot using the phase PHASE [0] is 300 times, the slot using the phase PHASE [1] is 300 times, and the slot using the phase PHASE [2] is 300 times. There must be 300 slots using phase PHASE [3] 300 times, 300 slots using phase PHASE [4], and phase PHASE to transmit the second coded block. 300 slots using [0], 300 slots using phase PHASE [1], 300 slots using phase PHASE [2], 300 slots using phase PHASE [3], It is preferable that the number of slots using the phase PHASE [4] is 300.

Similarly, when the modulation method is 64QAM, in the 1000 slots described above for transmitting the number of bits 6000 × 2 bits constituting the two coded blocks, there are 200 slots using the phase PHASE [0]. Slots, 200 slots using phase PHASE [1], 200 slots using phase PHASE [2], 200 slots using phase PHASE [3], slots using phase PHASE [4] Must be 200 slots.

Further, in order to transmit the first coded block, the slot using the phase PHASE [0] is 200 times, the slot using the phase PHASE [1] is 200 times, and the slot using the phase PHASE [2] is 200 times. There must be 200 slots using phase PHASE [3] 200 times, 200 slots using phase PHASE [4], and phase PHASE to transmit the second coded block. 200 slots using [0], 200 slots using phase PHASE [1], 200 slots using phase PHASE [2], 200 slots using phase PHASE [3], It is preferable that the number of slots using the phase PHASE [4] is 200.

As described above, in the method of regularly changing the phase, the phase change value (or phase change set) to be prepared is PHASE [0], PHASE [1], PHASE [2], ..., PHASE [N. -2], PHASE [N-1]), the number of slots that use the phase PHASE [0] when transmitting all the bits that make up the two coded blocks is K. ₀ , the number of slots using phase PHASE [1] is K _{1, the} number of slots using phase PHASE [i] is K _i (i = 0,1,2, ..., N-1), phase PHASE [ When the number of slots that use N-1] is K _N-1 ,

<Condition # A03>
K ₀ = K ₁ = ... = K _i = ... = K _N-1 , that is, K _a = K _b , (for ∀a, ∀b, but a, b = 0,1,2,・ ・ ・, N-1, a ≠ b)

The number of times the phase PHASE [0] is used when transmitting all the bits constituting the first encoded block is K ₀ , 1, and the number of times the phase PHASE [1] is used is K _{1, 1. 1. The number of times the} phase PHASE [i] is used is K _{i, 1} (i = 0,1,2, ..., N-1), and the number of times the phase PHASE [N-1] is used is K _N-1 . _{, When set to 1} ,

<Condition # A04>
K ₀ , 1 = K ₁ , 1 = ... = Ki, ₁ = ... = K _N-1 , 1, that is, Ka, ₁ = K _{b, 1} , (for ∀a, ∀b, However, a, b = 0,1,2, ..., N-1, a ≠ b)

The number of times the phase PHASE [0] is used when transmitting all the bits constituting the second encoded block is K ₀ , 2, and the number of times the phase PHASE [1] is used is K _{1, 1. 2. The number of times the} phase PHASE [i] is used is K _{i, 2} (i = 0,1,2, ..., N-1), and the number of times the phase PHASE [N-1] is used is K _N-1 . _{, When set to 2} ,

<Condition # A05>
K ₀ , 2 = K ₁ , 2, = ... = Ki, ₂ = ... = K _N-1 , 2, that is, K _{a, 2} = K _{b, 2} , (for ∀a, ∀b,) However, a, b = 0,1,2, ..., N-1, a ≠ b)

It should be.

When the communication system supports a plurality of modulation methods and is used by selecting from the supported modulation methods, <condition # A03> <condition # A04> <conditions in the supported modulation methods. It is good if # A05> is established.

However, when a plurality of modulation methods are supported, the number of bits that can be transmitted by one symbol is generally different for each modulation method (in some cases, they may be the same). In some cases, there may be a modulation method that cannot satisfy <Condition # A03>, <Condition # A04>, and <Condition # A05>. In this case, the following conditions may be satisfied instead of <Condition # A03> <Condition # A04> <Condition # A05>.

<Condition # A06>
The difference between K _a and K _b is 0 or 1, that is, | K _a -K _b | is 0 or 1.
(For ∀a, ∀b, but a, b = 0,1,2, ..., N-1, a ≠ b)

<Condition # A07>
The difference between K _{a, 1} and K _{b, 1} is 0 or 1, that is, | K _{a, 1} -K _{b, 1} | is 0 or 1.
(For ∀a, ∀b, but a, b = 0,1,2, ..., N-1, a ≠ b)

<Condition # A08>
The difference between K _{a, 2} and K _{b, 2} is 0 or 1, that is, | K _{a, 2} -K _{b, 2} | is 0 or 1.
(For ∀a, ∀b, but a, b = 0,1,2, ..., N-1, a ≠ b)

As described above, by associating the coded block with the phase to be multiplied, the phase used for transmitting the coded block is not biased, so that the data reception quality is improved in the receiving device. The effect can be obtained.

In the present embodiment, in the method of regularly changing the phase, N phase change values (or phase change sets) are required for the phase change method having a period N. At this time, PHASE [0], PHASE [1], PHASE [2], ..., As N phase change values (or phase change sets),
PHASE [N-2] and PHASE [N-1] will be prepared, but PHASE [0], PHASE [1], PHASE [2], ..., PHASE [N-2] in the frequency axis direction. , PHASE [N-1] can be arranged in this order, but it is not limited to this, and N phase change values (or phase change set) PHASE [0], PHASE [1]
, PHASE [2], ..., PHASE [N-2], PHASE [N-1] by arranging symbols for blocks on the time axis and frequency-time axis, as in the first embodiment. , The phase can also be changed. Although the method of changing the phase of the period N is described, the same effect can be obtained by randomly using N phase change values (or phase change sets), that is, it is not always a rule. It is not necessary to use N phase change values (or phase change sets) so as to have a certain period, but the condition described above is satisfied in order to obtain high data reception quality in the receiving device. , Will be important.

Further, a spatial multiplex MIMO transmission method, a MIMO transmission method with a fixed precoding matrix, a spatiotemporal block coding method, a method of transmitting only one stream, and a method of regularly changing the phase (described in the first to fourth embodiments). The mode of the transmission method) exists, and the transmission device (broadcasting station, base station) may be able to select one of the transmission methods from these modes.

As shown in Non-Patent Document 3, the spatial multiplex MIMO transmission method is a method of transmitting signals s1 and s2 mapped by the selected modulation method from different antennas, and the precoding matrix is fixed. The MIMO transmission method is a method in which only precoding is performed (phase change is not performed) in the first to fourth embodiments. The space-time block coding method is a transmission method shown in Non-Patent Documents 9, 16 and 17. The transmission of only one stream is a method in which the signal of the signal s1 mapped by the selected modulation method is subjected to predetermined processing and transmitted from the antenna.

Further, a multi-carrier transmission method such as OFDM is used, and a first carrier group composed of a plurality of carriers, a second carrier group different from the first carrier group composed of a plurality of carriers, ... Multi-carrier transmission is realized by multiple carrier groups, such as spatial multiplex MIMO transmission method, MIMO transmission method with fixed precoding matrix, spatiotemporal block coding method, and transmission of only one stream for each carrier group. It may be set to one of the methods of changing the phase regularly.
In particular, in the (sub) carrier group in which the method of regularly changing the phase is selected, the present embodiment may be implemented.

When the phase is changed for one of the precoded baseband signals, for example, when the phase change value of PHASE [i] is "X radian", FIGS. 3, 4, 6, and 12 ， ，
In the phase change section in FIGS. 25, 29, 51, and 53, ^ejX is multiplied by the precoded baseband signal z2'. Then, when the phase change is performed on the baseband signals after both precoding, for example, when the phase change set of PHASE [i] is "X radian" and "Y radian", FIGS. 26 and 27, In the phase change section in FIGS. 28, 52, and 54, the baseband signal z2 after precoding ^ejX .
'Will be multiplied, and e ^jY will be multiplied by the precoded baseband signal z1'.

(Embodiment B1)
Hereinafter, application examples of the transmission method and the reception method shown in each of the above embodiments and a system configuration example using the same will be described.

FIG. 36 is a diagram showing a configuration example of a system including a device for executing the transmission method and the reception method shown in the above embodiment. The transmission method and the reception method shown in each of the above embodiments are shown in FIG. 36.
Digital broadcasting including broadcasting stations as shown in the above and various types of receivers such as television (television) 3611, DVD recorder 3612, STB (Set Top Box) 3613, computer 3620, in-vehicle television 3641 and mobile phone 3630. It is carried out in the system 3600. Specifically, the broadcasting station 3601 transmits the multiplexed data in which video data, audio data, and the like are multiplexed to a predetermined transmission band by using the transmission method shown in each of the above embodiments.

The signal transmitted from the broadcasting station 3601 is received by an antenna (for example, antennas 3660 and 3640) built in or externally installed in each receiver and connected to the receiver. Each receiver demodulates the signal received at the antenna by using the receiving method shown in each of the above embodiments, and acquires the multiplexed data. Thereby, the digital broadcasting system 3600 can obtain the effect of the present invention described in each of the above embodiments.

Here, the video data included in the multiplexed data is, for example, MPEG (Moving Picture Experts Group) 2 or MPEG4-AVC (Advanced).
It is encoded using a moving image coding method compliant with standards such as Video Coding) and VC-1. The audio data included in the multiplexed data is, for example, Dolby AC (Audio Coding) -3, Dolby Digital Plus, MLP (Meridian Lossless Packing), DTS (Digital Theater Systems), DTS-HD, Linear PCM (Pulse).
It is coded by a voice coding method such as Modulation).

FIG. 37 is a diagram showing an example of the configuration of the receiver 7900 that implements the receiving method described in each of the above embodiments. The receiver 3700 shown in FIG. 37 corresponds to the configuration provided in the television (television) 3611 shown in FIG. 36, the DVD recorder 3612, the STB (Set Top Box) 3613, the computer 3620, the in-vehicle television 3641, the mobile phone 3630, and the like. do. The receiver 3700 includes a tuner 3701 that converts a high-frequency signal received by the antenna 3760 into a baseband signal, and a demodulation unit 3702 that demodulates the frequency-converted baseband signal and acquires multiplexed data. The receiving method shown in each of the above embodiments is carried out by the demodulation unit 3702, whereby the effect of the present invention described in each of the above embodiments can be obtained.

Further, the receiver 3700 uses a stream input / output unit 3720 that separates video data and audio data from the multiplexed data obtained by the demodulation unit 3702, and a video decoding method corresponding to the separated video data. A signal processing unit 3704 that decodes data into a video signal and decodes the audio data into an audio signal using an audio decoding method corresponding to the separated audio data, and an audio output unit such as a speaker that outputs the decoded audio signal. It has a 3706 and a video display unit 3707 such as a display for displaying the decoded video signal.

For example, the user uses the remote controller (remote controller) 3750 to transmit information on the selected channel (selected (television) program, selected audio broadcast) to the operation input unit 3710. Then, the receiver 3700 demodulates the signal corresponding to the selected channel in the received signal received by the antenna 3760, performs processing such as error correction and decoding, and obtains the received data. At this time, the receiver 3700 is a transmission method (transmission method, modulation method, error correction method, etc. described in the above embodiment) included in the signal corresponding to the selected channel (for this, FIGS. 5 and 5 and FIG. By obtaining the information of the control symbol including the information of (41), the reception operation, the demodulation method, the error correction / decoding, and the like are correctly set, and the transmission is performed by the broadcasting station (base station). It is possible to obtain the data contained in the data symbol. In the above, the user has described an example of selecting a channel by using the remote controller 3750. However, even if the channel is selected by using the channel selection key mounted on the receiver 3700, the same operation as described above can be obtained. Become.

With the above configuration, the user can watch the program received by the receiver 3700 by the receiving method shown in each of the above embodiments.
Further, the receiver 3700 of the present embodiment demodulates with the demodulation unit 3702, and the multiplexed data obtained by decoding the error correction (in some cases, with respect to the signal obtained by demodulation by the demodulation unit 3702). In addition, the receiver 3700 may be subjected to other signal processing after the error correction / decoding. In the following, the same expression may be applied to this point. Is the same.), Data corresponding to the data (for example, data obtained by compressing the data), video, and data obtained by processing audio can be used as a magnetic disk. , A recording unit (drive) 3708 for recording on a recording medium such as an optical disk or a non-volatile semiconductor memory. Here, the optical disk is a recording medium such as a DVD (Digital Versaille Disc) or a BD (Blu-ray (registered trademark) Disc) in which information is stored and read out using a laser beam. A magnetic disk is a recording medium such as an FD (Floppy Disk) (registered trademark) or a hard disk (Hard Disk) that stores information by magnetizing a magnetic material using a magnetic flux. The non-volatile semiconductor memory is a recording medium composed of semiconductor elements such as a flash memory and a ferroelectric memory (Feroelectric Random Access Memory), and is an SD card using a flash memory or a Flash SSD (Solid State Drive). ) And so on. It should be noted that the types of recording media listed here are just examples, and it goes without saying that recording may be performed using recording media other than the above-mentioned recording media.

With the above configuration, the user records and stores the program received by the receiver 3700 by the receiving method shown in each of the above embodiments, and the data recorded at an arbitrary time after the broadcast time of the program. Can be read and viewed.

In the above description, the receiver 3700 demodulates with the demodulation unit 3702 and records the multiplexed data obtained by decoding the error correction with the recording unit 3708, but the data included in the multiplexed data. Some of the data may be extracted and recorded. For example, when the multiplexed data obtained by demodulating with the demodulating unit 3702 and decoding the error correction includes the contents of the data broadcasting service other than the video data and the audio data, the recording unit 3708 may use the demodulating unit 3702. Video data and audio data may be extracted from the multiplexed data demolished in step 1 and new multiplexed data may be recorded. Further, the recording unit 3708 demodulates with the demodulation unit 3702, and the new multiplexed data in which only one of the video data and the audio data included in the multiplexed data obtained by decoding the error correction is multiplexed. May be recorded. Then, the recording unit 3708 may record the content of the data broadcasting service included in the multiplexed data described above.

Furthermore, if the receiver 3700 described in the present invention is mounted on a television, a recording device (for example, a DVD recorder, a Blu-ray (registered trademark) recorder, an HDD recorder, an SD card, etc.), or a mobile phone, demodulation is performed. Data, personal information, and records for correcting defects (bugs) in software used to operate televisions and recording devices in the multiplexed data obtained by demodulating in section 3702 and decoding error corrections. If data is included to fix software defects (bugs) to prevent data leakage, installing these data may correct software defects in TVs and recording devices. .. Then, if the data includes data for correcting a software defect (bug) of the receiver 3700, this data can also be used to correct a defect of the receiver 3700. As a result, the television, recording device, and mobile phone on which the receiver 3700 is mounted can be operated more stably.

Here, the process of extracting a part of the data from the plurality of data included in the multiplexed data obtained by demodulating with the demodulation unit 3702 and decoding the error correction and multiplexing the data is, for example, the stream input / output unit 3703. It is done in. Specifically, the stream input / output unit 3703 converts the multiplexed data demoded by the demodulation unit 3702 into video data, audio data, data broadcasting service content, etc. in response to an instruction from a control unit such as a CPU (not shown). It separates into multiple data, extracts only the specified data from the separated data and multiplexes it, and generates new multiplexed data. The user may decide, for example, which data should be extracted from the separated data, or may be predetermined for each type of recording medium.

With the above configuration, the receiver 3700 can extract and record only the data necessary for viewing the recorded program, so that the data size of the recorded data can be reduced.

Further, in the above description, the recording unit 3708 is supposed to record the multiplexed data obtained by demodulating the data in the demodulatoring unit 3702 and decoding the error correction. The video data included in the multiplexed data obtained by performing the above is different from the video coding method applied to the video data so that the data size or bit rate is lower than that of the video data. It may be converted into video data encoded by the conversion method, and new multiplexed data in which the converted video data is multiplexed may be recorded. At this time, the moving image coding method applied to the original video data and the moving image coding method applied to the converted video data may comply with different standards or conform to the same standard. And only the parameters used at the time of encoding may be different. Similarly, the recording unit 3708 demodulates the voice data included in the multiplexed data obtained by demodulating with the demodulating unit 3702 and decoding the error correction so that the data size or bit rate of the voice data is lower than that of the voice data. , The voice data may be converted into voice data encoded by a voice coding method different from the voice coding method applied to the voice data, and new multiplexed data in which the converted voice data is multiplexed may be recorded.

Here, the process of converting the video data and audio data included in the multiplexed data obtained by demodulating with the demodulator 3702 and decoding the error correction into video data and audio data having different data sizes or bit rates is performed. For example, it is performed by the stream input / output unit 3703 and the signal processing unit 3704. Specifically, the stream input / output unit 3703 demodulates in the demodulation unit 3702 according to an instruction from a control unit such as a CPU, and decodes the error correction to obtain multiplexed data, which is video data, audio data, and the like. Separate into multiple data such as data broadcasting service contents. The signal processing unit 3704 is a process of converting the separated video data into video data encoded by a video coding method different from the video coding method applied to the video data according to an instruction from the control unit. , And the process of converting the separated voice data into voice data encoded by a voice coding method different from the voice coding method applied to the voice data. The stream input / output unit 3703 multiplexes the converted video data and the converted audio data according to an instruction from the control unit, and generates new multiplexed data. Note that the signal processing unit 3704 may perform conversion processing on only one of the video data and the audio data, or perform conversion processing on both, in response to an instruction from the control unit. Is also good. Further, the data size or bit rate of the converted video data and audio data may be determined by the user or may be predetermined for each type of recording medium.

With the above configuration, the receiver 3700 changes the data size or bit rate of video data and audio data according to the data size that can be recorded on the recording medium and the speed at which the recording unit 3708 records or reads the data. can do. As a result, when the data size that can be recorded on the recording medium is smaller than the data size of the multiplexed data obtained by demodulating the data in the demodulator 3702 and performing error correction decoding, or when the recording unit records or reads the data. Even if the speed at which the data is performed is lower than the bit rate of the multiplexed data demolished by the demodulator 3702, the recording unit can record the program, so that the user can record the program at any time after the broadcast time of the program. It becomes possible to read out and view the data recorded in.

Further, the receiver 3700 includes a stream output IF (Interface) 3709 that transmits the multiplexed data demodulated by the demodulation unit 3702 to the external device via the communication medium 3730. As an example of the stream output IF3709, Wi-Fi (registered trademark) (IEEE802.11a, IEEE802.11b, IEEE802.11g, IEEE802.11n, etc.), WiGiG, WirelessHD, Bluetooth (registered trademark), Zigbee (registered trademark), etc. Examples thereof include a wireless communication device that transmits multiplexed data modulated using a wireless communication method compliant with the wireless communication standard of the above to an external device via a wireless medium (corresponding to a communication medium 3730). Further, the stream output IF3709 includes Ethernet (registered trademark), USB (Universal Serial Bus), and PLC (Power Line).
A wired transmission line (communication medium 3730) in which multiplexed data modulated using a communication method compliant with a wired communication standard such as Communication) or HDMI (registered trademark) (High-Definition Multimedia Interface) is connected to the stream output IF3709. It may be a wired communication device that transmits to an external device via (corresponding to).

With the above configuration, the user can use the multiplexed data received by the receiver 3700 by the receiving method shown in each of the above embodiments in the external device. The use of multiplexed data here means that the user can view the multiplexed data in real time using an external device, record the multiplexed data in the recording unit provided in the external device, and further from the external device. Includes sending multiplexed data to another external device, etc.

In the above description, the receiver 3700 demodulates with the demodulation unit 3702, and the stream output IF3709 outputs the multiplexed data obtained by decoding the error correction. However, the data included in the multiplexed data. Some of the data may be extracted and output. For example, when the multiplexed data obtained by demodulating with the demodulator 3702 and decoding the error correction includes the contents of the data broadcasting service other than the video data and the audio data, the stream output IF3709 is the demodulator 3702. You may output the new multiplexed data by extracting the video data and the audio data from the multiplexed data obtained by demodulating with and decoding the error correction. Further, the stream output IF3709 may output new multiplexed data in which only one of the video data and the audio data included in the multiplexed data demodulated by the demodulation unit 3702 is multiplexed.

Here, the process of extracting a part of the data from the plurality of data included in the multiplexed data obtained by demodulating with the demodulation unit 3702 and decoding the error correction and multiplexing the data is, for example, the stream input / output unit 3703. It is done in. Specifically, the stream input / output unit 3703 broadcasts video data, audio data, and data broadcasting of the multiplexed data demolished by the demodulation unit 3702 in response to an instruction from a control unit such as a CPU (Central Processing Unit) (not shown). It separates into multiple data such as service contents, extracts only the specified data from the separated data and multiplexes it, and generates new multiplexed data. The user may determine, for example, which data should be extracted from the separated data, or may be predetermined for each type of stream output IF3709.

With the above configuration, the receiver 3700 can extract and output only the data required by the external device, so that the communication band consumed by the output of the multiplexed data can be reduced.

Further, in the above description, the stream output IF3709 is demoted by the demodulator 3702 and outputs the multiplexed data obtained by decoding the error correction. The video data included in the multiplexed data obtained by performing the above is different from the video coding method applied to the video data so that the data size or bit rate is lower than that of the video data. It may be converted into video data encoded by the conversion method, and new multiplexed data in which the converted video data is multiplexed may be output. At this time, the moving image coding method applied to the original video data and the moving image coding method applied to the converted video data may comply with different standards or conform to the same standard. And only the parameters used at the time of encoding may be different. Similarly, the stream output IF3709 demodulates the voice data included in the multiplexed data obtained by demodulating with the demodulator 3702 and decoding the error correction so that the data size or bit rate of the voice data is lower than that of the voice data. , The voice data may be converted into voice data encoded by a voice coding method different from the voice coding method applied to the voice data, and new multiplexed data in which the converted voice data is multiplexed may be output.

Here, the process of converting the video data and audio data included in the multiplexed data obtained by demodulating with the demodulator 3702 and decoding the error correction into video data and audio data having different data sizes or bit rates is performed. For example, it is performed by the stream input / output unit 3703 and the signal processing unit 3704. Specifically, the stream input / output unit 3703 demodulates with the demodulation unit 3702 according to an instruction from the control unit, and the multiplexed data obtained by decoding the error correction is video data, audio data, and a data broadcasting service. Separate into multiple data such as the contents of. The signal processing unit 3704 is a process of converting the separated video data into video data encoded by a video coding method different from the video coding method applied to the video data according to an instruction from the control unit. , And the process of converting the separated voice data into voice data encoded by a voice coding method different from the voice coding method applied to the voice data. The stream input / output unit 3703 multiplexes the converted video data and the converted audio data according to an instruction from the control unit, and generates new multiplexed data. Note that the signal processing unit 3704 may perform conversion processing on only one of the video data and the audio data, or perform conversion processing on both, in response to an instruction from the control unit. Is also good. Further, the data size or bit rate of the converted video data and audio data may be determined by the user or may be predetermined for each type of stream output IF3709.

With the above configuration, the receiver 3700 can output the video data and the audio data by changing the bit rate according to the communication speed with the external device. As a result, even if the communication speed with the external device is lower than the bit rate of the multiplexed data obtained by demodulating with the demodulation unit 3702 and performing error correction decoding, the external device new multiplexing from the stream output IF. Since the demodulated data can be output, the user can use the new multiplexed data in other communication devices.

Further, the receiver 3700 includes an AV (Audio and Visual) output IF (Interface) 3711 that outputs a video signal and an audio signal decoded by the signal processing unit 3704 to an external device to an external communication medium. As an example of AV output IF3711, wireless communication standards such as Wi-Fi (registered trademark) (IEEE802.11a, IEEE802.11b, IEEE802.11g, IEEE802.11n, etc.), WiGiG, WiressHD, Bluetooth (registered trademark), Gigabit, etc. Examples thereof include a wireless communication device that transmits a video signal and an audio signal modulated by using a wireless communication method compliant with the above to an external device via a wireless medium. Further, the stream output IF3709 connects a video signal and an audio signal modulated by a communication method compliant with a wired communication standard such as Ethernet (registered trademark), USB, PLC, and HDMI (registered trademark) to the stream output IF3709. It may be a wired communication device that transmits to an external device via the wired transmission line. Further, the stream output IF3709 may be a terminal for connecting a cable that outputs a video signal and an audio signal as analog signals.

With the above configuration, the user can use the video signal and the audio signal decoded by the signal processing unit 3704 in an external device.
Further, the receiver 3700 includes an operation input unit 3710 that receives an input of a user operation. The receiver 3700 switches the power ON / OFF, the receiving channel, the presence / absence of subtitle display, and the language to be displayed based on the control signal input to the operation input unit 3710 according to the user's operation. , Switching various operations such as changing the volume output from the audio output unit 3706, and changing the settings such as the setting of the receivable channel.

Further, the receiver 3700 may have a function of displaying an antenna level indicating the reception quality of the signal being received by the receiver 3700. Here, the antenna level is, for example, RSSI (Received Signal Strength Indicator, Received Signal Strength), received electric field strength, C / N (Carrier-to-noise power) of the signal received by the receiver 3700. , BER (Bit Error Rate), Packet Error Rate, Frame Error Rate, Channel Status Information (Channel)
It is an index indicating the reception quality calculated based on the State Information) and the like, and is a signal indicating the signal level and the superiority or inferiority of the signal. In this case, the demodulation unit 3702 includes a reception quality measurement unit that measures RSSI, received electric field strength, C / N, BER, packet error rate, frame error rate, channel state information, etc. of the received signal, and the receiver 3700 is a user. The antenna level (signal level, signal indicating superiority or inferiority of the signal) is displayed on the video display unit 3707 in a user-identifiable format according to the operation of. The display format of the antenna level (signal level, signal indicating superiority or inferiority of the signal) displays numerical values according to RSSI, received electric field strength, C / N, BER, packet error rate, frame error rate, channel state information, etc. It may be such that different images are displayed according to RSSI, received electric field strength, C / N, BER, packet error rate, frame error rate, channel state information, and the like. Further, the receiver 3700 has a plurality of antenna levels (signal level, signal) obtained for each of a plurality of streams s1, s2, ... Received and separated by using the receiving method shown in each of the above embodiments. A signal indicating superiority or inferiority) may be displayed, or one antenna level (signal level, signal indicating superiority or inferiority of the signal) obtained from a plurality of streams s1, s2, ... May be displayed. Further, when the video data and the audio data constituting the program are transmitted by the hierarchical transmission method, it is also possible to indicate the signal level (signal indicating superiority or inferiority of the signal) for each layer.

With the above configuration, the user can numerically or visually grasp the antenna level (signal level, signal indicating superiority or inferiority of the signal) when receiving using the receiving method shown in each of the above embodiments. Can be done.

In the above description, the case where the receiver 3700 includes an audio output unit 3706, a video display unit 3707, a recording unit 3708, a stream output IF3709, and an AV output IF3711 has been described as an example, but these configurations have been described. You don't have to have all of them. If the receiver 3700 has at least one of the above configurations, the user can use the multiplexed data obtained by demodulating with the demodulation unit 3702 and performing error correction decoding. , Each receiver may be provided with any combination of the above configurations according to the intended use.
(Multiplexed data)
Next, an example of the structure of the multiplexed data will be described in detail. MPEG2-Transport Stream (TS) is generally used as the data structure used for broadcasting, and here M
PEG2-TS will be described as an example. However, the data structure of the multiplexed data transmitted by the transmission method and the reception method shown in each of the above embodiments is not limited to MPEG2-TS, and any other data structure will be described in each of the above embodiments. Needless to say, you can get the desired effect.

FIG. 38 is a diagram showing an example of the configuration of multiplexed data. As shown in FIG. 38, the multiplexed data is an element that constitutes a program (program or an event that is a part thereof) currently provided by each service, for example, a video stream, an audio stream, or a presentation graphics stream (PG). ), Interactive Grafix Stream (IG), etc., obtained by multiplexing one or more of the elemental streams. If the program provided by the multiplexed data is a movie, the video stream is the main and sub-video of the movie, and the audio stream is the main audio part of the movie and the sub-audio that mixes with the main audio, as the presentation graphics stream. Shows the subtitles of each movie. Here, the main image is a normal image displayed on the screen, and the sub image is an image displayed on a small screen in the main image (for example, a text data image showing the outline of a movie). be. Further, the interactive graphics stream shows an interactive screen created by arranging GUI components on the screen.

Each stream contained in the multiplexed data is identified by a PID, which is an identifier assigned to each stream. For example, 0x1011 for video streams used for movie images, 0x1100 to 0x111F for audio streams, 0x1200 to 0x121F for presentation graphics, and 0x1400 to 0x141F for interactive graphics streams. 0x1B00 to 0x1B1F are assigned to the video stream used for the sub video, and 0x1A00 to 0x1A1F are assigned to the audio stream used for the sub audio to be mixed with the main audio.

FIG. 39 is a diagram schematically showing an example of how the multiplexed data is multiplexed. First, the video stream 3901 composed of a plurality of video frames and the audio stream 3904 composed of a plurality of audio frames are converted into PES packet strings 3902 and 3905, respectively, and converted into TS packets 3903 and 3906, respectively. Similarly, the data of the presentation graphics stream 3911 and the interactive graphics 3914 are converted into PES packet strings 3912 and 3915, respectively, and further converted into TS packets 3913 and 3916. The multiplexed data 3917 is configured by multiplexing these TS packets (3903, 3906, 3913, 3916) into one stream.

FIG. 40 shows in more detail how the video stream is stored in the PES packet sequence. The first stage in FIG. 40 shows a video frame sequence of a video stream. The second stage shows the PES packet sequence. As shown by arrows yy1, yy2, yy3, and yy4 in FIG. 40, I-pictures, B-pictures, and P-pictures, which are a plurality of Video Presentation Units in the video stream, are divided into pictures and stored in the payload of the PES packet. .. Each PES packet has a PES header, and the PTS header stores PTS (Presentation Time-Stamp), which is the display time of the picture, and DTS (Decoding Time-Stamp), which is the decoding time of the picture.

FIG. 41 shows the format of the TS packet that is finally written to the multiplexed data. The TS packet is a 188 BYTE fixed-length packet composed of a 4 BYTE TS header having information such as a PID that identifies a stream and a 184 BYTE TS payload that stores data, and the PES packet is divided and stored in the TS payload. Ru. In the case of BD-ROM, 4Bite TP_Extra_Header is added to the TS packet, constitutes a 192Bite source packet, and is written to the multiplexed data. Information such as ATS (Arrival_Time_Stamp) is described in TP_Extra_Header. ATS indicates the transfer start time of the TS packet to the PID filter of the decoder. As shown in the lower part of FIG. 41, source packets are arranged in the multiplexed data, and the number incremented from the beginning of the multiplexed data is called SPN (source packet number).

In addition to each stream such as a video stream, an audio stream, and a presentation graphics stream, the TS packet included in the multiplexed data includes PAT (Program Association Table) and PMT (Program).
Map Table), PCR (Program Lock Reference) and the like. The PAT indicates what the PID of the PMT used in the multiplexed data is, and the PID of the PAT itself is registered as 0. The PMT has the PID of each stream such as video, audio, and subtitles contained in the multiplexed data and the attribute information (frame rate, aspect ratio, etc.) of the stream corresponding to each PID, and also contains various descriptors related to the multiplexed data. Have. Descriptors include copy control information that instructs whether to allow or disallow copying of multiplexed data. The PCR corresponds to the ATS in which the PCR packet is transferred to the decoder in order to synchronize the ATC (Arrival Time Clock) which is the time axis of the ATS and the STC (System Time Clock) which is the time axis of the PTS / DTS. Has information on STC time.

FIG. 42 is a diagram illustrating the data structure of the PMT in detail. At the beginning of the PMT, a PMT header describing the length of the data included in the PMT is arranged. Behind it, a plurality of descriptors related to the multiplexed data are arranged. The copy control information and the like are described as descriptors. After the descriptor, a plurality of stream information about each stream included in the multiplexed data is arranged. The stream information is composed of a stream descriptor for describing a stream type for identifying a stream compression codec and the like, a stream PID, and stream attribute information (frame rate, aspect ratio, etc.). There are as many stream descriptors as there are streams in the multiplexed data.

When recording on a recording medium or the like, the multiplexed data is recorded together with the multiplexed data information file.
FIG. 43 is a diagram showing the structure of the multiplexed data information file. As shown in FIG. 43, the multiplexed data information file is management information of the multiplexed data, has a one-to-one correspondence with the multiplexed data, and is composed of the multiplexed data information, the stream attribute information, and the entry map.

As shown in FIG. 43, the multiplexed data information is composed of a system rate, a reproduction start time, and a reproduction end time. The system rate indicates the maximum transfer rate of the multiplexed data to the PID filter of the system target decoder described later. The ATS interval included in the multiplexed data is set to be less than or equal to the system rate. The reproduction start time is set to the PTS of the video frame at the beginning of the multiplexed data, and the reproduction end time is set to the PTS of the video frame at the end of the multiplexed data plus the reproduction interval for one frame.

FIG. 44 is a diagram showing the structure of stream attribute information included in the multiplexed data information file. As shown in FIG. 44, as the stream attribute information, the attribute information for each stream included in the multiplexed data is registered for each PID. The attribute information has different information for each of the video stream, audio stream, presentation graphics stream, and interactive graphics stream. The video stream attribute information includes what compression codec the video stream was compressed with, what the resolution of the individual picture data that makes up the video stream is, what the aspect ratio is, and the frame rate. It has information such as how much it is. The audio stream attribute information includes what compression codec the audio stream was compressed with, what number of channels the audio stream contains, what language it supports, what sampling frequency it is, and so on. Have information on. This information is used for initializing the decoder before the player plays it.

In the present embodiment, the stream type included in the PMT is used among the above-mentioned multiplexed data. When the multiplexed data is recorded on the recording medium, the video stream attribute information included in the multiplexed data information is used. Specifically, in the moving image coding method or apparatus shown in each of the above embodiments, the moving image coding shown in each of the above embodiments is applied to the stream type or video stream attribute information included in the PMT. Provide steps or means to set unique information indicating that the video data is generated by the method or device. With this configuration, it becomes possible to distinguish between the video data generated by the moving image coding method or the apparatus shown in each of the above embodiments and the video data conforming to other standards.

FIG. 45 is an example of the configuration of a video / audio output device 4500 including a receiving device 4504 that receives video and audio data transmitted from a broadcasting station (base station) or a modulated signal including data for data broadcasting. Is shown. The configuration of the receiving device 4504 corresponds to the receiving device 3700 in FIG. 37. The video / audio output device 4500 is equipped with an OS (Operating System), for example, and is used for a communication device 4506 (for example, a wireless LAN (Local Area Network) or an ether net) for connecting to the Internet. Communication device) is installed. As a result, in the part 4501 for displaying the video, the video 4502 in the video and audio data or the data for data broadcasting, and the hypertext provided on the Internet (World Wide Web (WWW)). ) 4503 can be displayed at the same time. Then, by operating the remote controller (which may be a mobile phone or keyboard) 4507, either the video 4502 in the data for data broadcasting or the hypertext 4503 provided on the Internet is selected and the operation is changed. Will be done. For example, when the hypertext 4503 provided on the Internet is selected, the displayed WWW site can be changed by operating the remote controller. When the video 4502 in the video and audio data or the data for data broadcasting is selected, the channel selected by the remote controller 4507 (selected (television) program, selected audio broadcast). Send information. Then, the IF4505 acquires the information transmitted by the remote controller, and the receiving device 4504 demodulates the signal corresponding to the selected channel, performs processing such as error correction and decoding, and obtains the received data. At this time, the receiving device 4504 receives the information of the control symbol including the information of the transmission method (this is as shown in FIG. 5) included in the signal corresponding to the selected channel. By correctly setting the operation, demodulation method, error correction / decoding method, etc., it is possible to obtain the data included in the data symbol transmitted by the broadcasting station (base station). In the above, the user has described an example of selecting a channel by the remote controller 4507, but the same as above can be obtained even if the channel is selected by using the channel selection key mounted on the video / audio output device 4500. It becomes an operation.

Further, the video / audio output device 4500 may be operated using the Internet. For example, recording (memory) is reserved for the video / audio output device 4500 from another terminal connected to the Internet. (Therefore, the video / audio output device 4500 has a recording unit 3708 as shown in FIG. 37.) Then, before starting recording, the channel is selected, and the receiving device 4504 Will demodulate the signal corresponding to the selected channel, perform processing such as error correction and decoding, and obtain received data. At this time, the receiving device 4504 is a transmission method (transmission method, modulation method, error correction method, etc. described in the above embodiment) included in the signal corresponding to the selected channel (this is described in FIG. 5). By obtaining the information of the control symbol including the information of), the data symbol transmitted by the broadcasting station (base station) can be used by correctly setting the reception operation, demodulation method, error correction / decoding, and other methods. It is possible to obtain the included data.

(Other supplements)
In the present specification, it is considered that a transmission device is provided in, for example, a communication / broadcasting device such as a broadcasting station, a base station, an access point, a terminal, or a mobile phone (mobile phone). It is conceivable that the receiver is equipped with a communication device such as a television, a radio, a terminal, a personal computer, a mobile phone, an access point, and a base station. Further, the transmitting device and the receiving device in the present invention are devices having a communication function, and the device has some kind of interface to a device for executing an application such as a television, a radio, a personal computer, and a mobile phone. For example, it may be possible to connect via USB).

Further, in the present embodiment, symbols other than data symbols, for example, pilot symbols (pilot symbols may be referred to as preambles, unique words, postambles, reference symbols, scattered pilots, etc.), symbols for control information, etc. Etc. may be arranged in the frame. Here, the names are pilot symbols and symbols for control information, but any naming method may be used, and the function itself is important.

The pilot symbol may be, for example, a known symbol modulated using PSK modulation in the transmitter / receiver (or by synchronizing the receiver, the receiver may be able to know the symbol transmitted by the transmitter. ), And the receiver uses this symbol to perform frequency synchronization, time synchronization, channel estimation (estimation of CSI (Channel State Information)) (estimation of CSI (Channel State Information)), signal detection, and the like. Become.

In addition, the symbol for control information is information that needs to be transmitted to the communication partner (for example, the modulation method / error correction coding method used for communication) in order to realize communication other than data (such as an application). It is a symbol for transmitting the coding rate of the error correction coding method, setting information in the upper layer, etc.).

It should be noted that the present invention is not limited to all embodiments, and various modifications can be made. For example, in the above embodiment, the case of performing as a communication device is described, but the present invention is not limited to this, and this communication method can also be performed as software.

Further, in the above, the phase changing method in the method of transmitting two modulated signals from two antennas has been described, but the present invention is not limited to this, and the four mapped signals are precoded and the phase is changed. A method of changing to generate 4 modulated signals and transmitting from 4 antennas, that is, precoding the N mapped signals, generating N modulated signals, and N antennas. Similarly, in the method of transmitting from, the phase can be changed regularly, and the phase can be changed in the same manner.

Further, in the system example shown in the above embodiment, a MIMO-type communication system in which two modulated signals are transmitted from two antennas and each is received by two antennas is disclosed, but the present invention naturally discloses MISO. It can also be applied to a (Multiple Input Single Output) type communication system. In the case of the MISO method, the receiving device does not have the antenna 701_Y, the radio unit 703_Y, the channel variation estimation unit 707_1 of the modulation signal z1, and the channel variation estimation unit 707_2 of the modulation signal z2 in the configuration shown in FIG. Even in this case, r1 and r2 can be estimated by executing the process shown in the first embodiment. It is well known that a plurality of transmitted signals can be received and decoded by one antenna in the same frequency band and at the same time, and in the present specification, the phase changed on the transmitting side in the signal processing unit. The process for returning is a process added to the prior art.

Further, in the system example shown in the description of the present invention, a MIMO-type communication system in which two modulated signals are transmitted from two antennas and each is received by two antennas is disclosed, but the present invention naturally discloses MISO. It can also be applied to a (Multiple Input Single Output) type communication system. In the case of the MISO method, the point that precoding and phase change are applied in the transmitting device is as described above. On the other hand, in the configuration shown in FIG. 7, the receiving device does not have the antenna 701_Y, the radio unit 703_Y, the channel fluctuation estimation unit 707_1 of the modulation signal z1, and the channel fluctuation estimation unit 707_1 of the modulation signal z2. Even so, the data transmitted by the transmitting device can be estimated by executing the processing shown in the present specification. It is well known that a plurality of transmitted signals can be received and decoded by one antenna in the same frequency band and at the same time (in one antenna reception, processing such as ML calculation (Max-log APP etc.) should be performed. In the present invention, the signal processing unit 711 of FIG. 7 may perform demodulation (detection) in consideration of precoding and phase change used on the transmitting side.

In this specification, terms such as "precoding", "precoding weight", and "precoding matrix" are used, but the term itself may be anything (for example, it may be called a codebook). Good), in the present invention, the signal processing itself is important.
Further, in this specification, the receiving device is described by using the ML calculation, APP, Max-log APP, ZF, MMSE, etc. As a result, the soft judgment result of each bit of the data transmitted by the transmitting device is obtained. (Log-likelihood, log-likelihood ratio) and hardness determination result ("0" or "1") will be obtained, but these may be collectively referred to as detection, demodulation, detection, estimation, and separation.

Different data may be transmitted or the same data may be transmitted by the streams s1 (t) and s2 (t) (s1 (i) and s2 (i)).
Also, regular phase changes and precoding are applied to the two streams of baseband signals s1 (i) and s2 (i) (where i represents the order (of time or frequency (carrier))). In the baseband signals z1 (i) and z2 (i) after both signals are processed, the baseband signals z1 (i) after both signals are generated. The in-phase I component is I ₁ (i), the orthogonal component is Q ₁ (i), the in-phase I component of the baseband signal z2 (i) after processing both signals is I ₂ (i), and the orthogonal component is Q ₂ ( i). At this time, replace the baseband components and replace them.
The in-phase component of the replaced baseband signal r1 (i) is I ₁ (i), the orthogonal component is Q ₂ (i), and the in-phase component of the replaced baseband signal r2 (i) is I ₂ (i). The orthogonal component is Q ₁ (i)
The modulated signal corresponding to the replaced baseband signal r1 (i) is transmitted from the transmitting antenna 1, and the modulated signal corresponding to the replaced baseband signal r2 (i) is transmitted from the transmitting antenna 2 at the same time and at the same frequency. The modulated signal corresponding to the replaced baseband signal r1 (i) and the replaced baseband signal r2 (i) are transmitted from different antennas at the same time and using the same frequency. May be good. again,
-The common mode component of the baseband signal r1 (i) after replacement is I ₁ (i), and the orthogonal component is I ₂ (i).
), The common mode component of the baseband signal r2 (i) after replacement is Q ₁ (i), and the orthogonal component is Q ₂ (i).
-The common mode component of the baseband signal r1 (i) after replacement is I ₂ (i), and the orthogonal component is I ₁ (i).
), The common mode component of the baseband signal r2 (i) after replacement is Q ₁ (i), and the orthogonal component is Q ₂ (i).
-The common mode component of the baseband signal r1 (i) after replacement is I ₁ (i), and the orthogonal component is I ₂ (i).
), The common mode component of the baseband signal r2 (i) after replacement is Q ₂ (i), and the orthogonal component is Q ₁ (i).
-The common mode component of the baseband signal r1 (i) after replacement is I ₂ (i), and the orthogonal component is I ₁ (i).
), The common mode component of the baseband signal r2 (i) after replacement is Q ₂ (i), and the orthogonal component is Q ₁ (i).
-The common mode component of the baseband signal r1 (i) after replacement is I ₁ (i), the orthogonal component is Q ₂ (i), and the common mode component of the baseband signal r2 (i) after replacement is Q ₁ (i), The orthogonal component is I ₂ (i)
The in-phase component of the replaced baseband signal r1 (i) is Q ₂ (i), the orthogonal component is I ₁ (i), and the in-phase component of the replaced baseband signal r2 (i) is I ₂ (i). The orthogonal component is Q ₁ (i)
The in-phase component of the replaced baseband signal r1 (i) is Q ₂ (i), the orthogonal component is I ₁ (i), and the in-phase component of the replaced baseband signal r2 (i) is Q ₁ (i). The orthogonal component is I ₂ (i)
-The common mode component of the baseband signal r2 (i) after replacement is I ₁ (i), and the orthogonal component is I ₂ (i).
), The common mode component of the baseband signal r1 (i) after replacement is Q ₁ (i), and the orthogonal component is Q ₂ (i).
-The common mode component of the baseband signal r2 (i) after replacement is I ₂ (i), and the orthogonal component is I ₁ (i).
), The common mode component of the baseband signal r1 (i) after replacement is Q ₁ (i), and the orthogonal component is Q ₂ (i).
-The common mode component of the baseband signal r2 (i) after replacement is I ₁ (i), and the orthogonal component is I ₂ (i).
), The common mode component of the baseband signal r1 (i) after replacement is Q ₂ (i), and the orthogonal component is Q ₁ (i).
-The common mode component of the baseband signal r2 (i) after replacement is I ₂ (i), and the orthogonal component is I ₁ (i).
), The common mode component of the baseband signal r1 (i) after replacement is Q ₂ (i), and the orthogonal component is Q ₁ (i).
The in-phase component of the replaced baseband signal r2 (i) is I ₁ (i), the orthogonal component is Q ₂ (i), and the in-phase component of the replaced baseband signal r1 (i) is I ₂ (i). The orthogonal component is Q ₁ (i)
-The common mode component of the replaced baseband signal r2 (i) is I ₁ (i), the orthogonal component is Q ₂ (i), and the common mode component of the replaced baseband signal r1 (i) is Q ₁ (i). The orthogonal component is I ₂ (i)
The in-phase component of the replaced baseband signal r2 (i) is Q ₂ (i), the orthogonal component is I ₁ (i), and the in-phase component of the replaced baseband signal r1 (i) is I ₂ (i). The orthogonal component is Q ₁ (i)
The in-phase component of the replaced baseband signal r2 (i) is Q ₂ (i), the orthogonal component is I ₁ (i), and the in-phase component of the replaced baseband signal r1 (i) is Q ₁ (i). The orthogonal component is I ₂ (i)
May be. Further, in the above, both signals are processed for the signals of two streams, and the replacement of the in-phase component and the orthogonal component of the signals after the signal processing of both is described, but the present invention is not limited to this and is more than two streams. It is also possible to perform both signal processing on the signal and replace the in-phase component and the orthogonal component of the signal after both signal processing.

Further, in the above example, the replacement of the baseband signals at the same time (same frequency ((sub) carrier)) is described, but the replacement of the baseband signals at the same time does not have to be performed. As an example, it can be described as follows: -The common mode component of the replaced baseband signal r1 (i) is I ₁ (i + v), the orthogonal component is Q ₂ (i + w), and the replaced baseband signal r2 ( The common mode component of i) is I ₂ (i + w), and the orthogonal component is Q ₁ (i + v).
-The common mode component of the baseband signal r1 (i) after replacement is I ₁ (i + v), and the orthogonal component is I ₂
(I + w), the common mode component of the baseband signal r2 (i) after replacement is Q ₁ (i + v), and the orthogonal component is Q ₂ (i + w).
-The common mode component of the baseband signal r1 (i) after replacement is I ₂ (i + w), and the orthogonal component is I ₁
(I + v), the common mode component of the baseband signal r2 (i) after replacement is Q ₁ (i + v), and the orthogonal component is Q ₂ (i + w).
-The common mode component of the baseband signal r1 (i) after replacement is I ₁ (i + v), and the orthogonal component is I ₂
(I + w), the common mode component of the baseband signal r2 (i) after replacement is Q ₂ (i + w), and the orthogonal component is Q ₁ (i + v).
-The common mode component of the baseband signal r1 (i) after replacement is I ₂ (i + w), and the orthogonal component is I ₁
(I + v), the common mode component of the baseband signal r2 (i) after replacement is Q ₂ (i + w), and the orthogonal component is Q ₁ (i + v).
The common mode component of the replaced baseband signal r1 (i) is I ₁ (i + v), the orthogonal component is Q ₂ (i + w), and the common mode component of the replaced baseband signal r2 (i) is Q ₁ (i + v). Orthogonal component is I ₂ (i + w)
The common mode component of the replaced baseband signal r1 (i) is Q ₂ (i + w), the orthogonal component is I ₁ (i + v), and the common mode component of the replaced baseband signal r2 (i) is I ₂ (i + w). The orthogonal component is Q ₁ (i + v)
The common mode component of the replaced baseband signal r1 (i) is Q ₂ (i + w), the orthogonal component is I ₁ (i + v), and the common mode component of the replaced baseband signal r2 (i) is Q ₁ (i + v). Orthogonal component is I ₂ (i + w)
-The common mode component of the baseband signal r2 (i) after replacement is I ₁ (i + v), and the orthogonal component is I ₂
(I + w), the common mode component of the baseband signal r1 (i) after replacement is Q ₁ (i + v), and the orthogonal component is Q ₂ (i + w).
-The common mode component of the baseband signal r2 (i) after replacement is I ₂ (i + w), and the orthogonal component is I ₁
(I + v), the common mode component of the baseband signal r1 (i) after replacement is Q ₁ (i + v), and the orthogonal component is Q ₂ (i + w).
-The common mode component of the baseband signal r2 (i) after replacement is I ₁ (i + v), and the orthogonal component is I ₂
(I + w), the common mode component of the replaced baseband signal r1 (i) is Q ₂ (i + w), and the orthogonal component is Q ₁ (i + v).
-The common mode component of the baseband signal r2 (i) after replacement is I ₂ (i + w), and the orthogonal component is I ₁
(I + v), the common mode component of the baseband signal r1 (i) after replacement is Q ₂ (i + w), and the orthogonal component is Q ₁ (i + v).
The common mode component of the replaced baseband signal r2 (i) is I ₁ (i + v), the orthogonal component is Q ₂ (i + w), and the common mode component of the replaced baseband signal r1 (i) is I ₂ (i + w). The orthogonal component is Q ₁ (i + v)
The common mode component of the replaced baseband signal r2 (i) is I ₁ (i + v), the orthogonal component is Q ₂ (i + w), and the common mode component of the replaced baseband signal r1 (i) is Q ₁ (i + v). Orthogonal component is I ₂ (i + w)
The common mode component of the replaced baseband signal r2 (i) is Q ₂ (i + w), the orthogonal component is I ₁ (i + v), and the common mode component of the replaced baseband signal r1 (i) is I ₂ (i + w). The orthogonal component is Q ₁ (i + v)
The common mode component of the replaced baseband signal r2 (i) is Q ₂ (i + w), the orthogonal component is I ₁ (i + v), and the common mode component of the replaced baseband signal r1 (i) is Q ₁ (i + v). Orthogonal component is I ₂ (i + w)
FIG. 55 is a diagram showing a baseband signal replacement unit 5502 for explaining the above description. As shown in FIG. 55, in the baseband signals z1 (i) 5501_1 and z2 (i) 5501_2 after both signal processing, the in-phase I component of the baseband signals z1 (i) 5501_1 after both signal processing is I ₁ . (I), the orthogonal component is Q ₁ (i), the in-phase I component of the baseband signal z2 (i) 5501_2 after both signal processing is I ₂ (i), and the orthogonal component is Q ₂ (i). Then, the in-phase component of the replaced baseband signal r1 (i) 5503_1 is I _r1 (i), the orthogonal component is Q _r1 (i), and the in-phase component of the replaced baseband signal r2 (i) 5503_1 is I _r2 ( i) If the orthogonal component is Q _r2 (i), the replaced baseband signal r1 (i) 5503_1 in-phase component I _r1 (i), the orthogonal component Q _r1 (i), and the replaced baseband signal r2 ( i) The in-phase component I _r2 (i) of 5503_2 and the orthogonal component Q _r2 (i) shall be represented by any of the above-mentioned ones. In this example, the replacement of the baseband signal after processing both signals at the same time (same frequency ((sub) carrier)) has been described, but as described above, different times (different frequency ((sub) carrier)) have been described. )) The baseband signal may be exchanged after processing both signals.

Both the transmitting antenna of the transmitting device and the receiving antenna of the receiving device, one antenna described in the drawings may be composed of a plurality of antennas.
In the present specification, "∀" represents a universal quantifier, and "∃" represents an existential quantifier.

Further, in the present specification, the unit of phase in the complex plane, for example, the argument angle, is referred to as "radian".
By using the complex plane, it can be displayed in polar format as a display in polar coordinates of complex numbers. Complex number
When a point (a, b) on the complex plane is associated with z = a + jb (both a and b are real numbers and j is an imaginary unit), this point is in polar coordinates [r, θ]. If it is expressed,
a = r × cos θ,
b = r × sinθ

Is true, r is the absolute value of z (r = | z |), and θ is the argument. And z = a + jb is expressed as re ^jθ .
In the description of the present invention, the baseband signals, s1, s2, z1, and z2 are complex signals, but the complex signal is I + jQ (when the in-phase signal is I and the orthogonal signal is Q, the complex signal is I + jQ ( j is an imaginary unit). At this time, I may be zero or Q may be zero.

FIG. 46 shows an example of a broadcasting system using the phase changing method described in the present specification. In FIG. 46, the video coding unit 4601 receives video as an input, performs video coding, and outputs data 4602 after video coding. The voice coding unit 4603 receives voice as an input, performs voice coding, and outputs data 4604 after voice coding. The data coding unit 4605 takes data as an input, encodes the data (for example, data compression), and outputs the data 4606 after the data coding. Collectively, these are referred to as an information source coding unit 4600.

The transmission unit 4607 receives data 4602 after video coding, data 4604 after audio coding, and data 4606 after data coding as inputs, and any one of these data or all of these data is used as transmission data. It performs processing such as error correction coding, modulation, precoding, and phase change (for example, signal processing in the transmission device of FIG. 3), and outputs transmission signals 4608_1 to 4608_N. Then, the transmission signals 4608_1 to 4608_N are transmitted as radio waves by the antennas 4609_1 to 4609_N, respectively.

The receiving unit 4612 receives the received signals 4611_1 to 4611_M received by the antennas 4610_1 to 4610_M as inputs, and performs processing such as frequency conversion, phase change, precoding decoding, log-likelihood ratio calculation, and error correction decoding (for example, FIG. 7). Processing in the receiving device) is performed, and the received data 4613, 4615, 4617 are output. The information source decoding unit 4619 receives the received data 4613, 4615, 4617 as inputs, and the video decoding unit 4614 receives the received data 4613 as an input, decodes for video, outputs a video signal, and outputs the video to the television. Displayed on the display. Further, the voice decoding unit 4616 receives the received data 4615 as an input. Decoding for audio is performed, an audio signal is output, and audio flows from a speaker. Further, the data decoding unit 4618 takes the received data 4617 as an input, decodes the data, and outputs the data information.

Further, in the embodiment in which the present invention is described, in the multi-carrier transmission system such as the OFDM system as described above, the number of encoders possessed by the transmitter is any number. You may. Therefore, for example, as shown in FIG. 4, it is naturally possible to apply the method in which the transmitting device includes one encoder and distributes the output to a multi-carrier transmission system such as an OFDM system. At this time, the wireless units 310A and 310B in FIG. 4 may be replaced with the OFDM method related processing units 1301A and 1301B in FIG. At this time, the description of the OFDM method-related processing unit is as in the first embodiment.

Further, in the first embodiment, the equation (36) is given as an example of the precoding matrix, but a method of using the following equation as the precoding matrix can be considered separately.

In the precoding equations (36) and (50), it is described that the equations (37) and (38) are set as the values of α, but the present invention is not limited to this, and α = 1. If set, it becomes a simple precoding matrix, so this value is also one of the valid values.

Further, in the embodiment A1, the phase change value for the period N in the phase change portions in FIGS. 3, 4, 6, 12, 25, 29, 51, and 53 (FIG. 3, FIG. 4, Fig. 6,
In FIGS. 12, 25, 29, 51, and 53, since the phase change is given only to one of the precoded baseband signals, the phase change value is used. ), PHASE [i] (i = 0,1,2, ..., N-2, N-1). Then, in the present specification, when the phase of one of the precoded baseband signals is changed (that is, FIG. 3, FIG. 4, FIG. 6, FIG. 12, FIG. 25, FIG. 29, FIG. 51, FIG. 53. ), FIG. 4, FIG. 6, FIG. 12, FIG. 25, FIG. 29, FIG. 51, and FIG. 53, the phase change is given only to the baseband signal z2'after precoding. At this time, PHASE [k] is given as follows.

At this time, k = 0,1,2, ..., N-2, N-1. Then, when N = 5, 7, 9, 11, 15 it is possible to obtain good data reception quality in the receiving device.
Further, in the present specification, the phase change method in the case of transmitting two modulation signals by a plurality of antennas has been described in detail, but the present invention is not limited to this, and the base in which three or more modulation methods are mapped is performed. The same can be applied to the case where the band signal is precoded and the phase is changed, the baseband signal after the precoding and the phase change is subjected to predetermined processing, and is transmitted from a plurality of antennas.

In addition, for example, a program for executing the above communication method is stored in ROM (Read Only) in advance.
It may be stored in Memory) and the program may be operated by a CPU (Central Processor Unit).

Further, a program for executing the above communication method is stored in a storage medium readable by a computer, the program stored in the storage medium is recorded in a RAM (Random Access Memory) of the computer, and the computer is operated according to the program. You may do so.

Then, each configuration such as each of the above-described embodiments may be realized as an LSI (Large Scale Integration), which is typically an integrated circuit. These may be individually integrated into one chip, or may be integrated into one chip so as to include all or a part of the configurations of each embodiment. Although it is referred to as an LSI here, it may be referred to as an IC (Integrated Circuit), a system LSI, a super LSI, or an ultra LSI depending on the degree of integration. Further, the method of making an integrated circuit is not limited to the LSI, and may be realized by a dedicated circuit or a general-purpose processor. An FPGA (Field Programmable Gate Array) that can be programmed after the LSI is manufactured, or a reconfigurable processor that can reconfigure the connection and settings of the circuit cells inside the LSI may be used.

Further, if an integrated circuit technology that replaces an LSI appears due to advances in semiconductor technology or another technology derived from it, it is naturally possible to integrate functional blocks using that technology. The application of biotechnology may be possible.

The present invention can be widely applied to a wireless system that transmits different modulated signals from a plurality of antennas, and is suitable for application to, for example, an OFDM-MIMO communication system. It also applies to the case of performing MIMO transmission in a wired communication system having a plurality of transmission points (for example, a PLC (Power Line Communication) system, an optical communication system, or a DSL (Digital Subscriber Line) system). At this time, a plurality of modulated signals as described in the present invention will be transmitted by using the plurality of transmission points. Further, the modulated signal may be transmitted from a plurality of transmission points.

302A, 302B Encoder 304A, 304B Interleaver 306A, 306B Mapping unit 314 Signal processing method Information generation unit 308A, 308B Weighted synthesizer 310A, 310B Radio unit 312A, 312B Antenna 317A, 317B Phase change unit 402 Encoder 404 Distributor 504 # 1,504 # 2 Transmit antenna 505 # 1,505 # 2 Receive antenna 600 Weighted synthesis unit 701_X, 701_Y Antenna 703_X, 703_Y Radio unit 705_1 Channel variation estimation unit 705_1 Channel variation estimation unit 707_1 Channel variation estimation unit 707_2 Channel variation estimation Unit 709 Control information decoding unit 711 Signal processing unit 803 INNER MIMO detection unit 805A, 805B Log likelihood calculation unit 807A, 807B Wireless 809A, 809B Log likelihood ratio calculation unit 811A, 811B Soft-in / soft-out decoder 813A, 813B Antenna 815 Storage unit 819 Coefficient generation unit 901 Soft-in / soft-out decoder 903 Distributor 1201A, 1201B OFDM method related processing unit 1302A, 1302A Serial parallel conversion unit 1304A, 1304B Sorting unit 1306A, 1306B Reverse high-speed Fourier conversion unit 1308A, 1308B Radio section

Claims (4)

It ’s a transmission method.
Where j is for a first modulation signal sequence s1 (j) containing a plurality of first modulation signals s1 and a second modulation signal sequence s2 (j) including a plurality of second modulation signals s2. For each pair of the first modulation signal s1 and the second modulation signal s2, which are index numbers of the first modulation signal and the second modulation signal and have the same index number,
Precoding processing for precoding the first modulation signal s1 and the second modulation signal s2, and
A phase change process for performing a phase change on at least one of the precoded signals, and a phase change process.
To generate a first transmission signal sequence z1 (j) including a plurality of first transmission signals z1 and a second transmission signal sequence z2 (j) including a plurality of second transmission signals z2.
The first transmission signal sequence z1 (j) and the second transmission signal sequence z2 (j) are transmitted by using a plurality of antennas.
In the precoding process, common precoding is applied to the first modulated signal sequence s1 (j) and the second modulated signal sequence s2 (j).
In the phase change processing, the phase change is performed by switching the phase change amount of N ways in the period N according to the index number, and the minimum value of the difference between the phase change amounts of the N ways is 2π /. N, the second phase change amount is used next to the first phase change amount, and the fourth phase change amount is used after the third phase change amount in the above N phase change amounts. When, the difference between the first phase change amount and the second phase change amount is not 2π / N, but the difference between the third phase change amount and the fourth phase change amount is 2π / N. can be,
The transmission method in which the first modulation signal and the second modulation signal are generated by using the same modulation method. It ’s a transmitter,
Where j is for a first modulation signal sequence s1 (j) containing a plurality of first modulation signals s1 and a second modulation signal sequence s2 (j) including a plurality of second modulation signals s2. For each pair of the first modulation signal s1 and the second modulation signal s2, which are index numbers of the first modulation signal and the second modulation signal and have the same index number,
Precoding processing for precoding the first modulation signal s1 and the second modulation signal s2, and
A phase change process for performing a phase change on at least one of the precoded signals, and a phase change process.
Is performed to generate a first transmission signal sequence z1 (j) including a plurality of first transmission signals z1 and a second transmission signal sequence z2 (j) including a plurality of second transmission signals z2. Department and
A transmission unit that transmits the first transmission signal sequence z1 (j) and the second transmission signal sequence z2 (j) using a plurality of antennas.
Equipped with
In the precoding process, common precoding is applied to the first modulated signal sequence s1 (j) and the second modulated signal sequence s2 (j).
In the phase change processing, the phase change is performed by switching the phase change amount of N ways in the period N according to the index number, and the minimum value of the difference between the phase change amounts of the N ways is 2π /. N, the second phase change amount is used next to the first phase change amount, and the fourth phase change amount is used after the third phase change amount in the above N phase change amounts. When, the difference between the first phase change amount and the second phase change amount is not 2π / N, but the difference between the third phase change amount and the fourth phase change amount is 2π / N. can be,
The first modulation signal and the second modulation signal are transmission devices generated by using the same modulation method. It ’s a receiving method.
The received signal is acquired, and the received signal is obtained by receiving the first transmission signal sequence z1 (j) and the second transmission signal sequence z2 (j) transmitted by using the plurality of antennas. The transmission signal sequence z1 (j) of 1 includes a plurality of first transmission signals z1, the second transmission signal sequence z2 (j) includes a plurality of second transmission signals z2, where j is the first transmission signal. The transmission signal of 1 and the index number of the second transmission signal, and the first transmission signal sequence z1 (j) and the second transmission signal sequence z2 (j) are a plurality of first modulation signals. The first modulated signal sequence s1 (j) including s1 and the second modulated signal sequence s2 (j) including a plurality of second modulated signals s2 are generated by performing predetermined signal processing.
The acquired received signal includes a process of performing demodulation processing according to the predetermined signal processing to generate received data.
The predetermined generation process is
A set of the first modulation signal s1 and the second modulation signal s2 having the same index number with respect to the first modulation signal sequence s1 (j) and the second modulation signal sequence s2 (j). Every time
Precoding processing for precoding the first modulation signal s1 and the second modulation signal s2, and
A phase change process for performing a phase change on at least one of the precoded signals, and a phase change process.
Including
In the precoding process, common precoding is applied to the first modulated signal sequence s1 (j) and the second modulated signal sequence s2 (j).
In the phase change processing, the phase change is performed by switching the phase change amount of N ways in the period N according to the index number, and the minimum value of the difference between the phase change amounts of the N ways is 2π /. N, the second phase change amount is used next to the first phase change amount, and the fourth phase change amount is used after the third phase change amount in the above N phase change amounts. When, the difference between the first phase change amount and the second phase change amount is not 2π / N, but the difference between the third phase change amount and the fourth phase change amount is 2π / N. can be,
The first modulation signal and the second modulation signal are reception methods generated by using the same modulation method. It ’s a receiver,
The received signal is acquired, and the received signal is obtained by receiving the first transmission signal sequence z1 (j) and the second transmission signal sequence z2 (j) transmitted by using the plurality of antennas. The transmission signal sequence z1 (j) of 1 includes a plurality of first transmission signals z1, the second transmission signal sequence z2 (j) includes a plurality of second transmission signals z2, where j is the first transmission signal. The transmission signal of 1 and the index number of the second transmission signal, and the first transmission signal sequence z1 (j) and the second transmission signal sequence z2 (j) are a plurality of first modulation signals. A first modulated signal sequence s1 (j) including s1 and a second modulated signal sequence s2 (j) including a plurality of second modulated signals s2 are generated by performing predetermined signal processing. Receiver and
A demodulation unit that generates received data by performing demodulation processing on the acquired received signal according to the predetermined signal processing.
Equipped with
The predetermined generation process is
A set of the first modulation signal s1 and the second modulation signal s2 having the same index number with respect to the first modulation signal sequence s1 (j) and the second modulation signal sequence s2 (j). Every time
Precoding processing for precoding the first modulation signal s1 and the second modulation signal s2, and
A phase change process for performing a phase change on at least one of the precoded signals, and a phase change process.
Including
In the precoding process, common precoding is applied to the first modulated signal sequence s1 (j) and the second modulated signal sequence s2 (j).
In the phase change processing, the phase change is performed by switching the phase change amount of N ways in the period N according to the index number, and the minimum value of the difference between the phase change amounts of the N ways is 2π /. N, the second phase change amount is used next to the first phase change amount, and the fourth phase change amount is used after the third phase change amount in the above N phase change amounts. When, the difference between the first phase change amount and the second phase change amount is not 2π / N, but the difference between the third phase change amount and the fourth phase change amount is 2π / N. can be,
The first modulation signal and the second modulation signal are a receiving device generated by using the same modulation method.

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