JP2022080945A - Control device for ac rotating machine - Google Patents

Abstract

To provide a control device for an AC rotating machine capable of improving the accuracy of setting the timing at which synchronous rectification is performed on variation of in rotational speed or behavior in winding current when alternator power generation is executed every control cycle.SOLUTION: In a control device for an AC rotating machine, alternator power generation control for switching a zero-on mode, a high-on mode, and a low-on mode by comparing a detection value and a determination value of a winding current is executed for each phase when power is generated with an induced voltage, and the determination value is set based on a margin time set according to a rotational angular velocity, the amplitude of current, and a delay time that occurs in switching.SELECTED DRAWING: Figure 2

Description

The present application relates to a control device for an AC rotary machine.

The induced voltage generated in the armature winding of the stator improves power generation efficiency by turning on the switching element in which the diode through which the current flows is connected in anti-parallel when the AC rotating machine and the inverter generate rectified power. , A technique for controlling alternator power generation to reduce heat generation of an element is known.

In the technique of Patent Document 1, a control circuit detects a zero-crossing time point in which the winding current of each phase crosses 0A, and the switching element is turned on or off based on the zero-crossing time point.

In the technique of Patent Document 2, the time during which synchronous rectification is possible is obtained from the conduction time of the diode for each cycle of AC power, and the timing for turning on and off the switching element on the high potential side and the low potential side is determined.

Japanese Unexamined Patent Publication No. 2011-135695 Japanese Unexamined Patent Publication No. 2009-284564

However, in the technique of Patent Document 1, the control circuit continuously detects the zero crossing time point when the current crosses 0A, and the switching element is turned on or off based on the zero crossing time point. Therefore, the alternator is used for each control cycle. The effect of delay due to the control cycle that occurs in the control device that generates power is not taken into consideration. Further, in the technique of Patent Document 1, since the influence of the delay due to the control cycle is not considered, it is not considered to change the threshold value for determining the zero cross time point from 0A. Further, since it is necessary to mount a control circuit, it is difficult to miniaturize the vehicle generator because the mounting area increases as the number of phases of the armature winding increases.

In the technique of Patent Document 2, if the rotation speed is constant, it is possible to perform a desired operation at the timing of turning on and off the switching element determined for each cycle of AC power. However, when the rotation speed fluctuates, the switching element turns on and the current is disturbed in the section where diode rectification should be performed, or the switching element turns off and the calorific value increases in the section where synchronous rectification can be performed. .. Further, in a generator motor having a field winding in the rotor, the field magnetic flux changes due to a change in the field current. When the field magnetic flux changes, the induced voltage changes and the amplitude of the winding current changes. Therefore, it is difficult to respond to the change in the behavior of the winding current by the determination for each cycle of the alternating current.

Therefore, in the present application, when the alternator power generation is executed for each control cycle, it is possible to improve the setting accuracy of the timing for performing synchronous rectification with respect to the fluctuation of the rotation speed or the behavior of the winding current. The purpose is to provide a control device for the machine.

The control device for an AC rotary machine according to the present application is a control device for an AC rotary machine that controls an AC rotary machine provided with a rotor and a stator having a multi-phase armature winding via an inverter.
In the inverter, for each phase, a switching element on the high potential side connected to the high potential side of the DC power supply and a switching element on the low potential side connected to the low potential side of the DC power supply are connected in series and connected in series. The connection point is provided with a series circuit connected to the armature winding of the corresponding phase, and the switching element has the function of a diode connected in antiparallel.
The control device for the AC rotary machine is
A zero-on mode in which the switching elements on the high-potential side and the low-potential side are turned off for each phase when the AC rotator is made to generate power by the induced voltage generated in the armature windings of a plurality of phases, and high. A high-on mode in which the switching element on the potential side is turned on and the switching element on the low potential side is turned off, and a low-on mode in which the switching element on the high potential side is turned off and the switching element on the low potential side is turned on. Is switched by comparing the detected value and the determined value of the current flowing through the armature winding, and the alternator power generation control is executed.
The determination value is set based on the rotational angular velocity of the AC rotary machine, the amplitude of the current flowing through the armature winding, and the margin time set corresponding to the delay time generated in the switching.

According to the control device of the AC rotary machine according to the present application, the detection value of the winding current and the determination value are compared to determine the mode switching, and the switching element is turned on / off based on the determination result until the mode is switched. There is a delay time between. Depending on the delay time generated in this switching, the state of the winding current changes between the time when the winding current is detected and the time when the mode is switched based on the determination result. Therefore, it is required to set the determination value in consideration of the change in the winding current during the delay time. The behavior of the winding current changes according to the rotational angular velocity and the amplitude of the winding current. According to the control device of the AC rotary machine according to the present application, the determination value is set based on the rotation angular velocity, the amplitude of the winding current, and the margin time set corresponding to the delay time generated in the switching, and thus the delay. The judgment value can be set in consideration of the change in the winding current over time, and the mode can be appropriately switched. Therefore, it is possible to improve the setting accuracy of the timing for performing each mode with respect to the fluctuation of the rotation speed or the behavior of the winding current.

It is a schematic block diagram of the AC rotary machine and the control device of the AC rotary machine which concerns on Embodiment 1. FIG. It is a schematic block diagram of the control device which concerns on Embodiment 1. FIG. It is a hardware block diagram of the control device which concerns on Embodiment 1. FIG. It is a time chart explaining the control timing at the time of execution of the inverter control which concerns on Embodiment 1. FIG. It is a time chart explaining the behavior of the winding current at the time of execution of the alternator power generation control which concerns on Embodiment 1. FIG. It is a figure explaining the current behavior of the inverter at the time t2a of FIG. 5 which concerns on Embodiment 1. FIG. It is a time chart explaining the control timing at the time of execution of the alternator power generation control which concerns on Embodiment 1. FIG. It is a flowchart explaining the mode switching determination process which concerns on Embodiment 1. It is a time chart explaining the behavior of the winding current at the time of execution of the alternator power generation control which concerns on Embodiment 1. FIG. It is a time chart explaining the control timing at the time of execution of the alternator power generation control which concerns on Embodiment 1. FIG. It is a schematic diagram of the AC rotary machine which was made into the generator motor for the vehicle which concerns on Embodiment 1. FIG. It is a time chart explaining the on / off control behavior of the switching element of the converter which concerns on Embodiment 1. FIG. It is a flowchart explaining the mode switching determination process which concerns on Embodiment 2.

1. 1. Embodiment 1
The control device 11 (hereinafter, simply referred to as the control device 11) of the AC rotary machine according to the first embodiment will be described with reference to the drawings. FIG. 1 is a schematic configuration diagram of an AC rotary machine 1, an inverter 5, and a control device 11 according to the present embodiment.

1-1. AC rotary machine 1
The AC rotating machine 1 includes a stator 18 and a rotor 14 arranged radially inside the stator 18. The AC rotating machine 1 is a field winding type synchronous rotating machine. A plurality of phase armature windings 12 are wound around the iron core of the stator 18. A field winding 4 is wound around the iron core of the rotor 14, and an electromagnet is provided.

In the present embodiment, the plurality of phase armature windings 12 are U-phase, V-phase, and W-phase three-phase armature windings Cu, Cv, and Cw. The three-phase armature windings Cu, Cv, and Cw may be star-connected or delta-connected.

The rotor 14 is provided with a rotation sensor 15 that detects the rotation angle (rotation angle) of the rotor 14. The output signal of the rotation sensor 15 is input to the control device 11. As the rotation sensor 15, various sensors such as a Hall element, a resolver, or an encoder are used. The rotation sensor 15 may not be provided, and may be configured to estimate the rotation angle (pole position) based on the current information obtained by superimposing the harmonic component on the current command value described later (so-called). Sensorless method).

1-2. DC power supply 2
The DC power supply 2 outputs a DC voltage Vdc to the inverter 5 and the converter 9. As the DC power supply 2, any device that outputs a DC voltage, such as a battery, a DC-DC converter, a diode rectifier, and a PWM rectifier, is used. A smoothing capacitor 3 is connected in parallel to the DC power supply 2.

1-3. Inverter 5
The inverter 5 has a plurality of switching elements and performs power conversion between the DC power supply 2 and the armature winding 12. In the inverter 5, for each phase, the switching element SP on the high potential side connected to the high potential side of the DC power supply 2 and the switching element SN on the low potential side connected to the low potential side of the DC power supply 2 are connected in series. A connected series circuit is provided. The connection points of the two switching elements in each series circuit are connected to the armature windings of the corresponding phase. Three sets of series circuits are provided corresponding to the armature windings of each of the three phases.

Specifically, in the U-phase series circuit, the switching element SPu on the high potential side of the U phase and the switching element SNu on the low potential side of the U phase are connected in series, and the connection points of the two switching elements SPu and SNu are connected. It is connected to the U-phase armature winding Cu. In the V-phase series circuit, the switching element SPv on the high potential side of the V phase and the switching element SNv on the low potential side of the V phase are connected in series, and the connection point of the two switching elements SPv and SNv is a V-phase armature. It is connected to the winding Cv. In the W-phase series circuit, the switching element SPw on the high potential side of W and the switching element SNw on the low potential side of W phase are connected in series, and the connection point of the two switching elements SPw and SNw is a W-phase armature winding. It is connected to the line Cw.

Each switching element of the inverter 5 has the function of a diode connected in antiparallel. For example, each switching element has an IGBT (Insulated Gate Bipolar Transistor) in which diodes are connected in anti-parallel connection, a bipolar transistor in which diodes are connected in anti-parallel connection, and a MOSFET (Metal Oxide Semiconductor Field Effect Transistor) having a parasitic diode connected in anti-parallel connection. ) Etc. are used. The gate terminal of each switching element is connected to the control device 11 via a gate drive circuit or the like. Therefore, each switching element is turned on or off by the switching signal output from the control device 11.

The armature current sensor 8 is a current detection circuit that detects the current flowing through the armature windings Cu, Cv, and Cw of each phase. In the present embodiment, the armature current sensor 8 is provided on the electric wire connecting the series circuit of the switching element of each phase and the armature winding. The output signal of the armature current sensor 8 of each phase is input to the control device 11. The armature current sensor 8 is a current sensor such as a Hall element and a shunt resistor. The armature current sensor 8 may be connected in series to the series circuit of the switching element of each phase.

1-4. Converter 9
The converter 9 has a switching element and performs power conversion between the DC power supply 2 and the field winding 4. In the present embodiment, in the converter 9, the switching element SP on the high potential side connected to the high potential side of the DC power supply 2 and the switching element SN on the low potential side connected to the low potential side of the DC power supply 2 are connected in series. It is an H-bridge circuit provided with two sets of connected series circuits. The connection point between the switching element SP1 on the high potential side and the switching element SN1 on the low potential side in the series circuit 28 of the first set is connected to one end of the field winding 4, and the high potential in the series circuit 29 of the second set. The connection point between the switching element SP2 on the side and the switching element SN2 on the low potential side is connected to the other end of the field winding 4.

As the switching element of the converter 9, an IGBT in which diodes are connected in antiparallel, a bipolar transistor in which diodes are connected in antiparallel, a MOSFET, and the like are used. The gate terminal of each switching element is connected to the control device 11 via a gate drive circuit or the like. Therefore, each switching element is turned on or off by the switching signal output from the control device 11.

In addition, the converter 9 is replaced with a diode, the switching element SN1 on the low potential side of the series circuit 28 of the first set is replaced with a diode, the switching element SP2 on the high potential side of the series circuit 29 of the second set is replaced with a diode, and the like. It may be configured as.

The field current sensor 6 is a current detection circuit that detects the field current if, which is the current flowing through the field winding 4. In the present embodiment, the field current sensor 6 is provided on an electric wire connecting the field winding 4 and the converter 9. The field current sensor 6 may be provided at another location where the field current if can be detected. The output signal of the field current sensor 6 is input to the control device 11. The field current sensor 6 is a current sensor such as a Hall element and a shunt resistance.

1-5. Control device 11
The control device 11 controls the AC rotary machine 1 via the inverter 5 and the converter 9. As shown in FIG. 2, the control device 11 has functions such as a rotation detection unit 31, an armature current detection unit 32, an armature winding control unit 33, a field current detection unit 34, and a field winding control unit 35. It has a part. Each function of the control device 11 is realized by the processing circuit provided in the control device 11. Specifically, as shown in FIG. 3, the control device 11 has, as a processing circuit, an arithmetic processing unit 90 (computer) such as a CPU (Central Processing Unit), a storage device 91 for exchanging data with the arithmetic processing unit 90, and the like. The arithmetic processing unit 90 includes an input circuit 92 for inputting an external signal, an output circuit 93 for outputting a signal from the arithmetic processing unit 90 to the outside, a communication circuit 94 for data communication with the external device, and the like.

The arithmetic processing device 90 is provided with an ASIC (Application Specific Integrated Circuit), an IC (Integrated Circuit), a DSP (Digital Signal Processor), an FPGA (Field Programmable Gate Array), various logic circuits, various signal processing circuits, and the like. You may. Further, the arithmetic processing apparatus 90 may be provided with a plurality of the same type or different types, and each processing may be shared and executed. As the storage device 91, a RAM (Random Access Memory) configured to be able to read and write data from the arithmetic processing device 90, a ROM (Read Only Memory) configured to be able to read data from the arithmetic processing device 90, and the like are used. It is prepared. The input circuit 92 is connected to various sensors and switches such as a rotation sensor 15, an armature current sensor 8, and a field current sensor 6, and A / D conversion in which the output signals of these sensors and switches are input to the arithmetic processing device 90. Equipped with vessels, etc. The output circuit 93 includes a drive circuit or the like to which an electric load such as a gate drive circuit for driving the switching elements of the inverter 5 and the converter 9 on and off is connected, and a control signal is output from the arithmetic processing device 90 to these electric loads. The communication circuit 94 communicates with an external device.

Then, in each function of the control units 31 to 35 included in the control device 11, the arithmetic processing device 90 executes software (program) stored in the storage device 91 such as a ROM, and the storage device 91 and the input circuit 92. , And by cooperating with other hardware of the control device 11 such as the output circuit 93. The setting data such as the control cycle, the margin time, and the determination value used by the control units 31 to 35 and the like are stored in the storage device 91 such as ROM as a part of the software (program). Hereinafter, each function of the control device 11 will be described in detail.

The rotation detection unit 31 detects the rotor magnetic pole position θ (rotor rotation angle θ) and the rotation angular velocity ω at the electric angle. In the present embodiment, the rotation detection unit 31 detects the magnetic pole position θ (rotation angle θ) and the rotation angular velocity ω of the rotor based on the output signal of the rotation sensor 15. The magnetic pole position is set in the direction of the north pole of the electromagnet provided in the rotor. The rotation detection unit 31 is configured to estimate the rotation angle (pole position) based on the current information obtained by superimposing the harmonic component on the current command value without using the rotation sensor. It is also good (so-called sensorless method).

The armature current detection unit 32 detects the winding currents ius, ivs, and iws flowing through the three-phase armature windings based on the output signal of the armature current sensor 8. Here, ius is the detected value of the U-phase winding current iu, ivs is the detected value of the V-phase winding current iv, and iws is the detected value of the W-phase winding current iv. .. The armature current sensor 8 may be configured to detect the two-phase winding current, and the remaining one-phase winding current may be calculated based on the detected value of the two-phase winding current. For example, the armature current sensor 8 may detect the winding currents ivs and iws of the V phase and the W phase, and the winding current ius of the U phase may be calculated by is = −ivs-iws.

1-5-1. Armature winding control unit 33
The armature winding control unit 33 includes an inverter control unit 331 that performs inverter control described later, an alternator power generation control unit 332 that performs alternator power generation control described later, and a control switching unit 333 that switches between inverter control and alternator power generation control. And, it has.

1-5-1-1. Control switching unit 333
The control switching unit 333 determines whether to execute the inverter control or the alternator power generation control, and switches between the inverter control and the alternator power generation control. For example, the control switching unit 333 determines that the inverter power generation control is executed when the command of the power generation control by the induced voltage is transmitted from the external control device, and executes the alternator power generation control to the alternator power generation control unit 332. Each switching signal commanded and generated by the alternator power generation control unit 332 is input to the gate terminal of each switching element of the inverter 5 via the gate drive circuit, and each switching element is turned on or off.

The control switching unit 333 determines that the inverter control is executed when the inverter control command is transmitted from the external control device, commands the inverter control unit 331 to execute the inverter control, and the inverter control unit 331 orders the inverter control unit 331 to execute the inverter control. Each generated switching signal is input to the gate terminal of each switching element of the inverter 5 via the gate drive circuit, and each switching element is turned on or off.

1-5-1-2. Inverter control unit 331
The inverter control unit 331 executes inverter control for turning on and off a plurality of switching elements by PWM control (Pulse Width Modulation) in the first control cycle Tc1 based on the voltage command value.

In the present embodiment, as shown in FIG. 2, the inverter control unit 331 includes a current coordinate conversion unit 331a, a current command value calculation unit 331b, a voltage command value calculation unit 331c, a voltage coordinate conversion unit 331d, and a PWM control unit 331e. It is equipped with.

The current coordinate conversion unit 331a converts the three-phase winding current detection values ius, ivs, and iws into d-axis current detection values ids and q-axis current detection values iqs on the d-axis and q-axis rotating coordinate systems. Convert. The rotation coordinate system of the d-axis and the q-axis is a two-axis rotation coordinate consisting of the d-axis determined in the direction of the detected magnetic pole position θ and the q-axis defined in the direction advanced by 90 ° in the electric angle from the d-axis. It rotates in synchronization with the rotation of the magnetic pole position θ of the rotor. Specifically, the armature current detection unit 32 performs three-phase two-phase conversion and rotational coordinate conversion on the three-phase winding current detection values ius, ivs, and iws based on the magnetic pole position θ, and performs d-axis. It is converted into the detected value ids of the current and the detected value iqs of the q-axis current.

The current command value calculation unit 331b calculates the current command value. In the present embodiment, the current command value calculation unit 331b calculates the current command value ido on the d-axis and the current command value iqo on the q-axis. For example, the current command value calculation unit 331b calculates the current command values ido and iqo of the d-axis and the q-axis based on the torque command value To, the rotational angular velocity ω, and the DC voltage Vdc.

The voltage command value calculation unit 331c calculates the voltage command value based on the detection value of the winding current and the current command value. For example, the voltage command value calculation unit 331c changes the voltage command value so that the detected value of the winding current approaches the current command value. For example, the voltage command value calculation unit 331c is proportionally integrated so that the detected value ids of the d-axis current approaches the current command value ido of the d-axis and the detected value iqs of the q-axis current approaches the current command value iqo of the q-axis. Control and the like are performed to execute feedback control for calculating the voltage command value Vdo on the d-axis and the voltage command value Vqo on the q-axis. Further, a known feedforward control for non-interference between the d-axis current and the q-axis current may be performed.

Alternatively, the voltage command value calculation unit 331c uses the electrical constants of the AC rotating machine based on the current command values of the d-axis and the q-axis without using the detected value of the winding current, and the voltage of the d-axis and the q-axis. Feed forward control that changes the command value may be executed. In addition, one or both of feedback control and feedforward control may be performed.

The voltage coordinate conversion unit 331d performs fixed coordinate conversion and two-phase three-phase conversion on the d-axis and q-axis voltage command values Vdo and Vqo based on the magnetic pole position θ, and performs three-phase voltage command values Vuo and Vvo. , Convert to Vwo. The voltage coordinate conversion unit 331d may apply modulation such as two-phase modulation and space vector modulation so that the line voltage does not change with respect to the three-phase voltage command value.

The PWM control unit 331e controls on / off of a plurality of switching elements of the inverter 5 by PWM control in the first control cycle Tc1 based on the voltage command value. In the present embodiment, as shown in FIG. 4, the PWM control unit 331e compares each of the three-phase voltage command values Vuo, Vvo, and Vwo with the carrier signal C1 vibrating in the first control cycle Tc1. , Controls on / off of multiple switching elements. The carrier signal C1 is a triangular wave that oscillates with an amplitude of Vdc / 2, which is half the power supply voltage, centered on 0 in the first control cycle Tc1. The DC voltage Vdc may be detected by a voltage sensor.

When the carrier signal C1 falls below the voltage command value for each phase, the PWM control unit 331e turns on the switching signal QP of the switching element on the high potential side (1 in this example) to switch on the high potential side. When the element is turned on and the carrier signal C1 exceeds the voltage command value, the switching signal QP of the switching element on the high potential side is turned off (0 in this example), and the switching element on the high potential side is turned off. On the other hand, when the carrier signal C1 falls below the voltage command value for each phase, the PWM control unit 331e turns off the switching signal QN of the switching element on the low potential side (0 in this example) to turn off the switching signal QN on the low potential side. When the switching element of the low potential side is turned off, the switching element on the low potential side is turned off, and the carrier signal C1 exceeds the voltage command value, the switching signal QN of the switching element on the low potential side is turned on (1 in this example). Then, the switching element on the low potential side is turned on. For each phase, between the on period of the switching element on the high potential side and the on period of the switching element on the low potential side, a short circuit prevention period in which both the switching element on the high potential side and the switching element on the low potential side are turned off. (Dead time) may be provided.

As shown in FIG. 4, when the inverter control is executed, the three-phase winding currents us, ivs, and iws are detected at the peak of the carrier signal C1 that vibrates in the first control cycle Tc1. After the winding current is detected, each part of the inverter control unit 331 performs calculation processing of the three-phase voltage command values Vuo, Vvo, and Vwo based on the detected value of the winding current, and the next carrier signal C1 valley At the apex, the three-phase voltage command values Vuo, Vvo, and Vwo are updated and reflected in the PWM control. If the calculation process of the voltage command value is not completed by the apex of the valley of the next carrier signal C1, the voltage command value may be updated at the apex of the valley of the next carrier signal C1.

The first control cycle Tc1 may be set to be equal to or less than the maximum value of the control cycle that allows the component of the first control cycle included in the current ripple at the maximum rotation speed at which the inverter control is executed. For example, the first control cycle Tc1 is set to the reciprocal of 10 kHz.

1-5-1-3. Alter power generation control unit 332
1-5-1-3-1. Issues of alternator power generation <Power generation by induced voltage>
With all switching elements of the inverter 5 turned off, when the induced voltage of the armature winding generated by the rotation of the rotor exceeds the voltage on the high potential side of the DC power supply for each phase, DC is applied from the armature winding. A current flows on the high potential side of the power supply through the antiparallel diode of the switching element on the high potential side. On the other hand, when the induced voltage of the armature winding falls below the voltage on the low potential side of the DC power supply, a current flows from the low potential side of the DC power supply to the armature winding through the antiparallel diode of the switching element on the low potential side. Flows. In this way, when the induced voltage of the armature winding generated by rotation exceeds the voltage on the high potential side of the DC power supply and falls below the voltage on the low potential side of the DC power supply, the inverter 5 functions as a rectifier. The AC power generated by the AC rotating machine is rectified into DC power and supplied to the DC power supply. That is, the AC rotating machine generates electricity by the induced voltage generated in the three-phase armature winding. Such rectification by a diode is called diode rectification.

<Synchronous rectification>
When a current flows through a diode, the amount of heat generated increases because the power loss is large. Therefore, if the switching element of the diode is turned on when the current flows through the diode due to the induced voltage, the current flows through the switching element instead of the diode, so that the power loss can be reduced and the calorific value can be reduced. Rectification that turns on such a switching element is called synchronous rectification.

For example, FIG. 5 shows the three-phase winding currents iu, iv, and iwa flowing through the three-phase armature winding during power generation by the induced voltage. FIG. 5 shows a waveform of only the first-order electrical angle component for the sake of simplicity, but the same can be said even if a harmonic component such as the fifth-order component is included.

<Synchronous rectification according to winding current>
At the time t2a of FIG. 5, the current flows in the inverter 5 as shown in FIG. At time t2a, the winding current of the U phase is positive, and when synchronous rectification is not performed, the current flows through the diode on the low potential side of the U phase, so the switching element SNu on the low potential side of the U phase should be turned on. Therefore, the calorific value can be reduced. Similarly, at time t2a, the V-phase current is negative and the current flows through the diode on the high-potential side of the V-phase. Therefore, by turning on the switching element SPv on the high-potential side of the V-phase, the calorific value is reduced. do. At time t2a, the W phase current is positive and the current flows through the diode on the low potential side of the W phase. Therefore, the calorific value is reduced by turning on the switching element SNw on the low potential side of the W phase. Therefore, in synchronous rectification, when the winding current generated by the induced voltage is negative for each phase, the switching element SP on the high potential side is turned on, the switching element SN on the low potential side is turned off, and the winding current is changed. When positive, the switching element SP on the high potential side is turned off, and the switching element SN on the low potential side is turned on.

<Implementation of diode rectification near 0A>
On the other hand, at the time t6a in FIG. 5, the winding current iw of the W phase is a negative value, but is near 0A. Since the detection value iws of the winding current of the W phase includes a detection error, the detected value iws of the winding current may be a positive value even if the winding current iw is a negative value. If the switching element on the opposite side where the diode is not energized is erroneously turned on, a current flows through the switching element on the opposite side which is erroneously turned on, the current is disturbed, and the power generation efficiency is lowered. Further, in the vicinity of 0A, the calorific value does not increase even if a current flows through the diode. Therefore, in consideration of the current detection error, in the vicinity of 0A, both the switching element on the high potential side and the switching element on the low potential side are turned off to perform diode rectification so that the switching element on the opposite side is not accidentally turned on. Is possible.

Further, in Patent Document 1, since the zero crossing time point at which the current crosses 0A is continuously detected and the switching element is turned on or off based on the zero crossing time point, the influence of the delay due to the control cycle is not taken into consideration. .. However, in the present embodiment, as will be described later, the current is detected every second control cycle Tc2 and the switching element is turned on or off. The switching element on the opposite side may be turned on. Therefore, in consideration of the delay due to the control cycle, in the vicinity of 0A, both the switching element on the high potential side and the switching element on the low potential side are turned off to perform diode rectification so that the switching element on the opposite side is not accidentally turned on. Is possible.

1-5-1-3-2. Alter power generation control Therefore, when the alternator power generation control unit 332 causes the AC rotator to generate power by the induced voltage generated in the three-phase armature winding, the zero-on mode, high-on mode, and low-on mode are used for each phase. The switching with is determined for each second control cycle Tc2, and the alternator power generation control for switching is executed. The zero-on mode is a mode in which the switching element on the high potential side and the switching element on the low potential side are turned off. The hion mode is a mode in which the switching element on the high potential side is turned on and the switching element on the low potential side is turned off. The low-on mode is a mode in which the switching element on the high potential side is turned off and the switching element on the low potential side is turned on.

According to this configuration, since both the high-potential side and low-potential side switching elements are switched to the zero-on mode, even if a current detection error and a delay due to the control cycle occur, an error occurs near 0A. Therefore, it is possible to suppress the switching element on the opposite side where the diode is not energized from being turned on, and to suppress the decrease in power generation efficiency.

<Control timing>
As shown in FIG. 7, when the alternator power generation control is executed, the three-phase winding currents ius, ivs, and iws are detected at the peak of the carrier signal C2 of the triangular wave oscillating in the second control cycle Tc2. After the winding current is detected, switching determination processing of zero-on mode, high-on mode, and low-on mode is performed based on the detected value of the winding current of each phase, and switching is performed at the apex of the valley of the next carrier signal C2. Based on the determination result of, the on or off setting of the switching signal of each switching element is updated, and the updated on or off setting is held until the apex of the valley of the next next carrier signal C2. That is, the switching signal set based on the detected value of the winding current at the peak of the peak of the carrier signal C2 is held from the top of the valley of the next carrier signal C2 to the top of the valley of the next next carrier signal C2. Will be done.

<Switching judgment by comparing the detected value of winding current and the judgment value>
The alternator power generation control unit 332 determines switching between the zero-on mode, the high-on mode, and the low-on mode by comparing the detected value and the determination value of the winding current of the armature winding for each phase. The alternator power generation control unit 332 sets the determination value for each phase based on the rotation angular velocity ω, the amplitude I of the current flowing through the armature winding, and the margin time Tmg set corresponding to the delay time generated in the switching. do.

The detection value of the winding current and the determination value are compared to determine the mode switching, the switching element is turned on and off based on the determination result, and a delay time occurs until the mode is switched. Depending on the delay time generated in this switching, the state of the winding current changes between the time when the winding current is detected and the time when the mode is switched based on the determination result. Therefore, it is required to set the determination value in consideration of the change in the winding current during the delay time. The behavior of the winding current changes according to the rotation angular velocity ω and the current amplitude I. According to the above configuration, the determination value is set based on the rotation angular velocity ω, the current amplitude I, and the margin time Tmg set corresponding to the delay time generated in the switching, so that the winding during the delay time is set. The judgment value can be set in consideration of the change in the current, and the mode can be appropriately switched.

In the present embodiment, the alternator power generation control unit 332 sets the high-on determination value IsH and the low-on determination value IsL based on the rotation angular velocity ω, the amplitude I of the current flowing through the armature winding, and the margin time Tmg. Then, the alternator power generation control unit 332 determines that the armature winding is switched to the low-on mode when the detected value of the winding current of the armature winding is equal to or higher than the low-on determination value IsL for each phase. When the detected value of the winding current is equal to or less than the high-on judgment value IsH, it is determined to switch to the high-on mode, and the detected value of the armature winding winding current is smaller than the low-on judgment value IsL and the high-on judgment value. If it is larger than IsH, it is determined to switch to the zero-on mode.

According to this configuration, for each phase, when the detected value of the winding current of the armature winding is within the range from the high-on determination value IsH to the low-on determination value IsL, the zero-on mode is set and diode rectification is performed. Therefore, even if a current detection error and a delay due to the control cycle occur, it is possible to prevent the switching element on the opposite side where the diode is not energized from being accidentally turned on near 0A, and the power generation efficiency is improved. It is possible to suppress the decrease.

This switching determination process can be configured as shown in the flowchart shown in FIG. The determination process of FIG. 8 is executed for each phase after the winding currents of the three phases are detected. In step S130, the alternator power generation control unit 332 determines whether or not the detected value of the winding current is the low-on determination value IsL or more, and if it is the low-on determination value IsL or more, proceeds to step S132 and proceeds to the low-on mode. If it is determined to switch to, and the row-on determination value is not equal to or greater than IsL, the process proceeds to step S131. In step S131, the alternator power generation control unit 332 determines whether or not the detected value of the winding current is the high-on determination value IsH or less, and if it is the high-on determination value IsH or less, the process proceeds to step S133 to enter the high-on mode. It is determined to switch, and if it is not equal to or less than the high-on determination value IsH, the process proceeds to step S134, and it is determined to switch to the zero-on mode. The determination result of each phase is reflected in the setting of the switching signal at the apex of the valley of the next carrier signal C2.

<Alternative to dead time with zero-on mode>
Here, in each phase, when switching from the low-on mode to the high-on mode and when switching from the high-on mode to the low-on mode, the switching element on the high potential side and the switching element on the low potential side should not be turned on at the same time. It is necessary to consider providing a dead time for turning off both the switching element on the high potential side and the switching element on the low potential side. This dead time is the same as the zero-on mode. According to the switching determination process based on the detection value of the winding current described above, the zero-on mode is switched between the high-on mode and the low-on mode, which is a substitute for the dead time.

The alternator power generation control unit 332 switches from the zero-on mode to the high-on mode or the low-on mode, and switches from the high-on mode or the low-on mode to the zero-on mode, but switches from the high-on mode to the low-on mode and low. It is configured not to switch from on mode to high on mode.

<Effect of delay due to control cycle>
FIG. 9 is an enlarged view of the vicinity of time t1a to time t6a in FIG. The switching signal determined based on the detected value of the winding current detected at the time t4a is output between the time t5a and the time t7a. Therefore, it is necessary that the current state corresponding to the mode determined by the detected value of the winding current at time t4a and the actual current state between time t5a and time t7a match. That is, it is necessary to anticipate the state of the current between the time t5a and the time t7a and determine the mode based on the detected value of the winding current at the time t4a.

For example, the detected value iws of the winding current of the W phase is a positive value at time t4a, but the current iw of the W phase changes from a positive value to a negative value between the time t5a and the time t7a. In the low-on mode, there will be a period during which the switching element on the opposite side is turned on, and it is necessary to set the zero-on mode. Therefore, the detected value iws of the winding current of the W phase is a positive value at time t4a, but the low-on determination value ItL is set to 0 by the change in current so that it is determined in the zero-on mode instead of the low-on mode. Must be set higher than.

<Setting of IsL and IsH>
Therefore, it is necessary to set the low-on determination value IsL and the high-on determination value IsH in consideration of the influence of the delay due to the control cycle, and the settings will be described below. As described above, the on / off period of the switching element based on the switching determination result based on the current winding current detection value is from the on / off time point based on the current winding current detection value to the on / off time point based on the next winding current detection value. It will be a period until. Therefore, as shown in FIG. 7, the longest delay time due to the control cycle is determined based on the switching determination result determined based on the detection value of the winding current detected from the current current detection time point to the next current detection time point. It is a period until the time when the switching element is turned on and off, and this period is defined as the next on / off time Tnxt. Therefore, the low-on determination value IsL and the high-on determination value IsH may be set so that the state of the winding current at the next on / off time Tnxt destination and the state of the current corresponding to the determined mode match. For that purpose, the low-on determination value IsL and the high-on determination value IsH may be set based on the winding current at the time point corresponding to the next on / off time Tnxt as the margin time Tmg before the time when the winding current becomes 0. .. The set values will be described below.

The period from the current current detection time to the time when the switching element is turned on / off based on the switching judgment result determined based on the winding current detection value detected at the current current detection time is defined as the on / off delay time Tdry. do. The next on / off time Tnxt becomes the on / off delay time Tdry + the second control cycle Tc2 (Tnxt = Tdry + Tc2). The on / off delay time Tdry is a half cycle Tc2 / 2 of the second control cycle.

The three-phase winding currents iu, iv, and iwa are approximately given by Eq. (1), where I is the current amplitude and ω is the rotational angular velocity.

The winding current (hereinafter referred to as the winding current value before the next on / off time) at a time point equal to the next on / off time Tnxt before the time when the winding current becomes 0 is given by the following equation. Here, in the following equation, in order to consider the case where the current is decreasing at the time when the winding current becomes 0 mainly for setting the low-on determination value IsL, the case where the phase is advanced by π and the case where the phase is advanced by π. Mainly, in order to set the high-on determination value IsH, the case where the phase is advanced by π is set in order to consider the case where the current is increasing when the winding current becomes 0.

Therefore, if the low-on determination value IsL and the high-on determination value IsH are set so as to satisfy the following equations, the state of the winding current at the next on / off time Tnxt destination and the state of the current corresponding to the determined mode match. ..

As shown in the following equation, the low-on judgment value IsL is obtained by adding the preset positive offset value αL to the winding current value (positive value) before the next on / off time when the current decreases. The high-on judgment value IsH is a positive offset value αH preset in consideration of the current detection error from the winding current value (negative value) before the next on / off time when the current increases. It may be set to the value obtained by subtracting.

Therefore, the alternator power generation control unit 332 sets the low-on determination value IsL and the high-on determination value IsH based on the rotation angular velocity ω, the winding current amplitude I, and the next on / off time Tnxt as the margin time Tmg. The amplitude I of the winding current may be calculated from the maximum value and the minimum value of the detected values of the winding current in the past. The alternator power generation control unit 332 sets the low-on determination value ItL and the high-on determination value IsH based on the winding current at the time point before the next on / off time Tnxt before the time when the winding current becomes 0. For example, the alternator power generation control unit 332 sets the low-on determination value IsL and the high-on determination value IsH using the equation (4).

In this way, since the low-on determination value IsL and the high-on determination value IsH are set based on the winding current at the time point before the next on-off time Tnxt, the detection of the next winding current that is ahead of the next on-off time Tnxt. It is possible to determine whether or not the winding current straddles 0A in the period up to the on / off time according to the value, and if it straddles 0A, it is possible to switch to the zero-on mode, and the diode is erroneously energized near 0A. It is possible to suppress the switching element on the opposite side from being turned on and to suppress the decrease in power generation efficiency.

Although it may be set using the equation (4), the following equation which approximates the sine function may be used as shown in the following equation.

Alternatively, the low-on determination value IsL may be set by referring to the determination value setting map in which the relationship between the rotation angular velocity ω and the amplitude I of the winding current and the low-on determination value IsL is set in advance, and the rotation angular velocity ω and The high-on determination value IsH may be set with reference to the determination value setting map in which the relationship between the amplitude I of the winding current and the high-on determination value IsH is set in advance. The determination value setting map may be set in advance based on experimental data or analysis data.

Further, as the rotation angular velocity ω, the maximum rotation angular velocity ωmax set in advance in the operating region of the alternator power generation control may be used. Further, as the winding current amplitude I, the maximum preset winding current amplitude Imax in the operating region of the alternator power generation control may be used.

In the above, each switching element was turned on and off at the apex of the valley of the carrier signal C2 based on the determination result of switching. However, as shown in FIG. 10, switching is performed without waiting for the apex of the valley of the carrier signal C2. When the determination is completed, each switching element may be turned on and off based on the determination result of switching. The next on / off time Tnxt used for calculating the determination value may be set based on the past next on / off time Tnxt, or may be set in advance. Since the processing load of the alternator power generation control process is significantly smaller than that of the inverter control process, the switching determination is completed early. For each phase, as soon as the switching determination of each phase is completed, the switching of each phase may be turned on / off based on the switching determination result. With this configuration, the on / off delay time Tdry and the next on / off time Tnxt can be shortened, and the low-on determination value IsL and the high-on determination value IsH can be brought close to zero. Therefore, the period of the low-on mode and the high-on mode can be lengthened, the period of the zero-on mode can be shortened, the power generation efficiency can be improved, and the calorific value can be reduced.

In order to carry out induced power generation, the induced voltage that increases with an increase in rotation speed must exceed the voltage of the DC power supply. Therefore, whether to execute the inverter control or the alternator power generation control may be determined based on the rotation speed of the AC rotating machine and the DC voltage Vdc.

<Setting of 2nd control cycle Tc2>
The second control cycle Tc2 is set to a shorter cycle than the first control cycle Tc1. According to this configuration, even if the behavior of the winding current changes due to a change in the state such as a change in the rotation speed or a change in the field magnetic flux, the winding current is detected and the switching element is turned on and off. The time difference from the time point can be reduced, the influence of the state change can be made relatively small, and the accuracy of the timing setting of the synchronous rectification can be improved.

In the inverter control, the arithmetic processing load for calculating the voltage command value is large, but in the alternator power generation control, the arithmetic processing load is relatively small because the switching determination is performed based on the current command value. Therefore, in the arithmetic processing apparatus having a processing speed capable of executing the inverter control in the first control cycle Tc1, the second control cycle Tc2 can be made shorter than the first control cycle Tc1.

<When used as a generator motor for vehicles>
When the control device for the AC rotary machine of the present embodiment is used for a generator motor for a vehicle, the configuration is as shown in FIG. The rotary shaft of the rotor of the AC rotary machine 1 is connected to the crank shaft of the internal combustion engine 100 via a pulley and a belt mechanism 101. The rotating shaft of the AC rotating machine 1 is connected to the wheel 103 via the internal combustion engine 100 and the transmission 102. The AC rotary machine 1 functions as an electric motor, serves as a driving force source for the wheels 103 as an auxiliary machine of the internal combustion engine 100, and also functions as a generator, and generates electricity by utilizing the rotation of the internal combustion engine 100. Since the AC rotary machine 1 is connected to the internal combustion engine 100, the rotation fluctuation becomes gradual due to the inertia of the internal combustion engine 100. Therefore, when the alternator power generation control is performed in the second control cycle Tc2, the rotation fluctuation changes. The impact can be reduced. Further, it is possible to obtain the same effect even with a generator for a vehicle.

1-5-2. Field winding control unit 35
The field current detection unit 34 detects the field current ifs, which is the current flowing through the field winding 4, based on the output signal of the field current sensor 6. Here, ifs is a detected value of the field current if.

The field winding control unit 35 is proportional to the deviation Δif between the field current command value ifo and the field current detection value ifs so that the field current detection value ifs approaches the field current command value ifo. Integral control is performed to calculate the field voltage command value Vf, and a current is applied to the field winding 4 based on the field voltage command value Vf.

In the present embodiment, as shown in FIG. 2, the field winding control unit 35 includes a current command value calculation unit 351, a voltage command value calculation unit 352, and a PWM control unit 353.

The current command value calculation unit 351 sets the field current command value ifo. For example, when the inverter control is executed, the current command value calculation unit 351 sets the field current command value ifo based on the torque command value To or the like. When the alternator power generation control is executed, the current command value calculation unit 351 changes the field current command value ifo so that the DC voltage Vdc approaches the target voltage.

Then, the voltage command value calculation unit 352 performs proportional integral control with respect to the deviation between the field current command value ifo and the field current detection value ifs, and calculates the field voltage command value Vf.

The PWM control unit 353 controls on / off of a plurality of switching elements of the converter 9 by PWM control based on the field voltage command value Vf.

For example, as shown in FIG. 12, the PWM control unit 353 controls a plurality of switching elements on and off by comparing the field voltage command value Vf with the field carrier signal Cf vibrating in the field control cycle Tsf. The field carrier signal Cf is a triangular wave that oscillates between -1 × DC voltage Vdc and DC voltage Vdc in the field control cycle Tsf. The DC voltage Vdc may be detected by a voltage sensor.

When the field carrier signal Cf falls below the field voltage command value Vf, the PWM control unit 353 turns on the switching signal QP1 of the switching element SP1 on the high potential side of the first set (1 in this example). The switching signal QN1 of the switching element SN1 on the low potential side of the first set is turned off (0 in this example), the switching signal QP2 of the switching element SP2 on the high potential side of the second set is turned off (0), and the second set. The switching signal QN2 of the switching element SN2 on the low potential side of the set is turned on (1).

On the other hand, when the field carrier signal Cf exceeds the field voltage command value Vf, the PWM control unit 353 turns off (0) the switching signal QP1 on the high potential side of the first set, and the low potential of the first set. The switching signal QN1 on the side is turned on (1), the switching signal QP2 on the high potential side of the second set is turned on (1), and the switching signal QN2 on the low potential side of the second set is turned off (0). For each set, between the on period of the switching element on the high potential side and the on period of the switching element on the low potential side, a short circuit prevention period in which both the switching element on the positive electrode side and the switching element on the low potential side are turned off ( A dead time) may be provided.

If it is not necessary to change the current direction of the field winding, the switching signal QP2 on the high potential side of the second set may be turned off at all times, and the switching signal QN1 on the low potential side of the first set may be constantly turned off. You may turn it off. Since the inductance of the field winding is larger than the inductance of the armature winding in many cases, the fluctuation of the field current during the second control cycle Tc2 during alternator power generation control is small, and the field magnetic flux is directly changed. It is suitable for alternator power generation control because it can be used.

2. 2. Embodiment 2
Next, the AC rotary machine 1 and the control device 11 according to the second embodiment will be described. The description of the same components as those in the first embodiment will be omitted. The basic configuration of the AC rotary machine 1 and the control device 11 according to the present embodiment is the same as that of the first embodiment, but the mode switching determination method using the determination value is different from the first embodiment.

In the present embodiment, the alternator power generation control unit 332 determines the low-zero determination value IsL0 and the high-zero determination value IsH0 as determination values based on the rotational angular velocity ω, the amplitude I of the current flowing through the armature winding, and the margin time Tmg. Set. The margin time Tmg is the period from the time when the current current is detected to the time when the switching element is turned on and off based on the switching judgment result determined based on the detection value of the winding current detected at the time when the next current is detected. The time is set to Tnxt.

The alternator power generation control unit 332 sets the low-zero determination value IsL0 and the high-zero determination value IsH0 based on the winding current at the time point before the next on / off time Tnxt before the time when the winding current becomes 0. The low-zero determination value IsL0 is set in the same manner as the low-on determination value IsL of the first embodiment. Further, the high-zero determination value IsH0 is set in the same manner as the high-on determination value IsH of the first embodiment.

Then, the alternator power generation control unit 332 is currently in the low-on mode for each phase, and switches to the zero-on mode when the detected value of the winding current of the armature winding becomes smaller than the low-zero determination value IsL0. .. Further, the alternator power generation control unit 332 is currently in the high-on mode for each phase, and switches to the zero-on mode when the detected value of the winding current of the armature winding becomes larger than the high-zero determination value IsH0. As described above, in the case of the high-on mode or the low-on mode at present, the margin time Tmg is determined based on the detection value of the winding current detected at the time of the next current detection from the time of the current current detection. The next on / off time Tnxt, which is the period until the time when the switching element is turned on / off, is set according to the switching determination result.

In the case of switching from low-on mode or high-on mode to zero-on mode, the low-zero judgment value IsL0 and the high-zero judgment value IsH0 are set based on the winding current at the previous time by the next on / off time Tnxt, so that the next on / off time is performed. It is possible to determine whether or not the winding current straddles 0A in the period up to the on / off time according to the detection value of the next winding current, which is the time Tnxt ahead, and switch to the zero-on mode when the winding current straddles 0A. , It is possible to suppress that the switching element on the opposite side where the diode is not energized is accidentally turned on in the vicinity of 0A, and it is possible to suppress the decrease in power generation efficiency.

The alternator power generation control unit 332 sets the zero-low determination value Is0L and the zero-high determination value Is0H as determination values based on the rotation angular velocity ω, the amplitude I of the current flowing through the armature winding, and the margin time Tmg. The margin time Tmg is the on / off delay, which is the period from the time when the current current is detected to the time when the switching element is turned on and off based on the switching judgment result determined based on the detection value of the winding current detected at the time when the current current is detected. The time is set to Tdry.

The alternator power generation control unit 332 sets the zero-low determination value Is0L and the zero-high determination value Is0H based on the winding current at the time point before the on / off delay time Tdry before the time when the winding current becomes 0. The zero-low determination value Is0L is set by a calculation method in which the next on-off time Tnxt is replaced with the on-off delay time Tdry in the calculation of the low-on determination value IsL of the first embodiment. Further, the zero-high determination value Is0H is set by a calculation method in which the next on-off time Tnxt is replaced with the on-off delay time Tdry in the calculation of the high-on determination value IsH of the first embodiment.

Then, the alternator power generation control unit 332 is currently in the zero-on mode for each phase, and switches to the low-on mode when the detected value of the winding current of the armature winding becomes the zero-low determination value Is0L or more. .. Further, the alternator power generation control unit 332 is currently in the zero-on mode for each phase, and switches to the high-on mode when the detected value of the winding current of the armature winding becomes zero high determination value Is0H or less.

In the case of switching from zero-on mode to low-on mode or high-on mode, there is a possibility of straddling 0A in the period from the on-off time based on the current winding current detection value to the on-off time based on the next winding current detection value. If there is no, you want to set the low-on mode or high-on mode to improve the power generation efficiency. According to the above configuration, since the zero-low determination value Is0L and the zero-high determination value Is0H are set based on the winding current at the time point before the on / off delay time Tdly, the current winding current that is ahead of the on / off delay time Tdly. It is determined whether or not it has already straddled 0A at the on / off time based on the detected value of, and if it has already straddled 0A, the detection value of the next winding current from the on / off time based on the detected value of the current winding current. It is possible to switch to the low-on mode or the high-on mode at an early stage in the period up to the on-off time, increase the period of synchronous rectification, and improve the power generation efficiency.

<Flow chart>
This switching determination process can be configured as shown in the flowchart shown in FIG. The determination process of FIG. 13 is executed for each phase after the winding currents of the three phases are detected. In step S150, the alternator power generation control unit 332 determines whether or not it is currently in the low-on mode, and if it is in the low-on mode, it proceeds to step S151, and if it is not in the low-on mode, it proceeds to step S154. In step S151, the alternator power generation control unit 332 sets the low zero determination value IsL0 based on the rotation angular velocity ω, the amplitude I of the winding current, and the next on / off time Tnxt, and the detection value of the winding current is the low zero determination value. It is determined whether or not it is smaller than IsL0, and if it is smaller than the low-zero determination value IsL0, the process proceeds to step S152 to determine that the mode is switched to the zero-on mode. Judge to maintain the mode.

On the other hand, in step S154, the alternator power generation control unit 332 determines whether or not it is currently in the high-on mode, and if it is in the high-on mode, it proceeds to step S155, and if it is not in the high-on mode, it proceeds to step S158. In step S155, the alternator power generation control unit 332 sets the high-zero determination value IsH0 based on the rotation angular velocity ω, the amplitude I of the winding current, and the next on / off time Tnxt, and the detection value of the winding current is the high-zero determination value. It is determined whether or not it is larger than IsH0, and if it is larger than the high-zero determination value IsH0, the process proceeds to step S156 to determine that the mode is switched to the zero-on mode. Judged to be maintained at.

On the other hand, since the zero-on mode is currently set in step S158, the alternator power generation control unit 332 sets the zero-low determination value Is0L based on the rotation angular velocity ω, the winding current amplitude I, and the on / off delay time Tdry. It is determined whether or not the detection value of the winding current is the zero-low determination value Is0L or more. If not the above, the process proceeds to step S160. In step S160, the alternator power generation control unit 332 sets the zero-high determination value Is0H based on the rotation angular velocity ω, the amplitude I of the winding current, and the on / off delay time Tdry, and the detection value of the winding current is the zero-high determination value. It is determined whether or not it is Is0H or less, and if it is the zero-high determination value Is0H or less, the process proceeds to step S161 to determine that the mode is switched to the high-on mode. Judge to maintain the mode.

<Example of diversion>
(1) In each of the above embodiments, the case where the AC rotary machine is a generator motor for a vehicle has been described as an example. However, the AC rotating machine may be used as a driving force source for various devices other than the vehicle.

(2) In each of the above embodiments, a field winding type AC rotary machine has been described as an example. However, the AC rotating machine may be a permanent magnet type AC rotating machine.

(3) In each of the above embodiments, the case where the armature winding control unit 33 switches between the inverter control and the alternator power generation control to be executed has been described as an example. However, the armature winding control unit 33 may execute the alternator power generation control without executing the inverter control.

(4) In each of the above embodiments, a case where three-phase windings are provided has been described as an example. However, the number of phases of the winding may be set to any number such as two phases and four phases as long as it is a plurality of phases.

(5) In each of the above embodiments, a case where a set of three-phase windings and an inverter is provided has been described as an example. However, two or more sets of the plurality of phase windings and the inverter may be provided, and the same control as in each embodiment may be performed for each set of the plurality of phase windings and the inverter.

Although the present application describes various exemplary embodiments and examples, the various features, embodiments, and functions described in one or more embodiments are applications of a particular embodiment. It is not limited to, but can be applied to embodiments alone or in various combinations. Therefore, innumerable variations not exemplified are envisioned within the scope of the techniques disclosed herein. For example, it is assumed that at least one component is modified, added or omitted, and further, at least one component is extracted and combined with the components of other embodiments.

1 AC rotating machine, 2 DC power supply, 4 field winding, 5 inverter, 11 AC rotating machine control device, 12 armature winding, 14 rotor, 18 stator, Is0H zero high judgment value, Is0L zero low judgment value, IsH Hion Judgment value, ItH0 high-zero judgment value, ItL low-on judgment value, ItL0 low-zero judgment value, Tc1 first control cycle, Tc2 second control cycle, Tnxt next on-off time, Tdly on-off delay time

The control device for an AC rotary machine according to the present application is a control device for an AC rotary machine that controls an AC rotary machine provided with a rotor and a stator having a multi-phase armature winding via an inverter.
In the inverter, for each phase, a switching element on the high potential side connected to the high potential side of the DC power supply and a switching element on the low potential side connected to the low potential side of the DC power supply are connected in series and connected in series. The connection point is provided with a series circuit connected to the armature winding of the corresponding phase, and the switching element has the function of a diode connected in antiparallel.
The control device for the AC rotary machine is
A zero-on mode in which the switching elements on the high-potential side and the low-potential side are turned off for each phase when the AC rotator is made to generate power by the induced voltage generated in the armature windings of a plurality of phases, and high. A high-on mode in which the switching element on the potential side is turned on and the switching element on the low potential side is turned off, and a low-on mode in which the switching element on the high potential side is turned off and the switching element on the low potential side is turned on. Is switched by comparing the detected value and the determined value of the current flowing through the armature winding, and the alternator power generation control is executed.
The control device for the AC rotator sets the determination value based on the rotational angular velocity of the AC rotator, the amplitude of the current flowing through the armature winding, and the margin time .
The margin time is preset in the delay time that occurs in the switching, or the control device of the AC rotating machine sets the margin time based on the delay time that has occurred in the past switching.

Claims (15)

An AC rotary machine control device that controls an AC rotary machine provided with a rotor and a stator having a multi-phase armature winding via an inverter.
In the inverter, for each phase, a switching element on the high potential side connected to the high potential side of the DC power supply and a switching element on the low potential side connected to the low potential side of the DC power supply are connected in series and connected in series. The connection point is provided with a series circuit connected to the armature winding of the corresponding phase, and the switching element has the function of a diode connected in antiparallel.
The control device for the AC rotary machine is
A zero-on mode in which the switching elements on the high-potential side and the low-potential side are turned off for each phase when the AC rotator is made to generate power by the induced voltage generated in the armature windings of a plurality of phases, and high. A high-on mode in which the switching element on the potential side is turned on and the switching element on the low potential side is turned off, and a low-on mode in which the switching element on the high potential side is turned off and the switching element on the low potential side is turned on. Is switched by comparing the detected value and the determined value of the current flowing through the armature winding, and the alternator power generation control is executed.
A control device for an AC rotor that sets the determination value based on the rotational angular velocity of the AC rotor, the amplitude of the current flowing through the armature winding, and the margin time set corresponding to the delay time that occurs in switching. .. The control device for an AC rotary machine according to claim 1, wherein the rotor has a field winding. The first or second aspect of claim 1 or 2, wherein the determination value is set based on the current flowing through the armature winding at a time point before the margin time before the time when the current flowing through the armature winding becomes 0. Control device for AC rotating machine. In the alternator power generation control, the zero-on mode is switched to the high-on mode or the low-on mode, and the high-on mode or the low-on mode is switched to the zero-on mode, but the high-on mode is switched to the low-on mode. The control device for an AC rotary machine according to any one of claims 1 to 3, wherein the switching to the on mode and the switching from the low-on mode to the high-on mode are not performed. Based on the rotational angular velocity, the amplitude of the current, and the margin time, the high-on determination value and the low-on determination value as the determination values are set.
For each phase, if the detected value of the current of the armature winding is equal to or higher than the low-on determination value, the mode is switched to the low-on mode, and the detected value of the current of the armature winding is equal to or less than the high-on determination value. From claim 1, the mode is switched to the high-on mode, and when the detected value of the current of the armature winding is smaller than the low-on determination value and larger than the high-on determination value, the mode is switched to the zero-on mode. The control device for an AC rotary machine according to any one of 4. The margin time used for calculating the high-on determination value and the low-on determination value is the switching element determined based on the switching determination result determined based on the current detection value detected from the current current detection time point to the next current detection time point. The control device for an AC rotary machine according to claim 5, which is set in a period until a time point of turning on and off. Based on the rotational angular velocity, the amplitude of the current, and the margin time, the low-zero determination value and the high-zero determination value as the determination values are set.
Each phase is currently in the low-on mode, and when the detected value of the current becomes smaller than the low-zero determination value, the mode is switched to the zero-on mode.
The aspect according to any one of claims 1 to 4, wherein each phase is currently in the high-on mode, and when the detected value of the current becomes larger than the high-zero determination value, the mode is switched to the zero-on mode. Control device for AC rotating machine. The margin time used for calculating the low-zero determination value and the high-zero determination value is the switching element determined based on the switching determination result determined based on the current detection value detected from the current current detection time point to the next current detection time point. The control device for an AC rotary machine according to claim 7, which is a period until the time when the current is turned on and off. Based on the rotational angular velocity, the amplitude of the current, and the margin time, the zero-low determination value and the zero-high determination value as the determination values are set.
Each phase is currently in the zero-on mode, and when the detected value of the current becomes equal to or higher than the zero-low determination value, the mode is switched to the low-on mode.
The control device for an AC rotary machine according to claim 7 or 8, which is currently in the zero-on mode and switches to the high-on mode when the detected value of the current becomes equal to or less than the zero-high determination value. The margin time used for calculating the zero-low determination value and the zero-high determination value is a switching element determined based on the switching determination result determined based on the current detection value detected at the current current detection time from the current current detection time. The control device for an AC rotary machine according to claim 9, which is a period until the time when the current is turned on and off. The rotational angular velocity at the electric angle is ωm, the amplitude of the current is I, and the margin time is Tmg.
I x sin (ωm x Tmg)
The control device for an AC rotary machine according to any one of claims 1 to 10, wherein the determination value is set based on the calculated value according to the above equation. The rotational angular velocity at the electric angle is ωm, the amplitude of the current is I, and the margin time is Tmg.
I x ωm x Tmg
The control device for an AC rotary machine according to any one of claims 1 to 10, wherein the determination value is set based on the calculated value according to the above equation. The control device for an AC rotary machine according to any one of claims 1 to 12, wherein the maximum rotation angular velocity is used as the rotation angular velocity. The control device for an AC rotary machine according to any one of claims 1 to 12, wherein the maximum current amplitude is used as the current amplitude. The control device for an AC rotator according to any one of claims 1 to 14, wherein the AC rotator is a generator for a vehicle or a generator motor.

Images