JP2020145865A - Motor system - Google Patents
Motor system Download PDFInfo
- Publication number
- JP2020145865A JP2020145865A JP2019041200A JP2019041200A JP2020145865A JP 2020145865 A JP2020145865 A JP 2020145865A JP 2019041200 A JP2019041200 A JP 2019041200A JP 2019041200 A JP2019041200 A JP 2019041200A JP 2020145865 A JP2020145865 A JP 2020145865A
- Authority
- JP
- Japan
- Prior art keywords
- component
- phase
- current
- fundamental wave
- harmonic
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Granted
Links
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P25/00—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details
- H02P25/02—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details characterised by the kind of motor
- H02P25/022—Synchronous motors
- H02P25/024—Synchronous motors controlled by supply frequency
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P25/00—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details
- H02P25/16—Arrangements or methods for the control of AC motors characterised by the kind of AC motor or by structural details characterised by the circuit arrangement or by the kind of wiring
- H02P25/22—Multiple windings; Windings for more than three phases
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Control Of Ac Motors In General (AREA)
- Permanent Magnet Type Synchronous Machine (AREA)
- Permanent Field Magnets Of Synchronous Machinery (AREA)
Abstract
Description
本発明は、モータと電流供給回路を有するモータシステムに関する。 The present invention relates to a motor system having a motor and a current supply circuit.
従来から、モータと当該モータに電流を供給する電流供給回路を備えたモータシステムが知られている。 Conventionally, a motor system including a motor and a current supply circuit for supplying a current to the motor has been known.
例えば特許文献１には、電動機（モータ）とインバータ（電流供給回路）を備えた電動機システム（モータシステム）が記載されている。特許文献１に記載されるシステムにおいて、電動機は回転子と固定子を有しており、回転子には永久磁石が配置され、固定子には中性点で結線された多相巻線が設けられている。そして、特許文献１に記載されるシステムでは、インバータの直流側の電圧の中点と多相巻線が有する中性点のうちの１つとを接続する接続手段に零相電流が流れるようにインバータが制御される。これにより、特許文献１に記載されるシステムは、接続手段に零相電流を流すことにより発生する磁束と永久磁石に発生する磁束により、回転子に対して半径方向の力を発生させる。 For example, Patent Document 1 describes an electric motor system (motor system) including an electric motor (motor) and an inverter (current supply circuit). In the system described in Patent Document 1, the electric motor has a rotor and a stator, a permanent magnet is arranged on the rotor, and the stator is provided with a multi-phase winding connected at a neutral point. Has been done. Then, in the system described in Patent Document 1, the inverter so that the zero-phase current flows through the connecting means for connecting the middle point of the voltage on the DC side of the inverter and one of the neutral points of the multi-phase winding. Is controlled. As a result, the system described in Patent Document 1 generates a force in the radial direction with respect to the rotor by the magnetic flux generated by passing a zero-phase current through the connecting means and the magnetic flux generated in the permanent magnet.
特許文献１に記載されるシステムでは、零相電流を流すことで発生する磁界（零相磁界）により、回転子に対して半径方向の力を発生させているが、零相磁界により得られる力をトルク成分として利用できていない。 In the system described in Patent Document 1, a force in the radial direction is generated with respect to the rotor by a magnetic field (zero-phase magnetic field) generated by passing a zero-phase current, but the force obtained by the zero-phase magnetic field is generated. Is not available as a torque component.
本発明は、零相磁界により得られる力をトルク成分として利用できるモータシステムを実現することにある。 The present invention is to realize a motor system in which the force obtained by a zero-phase magnetic field can be used as a torque component.
本発明の具体例の一つであるモータシステムは、モータと電流供給回路を有するモータシステムであって、前記モータは、Ｎ相巻線（Ｎは自然数）を備えたステータと、永久磁石を備えたロータと、を有し、前記ロータによる前記ステータの鎖交磁束が基本波磁束成分とＮ×Ｋ次高調波磁束成分（Ｋは自然数）とを含み、前記電流供給回路は、回転磁界を発生させる基本波電流成分と零相磁界を発生させるＮ×Ｋ次高調波電流成分とを含んだ電流を前記Ｎ相巻線に供給することを特徴とする。 The motor system, which is one of the specific examples of the present invention, is a motor system having a motor and a current supply circuit, and the motor includes a stator having an N-phase winding (N is a natural number) and a permanent magnet. The interlinkage magnetic flux of the stator by the rotor includes a fundamental wave magnetic flux component and an N × Kth harmonic magnetic flux component (K is a natural number), and the current supply circuit generates a rotating magnetic field. It is characterized in that a current including a fundamental wave current component to be generated and an N × K harmonic current component to generate a zero-phase magnetic field is supplied to the N-phase winding.
例えば、前記電流供給回路は、前記基本波電流成分の極値の絶対値よりも合成後の極値の絶対値が小さくなる位相関係で前記基本波電流成分と前記Ｎ×Ｋ次高調波電流成分を合成した電流を前記Ｎ相巻線に供給するようにしてもよい。 For example, in the current supply circuit, the fundamental wave current component and the N × K harmonic current component have a phase relationship in which the absolute value of the extremum after synthesis is smaller than the absolute value of the extreme value of the fundamental wave current component. The combined current may be supplied to the N-phase winding.
また、例えば、前記モータは、前記基本波電流成分による回転磁界と前記鎖交磁束の前記基本波磁束成分とにより得られる基本波トルク成分と、前記Ｎ×Ｋ次高調波電流成分による零相磁界と前記鎖交磁束の前記Ｎ×Ｋ次高調波磁束成分とにより得られるＮ×Ｋ次高調波トルク成分と、を含んだトルクを発生し、前記電流供給回路は、トルクの増加を必要とする動作期間において、前記基本波トルク成分と前記Ｎ×Ｋ次高調波トルク成分が互いに同じ方向となる位相関係で、前記基本波電流成分と前記Ｎ×Ｋ次高調波電流成分が合成された電流を、前記Ｎ相巻線に供給するようにしてもよい。 Further, for example, the motor has a fundamental wave torque component obtained by the rotating magnetic field due to the fundamental wave current component and the fundamental wave magnetic flux component of the interlinkage magnetic flux, and a zero-phase magnetic field due to the N × K order harmonic current component. And the N × K harmonic torque component obtained by the N × K harmonic flux component of the interlinkage magnetic flux, and the current supply circuit requires an increase in torque. During the operation period, the current obtained by combining the fundamental wave current component and the N × K harmonic current component in a phase relationship in which the fundamental wave torque component and the N × K harmonic torque component are in the same direction as each other. , The N-phase winding may be supplied.
また、例えば、前記ロータの永久磁石の開角が前記ステータのＮ相巻線の巻幅よりも小さくてもよいし、前記ロータの突極の開角が当該ロータの永久磁石の開角よりも小さくてもよい。 Further, for example, the opening angle of the permanent magnet of the rotor may be smaller than the winding width of the N-phase winding of the stator, and the opening angle of the salient pole of the rotor may be smaller than the opening angle of the permanent magnet of the rotor. It may be small.
本発明により、零相磁界により得られる力をトルク成分として利用できるモータシステムが実現される。 According to the present invention, a motor system capable of utilizing the force obtained by the zero-phase magnetic field as a torque component is realized.
図１，図２は、本発明の具体的な実施態様の一例を示す図である。図１，図２には、モモータシステムに関するいくつかの具体例が図示されている。 1 and 2 are views showing an example of a specific embodiment of the present invention. 1 and 2 show some specific examples of the motor motor system.
図１，図２に示す各具体例のモータシステムは、モータ１０とインバータ２０と電池３０を備えている。モータ１０は、Ｎ相巻線（Ｎは自然数）を備えている。また、インバータ２０は、モータ１０が備えるＮ相巻線に電流を供給する電流供給回路の一例である。インバータ２０は、電池３０から電力を得てモータ１０のＮ相巻線に電流を供給する。インバータ２０は、回転磁界を発生させる電流成分と零相磁界を発生させる電流成分を含んだ電流をＮ相巻線に供給する。 The motor system of each specific example shown in FIGS. 1 and 2 includes a motor 10, an inverter 20, and a battery 30. The motor 10 includes an N-phase winding (N is a natural number). Further, the inverter 20 is an example of a current supply circuit that supplies a current to the N-phase winding included in the motor 10. The inverter 20 obtains electric power from the battery 30 and supplies a current to the N-phase winding of the motor 10. The inverter 20 supplies the N-phase winding with a current including a current component that generates a rotating magnetic field and a current component that generates a zero-phase magnetic field.
図１は、中性点を利用したモータシステムの具体例を示す図である。図１には、３相巻線（Ｎ＝３）のモータ１０を備えた具体例Ａと、５相巻線（Ｎ＝５）のモータ１０を備えた具体例Ｂが例示されている。 FIG. 1 is a diagram showing a specific example of a motor system using a neutral point. FIG. 1 illustrates a specific example A provided with a motor 10 having a three-phase winding (N = 3) and a specific example B provided with a motor 10 having a five-phase winding (N = 5).
図１に示す具体例Ａでは、モータ１０が備える３相巻線の中性点Ｇと零相用回路２２の間に、零相磁界を発生させる電流成分である零相電流が流れる。また、図１に示す具体例Ｂでは、モータ１０が備える５相巻線の中性点Ｇと零相用回路２２の間に零相電流が流れる。 In the specific example A shown in FIG. 1, a zero-phase current, which is a current component that generates a zero-phase magnetic field, flows between the neutral point G of the three-phase winding included in the motor 10 and the zero-phase circuit 22. Further, in the specific example B shown in FIG. 1, a zero-phase current flows between the neutral point G of the five-phase winding included in the motor 10 and the zero-phase circuit 22.
図２は、オープン巻線を利用したモータシステムの具体例を示す図である。図２には、３相巻線（Ｎ＝３）のモータ１０を備えた具体例Ｃと、５相巻線（Ｎ＝５）のモータ１０を備えた具体例Ｄが例示されている。 FIG. 2 is a diagram showing a specific example of a motor system using an open winding. FIG. 2 illustrates a specific example C provided with a motor 10 having a three-phase winding (N = 3) and a specific example D provided with a motor 10 having a five-phase winding (N = 5).
図２に示す具体例Ｃでは、モータ１０が備える３相巻線の各巻線を介して、インバータ２０と第２インバータ２４の間に、零相磁界を発生させる電流成分である零相電流が流れる。また、図２に示す具体例Ｄでは、モータ１０が備える５相巻線の各巻線を介して、インバータ２０と第２インバータ２４の間に零相電流が流れる。 In the specific example C shown in FIG. 2, a zero-phase current, which is a current component that generates a zero-phase magnetic field, flows between the inverter 20 and the second inverter 24 via each winding of the three-phase winding included in the motor 10. .. Further, in the specific example D shown in FIG. 2, a zero-phase current flows between the inverter 20 and the second inverter 24 via each winding of the five-phase winding included in the motor 10.
なお、図１，図２には、Ｎ相巻線の代表例として３相巻線と５相巻線のモータ１０を有するモータシステムを例示したが、３相巻線と５相巻線以外のＮ相巻線を備えたモータ１０によりモータシステムが実現されてもよい。 Note that FIGS. 1 and 2 exemplify a motor system having a motor 10 having a 3-phase winding and a 5-phase winding as a typical example of the N-phase winding, but other than the 3-phase winding and the 5-phase winding. A motor system may be realized by a motor 10 with N-phase windings.
図３は、モータ１０の構成例１を示す図である。図３には、ステータ１２とロータ１４を備えたモータ１０の構成例が図示されている。ステータ１２はＮ相巻線（Ｎは自然数）を備えており、ロータ１４は磁石（永久磁石）を備えている。なお、図３（Ａ）は、モータ１０の回転軸を中心とする円周全体の構成例であり、図３（Ｂ）は、図３（Ａ）に示す円周全体を円周方向に８等分したうちの１つに対応した部分構成を示している。 FIG. 3 is a diagram showing a configuration example 1 of the motor 10. FIG. 3 shows a configuration example of the motor 10 including the stator 12 and the rotor 14. The stator 12 has an N-phase winding (N is a natural number), and the rotor 14 has a magnet (permanent magnet). Note that FIG. 3 (A) is an example of the configuration of the entire circumference centered on the rotation axis of the motor 10, and FIG. 3 (B) shows the entire circumference shown in FIG. 3 (A) being 8 in the circumferential direction. The partial configuration corresponding to one of the equal parts is shown.
図３に示す構成例のステータ１２は３相巻線（Ｎ＝３）を備えている。つまり、図３のステータ１２は、Ｕ相とＶ相とＷ相の３相に対応した巻線Ｃを備えている。また、図３に示す構成例のロータ１４は、図３（Ｂ）に示す部分構成ごとに、２つで１つの組を構成する磁石（永久磁石）を備えている。 The stator 12 of the configuration example shown in FIG. 3 includes a three-phase winding (N = 3). That is, the stator 12 in FIG. 3 includes windings C corresponding to three phases of U phase, V phase, and W phase. Further, the rotor 14 of the configuration example shown in FIG. 3 is provided with magnets (permanent magnets) that form one set of two for each partial configuration shown in FIG. 3 (B).
図４は、ロータ磁石鎖交磁束の具体例１を示す図である。図４には、図３に示す構成例１のロータ１４によるステータ１２への鎖交磁束の具体例が図示されている。Ｎ相巻線（Ｎは自然数）を備えたステータ１２への鎖交磁束には、基本波磁束成分とＮ×Ｋ次高調波磁束成分（Ｋは自然数）が含まれている。 FIG. 4 is a diagram showing a specific example 1 of the rotor magnet interlinkage magnetic flux. FIG. 4 shows a specific example of the interlinkage magnetic flux to the stator 12 by the rotor 14 of the configuration example 1 shown in FIG. The interlinkage magnetic flux to the stator 12 provided with the N-phase winding (N is a natural number) includes a fundamental wave magnetic flux component and an N × K harmonic flux component (K is a natural number).
図４には、３相巻線（Ｎ＝３）を備えたステータ１２のロータ磁石鎖交磁束が実線で示されている。また、図４に実線で示されるロータ磁石鎖交磁束は、破線で示す基本波磁束成分と点線で示す３次高調波磁束成分（Ｎ＝３，Ｋ＝１）を含んでいる。 In FIG. 4, the rotor magnet interlinkage magnetic flux of the stator 12 provided with the three-phase winding (N = 3) is shown by a solid line. Further, the rotor magnet interlinkage magnetic flux shown by the solid line in FIG. 4 includes a fundamental wave magnetic flux component shown by a broken line and a third harmonic magnetic flux component (N = 3, K = 1) shown by a dotted line.
図５は、Ｎ相巻線に供給される電流の具体例１を示す図である。インバータ２０（図１，図２）は、回転磁界を発生させる基本波電流成分と零相磁界を発生させるＮ×Ｋ次高調波電流成分とを含んだ電流をＮ相巻線に供給する。図５には、３相巻線（Ｎ＝３）のロータ磁石鎖交磁束（図４）に対して同方向のトルクを発生させる基本波電流成分と３次高調波電流成分（Ｎ＝３，Ｋ＝１）の具体例が図示されている。 FIG. 5 is a diagram showing a specific example 1 of the current supplied to the N-phase winding. The inverter 20 (FIGS. 1 and 2) supplies a current including a fundamental wave current component that generates a rotating magnetic field and an N × K harmonic current component that generates a zero-phase magnetic field to the N-phase winding. FIG. 5 shows a fundamental wave current component and a third harmonic current component (N = 3,) that generate torque in the same direction with respect to the rotor magnet interlinkage magnetic flux (FIG. 4) of the three-phase winding (N = 3). A specific example of K = 1) is shown.
なお、インバータ２０は、基本波電流成分の極値の絶対値よりも、合成後の極値の絶対値が小さくなる位相関係で、基本波電流成分とＮ×Ｋ次高調波電流成分を合成した電流をＮ相巻線に供給するようにしてもよい。 The inverter 20 combines the fundamental wave current component and the N × K harmonic current component in a phase relationship in which the absolute value of the extremum after synthesis is smaller than the absolute value of the extreme value of the fundamental wave current component. The current may be supplied to the N-phase winding.
例えば、図５に示す具体例のように、破線で示す基本波電流成分の極大値Ｐｆよりも、実線で示す合成後の相電流の極大値Ｐｃが小さくなる位相関係で、基本波電流成分と点線で示す３次高調波電流成分である零相電流を合成した相電流が供給されてもよい。これにより、実線で示す合成後の相電流のピークを減少させることができる。 For example, as in the specific example shown in FIG. 5, the phase relationship with the fundamental wave current component is such that the maximum value Pc of the combined phase current shown by the solid line is smaller than the maximum value Pf of the fundamental wave current component shown by the broken line. A phase current obtained by synthesizing a zero-phase current, which is a third-order harmonic current component indicated by a dotted line, may be supplied. As a result, the peak of the phase current after synthesis shown by the solid line can be reduced.
図６は、モータ１０（図１〜図３）が発生するトルクの具体例を示す図である。モータ１０は、基本波電流成分による回転磁界と鎖交磁束の基本波磁束成分とにより得られる基本波トルク成分と、Ｎ×Ｋ次高調波電流成分による零相磁界と鎖交磁束のＮ×Ｋ次高調波磁束成分とにより得られるＮ×Ｋ次高調波トルク成分を含んだトルクを発生する。 FIG. 6 is a diagram showing a specific example of the torque generated by the motor 10 (FIGS. 1 to 3). The motor 10 has a fundamental torque component obtained by a rotating magnetic field due to a fundamental current component and a fundamental magnetic flux component of an interlinkage magnetic flux, and a zero-phase magnetic field and an interlinkage magnetic flux N × K due to an N × K order harmonic current component. A torque including the N × K order harmonic torque component obtained by the second harmonic magnetic flux component is generated.
図６には、破線で示す基本波トルク成分と点線で示す３次高調波トルク成分（Ｎ＝３，Ｋ＝１）と、これらの２つのトルク成分を合成した実線で示す合成トルクの具体例が図示されている。 FIG. 6 shows a specific example of the fundamental wave torque component shown by the broken line, the third harmonic torque component (N = 3, K = 1) shown by the dotted line, and the combined torque shown by the solid line obtained by combining these two torque components. Is illustrated.
また、インバータ２０（図１，図２）は、トルクの増加を必要とする動作期間において基本波トルク成分とＮ×Ｋ次高調波トルク成分が互いに同じ方向となる位相関係で、基本波電流成分とＮ×Ｋ次高調波電流成分が合成された電流をＮ相巻線に供給してもよい。 Further, in the inverter 20 (FIGS. 1 and 2), the fundamental wave current component has a phase relationship in which the fundamental wave torque component and the N × K harmonic torque component are in the same direction during an operation period requiring an increase in torque. A current in which the N × K harmonic current components are combined may be supplied to the N-phase winding.
例えば、図６に示す具体例のように、電流進角３０〜９０ｄｅｇ．の動作期間（例えば弱め界磁の期間）において、基本波トルク成分と３次高調波トルク成分が共に正方向となる位相関係で合成されてもよい。 For example, as in the specific example shown in FIG. 6, the current advance angle is 30 to 90 deg. In the operation period of (for example, the period of field weakening), the fundamental wave torque component and the third harmonic torque component may be combined in a positive phase relationship.
図７は、ロータ１４の構造とロータ磁石鎖交磁束の関係を示す図である。ステータ１２はＮ相巻線を備えており、ロータ１４は磁石（永久磁石）を備えている。図７には、ステータ１２が備えるＵ相巻線と、ロータ１４の磁石が角度Ａ，角度Ｂ，角度Ｃの順に回転方向に回転する様子が例示されている。 FIG. 7 is a diagram showing the relationship between the structure of the rotor 14 and the magnetic flux interlinking the rotor magnets. The stator 12 includes N-phase windings, and the rotor 14 includes magnets (permanent magnets). FIG. 7 illustrates how the U-phase winding included in the stator 12 and the magnet of the rotor 14 rotate in the rotational direction in the order of angle A, angle B, and angle C.
例えば、図７に例示するように、ロータ１４が備える磁石（永久磁石）の開角が、ステータ１２のＮ相巻線の巻幅よりも小さい構成例としてもよい。また、例えば、後に説明するロータ１４の突極の開角が、ロータ１４が備える磁石（永久磁石）の開角よりも小さい構成例としてもよい。 For example, as illustrated in FIG. 7, the opening angle of the magnet (permanent magnet) included in the rotor 14 may be smaller than the winding width of the N-phase winding of the stator 12. Further, for example, the opening angle of the salient pole of the rotor 14 described later may be smaller than the opening angle of the magnet (permanent magnet) included in the rotor 14.
図８，図９は、磁石の開角とＮ相巻線の巻幅と突極の開角に関する具体例を示す図である。図８，図９には、ロータ１４が備える磁石（永久磁石）の開角θｍと、Ｎ相巻線の巻幅（角度）θｃと、ロータ１４の突極の開角θｔの具体例が示されている。なお、図８，図９に示す各角度は、ロータ１４の回転軸を中心とする回転方向の角度である。 8 and 9 are diagrams showing specific examples of the opening angle of the magnet, the winding width of the N-phase winding, and the opening angle of the salient pole. 8 and 9 show specific examples of the opening angle θm of the magnet (permanent magnet) included in the rotor 14, the winding width (angle) θc of the N-phase winding, and the opening angle θt of the salient pole of the rotor 14. Has been done. The angles shown in FIGS. 8 and 9 are angles in the rotation direction about the rotation axis of the rotor 14.
磁石の開角θｍは、ロータ１４が備える磁石（永久磁石）の磁束がステータ１２に渡る部位の角度である。図８（Ａ）（Ｂ）に示す具体例では、ロータ１４が２つで１つの組を構成する磁石（永久磁石）を備えており、１つの組の磁石の磁束がステータ１２に渡る部位の角度が磁石の開角θｍとなる。図９に示す具体例では、ロータ１４が１つずつ個別に設けられた磁石（永久磁石）を備えており、個別に設けられた各磁石の磁束がステータ１２に渡る部位の角度が磁石の開角θｍとなる。 The opening angle θm of the magnet is the angle of the portion where the magnetic flux of the magnet (permanent magnet) included in the rotor 14 crosses the stator 12. In the specific example shown in FIGS. 8 (A) and 8 (B), the rotor 14 includes two magnets (permanent magnets) forming a set, and the magnetic flux of the one set of magnets reaches the stator 12. The angle is the opening angle θm of the magnet. In the specific example shown in FIG. 9, the rotor 14 is provided with magnets (permanent magnets) individually provided, and the angle of the portion where the magnetic flux of each individually provided magnet crosses the stator 12 is the opening of the magnet. The angle is θm.
また、突極の開角θｔは、ロータ１４が備える各突極（１つの突極）の回転方向の幅に対応した角度であり、巻幅θｃは、ステータ１２が備えるＮ相巻線の巻幅に関する回転方向の角度である。例えば、図８（Ａ）（Ｂ）に示す具体例では、磁石の開角θｍがＮ相巻線の巻幅θｃよりも小さく、突極の開角θｔが磁石の開角θｍよりも小さい。 Further, the opening angle θt of the salient pole is an angle corresponding to the width in the rotation direction of each salient pole (one salient pole) included in the rotor 14, and the winding width θc is the winding of the N-phase winding provided in the stator 12. The angle of rotation with respect to width. For example, in the specific example shown in FIGS. 8A and 8B, the opening angle θm of the magnet is smaller than the winding width θc of the N-phase winding, and the opening angle θt of the salient pole is smaller than the opening angle θm of the magnet.
図１０は、モータ１０の構成例２を示す図である。図１０には、ステータ１２とロータ１４を備えたモータ１０の構成例が図示されている。ステータ１２はＮ相巻線（Ｎは自然数）を備えており、ロータ１４は磁石（永久磁石）を備えている。なお、図１０（Ａ）はモータ１０の回転軸を中心とする円周全体の構成例であり、図１０（Ｂ）は、図１０（Ａ）に示す円周全体を円周方向に４等分したうちの１つに対応した部分構成を示している。 FIG. 10 is a diagram showing a configuration example 2 of the motor 10. FIG. 10 shows a configuration example of the motor 10 including the stator 12 and the rotor 14. The stator 12 has an N-phase winding (N is a natural number), and the rotor 14 has a magnet (permanent magnet). Note that FIG. 10A shows an example of the configuration of the entire circumference centered on the rotation axis of the motor 10, and FIG. 10B shows the entire circumference shown in FIG. 10A being 4 mag in the circumferential direction. The partial configuration corresponding to one of the divided parts is shown.
図１０に示す構成例のステータ１２は５相巻線（Ｎ＝５）を備えている。つまり、図１０のステータ１２は、Ｕ相とＶ相とＷ相とＸ相とＹ相の５相に対応した巻線Ｃを備えている。また、図１０に示す構成例のロータ１４は、また、図１０に示す構成例のロータ１４は、図１０（Ｂ）に示す部分構成ごとに個別に設けられた１つの磁石（永久磁石）を備えている。 The stator 12 of the configuration example shown in FIG. 10 includes a 5-phase winding (N = 5). That is, the stator 12 in FIG. 10 includes windings C corresponding to five phases of U phase, V phase, W phase, X phase, and Y phase. Further, the rotor 14 of the configuration example shown in FIG. 10 and the rotor 14 of the configuration example shown in FIG. 10 have one magnet (permanent magnet) individually provided for each partial configuration shown in FIG. 10 (B). I have.
図１１は、ロータ磁石鎖交磁束の具体例２を示す図である。図１１には、図１０に示す構成例２のロータ１４によるステータ１２への鎖交磁束の具体例が図示されている。Ｎ相巻線（Ｎは自然数）を備えたステータ１２への鎖交磁束には、基本波磁束成分とＮ×Ｋ次高調波磁束成分（Ｋは自然数）が含まれている。 FIG. 11 is a diagram showing a specific example 2 of the rotor magnet interlinkage magnetic flux. FIG. 11 shows a specific example of the interlinkage magnetic flux to the stator 12 by the rotor 14 of the configuration example 2 shown in FIG. The interlinkage magnetic flux to the stator 12 provided with the N-phase winding (N is a natural number) includes a fundamental wave magnetic flux component and an N × K harmonic flux component (K is a natural number).
図１１には、５相巻線（Ｎ＝５）を備えたステータ１２のロータ磁石鎖交磁束が実線で示されている。また、図１１に実線で示されるロータ磁石鎖交磁束は、破線で示す基本波磁束成分と点線で示す５次高調波磁束成分（Ｎ＝５，Ｋ＝１）を含んでいる。 In FIG. 11, the rotor magnet interlinkage magnetic flux of the stator 12 provided with the 5-phase winding (N = 5) is shown by a solid line. Further, the rotor magnet interlinkage magnetic flux shown by the solid line in FIG. 11 includes a fundamental wave magnetic flux component shown by a broken line and a fifth harmonic magnetic flux component (N = 5, K = 1) shown by a dotted line.
図１２は、Ｎ相巻線に供給される電流の具体例２を示す図である。インバータ２０（図１，図２）は、回転磁界を発生させる基本波電流成分と零相磁界を発生させるＮ×Ｋ次高調波電流成分とを含んだ電流をＮ相巻線に供給する。図１２には、５相巻線（Ｎ＝５）のロータ磁石鎖交磁束（図１１）に対して同方向のトルクを発生させる基本波電流成分と５次高調波電流成分（Ｎ＝５，Ｋ＝１）の具体例が図示されている。 FIG. 12 is a diagram showing a specific example 2 of the current supplied to the N-phase winding. The inverter 20 (FIGS. 1 and 2) supplies a current including a fundamental wave current component that generates a rotating magnetic field and an N × K harmonic current component that generates a zero-phase magnetic field to the N-phase winding. In FIG. 12, a fundamental wave current component and a fifth harmonic current component (N = 5,) that generate torque in the same direction with respect to the rotor magnet interlinkage magnetic flux (FIG. 11) of the 5-phase winding (N = 5) are shown. A specific example of K = 1) is shown.
なお、インバータ２０は、基本波電流成分の極値の絶対値よりも、合成後の極値の絶対値が小さくなる位相関係で、基本波電流成分とＮ×Ｋ次高調波電流成分を合成した電流をＮ相巻線に供給するようにしてもよい。 The inverter 20 synthesizes the fundamental wave current component and the N × K harmonic current component in a phase relationship in which the absolute value of the extreme value after synthesis is smaller than the absolute value of the extreme value of the fundamental wave current component. The current may be supplied to the N-phase winding.
例えば、図１２に示す具体例のように、破線で示す基本波電流成分の極大値Ｐｆよりも実線で示す合成後の相電流の極大値Ｐｃが小さくなる位相関係で、基本波電流成分と点線で示す５次高調波電流成分である零相電流を合成した相電流が供給されてもよい。これにより、実線で示す合成後の相電流のピークを減少させることができる。 For example, as in the specific example shown in FIG. 12, the fundamental wave current component and the dotted line have a phase relationship in which the maximum value Pc of the combined phase current shown by the solid line is smaller than the maximum value Pf of the fundamental wave current component shown by the broken line. A phase current obtained by synthesizing a zero-phase current, which is a fifth-order harmonic current component indicated by, may be supplied. As a result, the peak of the phase current after synthesis shown by the solid line can be reduced.
また、モータ１０（図１〜図３，図１０）は、基本波電流成分による回転磁界と鎖交磁束の基本波磁束成分とにより得られる基本波トルク成分と、Ｎ×Ｋ次高調波電流成分による零相磁界と鎖交磁束のＮ×Ｋ次高調波磁束成分とにより得られるＮ×Ｋ次高調波トルク成分を含んだトルクを発生する。 Further, the motor 10 (FIGS. 1 to 3 and 10) has a fundamental torque component obtained by a rotating magnetic field due to the fundamental current component and a fundamental magnetic flux component of the interlinkage magnetic flux, and an N × K harmonic current component. A torque including the N × K harmonic torque component obtained by the zero-phase magnetic field and the N × K harmonic flux component of the interlinkage magnetic flux is generated.
例えば、図１０に例示するモータ１０は、図１２に示す基本波電流成分による回転磁界と図１１に示す基本波磁束成分とにより得られる基本波トルク成分と、図１２に示す５次高調波電流成分による零相磁界と図１１に示す５次高調波磁束成分とにより得られる５次高調波トルク成分と、を合成した合成トルクを発生する。 For example, the motor 10 illustrated in FIG. 10 has a fundamental torque component obtained by a rotating magnetic field due to the fundamental wave current component shown in FIG. 12 and a fundamental wave magnetic flux component shown in FIG. 11, and a fifth harmonic current shown in FIG. A combined torque is generated by combining the zero-phase magnetic field due to the components and the fifth-order harmonic torque component obtained by the fifth-order harmonic flux component shown in FIG.
インバータ２０（図１，図２）は、トルクの増加を必要とする動作期間において基本波トルク成分とＮ×Ｋ次高調波トルク成分が互いに同じ方向となる位相関係で、基本波電流成分とＮ×Ｋ次高調波電流成分が合成された電流をＮ相巻線に供給してもよい。これにより、例えば図１０から図１２を利用して説明した具体例であれば、トルクの増加を必要とする動作期間（例えば弱め界磁の期間）において、基本波トルク成分と５次高調波トルク成分が共に同方向となる位相関係で合成されてもよい。 In the inverter 20 (FIGS. 1 and 2), the fundamental wave current component and the N are in a phase relationship in which the fundamental wave torque component and the N × K harmonic torque component are in the same direction during an operation period requiring an increase in torque. The current in which the × Kth harmonic current component is combined may be supplied to the N-phase winding. As a result, for example, in the specific example described with reference to FIGS. 10 to 12, the fundamental wave torque component and the fifth harmonic torque during an operation period requiring an increase in torque (for example, a period of field weakening). The components may be synthesized in a phase relationship in which both components are in the same direction.
以上、本発明の具体的な実施態様の一例を説明したが、上述した具体例はあらゆる点で単なる例示にすぎず、本発明の範囲を限定するものではない。本発明は、その本質を逸脱しない範囲で各種の変形形態を包含する。 Although an example of a specific embodiment of the present invention has been described above, the above-mentioned specific example is merely an example in all respects and does not limit the scope of the present invention. The present invention includes various modified forms without departing from its essence.
１０ モータ、１２ ステータ、１４ ロータ、２０ インバータ、３０ 電池。 10 motors, 12 stators, 14 rotors, 20 inverters, 30 batteries.
Claims (5)
前記モータは、
Ｎ相巻線（Ｎは自然数）を備えたステータと、
永久磁石を備えたロータと、
を有し、
前記ロータによる前記ステータの鎖交磁束が基本波磁束成分とＮ×Ｋ次高調波磁束成分（Ｋは自然数）とを含み、
前記電流供給回路は、
回転磁界を発生させる基本波電流成分と零相磁界を発生させるＮ×Ｋ次高調波電流成分とを含んだ電流を前記Ｎ相巻線に供給する、
ことを特徴とするモータシステム。 A motor system that has a motor and a current supply circuit.
The motor
A stator with an N-phase winding (N is a natural number),
A rotor with a permanent magnet and
Have,
The interlinkage magnetic flux of the stator by the rotor includes a fundamental wave magnetic flux component and an N × K harmonic flux component (K is a natural number).
The current supply circuit
A current including a fundamental wave current component that generates a rotating magnetic field and an N × K harmonic current component that generates a zero-phase magnetic field is supplied to the N-phase winding.
A motor system characterized by that.
前記電流供給回路は、
前記基本波電流成分の極値の絶対値よりも合成後の極値の絶対値が小さくなる位相関係で前記基本波電流成分と前記Ｎ×Ｋ次高調波電流成分を合成した電流を前記Ｎ相巻線に供給する、
ことを特徴とするモータシステム。 In the motor system according to claim 1,
The current supply circuit
The N phase is a combination of the fundamental wave current component and the N × K harmonic current component in a phase relationship in which the absolute value of the extremum after synthesis is smaller than the absolute value of the extreme value of the fundamental wave current component. Supply to the winding,
A motor system characterized by that.
前記モータは、
前記基本波電流成分による回転磁界と前記鎖交磁束の前記基本波磁束成分とにより得られる基本波トルク成分と、
前記Ｎ×Ｋ次高調波電流成分による零相磁界と前記鎖交磁束の前記Ｎ×Ｋ次高調波磁束成分とにより得られるＮ×Ｋ次高調波トルク成分と、
を含んだトルクを発生し、
前記電流供給回路は、
トルクの増加を必要とする動作期間において、前記基本波トルク成分と前記Ｎ×Ｋ次高調波トルク成分が互いに同じ方向となる位相関係で、前記基本波電流成分と前記Ｎ×Ｋ次高調波電流成分が合成された電流を、前記Ｎ相巻線に供給する、
ことを特徴とするモータシステム。 In the motor system according to claim 1 or 2.
The motor
The fundamental wave torque component obtained by the rotating magnetic field due to the fundamental wave current component and the fundamental wave magnetic flux component of the interlinkage magnetic flux, and
The N × K harmonic torque component obtained by the zero-phase magnetic field due to the N × K harmonic current component and the N × K harmonic flux component of the interlinkage magnetic flux, and
Generates torque including
The current supply circuit
The fundamental wave current component and the N × K harmonic current in a phase relationship in which the fundamental wave torque component and the N × K harmonic torque component are in the same direction during an operation period requiring an increase in torque. A current in which the components are combined is supplied to the N-phase winding.
A motor system characterized by that.
前記ロータの永久磁石の開角が前記ステータのＮ相巻線の巻幅よりも小さい、
ことを特徴とするモータシステム。 In the motor system according to any one of claims 1 to 3.
The opening angle of the permanent magnet of the rotor is smaller than the winding width of the N-phase winding of the stator.
A motor system characterized by that.
前記ロータの突極の開角が当該ロータの永久磁石の開角よりも小さい、
ことを特徴とするモータシステム。 In the motor system according to any one of claims 1 to 4.
The opening angle of the salient pole of the rotor is smaller than the opening angle of the permanent magnet of the rotor.
A motor system characterized by that.
Priority Applications (2)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2019041200A JP7181817B2 (en) | 2019-03-07 | 2019-03-07 | motor system |
| PCT/JP2020/009411 WO2020179867A1 (en) | 2019-03-07 | 2020-03-05 | Motor system |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2019041200A JP7181817B2 (en) | 2019-03-07 | 2019-03-07 | motor system |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JP2020145865A true JP2020145865A (en) | 2020-09-10 |
| JP7181817B2 JP7181817B2 (en) | 2022-12-01 |
Family
ID=72338186
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP2019041200A Active JP7181817B2 (en) | 2019-03-07 | 2019-03-07 | motor system |
Country Status (2)
| Country | Link |
|---|---|
| JP (1) | JP7181817B2 (en) |
| WO (1) | WO2020179867A1 (en) |
Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| WO2024095475A1 (en) * | 2022-11-04 | 2024-05-10 | 日産自動車株式会社 | Motor control method and motor control device |
| JP7516284B2 (en) | 2021-02-05 | 2024-07-16 | 日本キヤリア株式会社 | Motor Drive Unit |
Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP2016042768A (en) * | 2014-08-18 | 2016-03-31 | 国立大学法人東京工業大学 | Motor system |
| JP2017103910A (en) * | 2015-12-01 | 2017-06-08 | 株式会社デンソー | Motor system |
-
2019
- 2019-03-07 JP JP2019041200A patent/JP7181817B2/en active Active
-
2020
- 2020-03-05 WO PCT/JP2020/009411 patent/WO2020179867A1/en active Application Filing
Patent Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP2016042768A (en) * | 2014-08-18 | 2016-03-31 | 国立大学法人東京工業大学 | Motor system |
| JP2017103910A (en) * | 2015-12-01 | 2017-06-08 | 株式会社デンソー | Motor system |
Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP7516284B2 (en) | 2021-02-05 | 2024-07-16 | 日本キヤリア株式会社 | Motor Drive Unit |
| WO2024095475A1 (en) * | 2022-11-04 | 2024-05-10 | 日産自動車株式会社 | Motor control method and motor control device |
Also Published As
| Publication number | Publication date |
|---|---|
| JP7181817B2 (en) | 2022-12-01 |
| WO2020179867A1 (en) | 2020-09-10 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| Dwari et al. | Fault-tolerant control of five-phase permanent-magnet motors with trapezoidal back EMF | |
| Yu et al. | Controllability and performance of a nine-phase FSPM motor under severe five open-phase fault conditions | |
| EP2412091B1 (en) | Electric motor system | |
| US8896178B2 (en) | Synchronous electric motor drive system having slit windings | |
| CN104682807B (en) | A kind of short-circuit fault tolerant control method of five mutually fault-tolerant magnetoes | |
| JP4629659B2 (en) | Synchronous electric machine having one stator and at least one rotor and related control device | |
| US7852037B2 (en) | Induction and switched reluctance motor | |
| JP2015509697A (en) | Synchronous electrical machine | |
| JP2019022299A (en) | Drive system of rotary electric machine | |
| WO2020179867A1 (en) | Motor system | |
| JP5466742B2 (en) | Generator winding | |
| JP2010136523A (en) | Drive control device for rotary electric machine | |
| JP6432579B2 (en) | Multi-phase winding and rotating electric machine | |
| Ai et al. | Novel direct flux and direct torque control of six-phase induction machine with nearly square air-gap flux density | |
| CN109980824B (en) | Electric motor, actuating unit and method for operating an electric motor | |
| Scuiller | Design of a 7-phase surface-mounted pm machine with tooth-concentrated winding | |
| JP2010028957A (en) | Inductor and inductor pole-number switching system | |
| JPH10225035A (en) | Armature winding | |
| CN110063018B (en) | Field winding type rotating electrical machine | |
| Sirewal et al. | A self-excitation scheme for a brushless synchronous generator | |
| JP2007189818A (en) | Current control method of synchronous motor | |
| Qu et al. | Design and analysis of a new consequent-pole interior permanent magnet synchronous motor | |
| JP2017139864A (en) | Rotary electric machine | |
| Jiang et al. | New direct torque control of five-phase fault-tolerant flux-switching permanent-magnet motor drives | |
| WO2019009195A1 (en) | Consequent motor |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| A621 | Written request for application examination |
Free format text: JAPANESE INTERMEDIATE CODE: A621 Effective date: 20210825 |
|
| A131 | Notification of reasons for refusal |
Free format text: JAPANESE INTERMEDIATE CODE: A131 Effective date: 20220830 |
|
| A521 | Request for written amendment filed |
Free format text: JAPANESE INTERMEDIATE CODE: A523 Effective date: 20221025 |
|
| TRDD | Decision of grant or rejection written | ||
| A01 | Written decision to grant a patent or to grant a registration (utility model) |
Free format text: JAPANESE INTERMEDIATE CODE: A01 Effective date: 20221101 |
|
| A61 | First payment of annual fees (during grant procedure) |
Free format text: JAPANESE INTERMEDIATE CODE: A61 Effective date: 20221118 |
|
| R150 | Certificate of patent or registration of utility model |
Ref document number: 7181817 Country of ref document: JP Free format text: JAPANESE INTERMEDIATE CODE: R150 |