JP2016082775A - Motor and driving method for motor - Google Patents

Abstract

PROBLEM TO BE SOLVED: To provide a motor which is capable of avoiding a dead point and improves startability and in which high torque can be expected.SOLUTION: The motor is a two-layer two-phase Lundell type motor that is configured by laminating a Lundell type A-phase motor and also a Lundell type B-phase motor in order. In a stator 3 of the motor, a B-phase stator 3b is deviated from at 45° of an electric angle θ1 in a clock-wise direction in a view from a side of the A-phase motor in an axial direction relatively to an A-phase stator 3a. In a rotor 2 of the motor, a B-phase rotor 2b is deviated at 45° of an electric angle θ2 in a counter-clock-wise direction in a view from the side of the A-phase motor in the axial direction relatively to an A-phase rotor 2a. Further, an A-phase input voltage to be applied to an annular coil 61 of the A-phase stator 3a is delayed with a phase difference at 90° relatively to a B-phase input voltage to be applied to an annular coil 61 of the B-phase stator 3b.SELECTED DRAWING: Figure 3

Description

  The present invention relates to a motor and a motor driving method.

  2. Description of the Related Art Conventionally, an outer rotor type motor is a Landel type motor in which windings are arranged between a SPM rotor having a permanent magnet attached to the surface of a rotor core and a pair of stator core bases having a plurality of claw-shaped magnetic poles at equal circumferential intervals. A brushless motor including a stator has been proposed (for example, Patent Document 1). In this brushless motor, the winding disposed between the pair of stator core bases has two types of windings laminated in the axial direction. The two types of windings are applied with different power sources of the first system and the second system, respectively.

JP 2005-192384 A

  By the way, this brushless motor is a two-phase motor in which a Landel-type stator is configured by a two-layer structure of a first system winding and a second system winding. Therefore, since it is a two-phase motor, there is a dead point and there is a problem in startability.

  By the way, windings are arranged between a Landel-type rotor in which field magnets are arranged between a pair of rotor cores having a plurality of claw-shaped magnetic poles in the circumferential direction and a pair of stator cores having a plurality of claw-shaped magnetic poles in the circumferential direction. There is a so-called multi-rundel type motor composed of the rundel type stator. A similar problem occurs in a two-layer, two-phase multi-Landel motor obtained by tandemizing this multi-Randel motor.

In addition, in a two-layer, two-phase multi-Landel type motor, the effect of leakage magnetic flux in the gap portion between adjacent claw-shaped magnetic poles is large, so that effective magnetic flux is reduced and high torque cannot be expected.
The present invention has been made to solve the above-described problems, and an object of the present invention is to provide a motor that can avoid a dead point and has excellent startability and high torque, and a method for driving the motor.

  A motor for solving the above problems includes an A-phase rotor in which an A-phase field magnet is arranged between a pair of A-phase rotor core bases having a plurality of claw-shaped magnetic poles at equal circumferential intervals, and an equal circumferential interval. A two-layer rotor in which a B-phase rotor having a B-phase field magnet disposed between a pair of B-phase rotor core bases having a plurality of claw-shaped magnetic poles and a plurality of claw-shaped magnetic poles at equal intervals in the circumferential direction A phase stator in which windings are arranged between a pair of A phase stator core bases and a B phase in which windings are arranged between a pair of B phase stator core bases having a plurality of claw-shaped magnetic poles at equal intervals in the circumferential direction A motor comprising a two-layer stator in which a stator is laminated, wherein a relative arrangement angle of the B-phase stator with respect to the A-phase stator in the clockwise direction in the circumferential direction is θ1 in electrical angle, and the motor with respect to the A-phase rotor Circumference of B-phase rotor When the .theta.2 in electrical angle relative placement angle in direction counterclockwise, θ1 + | θ2 | = 90 °, characterized in that the hold.

According to this configuration, it is possible to avoid dead points and improve startability.
In the above configuration, each of the winding wound around the A-phase stator and the winding wound around the B-phase stator includes two first annular windings and second annular windings, respectively. Power supplies having different phases are applied to the annular winding and the second annular winding, respectively.

According to this configuration, it is possible to suppress the ripple rate, improve the average torque, and improve the motor performance.
In the above configuration, the A-phase rotor and the B-phase rotor are at least one of a radial direction between the field magnet and the claw-shaped magnetic pole and a circumferential direction between the adjacent claw-shaped magnetic poles. An auxiliary magnet was interposed between the two.

  According to this configuration, by providing the auxiliary magnet, the magnetic flux generated between the claw-shaped magnetic pole of the rotor and the stator is increased, so that the effective magnetic flux can be further increased and the motor performance can be improved.

In the above configuration, the field magnet and the auxiliary magnet are integrally molded magnets.
According to this configuration, assembling becomes easy, and there is no possibility that the auxiliary magnet is dropped between the magnetic poles due to centrifugal force during rotation.

  A motor driving method for solving the above problems includes an A-phase rotor in which an A-phase field magnet is disposed between a pair of A-phase rotor core bases having a plurality of claw-shaped magnetic poles at equal circumferential intervals, A two-layer rotor in which a B-phase rotor having a B-phase field magnet disposed between a pair of B-phase rotor core bases having a plurality of claw-shaped magnetic poles at equal intervals in the direction, and a plurality of claws at equal intervals in the circumferential direction Windings are arranged between a pair of A-phase stator core bases having a plurality of claw-shaped magnetic poles at equal intervals in the circumferential direction, and a phase-A stator having windings arranged between a pair of A-phase stator core bases having a magnetic pole A method for driving a motor comprising a two-layer stator in which a B-phase stator is laminated, wherein the phase differs between the winding arranged in the A-phase stator and the winding arranged in the B-phase stator. A power supply is applied.

According to this configuration, it is possible to suppress the ripple rate, improve the average torque, and improve the motor performance.
In the above configuration, the phase difference between the power source applied to the windings of the A-phase stator and the power source applied to the windings of the B-phase stator is 75 ° to 90 °.

According to this configuration, it is possible to suppress the ripple rate, improve the average torque, and improve the motor performance.
In the above configuration, the motor is configured such that a relative arrangement angle of the B-phase stator with respect to the A-phase stator relative to the A-phase stator in the clockwise direction in the circumferential direction is θ1, and the A-phase When the relative arrangement angle of the B-phase stator in the counterclockwise direction in the circumferential direction with respect to the stator for the stator is θ2 in electrical angle, θ1 + | θ2 | = 90 degrees is established.

According to this configuration, it is possible to avoid dead points and improve startability.
A motor driving method for solving the above problems includes an A-phase rotor in which an A-phase field magnet is disposed between a pair of A-phase rotor core bases having a plurality of claw-shaped magnetic poles at equal circumferential intervals, A two-layer rotor in which a B-phase rotor having a B-phase field magnet disposed between a pair of B-phase rotor core bases having a plurality of claw-shaped magnetic poles at equal intervals in the direction, and a plurality of claws at equal intervals in the circumferential direction Windings are arranged between a pair of A-phase stator core bases having a plurality of claw-shaped magnetic poles at equal intervals in the circumferential direction, and a phase-A stator having windings arranged between a pair of A-phase stator core bases having a magnetic pole A motor driving method comprising a two-layer stator in which a B-phase stator is laminated, each of which has two windings wound around the A-phase stator and two windings wound around the B-phase stator. 1st system annular winding and 2nd system annular winding Will, with respect to the first system loop winding and the second system loop winding, respectively and applying power to different phases.

According to this configuration, it is possible to suppress the ripple rate, improve the average torque, and improve the motor performance.
In the above configuration, the power supply applied to the first system winding and the second system winding has a phase difference of 10 degrees to 40 degrees.

According to this configuration, it is possible to suppress the ripple rate, improve the average torque, and improve the motor performance.
In the above configuration, the motor has an electrical angle θ1 in the circumferential direction of the B-phase stator with respect to the A-phase stator, and is opposite to the circumferential direction of the B-phase rotor with respect to the A-phase rotor. When the relative arrangement angle in the clockwise direction is θ2 in electrical angle, θ1 + | θ2 | = 90 degrees is established.

  According to this configuration, it is possible to avoid dead points and improve startability.

  ADVANTAGE OF THE INVENTION According to this invention, a dead point can be avoided, the startability is excellent, and the motor which can expect high torque can be provided.

The perspective view of the motor of a 1st embodiment. Similarly, the exploded perspective view of the motor which cut a part of stator. Similarly, the exploded front view of the motor seen from the radial direction which cut a part of stator. Similarly, the perspective view of a single motor. Similarly, sectional drawing of the single motor seen from radial direction. Similarly, the exploded perspective view of the rotor which comprises a single motor. Similarly, the disassembled perspective view of the stator which comprises a single motor. Similarly, the drive control circuit diagram of a motor. Similarly, (a) is a waveform diagram of the B phase input voltage supplied to the B phase motor, and (b) is a waveform diagram of the A phase input voltage supplied to the A phase motor. Similarly, the graph which shows the average torque and ripple rate with respect to the phase difference of the input voltage of an A phase motor and a B phase motor. The disassembled perspective view of the motor which cut | disconnected a part of stator of 2nd Embodiment. Similarly, the drive control circuit diagram of a motor. Similarly, (a) is a waveform diagram of the first system input voltage supplied to the first system annular winding, and (b) is a waveform diagram of the second system input voltage supplied to the second system annular winding. Similarly, the graph which shows the average torque and ripple rate with respect to the phase difference of a 1st system input voltage and a 2nd system input voltage. The perspective view for demonstrating another example of a rotor. Similarly, the disassembled perspective view for demonstrating an interpole auxiliary magnet and a back auxiliary magnet.

(First embodiment)
Hereinafter, a first embodiment of a motor will be described with reference to FIGS.
FIG. 1 is an overall perspective view of a motor M of this embodiment, and a rotor 2 is fixed to a rotating shaft 1. A stator 3 fixed to a motor housing (not shown) is disposed outside the rotor 2.

  1, the motor M is a two-layer, two-phase multi-Landel motor in which a multi-Landel type A-phase motor Ma and a multi-Landel type B-phase motor Mb are sequentially stacked from the top. As shown in FIG. 4, the A-phase motor Ma and the B-phase motor Mb are each formed by a single multi-Landel motor M1.

(Rotor 2)
As shown in FIG. 2, the rotor 2 of the motor M is a rotor having a two-layer two-phase structure in which an A-phase rotor 2a and a B-phase rotor 2b having a Landell structure are stacked. The A-phase rotor 2a and the B-phase rotor 2b have the same configuration, and are each composed of a first rotor core 10, a second rotor core 20, and a field magnet 30, as shown in FIG.

(First rotor core 10)
As shown in FIG. 6, the first rotor core 10 has a first rotor core base 11 formed of an annular plate-shaped electromagnetic steel plate. A through hole 12 is formed at the center position of the first rotor core base 11 for penetrating and fixing the rotary shaft 1. Further, on the outer peripheral surface of the first rotor core base 11, eight first rotor side claw-shaped magnetic poles 13 having the same shape are projected radially outward, and the tip thereof is directed to the axial second rotor core 20 side. It is bent.

  Here, in the first rotor side claw-shaped magnetic pole 13, a portion protruding radially outward from the outer peripheral surface 11 a of the first rotor core base 11 is referred to as a first rotor side base portion 13 x, and a tip portion bent in the axial direction is referred to as a first portion. It is called 1 rotor side magnetic pole part 13y. And when the 1st rotor side base 13x is seen from an axial direction, the shape is formed in the trapezoid shape which becomes narrow as it goes to a radial direction outer side. Further, the shape of the first rotor-side magnetic pole portion 13y when viewed from the radial direction is a quadrangular shape. Furthermore, the circumferential end surfaces 13a and 13b of the first rotor-side claw-shaped magnetic pole 13 composed of the first rotor-side base portion 13x and the first rotor-side magnetic pole portion 13y are both flat surfaces.

  The first rotor-side magnetic pole part 13y bent in the axial direction has a fan-shaped cross section in the direction perpendicular to the axis. The radial outer side surface 13c and the radial inner side surface 13d of the first rotor-side magnetic pole portion 13y are concentric with the outer peripheral surface 11a of the first rotor core base 11 with the central axis O of the rotating shaft 1 as the center when viewed from the axial direction. It is the circular arc surface which makes.

  Moreover, the angle in the circumferential direction of the first rotor side base portion 13x of each first rotor side claw-shaped magnetic pole 13, that is, the angle between the base end portions of the circumferential end surfaces 13a and 13b and the central axis O of the rotary shaft 1 is It is set smaller than the angle of the gap between the adjacent first rotor side claw-shaped magnetic poles 13.

(Second rotor core 20)
As shown in FIG. 6, the second rotor core 20 has a second rotor core base 21 that is the same material and shape as the first rotor core 10 and is formed in an annular plate shape. A through hole 22 is formed at the center position of the second rotor core base 21 for penetrating and fixing the rotary shaft 1. Further, eight second rotor side claw-shaped magnetic poles 23 are projected radially outward on the outer peripheral surface of the second rotor core base 21 at equal intervals, and the tips thereof are bent toward the first rotor core 10 side in the axial direction. Yes.

  Here, in the second rotor-side claw-shaped magnetic pole 23, a portion protruding radially outward from the outer peripheral surface 21a of the second rotor core base 21 is referred to as a second rotor-side base portion 23x, and a tip portion bent in the axial direction is referred to as a first portion. This is called a 2-rotor side magnetic pole part 23y. And when the 2nd rotor side base 23x is seen from an axial direction, the shape is formed in the trapezoid shape which becomes narrow as it goes to a radial direction outer side. The shape of the second rotor-side magnetic pole portion 23y when viewed from the radial direction is a quadrangular shape. Furthermore, the circumferential end surfaces 23a and 23b of the second rotor-side claw-shaped magnetic pole 23 composed of the second rotor-side base portion 23x and the second rotor-side magnetic pole portion 23y are both flat surfaces.

  The second rotor-side magnetic pole part 23y bent in the axial direction has a fan-shaped cross section in the direction perpendicular to the axis. The radial outer side surface 23c and the radial inner side surface 23d are arcuate surfaces that are concentric with the outer peripheral surface 21a of the second rotor core base 21 with the central axis as the center when viewed from the axial direction.

  Further, the angle in the circumferential direction of the second rotor-side base portion 23x of each second rotor-side claw-shaped magnetic pole 23, that is, the angle between the base end portions of the circumferential end surfaces 23a and 23b and the central axis O of the rotating shaft 1 is It is set smaller than the angle of the gap between the adjacent second rotor side claw-shaped magnetic poles 23.

  In the second rotor core 20, the second rotor side claw-shaped magnetic pole 23 of the second rotor core 20 is compared with the first rotor core 10 in the first rotor side claw-shaped magnetic pole 13 of the first rotor core 10 when viewed from the axial direction. The arrangement is fixed so as to be located between them. At this time, the second rotor core 20 is assembled to the first rotor core 10 such that the field magnet 30 is disposed between the first rotor core 10 and the second rotor core 20 in the axial direction.

(Field magnet 30)
In this embodiment, the field magnet 30 is an annular plate-like permanent magnet made of a sintered ferrite magnet. As shown in FIG. 6, the field magnet 30 has a through hole 32 penetrating the rotary shaft 1 at the center position. The one side surface 30a of the field magnet 30 abuts the opposing surface 11b of the first rotor core base 11, and the other side surface 30b of the field magnet 30 abuts the opposing surface 21b of the second rotor core base 21, respectively. The magnet 30 is sandwiched and fixed between the first rotor core 10 and the second rotor core 20.

The outer diameter of the field magnet 30 is set to coincide with the outer diameters of the first and second rotor core bases 11 and 21, and the thickness is set to a predetermined thickness.
That is, as shown in FIG. 5, the field magnet 30 is disposed between the first rotor core 10 and the second rotor core 20. At this time, the front end surface 13e of the first rotor side claw-shaped magnetic pole 13 and the opposing surface 21b of the second rotor core base 21 are flush with each other, and the front end surface 23e of the second rotor side claw-shaped magnetic pole 23 and the first rotor core base. 11 facing surfaces 11b are flush with each other.

  As shown in FIG. 5, the field magnet 30 is magnetized in the axial direction, and is magnetized so that the first rotor core 10 side is an N pole and the second rotor core 20 side is an S pole. Therefore, by this field magnet 30, the first rotor side claw-shaped magnetic pole 13 of the first rotor core 10 functions as an N pole, and the second rotor side claw-shaped magnetic pole 23 of the second rotor core 20 functions as an S pole.

  As described above, the A-phase rotor 2 a and the B-phase rotor 2 b configured by the first and second rotor cores 10 and 20 and the field magnet 30 are so-called Randel type rotors using the field magnet 30. It becomes. In the A-phase rotor 2a and the B-phase rotor 2b, the first rotor-side claw-shaped magnetic poles 13 that are N poles and the second rotor-side claw-shaped magnetic poles 23 that are S poles are alternately arranged in the circumferential direction. Becomes a rotor with 16 poles (8 pairs of poles).

  As shown in FIGS. 2 and 3, the A-phase rotor 2a and the B-phase rotor 2b are stacked in the axial direction to form a two-layer, two-phase Landell-type rotor 2. Here, the A-phase rotor 2a and the B-phase rotor 2b are stacked and fixed to the rotating shaft 1 as follows.

  Specifically, the A-phase rotor 2a and the B-phase rotor 2b are composed of the second rotor core 20 (the opposite surface 21c of the second rotor core base 21) of the A-phase rotor 2a and the second rotor core 20 (second rotor core) of the B-phase rotor 2b. The base 21 is laminated so that the opposite surface 21c) contacts.

  Further, as shown in FIG. 3, the arrangement angle of the B-phase rotor 2b with respect to the A-phase rotor 2a is shifted by a predetermined angle in the counterclockwise direction when viewed from the axial A-phase motor Ma side. .

  More specifically, the second rotor-side claw-shaped magnetic pole 23 (first rotor) of the B-phase rotor 2b facing the second rotor-side claw-shaped magnetic pole 23 (first rotor-side claw-shaped magnetic pole 13) of the A-phase rotor 2a. Side claw-shaped magnetic poles 13) are stacked while being shifted by a predetermined electrical angle θ2 in the counterclockwise direction.

(Stator 3)
As shown in FIG. 2, the stator 3 disposed on the outer side in the radial direction of the rotor 2 is a two-layer two-phase structure in which an A-phase stator 3 a and a B-phase stator 3 b having a Landell structure are stacked. The A-phase stator 3a and the B-phase stator 3b are sequentially laminated in the axial direction so as to face the corresponding A-phase rotor 2a and B-phase rotor 2b on the radially inner side.

  The A-phase stator 3a and the B-phase stator 3b have the same configuration, and are each composed of a first stator core 40, a second stator core 50, and a coil portion 60, as shown in FIG.

(First stator core 40)
As shown in FIG. 7, the first stator core 40 has a first stator core base 41 formed of an annular plate-shaped electromagnetic steel plate. The first stator core base 41 is a facing surface 41b facing the second stator core 50, and a cylindrical first stator side cylindrical outer wall 42 extends toward the axial second stator core 50 side on the radially outer side thereof. Is formed. Further, eight first stator side claw-shaped magnetic poles 43 are projected radially inwardly on the inner peripheral surface 41a of the first stator core base 41, and the tips thereof are bent toward the second stator core 50 side in the axial direction. Is formed.

  Here, in the first stator side claw-shaped magnetic pole 43, a portion protruding radially inward from the inner peripheral surface 41a of the first stator core base 41 is called a first stator side base portion 43x, and a tip portion bent in the axial direction is called a first stator side base portion 43x. This is referred to as a first stator side magnetic pole portion 43y. And when the 1st stator side base part 43x is seen from an axial direction, it is formed in the trapezoid shape which becomes narrow as it goes to radial direction inner side. Further, the shape of the first stator side magnetic pole portion 43y when viewed from the radial direction is a quadrangular shape. Further, the circumferential end surfaces 43a and 43b of the first stator side claw-shaped magnetic pole 43 including the first stator side base portion 43x and the first stator side magnetic pole portion 43y are both flat surfaces.

  The first stator side magnetic pole portion 43y bent in the axial direction has a fan-shaped cross section in the direction perpendicular to the axis. The radially outer side surface 43c and the radially inner side surface 43d of the first stator side magnetic pole portion 43y are concentric with the inner peripheral surface 41a of the first stator core base 41 with the central axis O as the center when viewed from the axial direction. Surface.

  The circumferential angle of the first stator side base portion 43x of each first stator side claw-shaped magnetic pole 43, that is, the angle formed between the base end portions of the circumferential end surfaces 43a and 43b and the central axis O of the rotating shaft 1 is adjacent. It is set smaller than the angle of the gap between the first stator side claw-shaped magnetic poles 43.

(Second stator core 50)
As shown in FIG. 7, the second stator core 50 has an annular plate-like second stator core base 51 having the same material and shape as the first stator core base 41. The second stator core base 51 is a facing surface 51b that faces the first stator core 40, and a cylindrical second stator-side cylindrical outer wall 52 extends from the radially outer portion thereof. The second stator side cylindrical outer wall 52 comes into contact with the first stator side cylindrical outer wall 42 in the axial direction.

  On the inner peripheral surface 51a of the second stator core base 51, eight second stator side claw-shaped magnetic poles 53 are protruded radially inward at equal intervals, and the tips thereof are bent toward the first stator core 40 in the axial direction. ing.

  Here, in the second stator side claw-shaped magnetic pole 53, a portion protruding radially inward from the inner peripheral surface 51a of the second stator core base 51 is referred to as a second stator side base portion 53x, and a tip portion bent in the axial direction is referred to as a second stator side base portion 53x. This is referred to as a second stator side magnetic pole portion 53y. And when the 2nd stator side base 53x is seen from an axial direction, it is formed in the trapezoid shape which becomes narrow as it goes to radial direction inner side. Further, the shape of the second stator side magnetic pole portion 53y when viewed from the radial direction is a quadrangular shape. Furthermore, circumferential end surfaces 53a and 53b of the second stator side claw-shaped magnetic pole 53 composed of the second stator side base portion 53x and the second stator side magnetic pole portion 53y are both flat surfaces.

  The second stator-side magnetic pole portion 53y that is bent in the axial direction has a fan-shaped cross section in the direction perpendicular to the axis. The radially outer side surface 53c and the radially inner side surface 53d of the second stator side magnetic pole portion 53y are concentric with the inner peripheral surface 51a of the second stator core base 51 around the central axis O when viewed from the axial direction. Surface.

  The circumferential angle of the second stator side base portion 53x of each second stator side claw-shaped magnetic pole 53, that is, the angle between the base end portions of the circumferential end surfaces 53a and 53b and the central axis O of the rotating shaft 1 is adjacent. It is set smaller than the angle of the gap between the second stator side claw-shaped magnetic poles 53.

  That is, by forming in this way, the shape of the second stator core 50 becomes the same shape as the first stator core 40. Then, the first stator side cylindrical outer wall 42 formed on the first stator core base 41 and the second stator side cylindrical outer wall 52 formed on the second stator core base 51 are brought into contact with each other. At this time, the second stator core 50 includes the second stator side cylindrical outer wall 52 so that each second stator side claw-shaped magnetic pole 53 is positioned between the first stator side claw-shaped magnetic poles 43 as viewed from the axial direction. One stator side cylindrical outer wall 42 is brought into contact.

  The first stator side claw-shaped magnetic pole 43 is set at a position where the front end surface 43e of the first stator side magnetic pole portion 43y is flush with the opposing surface 51b of the second stator core base 51. Similarly, the second stator side claw-shaped magnetic pole 53 is set at a position where the front end surface 53e of the second stator side magnetic pole portion 53y is flush with the opposing surface 41b of the first stator core base 41.

  In this state, an annular space having a quadrangular cross section is formed which is defined by the opposing surfaces 41b and 51b of the first and second stator core bases 41 and 51 and the inner peripheral surfaces of the first and second stator side cylindrical outer walls 42 and 52. The And the coil part 60 is arrange | positioned and fixed in the cyclic | annular space of the cross-sectional square shape.

(Coil 60)
As shown in FIGS. 5 and 7, the coil portion 60 has an annular winding 61. The circumference of the annular winding 61 is covered with a coil insulating layer 62 with a resin mold. For convenience of explanation, the coil insulating layer 62 is omitted in FIG.

  Further, as shown in FIG. 5, the outer surface on the first stator core 40 side in the axial direction of the coil portion 60 is in contact with the facing surface 41 b of the first stator core base 41, and is in the axial direction of the coil portion 60. The outer surface on the second stator core 50 side comes into contact with the facing surface 51 b of the second stator core base 51.

The thickness (axial length) of the coil portion 60 is set to a predetermined thickness according to the axial length of the first stator side claw-shaped magnetic pole 43 (second stator side claw-shaped magnetic pole 53). Has been.
That is, as shown in FIG. 5, the coil portion 60 is disposed between the first stator core 40 and the second stator core 50. At this time, the front end surface 43e of the first stator side claw-shaped magnetic pole 43 and the opposing surface 51b of the second stator core base 51 are flush with each other, and the front end surface 53e of the second stator side claw-shaped magnetic pole 53 and the first stator core base 41 are aligned. The opposite surface 41b is flush with the opposite surface 41b.

  Further, at this time, the axial length from the anti-facing surface 41 c of the first stator core base 41 to the anti-facing surface 51 c of the second stator core base 51 is from the anti-facing surface 11 c of the first rotor core base 11 to the second rotor core base 21. It is made to correspond with the length of the axial direction to the anti-opposing surface 21c.

  Therefore, the axial length of the first stator side claw-shaped magnetic pole 43 (second stator side claw-shaped magnetic pole 53) is the axial length of the first rotor side claw-shaped magnetic pole 13 (second rotor side claw-shaped magnetic pole 23). Match the length.

  In FIG. 7, the drawing terminal of the annular winding 61 is omitted in the drawing for convenience of explanation. In accordance with this, notches for drawing out terminal mounting portions formed on the cylindrical outer walls 42 and 52 of the first and second stator cores 40 and 50 to the outside are omitted in the drawing.

  As described above, the A-phase stator 3a and the B-phase stator 3b configured by the first and second stator cores 40 and 50 and the coil section 60 are so-called Landel type stators. More specifically, the A-phase stator 3a and the B-phase stator 3b are configured such that the first and second stator side claw-shaped magnetic poles 43 and 53 are sometimes mutually connected by an annular winding 61 between the first and second stator cores 40 and 50. A 16-pole stator having a so-called Randel structure that excites different magnetic poles.

  As shown in FIGS. 2 and 3, the A-phase stator 3a and the B-phase stator 3b are laminated in the axial direction to form a two-layer two-phase Landell-type stator 3. The A-phase stator 3a and the B-phase stator 3b are stacked as follows and fixed to the motor housing.

  Specifically, the A-phase stator 3a and the B-phase stator 3b are composed of the second stator core 50 (the opposite surface 51c of the second stator core base 51) of the A-phase stator 3a and the second stator core 50 (second stator core) of the B-phase stator 3b. The base 51 is laminated so that the opposite surface 51c) contacts.

  Further, as shown in FIG. 3, the arrangement angle of the B-phase stator 3b with respect to the A-phase stator 3a is shifted by a predetermined angle in the clockwise direction when viewed from the axial A-phase motor Ma side.

  Specifically, the first stator side claw-shaped magnetic pole 43 (second stator) of the B-phase stator 3b facing the first stator side claw-shaped magnetic pole 43 (second stator side claw-shaped magnetic pole 53) of the A-phase stator 3a. Side claw-shaped magnetic poles 53) are laminated while being shifted by a predetermined electrical angle θ1 in the clockwise direction.

  Here, as viewed from the axial A-phase stator side, the electrical angle θ1 in the clockwise direction of the B-phase stator 3b with respect to the A-phase stator 3a and the electrical power in the counterclockwise direction of the B-phase rotor 2b with respect to the A-phase rotor 2a described above. The angle θ2 is set so that the following relational expression is established.

θ1 + | θ2 | = 90 degrees (electrical angle)
In order to avoid the dead point of the two-phase motor and improve the startability, the electrical angles θ1 and θ2 are set based on the above relational expression.

  In this embodiment, the electrical angle θ2 in the counterclockwise direction of the B-phase rotor 2b with respect to the A-phase rotor 2a is set to −45 degrees (counterclockwise direction), and the clock of the B-phase stator 3b with respect to the A-phase stator 3a is set. The electrical angle θ1 in the rotation direction is set to 45 degrees (clockwise direction).

In this embodiment, the electrical angle θ2 is set to −45 degrees and the electrical angle θ1 is set to 45 degrees (clockwise direction). However, the electrical angle θ2 may be appropriately changed within the range in which the above relational expression is satisfied.
The A-phase input voltage va of the two-phase AC power supply is applied to the annular winding 61 of the A-phase stator 3a, and the B-phase input of the two-phase AC power supply is applied to the annular winding 61 of the B-phase stator 3b. A voltage vb is applied.

Next, a drive control circuit for the two-layer two-phase Landell motor M configured as described above will be described with reference to FIG.
As shown in FIG. 8, the drive control circuit includes an A-phase drive circuit unit 71, a B-phase drive circuit unit 72, and a control circuit 73 that controls the drive of both the drive circuit units 71 and 72.

(A phase drive circuit unit 71)
The A-phase drive circuit unit 71 is a known H-type bridge circuit to which a DC power supply G of 12 volts is applied, and includes four MOS transistors Qa1, Qa2, Qa3, and Qa4. The four MOS transistors Qa1 to Qa4 are composed of a pair of MOS transistors Qa1 and Qa4 connected in a hanging manner with a ring winding 61 of the A-phase stator 3a (hereinafter referred to as A-phase ring winding 61a) and a MOS transistor. It is divided into a set of Qa2 and Qa3. The A-phase annular winding 61a is energized by alternately turning on and off the two sets.

  That is, by turning on the pair of MOS transistors Qa1 and Qa4 and turning off the pair of MOS transistors Qa2 and Qa3, the current flows in the direction of the arrow shown in FIG. 8 with respect to the A-phase annular winding 61a (A-phase annular winding 61a). Flow from the winding end Pa1 toward the winding end Pa2. More specifically, the current flowing through the A-phase annular winding 61a flows in the clockwise direction when viewed from the axial A-phase motor Ma side.

  Conversely, by turning off the pair of MOS transistors Qa1 and Qa4 and turning on the pair of MOS transistors Qa2 and Qa3, the current flows in the direction opposite to the arrow direction shown in FIG. It flows from the winding end Pa2 to the winding end Pa1 of the A-phase annular winding 61a. More specifically, the current flowing through the A-phase annular winding 61a flows in the counterclockwise direction when viewed from the axial A-phase motor Ma side.

(B-phase drive circuit unit 72)
The B-phase drive circuit unit 72 is a known H-type bridge circuit to which the DC power supply G is applied, and has four MOS transistors Qb1, Qb2, Qb3, and Qb4. The four MOS transistors Qb1 to Qb4 are composed of a pair of MOS transistors Qb1 and Qb4 connected in a hanging manner with the annular winding 61 of the B-phase stator 3b (hereinafter referred to as B-phase annular winding 61b) sandwiched between the MOS transistors It is divided into a set of Qb2 and Qb3. Then, the B-phase annular winding 61b is energized by alternately turning on and off the two sets.

  That is, by turning on the pair of MOS transistors Qb1 and Qb4 and turning off the pair of MOS transistors Qb2 and Qb3, the current flows in the direction of the arrow shown in FIG. 8 with respect to the B-phase annular winding 61b (B-phase annular winding 61b). Flow from the winding end Pb1 toward the winding end Pb2. More specifically, the current flowing through the B-phase annular winding 61b flows in the clockwise direction when viewed from the axial A-phase motor Ma side.

  Conversely, by turning off the pair of MOS transistors Qb1 and Qb4 and turning on the pair of MOS transistors Qb2 and Qb3, the current flows in the direction opposite to the arrow direction shown in FIG. The B-phase annular winding 61b flows from the winding end Pb2 toward the winding end Pb1. More specifically, the current flowing through the B-phase annular winding 61b flows in the counterclockwise direction when viewed from the axial A-phase motor Ma side.

(Control circuit 73)
The control circuit 73 generates drive signals Sa1 to Sa4 to be output to the gate terminals of the MOS transistors Qa1 to Qa4 of the A phase drive circuit unit 71, respectively. That is, the control circuit 73 alternately turns on / off the set of the MOS transistors Qa1 and Qa4 and the set of the MOS transistors Qa2 and Qa3 to generate the drive signals Sa1 to Sa4 that energize the A-phase annular winding 61a.

  More specifically, the control circuit 73 outputs drive signals Sa1 and Sa4 having the same pulse waveform to the gate terminals of one pair of MOS transistors Qa1 and Qa4, respectively. The control circuit 73 outputs drive signals Sa2 and Sa3 having the same pulse waveform to the gate terminals of the other pair of MOS transistors Qa2 and Qa3 and complementary signals to the drive signals Sa1 and Sa4, respectively. Accordingly, one set of MOS transistors Qa1 and Qa4 and the other set of MOS transistors Qa2 and Qa3 are alternately turned on and off to energize the A-phase annular winding 61a.

  FIG. 9B shows a voltage waveform of the A-phase input voltage va applied to the A-phase annular winding 61a. Here, when a potential of the A-phase input voltage va (= + 12 volts) is applied to the winding end Pa1 of the A-phase annular winding 61a, a potential of 0 V is applied to the winding end Pa2 of the A-phase annular winding 61a. The current flowing through the line 61a flows in the clockwise direction when viewed from the axial A-phase motor Ma side. Conversely, when a potential of 0 volt is applied to the winding end Pa1 and a potential of the A-phase input voltage va (= -12 volts) is applied to the winding end Pa2, the current flowing through the A-phase annular winding 61a is the axial A-phase motor. It flows in the counterclockwise direction when viewed from the Ma side.

  The control circuit 73 generates drive signals Sb1 to Sb4 that are output to the gate terminals of the MOS transistors Qb1 to Qb4 of the B-phase drive circuit unit 72, respectively. That is, the control circuit 73 alternately turns on / off the pair of MOS transistors Qb1, Qb4 and the pair of MOS transistors Qb2, Qb3, and generates drive signals Sb1-Sb4 that energize the B-phase annular winding 61b.

  More specifically, the control circuit 73 outputs drive signals Sb1 and Sb4 having the same pulse waveform to the gate terminals of one set of MOS transistors Qb1 and Qb4, respectively. The control circuit 73 outputs drive signals Sb2 and Sb3 having the same pulse waveform to the gate terminals of the other pair of MOS transistors Qb2 and Qb3, which are complementary to the drive signals Sb1 and Sb4, respectively. Accordingly, one set of MOS transistors Qb1 and Qb4 and the other set of MOS transistors Qb2 and Qb3 are alternately turned on and off to energize the B-phase annular winding 61b.

  FIG. 9A shows a voltage waveform of the B-phase input voltage vb applied to the B-phase annular winding 61b. Here, when the potential of the B-phase input voltage vb (= + 12 volts) is applied to the winding end Pb1 of the B-phase annular winding 61b and the potential of 0 volts is applied to the winding end Pb2 of the B-phase annular winding 61b, The current flowing through the winding 61b flows in the clockwise direction when viewed from the axial A-phase motor Ma side. Conversely, when a potential of 0 volt is applied to the winding end Pb1 and a potential of the B phase input voltage vb (= −12 volts) is applied to the winding end Pb2, the current flowing in the B phase annular winding 61b is the axial A phase motor. It flows in the counterclockwise direction when viewed from the Ma side.

  Here, as shown in FIGS. 9A and 9B, the control circuit 73 uses the same frequency for the A-phase and B-phase input voltages va and vb applied to the A-phase and B-phase annular windings 61a and 61b, respectively. I have to. In addition, the control circuit 73 controls the A-phase and B-phase drive circuit units 71 and 72 to shift the phase of the A-phase input voltage va with respect to the B-phase input voltage vb.

  More specifically, as shown in FIGS. 9A and 9B, in this embodiment, the phase of the A-phase input voltage va is delayed with respect to the B-phase input voltage vb, and the phase difference θd is set to this embodiment. Then, it is 90 degrees.

Next, the operation of the motor M configured as described above will be described.
Now, the A phase input voltage va and the B phase input voltage vb are applied to the motor M. That is, the A-phase input voltage va is applied to the annular winding 61a of the A-phase stator 3a, and the B-phase input voltage vb is applied to the annular winding 61b of the B-phase stator 3b. As a result, a rotating magnetic field is generated in the stator 3 and the rotor 2 is driven to rotate.

  At this time, the stator 3 has a two-layer structure of an A-phase stator 3a and a B-phase stator 3b in accordance with the A-phase input voltage va and the B-phase input voltage vb. Correspondingly, the rotor 2 has a two-layer structure of an A-phase rotor 2a and a B-phase rotor 2b. Thereby, in each of the stators 3a, 3b and the rotors 2a, 2b of each phase, the stators facing each other along the axial direction can receive the magnetic flux of the field magnet 30, respectively, and the output can be increased.

  By the way, for example, in a Landell type rotor in which U-phase, V-phase, and W-phase rotors are stacked in a three-layer structure, the U-phase, V-phase, and W-phase rotor field magnets have two phase rotors. The field magnets have the same magnetization direction, and the remaining one-phase field magnet has the opposite magnetization direction. For this reason, in the relationship between the U-phase, V-phase, and W-phase rotors, there is a difference in magnitude in the magnetic fluxes of the claw-shaped magnetic poles of each phase, and the magnetic balance is largely disturbed as a whole.

  In contrast, in the present embodiment, the rotor 2 has a two-layer structure of an A-phase rotor 2a and a B-phase rotor 2b. In the A-phase rotor 2a and the B-phase rotor 2b, the magnetization directions of the respective field magnets 30 are opposite to each other, and the claw-shaped magnetic poles 13 and 23 are in the relationship between the A-phase rotor 2a and the B-phase rotor 2b. Magnetic disturbance is small.

  Thereby, since the disturbance of the magnetic balance of the claw-shaped magnetic poles 43 and 53 formed on the opposing A-phase stator 3a and B-phase stator 3b can be reduced, the motor performance can be improved.

  Moreover, in the present embodiment, the electrical angle θ1 at which the B-phase stator 3b is shifted in the clockwise direction with respect to the A-phase stator 3a, and the electrical angle θ2 at which the B-phase rotor 2b is shifted in the counterclockwise direction with respect to the A-phase rotor 2a. Was set to a value determined by θ1 + | θ2 | = 90 degrees (electrical angle).

  More specifically, the stator 3 shifts the B-phase stator 3b with respect to the A-phase stator 3a by a predetermined electrical angle θ1 (= 45 degrees) in the clockwise direction when viewed from the axial A-phase motor Ma side. On the other hand, the rotor 2 shifts the B-phase rotor 2b with respect to the A-phase rotor 2a by a predetermined electrical angle θ2 (= 45 degrees) in a counterclockwise direction when viewed from the axial A-phase motor Ma side.

As a result, it is possible to avoid dead points that cannot be started in the two-phase motor and to improve startability.
Moreover, the movement of the rotor 2 with respect to the switching of the first and second stator side claw-shaped magnetic poles 43 and 53 due to the respective currents flowing through the A-phase and B-phase annular windings 61a and 61b of the A-phase and B-phase stators 3a and 3b. Since the amount (rotation amount) can be increased, the number of rotations can be increased.

Further, the A-phase input voltage va of the A-phase stator 3a of the stator 3 is delayed with a phase difference θd of 90 degrees with respect to the B-phase input voltage vb of the B-phase stator 3b.
That is, leakage magnetic flux is generated between the claw-shaped magnetic poles 13 and 23 of the A-phase and B-phase rotors 2a and 2b, and the effective magnetic flux is reduced. This leakage magnetic flux distorts the magnetic flux distribution, causing vibration and lowering the output. Therefore, in this embodiment, the A-phase input voltage va of the A-phase stator 3a and the B-phase input voltage vb of the B-phase stator 3b are given a 90-degree phase difference θd to suppress vibration of the motor M and Improved.

  Incidentally, the phase difference θd was changed from 70 degrees to 100 degrees, and the ripple rate and the average torque with respect to the phase difference θd at that time were verified. FIG. 10 shows the verification result. In the verification, the ripple rate and average torque at the phase difference θd of 70 degrees to 100 degrees were obtained with the reference (100%) when the phase difference θd was 90 degrees.

  As is clear from FIG. 10, the ripple rate indicated by the characteristic line L1 decreases as the phase difference θd increases from 70 degrees to 82 degrees, and the phase difference θd decreases from 82 degrees to 100 degrees. Until the phase difference θd increases. Therefore, it can be seen that the minimum ripple rate is obtained by setting the phase difference θd to 82 degrees.

As is clear from FIG. 10, the average torque indicated by the characteristic line L2 decreases as the phase difference θd increases as the phase difference θd increases from 70 degrees to 100 degrees.
Therefore, in order to suppress the ripple rate to 100% or less and keep the average torque at 100% or more, the phase difference θd may be set in the range of 75 degrees to 90 degrees, and the motor performance is improved. You can see that

  Further, the A-phase driving circuit unit 71 that drives (energizes) the A-phase annular winding 61a and the B-phase driving circuit unit 72 that drives (energizes) the B-phase annular winding 61b are configured by an H-type bridge circuit. . The A-phase and B-phase input voltages va and vb applied to the A-phase annular winding 61a and the B-phase annular winding 61b can be applied in a full range of +12 volts to -12 volts. Therefore, even a two-layer, two-phase multi-Landel motor M can be a high-output motor.

As described above in detail, the first embodiment has the following effects.
(1) According to the above embodiment, the motor M is a two-layer, two-phase motor, that is, the stator 3 has a two-stage structure of the A-phase and B-phase stators 3a and 3b, and the rotor 2 correspondingly. The A-phase and B-phase rotors 2a and 2b have the same two-stage structure. The A-phase input voltage va was applied to the A-phase stator 3a, and the B-phase input voltage vb was applied to the B-phase stator 3a. In each phase of the stators 3a, 3b and the rotors 2a, 2b, the stators 3a, 3b opposed in the axial direction can individually receive the magnetic fluxes of the field magnets 30 of the rotors 2a, 2b, respectively. Therefore, the output of the motor M can be increased.

  In addition, the A-phase rotor 2a and the B-phase rotor 2b are configured in a two-layer structure, and the field magnets 30 of the A-phase rotor 2a and the field magnet 30 of the B-phase rotor 2b have opposite magnetization directions. It comprised so that it might become. Therefore, the disturbance of the magnetic balance of the claw-shaped magnetic poles 13 and 23 can be reduced by the A-phase rotor 2a and the B-phase rotor 2b, and the motor performance can be improved.

  (2) According to the above embodiment, the stator 3 shifts the B-phase stator 3b with respect to the A-phase stator 3a by an electrical angle θ1 (= 45 degrees) in the clockwise direction when viewed from the axial A-phase motor Ma side. It was. Moreover, the rotor 2 shifted the electrical angle θ2 (= 45 degrees) from the A-phase rotor 2a in the counterclockwise direction when the B-phase rotor 2b is viewed from the axial A-phase motor Ma side.

As a result, it is possible to avoid dead points that cannot be started in the two-phase motor and to improve startability.
Moreover, the movement of the rotor 2 with respect to the switching of the first and second stator side claw-shaped magnetic poles 43 and 53 due to the respective currents flowing in the A phase and B phase annular windings 61a and 61b of the A phase and B phase stators 3a and 3b. Since the amount (rotation amount) can be increased, the number of rotations can be increased.

  (3) According to the above embodiment, the A-phase input voltage va of the A-phase stator 3a of the stator 3 has a phase difference θd of 75 to 90 degrees with respect to the B-phase input voltage vb of the B-phase stator 3b. Delayed. As a result, the ripple rate can be suppressed to 100% or less, and the average torque can be kept to 100% or more to improve the motor performance.

  (4) According to the above embodiment, the A-phase and B-phase drive circuit units 71 and 72 are configured by an H-type bridge circuit, and applied to the A-phase and B-phase annular windings 61a and 61b. The input voltages va and vb can be applied in a full range of +12 volts to -12 volts. Therefore, even a two-layer, two-phase multi-Landel motor M can be a high-output motor.

(Second Embodiment)
Next, a second embodiment of the motor M having a two-layer two-phase structure will be described.
In addition, since this embodiment differs only in the structure of the annular winding 61 of the coil part 60 of the A-phase and B-phase stators 3a and 3b of the first embodiment, the different parts will be described in detail for convenience of explanation. To do.

  As shown in FIG. 11, in the A-phase and B-phase stators 3a and 3b, a coil insulating layer 62 is provided in an annular space formed between the first and second stator core bases 41 and 51 of each phase and having a quadrangular cross section. The covered first system annular winding 61x and second system annular winding 61y are respectively provided.

  The first system annular winding 61x and the second system annular winding 61y of the A phase and the B phase are laminated in the axial direction. A-phase and B-phase first system annular winding 61x is disposed on the first stator core 40 side of the phase, and A-phase and B-phase second system winding 61y is on the second stator core 50 side of the phase. Is arranged.

  FIG. 12 shows a drive control circuit for the motor M that energizes the first and second phase annular windings 61x and 61y of the A phase and the B phase. In FIG. 12, reference numeral “61x” indicates the whole of the A-phase and B-phase first-system annular windings 61x connected in series, and reference numeral “61y” indicates the A-phase and B-phase second-system annular windings 61y. The whole is connected in series.

  In this embodiment, the A-phase and B-phase first-system annular windings 61x are connected in series, and the A-phase and B-phase second-system annular windings 61y are connected in series so that the A-phase and B-phase are connected. The first system annular winding 61x and the A-phase and B-phase second system annular winding 61y are driven and controlled.

  The A-phase and B-phase first system annular windings 61x are connected in parallel, and the A-phase and B-phase second system annular windings 61y are connected in parallel, so that the A-phase and B-phase first systems The annular winding 61x and the A-phase and B-phase second system annular winding 61y may be driven and controlled.

Alternatively, the drive control may be performed for each of the first system annular winding 61x of the A phase and the B phase and for each of the second system annular winding 61y of the A phase and the B phase.
The first-system annular winding 61x is applied with a 12-volt DC power supply G in a first-system drive circuit section 81 including a known H-type bridge circuit having four MOS transistors Qa1, Qa2, Qa3, and Qa4. Is done. The four MOS transistors Qa1 to Qa4 are divided into a pair of MOS transistors Qa1 and Qa4 and a pair of MOS transistors Qa2 and Qa3 that are connected to each other across the first system annular winding 61x. Then, the first system annular winding 61x is energized by alternately turning on and off the two sets.

  That is, by turning on the pair of MOS transistors Qa1 and Qa4 and turning off the pair of MOS transistors Qa2 and Qa3, the current flows in the direction indicated by the arrow in FIG. It flows from the winding end Px1 of 61x toward the winding end Px2. More specifically, currents flowing in the first system annular winding 61x in the A-phase and B-phase motors Ma and Mb flow in the clockwise direction when viewed from the axial A-phase motor Ma side.

  Conversely, by turning off the pair of MOS transistors Qa1 and Qa4 and turning on the pair of MOS transistors Qa2 and Qa3, the current flows in the direction opposite to the arrow direction shown in FIG. It flows from the winding end Px2 of the one-system annular winding 61x toward the winding end Px1. More specifically, the current flowing through the first system annular winding 61x in the A-phase and B-phase motors Ma and Mb flows counterclockwise when viewed from the axial A-phase motor Ma side.

  On the other hand, the DC power supply G is applied to the second system annular winding 61y by a second system drive circuit unit 82 comprising a known H-type bridge circuit having four MOS transistors Qb1, Qb2, Qb3, and Qb4. The The four MOS transistors Qb1 to Qb4 are divided into a pair of MOS transistors Qb1 and Qb4 and a pair of MOS transistors Qb2 and Qb3 that are connected in a hanging manner with the second ring winding 61y interposed therebetween. The second system annular winding 61y is energized by alternately turning on and off the two sets.

  That is, by turning on the pair of MOS transistors Qb1 and Qb4 and turning off the pair of MOS transistors Qb2 and Qb3, the current flows in the direction indicated by the arrow in FIG. 61y flows from the winding end Py1 toward the winding end Py2. More specifically, the currents flowing through the second system annular winding 61y in the A-phase and B-phase motors Ma and Mb both flow in the clockwise direction when viewed from the axial A-phase motor Ma side.

  Conversely, by turning off the pair of MOS transistors Qb1 and Qb4 and turning on the pair of MOS transistors Qb2 and Qb3, the current flows in the direction opposite to the arrow direction shown in FIG. Flows from the winding end Py2 of the two-system annular winding 61y toward the winding end Py1. More specifically, currents flowing through the second system annular winding 61y in the A-phase and B-phase motors Ma and Mb flow counterclockwise as viewed from the axial A-phase motor Ma side.

  The control circuit 83 generates drive signals Sa1 to Sa4 to be output to the gate terminals of the MOS transistors Qa1 to Qa4 of the first system drive circuit unit 81, respectively. That is, the control circuit 83 alternately turns on / off the set of the MOS transistors Qa1 and Qa4 and the set of the MOS transistors Qa2 and Qa3 to generate the drive signals Sa1 to Sa4 that energize the first system annular winding 61x.

  More specifically, the control circuit 83 outputs drive signals Sa1 and Sa4 having the same pulse waveform to the gate terminals of one set of MOS transistors Qa1 and Qa4, respectively. In addition, the control circuit 83 outputs drive signals Sa2 and Sa3 having the same pulse waveform to the gate terminals of the other pair of MOS transistors Qa2 and Qa3 and being complementary to the drive signals Sa1 and Sa4, respectively. Accordingly, one set of MOS transistors Qa1 and Qa4 and the other set of MOS transistors Qa2 and Qa3 are alternately turned on and off to energize the first system annular winding 61x of each phase.

  FIG. 13A shows a voltage waveform of the first system input voltage vx applied to the first system annular winding 61x. Here, when the potential of the first system input voltage vx (= + 12 volts) is applied to the winding end Px1 of the first system annular winding 61x and the potential of 0 volts is applied to the winding end Px2 of the first system annular winding 61x, The current flowing through the first system annular winding 61x flows in the clockwise direction when viewed from the axial A-phase motor Ma side. Conversely, when a potential of 0 volt is applied to the winding end Px1 and a potential of the first system input voltage vx (= −12 volts) is applied to the winding end Px2, the current flowing through the first system annular winding 61x is As viewed from the phase motor Ma side, it flows in the counterclockwise direction.

  The control circuit 83 generates drive signals Sb1 to Sb4 that are output to the gate terminals of the MOS transistors Qb1 to Qb4 of the second system drive circuit section 82, respectively. That is, the control circuit 83 alternately turns on / off the pair of MOS transistors Qb1 and Qb4 and the pair of MOS transistors Qb2 and Qb3, and generates drive signals Sb1 to Sb4 for energizing the second system annular winding 61y.

  More specifically, the control circuit 83 outputs drive signals Sb1 and Sb4 having the same pulse waveform to the gate terminals of one set of MOS transistors Qb1 and Qb4, respectively. Further, the control circuit 83 outputs drive signals Sb2 and Sb3 having the same pulse waveform to the gate terminals of the other pair of MOS transistors Qb2 and Qb3, which are complementary signals to the drive signals Sb1 and Sb4, respectively. Accordingly, one set of MOS transistors Qb1 and Qb4 and the other set of MOS transistors Qb2 and Qb3 are alternately turned on and off to energize the second system annular winding 61y.

  FIG. 13B shows a voltage waveform of the second system input voltage vy applied to the second system annular winding 61y. Here, when the potential of the second system input voltage vy (= + 12 volts) is applied to the winding end Py1 of the second system annular winding 61y and the potential of 0 volts is applied to the winding end Py2 of the second system annular winding 61y, The current flowing through the second system annular winding 61y flows in the clockwise direction when viewed from the axial A-phase motor Ma side. Conversely, when a potential of 0 volt is applied to the winding end Py1 and a potential of the second system input voltage vy (= −12 volts) is applied to the winding end Py2, the current flowing through the second system annular winding 61y is in the axial direction A As viewed from the phase motor Ma side, it flows in the counterclockwise direction.

  Here, as shown in FIGS. 13A and 13B, the control circuit 83 uses the frequencies of the first and second system input voltages vx and vy to be applied to the first and second system annular windings 61x and 61y, respectively. Are the same. In addition, the control circuit 83 controls the first and second system drive circuit units 81 and 82 to shift the phase of the second system input voltage vy with respect to the first system input voltage vx.

  More specifically, as shown in FIGS. 13A and 13B, in this embodiment, after the first system input voltage vx falls from + volt to −volt, the first phase difference θd1 is delayed. The two-system input voltage vy rises from −volt to + volt.

As shown in FIGS. 13A and 13B, in this embodiment, the phase difference θd1 is 30 degrees in this embodiment.
Next, the operation of the second embodiment will be described.

  Now, the first system input voltage vx and the second system input voltage vy are applied to the motor M. That is, the first system input voltage vx is applied to the first system annular winding 61x of the A phase and B phase stators 3a, 3b, and the second system annular winding 61y of the A phase and B phase stators 3a, 3b is applied to the second system annular winding 61y. The system input voltage vy is applied. As a result, rotating magnetic fields are generated in the A-phase and B-phase stators 3a and 3b of the stator 3, and the rotor 2 is rotationally driven.

  At this time, as shown in FIGS. 13A and 13B, in the relationship between the first and second system input voltages vx and vy, after the first system input voltage vx falls from + volt to −volt, 30 The second system input voltage vy rises from −volt to + volt with a phase difference θd1 of the degree.

As in the first embodiment, a leakage magnetic flux is generated between the claw-shaped magnetic poles 13 and 23 of the A-phase and B-phase rotors 2a and 2b, and the leakage magnetic flux distorts the magnetic flux distribution to generate vibration.
In the present embodiment, after the first system input voltage vx falls from + volt to −volt, the second system input voltage vy rises from −volt to + volt with a phase difference θd1 of 60 degrees. The vibration of the motor M is suppressed.

  Incidentally, the phase difference θd1 was changed by 0 to 50 degrees, and the ripple rate and the average torque with respect to the phase difference θd1 at that time were verified. FIG. 14 shows the verification result. In the verification, the ripple rate and average torque in the phase difference θd1 of 0 to 50 degrees were obtained with the reference (100%) when the phase difference θd1 was 0 degrees.

  As is clear from FIG. 14, the ripple rate indicated by the characteristic line L1 is 100% or less when the phase difference θd1 is 0 degrees to 40 degrees, and the phase difference θd1 exceeds 100% exceeding 40 degrees. .

  As is apparent from FIG. 14, the average torque indicated by the characteristic line L2 increases as the phase difference θd1 increases from 0 degrees to 40 degrees, and the phase difference θd1 exceeds 40 degrees. And decrease.

  From this, in order to suppress the ripple rate to 100% or less and keep the average torque at 105% or more, the phase difference θd1 may be set in the range of 10 degrees to 40 degrees, and the motor performance is improved. You can see that

  In addition, the first system drive circuit unit 81 that drives (energizes) the first system annular winding 61x and the second system drive circuit unit 82 that drives (energizes) the second system annular winding 61y include an H-shaped bridge. Configured with circuit. The first and second system input voltages vx and vy applied to the first system annular winding 61x and the second system annular winding 61y can be applied in a full range of +12 volts to -12 volts. Therefore, even a two-layer, two-phase multi-Landel motor M can be a high-output motor.

As described above in detail, the second embodiment has the following effects in addition to the effects (1) and (2) of the first embodiment.
(1) According to the second embodiment, after the first system input voltage vx falls from + volts to −volts, the second system input voltage vy is −volts with a phase difference θd1 of 10 to 40 degrees. To + volts. As a result, the ripple rate can be suppressed to 100% or less, and the average torque can be held to 105% or more to improve the motor performance.

  (2) According to the above-described embodiment, the first and second system drive circuit units 81 and 82 are configured as H-type bridge circuits, and are applied to the first and second system annular windings 61x and 61y. The second system input voltages vx and vy can be applied in a full range of +12 volts to -12 volts. Therefore, even a two-layer, two-phase multi-Landel motor M can be a high-output motor.

The above embodiment may be modified as follows.
In the above embodiment, in the motor M in which the A-phase rotor 2a and the B-phase rotor 2b are 16-pole Landel-type rotors, and the A-phase stator 3a and the B-phase stator 3b are 16-pole Landel-type stators. there were.

  This is embodied in a motor M in which the A-phase rotor 2a and the B-phase rotor 2b are 8-pole Landel-type rotors, and the A-phase stator 3a and the B-phase stator 3b are 8-pole Landel-type stators. Also good. Further, the A-phase rotor 2a and the B-phase rotor 2b are 24-pole Landel-type rotors, and the A-phase stator 3a and the B-phase stator 3b are 24-pole Landell-type stators, such as a motor M, and other magnetic poles. It may be applied to several motors.

  In the above embodiment, the field magnets 30 of the A-phase rotor 2a and the B-phase rotor 2b are formed of ferrite sintered magnets, but are not limited thereto. For example, the field magnet 30 may be formed of another permanent magnet such as a neodymium magnet or a samarium cobalt magnet.

  ○ For the A-phase rotor 2a and B-phase rotor 2b of the motor M shown in the above embodiments, as shown in FIGS. 15 and 16, the first rotor-side claw-shaped magnetic pole 13 and the second rotor-side claw-shaped magnetic pole 23 The interpole auxiliary magnet 35 may be provided between the circumferential directions, and the back auxiliary magnet 36 may be provided on the radially inner side surfaces 13d and 23d of the first and second rotor side magnetic pole portions 13y and 23y.

  Each inter-pole auxiliary magnet 35 has the same magnetic pole as the first and second rotor-side claw-shaped magnetic poles 13 and 23 (the first rotor-side claw-shaped magnetic pole 13 side is N-pole, and the second rotor-side claw-shaped claw The magnet is magnetized in the circumferential direction so that the side of the magnetic pole 23 becomes the S pole.

  On the other hand, the back auxiliary magnet 36 of the first rotor-side magnetic pole portion 13y has a radially inner side surface 13d of the first rotor-side claw-shaped magnetic pole 13 (first rotor-side magnetic pole portion 13y) in order to reduce the leakage magnetic flux at that portion. Is magnetized in the radial direction so that the side contacting the first rotor side claw-shaped magnetic pole 13 is the same polarity as the first rotor side claw-shaped magnetic pole 13 and the side contacting the second rotor core base 21 is the same polarity as the second rotor core base 21. ing. Further, the back auxiliary magnet 36 of the second rotor side magnetic pole portion 23y has a radially inner side surface 23d of the second rotor side claw-shaped magnetic pole 23 (second rotor side magnetic pole portion 23y) in order to reduce the leakage magnetic flux at that portion. Is magnetized in the radial direction so that the side in contact with the second rotor side claw-shaped magnetic pole 23 has the same polarity as the second rotor side claw-shaped magnetic pole 23 and the side in contact with the first rotor core base 11 has the same polarity as the first rotor core base 11. ing.

As a result, the amount of magnetic flux can be increased by providing the back surface auxiliary magnet 36 and the interelectrode auxiliary magnet 35, so that the output can be increased and the motor performance is improved.
At this time, the inter-pole auxiliary magnet 35 and the back auxiliary magnet 36 are formed of the same magnet as the field magnet 30, for example, a ferrite sintered magnet, or a magnet different from the field magnet 30 (neodymium magnet, samarium cobalt magnet, etc.). Or may be implemented. Of course, the inter-pole auxiliary magnet 35 and the back auxiliary magnet 36 may be implemented by different magnets.

  When the inter-pole auxiliary magnet 35 and the back-side auxiliary magnet 36 are composed of permanent magnets made of the same material as the field magnet 30, the field magnet 30, the inter-pole auxiliary magnet 35 and the back-side auxiliary magnet 36 are integrally formed. May be.

This facilitates the assembly of the field magnet 30 and the inter-pole auxiliary magnet 35 and eliminates the possibility of the inter-pole auxiliary magnet 35 dropping off due to centrifugal force during rotation.
In the above embodiment, each of the first and second rotor cores 10 and 20 and the first and second stator cores 40 and 50 is formed of one electromagnetic steel plate, but a plurality of thin electromagnetic steel plates are overlapped. May be formed. Moreover, you may form the 1st and 2nd rotor cores 10 and 20 and the 1st and 2nd stator cores 40 and 50 with a dust core. As a result, the cost of the motor M can be reduced.

  In the above embodiment, in the coil portion 60, the circumference of the annular winding 61 is covered with the coil insulating layer 62 with a resin mold, but it may be implemented with a cylindrical coil bobbin.

  DESCRIPTION OF SYMBOLS 1 ... Rotary shaft, 2 ... Rotor, 2a ... A phase rotor, 2b ... B phase rotor, 3 ... Stator, 3a ... A phase stator, 3b ... B phase stator, 10 ... 1st rotor core, 11 ... 1st rotor core base, 11a ... outer peripheral surface, 11b ... opposing surface, 11c ... anti-opposing surface, 12 ... through hole, 13 ... first rotor side claw-shaped magnetic pole, 13a, 13b ... circumferential end surface, 13c ... radially outer surface, 13d ... radial direction Inner side surface, 13e ... tip surface, 13x ... first rotor side base, 13y ... first rotor side magnetic pole portion, 20 ... second rotor core, 21 ... second rotor core base, 21a ... outer peripheral surface, 21b ... opposite surface, 21c ... Anti-opposing surface, 22 ... through hole, 23 ... second rotor side claw-shaped magnetic pole, 23a, 23b ... circumferential end surface, 23c ... radial outer surface, 23d ... radial inner surface, 23e ... tip surface, 23x ... second Rotor side base, 23y ... second Data side magnetic pole portion, 30 ... field magnet, 30a, 30b ... side surface, 32 ... through hole, 35 ... interpole auxiliary magnet, 36 ... back auxiliary magnet, 40 ... first stator core, 41 ... first stator core base, 41a ... inner peripheral surface, 41b ... opposing surface, 41c ... anti-opposing surface, 42 ... first stator side cylindrical outer wall, 43 ... first stator side claw-shaped magnetic pole, 43a, 43b ... circumferential end surface, 43c ... radially outer surface, 43d: radially inner surface, 43e: tip surface, 43x: first stator side base, 43y: first stator side magnetic pole part, 50 ... second stator core, 51 ... second stator core base, 51a ... inner peripheral surface, 51b ... Opposing surface, 51c ... anti-facing surface, 52 ... second stator side cylindrical outer wall, 53 ... second stator side claw-shaped magnetic pole, 53a, 53b ... circumferential end surface, 53c ... radial outer side surface, 53d ... radial inner side surface, 53e ... tip 53x ... second stator side base, 53y ... second stator side magnetic pole part, 60 ... coil part, 61 ... annular winding, 61a ... A phase annular winding, 61b ... B phase annular winding, 61x ... first system Annular winding (first winding), 61y ... second annular winding (second winding), 62 ... coil insulation layer, 71 ... A phase driving circuit, 72 ... B phase driving circuit, 73 ... Control circuit, 81 ... First system drive circuit section, 82 ... Second system drive circuit section, 83 ... Control circuit, M ... Motor, M1 ... Single motor, Ma ... A phase motor, Mb ... B phase motor, O ... center axis, G ... DC power supply, va ... A phase input voltage, vb ... B phase input voltage, vx ... first system input voltage, vy ... second system input voltage, θd ... phase difference, θd1 ... phase difference, Qa1 ~ Qa4, Qb1 ~ Qb4 ... MOS transistors, L1, L2 ... characteristic lines.

Claims (10)

An A-phase rotor in which an A-phase field magnet is arranged between a pair of A-phase rotor core bases having a plurality of claw-shaped magnetic poles at equal intervals in the circumferential direction, and a pair of claw-shaped magnetic poles at equal intervals in the circumferential direction A two-layer rotor in which a B-phase rotor having a B-phase field magnet disposed between B-phase rotor core bases is laminated;
An A-phase stator in which windings are arranged between a pair of A-phase stator core bases having a plurality of claw-shaped magnetic poles at equal intervals in the circumferential direction, and a pair of B-phase stator cores having a plurality of claw-shaped magnetic poles at equal intervals in the circumferential direction A two-layer stator in which a B-phase stator having windings arranged between bases is laminated;
A motor consisting of
The relative arrangement angle of the B-phase stator in the clockwise direction with respect to the A-phase stator is defined as an electrical angle θ1, and the relative arrangement angle of the B-phase rotor in the counterclockwise direction with respect to the A-phase rotor is set as an electric angle. When the angle is θ2,
A motor characterized by θ1 + | θ2 | = 90 degrees. The motor according to claim 1,
The winding wound around the A-phase stator and the winding wound around the B-phase stator are each composed of two first annular windings and second annular windings, A motor having different phases applied to the second annular winding. The motor according to claim 1 or 2,
The A-phase rotor and the B-phase rotor each include an auxiliary magnet in at least one of a radial direction between the field magnet and the claw-shaped magnetic pole and a circumferential direction between the adjacent claw-shaped magnetic poles. A motor characterized by being interposed. The motor according to claim 3, wherein
The motor, wherein the field magnet and the auxiliary magnet are integrally molded magnets. An A-phase rotor in which an A-phase field magnet is arranged between a pair of A-phase rotor core bases having a plurality of claw-shaped magnetic poles at equal intervals in the circumferential direction, and a pair of claw-shaped magnetic poles at equal intervals in the circumferential direction A two-layer rotor in which a B-phase rotor having a B-phase field magnet disposed between B-phase rotor core bases is laminated;
An A-phase stator in which windings are arranged between a pair of A-phase stator core bases having a plurality of claw-shaped magnetic poles at equal intervals in the circumferential direction, and a pair of B-phase stator cores having a plurality of claw-shaped magnetic poles at equal intervals in the circumferential direction A two-layer stator in which a B-phase stator having windings arranged between bases is laminated;
A motor driving method comprising:
A method for driving a motor, comprising: applying power supplies having different phases to a winding arranged in the A-phase stator and a winding arranged in the B-phase stator. The motor driving method according to claim 5,
The motor driving method, wherein a phase difference between a power source applied to the winding of the A-phase stator and a power source applied to the winding of the B-phase stator is 75 to 90 degrees. In the motor drive method according to claim 5 or 6,
The motor is
A relative arrangement angle of the B-phase stator with respect to the A-phase stator relative to the A-phase stator in the clockwise direction in the circumferential direction is θ1, and the B-phase stator with respect to the A-phase stator. When the relative arrangement angle in the counterclockwise direction is set to θ2 in electrical angle,
A method of driving a motor, wherein θ1 + | θ2 | = 90 degrees is established. An A-phase rotor in which an A-phase field magnet is arranged between a pair of A-phase rotor core bases having a plurality of claw-shaped magnetic poles at equal intervals in the circumferential direction, and a pair of claw-shaped magnetic poles at equal intervals in the circumferential direction A two-layer rotor in which a B-phase rotor having a B-phase field magnet disposed between B-phase rotor core bases is laminated;
An A-phase stator in which windings are arranged between a pair of A-phase stator core bases having a plurality of claw-shaped magnetic poles at equal intervals in the circumferential direction, and a pair of B-phase stator cores having a plurality of claw-shaped magnetic poles at equal intervals in the circumferential direction A two-layer stator in which a B-phase stator having windings arranged between bases is laminated;
A motor driving method comprising:
The winding wound around the A-phase stator and the winding wound around the B-phase stator each include two first-system annular windings and a second-system annular winding, and the first-system annular winding A method for driving a motor, wherein power supplies having different phases are applied to the winding and the second system annular winding, respectively. The method of driving a motor according to claim 8,
The motor drive method according to claim 1, wherein the power supply applied to the first system winding and the second system winding has a phase difference of 10 degrees to 40 degrees. The method for driving a motor according to claim 8 or 9,
The motor is
The relative arrangement angle of the B-phase stator in the clockwise direction with respect to the A-phase stator is defined as an electrical angle θ1, and the relative arrangement angle of the B-phase rotor in the counterclockwise direction with respect to the A-phase rotor is set as an electric angle. When the angle is θ2,
A method of driving a motor, wherein θ1 + | θ2 | = 90 degrees is established.