JP2012147243A - Antenna device and array antenna device - Google Patents

Abstract

PROBLEM TO BE SOLVED: To obtain an antenna device capable of improving antenna characteristics during operation in two frequency bands closer to each other than conventional ones.SOLUTION: The antenna device includes a first dielectric layer with a first conductor part having a first feeding point and a ground conductor formed on upper and lower surfaces thereof, respectively; a second dielectric layer with a second conductor part formed on an upper surface thereof; and a third dielectric layer with a third conductor part having a second feeding point formed on an upper surface thereof. The first to third conductor parts have regions overlapping with each other when viewed in a stacking direction. The first conductor part has a first opening at a position overlapping with the second feeding point when viewed in the stacking direction. Electrical connections between the ground conductor and the first conductor part and between the ground conductor and the second conductor part are respectively established by a first coupling conductor group composed of a plurality of coupling conductors which extend through the first dielectric layer in the stacking direction and are not in contact with each other, and a second coupling conductor group composed of a plurality of coupling conductors which extend through the second dielectric layer in the stacking direction and are not in contact with each other.

Description

  The present invention relates to an antenna device, and more particularly to a dual-frequency antenna device that operates in two frequency bands.

  Space-saving and low cost are required for navigation satellites such as GPS (Global Positioning System) satellites and Galileo satellites and antennas for satellite communications and mobile communications. Therefore, the antenna used in these fields is preferably a microstrip antenna (MSA) having a simple configuration and a small shape. However, in general, the MSA has a narrow band, and it is difficult to cover all desired bands with a single planar antenna. Therefore, a technique is adopted in which planar antennas that operate (resonate) in different frequency bands are arranged on the same plane.

  Conventionally, as an antenna device that operates in two frequency bands, an annular microstrip antenna in which the entire inner circumference of an annular radiating conductor is short-circuited to a ground conductor, and an inner diameter of the annular radiating conductor inside the annular radiating conductor. There is a composite microstrip antenna in which a circular microstrip antenna having a small circular radiation conductor is concentrically disposed (see, for example, Patent Document 1).

Japanese Patent Laid-Open No. 5-160633

  However, in such a composite microstrip antenna, when the diameters of the annular microstrip antenna and the circular microstrip antenna are made closer to operate in a closer frequency band, the resonance frequency of the annular microstrip antenna becomes higher, which is desired. There is a problem that the mode of the antenna and other modes are mixed to deteriorate the characteristics of the antenna. That is, the conventional composite microstrip antenna cannot be operated in a closer frequency band.

  The present invention solves the above-described problems and improves the antenna characteristics when operating in two closer frequency bands than in the prior art, and an array in which the antenna apparatuses are arranged in a plurality of arrays. An object is to obtain an antenna device.

  In order to solve the above-described problems, an antenna device according to the present invention has a first conductor portion having a first feeding point to which a first high-frequency signal is supplied provided on an upper surface and a ground conductor provided on a lower surface. A first dielectric layer, a second dielectric layer laminated on the first dielectric layer and having a second conductor portion provided on the upper surface, and the second dielectric layer And a third dielectric layer provided on the upper surface with a third conductor portion having a second feeding point to which a second high-frequency signal different from the first high-frequency signal is supplied. The first conductor portion, the second conductor portion, and the third conductor portion have regions overlapping each other when viewed from the stacking direction, and the first conductor portion is the second conductor when viewed from the stacking direction. A first opening is provided at a position overlapping the feeding point, and the second conductor portion overlaps the second feeding point when viewed from the stacking direction. A first opening made of a plurality of non-contact connecting conductors penetrating through the first dielectric layer in the stacking direction. And the ground conductor and the second conductor portion are formed of a plurality of non-contact coupling conductors penetrating the second dielectric layer in the stacking direction. It is electrically connected by a connecting conductor group.

  According to the present invention, it is possible to provide an antenna device and an array antenna device that have improved antenna characteristics during operation in two frequency bands closer to each other than before.

1 is an exploded perspective view of an antenna device according to Embodiment 1 of the present invention. It is the top view and sectional drawing of the antenna apparatus of FIG. It is a disassembled perspective view of the antenna device by Embodiment 2 of this invention. It is a disassembled perspective view of the antenna device by Embodiment 3 of this invention. It is a disassembled perspective view of the antenna apparatus by Embodiment 4 of this invention. It is the schematic of the antenna apparatus by Embodiment 5 of this invention. It is the upper side figure and sectional drawing of the antenna apparatus of FIG. It is the schematic of a single PSA. It is a figure which shows the graph of the result of having simulated the relationship between the internal diameter outer diameter ratio (beta) and resonance frequency of PSA of FIG. It is a figure which shows the graph of the relationship between the internal diameter outer diameter ratio (beta) of PSA, and a spurious detuning rate. It is the schematic of the annular | circular shaped MSA single-piece | unit. It is a figure which shows the graph of the result of having simulated the relationship between the internal diameter outer diameter ratio (beta) of annular | circular shaped MSA of FIG. 11, and the resonant frequency of annular | circular shaped MSA. It is a figure which shows the graph of the relationship between the internal diameter outer diameter ratio (beta) of an annular | circular shaped MSA, and a spurious detuning rate.

  Hereinafter, an antenna device and an array antenna device according to the present invention will be described with reference to the drawings according to each embodiment. Note that, in each embodiment, the same or corresponding parts are denoted by related reference numerals, and redundant description is omitted.

Embodiment 1 FIG.
1 is an exploded perspective view of an antenna apparatus according to Embodiment 1 of the present invention. The antenna device of FIG. 1 is shown with a part cut away in order to explain the internal structure. 2A and 2B are a top view and a cross-sectional view of the antenna device of FIG. 1, in which FIG. 2A is a top view, FIG. 2B is a cross-sectional view along AA ′ indicated by a one-dot chain line in FIG. c) is a cross-sectional view along the line BB ′ indicated by a one-dot chain line.

  1 and 2, the antenna device 100 includes a dielectric substrate (first dielectric layer) 110, a dielectric substrate (second dielectric layer) 120, and a dielectric substrate (third dielectric layer) 130. Has a structure in which layers are stacked in this order from the bottom. A ground conductor GND is provided on the lower surface of the dielectric substrate 110, and an annular conductor pattern (first conductor portion) 111 is provided on the upper surface. The annular conductor pattern 111 has a feeding point (first feeding point) 141. A high-frequency signal (first high-frequency signal) is supplied to the feeding point 141 from the feeding circuit 160 via the (coaxial) feeding line 151. That is, the annular conductor pattern 111 functions as a radiation conductor (microstrip antenna: MSA).

  The dielectric substrate 120 is laminated on the dielectric substrate 110, and a circular conductor pattern (second conductor portion) 121 is provided on the upper surface. The dielectric substrate 130 is laminated on the dielectric substrate 120, and a circular conductor pattern (third conductor portion) 131 is provided on the upper surface. The circular conductor pattern 131 has a feeding point (second feeding point) 143. A high-frequency signal (second high-frequency signal) is supplied to the feed point 143 from the feed circuit 160 via the (coaxial) feed line 153.

  In order to guide the feed line 153 to the circular conductor pattern 131 in the antenna device 100, the dielectric substrate 110, the dielectric substrate 120, and the circular conductor pattern 121 are respectively positioned so as to overlap the feed point 143 when viewed from the stacking direction. A through hole 113, a through hole 123, and an opening (second opening) 125 are provided.

  In the antenna device 100 shown in the figure, a dielectric substrate is used as the dielectric layer. However, the present invention is not limited to this, and an air layer can be used as the dielectric layer. A combination of air layers may be used. In addition, although circular and annular conductor patterns are used as the conductor pattern shape, the shape of the conductor pattern is not limited to this, for example, a rectangular MSA and a rectangular shape having an opening at the center surrounding the rectangular MSA. It may be a conductor pattern.

  The operation of the conductor pattern provided on each of the dielectric substrates 110 to 130 will be described below. The annular conductor pattern 111 has an opening (first opening) 115 at a position overlapping the feeding point 143 when viewed from the stacking direction. Further, the annular conductor pattern 111 is electrically connected to the ground conductor GND by a first connecting conductor group including a plurality of non-contact connecting conductors 112a to 112d penetrating the dielectric substrate 110 in the stacking direction. . The connecting conductors 112a to 112d can be realized by, for example, through holes or plate-like conductors.

  1 and 2, the connecting conductors 112 a to 112 d are arranged on the periphery of the opening 115 so as to surround the opening 115. That is, a part of the peripheral edge on the inner peripheral side of the ground conductor GND and the annular conductor pattern 111 is connected by the connecting conductors 112a to 112d and partially short-circuited. Such an antenna including the annular conductor pattern 111 and the connecting conductors 112a to 112d is referred to as a “PSA (Partially Shorted Antenna)” 111a as a partially patched annular patch antenna.

  As shown in FIGS. 1 and 2, the annular conductor pattern 111, the circular conductor pattern 121, and the circular conductor pattern 131 have regions that overlap each other when viewed from the stacking direction. The size of the circular conductor pattern 121 is set so as to cause resonance with the annular conductor pattern 111 so as to be a non-excited element of the PSA 111a. In addition, the circular conductor pattern 121 and the annular conductor pattern 111 are electrically connected by a second connecting conductor group including a plurality of connecting conductors 122a to 122d that pass through the dielectric substrate 120 in the stacking direction and are not in contact with each other. Has been.

  Here, since the annular conductor pattern 111 and the ground conductor GND are electrically connected by the connecting conductors 112a to 112d, the circular conductor pattern 121 and the ground conductor GND are also electrically connected. That is, the circular conductor pattern 121 also functions as a ground conductor when the circular conductor pattern 131 functions as a radiation conductor (microstrip antenna).

  As described above, the circular conductor pattern 131 has the feeding point 143. A high-frequency signal is supplied to the feed point 143 from the feed circuit 160 via the coaxial feed line 153, and the circular conductor pattern 131 operates as a circular MSA having the circular conductor pattern 121 as a ground conductor. Hereinafter, an antenna including the circular conductor pattern 131 and the circular conductor pattern 121 is referred to as a circular MSA 131a. The circular MSA 131a and the PSA 111a have different operating frequency bands, and the circular MSA 131a operates in a higher frequency band than the PSA 111a. That is, the antenna device 100 operates in two frequency bands.

  Here, the operation characteristics and advantages of the PSA 111a will be described in comparison with an annular microstrip antenna (annular MSA) in a general composite microstrip antenna. 8 is a perspective view of a single PSA (invention), and FIG. 11 is a perspective view of a single ring MSA (general). As shown in FIG. 8, the PSA 10 includes a dielectric substrate 11 having a ground conductor GND on the lower surface and an annular conductor pattern 12 on the upper surface, and a ground conductor GND and an annular conductor pattern 12 penetrating the dielectric substrate 11. Are provided with a plurality of connecting conductors 13a to 13d. Further, the PSA 10 includes a feeding point 14 to which a high frequency signal is input from the feeding circuit 16 via the feeding line 15.

  As shown in FIG. 11, the annular MSA 20 includes a dielectric substrate 21 provided with a ground conductor GND on the lower surface and a radiation conductor 22 constituting the annular MSA on the upper surface. Unlike the PSA 10, the inner peripheral portion of the radiation conductor 22 is connected to the ground conductor GND by a short-circuit wall 23 made of a through hole or the like, and is configured as an inner wall short-circuit type. A pair of notches 27a and 27b are formed on the outer peripheral edge of the radiation conductor 22 at an angular interval of 180 °. The annular MSA 20 includes a feeding point 24 to which a high frequency signal is input from the feeding circuit 26 via the feeding line 25.

  FIG. 9 shows the ratio between the inner diameter / outer diameter ratio β (= b / a) and the resonance frequency of the PSA 10 when the outer diameter of the PSA 10 in FIG. 8 is a, the inner diameter is b, and the outer diameter a is fixed to 74 mm. It is a graph which shows the result of having simulated the relationship. FIG. 12 shows the ratio β between the inner diameter and the outer diameter and the resonance frequency of the annular MSA 20 when the outer diameter of the annular MSA 20 in FIG. 11 is a, the inner diameter is b, and the outer diameter a is fixed to 74 mm. It is a graph which shows the result of having simulated the relationship. Although predetermined modes such as TM01, TM11, and TM21 are excited according to the resonance frequency, the TM11 mode is indicated by a solid line as a desired mode in the figure, and the TM01 mode and the TM21 mode that are other modes are indicated by a broken line. ing.

  As shown in FIG. 12, the general annular MSA 20 has a larger ratio β between the inner diameter and the outer diameter of the conductor pattern 22 (that is, the closer the length between the inner diameter and the outer diameter), the TM01, TM11, and TM21. The resonance frequency increases in each mode. On the other hand, as shown in FIG. 9, the resonance frequency of the PSA 10 does not rapidly increase in the TM01, TM11, and TM21 modes even when the ratio β between the inner diameter and the outer diameter of the conductor pattern 12 increases. .

For example, when designing an antenna having a resonance frequency of 1.2 GHz in the TM11 mode, β = 0.2 (see FIG. 12) in a general annular MSA20, whereas β = 0.6 (see FIG. 9) in PSA10. ). That is, the inner diameter of a _general annular MSA is b _general = 0.2 × 74 = 14.8 mm, and the inner diameter of the _{PSA 10} is b _PSA = 0.6 × 74 = 44.4 mm. Thus, the inner diameter b _PSA of the _PSA can be larger than the inner diameter b of the _general annular MSA.

  By the way, if the frequency at which the TM11 mode which is a desired mode is excited and the frequency at which another mode is excited are close to each other and these modes are mixed, the reflection characteristic which is one of the antenna characteristics deteriorates. Preferably, the frequencies at which are excited are separated. The antenna device 100 described in this embodiment excites linearly polarized waves. However, if the antenna device excites circularly polarized waves, the axial ratio characteristics deteriorate when a plurality of modes coexist.

  Here, a value indicating the degree to which the frequency at which the TM11 mode, which is a desired mode, is excited and the frequency at which another mode is excited is separated is referred to as a “spurious detuning rate”, and β and the spurious detuning rate are The graphs obtained from the relationships shown in FIGS. 9 and 12 are shown in FIGS. 10 and 13, respectively. For example, when β = 0.6, the spurious detuning rate between the TM11 mode and the TM21 mode is 10% or less in FIG. On the other hand, in FIG. 10, a spurious detuning rate of 10% or more is secured between the TM11 mode and the TM01 mode and between the TM11 mode and the TM21 mode. That is, it can be seen that even when the outer diameter is reduced (β is increased), the degree of deterioration of the characteristics of the PSA is smaller than that of the annular MSA.

  As described above, since the PSA can bring the inner diameter closer to the outer diameter than a general annular MSA, there are the following advantages when using the PSA in the antenna device 100 according to the present invention. As shown in FIG. 1, the antenna device 100 is provided with a feeding point 143 for feeding power to a circular conductor pattern 131. The feeding point 143 is preferably set to an appropriate position moved in the radial direction from the center in order to achieve impedance matching between the feeding line 153 and the circular MSA 131a. At this time, if the position of the feed line 153 is close to the conductor pattern 111 of the PSA 111a, the antenna characteristics may be affected.

  However, in the antenna device 100, since the diameter of the opening 115 of the PSA 111a can be increased (the inner diameter is made closer to the outer diameter), the feed line 153 can be separated from the conductor pattern 111. That is, the degree of freedom in setting the position of the feeding point 143 of the MSA 131a is increased, and impedance matching of the circular MSA 131a can be easily achieved. On the other hand, when a general annular MSA is used for the first dielectric layer (110), the distance between the inner diameter and the outer diameter cannot be reduced as described above, and therefore the feeding point 143 of the circular MSA 131a is There is a drawback that it takes time to arrange the feeder line 153 when matching is performed at the position.

  As described above, in the antenna device 100, the circular MSA 131a and the PSA 111a are provided on different surfaces, so that there is a degree of freedom in setting each size compared to a composite MSA in which two antennas are provided on the same plane. , Each can be operated in a closer frequency band. Moreover, since the conductor pattern 121 is provided as a non-excitation element of the PSA 111a, the low frequency band can be widened. Furthermore, by using the PSA 111a, there is a degree of freedom in setting the position of the feeding point 143 of the circular MSA 131a, and the design can be simplified compared to the case of using the conventional annular MSA.

  In each of the drawings described above, there are four connection conductors 112a to 112d and 122a to 122d, respectively, showing a state where the PSA 111a and the circular conductor pattern 121 are arranged symmetrically with respect to the center. However, the present invention is not limited to this, and the number, size and position of the connecting conductors can be changed according to desired antenna characteristics. In each figure, the connection conductors 112a to 112d and 122a to 122d are connected to each other (for example, they can be integrally formed). However, they can be provided independently on each dielectric substrate. Furthermore, if the connection conductors 112a to 112d locally connect a part of the PSA 111a and the ground conductor GND, the connection conductors 112a to 112d do not connect the pattern central portion of the annular conductor pattern 111 and the ground conductor GND instead of the inner peripheral side peripheral portion of the PSA 111a. You may connect.

Embodiment 2. FIG.
3 is an exploded perspective view of an antenna apparatus according to Embodiment 2 of the present invention. The antenna device 200 according to the second embodiment has substantially the same configuration as the antenna device 100 according to the first embodiment. In FIG. 3, the position corresponding to FIG. 1 described above is changed from “1” to “2”. The code | symbol changed into is attached | subjected and the overlapping description is abbreviate | omitted. As shown in FIG. 3, the antenna device 200 includes a pair of cutout portions 281 and 282 at positions symmetrical to the center of the conductor pattern 211 on the outer peripheral side of the annular conductor pattern 211 in the PSA 211a. Furthermore, a pair of notch parts 271 and 272 are provided at positions symmetrical to the center of the conductor pattern 231 on the outer peripheral side of the circular conductor pattern 231 in the circular MSA 231a.

  Since the cutout portions 281 and 282 of the PSA 211a have different diameters from the other portions, when a high frequency signal is supplied to the PSA 211a, the current level varies between the diameter in the direction in which the cutout portion is present and the diameter perpendicular thereto. The phase difference becomes 90 degrees, and circularly polarized waves are excited. Similarly, since the circular MSA 231a also has different diameters at the cutout portions 271 and 272 and the other portions, when a high frequency signal is supplied to the circular MSA231a, the diameter in the direction in which the cutout portion is present and the diameter orthogonal thereto are obtained. Between them, the phase difference of the current becomes 90 degrees, and the circularly polarized wave is excited.

  The number, size, and position of the connecting conductors 212a to 212d can be arbitrarily set according to the desired antenna characteristics, but if they are arranged at symmetrical positions with respect to the center of the PSA 211a, the axial ratio characteristics can be improved. . In FIG. 3, the pair of cutout portions 271 and 272 of the circular MSA 231a and the pair of cutout portions 281 and 282 of the PSA 211a are arranged at orthogonal positions. However, depending on the shape of the antenna device 200, the reflection characteristics may be improved. In order to achieve this, it may be arranged slightly shifted from the orthogonal position.

  As described above, according to the second embodiment, circularly polarized waves can be excited in addition to the effects described in the first embodiment.

Embodiment 3 FIG.
4 is an exploded perspective view of an antenna apparatus according to Embodiment 3 of the present invention. The antenna device 300 according to the third embodiment has substantially the same configuration as that of the antenna device 100 according to the first embodiment. In FIG. 4, in the portion corresponding to FIG. The code | symbol changed into is attached | subjected and the overlapping description is abbreviate | omitted. As shown in FIG. 4, in the antenna device 300, the PSA 311a further includes a feeding point 342, that is, a third feeding point, and the feeding points 341 and 342 are arranged at 90 degrees with respect to the center of the PSA 311a. . Similarly, the circular MSA 331a further includes a feeding point 344, that is, a fourth feeding point, and the feeding points 343 and 344 are arranged at 90 degrees with respect to the center of the circular MSA 331a.

  Two high-frequency signals with a phase difference of 90 degrees branched by a hybrid circuit (HYB) 361 are supplied to the feeding points 341 and 342 of the PSA 311a via coaxial feeding lines 351 and 352, respectively. In FIG. 4, the positions of the feeding point 341 and the feeding point 342 have an angle difference of 90 degrees with respect to the center of the PSA 311a, and the phase difference of the high-frequency signal supplied to each feeding point is also 90 degrees. When a high frequency signal is supplied to the PSA 311a, circular polarization is excited.

  For example, as shown in FIG. 4, the feed point 342 is arranged at a position 90 degrees clockwise (clockwise when viewed from the lower side of the figure (ground conductor GND side)) and supplied to the feed point 341. When the phase of the high-frequency signal is 90 degrees ahead of the phase of the high-frequency signal supplied to the feeding point 342, clockwise circular polarization is excited. On the other hand, the feeding point 342 is disposed 90 degrees clockwise of the feeding point 341, and the phase of the high-frequency signal supplied to the feeding point 341 is 90 degrees from the phase of the high-frequency signal supplied to the feeding point 342. If it is delayed, a left-handed circularly polarized wave is excited. Thus, the turning direction of the circularly polarized wave can be arbitrarily set in the antenna device 300 according to desired characteristics.

  Similarly, two high-frequency signals having a phase difference of 90 degrees branched by the hybrid (HYB) circuit 362 are supplied to the feed points 343 and 344 of the circular MSA 331a through the coaxial feed lines 353 and 354, respectively. Therefore, the dielectric substrate 310 has two through holes 313 and 314, and the dielectric substrate 320 has two through holes 323 and 324, respectively. The feeding point 343 and the feeding point 344 are arranged with an angle difference of 90 degrees with respect to the center of the circular MSA 331a, and the phase of the high-frequency signal supplied to the feeding point 343 and the phase of the high-frequency signal supplied to the feeding point 344 Since the difference between them is 90 degrees, when a high frequency signal is supplied to the circular MSA 331a, circularly polarized waves are excited.

  In FIG. 4, since the feeding point 344 is arranged at a position 90 degrees counterclockwise (counterclockwise when viewed from the lower side of the figure (the ground conductor GND side)), the feeding point 343 is supplied to, for example, the feeding point 343. If the phase of the high-frequency signal is 90 degrees ahead of the phase of the high-frequency signal supplied to the feed point 344, the left-handed circularly polarized wave is excited, and the phase of the high-frequency signal supplied to the feed point 343 is When the phase of the high-frequency signal supplied to 344 is 90 degrees behind, right-handed circularly polarized wave is excited.

  Here, the angle difference between the feed point 341 and the feed point 342 of the PSA 311a (relative angle at the center of the PSA 311a) and the angle difference between the feed point 343 and the feed point 344 of the circular MSA 331a (at the center of the circular MSA 331a). However, depending on the shape of the antenna device 300, the relative angle may be slightly shifted from 90 degrees in order to improve the axial ratio characteristics.

  Note that the position where the circularly polarized wave is excited is specifically the position where the angle difference (relative angle) is approximately 90 degrees with respect to the center of the circular MSA 331a, and the angle difference (relative angle) with respect to the center of the PSA 311a. It refers to a position of approximately 90 degrees. At this time, the axial ratio characteristics of the PSA 311a can be improved by arranging the connecting conductors 312a to 312d at symmetrical positions with respect to the center of the conductor pattern 311 of the PSA 311a.

  As described above, according to the third embodiment, in addition to the effects described in the first embodiment, the antenna device 300 can excite circularly polarized waves that rotate in arbitrary directions in each of the circular MSA 331a and the PSA 311a.

  The same effect can be obtained even if either one of the circular MSA and the PSA has the notch portion described in the second embodiment. Such a case will be described below as a fourth embodiment.

Embodiment 4 FIG.
FIG. 5 is an exploded perspective view of an antenna apparatus according to Embodiment 4 of the present invention. In FIG. 5, parts corresponding to those in FIGS. 1 to 4 described above are denoted by reference numerals in which the 100's place is changed to “4”, and redundant description is omitted. As shown in FIG. 5, in the antenna device 400, the PSA 411a has two feeding points 441 and 442, and these feeding points 441 and 442 are arranged at 90 degrees with respect to the center of the PSA 411a. Two high-frequency signals with a phase difference of 90 degrees branched by a hybrid circuit (HYB) 461 are supplied to the feeding points 441 and 442 of the PSA 411a through coaxial feeding lines 451 and 452, respectively, and circularly polarized waves are excited. The

  Unlike Embodiment 3, which includes two feeding points, circular MSA 431a is excited by circularly polarized waves by the same notch as in Embodiment 2. As shown in FIG. 5, the circular MSA 431 a includes a pair of notches 471 and 472 at symmetrical positions on the outer peripheral side of the circular conductor pattern 431. Therefore, when a high frequency signal is supplied from the power supply circuit 460 to the power supply point 443 of the circular MSA 431a, circularly polarized waves are excited.

  Thus, according to Embodiment 4, in addition to the effects described in Embodiment 1, it is possible to excite circularly polarized waves. In general, when circularly polarized waves are excited, one-point feeding has an advantage that the antenna configuration becomes simpler than two-point feeding. Further, the two-point power supply has an advantage that the axial ratio characteristic is better than that of the one-point power supply. Therefore, it is only necessary to appropriately determine whether to use one-point power supply or two-point power supply in consideration of desired characteristics in the two frequency bands.

Embodiment 5 FIG.
6 is an exploded perspective view of an antenna apparatus according to Embodiment 5 of the present invention. 7A and 7B are a top view and a cross-sectional view of the antenna device of FIG. 6, where FIG. 7A is a top view, FIG. 7B is a cross-sectional view along AA ′ indicated by a one-dot chain line in FIG. c) is a cross-sectional view along the line BB ′ indicated by a one-dot chain line. The antenna device 500 according to the fifth embodiment has substantially the same configuration as the antenna device 400 according to the fourth embodiment. In FIGS. 6 and 7, the part corresponding to FIG. The code | symbol changed to "5" is attached | subjected and the overlapping description is abbreviate | omitted.

  Unlike the antenna device 400 illustrated in FIG. 5, the antenna device 500 includes a hollow metal cylinder 580 instead of the through holes 413 and 423 in the antenna device 400. An opening 525 is provided in the conductor pattern 521. The metal cylinder 580 penetrates the ground conductor GND and the dielectric layers 110 and 120 in the stacking direction at a position overlapping the feeding point 543 when viewed from the stacking direction. By adopting such a structure, it is possible to reduce the influence that the feed line 553 penetrating the dielectric layers 110 and 120 may have on the PSA 511a.

  Furthermore, by using the antenna device described in the first to fifth embodiments as an array antenna device in which a two-dimensional or three-dimensional array is arranged at an appropriate interval, a high gain can be expected and a control of a radiated beam can be achieved. It becomes possible.

As described above, according to the present invention, since the circular MSA and the PSA are provided on different surfaces, the degree of freedom in setting each size is higher than that of the composite MSA in which two antennas are provided on the same plane. Yes, each can be operated in a closer frequency band.
Further, since the conductor pattern is provided as a PSA non-excitation element, the low frequency band can be widened.
Furthermore, by using the PSA 111a, there is a degree of freedom in setting the position of the feeding point 143 of the circular MSA 131a, and the design can be simplified compared to the case of using the conventional annular MSA.
Moreover, circularly polarized waves can be arbitrarily set according to desired characteristics by appropriately providing a notch or by using two-point power feeding.
Furthermore, high gain can be expected by arraying the antenna device in two dimensions or three dimensions.

Although the present invention has been described based on the drawings and embodiments, it should be noted that those skilled in the art can easily make various changes and modifications based on the present disclosure. Therefore, it should be noted that these variations and modifications are included in the scope of the present invention.
For example, in the above description, a dielectric substrate is used as the dielectric layer of the antenna device, but the present invention is not limited to this, and an air layer can be used as the dielectric layer. And an air layer may be used in combination.
In addition, although circular and annular conductor patterns are used as the conductor pattern shape, the shape of the conductor pattern is not limited to this, for example, a rectangular MSA and a rectangular shape having an opening at the center surrounding the rectangular MSA. It may be a conductor pattern.
The application of the present invention is not limited to satellites and mobile communication devices.

  Further, the present invention is not limited to the above-described embodiments, and it is needless to say that all possible combinations of the features of the respective embodiments are included.

10, 111a, 211a, 311a, 411a, 511a PSA,
11, 21, 110, 120, 130, 210, 220, 230, 310, 320, 330, 410, 420, 430, 510, 520, 530 dielectric substrate (dielectric layer),
12, 22, 111, 121, 131, 211, 221, 231, 311, 321, 331, 411, 421, 431, 511, 521, 531 conductor pattern,
13a to 13d, 112a to 112d, 122a to 122d, 212a to 212d, 222a to 222d, 312a to 312d, 322a to 322d, 412a to 412d, 422a to 422d, 512a to 512d, 522a to 522d
14, 24, 141, 143, 241, 243, 251, 253, 341-344, 441-443, 541-543 feeding point,
15, 25, 151, 153, 251, 253, 351-354, 451-453, 551-553 feed line,
16, 26, 160, 260, 460, 560 feeding circuit,
20, 131a, 231a, 331a, 431a, 531a Circular MSA,
23 Short-circuit wall,
27a, 27b Notch,
100, 200, 300, 400, 500 antenna device,
113,123,213,223,313,314,323,324,413,423,513,523 through-hole,
115,125,215,225,315,325,326,415,425,515,525 opening,
271, 272, 281, 282, 471, 472, 571, 572 notch,
361, 362, 461, 561 hybrid (HYB) circuit,
580 metal cylinder,
GND Ground conductor.

Claims (8)

A first dielectric layer having a first conductor portion having a first feeding point to which a first high-frequency signal is supplied provided on the upper surface and a ground conductor provided on the lower surface;
A second dielectric layer laminated on the first dielectric layer and having a second conductor portion provided on the upper surface;
A third conductor portion having a second feeding point that is laminated on the second dielectric layer and is supplied with a second high-frequency signal different from the first high-frequency signal is provided on the upper surface. 3 dielectric layers;
With
The first conductor portion, the second conductor portion, and the third conductor portion have regions that overlap each other when viewed from the stacking direction;
The first conductor portion has a first opening at a position overlapping the second feeding point when viewed from the stacking direction,
The second conductor portion has a second opening at a position overlapping the second feeding point when viewed from the stacking direction,
The ground conductor and the first conductor portion are electrically connected by a first connection conductor group including a plurality of contact conductors that are in non-contact with each other and penetrate the first dielectric layer in the stacking direction;
The ground conductor and the second conductor portion are electrically connected by a second connecting conductor group including a plurality of non-contact connecting conductors that penetrate the second dielectric layer in the stacking direction. An antenna device characterized by the above.   2. The antenna device according to claim 1, wherein the first connecting conductor group is disposed on a periphery of the first opening of the first conductor so as to surround the opening.   The antenna device according to claim 1 or 2, wherein the first connecting conductor group and the second connecting conductor group are integrally formed. The first conductor portion has a pair of notches at symmetrical positions with respect to the center of the first conductor portion,
The third conductor portion has a pair of cutout portions at symmetrical positions with respect to the center of the third conductor portion.
The antenna device according to any one of claims 1 to 3, wherein The first conductor portion has a third feeding point to which a high-frequency signal having the same frequency as the first high-frequency signal and a phase difference of 90 degrees is supplied.
The third conductor portion has a fourth feeding point to which a high-frequency signal having the same frequency as the second high-frequency signal and a phase difference of 90 degrees is supplied.
The first opening of the first conductor portion is disposed at a position overlapping the fourth feeding point as seen from the stacking direction,
The first feeding point and the third feeding point are arranged at positions where circularly polarized waves are excited in the first conductor portion,
The second feeding point and the fourth feeding point are arranged at positions where circularly polarized waves are excited in the third conductor portion.
The antenna device according to any one of claims 1 to 3, wherein The third conductor portion further includes a pair of cutout portions at symmetrical positions with respect to the center of the third conductor portion.
The first conductor portion has a third feeding point to which a high-frequency signal having the same frequency as the first high-frequency signal and a phase difference of 90 degrees is supplied.
The first feeding point and the third feeding point are arranged at positions where circularly polarized waves are excited in the first conductor portion.
The antenna device according to any one of claims 1 to 3, wherein   The ground conductor, the first dielectric layer, and the second dielectric layer are laminated at a position overlapping the second feeding point or the second feeding point and the fourth feeding point when viewed from the stacking direction. The antenna device according to any one of claims 1 to 6, further comprising a hollow metal cylinder penetrating in a direction.   An array antenna apparatus comprising a plurality of antenna apparatuses according to claim 1 arranged in an array.

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