JP2011254682A - Axial gap type rotary electric machine, compressor, and rotary electric machine apparatus - Google Patents

Abstract

PROBLEM TO BE SOLVED: To provide an axial gap type rotary electric machine in which a rotator can move in a rotary shaft direction at a low cost with a simple structure.SOLUTION: The axial gap type rotary electric machine comprises: first and second bearings (50a and 50b) for supporting a rotary shaft (40); a first stator (20) which is fixed to a housing (60) and has a plurality of magnetic cores (20e) with windings; a second stator (30) arranged in the housing; a rotator (10) which is arranged on the rotary shaft so as to be arranged between the first and second stators, has a plurality of magnetic field members (10i) and is movable to the first stator side or the second stator side; a first stopper (70a) which controls a range of moving the rotator to the first stator side; and a second stopper (70b) which controls a range of moving the rotator to the second stator side.

Description

  The present invention relates to an axial gap type rotating electrical machine, a compressor, and a rotating electrical machine apparatus in which a rotor can move in the direction of a rotation axis.

  In recent high efficiency of rotating electrical machines, the influence of permanent magnet synchronous rotating electrical machines represented by rare earth magnets is large. On the other hand, the permanent magnet synchronous rotating electric machine has a feature that an induced voltage proportional to the rotation speed is generated as a difference from the induction rotating electric machine. In such a permanent magnet synchronous rotating electric machine, so-called field weakening control (or “weakening magnetic flux control”) is proposed in which the field magnetic flux is weakened to suppress the induced voltage as a high-speed technique within the drive voltage limit. This is realized, for example, by controlling the current phase angle to an advance angle with respect to the induced voltage phase during no-load rotation. With this control technology, it is possible to achieve large torque during low-speed operation, large output during high-speed operation, and high efficiency during rated operation, and similar control is used in many products.

  However, due to demands for higher speed and higher efficiency in the flux-weakening control region (in other words, further improvement of rotational efficiency) or current phase advance control, the torque / current ratio is lowered to reduce the copper loss. In order to increase the magnetic field flux, a technique that can weaken the field magnetic flux mechanically (in a broader sense, a technique that can mechanically increase / decrease the field magnetic flux) has been proposed.

  For example, Patent Document 1 discloses a technique for widening an air gap between the rotor and the stator by moving the stator in the direction of the rotation axis of the rotor by an actuator with a rack and a pinion.

  In Patent Document 2, although not variable during driving, as an air gap adjustment technique after assembly, the stator hub and the rotor are rotated by rotating the bearing hub via the bearing hub and the screw portion on the inner surface of the stator. A technique for adjusting the air gap is disclosed.

  In the axial gap type permanent magnet synchronous rotating electric machine, unlike the radial gap type, a large magnetic attraction force is generated between the stator and the rotor in the direction of the rotation axis. Therefore, a large force is required when changing the air gap. Necessary. As a countermeasure technique, Patent Document 3 discloses a technique for reducing the force required for movement by moving only the inner diameter portion without moving the outer diameter portion of the rotor.

  In Patent Document 4, the air gap between two stators is made to be equal in length so as to reduce the necessary support rigidity against the above-described large magnetic attraction force, thereby reducing the cost and the weight of the entire apparatus. Technology is disclosed.

  Patent Document 5 discloses a technology that uses a variable electromagnetic force of a stator and makes an air gap between two stators variable by a spring that antagonizes it.

JP 2002-247822 JP Japanese Patent Laid-Open No. 11-069697 JP 2008-048497 JP 2006-014466 A JP 2005-318718

  However, in each of Patent Documents 1-5, an application for driving an automobile or a flywheel power storage device is assumed, and the mechanism and cost allowed for such an application are still complicated for an air conditioner compressor. In addition, there is a problem of high cost.

  In view of the above problems, it is desirable to be able to increase / decrease the field magnetic flux with a simpler configuration at a lower cost. In a conventional axial gap type rotating electrical machine, a rotor is fixed to a rotating shaft, and the rotating shaft is disposed in a bearing so that movement in the direction of the rotating shaft is restricted. Therefore, even if the drive current is controlled, the gap between the rotor and the stator cannot be adjusted. Therefore, there is a problem that control for adjusting the gap is necessary in addition to control of the drive current.

  In addition, among conventional axial gap type rotating electrical machines, sensorless for estimating the rotational position of the rotor from each constant of the motor (for example, linkage flux φa, d-axis inductance Ld, q-axis inductance Lq, winding phase resistance Ra, etc.). Some use control. In this sensorless control, the phase current is controlled based on the estimated rotational position of the rotor. However, each constant may vary for each rotating electrical machine due to mass production, and due to the variation, an error occurs in the estimated rotational position, and this error causes a current phase β larger than expected (and therefore limited). In some cases, the rotor is controlled to rotate with a negative d-axis current greater than the value. When the rotor is controlled to rotate by such a large negative d-axis current, there is a problem in that the field member of the rotor may be demagnetized.

  In addition, there are the following generation causes as other generation causes of demagnetization. That is, when the control cannot follow the disturbance and step out and the current phase β is energized in the third quadrant (90 ° <β <180 °) of the dq coordinate, that is, in the regenerative state (power generation state) of the rotating electrical machine. In this case, both the d-axis current and the q-axis current are negative values and the phase currents are reversed, so even if a large current flows, the current is not detected by the mechanism for maximum current limit (OCP). As a result, the current value cannot be limited, and a negative d-axis current whose absolute value is larger than expected will flow, causing demagnetization.

  SUMMARY OF THE INVENTION An object of the present invention is to solve the above-mentioned problems. First, an axial gap type rotating electrical machine in which a rotor can move in the direction of a rotating shaft with a simple structure at a low cost and a compression are provided. Is to provide a machine. A second object of the present invention is to provide a rotating electrical machine apparatus capable of mechanically increasing / decreasing the field magnetic flux with a low-cost and simple configuration, thereby improving the rotational efficiency of the rotating electrical machine. A third object is to provide a rotating electrical machine apparatus that can avoid demagnetization with a simple structure at low cost.

  In order to solve the above-described problem, an axial gap type rotating electrical machine according to the first aspect of the present invention includes a housing (70), a rotating shaft (40, 40C) disposed along the rotating shaft (Q1), and the like. , First and second bearings (50a, 50b, 50aB, 50bB, 50aC, 50bC) disposed in the housing and supporting the rotating shaft, fixed to the housing, and one side in the rotating shaft direction A first stator (20) having a plurality of winding cores (20e) arranged in a ring around the rotation axis on the surface (20d) of (Q +), and the rotation axis with respect to the first stator It arrange | positions between the said 2nd stator (30) arrange | positioned at the said housing, and the said 1st and 2nd stator so that the said 1st stator may be spaced apart in the one side (Q +) of a direction. Like the above rotation The first stator side surface (10c1) is disposed on the shaft, and has a plurality of field members (10i) arranged around the rotation axis, and the first stator along the rotation axis direction. A rotor (10, 10B, 10C) that is movable toward the stator side or the second stator side, and a first stopper (70a, 70aB) that limits the range of movement of the rotor toward the first stator side , 70aC) and second stoppers (70b, 70bB, 70bC) for limiting the range of movement of the rotor toward the second stator.

  The axial gap type rotating electrical machine according to the second aspect of the present invention is the axial gap type rotating electrical machine (100) according to the first aspect, wherein the rotor (10) is connected to the rotating shaft (40). The first and second bearings (50a, 50b) are fixed and support the rotary shaft movably in the direction of the rotary axis (Q1) while being fixed to the housing (60). is there.

  The axial gap type rotating electrical machine according to the third aspect of the present invention is the axial gap type rotating electrical machine (100) according to the second aspect, wherein the first stopper (70a) is the rotating shaft (40). ) Is fixed between the first bearing (50a) and the first stator (20), and the second stopper (70b) is fixed to the second bearing (50b) and the second fixed on the rotating shaft. It is fixed between the child (30).

  The axial gap type rotating electrical machine according to the fourth aspect of the present invention is the axial gap type rotating electrical machine (100B) according to the first aspect, wherein the rotor (10B) is connected to the rotating shaft (40). The first and second bearings (50aB, 50bB) are fixed with respect to the rotating shaft, and are movable in the rotating shaft direction (Q1) with respect to the housing (60). And it is arrange | positioned so that it may fix in the direction orthogonal to the said rotating shaft direction.

  The axial gap type rotating electrical machine according to the fifth aspect of the present invention is the axial gap type rotating electrical machine (100B) according to the fourth aspect, wherein the first stopper (70aB) is the first bearing ( 50a) is disposed in the housing (60) so as to limit the movement range of the rotation axis (Q1) in the direction of the rotation axis (Q1), and the second stopper (70bB) 50b) is arranged in the housing so as to limit the movement range to one side (Q +) in the rotation axis direction.

  The axial gap type rotating electrical machine according to the sixth aspect of the present invention is the axial gap type rotating electrical machine (100C) according to the first aspect, wherein the rotor (10C) is the rotating shaft (40C). The first and second bearings (50aC, 50bC) are arranged so as to be relatively movable in the direction of the rotation axis (Q1) and not relatively rotatable around the rotation axis. Each of the rotating shafts is supported so as to be rotatable around the rotating shaft and fixed in the rotating shaft direction while being fixed to the housing (60).

  An axial gap type rotating electric machine according to a seventh aspect of the present invention is the axial gap type rotating electric machine (100C) according to the sixth aspect, wherein the rotating shaft (40C) includes the first and the first A portion arranged between the two stators (20, 30) and having a first diameter (d3), and a portion (40d) on both sides of the narrow portion and being larger than the first diameter A large-diameter portion (40e) having a large second diameter (d4), and the rotor (10C) is movable relative to the small-diameter portion in the rotational axis direction and the rotation The first stopper (70aC) is configured by a step at the boundary between the small diameter portion and the large diameter portion (40e +) on one side (Q +). The second stopper (70bC) It said portion and the other side (Q-) is formed using the steps of the boundary between the thick diameter portion (40e-).

  An axial gap type rotating electric machine according to an eighth aspect of the present invention is the axial gap type rotating electric machine (100C) according to the seventh aspect, wherein the rotating shaft (Q1) in the small diameter portion (40d). The rotor (10C) is formed with a central hole (10n) into which the cross section is fitted so as to penetrate the surfaces on both sides in the rotation axis direction. The small-diameter portion is inserted into the center hole.

  The axial gap type rotating electrical machine according to the ninth aspect of the present invention is the axial gap type rotating electrical machine (100C) according to the eighth aspect, wherein the rotating shaft (Q1) in the small diameter portion (40d). The cross-section orthogonal to is a gear shape or a star shape.

  The compressor according to the tenth aspect of the present invention includes a container (300), a rotation shaft (40) disposed along the rotation axis (Q1), the container disposed on the container, and the rotation shaft. First and second bearings (50a, 50b) that are movable in the direction of the rotation axis and supported so as to be fixed in a direction orthogonal to the rotation axis, and fixed to the container, A first stator (20) having a plurality of winding cores (20e) disposed around the rotation axis on one side (Q +) surface (20d), and the first stator (20) with respect to the first stator Between the second stator (30) disposed in the container and the first and second stators so as to be spaced from the first stator on one side (Q +) in the rotation axis direction. The first stator side surface (1) is disposed on the rotating shaft so as to be disposed. c1) has a plurality of field members (10i) annularly arranged around the rotation axis, and is movable to the first stator side or the second stator side along the rotation axis direction. A rotor (10), a cylinder (401) disposed in the container, an upper end plate (402) for closing the upper opening of the cylinder, and a lower end plate (403) for closing the lower opening of the cylinder And a crank pin (406) disposed on the rotating shaft inserted through the upper end plate and the lower end plate in the cylinder, and fitted on the outer periphery of the crank pin in the cylinder. The height (D1) of the crank pin in the rotational axis direction is set to be shorter than the height (D2) of the piston in the same direction. Said The lower surface (402a) of the upper end plate functions as a first stopper that regulates the movement range of the other side (Q-) of the crank in the rotation axis direction. The upper surface (403a) of the lower end plate functions as a second stopper that regulates the movement range of one side (Q +) of the crank in the rotation axis direction.

  A rotating electrical machine apparatus according to an eleventh aspect of the present invention is the axial gap rotating electrical machine according to any one of the first to ninth aspects or the compressor according to the tenth aspect, and the magnetic core with each winding. Inverter means (80) for selectively passing a current through the winding (20a) of (20e), and a control means for controlling the rotation of the rotor by selectively passing a current through each of the windings by controlling the inverter means. (100, 100B), and the direction of the rotation axis of the resultant force of the magnetic force acting between the first and second stators (20, 30) and the rotor (10, 10B, 10C) And the total force (F1) of the components other than the magnetic force acting on the rotor in the direction of the rotation axis is positive in the direction from the one side to the other side, and the value is positive. In order to selectively take between a negative value and a negative value, There is for controlling said inverter means.

  A rotating electrical machine apparatus according to a twelfth aspect of the present invention is the rotating electrical machine apparatus (1, 1B) according to the eleventh aspect, wherein the control means (100, 100B) is the inverter means (80). By controlling the current value and the phase angle of the current flowing through each of the windings (20a), the total force can selectively take a value between the positive value and the negative value. .

  The rotating electrical machine apparatus according to a thirteenth aspect of the present invention is the rotating electrical machine apparatus (1) according to the eleventh or twelfth aspect, wherein the control means (100) Until the upper limit of the output voltage of the control means is reached, the rotor is rotationally controlled with the phase angle (β) of the current flowing through each winding (20a) being zero.

  The rotating electrical machine apparatus according to a fourteenth aspect of the present invention is the rotating electrical machine apparatus according to any one of the eleventh to thirteenth aspects, wherein the control means (100) is configured such that the drive voltage of the rotating electrical machine is When the output voltage upper limit value of the control means is reached, the rotor is weakened and the rotation is controlled by magnetic flux control so that the total force (F1) faces the second stator side.

  A rotating electrical machine apparatus according to a fifteenth aspect of the present invention is the rotating electrical machine apparatus (1B) according to the eleventh or twelfth aspect, wherein the control means (100B) has a predetermined torque of the rotating electrical machine apparatus. When the value is less than the value, the rotation of the rotor is controlled so that the total force (F1) faces the second stator side.

  A rotating electrical machine apparatus according to a sixteenth aspect of the present invention is the rotating electrical machine apparatus (1B) according to any of the eleventh, twelfth and fifteenth aspects, wherein the control means (100B) is the rotating electrical machine. When the torque of the device is equal to or greater than the predetermined value, the current value of the current flowing through each winding (20a) and the phase angle (β) are set so that the total force (F1) faces the first stator side. By controlling the rotation of the rotor, the rotation of the rotor is controlled.

  A rotating electrical machine apparatus according to a seventeenth aspect of the present invention is the axial gap type rotating electrical machine according to any one of the first to ninth aspects or the compressor according to the tenth aspect, and the magnetic core with each winding. Inverter means (80) for selectively passing a current through the winding (20a) of (20e), and a control means for controlling the rotation of the rotor by selectively passing a current through each of the windings by controlling the inverter means. (100C), and the control means (100C) includes a total force (F1) of a component of the resultant force in the rotation axis direction and a component of the force other than the magnetic force acting on the rotor in the rotation axis direction. ) Controls the rotation of the rotor so that it faces the first stator.

  A rotating electrical machine apparatus according to an eighteenth aspect of the present invention is the rotating electrical machine apparatus according to the seventeenth aspect, wherein the control means (100C) is configured such that the phase angle (β) becomes zero, or The rotation of the rotor (10) is controlled so that the rotor is weakened and the magnetic flux is controlled in a range where the total force (F1) faces the first stator.

  According to the first aspect of the present invention, the rotor can be moved in the direction of the rotation axis with a low-cost and simple configuration. Further, since the rotor is movable in the direction of the rotation axis, the total force of the component in the rotation axis direction of the magnetic force acting on the rotor and the component in the rotation axis direction of the force other than the magnetic force acting on the rotor is on one side. Alternatively, when the value on the other side is taken, the rotor is moved to the same side in the rotation axis direction by the total force, so that the size of the gap between the rotor and the stator can be adjusted.

  According to the second aspect of the present invention, the rotor can be moved in the direction of the rotation axis with a simple and low-cost configuration.

  According to the third aspect of the present invention, the first and second stoppers can be provided with a low-cost and simple configuration.

  According to the fourth aspect of the present invention, the rotor can be moved in the direction of the rotation axis with a simple and low-cost configuration.

  According to the fifth aspect of the present invention, the first and second stoppers can be provided with a low-cost and simple configuration.

  According to the sixth aspect of the present invention, the rotor can be moved in the direction of the rotation axis with a simple and low-cost configuration.

  According to the seventh aspect of the present invention, since the step between the small diameter portion and the large diameter portion is used as the first stopper and the second stopper, there is no need to provide the first stopper and the second stopper as separate members.

  According to the eighth and ninth aspects of the present invention, the rotor can be moved relative to the small-diameter portion in the direction of the rotation axis and relatively around the rotation axis with a low-cost and simple configuration. It can arrange | position so that it may be fixed.

  According to the tenth aspect of the present invention, the upper end plate and the lower end plate can function as the first stopper and the second stopper, thereby eliminating the need to separately provide the first stopper and the second stopper.

  According to the eleventh aspect of the present invention, the total force can be selectively set to a value between a positive value and a negative value. Can be directed selectively to the stator side. As a result, when the total force is directed to the first stator side, the distance between the rotor and the first stator is reduced, so that the interlinkage magnetic flux is reduced with respect to the same current value as compared with the conventional motor. It is possible to increase the torque efficiently, thereby improving the rotational efficiency of the axial gap type rotating electrical machine. In addition, when the total force is directed to the second stator side, the distance between the rotor and the first stator is widened, thereby reducing the interlinkage magnetic flux and iron loss, thereby rotating the axial gap. The rotation efficiency of the electric machine can be improved.

  According to the twelfth aspect of the present invention, the component of the resultant force in the rotation axis direction can be controlled by controlling the current value and the phase angle (that is, by simple control).

  According to the thirteenth aspect of the present invention, in the state where the phase angle is zero, the total force increases toward the first stator as the current value increases, so the rotor and the first force increase as the current value increases. The distance from the stator can be reduced. Thereby, until the drive voltage reaches the upper limit value of the output voltage, the rotational efficiency of the axial gap rotating electrical machine can be improved only by controlling the current value.

  According to the fourteenth aspect of the present invention, when the drive voltage of the rotating electrical machine reaches the upper limit value of the output voltage, the total force is directed to the second stator side by the flux weakening control (ie, the rotor and By controlling (to widen the gap with the first stator), the interlinkage magnetic flux is reduced mechanically, the current value for flux-weakening control is reduced, the iron loss is reduced, and the speed is further increased. Can be The rotation rate is improved at the same time.

  According to the fifteenth aspect of the present invention, particularly in the low speed rotation region and the low torque region, the copper loss slightly increases due to the reduction of the interlinkage magnetic flux, but the main loss is the iron loss. The iron loss is reduced and the total loss of iron loss and copper loss is reduced. This increases the rotation efficiency of the rotating electrical machine.

  According to the sixteenth aspect of the present invention, as the current increases, the torque of the rotating electrical machine increases and the total force increases toward the positive side. As the total force increases to the positive side, the rotor is moved to the first stator side by the total force, and the interlinkage magnetic flux interlinking the windings is further increased. In general, the copper loss is proportional to the square of the torque and inversely proportional to the square of the interlinkage magnetic flux. Therefore, in the high torque region, the increase of the copper loss is suppressed by the increase of the mechanical interlinkage magnetic flux. Iron loss is proportional to the square of the interlinkage magnetic flux, but the main loss in the high torque region is copper loss. Therefore, even if the iron loss increases due to the increase of interlinkage magnetic flux, it is better to suppress the increase in copper loss. The total value is reduced. This increases the rotation efficiency of the rotating electrical machine.

  According to the seventeenth aspect of the present invention, when the total force is directed to the first stator side, and the demagnetizing current does not flow through the winding, the rotor moves to the first stator side by the total force. Since the distance between the rotor and the first stator is reduced, the rotational efficiency of the axial gap type rotating electrical machine can be improved due to the current value reduction effect. If a demagnetizing current flows through the winding, the demagnetizing current The total force is increased to the negative side in a self-supporting manner, whereby the rotor is moved in a self-supporting manner to the second stator side, and the distance between the rotor and the first stator is increased, thereby the rotor. Is prevented from being demagnetized by the demagnetizing current.

  According to the eighteenth aspect of the present invention, the total force can be controlled to face the first stator side only by controlling the phase angle.

1 is a schematic cross-sectional view of an axial gap type rotating electrical machine 90 according to a first embodiment. FIG. 2 is an exploded perspective view of the rotor 10, the first stator 20, and the second stator 30 of FIG. It is a figure explaining the specific example of the 1st and 2nd stoppers 70a and 70b of FIG. It is a figure which shows an example of the perspective view of resin board 120a, 120b. It is the cross-sectional schematic of the axial gap type rotary electric machine 90B which concerns on 2nd Embodiment. It is the cross-sectional schematic of the axial gap type rotary electric machine 90C which concerns on 3rd Embodiment. It is VII-VII sectional drawing of FIG. It is an example of the block diagram of the rotary electric machine apparatuses 1 and 1B which concern on 5th Embodiment and 6th Embodiment. It is the actual measurement result of the figure which shows the relationship between total force F1 and phase angle (beta). It is a figure which shows the relationship between d-axis current command value Id * and rotational speed command value (omega) * in 5th Embodiment. It is a figure which shows the relationship between q-axis electric current command value Iq * and rotational speed command value (omega) * in 5th Embodiment. It is a figure which shows the relationship between the total force F1 and rotational speed command value (omega) * in 5th Embodiment. It is a figure which shows the relationship between the total force F1 at the time of shifting the initial value Fs to the 1st stator 20 side, and phase angle (beta). It is a figure which shows the relationship between the total force F1 at the time of shifting the initial value Fs to the 2nd stator 30 side, and phase angle (beta). It is a figure which shows the relationship between electric current phase angle (beta) and the output torque T in 6th Embodiment. It is a figure which shows the relationship between d-axis current command value Id * and q-axis current command value Iq * and output torque T in 6th Embodiment. It is a figure which shows the relationship between the absolute value Ia of the electric currents Iu, Iv, and Iw and output torque T in 6th Embodiment. It is an example of the block diagram of the rotary electric machine apparatus 100C which concerns on 7th Embodiment. It is a flowchart explaining operation | movement of the principal part of the rotary electric machine apparatus 100C which concerns on 7th Embodiment. It is an example of sectional drawing of the compressor 200 which concerns on 4th Embodiment. It is a figure explaining the modification of FIG. It is a figure explaining the modification of FIG. It is a figure which shows the correlation of the torque of a motor 90, and loss when d1 is small (g50) and d1 is large (g60).

<First Embodiment>
An axial gap type rotating electrical machine 90 (hereinafter also referred to as “motor 90”) according to this embodiment includes a rotor 10, first and second stators 20 and 30, and a rotating shaft as shown in FIGS. 40, first and second bearings 50a and 50b, a housing 60, and first and second stoppers 70a and 70b.

  As shown in FIG. 1, the housing 60 is formed in a box shape having an accommodation space therein, and each component 10, 20, 30, 40, 50a, 50b, 70a, 70b is disposed therein. Yes. Holes 60b and 60d are formed in one surface 60a and the opposite surface 60c of the housing 60, respectively, and the rotation shaft 40 is inserted into the holes 60b and 60d so as to be rotatable around the rotation axis Q1. Be placed.

  As shown in FIGS. 1 and 2, the rotor 10 includes a plurality of field members 10i, a plurality of core members 10f, a holding member 10h, and a steel plate 10g.

  The field members 10i are annularly arranged apart from each other around the rotation axis Q1. Each field member 10i is formed in a substantially trapezoidal plate shape in plan view, for example, and includes a field magnet 10a and a core member 10c.

  The field magnet 10a is a rare earth magnet whose main component is, for example, neodymium, iron, or boron. The field magnet 10a is formed in, for example, a substantially trapezoidal plate shape in plan view. Here, the side 10a3 corresponding to the lower base of the substantially trapezoidal shape of the field magnet 10a is convexly formed on the outer peripheral side in an arc shape. In the field magnet 10a, main surfaces 10a1 and 10a2 on both sides thereof are magnetic pole surfaces. Each field magnet 10a has its principal surfaces 10a1 and 10a2 on both sides thereof substantially orthogonal to the direction of the rotation axis Q1 and the side 10a3 corresponding to the bottom of the field magnet 10a faces the outside so that they are mutually connected around the rotation axis Q1. Spaced apart. In addition, each field magnet 10a has the polarity of the magnetic pole of the main surface (for example, main surface 10a1) on the same side (for example, the Q-side in the direction of the rotation axis Q1) alternately along the circumferential direction Q2 with respect to the rotation axis Q1. Arranged differently.

  The core member 10c is formed of a magnetic material (for example, a soft magnetic material such as iron) into a plate shape having a planar view shape (here, substantially trapezoidal shape) that is the same shape and size as the field magnet 10a. The core member 10c is disposed on one main surface 10a1 of the field magnet 10a.

  Each core member 10f is formed, for example, in a substantially rectangular parallelepiped shape from a magnetic material (for example, a soft magnetic material such as iron). Each core member 10f is disposed between adjacent field members 10i so that the longitudinal direction thereof is along the radial direction Q3 with respect to the rotation axis Q1.

  The holding member 10h holds the plurality of field members 10i and the plurality of core members 10f. The holding member 10h is made of a nonmagnetic material, such as a nonmagnetic metal, and includes an inner peripheral frame portion 10j, an outer peripheral frame portion 10k, and a plurality of connecting portions 10m.

  The inner peripheral frame portion 10j is formed in an annular shape (for example, a substantially annular plate shape). Here, the outer peripheral shape of the inner peripheral frame portion 10j is formed in, for example, a substantially hexagonal shape in a plan view viewed along the direction of the rotation axis Q1. The outer peripheral frame portion 10k is formed in an annular shape (for example, an annular shape), and is arranged concentrically on the outer peripheral side of the inner peripheral frame portion 10j. A rotating shaft 40 is inserted into a central hole 10n of the inner peripheral frame portion 10j in a concentric shaft shape and fixed.

  The rotation shaft 40 is disposed along the rotation axis Q1, one side Q− in the direction of the rotation axis Q1 is supported by the first bearing 50a, and the other side Q + in the rotation axis direction Q1 is supported by the second bearing 50b. It is supported. More specifically, the first bearing 50a and the second bearing 50b are respectively fixed to the housing 60 and support the rotary shaft 40 so as to be rotatable about the rotary axis Q1 and movable in the direction of the rotary axis Q1. ing.

  As such bearings, for example, sintered oil-impregnated bearings are used as the first bearing 50a and the second bearing 50b. That is, the first bearing 50a and the second bearing 50b are formed so as to include a porous material by a sintered material made of iron or the like, and the porous material is impregnated with a lubricating oil. The inner diameter of each of the first bearing 50a and the second bearing 50b is designed to be slightly larger (for example, about several μm to several tens of μm) than the outer diameter of the rotating shaft 40, whereby the rotating shaft 40 is designed to be the first bearing. When rotating in a state of being inserted into the inner diameter portions of 50a and the second bearing 50b, lubrication impregnated in the porous member in a gap near the contact portion between the rotating shaft 40 and each of the bearings 50a and 50b is caused by a pumping action due to the rotation. Oil oozes out and the rotating shaft 40 is supported by the lubricating oil. As described above, the rotation shaft 40 is supported by the lubricating oil, so that the rotation shaft 40 is supported so as to be rotatable around the rotation axis Q1 and movable in the direction of the rotation axis Q1 as described above.

  Further, here, a recess 60h is formed in the inner surface 60g of the other side Q− of the housing 60, and the first bearing 50a is press-fitted and fitted in the recess 60h, for example, so that the first bearing 50 a is fixed to the housing 60. Further, a recess 60f is formed in the inner surface 60e on one side Q + of the housing 60, and the second bearing 50b is fitted into the recess 60f, for example, by being press-fitted, so that the second bearing 50b is fitted into the housing 60. It is fixed to. The hole 60b is formed at the bottom of the recess 60h, and the hole 60d is formed at the bottom of the recess 60d. In this way, the rotating shaft 40 is supported by the first bearing 50a and the second bearing 50b, so that the rotor 10 can move to the one side Q− side or the other side Q + along the direction of the rotating shaft Q1. It is arranged. With such a configuration, the rotor 10 can move in the direction of the rotation axis Q1 with a simple and low-cost configuration.

  Each connecting portion 10m is arranged along the radial direction Q3 between the inner peripheral frame portion 10j and the outer peripheral frame portion 10m, and connects the inner peripheral frame portion 10j and the outer peripheral frame portion 10m. As for the interval between the adjacent connecting portions 10m, a relatively small interval and a relatively large interval are alternately repeated along the circumferential direction Q2. A core member 10f is fitted and disposed in the section 10p1 corresponding to the relatively small interval, and a field member 10i is fitted and disposed in the space 10p2 corresponding to the relatively large interval.

  That is, the field members 10i are annularly arranged around the rotation axis Q1, and the main surface 10a2 on one side Q + of the field magnet 10a is exposed from the main surface 10h1 on the same side Q + of the holding member 10h. At the same time, the main surface (magnetic pole surface) 10c1 on the other side Q− of the core member 10c is disposed on the holding member 10h with the main surface 10h2 on the same side Q− of the holding member 10h exposed. The core member 10f is disposed between adjacent field member 10i so as to penetrate between the main surfaces 10h1 and 10h2 on both sides of the holding member 10h.

  The steel plate 10g is formed, for example, in a substantially annular plate shape (for example, an annular plate shape) by a magnetic material (for example, a soft magnetic material such as iron), and the holding member is covered so as to cover the main surface 10a2 of each field magnet 10a. It is arranged concentrically on the surface of one side Q + of 10h.

  The first stator 20 includes, for example, a back yoke 20c and a plurality of winding cores 20e. For example, the first stator 20 is fixed to the housing 60 between the rotor 10 and the first bearing 50.

  The back yoke 20c is formed in, for example, a substantially annular plate shape (for example, an annular plate shape), and the rotation shaft 40 is inserted through the center hole 20f so as to be rotatable around the rotation axis Q1. The back yoke 20c is fixedly disposed on the housing 60 between the rotor 10 and the first bearing 50a so as to be disposed concentrically with the rotor 10.

  Each winding core 20e includes an armature core 20b and an armature winding 20a. The armature core 20b is formed in a substantially trapezoidal column shape, for example, and an armature winding 20a is wound around the outer periphery thereof. A plurality of armature cores 20b are annularly arranged around the rotation axis Q1 so that the side surface 20b3 facing the lower base of the substantially trapezoidal shape faces the outside on the main surface 20d of the back yoke 20c on the rotor 10 side. Has been. As shown in FIG. 1, the armature core 20b is, for example, a substantially trapezoidal columnar magnetic core body 20b1 around which the armature winding 20a is wound, and the rotor 10 side surface of the magnetic core body 20b1. For example, a substantially trapezoidal plate-like wide magnetic core portion 20b2 is formed integrally with the magnetic core main body portion 20b1 so as to project to the outer peripheral side of the magnetic core main body portion 20b1.

  The armature winding 20a is wound around the outer periphery of the armature core 20b via an insulator (not shown). In the present application, unless otherwise specified, the armature winding 20a does not indicate one of the conductive wires constituting the armature winding 20a, but indicates a mode in which the conductive wires are wound together. Further, the lead lines at the beginning and the end of the winding, and their connection are also omitted in the drawings. Each armature winding 20a is connected by wiring so as to constitute a motor, and is connected to an electrode (not shown) for each phase U, V, W provided in the motor 90.

  The second stator 30 is formed of a magnetic material, for example, in a substantially annular plate shape (for example, an annular plate shape), and the rotation shaft 40 is inserted through the central hole 30c so as to be rotatable around the rotation axis Q1. For example, the second stator 30 is disposed between the rotor 10 and the second bearing 50b by being fixed to the housing 60 so as to be disposed concentrically with the rotor 10.

  The first stopper 70a limits the movement range of the rotor 10 toward the first stator 20 side. For example, the first stopper 70a is fixed between the first bearing 50a and the first stator 20 in the rotary shaft 40, moves together with the rotary shaft 40 (and thus the rotor 10) in the direction of the rotary axis Q1, 1 stopper 70a contacts the 1st bearing 50a, and the range of movement to the 1st stator 20 side of rotor 10 is restricted. Similarly, the second stopper 70b limits the range of movement of the rotor 10 toward the second stator 30 side. For example, the second stopper 70b is fixed between the second bearing 50b and the second stator 30 on the rotary shaft 40, moves together with the rotary shaft 40 (and thus the rotor 10) in the direction of the rotary axis Q1, 2 The stopper 70b abuts on the second bearing 50b, thereby limiting the range of movement of the rotor 10 toward the second stator 20 side. Here, each of the first stopper 70a and the second stopper 70b is formed of, for example, a disk-shaped metal plate having a hole (hereinafter referred to as a central hole) in the center thereof. Each of the first stopper 70a and the second stopper 70b is fixed to the rotating shaft 40 by press-fitting the rotating shaft 40 into the center hole thereof. With such a configuration, the first stopper 70a and the second stopper 70 can be provided with a simple configuration.

  In the motor 90, the first stopper 70a and the second stopper 70b are as follows so that the rotor 10 does not contact the first stator 20 and the second stator 30 when the rotor 10 moves in the direction of the rotation axis Q1. (A) It arrange | positions so that (b) may be satisfy | filled. (A) The sum (G1 + G2) of the gap G1 between the first stopper 70a and the first bearing 50a and the gap G2 between the second stopper 70b and the second bearing 50b is the difference between the first stator 20 and the rotor 10. An interval (more specifically, an interval between the end surface 20g of the armature core 20e and the main surface 10c1 of the core member 10c) d1 and an interval d2 between the second stator 30 and the rotor 10 It becomes smaller than the sum (d1 + d2). (B) When G1 = 0 (that is, when the first stopper 70a contacts the first bearing 50a), d1> 0 (that is, the rotor 10 does not contact the first stator 20), and G2 = 0 (That is, when the second stopper 70b contacts the second bearing 50b), d2> 0 (that is, the rotor 10 does not contact the second stator 30).

  In this motor 90, each armature core 20b is excited by supplying current to each armature winding 20a from the electrodes of the respective phases U, V, W from a predetermined inverter circuit (not shown). Is done. A magnetic force is generated between the excited armature core 20b and each field member 10i of the rotor 10, and the rotor 10 is rotated about the rotation axis Q1 by this force. Is output to the outside. At that time, the component (thrust force) of the resultant magnetic force in the direction of the rotation axis Q1 is the difference between the one side Q− and the other side Q + according to the current value or phase angle of the current supplied to the armature winding 20a. Take the value between. When the total force F1 of the thrust force and the component other than the magnetic force acting on the rotor 10 (for example, the weight of the rotor 10) in the direction of the rotation axis Q1 takes the value of one side Q− When the total force F1 moves the rotor 10 to the same side Q−, and the total force F1 takes the value of the other side Q +, the rotor 10 is moved to the same side Q + by the total force F1.

  According to the axial gap type rotating electrical machine 90 configured as described above, the rotor 10 can be moved in the direction of the rotation axis Q1 at a low cost and with a simple configuration. Further, since the rotor 10 is movable in the direction of the rotation axis Q1, when the total force F1 takes the value of one side Q− or the other side Q +, the total force F1 causes the rotor 10 to move in the direction of the rotation axis Q1. Since it is moved to the side, the size of the gap can be adjusted. Although details will be described later, when field-weakening control is performed to increase the rotation speed, the total force F1 can be controlled to face the other side Q +, and the field magnetic flux is substantially reduced by widening the gap. Thus, the effect of field weakening control can be enhanced. Conversely, the integration force F1 can be controlled to face the one side Q-. In this case, since the gap is narrowed, the electromagnetic interaction between the rotor 10 and the first stator 20 is enhanced, and the output torque is increased.

  In this embodiment, the first resin plate disposed between the first stopper 70a and the first bearing 50a, and the second resin plate disposed between the second stopper 70b and the second bearing 50b are further provided. May be provided. More specifically, the first and second resin plates 120a and 120b are each formed in a disk shape by a resin member as shown in FIG. The first resin plate 120a is disposed on the rotary shaft 40 by inserting the rotary shaft 40 through the center hole 120i so as to be positioned between the first stopper 70a and the first bearing 50a. The second resin plate 120b is disposed on the rotation shaft 40 by inserting the rotation shaft 40 through the center hole 120i so as to be positioned between the second stopper 70b and the second bearing 50b. Thereby, the friction between the first stopper 70a and the first bearing 50a can be reduced by the first resin plate 120a, and the friction between the second stopper 70b and the second bearing 50b can be reduced by the second resin plate 120b. .

  In this embodiment, the first stopper 70a and the second stopper 70b are formed of a disk-shaped metal plate, and are fixed to the rotary shaft 40 by press-fitting the rotary shaft 40 into the center hole. It is not limited to like. Each of the first stopper 70a and the second stopper 70b may be configured as a circlip. More specifically, each of the first and second stoppers 70a and 70b is formed by a spring member or the like so as to have a substantially C-shaped portion 70i and a protruding portion 70j as shown in FIG. The substantially C-shaped part 70i is a part that functions as a circlip. The overhanging portion 70j is extended at the both ends 70m in the circumferential direction of the substantially C-shaped portion 70i so as to project to the outer peripheral side of the substantially C-shaped portion 70i and to be folded back in the circumferential direction of the substantially C-shaped portion 70i. Has been. A hole 70k is formed in the overhanging portion 70j. Each of the first and second stoppers 70a and 70b is formed such that the inner corner portion 70m of the portion facing the open space 70p, which is a substantially C-shaped dividing portion, has an arc shape, and the open space 70p. The outer corner portion 70n of the portion facing the surface is formed in an arc shape. The first and second stoppers 70a and 70b formed in this way can be elastically deformed so that the interval d in the circumferential direction of the open space 70p increases. Further, on the outer peripheral surface of the rotary shaft 40, as shown in FIG. 3, grooves 40a into which the first and second stoppers 70a and 70b are fitted are provided at respective locations where the first and second stoppers 70a and 70b are disposed. It is installed around.

  The first stopper 70a formed in this way is disposed in the groove 40a of the rotating shaft 40 as described below. That is, the first stopper 70a is pushed into the groove 40a so that both corners 70n of the first stopper 70a are brought into contact with the bottom 40b of the groove 40a of the rotating shaft 40. As a result, the bottom 40b advances to the back of the open space 70p while increasing the interval d of the open space 70p, and finally the bottom 40b fits on the inner peripheral side of the first stopper 70a (that is, the first stopper 70a fits in the groove 40). Match). At this time, since both corner portions 70n of the first stopper 70a are formed in an arc shape, the bottom portion 40b can advance deeply into the open space 70p while widening the interval d of the open space 70p. In this way, the first stopper 70 a is disposed in the groove 40 a of the rotating shaft 40. The second stopper 70b is also disposed in the groove 40a of the rotating shaft 40 in the same manner as the first stopper 70b.

  The first stopper 70a formed in this way is detached from the rotating shaft 40 as described below. That is, the distance d of the open space 70p is widened by pulling both the protruding portions 70j of the first stopper 70a to the outside in the facing direction. Then, the first stopper 70a is pulled away from the rotary shaft 40 so that the rotary shaft 40 moves from the inner peripheral side of the first stopper 70a to the outer peripheral side through the open space 70p. At this time, since both corners 70m of the first stopper 70a are formed in an arc shape, the rotary shaft 40 can smoothly pass through the open space 70p from the inner peripheral side of the first stopper 70a. In this way, the first stopper 70a is detached from the rotary shaft 40. The second stopper 70b is also detached from the rotating shaft 40 in the same manner as the first stopper 70b.

  Thus, when the 1st stopper 70a and the 2nd stopper 70b are formed as a circlip, there exists an advantage which can attach to the rotating shaft 40 of the 1st stopper 70a and the 2nd stopper 70b easily.

Second Embodiment
In the first embodiment, as shown in FIG. 1, the first bearing 50 a and the second bearing 50 b are respectively fixed to the housing 60 in the direction of the rotation axis Q <b> 1. The first bearing 50a and the second bearing 50b are respectively disposed so as to be movable in the direction of the rotation axis Q1 with respect to the housing 60. Hereinafter, based on FIG. 5, the same parts as those of the first embodiment are denoted by the same reference numerals, description thereof will be omitted, and differences from the first embodiment will be mainly described.

  In this embodiment, as shown in FIG. 5, compared to the first embodiment, (a1) the first stopper 70a and the second stopper 70b (see FIG. 1) of the first embodiment are omitted, and (b1) the first Each of the first bearing 50aB and the second bearing 50bB is movable in the direction of the rotation axis Q1 with respect to the housing 60 and fixed to a direction Q3 (hereinafter referred to as a radial direction) orthogonal to the rotation axis Q1. The rotating shaft 40 is arranged so as to be rotatable around the rotation axis Q1 and fixed in the direction of the rotation axis Q1.

  More specifically, in the above (b1), the first bearing 50aB and the second bearing 50bB are each frictioned by using, for example, a rolling bearing (that is, rolling of a rolling element disposed between the inner diameter portion and the outer diameter portion). It is configured as a bearing with reduced resistance, specifically a ball bearing, for example. The rotary shaft 40 is fixed by being press-fitted into the inner diameter portions of the first bearing 50aB and the second bearing 50bB. As a result, the first bearing 50aB and the second bearing 50bB are disposed so as to be rotatable about the rotation axis Q1 and fixed in the direction of the rotation axis Q1 with respect to the rotation shaft 40 as described above.

  A recess 60h is formed in the inner surface 60g on one side Q- of the housing 60, and the outer diameter portion of the second bearing 50aB is movably fitted in the direction of the rotation axis Q1 with respect to the recess 60h. By being fitted so as to be positioned in the radial direction Q3, it is disposed in the housing 60. Similarly, a recess 60f is formed on the inner surface 60e of the other side Q + of the housing 60, and the outer diameter portion of the second bearing 50bB is movably fitted in the direction of the rotation axis Q1 with respect to the recess 60f. And it is arrange | positioned in the housing 60 by fitting so that it may be positioned in radial direction Q3. The hole 60b is formed at the bottom of the recess 60h, and the hole 60d is formed at the bottom of the recess 60d. Note that (b1) makes it possible to move the rotor 10 in the direction of the rotation axis Q1 with a low-cost and simple configuration.

  In this embodiment, the bottom portion of the recess 60h of the housing 60 functions as a first stopper 70aB that limits the range of movement of the rotor 10 toward the first stator 10 (that is, in this embodiment, the first stopper 70aB). Is formed integrally with the bottom of the recess 60h). Further, the bottom portion of the recess 60f of the housing 60 functions as a second stopper 70bB that restricts the range of movement of the rotor 10 toward the twelfth stator 20 (that is, in this embodiment, the second stopper 70bB is the bottom portion of the recess 60f). And is formed integrally.) Accordingly, the first stopper 70aB and the second stopper 70bB can be provided with a simple configuration. In particular, since the first stopper 70aB and the second stopper 70bB are integrally formed with the housing 60, the first stopper 70aB and the second stopper 70bB can be provided without adding additional members.

  In addition, since the other component of this embodiment is comprised similarly to 1st Embodiment, description is abbreviate | omitted.

  Further, in this embodiment, the first stopper 70aB and the second stopper 70bB are provided so that the rotor 10 does not contact the first stator 20 and the second stator 30 when the rotor 10 moves in the direction of the rotation axis Q1. Are set so as to satisfy the following (a2) and (b2). (A2) The sum (G1 + G2) of the gap G1 between the first stopper 70aB and the first bearing 50a and the gap G2 between the second stopper 70b and the second bearing 50b is the difference between the first stator 20 and the rotor 10. It becomes smaller than the sum (d1 + d2) of the space | interval d1 between and the space | interval d2 between the 2nd stator 30 and the rotor 10. FIG. (B2) When G1 = 0 (that is, when the first bearing 50a contacts the first stopper 70aB), d1> 0 (that is, the rotor 10 does not contact the first stator 20), and G2 = 0 (I.e., when the second bearing 50b comes into contact with the second stopper 70bB), d2> 0 (i.e., the rotor 10 does not come into contact with the second stator 30).

  In this embodiment, as in the case of the first embodiment, the rotating shaft 40 is rotated by the magnetic force acting between the rotor 10 and the first stator 20. Further, as described above, the first bearing 50aB and the second bearing 50bB are arranged to be movable in the direction of the rotation axis Q1 with respect to the housing 60, so that the rotor 10B is movable in the direction of the rotation axis Q1. Thus, as in the first embodiment, when the total force F1 takes the value of one side Q-, the rotor 10 is moved to the same side Q- by the total force F1, and on the other hand, the total force F1 Takes the value of the other side Q +, the rotor 10 is moved to the same side Q + by the total force F1.

  Also with the axial gap type rotating electrical machine 90B configured as described above, the same effects as in the first embodiment can be obtained.

<Third Embodiment>
In the first embodiment, as shown in FIG. 1, the rotor 10 is fixed to the rotating shaft 40, and the rotating shaft 40 moves in the direction of the rotation axis Q <b> 1, so that the rotor 10 moves in the direction of the rotation axis Q <b> 1. In this embodiment, as shown in FIG. 6, in the rotating shaft 40, the rotor 10C is disposed so as to be movable in the direction of the rotation axis Q1, so that the rotor 10C moves in the direction of the rotation axis Q1. In the following, based on FIG. 6, the same parts as those in the first embodiment are denoted by the same reference numerals, and the description thereof is omitted.

  In this embodiment, as shown in FIG. 6, compared to the first embodiment, (a3) the first stopper 70a and the second stopper 70b (see FIG. 1) of the first embodiment are omitted, and (b3) Each of the first bearing 50aC and the second bearing 50bC is disposed so as to be rotatable around the rotation axis Q1 and fixed in the direction of the rotation axis Q1 while being fixed to the housing 60. c3) The rotor 10C is configured similarly except that the rotor 10C is arranged so as to be relatively movable in the direction of the rotation axis Q1 and not to be relatively rotatable around the rotation axis Q1. .

  More specifically, in the above (b3), the first bearing 50aC and the second bearing 50bC are each frictioned by using, for example, a rolling bearing (that is, rolling of a rolling element disposed between the inner diameter portion and the outer diameter portion). It is configured as a bearing with reduced resistance, specifically a ball bearing, for example. The outer diameter portion of the first bearing 50aC is, for example, press-fitted and fixed in the recess 60h of the housing 60, and the outer diameter portion of the second bearing 50bC is, for example, press-fitted and fixed in the recess 60f of the housing 60. Further, a later-described large-diameter portion 40e + of the rotary shaft 40C is, for example, press-fitted and fixed in the inner diameter portion of the first bearing 50aC, and a later-described large-diameter portion 40e of the rotation shaft 40C is fixed in the inner diameter portion of the second bearing 50bC. -Is pressed and fixed, for example.

  The rotating shaft 40C is a portion disposed between the first stator 20 and the second stator 30 and has a small diameter portion (first portion) 40d having a first diameter d3 and both sides of the small diameter portion 40d. A portion (in other words, a portion other than the small-diameter portion 40d) and a large-diameter portion (second portion) 40e having a second diameter d4 larger than the first diameter d1 are configured. Here, the cross section orthogonal to the rotation axis Q1 in the small diameter portion 40d is formed in a non-circular shape such as a gear shape or a star shape as shown in FIG. 7, and the cross section orthogonal to the rotation axis Q1 in the large diameter portion 40e. Is formed in a circular shape, for example. Further, a first stopper 70aC that limits the range of movement of the rotor 10C toward the first stator 20 due to a step at the boundary between the small-diameter portion 40d and the large-diameter portion 40e on the other side Q- (hereinafter referred to as 40e-). And a second stopper that limits the range of movement of the rotor 10C toward the second stator 30 due to a step at the boundary between the small-diameter portion 40e and the large-diameter portion 40e on one side Q + (hereinafter referred to as 40e +). 70bC is configured.

  Further, the rotor 10C is disposed in the small diameter portion 40d so as to be relatively movable in the direction of the rotation axis Q1 and relatively fixed around the rotation axis Q1. More specifically, the cross section perpendicular to the rotation axis Q1 in the central hole 10n of the rotor 10C is substantially the same shape and slightly larger than the cross section of the small diameter portion 40d as shown in FIG. Thus, the rotor 10C is disposed so as to be relatively fixed around the rotation axis Q1 in the small diameter portion 40d. In particular, since the cross section of the rotor 10C is slightly larger than the cross section of the small diameter portion 40d, the rotor 10C can move relatively smoothly in the direction of the rotation axis Q1 in the small diameter portion 40d. It has become.

  In this embodiment, the first stopper 70aC and the second stopper 70bC are configured so that the rotor 10C does not contact the first stator 20 and the second stator 30 when the rotor 10C moves in the direction of the rotation axis Q1. It is set so as to satisfy the following (a4) and (b4). (A4) The sum (G1 + G2) of the gap G1 between the first stopper 70aC and the rotor 10C and the gap G2 between the second stopper 70bC and the rotor 10C is between the first stator 20 and the rotor 10C. It becomes smaller than the sum (d1 + d2) of the distance d1 and the distance d2 between the second stator 30 and the rotor 10C. (B4) When G1 = 0 (that is, when the first bearing 50a contacts the first stopper 70aC), d1> 0 (that is, the rotor 10C does not contact the first stator 20), and G2 = 0 (I.e., when the second bearing 50b contacts the second stopper 70bC), d2> 0 (that is, the rotor 10C does not contact the second stator 30).

  In this embodiment, as in the case of the first embodiment, the rotating shaft 40C is rotated by the magnetic force acting between the rotor 10C and the first stator 20 and the second stator 30. Further, as described above, the rotor 10C is disposed on the rotary shaft 40C so as to be movable in the direction of the rotation axis Q1, so that the rotor 10C can be moved in the direction of the rotation axis Q1. Similarly to the configuration, when the total force F1 takes the value of the one side Q−, the rotor 10C is moved to the same side Q− by the total force F1, while the total force F1 has the value of the other side Q +. When it is taken, the rotor 10C is moved to the same side Q + by the total force F1.

  The effect similar to that of the first embodiment can be obtained also by the axial gap type rotating electric machine 90C configured as described above. Further, since the rotor 10C does not rotate around the rotation axis Q1 relative to the first stopper 70aC and the second stopper 70bC, even if the rotor 10C contacts the first stopper 70aC, the rotor 10C and the first stopper There is an advantage that friction does not occur with 70aC (that is, the rotation of the rotor 10C does not decelerate).

  In this embodiment, the first stopper 70aC is configured by the boundary between the small diameter portion 40d and the large diameter portion 40e−, and the second stopper 70bC is configured by the boundary between the small diameter portion 40d and the large diameter portion 40e +. However, it is not limited to this. For example, each of the first stopper 70aC and the second stopper 70bC may be formed in a disk shape having a central hole at the center thereof by a metal plate as in the first embodiment. In this case, each of the first stopper 70aC and the second stopper 70bC is disposed on the rotary shaft 40C by, for example, press-fitting and fixing the small-diameter portion 40d in the center hole thereof. Alternatively, each of the first stopper 70aC and the second stopper 70bC may be formed as the circlip of FIG. 3 described above. Also in this case, the groove 40a is provided around the outer peripheral surface of the small-diameter portion 40d, and the first stopper 70aC and the second stopper 70bC are disposed in the groove 40a. In these cases, the above-described resin plate 120a of FIG. 4 is disposed between the first stopper 70aC and the rotor 10, and the above-described resin plate 120a of FIG. 4 is disposed between the second stopper 70aC and the rotor 10. A resin plate 120b may be disposed.

<Fourth embodiment>
In the first embodiment, the axial gap type rotating electrical machine 90 includes the first and second stoppers 70a and 70b. In this embodiment, a modified example of a stopper when an axial gap type rotating electrical machine is used as a motor for compressing a refrigerant in a compressor is shown.

  The compressor 200 according to this embodiment compresses a refrigerant, for example, and includes a container 300, a three-phase motor 90D, and a compression mechanism unit 400 as shown in FIG. FIG. 20 is a cross-sectional view of the compressor 200, but the three-phase motor 90D is shown in a side view.

  The container 300 is formed in a hollow cylindrical shape, for example, and is arranged so that its column axis Q4 is vertical. For example, a suction pipe 301 for supplying a refrigerant into the container 300 is connected to the lower side surface of the container 300. Further, a discharge pipe 302 that discharges the refrigerant from the inside of the container 300 is connected to the ceiling of the container 300. In FIG. 20, the suction pipe 301 and the discharge pipe 302 are shown in a side view.

  The three-phase motor 90D is obtained by omitting the first and second stoppers 70a and 70b and the housing 60 in the axial gap type rotating electrical machine 90 of the first embodiment. Here, the container 300 functions as the housing 90 of the first embodiment. The three-phase motor 90D is accommodated and disposed on the upper side in the container 300. More specifically, the three-phase motor 90D is arranged so that the rotation axis Q1 is vertical. In the three-phase motor 90D, the outer peripheral side surface of the back yoke 20c is fixed to the inner peripheral surface of the container 300 in a state where the first stator 20 is disposed above the rotor 10, and the second stator 30 is the rotor. 10, the outer peripheral side surface of the second stator 30 is disposed so as to be fixed to the inner peripheral surface of the container 300.

  The compression mechanism 400 is accommodated and disposed in the container 300 so as to be positioned below the three-phase motor 90D. The compression mechanism 400 is connected to the rotary shaft 40 of the three-phase motor 90D and is driven by the three-phase motor 90D via the rotary shaft 40.

  The compression mechanism unit 400 includes a cylinder 401, an upper end plate 402 and a lower end plate 403.

  On the side surface of the cylinder 401, a suction port 410 for sucking the refrigerant from the suction pipe 301 is provided in the cylinder 401. The upper end plate 402 is disposed so as to close the upper opening of the cylinder 401, and the lower end plate 403 is disposed so as to close the lower opening of the cylinder 401. The rotating shaft 40 passes through the upper end plate 402 and the lower end plate 403 and is inserted into the cylinder 401. The rotary shaft 40 is supported by a bearing 404 provided on the upper end plate 402 and a bearing 405 provided on the lower end plate 403 so as to be rotatable about the rotation axis Q1 and movable in the direction of the rotation axis Q1. That is, the bearing 404 functions as the bearing 50a in FIG. 1, and the bearing 405 functions as the bearing 50b in FIG.

  In the cylinder 401, a crank pin 406 is provided on the rotary shaft 40, and a piston 407 is fitted on the outer periphery of the crank pin 406. A compression chamber 408 is formed by a space between the piston 407 and the corresponding cylinder 401. As the rotating shaft 40 rotates, the volume of the compression chamber 408, which is a gap with the cylinder 401, is changed by rotating or revolving with the piston 407 eccentric. Due to this change, the refrigerant supplied from the suction pipe 301 is compressed in the compression chamber 408.

  The height D3 of the cylinder 401 in the direction of the rotation axis Q1 and the height D2 of the piston 407 in the same direction are set to the same height. Further, the height D1 of the crank pin 406 in the direction of the rotation axis Q1 is set to be shorter than the height D2 of the piston 407 in the same direction, and the crank pin 406 has a lower surface 402a of the upper end portion 402 and an upper surface 403a of the lower end portion 403. Is freely movable in the direction of the rotation axis Q1. As a result, the rotor 10 can move toward the first stator 20 until the crank pin 406 contacts the upper surface 402a, and can move toward the second stator 30 until the crank pin 406 contacts the lower surface 403a. That is, the upper surface 402a functions as the first stopper 70a of the first embodiment, and the lower surface 403a functions as the second stopper 70b of the first embodiment. The difference (D2−D1) between the heights D1 and D2 is set to be smaller than the sum (d1 + d2) of the distances d1 and d2 between the rotor 10, the first stator 20, and the second stator 30. .

  Since the height D1 of the crank pin 406 is shorter than the height D2 of the piston 407 in this way, loss due to friction between the crank pin 406 and the upper end plate 402 and the lower end plate 403 can be reduced. By the pressure deformation of the lower end plate 403, it is possible to avoid the crank pin 406 being caught between the plates 402 and 403 and being locked. Note that the crank pin 406 is pressed against the upper end plate 402 or the lower end plate 403 by the total force F1 acting on the rotor 10 in order to prevent the rotating shaft 40 from vibrating in the direction of the rotating shaft Q1 and generating abnormal noise. It is desirable that

  In the compressor 200, when the three-phase motor 90D is rotationally driven to drive the compression mechanism unit 400, the refrigerant is supplied from the suction pipe 301 to the compression mechanism unit 400, and the compression mechanism unit 400 (particularly, the compression chamber 408). The refrigerant is compressed. The high-pressure refrigerant compressed by the compression mechanism unit 400 is discharged into the container 300 from the discharge port 409 of the compression mechanism unit 400. The high-pressure refrigerant passes through the space between the second stator 30 and the rotary shaft 40 or the container 300, and passes through the space between the rotor 10 and the container 300, and the first stator 30 and the container. 300 or through a through hole (not shown) in the direction of the rotation axis Q1 provided in the first stator 30 and carried to the upper space of the three-phase motor 90D, and the discharge pipe It is discharged to the outside of the container 300 through 302.

  According to the compressor 200 configured as described above, the same effect as that of the first embodiment can be obtained with respect to the motor 90D, and the height D1 of the crank 406 in the direction of the rotation axis Q1 is set to the same direction as the piston 407. And the crank 406 is movable in the direction of the rotation axis Q1 between the upper end plate 402 and the lower end plate 403, whereby the upper end plate 402 and the lower end plate 403 are moved to the first stopper and the second end. It can function as a stopper, thereby eliminating the need to provide a first stopper and a second stopper separately.

<Fifth Embodiment>
The rotating electrical machine apparatus 1 according to this embodiment efficiently drives the motor to rotate by allowing the rotor to move in the direction of the rotation axis according to the rotation speed of the motor while rotating the rotor about the rotation axis. Is.

  As shown in FIG. 8, the rotating electrical machine 1 converts a DC power source 70, a three-phase motor 90, and DC power of the DC power source 70 into three-phase AC power to convert each phase U, V, Inverter circuit (inverter means) 80 for supplying current to W, a plurality of current sensors 120u, 120v, 120w for detecting currents Iu, Iv, Iw flowing in the respective phases, and detection of each of current sensors 120u, 120v, 120w And a control circuit (control means) 100 for controlling the inverter circuit 80 based on the result. The direct current power source may be formed by an alternating current power source and a converter.

  For example, as shown in FIG. 1, the motor 90 is arranged such that the rotor 10 is rotatable about the rotation axis Q1 and is movable in the direction of the rotation axis Q1, and one side Q− of the rotor 10 in the direction of the rotation axis Q1. Is a sensorless axial gap type rotating electrical machine having a structure in which a stator 20 with a winding is disposed on the other side and a stator 30 without a winding is disposed on the other side Q + of the rotor 10 in the direction of the rotation axis Q1. . Here, the axial gap type rotating electrical machine 90 of the first embodiment is used as such a motor 90, but the axial gap type rotating electrical machine according to the second or third embodiment is used instead of the axial gap type rotating electrical machine 90. 90B and 90C may be used. In particular, when the rotating electrical machine apparatus 1 is applied to a motor for compressing a refrigerant in a compressor, the motor 90D of the fourth embodiment may be used.

  In the motor 90, each armature core 20b is excited by supplying current from the inverter circuit 80 to each armature winding 20a via the electrodes 11u, 11v, and 11w of each phase U, V, and W. The A magnetic force is generated between the energized armature core 20b and each field member 10i of the rotor 10, and the rotor 10 is rotated around the rotation axis Q1 by the magnetic force, and the rotation force is applied to the rotating shaft. It is output to the outside via 40.

  Here, for convenience of explanation, the motor 90 is disposed so that the rotation axis Q1 is horizontal (that is, the component of the motor 90 in the direction of the rotation axis Q1 is zero).

  Further, in this motor 90, a component in the direction of the rotation axis Q1 of the resultant magnetic force acting between the rotor 10, the first stator 20 and the second stator 30 (hereinafter referred to as thrust force), the rotor The total force F1 with a force other than the magnetic force acting on the motor 10 (here, a component in the direction of the rotation axis Q1 of the weight of the rotor 10 (here, this component is zero)) is a non-energized state of the motor 90 (that is, the motor 9 is designed to be a negative initial value Fs (Fs≈-80 in FIG. 9) as shown in FIG. Further, in the energized state of the motor 90 (that is, the rotational state of the motor 90), the total force F1 is increased as the phase angle β of the currents Iu, Iv, and Iw flowing through the windings 20a increases while the torque of the motor 90 is at least within a certain range. Is designed to decrease from a positive value to a negative value. The total force F1 is positive in the direction from one side (second stator 30 side) Q + to the other side (first stator 20 side) Q− in the direction of the rotation axis Q1.

  In the above design, for example, the distances d1 and d2 between the rotor 10 and the first stator 20 and the second stator 30 may be adjusted, and the thickness of the steel plate 10g may be adjusted. The shape or material of each of the surface 20g on the rotor 10 side of the magnetic core 20e and the surface 30a on the rotor 10 side of the second stator 30 may be changed, and the magnetic flux density on each surface 20g, 30a may be changed. The surfaces 20g and 30a may be inclined with respect to the direction of the rotation axis Q1 (in this embodiment, the surfaces 20g and 30a are orthogonal to the direction of the rotation axis Q1). .

  In FIG. 9, when the torque of the motor 90 is 0 [Nm] (no load state) (graph g5), 0.5 [Nm] (graph g4), and 1.0 [Nm] (graph) The relationship between the total force F1 and the phase angle β is shown for g3), 2.0 [Nm] (graph g2), and 3.0 [Nm] (graph g1). When the torque of the motor 90 is 3.0 [Nm] and 2.0 [Nm], the total force F1 changes from a positive value to a negative value according to the phase angle β, and is 0.5 [Nm]. And 1.0 [Nm], the total force F1 is designed to be negative over the entire range of the phase angle β.

  As shown in FIG. 8, the inverter circuit 80 includes a plurality (six in this case) of switch elements SU1, SU2, SV1, SV2, SW1, and SW2. Each switch element SU1, SU2 is connected between the anode and the cathode of the DC power supply 70 in a state of being connected in series with each other, and the potential between them is applied to the U-phase electrode 11u of the three-phase load 90. The switch elements SV1 and SV2 are connected between the anode and the cathode of the DC power supply 70 in a state of being connected in series, and the potential between them is applied to the V-phase electrode 11v of the motor 90. The switch elements SW1 and SW2 are connected between the anode and the cathode of the DC power supply 70 in a state of being connected in series with each other, and the potential therebetween is applied to the W-phase electrode 11w of the motor 90.

  Each switch element SU1, SU2, SV1, SV2, SW1, SW2 includes a transistor T and a diode D provided between the main electrodes of the transistor T. The diode D is provided between the main electrodes of the transistor T so that the energization direction is opposite to the energization direction of the transistor T. The control electrode G of each switch element is connected to the control circuit 100. As the switch elements SU1, SU2, SV1, SV2, SW1, and SW2, an IGBT or the like including a reflux diode can be used.

  In the inverter circuit 80, a voltage is applied by the control circuit 100 to the control electrodes G of the switch elements SU1, SU2, SV1, SV2, SW1, SW2, and the conduction / non-conduction of these switch elements is controlled. As a result, the DC power of the DC power supply 70 is converted into three-phase AC power, current is supplied to the electrodes 11u, 11v, and 11w of the phases U, V, and W of the motor 90, and the motor 90 is rotationally driven.

  The control circuit 100 obtains the rotational speed of the motor 90 based on the currents Iu, Iv, Iw flowing through the motor 90 (that is, the current flowing through the windings 20a). Further, the control circuit 100 (i) makes the rotational speed ω of the motor 90 coincide with the rotational speed command value ω *, and (ii) the rotor 10 moves in the direction of the rotation axis Q1 according to the rotational speed ω of the motor 90. The inverter circuit 80 is controlled so as to move. More specifically, in the above (ii), the control circuit 100 moves the rotor 10 toward the first stator 20 until the rotational speed of the motor 90 reaches the high rotational speed upper limit ω2, as shown in FIG. On the other hand, the inverter circuit 80 is controlled so that the rotor 10 moves to the second stator 30 side in the range where the rotational speed ω of the motor 90 is equal to or higher than the high rotational speed upper limit ω2.

  Note that, in order to control the total force F1 as in (ii) above, the control circuit 100 controls the inverter circuit 80 as described below for the operation, and the currents Iu, Iv, and Iw flowing through the windings 20a. By controlling the value and the phase angle β, the thrust force value is set so that it can selectively take a positive value and a negative value even when the torque is maintained.

  As shown in FIG. 8, the control circuit 100 includes a rotational speed command value generation unit 100j, a d-axis current command value generation unit 100d, a d-axis voltage command value generation unit 100e, a q-axis current command value generation unit 100f, q-axis voltage command value generation unit 100g, first coordinate conversion unit 100a, second coordinate conversion unit 100h, PWM signal generation unit 100i, third coordinate conversion unit 100b, and fourth coordinate conversion unit 100c, a position estimation unit 100k, a rotation speed calculation unit 100m, and an initial rotation estimation unit 100q.

  The PWM signal generation unit 100i applies a PWM signal to each control electrode G of the inverter circuit 80 immediately before the rotation of the motor 90 is started, and the predetermined one of the electrodes 11u, 11v, 11w of the motor 90 from the inverter circuit 80 is applied. A predetermined voltage (for example, a high frequency voltage at which the motor 90 does not react) is applied to the two (for example, 11v, 11w). Thus, a voltage is generated at a predetermined one (for example, 11u) of the electrodes 11u, 11v, and 11w of the motor 90 in a state where the rotation of the motor 90 is stopped. Hereinafter, the phase to which the predetermined voltage is not applied is referred to as a non-conducting phase (here, U phase).

  The initial rotational position estimation unit 100q detects the initial rotational position θ0 of the rotor 20 using the detection result of the current sensor corresponding to the non-energized phase of the motor 90 and the voltage generated at the non-conducting phase electrode. More specifically, since the inductance of the motor 90 depends on the rotational position θ of the motor 90, the initial rotational position estimating unit 100q detects the detection result of the current sensor corresponding to the non-conduction phase and the voltage generated at the electrode of the non-conduction phase. From this, the inductance of the motor 90 is estimated, and the initial rotational position θ0 of the motor 90 is estimated from the estimated value.

  The third coordinate conversion unit 100b performs predetermined coordinate conversion on the currents Iv and Iw detected by the current sensors 120v and 120w (ie, from a three-axis three-dimensional coordinate system corresponding to each phase U, V, and W). The α-axis current Iα and the β-axis current Iβ are calculated by performing a coordinate conversion of the α-axis and the β-axis into a two-dimensional coordinate system (two-phase orthogonal stator coordinate system).

  The fourth coordinate conversion unit 100c performs predetermined coordinate conversion (that is, each phase U, V) with respect to a V-phase voltage command value Vv * and a W-phase voltage command value Vw * described later calculated by the second coordinate conversion unit 100h. Coordinate conversion from the three-axis three-dimensional coordinate system corresponding to V and W to the two-dimensional coordinate system (two-phase orthogonal stator coordinate system) of the α-axis and β-axis), and the α-axis voltage command value Vα * and A β-axis voltage Vβ * is calculated.

  The position estimation unit 100k includes an α-axis current Iα and a β-axis current Iβ calculated by the third coordinate conversion unit 100b, and an α-axis voltage command value Vα * and a β-axis voltage calculated by the fourth coordinate conversion unit 100c. Based on the command value Vβ *, a rotational position (position estimation value) θ during rotation of the motor 90 is calculated.

  The rotational speed calculation unit 100m is estimated based on the initial rotational position θ0 estimated by the initial rotational position estimation unit 100g immediately before the rotation start of the motor 90, and is estimated by the position estimation unit 100k when the motor 90 rotates. Based on the rotational position θ, the rotational speed ω of the motor 90 is calculated.

  The first coordinate conversion unit 100a performs the initial calculation calculated by the initial position estimation unit 100g immediately before the rotation of the motor 90 with respect to the currents Iu, Iv, and Iw detected by the current sensors 120u, 120v, and 120w. Using the rotational position θ0 and when the motor 90 rotates, the rotational position θ calculated by the position estimation unit 100k is used to perform predetermined coordinate transformation (that is, three-axis three-dimensional corresponding to each phase U, V, W). Coordinate conversion from a coordinate system to a two-dimensional coordinate system of d-axis and q-axis) is performed to calculate d-axis current Id and q-axis current Iq.

  The d-axis is an axis taken in the direction of the field magnetic flux generated by the field magnet 10a, and the q-axis is an axis orthogonal to the d-axis. The d-axis current Id is a current component that contributes to the d-axis direction of a magnetic field (armature magnetic field) generated by excitation of the armature winding 20a, and the q-axis current Iq is generated by excitation of the armature winding 20a. It is a current component that contributes to the q-axis direction of the magnetic field.

  The rotation speed command value generation unit 100j generates a rotation speed command value ω * for rotating the motor 90 at a desired rotation speed ω.

  The q-axis current command value generation unit 100f is configured such that the rotation speed ω calculated by the rotation speed calculation unit 100m approaches the rotation speed command value ω * from the rotation speed command value generation unit 100j. * Is generated. Specifically, the q-axis current command value generation unit 100f generates a q-axis current command value Iq * by performing a proportional-integral calculation (PI) on the deviation between the rotation speed ω and the rotation speed command value ω *.

  The q-axis voltage command value generation unit 100g is configured such that the q-axis current Iq calculated by the first coordinate conversion unit 100a approaches the q-axis current command value Iq * generated by the q-axis current command value generation unit 100f. Then, the driving voltage Va of the motor 90 at the rotational speed command value ω * is calculated, and the q-axis voltage command value Vq * is generated therefrom. The driving voltage Va on the dq axis model in the steady state is expressed by Equation 1. In Equation 1, Vd * is a d-axis voltage command value [V], Vq * is a q-axis voltage command value [V], φa is a permanent magnet interlinkage magnetic flux [wb], and Ld is an electric machine Child d-axis inductance [H], Lq: armature q-axis inductance [H], Ra is phase resistance [Ω], Id is d-axis current [A], and Iq is q-axis current [H]. A].

  The d-axis current command value generation unit 100d generates a d-axis current command value Id * according to the rotation speed command ω * from the rotation speed command value generation unit 100j. More specifically, as will be described later, the d-axis current command value generation unit 100d determines that the d-axis current command value Id does not perform the weak magnetic field control until the rotation speed command value ω * reaches the rated rotation speed upper limit ω1. On the other hand, in the range where the rotational speed command value ω * is equal to or higher than the rated rotational speed upper limit ω1, the d-axis current command value Id * is generated so that the weak magnetic field control is performed.

  The d-axis voltage command value generation unit 100e is configured such that the d-axis current Id calculated by the first coordinate conversion unit 100a approaches the d-axis current command value Id * generated by the d-axis current command value generation unit 100d. Then, the driving voltage Va of the motor 90 at the rotational speed command value ω * is calculated, and the d-axis voltage command value Vd * is generated therefrom.

  The second coordinate conversion 100h is performed on the motor 90 with respect to the d-axis voltage command value Vd * and the q-axis voltage command value Vq * generated by the d-axis voltage command value generation unit 100e and the q-axis voltage command value generation unit 100g. Before starting the rotation, a predetermined coordinate transformation (ie, using the initial rotational position θ0 calculated by the initial position estimation unit 100g and using the rotational position θ calculated by the position estimation unit 100k when the motor 90 rotates). (coordinate conversion from a two-dimensional coordinate system of d-axis and q-axis to a three-dimensional three-dimensional coordinate system corresponding to each phase U, V, W), U-phase voltage command value Vu *, V-phase voltage command value Vv * and W-phase voltage command value Vw * are calculated.

  Further, the PWM signal generation unit 100i applies a PWM signal to each control electrode G of the inverter circuit 80 during rotation of the motor 90, and performs third coordinate conversion on each phase electrode 11u, 11v, 11w of the motor 90, respectively. The inverter circuit 80 is controlled so that voltages that match the phase voltage command values Vu *, Vv *, and Vw * calculated by the unit 100b are applied. As a result, the rotational speed ω of the motor 90 is controlled to coincide with the rotational speed command value ω *.

  Next, based on FIGS. 10 to 12, the operation of the main part of the rotating electrical machine apparatus 1 (that is, the operation of the q-axis current command value generation unit 100f and the d-axis current command value generation unit 100d) will be mainly described. Hereinafter, a case where the rotational speed command value ω * increases from zero to the maximum rotational speed ωmax (that is, a case where the rotational speed ω of the motor 90 increases from zero to the maximum rotational speed ωmax) will be described as an example. The q-axis current command value Iq * is limited to a range of Iqmin ≦ Iq * ≦ Iqmax, and the d-axis current command value Id * is limited to a range of Idmin ≦ Id * ≦ Idmax, and the currents Iu and Iv flowing through the motor 90 , Iw is limited to the range of Imin ≦ Iu, Iv, Iw ≦ Imax. 10 to 12, a section K1 from 0 to ω3 is a starting area until the rotation of the motor 90 reaches a target rotational speed ω3, and a section K2 from ω3 to ω4 is a low speed rotation area. , Ω4 to ω1 is a rated rotational speed region, ω1 to ω2 is a high-speed rotational region, and ω2 to ωmax is a super-high-speed rotational region. In the following, for convenience of explanation, the motor 90 will be described as being used in a compressor, for example.

  When the rotational speed command value ω * is zero, the d-axis current command value generation unit 100d sets the d-axis current command value Id * to zero so that the d-axis current Id becomes zero as shown in FIG. At this time, the q-axis current command value generation unit 100f sets the q-axis current command value Iq * to zero so that the q-axis current Iq becomes zero as shown in FIG. As a result, the currents Iu, Iv, and Iw are controlled to zero, and the rotational speed ω of the motor 90 is controlled to zero (that is, the motor 90 is stopped). In this state, as shown in FIG. 12 (see also FIG. 9), the total force F1 becomes a negative initial value Fs.

  Then, during the period until the rotational speed command value ω * rises from zero and reaches the rated rotational speed region upper limit ω1 (that is, the sections K1, K2, and K3), the d-axis current command value generation unit 100d is as shown in FIG. The d-axis current command value Id * is set to zero so that the phase angle β = 0 (and thus the d-axis current Id = 0). During this period (0 <ω * ≦ ω1), in the section K1 until the rotational speed command value ω * reaches the target rotational speed ω3, the q-axis current command value generation unit 100f performs the rotational speed ω as shown in FIG. Q-axis current command value Iq * is generated so that reaches the target rotational speed ω3 (that is, q-axis current command value Iq * increases). In the section K2 until the rotational speed command value ω * reaches from ω3 to ω4, the q-axis current command value generation unit 100f provides the torque necessary for the motor 90 to reach the rotational speed command value ω *. The q-axis current command value Iq * is generated so that the q-axis current command value Iq * increases as the rotational speed command value ω * increases. That is, in the case of a compressor, the compression torque for the rotational speed ω is automatically determined by the refrigerant conditions, mechanical loss torque, etc., so q is required to ensure the necessary torque for maintaining the rotational speed command value ω *. A shaft current command Iq * is generated. Here, the q-axis current command value Iq * is generated so as to be the upper limit value Iqmax when ω * = ω4. During the period K3 until the rotational speed command value ω * reaches from ω4 to ω1, the q-axis current command value generation unit 100f maintains the q-axis current command value Iq * at the upper limit value Iqmax as shown in FIG. Similarly, a q-axis current command value Iq * is generated. Note that the rated rotational speed range upper limit ω1 is a rotational speed at which the drive voltage of the motor 90 reaches the upper limit value of the output voltage of the control circuit 100 when β = 0 (in other words, the maximum rotational speed when β = 0). is there.

  Therefore, in the starting region K1 and the low-speed rotation region K2, the currents Iu, Iv, Iw increase with an increase in the rotational speed command value ω * at the phase angle β = 0. In the starting region K1 and the low-speed rotation region K2, the torque of the motor 90 increases as the currents Iu, Iv, and Iw increase, and the total force F1 is initially negative in the starting region K1 as shown in FIG. The value increases from the value Fs toward the positive side to become a positive value, and further increases in the low-speed rotation region K2 and reaches the predetermined value F1a when the rotation speed ω reaches ω4. Note that F1a is the total force F1 when ω = ω4. When the total force F1 moves to the positive side, the rotor 10 is moved to the first stator 10 side by the total force F1, and the torque of the motor 90 increases due to this movement. In this way, the rotor 10 is moved to the first stator 10 side and the torque of the motor 90 is increased, so that the conventional motor (that is, the structure in which the movement of the rotor 10 in the direction of the rotation axis Q1 is restricted) and In comparison, the torque of the motor 90 increases for the same current value (hereinafter, this effect is referred to as a current value reduction effect). In these regions K1 and K2, since the rotational speed is relatively low, the bearing loss in the first and second bearings 50a and 50b is very small.

  Of the low speed rotation region K2, the region where the q-axis current command value Iq * is smaller than the predetermined value Iq1 (that is, the low torque region where the torque of the motor 90 is lower than the predetermined value (region of ω <ω5 in FIGS. 11 and 12). )), Since the total force F1 is positive, no thrust loss occurs in the second bearing 50b, so the bearing loss is very small. Further, since the absolute value of the total force F1 is relatively small as shown in FIG. 12, even if the first stopper 70a contacts the first bearing 50a, the force applied to the first bearing 50a is small, and the bearing loss of the first bearing 50a is also small. small. Therefore, in this case, the rotational efficiency of the motor 90 is increased due to the current value reduction effect and the reduction in bearing loss.

  Further, in this low speed rotation region K2, a region where the q-axis current command value Iq * is larger than the predetermined value Iq1 (that is, a high torque region where the torque of the motor 90 is higher than the predetermined value (in FIGS. 11 and 12, ω5 <ω ≦ In the region of ω4), the total force F1 increases with the torque of the motor 90, so the total force F1 is relatively large. However, since the rotational speed ω of the motor 90 is in the low-speed rotation region, generally load × rotation Compared to the rated rotational speed range K3, both the bearing loss proportional to the speed, the hysteresis loss proportional to the primary speed of the rotational speed, and the eddy current loss proportional to the square of the rotational speed are combined. Small value. Specifically, both the bearing loss and the iron loss applied to the first bearing 50a and the second bearing 50b are relatively small. Most of the loss of the motor 90 in this case is a copper loss in the winding 20a that is proportional to the square of the current value (that is, the square of the torque), but in this case also, the current value reduction effect is exhibited more greatly. Thus, the copper loss is reduced, and the rotational efficiency of the motor 90 is increased.

  When the rotational speed command value ω * becomes larger than ω1 (that is, when entering the high speed rotation region K4), the d-axis current command value generation unit 100d responds to the torque of the motor 90 as shown in FIGS. (Actually, since the torque of the motor 90 has a positive correlation with the q-axis current Iq (and therefore the q-axis current command value Iq *), for example, according to the q-axis current command value Iq *), the total force F1 is positive. The d-axis current command value Id * is generated as a negative value Id1 so that the flux-weakening control is performed in the range (that is, the phase angle β is advanced while the total force F1 is in the positive range). Specifically, referring to FIG. 9, when the torque of motor 90 is 2.0 Nm, phase angle β is advanced to a value greater than 0 [deg] and less than 15 [deg], and motor 90 When the torque is 3.0 Nm, the phase angle β is advanced to 0 [deg] and less than 37 [deg]. Further, the q-axis current command value generation unit 100f causes the absolute value of the q-axis current command value Iq * to decrease as shown in FIG. 11 in response to the increase of the absolute value of the d-axis current command value Id *. Q-axis current command value Iq * is generated. In FIG. 11, the q-axis current command value Iq * is generated so that the q-axis current command value Iq * becomes a predetermined value Iq2 which is a positive value.

  In this high-speed rotation region K4, the torque / current ratio decreases, and the copper loss / torque ratio increases due to this decrease. However, the motor 90 operates at a higher speed within the drive voltage limit range of the motor 90 by the above-described weakening magnetic flux control. It rotates and reaches the rotational speed ω2. The rotational speed ω2 is the maximum rotational speed when the phase angle β is advanced while the total force F1 is in the positive range. In this high-speed rotation region K4, the copper loss increases, but the main cause of the loss of the motor 90 is shifting to the iron loss due to the increase in speed, and the iron loss is reduced by the above-described weakening magnetic flux control. The increase in copper loss is offset by the effect of reducing the loss, whereby the rotational efficiency of the motor 90 is kept relatively high. Further, in the high speed rotation region K4, the total force F1 is also reduced to, for example, F1b within a positive range by the above-described weakening magnetic flux control. Therefore, the bearing loss is also reduced, and the rotation efficiency of the motor 90 is further increased. In FIG. 12, during this period (between ω1 and ω2), the total force F1 is shown as a constant value for convenience of drawing, but it is not always a constant value.

  When the rotational speed command value ω * becomes larger than the high rotational speed upper limit ω2, the d-axis current command value generation unit 100d controls the flux weakening within a range where the total force F1 becomes a negative value as shown in FIGS. In other words, the d-axis current command value Id * is generated (in other words, the d-axis current command value Id * becomes a predetermined negative value Id2 whose absolute value is larger than the negative predetermined value Id1). Specifically, referring to FIG. 9, when the torque of motor 90 is 2.0 Nm, phase angle β is advanced to a value larger than, for example, 15 [deg], and torque of motor 90 is 3.0 Nm. In this case, the advance angle of the phase angle β is controlled to a value larger than 40 [deg], for example. Further, the q-axis current command value generation unit 100f further decreases the absolute value of the q-axis current command value Iq * as shown in FIG. 11 in response to the increase of the absolute value of the d-axis current command value Id *. Then, the q-axis current command value Iq * is generated so that the q-axis current command value Iq * becomes Iq3.

  When the total force F1 becomes a negative value (for example, a predetermined value F1c) by the above-described weakening magnetic flux control, the rotor 10 is moved to the second stator 30 side by the total force F1. As a result of this movement, the interlinkage magnetic flux interlinking the winding 20a of the first stator 10 is reduced (hereinafter, the interlinkage magnetic flux is reduced by reducing the mechanical interlinkage magnetic flux (mechanical weakening magnetic flux control)). In addition, the effect of reducing the flux linkage by the flux weakening control itself is added, so that the rotational speed ω of the motor 90 is further increased and reaches the maximum rotational speed ωmax. In FIG. 12, during this period (between ω2 and ωmax), the total force F1 is shown as a constant value for convenience of drawing, but it is not always a constant value.

  In order to optimize the average efficiency of the motor, drive control that makes the copper loss and the iron loss approximately half by half at a load point (for example, rated load point) that contributes greatly to the average efficiency during the period of use. Suppose. More specifically, although the copper loss does not depend on the excitation frequency f, among the iron loss, the hysteresis loss is generally proportional to the excitation frequency f, and the eddy current loss is proportional to the square of the excitation frequency f. In conventional motors, the load point that has a high contribution to the average efficiency during a certain period of use (for example, the rated load point), the copper loss and the iron loss are approximated in half by half, and the average during the period of use Oriented to optimize efficiency. Therefore, in the conventional motor that performs the drive control described above, it is inevitable that the iron loss occupies most of the loss in the high-speed rotation region K5. On the other hand, since the iron loss is generally proportional to the square of the interlinkage magnetic flux, in the motor according to the present embodiment, the iron loss is greatly reduced in the high-speed rotation region K5 due to the reduction of the mechanical interlinkage magnetic flux described above. By reducing the interlinkage magnetic flux, the value of the current Id that flows when the magnetic flux weakening control required by the conventional motor can be reduced, so that the copper loss is also suppressed. The total loss is reduced by superimposing the iron loss reduction, which is the main cause of the loss, and the copper loss value suppression effect. Therefore, the rotational efficiency of the motor 90 increases in this region, which tends to be lower than the rated load point.

  In the above description of the operation, the phase angle β is set to β until the driving voltage of the motor 90 reaches zero from the zero value of the output voltage of the control circuit 100 (that is, in the range K1 to K3 of 0 ≦ ω * ≦ ω1). Although the case where the drive angle of the motor 90 reaches the upper limit value of the output voltage of the control circuit 100 and the phase angle β is controlled to advance (that is, the magnetic flux weakening control) has been described, it is not limited to this. For example, the phase angle β may be advanced by K1 to K3 until the drive voltage of the motor 90 reaches zero from the upper limit value of the output voltage of the control circuit 100. In this case, for example, as shown in FIG. 21, the d-axis current command value Id * in the section K2 to K3 in ω3 <ω * ≦ ω1 is the value of the d-axis current command value Id * in the range K4 in ω1 <ω * ≦ ω2. The negative value Id5 having an absolute value smaller than Id1 is set, and the d-axis current command value Id * in the range K1 of 0 <ω ≦ ω3 is the d-axis current command value Id * in the range K2 to K3 of ω3 <ω * ≦ ω1. The negative value Id4 is smaller in absolute value than the value Id5. At this time, as shown in FIG. 22, the q-axis current command value Iq * in the range K3 of ω4 <ω ≦ ω1 is set to a value Iq4 smaller than the upper limit value Iqmax in correspondence with the non-zero value Id5. (For example, Iq4 is determined so that the sum of the square of Id5 and the square of Iq4 becomes the square of Iqmax).

  According to the rotating electrical machine apparatus 1 configured as described above, the thrust force (that is, the resultant force of the magnetic force acting between the rotor 10, the first stator 20, and the second stator 30) in the direction of the rotation axis Q1. Component) can be selectively taken between a positive value and a negative value, so that the total force F1 can be selectively directed to the first stator 20 side or the second stator 30 side by the selection. . As a result, when the total force F1 is directed to the first stator 20 side, the distance d1 between the rotor 10 and the first stator 20 is reduced, so that the current value is the same as that of the conventional motor structure. On the other hand, the flux linkage (field magnetic flux) can be increased and the torque can be efficiently generated, whereby the rotational efficiency of the motor 90 can be improved. Further, when the total force F1 is directed to the second stator 30 side, the distance d2 between the rotor 10 and the first stator 30 is widened, whereby the interlinkage magnetic flux can be reduced and the iron loss can be reduced. Thereby, the rotational efficiency of the motor 90 can be improved. Moreover, since the rotary electric machine 90 of 1st Embodiment is used, field flux can be increased / decreased mechanically with a low-cost and simple structure.

  Further, the thrust force (and hence the total force F1) can be controlled by controlling the current values of the currents Iu, Iv, Iw flowing through the windings 20a and the phase angle β (that is, by simple control).

  When the phase angle β is zero, the total force F1 is increased toward the first stator 20 as the q-axis current Iq (in this case, the q-axis current Iq is the same as the current value Ia of the current flowing through the winding 20a) increases. Since it increases, the space | interval d1 of the rotor 10 and the 1st stator 20 can be shortened with the increase in the q-axis current Iq. Thereby, until the q-axis current Iq reaches the current value Iqmax corresponding to the upper limit value of the drive voltage, the rotational efficiency of the axial gap type rotating electrical machine 1 can be improved substantially only by controlling the q-axis current Iq.

  In addition, when the q-axis current Iq reaches a current value Iqmax corresponding to the upper limit value of the drive voltage and is further rotated at a higher speed, the total force F1 is directed toward the second stator 30 by the weakening magnetic flux control (that is, the rotation). By controlling so that the distance d1 between the child 10 and the first stator 20 is increased, the iron loss can be reduced and the speed can be further increased (that is, the rotation efficiency can be improved).

  In this embodiment, as shown in FIG. 13, the initial value Fs of the total force F1 is set to the first stator 20 side (Q-side) from the initial value Fs value of FIG. 9 (Fs≈-80 in FIG. 9). You may set to the value shifted | deviated. With this setting, the graphs g1 to g4 shift to the first stator 20 side, and due to this shift, the negative value ranges of the graphs g1 and g2 (that is, the range of the phase angle β where the total force F1 is a negative value). The phase angle β is shifted in the increasing direction. This setting is suitable when the control of the rotating electrical machine apparatus 1 is robust and the upper limit value of the phase angle β is large. This is because a further ultra-high speed can be obtained by using the effect of the present invention while making full use of the effect of high speed and high torque, that is, high output in normal magnetic flux weakening control.

  Further, as shown in FIG. 14, the initial value Fs of the total force F1 may be set to a value shifted to the second stator 30 side (Q + side) from the value of the initial value Fs of FIG. This setting is a reverse pattern of the reason described above, and is suitable when the rotating electrical machine apparatus 1 has a small upper limit value of the phase angle β for some control reasons. This is because the range in which the effects of the present invention can be obtained can be secured and expanded within the upper limit of the phase angle β.

<Sixth Embodiment>
In the fifth embodiment, the mechanical flux-weakening control is performed in the high-speed rotation region, but in this embodiment, the mechanical flux-weakening control is performed in the low-speed rotation region. Since the configuration of this embodiment is the same as that of the fifth embodiment (FIG. 8), description thereof is omitted. Hereinafter, the operation of the rotating electrical machine apparatus 1B according to this embodiment (that is, the operation of the q-axis current command value generation unit 100f and the d-axis current command value generation unit 100d) will be mainly described with reference to FIGS. Hereinafter, a case where the rotational speed command value ω * increases from zero will be described as an example. Moreover, below, for convenience of explanation, the case where the motor 90 is used in, for example, a compressor will be described. The q-axis current Iq is limited to the range of Iqmin ≦ Iq ≦ Iqmax, the d-axis current Id is limited to the range of −Idmax ≦ Id ≦ Idmin, and the absolute values Ia of the currents Iu, Iv, and Iw are Iamin. It is assumed that the range is limited to a range of ≦ Ia ≦ Iamax.

  When the rotational speed command value ω * is zero, the output torque T is zero as shown in FIG. 17, and therefore the absolute values Ia of the currents Iu, Iv, Iw are also zero. Therefore, as shown in FIG. 16, the d-axis current command value generation unit 100d sets the d-axis current command value Id * to zero so that the d-axis current Id becomes zero, and the q-axis current command value generation unit 100f In this way, the q-axis current command value Iq * is set to zero so that the q-axis current Iq becomes zero. As a result, the currents Iu, Iv, and Iw are controlled to zero, and the rotational speed ω of the motor 90 is controlled to zero (that is, the motor 90 is stopped). In this state, the total force F1 becomes a negative initial value Fs.

  Then, the rotational speed command value ω * increases, and thus the rotational speed ω also increases, and the iron loss increases due to the increase of the excitation frequency. When Tmax is reached and the current is Tamax), the low speed region is defined as the region below the rotational speed ωL where the copper loss is greater than the iron loss. In the low speed region, the current phase angle β is controlled as shown in FIG. 15 according to the output torque T of the motor 90. In the case of a compressor, the compression torque for the rotational speed ω is automatically determined by the refrigerant conditions, mechanical loss torque, etc., so that the q axis is set so as to ensure the necessary torque for maintaining the rotational speed command value ω *. Current command Iq * is determined. More specifically, the q-axis current command value generation unit 100f determines that the q-axis current command value depends on the frequency of the rotation speed command value ω * when the rotation speed ω is smaller than the rotation speed command value ω *. When Iq * is increased and the rotational speed ω is larger than the rotational speed command value ω *, the q-axis current command value Iq * is decreased depending on the frequency of the rotational speed command value ω *. As a result, the q-axis current command value Iq * increases as the output torque T increases as shown in FIG. The d-axis current command generation unit 100d generates a d-axis current command value Id * corresponding to the q-axis current command value Iq * generated by the q-axis current command value generation unit 100f.

  Specifically, in the region of 0 <T <T1 (low torque region) in FIG. 15, the d-axis current command value generation unit 100d performs d-axis in order to maintain the d-axis current Id at zero as shown in FIG. The current command value Id * is maintained at zero. As a result, the currents Iu, Iv, and Iw are controlled to current values that can maintain the rotational speed of the rotational speed command value ω * with the phase angle β = 0. Therefore, in this region (0 <T <T1), the output torque T of the motor 90 increases as the absolute value Ia of each current Iu, Iv, Iw increases (FIG. 17) and the total force F1 becomes the initial value Fs. Increases from zero to zero (however, the total force F1 is maintained at a negative value, the rotor 10 is moved to the second stator 30 side, and the rotor 10 and the first stator 20 The distance d1 remains large). As a result, as will be described later, in the low torque region, the loss with respect to the torque is relatively small and the rotation efficiency is high.

  Next, in the region of T1 ≦ T ≦ T2 in FIG. 15 (low torque region, that is, when the torque is equal to or less than a predetermined value), the d-axis current command value generation unit 100d performs the q-axis current command value as shown in FIG. A d-axis current command value Id * (Id1 (= 0) <Id * ≦ Id2) corresponding to Iq * (Iq1 <Iq * ≦ Iq2 in this region) is generated. As a result, the currents Iu, Iv, and Iw are rotated at a phase angle β (for example, 0 ° ≦ β ≦ 10 °, that is, a phase angle β at which the total force F1 is a negative value) between T1 and T2 in FIG. The current value is controlled to maintain the rotational speed of the speed command value ω *. Therefore, in this region (T1 ≦ T ≦ T2), the output torque T of the motor 90 increases as the absolute values Ia of the currents Iu, Iv, and Iw increase (FIG. 17), and the total force F1 also has a negative value. Increases in the range (that is, when the total force F1 is maintained at a negative value, the rotor 10 is moved to the second stator 30 side, and the distance d1 between the rotor 10 and the first stator 20 is large. Maintained). As a result, as will be described later, in the low torque region, the loss with respect to the torque is relatively small and the rotation efficiency is high.

  Next, in the region of T2 <T ≦ T3 in FIG. 15 (high torque region, that is, when the torque is equal to or less than a predetermined value), the d-axis current command value generation unit 100d performs the q-axis current command value as shown in FIG. A d-axis current command value Id * (Id2 <Id * ≦ Id3) corresponding to Iq * (Iq2 <Iq * ≦ Iq3 in this region) is generated. As a result, each of the currents Iu, Iv, and Iw has a phase angle β between T2 and T3 in FIG. 15 (10 ° <β ≦ 20 °, that is, a phase angle at which the total force F1 becomes a positive value and reluctance torque can be obtained. β) and a current value that can maintain the rotational speed of the rotational speed command value ω *. Therefore, in this region (T2 <T ≦ T3), as the absolute value Ia of each current Iu, Iv, Iw increases, the output torque T of the motor 90 increases (FIG. 17) and the total force F1 is also a positive value. It increases in a range (that is, the total force F1 is maintained at a positive value, whereby the distance d1 between the rotor 10 and the first stator 20 is kept small). As a result, as will be described later, in the high torque region, the loss with respect to the torque is relatively small and the rotation efficiency is high. Further, since the reluctance torque is used, the torque / current ratio is increased by increasing the torque by the combined use of the reluctance torque and the magnet torque, thereby increasing the torque / copper loss ratio and further improving the rotation efficiency. Note that Iq3 and Id3 in FIG. 16 are the q-axis current value and the d-axis current value corresponding to the torque T3, respectively.

  23 is a graph of loss with respect to the torque of the motor 90 when the distance d1 (see FIG. 1) between the first stator 20 and the rotor 10 is small, and g60 in FIG. 23 is when the distance d1 is large. It is a graph of the loss with respect to the torque of the motor 90 of.

When d1 is large (hereinafter referred to as g60), the linkage magnetic flux of the first stator 20 is φ, and when d2 is small (hereinafter referred to as g50), the linkage of the first stator 20 The magnetic flux is Aφ. Here, A is a constant larger than 1 (A = √2 here). Also, since the flux linkage in the case of g50 is A times the flux linkage in the case of g60, assuming that the iron loss is proportional to the square of the magnetic flux density B by general theory, the iron loss in the case of g50 is the iron loss in the case of g60. to ^double a of loss (ie, 2-fold). The copper loss of a three-phase motor can be expressed in the form of 3 · I ² · R (I: phase currents Iu, Iv, Iw, R: phase resistance), so the copper loss for g50 is the copper loss for g60. 1 / A ² times (ie 1/2).

In the case of g50 and g60, the torque at the same torque and the same loss (that is, the intersection when g50 and g60 are represented on the same coordinate) is Tc (T2 = Tc in the above description), and Tc or less Is a low torque region, and Tc or higher is a high torque region. When a loss W1 in the case of g50 and a loss W2 in the case of g60 are compared with a loss W2 in the case of g60 at a certain torque T _L in the low torque region, W1> W2, so that the case of g60 (that is, when d1 is large) is higher. It turns out that it is efficiency. Further, when a loss W3 in the case of g50 and a loss W3 in the case of g60 are compared with a loss W3 in the case of g60 at a certain torque T _H (for example, Tmax) in the high torque region, W3 <W4. ) Is more efficient.

  Therefore, when the design is made so that the total force F1 crosses zero when the torque of the motor 90 crosses the torque Tc (in other words, the torque at which F1 = 0 and Tc are approximately the same), The desired effect (that is, the effect of increasing the rotational efficiency of the motor 90) is exhibited in the operation. For example, when the motor 90 is controlled at the current phase angle β = 0, although not shown in FIG. 9, the torque at which the total force F1 = 0 is about 1.5 Nm. Is larger so that the entire graph is shifted upward as shown in FIG. 13 so that Tc substantially matches the torque at which F1 = 0. Conversely, when 1.5 Nm is smaller than Tc, As shown in FIG. 14, the entire graph may be shifted downward, and the design may be made so as to roughly match the torque at which Tc becomes F1 = 0. With such a design, the ratio of copper loss to iron loss can be variably controlled in accordance with the torque region (for example, the high torque region and the low torque region) only with the q-axis current Iq with β = 0 °. The desired effect can be exhibited.

  It should be noted that the effect of the above purpose can be achieved by current control instead of the above design. For example, in the case of Tc = 20 Nm, in FIG. 9, for example, if the torque is variably controlled at the phase angle β = 20 ° (that is, the point A1 at β = 20 ° of g5 → g4 → the point A2 at β = 20 ° of g3 → If the torque is variably controlled so as to change in the order of the point A3 at β = 20 ° of g2 to the point A4 at β = 20 ° of g1, the torque at which F1 = 0 is shifted to slightly over 2.0 Nm (≈Tc). it can. Of course, as the torque increases, the contribution of the reluctance torque also increases, so that the phase angle β is advanced as the torque increases (for example, in FIG. 9, the point B1 of g5 → g4 = 0 ° → β = β3 of g3 = (Advance angle control in the order of 5 ° point B2 → g2 β = 10 ° point B3 → g1 β = 20 ° point A4). In this way, an effect of reducing copper loss can be obtained.

  According to the rotating electrical machine apparatus 1B configured as described above, the rotor 10 is moved in the direction of the rotation axis Q1 in accordance with the torque of the motor 90. Therefore, according to the torque region (for example, the high torque region and the low torque region). Thus, the ratio between the copper loss and the iron loss can be controlled, whereby the rotational efficiency of the motor 90 can be increased in accordance with the torque of the motor 90.

<Seventh embodiment>
In the fifth embodiment, the movement of the rotor 10 in the direction of the rotation axis Q1 was used to increase the rotation speed and efficiency of the motor 90. In this embodiment, the movement of the rotor 10 in the direction of the rotation axis Q1 is performed. The movement is used to avoid demagnetization of the field member 10 i of the rotor 10. In the following, based on FIG. 18, the same parts as those in the fifth embodiment are denoted by the same reference numerals, and the description thereof will be omitted and different parts will be mainly described.

  The control circuit 100C of this embodiment is the same as the control circuit 100 of the fifth embodiment except that the d-axis current command value generation unit 100dC is changed as follows with respect to the d-axis current command value generation unit 100d. Composed. The d-axis current command value generation unit 100dC generates the d-axis current command value Id * so that the total force F1 becomes a positive value. More specifically, the d-axis current command value generation unit 100dC sets the d-axis current command value Id * so that the total force F1 becomes a positive value (that is, the total force F1 faces the first stator 10 side). Is generated.

  Here, for convenience of explanation, the d-axis current command value generation unit 100dC generates the d-axis current command value Id * so that the total force F1 becomes a positive value, but it is not necessary to strictly control in this way. . When the total force F1 is a negative value, the rotor 10 is attracted to the second stator 30 side, and there is no need to avoid demagnetization. Therefore, the current command value ( Any control is possible as long as the d-axis current command value Id * and the q-axis current command value Iq *) are controlled.

  In this embodiment, a demagnetization avoidance mode detection unit 100t that detects that a demagnetization current flows through the winding 20a of the motor 90 is further provided. The demagnetizing current is a current that can cause irreversible demagnetization in the field member 10i. Here, the demagnetizing current is a current having a negative d-axis current Id whose absolute value is larger than a predetermined value.

  The demagnetization avoidance mode detection unit 100t is in a situation where a negative d-axis current Id whose absolute value is equal to or greater than a predetermined value does not flow if the current value of each of the currents Iu, Iv, Iw and the phase angle β are values as controlled. When a negative d-axis current Id having an absolute value greater than or equal to a predetermined value flows, it is determined that a demagnetizing current has flowed. When a demagnetizing current is generated, the total force F1 changes suddenly from a positive value to a negative value, the rotor 10 is moved to the second stator 30 side, and the interlinkage magnetic flux of the winding 20a is, for example, Aφa in the previous example. Is reduced to 1 / A from φa to φa, and as a result, ωAφa, which is the induced voltage of the flux linkage, also decreases to 1 / A of ωφa. From these, the demagnetization avoidance mode detection unit 100t avoids demagnetization by detecting both the demagnetization current and the detection of the sudden change in the induced voltage ωAφa calculated from the rotational speed ω to ωφa. It is determined that a mode has occurred. The demagnetization avoidance mode detection unit 100t detects, for example, the voltages of the electrodes 11u, 11v, and 11w (that is, the terminal voltage of the motor 90), obtains the interlinkage magnetic flux based on the detected value, and obtains the obtained interlinkage. The induced voltage is obtained using the value of the magnetic flux and the rotation speed ω calculated by the rotation speed calculation unit 100m. The demagnetization avoidance mode detection unit 100t makes a distinction from the case where the rotor 10 is moved in the direction of the rotation axis Q1 by its own control based on the determination result of the occurrence of the demagnetization avoidance mode.

  In addition to the rotation speed command value generation unit 100jC of this embodiment performing the same processing as the rotation speed command value generation unit 100j of the first embodiment, the following processing is added. That is, when the demagnetization avoidance mode detection unit 100t detects that the rotation speed command value generation unit 100jC has shifted to the demagnetization avoidance mode, the d-axis current command value Id * and the q-axis current are temporarily stopped. The command value Iq * is both set to zero, thereby resetting the initial rotational position estimation unit 100q and the rotational position estimation process based on the position.

  In addition, the control circuit 100C of this embodiment further performs synchronous pull-in of the rotor 10 and starts the rotor 10 at the same time when the rotation control of the rotor 10 is started in the control circuit 100 of the first embodiment as will be described later. The synchronous pull-in control unit 100x that performs suction toward the first stator 20 side, the synchronous pull-in failure detection unit 100r that detects whether the synchronous pull-in has failed, and the transition to the sensorless control of the rotor 10 have failed. A sensorless control transition failure detection unit 100s for detecting whether or not.

  Next, based on FIG. 19, it demonstrates centering around operation | movement of the principal part of the rotary electric machine apparatus 1C.

  In step S1, the control circuit 100C is activated. In step S2, the rotor 10 is synchronously retracted, and at the same time, the rotor 10 is sucked toward the first stator 20 side. More specifically, the synchronous pull-in control unit 100x causes the currents Iu, Iv, and Iw to flow from the inverter 80 to the motor 90 through the PWM signal generation unit 100i with the rotational position of the rotor 10 unknown. The inverter 80 is controlled so that a rotating magnetic field is applied to the rotor 10 and the current values of the currents Iu, Iv, and Iw gradually increase. Thereby, the rotor 10 starts to rotate gradually, and the field member 10i rotates in synchronization with the rotating magnetic field (this is called synchronous pull-in of the rotor 10). As the current values of the currents Iu, Iv, and Iw increase, the total force F1 increases to the positive side, and the rotor 10 is attracted to the first stator 20 side by the total force F1.

  In step S3, the synchronous pull-in failure detection unit 100r detects whether or not the synchronous pull-in of the rotor 10 in step S2 has failed. More specifically, the synchronization pulling failure detection unit 100r determines whether or not the output voltage of the motor 90 at the time of synchronous pulling (that is, the voltages of the electrodes 11u, 11v, and 11w) is equal to or higher than a predetermined voltage. When the voltage is less than the predetermined voltage (that is, when the output voltage of the motor 90 is less than the assumed value), it is determined that the synchronous pull-in of the rotor 10 has failed. Further, the synchronization pull-in failure detection unit 100r determines that the synchronization pull-in of the rotor 10 has succeeded when the output voltage of the motor 90 is equal to or higher than the predetermined voltage. The predetermined voltage is smaller than the output voltage ωφa of the motor 90 assumed when the synchronous pulling is successful with respect to the alternating speed ω of the current supplied to the motor 90 when the rotor 10 is synchronously pulled. Value. If the synchronous pull-in of the rotor 10 has failed, the process proceeds to step S7. If the synchronous pull-in of the rotor 10 has succeeded, the process proceeds to step S4.

  In step S4, the motor 90 is sensorlessly controlled by the control circuit 100jC. More specifically, the control circuit 100C rotationally drives the motor 90 based on the rotational position estimated by the position estimation unit 100k.

  In step S5, the sensorless control transition failure detection unit 100s detects whether or not the subsequent processing to the sensorless control in step S4 has failed. More specifically, the sensorless control transition failure detection unit 100s determines whether the difference between the measured value of each current Iu, Iv, Iw and the control value is equal to or greater than a predetermined value (that is, whether the difference is greater than expected). ) If the difference between the measured value and the control value is greater than or equal to a predetermined value, it is determined that the transition to sensorless control has failed, and the difference between the measured value and the control value is less than the predetermined value. In this case, it is determined that the transition to the sensorless control is successful. Alternatively, the sensorless control transition failure detection unit 100s detects whether or not the difference between the measured value of the phase angle β of each of the currents Iu, Iv, and Iw and the control value is equal to or greater than a predetermined value, If the difference is greater than or equal to a predetermined value, it is determined that the transition to sensorless control has failed, and if the difference between the actual measurement value and the control value is less than the predetermined value, it is determined that the transition to sensorless control has succeeded. To do. If both the current value and the phase angle β are detected and either or both are greater than or equal to the predetermined value, it is determined that the transition to the sensorless control has failed. Otherwise, the sensorless control is entered. It may be determined that the migration has succeeded.

  For example, the current values of the currents Iu, Iv, and Iw detected by the current sensors 120v, 120u, and 120w can be used as the measured values of the current values. As the control value of the current value, a value obtained from the d-axis current command value Id * and the q-axis current command value Iq * can be used. As the actual measurement value of the phase angle β, for example, a value obtained from the d-axis current Id and the q-axis current Iq obtained by the first coordinate conversion unit 100a can be used. As the control value of the phase angle β, for example, a value obtained from the d-axis current command value Id * and the q-axis current command value Iq * can be used.

  In step S5, if the transition to sensorless control is successful, the process proceeds to step S6. If the transition to sensorless control fails, the process proceeds to step S7.

  In step S6, the rotor 10 is controlled to avoid demagnetization by the control circuit 100C (that is, the rotor 10 is controlled to rotate so that the total force F1 faces the first stator 20 side). More specifically, the d-axis current command value generation unit 100dC performs the d-axis current command so that the phase angle β = 0 or the phase angle β is advanced while the total force F1 is positive. Generate the value Id *. The q-axis current command value generation unit 100f generates the q-axis current command value Iq * so that the difference between the rotation speed command value ω * and the rotation speed ω becomes zero. By this control, the total force F1 is directed to the first stator 20 side, so that the rotor 10 is maintained on the first stator 20 side, and thereby the current value reduction effect (see the fifth embodiment) causes the motor to 90 is rotated efficiently.

  When a negative d-axis current Id (that is, a demagnetizing current) having an absolute value greater than or equal to a predetermined value flows in step S7, the total force F1 is secondarily reflected by the influence of the demagnetizing current in step S8. The rotor 10 is directed to the stator 30 side, and thereby the rotor 10 is moved to the second stator 30 side in a self-reflection manner. Thereby, the space | interval of the rotor 10 and the 1st stator 20 spreads, and it is prevented that the rotor 10 is demagnetized. Then, the process proceeds to step S9. If no demagnetizing current flows in step S7, the process returns to step S6.

  In step S9, the transition to the demagnetization avoidance mode is detected by the demagnetization avoidance mode detection unit 100t, and the d-axis current command value Id * and the q-axis current are used to temporarily stop the motor 90 by the rotation speed command value generation unit 100jC. Both command values Iq * are made zero. Then, the process returns to step S1.

  According to the rotating electrical machine apparatus 1C configured as described above, as the demagnetization avoidance control, the rotation of the rotor 10 is controlled so that the total force F1 is directed toward the first stator 20 side. When the magnetic current does not flow, the rotor 10 is moved to the first stator 20 side by the total force F1 and the distance d1 between the rotor 10 and the first stator 20 is shortened. Therefore, the fifth embodiment will be described. The rotational efficiency of the motor 90 can be improved due to the reduced current value. Further, when a demagnetizing current flows through the winding 20a, the total force F1 is increased to the negative side in a self-reflex manner by the demagnetizing current, whereby the rotor 10 is moved in a self-reflex manner to the second stator 30 side. As a result, the distance d1 between the rotor 10 and the first stator 20 is increased, thereby preventing the rotor 10 from being demagnetized by the demagnetizing current.

  Further, as demagnetization avoidance control, specifically, control is performed so that the phase angle β = 0 or the phase angle β is advanced while the total force F1 is in a positive range. The total force F1 can be controlled to be directed toward the first stator 10 only by the control.

  In step S2, the synchronous pull-in of the rotor 10 and the suction of the rotor 10 toward the first stator 20 are performed at the same time, but first the rotor 10 toward the first stator 20 side. Then, the rotor 10 may be synchronously drawn. In this case, the following steps S2-1 and S2-2 are performed instead of the above step S2. That is, in step S2-1, the control circuit 100C causes a direct current (DC current) to flow from the inverter 80 to the motor 90 as the currents Iu, Iv, and Iw for a certain period of time with the rotational position of the rotor 10 unknown. Thereafter, the inverter 80 is controlled so that the current value of the direct current gradually increases. As a result, the rotor 10 does not rotate to the position where the magnetic field of “strong field” is applied to the field member 10i in the initial stage of the application of the direct current. As the angle rises, the rotor 10 is moved to the first stator 20 side. In step S2-2, the inverter 80 is controlled by the control circuit 100C so as to control the rotation of the rotor 10. Thereby, rotation control is performed in a state where the rotor 10 is synchronously drawn. Then, the process proceeds to step S3.

1, 1B, 1C Rotating electrical machine 10, 10B, 10C Rotor 20 First stator 30 Second stator 40, 40C Rotating shaft 50a, 50aB, 50aC, first bearing 50b, 50bB, 50bC Second bearing first fixed Child (20)
60 Housing 70a, 70aB, 70aC First stopper 70b, 70bB, 70bC Second stopper 80 Inverter means 90, 90B, 90C Axial gap type rotating electrical machine 100, 100B, 100C Control means 200 Compressor 300 Container 401 Cylinder 402 Upper end plate 403 Lower end Plate 406 Crankpin 407 Piston

Claims (18)

A housing (70);
A rotation shaft (40, 40C) disposed along the rotation axis (Q1);
First and second bearings (50a, 50b, 50aB, 50bB, 50aC, 50bC) disposed in the housing and supporting the rotating shaft;
First fixed having a plurality of winding cores (20e) fixed to the housing and annularly arranged around the rotation axis on one side (Q +) surface (20d) in the rotation axis direction. Child (20),
A second stator (30) disposed in the housing so as to be spaced from the first stator on one side (Q +) in the rotational axis direction with respect to the first stator;
A plurality of field magnets disposed on the rotary shaft so as to be disposed between the first and second stators and annularly disposed around the rotation axis on the first stator side surface (10c1). A rotor (10, 10B, 10C) which has a member (10i) and is movable to the first stator side or the second stator side along the rotation axis direction;
A first stopper (70a, 70aB, 70aC) for limiting a range of movement of the rotor toward the first stator;
A second stopper (70b, 70bB, 70bC) for limiting a range of movement of the rotor to the second stator side;
An axial gap type rotating electrical machine comprising: An axial gap type rotating electrical machine (100) according to claim 1,
The rotor (10) is fixed to the rotating shaft (40);
Each of the first and second bearings (50a, 50b) is fixed to the housing (60) and supports the rotating shaft so as to be movable in the direction of the rotating shaft (Q1). Axial gap type rotating electrical machine. An axial gap type rotating electrical machine (100) according to claim 2,
The first stopper (70a) is fixed between the first bearing (50a) and the first stator (20) in the rotating shaft (40),
The axial gap type rotating electrical machine, wherein the second stopper (70b) is fixed between the second bearing (50b) and the second stator (30) in the rotating shaft. An axial gap type rotating electrical machine (100B) according to claim 1,
The rotor (10B) is fixed to the rotating shaft (40),
The first and second bearings (50aB, 50bB) are respectively fixed to the rotating shaft, are movable in the rotating shaft direction (Q1) with respect to the housing (60), and An axial gap type rotating electrical machine characterized by being disposed so as to be fixed in a direction orthogonal to the rotational axis direction. An axial gap type rotating electrical machine (100B) according to claim 4,
The first stopper (70aB) is disposed on the housing (60) so as to limit a movement range of the first bearing (50a) to the other side (Q-) in the direction of the rotation axis (Q1),
The axial gap is characterized in that the second stopper (70bB) is disposed in the housing so as to limit a movement range of the second bearing (50b) to one side (Q +) in the rotation axis direction. Type rotating electric machine. An axial gap type rotating electrical machine (100C) according to claim 1,
The rotor (10C) is disposed so as to be relatively movable in the direction of the rotation axis (Q1) with respect to the rotation shaft (40C) and not to be relatively rotatable around the rotation axis.
The first and second bearings (50aC, 50bC) are fixed to the housing (60), respectively, and the rotary shaft is rotatable about the rotary shaft and fixed in the direction of the rotary shaft. An axial gap type rotating electrical machine characterized by supporting in the same manner. An axial gap type rotating electrical machine (100C) according to claim 6,
The rotating shaft (40C) is a portion disposed between the first and second stators (20, 30) and has a small diameter portion (40d) having a first diameter (d3), and the small diameter. A large-diameter portion (40e) on both sides of the portion and having a second diameter (d4) larger than the first diameter;
The rotor (10C) is disposed so as to be relatively movable in the direction of the rotation axis with respect to the small diameter portion and relatively fixed around the rotation axis,
The first stopper (70aC) is constituted by a step at the boundary between the small diameter portion and the large diameter portion (40e +) on one side (Q +),
The second stopper (70bC) is constituted by a step at a boundary between the small diameter portion and the large diameter portion (40e-) on the other side (Q-). An axial gap type rotating electrical machine (100C) according to claim 7,
A cross section perpendicular to the rotation axis (Q1) in the small diameter portion (40d) is formed in a non-circular shape,
The rotor (10C) is formed with a center hole (10n) into which the cross section is fitted so as to penetrate both surfaces in the rotation axis direction, and the small diameter portion is inserted into the center hole. An axial gap type rotating electrical machine characterized by that. An axial gap type rotating electrical machine (100C) according to claim 8,
The axial gap type rotating electrical machine characterized in that the cross section perpendicular to the rotation axis (Q1) in the small diameter portion (40d) is a gear shape or a star shape. A container (300);
A rotation shaft (40) disposed along the rotation axis (Q1);
First and second bearings (50a, 50b) disposed in the container and supporting the rotation shaft so as to be movable in the direction of the rotation axis and fixed in a direction perpendicular to the rotation axis;
First fixed having a plurality of magnetic cores (20e) with windings, which are fixed to the container and arranged in a ring around the rotation axis on one side (Q +) of the rotation axis direction (20d). Child (20),
A second stator (30) disposed in the container so as to be spaced from the first stator on one side (Q +) in the rotation axis direction with respect to the first stator;
A plurality of field magnets disposed on the rotary shaft so as to be disposed between the first and second stators and annularly disposed around the rotation axis on the first stator side surface (10c1). A rotor (10) having a member (10i) and movable to the first stator side or the second stator side along the rotation axis direction;
A cylindrical body (401) disposed in the container;
An upper end plate (402) for closing the upper opening of the main end;
A lower end plate (403) for closing the lower opening of the main end;
In the main body portion, a crank pin (406) disposed on the rotating shaft inserted through the upper end plate and the lower end plate,
A piston (407) disposed within the main body so as to be fitted to the outer periphery of the crankpin;
The height (D1) of the crank pin in the rotational axis direction is set to be shorter than the height (D2) of the piston in the same direction, and the crank is arranged to be movable in the rotational axis direction, The lower surface (402a) of the upper end plate functions as a first stopper that regulates the movement range of the other side (Q-) of the crank in the rotation axis direction, and the upper surface (403a) of the lower end plate A compressor that functions as a second stopper that regulates a movement range on one side (Q +) in the rotation axis direction. The axial gap type rotating electrical machine according to any one of claims 1 to 9, or the compressor according to claim 10,
Inverter means (80) for selectively passing a current through the winding (20a) of each winding core (20e);
Control means (100, 100B) for controlling the inverter means to selectively flow a current to each of the windings to control the rotation of the rotor;
With
A component of the resultant magnetic force acting between the first and second stators (20, 30) and the rotor (10, 10B, 10C) in the direction of the rotation axis, and acting on the rotor. The total force (F1) with the component in the rotation axis direction of the force other than the magnetic force is positive when the direction from the one side toward the other side is positive, and the value is selectively between a positive value and a negative value. The rotating electrical machine apparatus, wherein the control means controls the inverter means. The rotating electrical machine apparatus (1, 1B) according to claim 11,
The control means (100, 100B) controls the inverter means (80) to control the current value and the phase angle of the current flowing through the windings (20a), so that the total force includes the positive value and the A rotating electrical machine apparatus that selectively takes a value between negative values. The rotating electrical machine apparatus (1) according to claim 11 or 12,
The control means (100) sets the phase angle (β) of the current flowing through the windings (20a) to zero until the drive voltage of the rotating electrical machine reaches the output voltage upper limit value of the control means, and A rotating electrical machine apparatus that controls rotation of a child. The rotating electrical machine apparatus according to any one of claims 11 to 13,
When the driving voltage of the rotating electrical machine reaches the output voltage upper limit value of the control means, the control means (100) is configured so that the total force (F1) faces the second stator side. The rotating electrical machine apparatus is characterized in that the rotation is controlled by magnetic flux control. The rotating electrical machine apparatus (1B) according to claim 11 or 12,
The control means (100B) controls the rotation of the rotor so that the total force (F1) faces the second stator when the torque of the rotating electrical machine apparatus is less than a predetermined value. Rotating electrical machine device. A rotating electrical machine apparatus (1B) according to any one of claims 11, 12 and 15,
When the torque of the rotating electrical machine apparatus is equal to or greater than the predetermined value, the control means (100B) is configured to allow a current to flow through the windings (20a) so that the total force (F1) faces the first stator side. The rotor is controlled to rotate by controlling the current value and the phase angle (β). The axial gap type rotating electrical machine according to any one of claims 1 to 9, or the compressor according to claim 10,
Inverter means (80) for selectively passing a current through the winding (20a) of each winding core (20e);
Control means (100C) for controlling the inverter means to selectively flow a current to each of the windings to control the rotation of the rotor;
With
The control means (100C) is configured such that a total force (F1) of a component in the rotation axis direction of the resultant force and a component in the rotation axis direction of a force other than the magnetic force acting on the rotor is the first stator side. The rotating electrical machine apparatus is characterized in that the rotation of the rotor is controlled so as to face. The rotating electrical machine apparatus according to claim 17,
The control means (100C) is configured so that the phase angle (β) becomes zero, or the rotor is weakened and the magnetic flux control is performed in a range where the total force (F1) faces the first stator side. A rotating electrical machine apparatus that controls rotation of a rotor (10).

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