JP2011130254A - Radio communication apparatus - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To provide a radio communication apparatus having an RFID tag function commonly utilizable in an LF or HF band RFID system and a UHF band RFID system in which mounting areas of antennas as large as possible can be ensured and a communication distance is comparable to that of each single antenna for an LF band or an HF band and a UHF band. <P>SOLUTION: The radio communication apparatus includes: a dielectric body having one main surface and the other main surface; a coil antenna formed on the one main surface of the dielectric body and having an electrically connected IC chip for coil antenna; a monopole antenna formed on the one main surface or the other main surface of the dielectric body on an outer circumference of the coil constituting the coil antenna and grounded through the coil antenna; a meander line constituting the monopole antenna; and an IC chip for monopole antenna to which electricity is fed by the monopole antenna. <P>COPYRIGHT: (C)2011,JPO&INPIT

Description

  The present invention relates to a radio communication apparatus having a tag antenna configuration used in an RFID (Radio Frequency Identification) system, and more particularly to a radio communication apparatus (RFID tag) capable of sharing multiple frequencies, a so-called hybrid card.

In recent years, RFID systems for automatically recognizing and managing people and articles are rapidly spreading.
The electromagnetic field radiated from the antenna used in the RFID system has three fields: a quasi-electrostatic field, an induction field, and a radiation field. These field strengths are respectively the cube of the distance from the antenna and the antenna. It is inversely proportional to the square of the distance and the square of the distance from the antenna.

  From this point of view, the RFID system communication methods are roughly classified into an induction field coupling method using an induction field in the LF band and an HF band and a radiation field coupling method using a radiation field in the UHF band.

  As for the former inductive field coupling method, an RFID system using the LF band of 125 kHz to 135 kHz has been used in the factory automation (FA) field since the 1980s. The RFID system using the 13.56 MHz band of the HF band is widely used for entrance / exit security management, entrance / exit security management, and fee settlement in public transportation such as buses and railways.

On the other hand, the latter radiation field coupling method uses frequencies of 433 MHz, 860 MHz to 960 MHz, and 2.45 GHz, and has a longer communication distance than the former, mainly for logistics management and parts management in production plants. It is being put into practical use.
However, at present, the former inductive field coupling method, in particular, the HF band RFID system is most widely used.

  In such a situation, there is a desire to keep the existing HF band RFID system as it is and to introduce a new UHF band RFID system. In this case, considering the convenience of the user, it is not desirable for the user to own a plurality of RFID tags for each RFID system, and it is desirable that one tag can support a plurality of RFID systems.

  Against this background, in recent years, research and development of card-type RFID tags that can be used in both the HF band RFID system and the UHF band RFID system is underway. As an example, a method has been proposed in which a UHF band communication dipole antenna is formed inside a coil conductor for HF band communication formed on a card (see, for example, Patent Document 1 and Non-Patent Document 1).

  That is, as a method of arranging the HF band communication coil and the UHF band communication antenna in one card, as described in Patent Document 1 and Non-Patent Document 1, the UHF band coil is placed inside the HF band coil. Separately, there are two arrangement methods: a method of arranging the antenna and a method of arranging the UHF band antenna outside the HF band coil.

  Patent Document 2 discloses a folded monopole antenna that can also be used as an antenna for UHF band communication (described as “folded monopole antenna” in Patent Document 2). The monopole antenna is connected to a semiconductor chip (described as “semiconductor die” in Patent Document 2). Patent Document 3 discloses an RFID tag using a monopole antenna (described as “monopole antenna” in Patent Document 3) that can also be used as an antenna for UHF band communication.

JP 2004-240899 A JP 2008-259250 A (FIG. 1) JP 2009-219112 A

Non-patent document 1: K.K. S. Leon, M.M. L. Ng, and P.M. H. Cole, “Miniaturization of dual frequency RFID antenna with high frequency ratio,” 2007 IEEE Antenna and Propagation Society International Symposium. 5475-5478, July 2007

  In the conventional wireless communication device, as disclosed in Patent Document 1 and Non-Patent Document 1, regarding the method of arranging the UHF band antenna inside the HF band coil, the communication distance of the UHF band is described in Non-Patent Document 1. For example, when considering using this tag for vehicle entrance / exit management, the communication distance is not necessarily sufficient, and the communication distance needs to be improved, but it is sufficient for practical use. There is a problem that it is not easy to achieve a long communication distance.

  On the other hand, as another conventional technique, in the method of arranging the UHF band antenna outside the HF band coil, it is necessary to reduce the mounting area of the HF band coil in order to arrange the UHF band antenna. Since the communication distance of the HF band is roughly proportional to the area of the coil, there is a problem that reducing the mounting area of the coil for the HF band causes a decrease in the communication distance of the HF band.

  Furthermore, in either of the two arrangement methods, mutual interference between the HF band coil and the UHF band antenna occurs. Therefore, in order to reduce the communication distance reduction due to the mutual interference, the distance between the two antenna conductors is set. However, since it is required to be separated to some extent, there is a problem that the mounting area of each antenna is further reduced and the communication distance may be reduced.

  The folded monopole antenna described in Patent Document 2 can reduce the size of the UHF band antenna without reducing the communication distance by folding the conductor pattern. There is no description about mutual interference between the UHF band antenna and the LF band / HF band coil. Similarly, in Patent Document 3, there is no description regarding the HF band coil and no description regarding the mutual interference between the UHF band antenna and the LF band / HF band coil.

  The present invention has been made in order to solve the above-described problems, and secures the mounting area of each antenna as large as possible, and is equivalent to the communication distance of each of the LF band or the HF band and the UHF band. It is an object of the present invention to obtain a wireless communication apparatus having an RFID tag function that can be shared by an LF band RFID system or an HF band RFID system and a UHF band RFID system having a communication distance of 1 mm.

  According to a first aspect of the present invention, there is provided a radio communication device having a dielectric having one main surface and another main surface, formed on one main surface of the dielectric, and electrically connected to an IC chip for a coil antenna. A coil antenna, a monopole antenna formed on one main surface or the other main surface of the dielectric on the outer periphery of a winding constituting the coil antenna and grounded by the coil antenna, and a meander constituting the monopole antenna And a monopole antenna IC chip fed by the monopole antenna.

  According to a second aspect of the present invention, there is provided a radio communication device having a dielectric having one main surface and another main surface, formed on one main surface of the dielectric, and electrically connected to an IC chip for a coil antenna. A coil antenna and an outer periphery of a winding constituting the coil antenna, the monopole antenna being grounded to the coil antenna and formed on one main surface of the dielectric, and a meander line constituting the monopole antenna And an IC chip for a monopole antenna fed by the monopole antenna.

  According to a third aspect of the present invention, there is provided a radio communication device having a dielectric having one main surface and another main surface, formed on one main surface of the dielectric, and electrically connected to an IC chip for a coil antenna. A coil antenna, a monopole antenna connected to the outer periphery of a winding constituting the coil antenna and formed on one main surface of the dielectric, a meander line constituting the monopole antenna, and the coil antenna A loop conductor pattern that is arranged on the inner peripheral side of the winding to be coupled to a magnetic field generated by a current flowing through the monopole antenna, and an IC chip for a monopole antenna that is electrically connected to the loop conductor pattern Is.

  According to a fourth aspect of the present invention, there is provided a radio communication device having a dielectric having one main surface and another main surface, formed on one main surface of the dielectric, and electrically connected to an IC chip for a coil antenna. A coil antenna, a monopole antenna IC chip having one end connected to the outer periphery of a winding constituting the coil antenna, and the other end of the monopole antenna IC chip, and electrically connected to one end of the dielectric. A monopole antenna formed on the main surface and a meander line constituting the monopole antenna are provided.

  A radio communication apparatus according to a fifth aspect of the present invention is the radio communication apparatus according to the fourth aspect, wherein the monopole antenna has a short stub that is short-circuited with the coil antenna.

  According to a sixth aspect of the present invention, there is provided a radio communication device having a dielectric having one main surface and another main surface, formed on one main surface of the dielectric, and electrically connected to an IC chip for a coil antenna. A coil antenna, a monopole antenna connected to the outer periphery of a winding constituting the coil antenna and formed on one main surface of the dielectric, a meander line constituting the monopole antenna, and the coil antenna A loop conductor pattern that is arranged on the outer peripheral side of the winding to be coupled to a magnetic field generated by a current flowing through the monopole antenna, and an IC chip for a monopole antenna that is electrically connected to the loop conductor pattern It is.

  According to a seventh aspect of the present invention, in the wireless communication device according to the seventh aspect of the present invention, the portion of the winding constituting the coil antenna to which the monopole antenna IC chip or the monopole antenna is connected is a widened conductor pattern. The other main surface conductor pattern which is formed in the other main surface of the said dielectric material facing the formed conductor pattern, and carries out capacitive coupling between the windings which comprise the said coil antenna is given in any one of Claims 4-6 It is.

  According to an eighth aspect of the present invention, there is provided a radio communication device having a dielectric having one main surface and another main surface, formed on one main surface of the dielectric, and electrically connected to an IC chip for a coil antenna. A coil antenna, another main surface conductor pattern formed on the other main surface of the dielectric facing the coil antenna, and capacitively coupling between the windings constituting the coil antenna, and one end of the other main surface conductor pattern The connected monopole antenna IC chip, the monopole antenna electrically connected to the other end of the monopole antenna IC chip, formed on the other main surface of the dielectric, and the monopole antenna With a meander line.

  According to a ninth aspect of the present invention, in the radio communication device according to the eighth aspect, the winding constituting the coil antenna is a conductor pattern in which a portion on the outer circumference and facing the other main surface conductor pattern is widened. belongs to.

  The radio communication apparatus according to claim 10 of the present invention is the radio communication apparatus according to claim 7 or 9, wherein the windings constituting the coil antenna are widened at least one of the windings inside the widened conductor pattern. Is.

  According to an eleventh aspect of the present invention, in the radio communication device according to the eleventh aspect of the present invention, the monopole antenna is configured such that the distal end side is configured by the meander line and the proximal end side is configured by a linear conductor pattern or an L-shaped conductor pattern. 10 to 10.

  A radio communication apparatus according to a twelfth aspect of the present invention is the radio communication apparatus according to any one of the first to eleventh aspects, wherein the monopole antenna is disposed in a recessed portion of the coil antenna having a rectangular winding shape. is there.

  According to the present invention, an LF band RFID system or an HF band RFID system that secures as large a mounting area as possible for each antenna and has a communication distance equivalent to the communication distance of each of the LF band or the HF band and the UHF band. And a radio communication apparatus having an RFID tag function that can be shared by the UHF band RFID system. Further, according to the inventions according to claims 1 to 12, since the UHF band antenna is constituted by a monopole antenna having a meander line, a communication distance characteristic equivalent to that of a conventional UHF band antenna can be obtained. Miniaturization can be realized. Therefore, the free space area within the card size is increased, and it is possible to increase the amount (area) of the coil antenna that becomes a coil for the LF band or the HF band, and the communication distance characteristics of the LF band or the HF band are A more improved wireless communication device can be obtained.

It is a top view which shows the 1st structural example of the radio | wireless communication apparatus which concerns on Example 1 of this invention. Example 1 It is sectional drawing by the A-A 'line in FIG. Example 1 It is a top view which shows the structural example which deleted the parallel plate capacitor in FIG. Example 1 It is a characteristic view which shows the impedance frequency characteristic which looked at the antenna side from the input-output terminal of the integrated circuit in FIG. Example 1 It is explanatory drawing which shows the radiation pattern calculation result of the xz plane and yz plane in the antenna structure of FIG. Example 1 It is a top view which shows the structural example which has arrange | positioned the integrated circuit and parallel plate capacitor in FIG. 1 on the outer side of the spiral conductive object. Example 1 It is a top view which shows the structural example which has arrange | positioned the integrated circuit in FIG. 1 on the outer side of a spiral conductive object. Example 1 It is a top view which shows the 2nd structural example of the radio | wireless communication apparatus which concerns on Example 1 of this invention. Example 1 It is a characteristic view which shows the impedance frequency characteristic which looked at the antenna side from the input / output terminal of the integrated circuit in FIG. Example 1 It is a top view which shows the 3rd structural example of the radio | wireless communication apparatus which concerns on Example 1 of this invention. Example 1 It is a characteristic view which shows the calculation result of the impedance frequency characteristic obtained by the antenna structure of FIG. Example 1 It is a top view which shows the structural example which has arrange | positioned the integrated circuit and conductive object in FIG. 10 inside the spiral conductive object. Example 1 FIG. 2 is a plan view showing an antenna configuration in which a spiral conductive object in FIG. 1 is replaced with a ring-shaped conductive object. (Example 2) It is a characteristic view which shows the calculation result of the impedance frequency characteristic in the antenna structure of FIG. (Example 2) It is explanatory drawing which shows the radiation pattern calculation result of xz surface and yz surface with respect to the antenna structure of FIG. (Example 2) It is a characteristic view which shows the relationship between the number of short circuits and radiation efficiency at the time of providing the short circuit part between windings in the antenna structure of FIG. (Example 2) It is a characteristic view which shows the relationship between the number of the short circuit parts between winding | windings in 1st center frequency, and antenna impedance. (Example 2) It is a top view which shows the radio | wireless communication apparatus which concerns on Example 2 of this invention. (Example 2) It is a characteristic view which shows the relationship between the electrostatic capacitance value of the capacitor in FIG. 18, and the radiation efficiency in the 1st center frequency. (Example 2) It is a characteristic view which shows the relationship between the electrostatic capacitance value of the capacitor in FIG. 18, and the antenna impedance in the 1st center frequency. (Example 2) It is a characteristic view which shows the impedance frequency characteristic of the 1st frequency band in the antenna structure of FIG. (Example 2) It is a characteristic view which shows the relationship between the impedance of a spiral conductive object in FIG. 18, and an electrostatic capacitance value. (Example 2) It is explanatory drawing for demonstrating the effect by Example 2 of this invention in detail, and has shown the result of having calculated the frequency characteristic of radiation efficiency when the number of turns of a spiral conductive object is set to "3". (Example 2) It is explanatory drawing for demonstrating the effect by Example 2 of this invention in detail, and has shown the result of having calculated the frequency characteristic of radiation efficiency when the number of turns of a spiral conductive object is set to “6”. (Example 2) It is a top view which shows the radio | wireless communication apparatus which concerns on Example 3 of this invention. Example 3 FIG. 26 is a cross-sectional view taken along line B-B ′ in FIG. 25. Example 3 It is a top view which shows the radio | wireless communication apparatus which concerns on Example 4 of this invention. (Example 4) It is a top view which expands and shows the interdigital capacitor in FIG. (Example 4) It is a top view which shows the radio | wireless communication apparatus which concerns on Example 5 of this invention. (Example 5) It is the top view which expands and shows the capacitive coupling means between windings in FIG. 29, and sectional drawing by a C-C 'line. (Example 5) It is a characteristic view which shows the radiation efficiency of the 1st center frequency by Example 5 of this invention. (Example 5) It is a characteristic view which shows the input impedance of the spiral conductive object in the 2nd center frequency with respect to the antenna structure of Example 5 of this invention. (Example 5) It is a top view which shows the other structural example of the radio | wireless communication apparatus which concerns on Example 5 of this invention. (Example 5) It is a top view which shows the radio | wireless communication apparatus which concerns on Example 6 of this invention. (Example 6) It is a top view which shows the other structural example of the radio | wireless communication apparatus which concerns on Example 6 of this invention. (Example 6) It is a top view which shows the radio | wireless communication apparatus which concerns on Example 7 of this invention. (Example 7) It is a top view which shows the radio | wireless communication apparatus which concerns on Example 8 of this invention, and has shown the surface structure of the designed tag. (Example 8) It is the top view which saw through the back surface structure of the tag shown in FIG. 37 from the surface side. (Example 8) It is explanatory drawing which shows the design result with respect to the circuit structure of FIG. 37 and FIG. (Example 8) It is a top view which shows the other structural example of the radio | wireless communication apparatus based on Example 8 of this invention, and has shown the case where it replaces with the closed loop-shaped electroconductive object in FIG. 37, and uses the short stub. (Example 8) FIG. 38 is a plan view showing another configuration example of a wireless communication apparatus according to Embodiment 8 of the present invention, and shows a case where a chip capacitor is used instead of the conductive object in FIG. (Example 8) It is a top view which shows the other structural example of the radio | wireless communication apparatus which concerns on Example 8 of this invention, and has shown the case where a chip capacitor is used instead of the electroconductive object in FIG. (Example 8) It is a top view which shows the radio | wireless communication apparatus which concerns on Example 9 of this invention. Example 9 It is a top view which shows the radio | wireless communication apparatus which concerns on Example 9 of this invention. Example 9 It is a top view which shows the radio | wireless communication apparatus which concerns on Example 9 of this invention. Example 9 It is a top view which shows the radio | wireless communication apparatus which concerns on Example 9 of this invention. Example 9 It is a top view which shows the radio | wireless communication apparatus which concerns on Example 9 of this invention. Example 9 It is a top view which shows the radio | wireless communication apparatus which concerns on Example 9 of this invention. Example 9

Example 1
Hereinafter, preferred embodiments of a wireless communication apparatus of the present invention will be described with reference to the drawings.
1 is a plan view showing a wireless communication apparatus according to Embodiment 1 of the present invention, and FIG. 2 is a cross-sectional view taken along the line AA 'in FIG.

  In FIG. 1, the wireless communication apparatus includes a flat object 1, a spiral conductive object 2 having outer dimensions L and W, an L-shaped (extended) conductive object 3, integrated circuits 4 and 5, and , Conductive objects 7a and 7b, inter-layer connection portions 8 such as through holes, and a parallel plate capacitor 30 including a pair of flat plates 30a and 30b (see FIG. 2). One (upper surface side) flat plate 30a of the parallel plate capacitor 30 is electrically connected to the conductive object 7a, and the other (lower surface side) flat plate 30b of the parallel plate capacitor 30 is electrically connected to the conductive object 7b.

  The flat object 1 is made of an arbitrary substance. The integrated circuit 4 has a function necessary for communication in the first frequency band, and the integrated circuit 5 has a function necessary for communication in the second frequency band. The conductive objects 7 a and 7 b connect the spiral conductive object 2 and the input / output terminals of the integrated circuit 5. The different interlayer connection portion 8 connects an arbitrary conductive object formed on the surface of the flat object 1 and an arbitrary conductive object formed on the back surface of the flat object 1.

  The parallel plate capacitor 30 is electrically connected to the integrated circuit 5 in parallel. The capacitance value of the parallel plate capacitor 30 is normally designed so as to form an LC parallel resonance circuit together with the spiral conductive object 2 and to resonate at a desired frequency in the second frequency band. Alternatively, the capacitance value of the parallel plate capacitor 30 is designed so that impedance matching between the circuit formed by the spiral conductive body 2 and the integrated circuit 5 is good at a desired frequency in the second frequency band. Therefore, when the first frequency band is sufficiently larger than the second frequency band, the parallel plate capacitor 30 is often electrically short-circuited in the first frequency band in many cases.

  The electrical length of the conductive object 3 may be arbitrary as long as good communication performance can be obtained in the first frequency band, but is often selected to be about 1λ1e or less effective wavelength in the first frequency band. Here, the effective wavelength λ1e in the first frequency band is a value that takes into account the electrical influence of objects arranged around the conductive object 3, such as the flat object 1 and other surrounding objects (not shown). It is. In addition, here, the conductive object 3 is exemplified as a thin line, but may be any shape such as an ellipse or a polygon.

The configuration in which the integrated circuit 4 and the conductive object 3 are removed from the configuration of FIG. 1 is the most basic known configuration of a non-contact IC card that is widely spread at present.
The standing wave current distribution on the conductive object 3 is determined by the boundary condition that the current amplitude at the tip of the conductive object 3 is zero.
Therefore, when the desired frequency of the first frequency band is sufficiently larger than the desired frequency of the second frequency band, that is, the effective wavelength λ2e of the second frequency band is larger than the effective wavelength λ1e of the first frequency band. If it is sufficiently long, the current in the second frequency band hardly flows on the conductive object 3.

  As a result, even if the integrated circuit 4 and the conductive object 3 are connected to an arbitrary position of the spiral conductive object 2, the integrated circuit 5, the parallel plate capacitor 30 and the spiral conductive object 2 can be connected to an external device. It hardly affects the communication characteristics of the second frequency band performed in (1).

On the other hand, when considering the antenna operation in the first frequency band, the input / output terminal portion of the integrated circuit 4 corresponds to a so-called power feeding portion, and a current flows through the entire conductive object 3 and the spiral conductive object 2. Works as.
At this time, as described above, in the first frequency band, the parallel plate capacitor 30 is often electrically short-circuited in many cases. Therefore, the operation of the first frequency band is performed by the input of the integrated circuit 5. It becomes irrelevant to impedance.

  If the parallel plate capacitor 30 is not necessary for good communication in the second frequency band, basically, the input / output terminal portion of the integrated circuit 5 is substantially electrically connected in the first frequency band. It is desirable to determine the capacitance value of the parallel plate capacitor 30 so as to be in a short-circuited state and in a substantially open state in the second frequency band.

However, if it is determined that the capacitor 30 is unnecessary even in the first frequency band as a result of electromagnetic field analysis or experiment, it can be deleted as shown in FIG.
In other words, the characteristics of the antenna greatly depend on the size of the spiral conductive object, the number of turns, and the characteristics of the medium in the vicinity of the antenna, and depending on these physical and electrical conditions and the required communication distance, The capacitor 30 may be removable and is not necessarily an essential component in the present invention.
Hereinafter, a case where a capacitor is connected between the input and output terminals of the integrated circuit 5 will be described as an example.

  In general, when the capacitance value of the capacitor is C and the frequency of the AC power supply is f, the impedance value Z of the capacitor is given by the following equation (1) as is well known.

  Z = −j / (2πfC) (1)

As apparent from the equation (1), the ratio of the impedance value Z of the capacitor is the reciprocal of the ratio of the frequency f.
Here, the first center frequency of the first frequency band is f1, the second center frequency of the second frequency band is f2, the impedance value at the first center frequency f1 is Z1, and the second center frequency. Assuming that the impedance value at f2 is Z2, when the condition f1 >> f2 is satisfied, the following expression (2) is satisfied.

  | Z1 | <<< Z2 | (2)

Therefore, if the capacitance value C is appropriately selected, it is possible to electrically short-circuit at the first center frequency f1, and to electrically open at the second center frequency f2.
For example, the first and second center frequencies f1, f2 are
f1 = 2.45 [GHz]
f2 = 13.56 [MHz]
Then, the center frequency ratio f1 / f2 is given by the following equation (3).

  f1 / f2 ≒ 181 (3)

Also, the first and second center frequencies f1, f2 are
f1 = 960 [MHz]
f2 = 13.56 [MHz]
Then, the center frequency ratio f1 / f2 is given by the following equation (4).

  f1 / f2 ≒ 71 (4)

Further, the first and second center frequencies f1, f2 are
f1 = 860 [MHz]
f2 = 13.56 [MHz]
Then, the center frequency ratio f1 / f2 is given by the following equation (5).

  f1 / f2 ≒ 63 (5)

  In the above condition, the second center frequency f2 is set to 13.56 [MHz]. However, if f2 = 135 [kHz], the center frequency ratio f1 / f2 is expressed by the equations (3) to (5). ) Value 100 times.

For example, when the impedance value Z1 at the first center frequency f1 is 0-j36 [Ω], f1 = 860 MHz, and f2 = 13.56 MHz, f1 / f2≈63 as shown in the equation (5). Therefore, the impedance value Z2 at the second center frequency f2 is 0-j2268 [Ω].
Therefore, the first center frequency f1 is electrically short-circuited, and the second center frequency f2 is electrically open.

From the above consideration, as shown in FIG. 1, by using the spiral conductive object 2 as a part of the antenna conductor of the first frequency band, the mounting area of each antenna of the first and second frequency bands. Can be secured wider than the case where the antennas of the first frequency band and the antenna of the second frequency band are arranged in parallel.
As a result, the configuration shown in FIG. 1 makes it possible to ensure the same communication performance as when each antenna exists alone.

In order to verify the effectiveness of the antenna configuration of FIG. 1, the inventor performed numerical electromagnetic field analysis and experiments, and obtained the results of FIG. 4.
FIG. 4 is a characteristic diagram showing the impedance frequency characteristic Zf1 when the antenna side is viewed from the input / output terminals of the integrated circuit 4. In FIG.

  In FIG. 4, the numerical value in the circle indicates a value obtained by normalizing the impedance Z by 50 [Ω], and z of the spiral conductive object 2 with reference to the in-air wavelength λ1 of the first center frequency f1. , X-direction outer dimensions L and W are L = 0.19λ1 and W = 0.14λ1, respectively, and the width and length of the conductive object 3 are 0.0032λ1 and 0.254λ1, respectively. The calculation results are shown.

In FIG. 4, the impedance frequency characteristic Zf1 is plotted on a Smith chart over 5 points in increments of 0.053f1 from 0.894f1 to 1.106f1.
As apparent from the impedance frequency characteristic Zf1 of FIG. 4, the antenna configuration of FIG. 1 has a large reactance change amount and a narrow band compared to the half-wave dipole antenna placed in free space, but similar impedance characteristics. It can be seen that (series resonance characteristics) is shown.

FIGS. 5A and 5B are explanatory diagrams showing the radiation pattern calculation results on the xz plane and the yz plane, respectively, showing main polarization (Eθ component) and cross polarization (Eφ component). ing.
As is apparent from FIG. 5, the radiation configuration similar to that of the half-wave dipole antenna is obtained with the antenna configuration of FIG. 1, the radiation efficiency is -1.1 dB, and the gain is 1.3 dBi.
In FIG. 5B, cross polarization (Eφ component) is generated in the yz plane, but it is not at a level that causes a decrease in gain of the main polarization (Eθ component). Absent.

  Actually, as a result of making a prototype of an antenna equivalent to the above calculation model and measuring it, a result that corresponds well to the calculation results of FIGS. 4 and 5 was obtained as the impedance frequency characteristic and the radiation pattern. Further, the measured radiation efficiency was −1.9 dB, and the effectiveness of the antenna configuration in FIG. 1 was confirmed.

In FIG. 1, the integrated circuit 5 and the parallel plate capacitor 30 are arranged inside the spiral conductive object 2. However, the integrated circuit 5 and the parallel plate capacitor 30 are arranged inside the spiral conductive object 2. It is not limited to.
That is, as shown in FIG. 6, both may be arranged outside the spiral conductive object 2, or as shown in FIG. 7, the integrated circuit 5 is placed outside the spiral conductive object 2, and the parallel plate The capacitor 30 may be disposed inside the spiral conductive object 2. Although not shown, the integrated circuit 5 may be disposed inside the spiral conductive object 2 and the parallel plate capacitor 30 may be disposed outside the spiral conductive object 2.

These arrangements are appropriately designed by comprehensively considering the communication distance performance in the first frequency band, the communication distance performance in the second frequency band, the manufacturability (mounting) of the integrated circuit 5 by a machine, and the like.
Hereinafter, the case where the integrated circuit 5 and the parallel plate capacitor 30 are disposed inside the spiral conductive object 2 will be described as an example. However, even if they are disposed outside the spiral conductive object 2, the present invention is applicable. The operation of the antenna is not impaired in principle.

  By the way, generally, the impedance of the integrated circuit 4 used in the RFID tag is generally low resistance and has high capacitive reactance. Therefore, when impedance matching between the antenna and the integrated circuit 4 is considered, the antenna impedance as shown in FIG. 4 may be inconvenient.

In order to deal with the above inconvenient case, for example, as shown in the plan view of FIG. 8, a conductive object 10 is provided on the flat object 1, one end of the conductive object 10 is connected to the conductive object 3, What is necessary is just to comprise what is called a short stub by connecting the other end of the conductive object 10 to the spiral conductive object 2.
In FIG. 8, the same components as those described above (see FIG. 1) are denoted by the same reference numerals as those described above, and detailed description thereof is omitted. In this case, the configuration is the same as described above (see FIG. 1) except that the conductive object 10 is added.

With the antenna configuration of FIG. 8, as shown in the impedance frequency characteristic Zf2 of FIG. 9, the desired band impedance can be displaced in the vicinity of the impedance having a complex conjugate relationship with the impedance of the integrated circuit 4, and the antenna and Impedance matching with the integrated circuit 4 can be ensured.
In FIG. 9, the plot frequency of the impedance frequency characteristic Zf2 is shown over 9 points in increments of 0.01f1 from 0.96f1 to 1.04f1.

  Further, the impedance matching method is not limited to the short stub shown in FIG. 8, but as another means, for example, as shown in the plan view of FIG. An antenna configuration in which the integrated circuit 4 is inserted into a part of the sexual object 11 is conceivable.

In FIG. 10, the integrated circuit 4 is isolated from the conductive object 3.
The conductive object 11 is disposed in the vicinity of the spiral conductive object 2 and / or the conductive object 3 (at least one of the spiral conductive object 2 and the conductive object 3), and one end of the conductive object 11 is The other end of the conductive object 11 is connected to the other end of the terminal of the integrated circuit 4. In addition, the conductive object 3 is connected to the spiral conductive object 2.

  In the antenna configuration of FIG. 10, the magnetic field generated by the current flowing through the spiral conductive object 2 and the conductive object 3 penetrates the space in the loop of the conductive object 11, thereby comprising the integrated circuit 4 and the conductive object 11. A circuit and an antenna composed of the conductive object 3 and the spiral conductive object 2 are coupled via the magnetic field.

FIG. 11 is a characteristic diagram showing a calculation result of the impedance frequency characteristic Zf3 obtained by the antenna configuration of FIG.
In FIG. 11, the plot frequency of the impedance frequency characteristic Zf3 is shown over 21 points in increments of 0.005f1 from 0.95f1 to 1.05f1.

As is clear from FIG. 11, the antenna configuration shown in FIG. 10 can provide antenna impedance characteristics suitable for ensuring impedance matching with the integrated circuit 4.
The conductive object 11 may be in contact with the conductive object 3 and / or the spiral conductive object 2. This state is the limit in which the distance between the conductive object 11 and the conductive object 3 and / or the spiral conductive object 2 is zero, and it is considered that the antenna operates as described above.

  In FIG. 10, the integrated circuit 4 and the conductive object 11 are arranged outside the spiral conductive object 2. However, the integrated circuit 4 and the conductive object 11 are arranged outside the spiral conductive object 2. However, the two may be arranged inside the spiral conductive object 2 as shown in FIG. 12. The arrangement of the integrated circuit 4 and the conductive object 11 comprehensively considers the communication distance performance in the first frequency band, the communication distance performance in the second frequency band, and the manufacturability (mounting) of the integrated circuit 4 by a machine. It is designed as appropriate.

  Hereinafter, a case where the integrated circuit 4 and the conductive object 11 are arranged outside the spiral conductive object 2 will be described as an example. However, even if they are arranged inside the spiral conductive object 2, the present invention can be applied. The operation of the antenna is not impaired in principle.

As described above, the wireless communication apparatus according to the first embodiment of the present invention includes an integrated circuit 4 (first integrated circuit) having a communication function in the first frequency band, and the integrated circuit 4 as shown in FIG. A conductive object 3 (first conductive object) connected to one of the input / output terminals, an integrated circuit 5 (second integrated circuit) having a communication function in the second frequency band, and the integrated circuit 5 And the other of the input / output terminals of the integrated circuit 4 is a part of the spiral conductive object 2. It is connected.
Further, as shown in FIG. 8, a conductive object 10 (third conductive object) is further provided, one end of the conductive object 10 is connected to the conductive object 3, and the other end of the conductive object 10 is a spiral. Connected to the conductive object 2.

  Further, as shown in FIG. 10, the integrated circuit 4 having a communication function in the first frequency band, the conductive object 3, the integrated circuit 5 having the communication function in the second frequency band, and the integrated circuit 5 A spiral conductive object 2 connected between the input and output terminals, and a closed loop conductive object 11 (third conductive object) connected between the input and output terminals of the integrated circuit 4. One end of the conductive object 3 is connected to a part of the spiral conductive object 2, and the conductive object 11 is disposed in proximity to at least one of the conductive object 3 and the spiral conductive object 2.

  Thereby, the mounting area of each antenna is secured as large as possible, and the LF band RFID system or the HF band RFID system having a communication distance equivalent to the communication distance of each of the LF band or the HF band and the UHF band A wireless communication apparatus having an RFID tag function that can be shared with a UHF band RFID system can be obtained.

(Example 2)
In the antenna configuration of the first embodiment (FIGS. 1, 8, and 10), there may be a problem that the operating band is not so wide. Further, it is considered that there is a correlation between the operating bandwidth and the current distribution on the spiral conductive object 2.
In order to confirm this, first, for convenience, as shown in the plan view of FIG. 13, the spiral conductive object 2 is replaced with a ring-shaped conductive object 12, and the antenna configuration of FIG. The antenna characteristics in the frequency band were calculated.

FIG. 14 is a characteristic diagram showing a calculation result of the impedance frequency characteristic Zf4 in the antenna configuration of FIG.
In FIG. 14, the plot frequency of the impedance frequency characteristic Zf4 is the same as that of FIG. 4 and is shown over 5 points. However, the amount of reactance change is smaller than the impedance frequency characteristic Zf1 of FIG. I understand.

FIGS. 15A and 15B are explanatory views showing the radiation pattern calculation results on the xz plane and the yz plane for the antenna configuration of FIG.
In FIG. 15 with the antenna configuration of FIG. 13, there is no significant difference in the pattern shape compared to FIG. 5 with the antenna configuration of FIG. 1, but the gain is slightly higher.

Further, the calculated value of the radiation efficiency of FIG. 15 by the antenna configuration of FIG. 13 is −0.2 dB, which is about 1 dB higher than the radiation efficiency (= −1.1 dB) of FIG. 5 by the antenna configuration of FIG.
From the above examination, it was found that the bandwidth and the radiation efficiency can be improved at the same time by replacing the spiral conductive object 2 with the annular conductive object 12 as shown in FIG.

However, naturally, considering the communication performance in the second frequency band, the spiral conductive object 2 cannot be replaced with the annular conductive object 12 as shown in FIG.
Therefore, in actuality, in the antenna configuration of FIG. 1, the first winding without affecting the communication characteristics of the second frequency band by capacitively coupling adjacent windings of the spiral conductive object 2. Try to improve the antenna performance of the frequency band.

First, the number n for short-circuiting between adjacent windings of the spiral conductive object 2 is examined.
FIG. 16 is a characteristic diagram showing the relationship between the number n of inter-winding short-circuit portions and the radiation efficiency. The number n of inter-winding short-circuit portions 13 for short-circuiting the windings (n = 1,..., 6). The difference in radiation efficiency is shown.
In FIG. 16, the interwinding short-circuit portion 13 of the spiral conductive object 2 is composed of a plurality of conductive objects 14 that short-circuit adjacent coils, and is equidistant from the spiral conductive object 2. It is arranged to be.

  As is apparent from FIG. 16, the radiation efficiency is almost independent of the number n of the inter-winding short-circuit portions 13, and the inter-winding short-circuit portions 13 are the spiral conductive object 2 and the conductive object 3 or the integrated circuit. It can be seen that it is only necessary to dispose one in the vicinity of the joint with 4.

FIG. 17 is a characteristic diagram showing the relationship between the number n of the inter-winding short-circuit portions 13 and the antenna impedance (resistance value R [Ω], reactance value X [Ω]) at the first center frequency f1.
As is apparent from FIG. 17, the change in antenna impedance due to the number n of the inter-winding short-circuit portions 13 is 1 [Ω] or less for both the resistance value R and the reactance value X, and it can be seen that it hardly occurs.

18 is a plan view showing a configuration example of Embodiment 2 of the present invention, and shows a case where a circuit element 15 is provided instead of the inter-winding short-circuit portion 13 in FIG.
In FIG. 18, the circuit element 15 connects the windings of the spiral conductive object 2 in the vicinity of the joint between the spiral conductive object 2 and the conductive object 3 or the integrated circuit 4.

Next, the relationship between the capacitor capacitance value and the characteristics when the circuit element 15 is a capacitor is examined.
FIG. 19 is a characteristic diagram showing the relationship between the capacitance value (lumped constant) C [pF] of the capacitor and the radiation efficiency at the first center frequency f1.
As is clear from FIG. 19, the radiation efficiency tends to deteriorate as the capacitance value C decreases. However, if C ≧ 2 pF, the amount of deterioration of the radiation efficiency is within 0.2 dB, which is practically almost no. It turns out that there is no problem.

  FIG. 20 is a characteristic diagram showing the relationship between the capacitance value C of the capacitor and the antenna impedance (resistance value R, reactance X) at the first center frequency f1, and it can be seen that the same tendency as in FIG. 19 is shown.

FIG. 21 is a characteristic diagram in which the impedance frequency characteristic of the first frequency band is plotted on the Smith chart. FIG. 21A shows the impedance frequency characteristic Zf5 when the capacitance value C is 2 pF, and FIG. b) shows the impedance frequency characteristic Zf6 when the capacitance value C is 8 pF.
In FIG. 21, the plot frequencies are shown over 5 points in increments of 0.025f1, from 0.95f1 to 1.05f1.

  As can be seen from a comparison between the impedance frequency characteristic Zf6 (C = 8 pF) in FIG. 21B and the impedance frequency characteristic Zf5 (C = 2 pF) in FIG. Although the impedance tends to be displaced capacitively, this can be compensated by setting the electrical length of the conductive object 3 to be long, so that this is not a big problem.

On the other hand, FIG. 22 is a characteristic diagram showing the relationship between the impedance (resistance value R, reactance X) of the spiral conductive body 2 and the capacitance value C. At a second center frequency f2, A in FIG. The characteristic of the impedance which looked at the spiral conductive object 2 from -A 'is shown.
As can be seen from FIG. 22, the impedance characteristic of the second center frequency f2 also hardly depends on the capacitance value C.

  Hereinafter, an example in which the frequency characteristics of the radiation efficiency are obtained by numerical electromagnetic analysis by changing the number of turns, the outer size, and the capacitance value C of the spiral conductive object 2 with reference to FIGS. Therefore, the effect of interwinding capacitive coupling will be discussed in more detail. The unit of numerical values shown in the characteristic curve in each figure is [λc].

  23A to 23C, the number of turns is “3”, the length W in the x direction of the spiral conductive body 2 is 0.133λc, and the length L in the z direction of the spiral conductive body 2 is shown in FIG. It is explanatory drawing which shows the result of having calculated the frequency characteristic of radiation efficiency using (= Lc) as a parameter.

In FIGS. 23A to 23C, the horizontal axis represents the frequency normalized at fc = 910 MHz, and λc represents the in-air wavelength of the radio wave of 910 MHz.
FIG. 23A shows characteristics when C = 0 pF (electrically open), FIG. 23B shows characteristics when C = 2 pF, and FIG. 23C shows C = 4 pF. It is a characteristic at the time of.

  As is clear from FIG. 23, the dependence of the radiation efficiency on the size of the spiral conductive object is greatly suppressed even at C = 2 pF, and when C = 4 pF, for all the spiral conductive object sizes. It can be seen that a high radiation efficiency of −1.5 dB or more can be obtained over a wide band.

On the other hand, FIGS. 24A to 24E are explanatory diagrams showing calculation results when the number of turns is “6”, and FIG. 24A is a graph when C = 0 pF (electrically open). Show properties.
FIG. 24B shows the characteristics when C = 2 pF, FIG. 24C shows the characteristics when C = 4 pF, and FIG. 24D shows the characteristics when C = 8 pF. FIG. 24E shows the characteristics when C = ∞pF (electrically short-circuited).

  As is clear from FIG. 24, the required capacitance value tends to be larger than that in the case of FIG. 23 (Volume 3), but by capacitive coupling between the windings of the spiral conductive object 2 It can be seen that the dependence of the radiation efficiency on the size of the spiral conductive object can be greatly suppressed and high radiation efficiency can be secured over a wide band.

  As described above, according to the wireless communication apparatus according to Embodiment 2 (FIGS. 16 and 18) of the present invention, the circuit element 15 that capacitively couples the windings of the spiral conductive object 2 is provided, and the capacitance By appropriately selecting the value, it is possible to improve the antenna performance of the first frequency band with almost no influence on the communication characteristics of the second center frequency f2.

Note that the circuit element 15 is not limited to a chip capacitor, and other means may be used as long as the circuit element 15 has a frequency characteristic that allows the current in the first frequency band to pass and blocks the current in the second frequency band. There may be.
Therefore, as the circuit element 15, any resonator such as a dielectric resonator, a ceramic resonator, and a piezoelectric resonator used in a filter can be used as a frequency selective coupling unit.

  Here, the piezoelectric resonator is a filter in which electrodes are formed on the front and back sides of a piezoelectric thin film and the vibration of the thin film is used. A piezoelectric resonator connected in a ladder shape is called an FBAR (Film Bulk Acoustic Resonator) filter and is known as a band-pass filter having a low loss and a steep characteristic.

As described above, the radio communication apparatus according to Embodiment 2 of the present invention is provided between adjacent windings of a part of a spiral conductive object as shown in FIG. A circuit element 15 (frequency selective coupling means, for example, capacitive coupling means) for connection is further provided, and the circuit element 15 is constituted by a resonator, for example.
As a result, it is possible to appropriately select the electrical characteristics of the circuit element 15 and improve the antenna performance of the first frequency band without substantially affecting the communication characteristics of the second center frequency f2.

(Example 3)
When considering the antenna configuration shown in the first and second embodiments (FIGS. 1, 8, 10, 16, and 18) to be practically used, an arbitrary circuit is not necessarily provided on the flat object 1. It is not always possible to mount element parts, and an increase in the number of parts generally leads to an increase in manufacturing costs.
Therefore, instead of the configuration of FIG. 18, consider a configuration in which the windings of the spiral conductive object 2 are capacitively coupled only with the conductive objects 2a and 2b as shown in FIGS.

25 is a plan view showing a wireless communication apparatus according to Embodiment 3 of the present invention, and FIG. 26 is a sectional view taken along line BB ′ in FIG.
FIG. 25 and FIG. 26 show one configuration example in which the windings of the spiral conductive object 2 are capacitively coupled in the first frequency band.
In FIG. 25, a part of the spiral conductive object 2 (section from the different interlayer connection 8 a to the different interlayer connection 8 b) is a conductive object disposed on the back surface of the flat object 1.

In this case, as shown in FIG. 26, at the position where the capacitive coupling is desired, the surface where the winding is present is configured to be the front, back, front of the flat object 1 in order from the outside, and preferably the part. The winding shape of the conductive objects 2a and 2b is locally deformed so as to overlap with adjacent windings.
That is, in this example, in the capacitive coupling portion, the width of the conductive object 2a on the front side of the flat object 1 is formed larger than the width of the other part, and the conductive object 2b on the back side of the flat object 1 The width is formed more than twice the width of the conductive object 2a.

  25 and 26, the capacitance between the windings of the spiral conductive body 2 can be partially increased, so that the circuit element in the above-described second embodiment (FIG. 18) It is possible to obtain the same effect as when 15 is a capacitor and to reduce the number of parts.

As described above, the capacitive coupling means of the wireless communication apparatus according to the third embodiment of the present invention forms the winding width of the spiral conductive object 2 partially large as shown in FIGS. It is comprised by.
That is, the spirally conductive object 2 is formed on both the front surface and the back surface of the flat object 1 as a structure having a frequency characteristic that allows the current in the first frequency band to pass and blocks the current in the second frequency band. At the same time, the winding width of the spiral conductive objects 2a and 2b is partially increased.

As a result, the spiral conductive object 2 can be shared as an antenna conductor in both the first frequency band and the second frequency band.
As a result, as in the first and second embodiments, the coil conductor for the LF band or the HF band can be used as the antenna conductor for the UHF band, and the mounting area of each antenna is ensured as large as possible. It is possible to obtain a wireless communication apparatus using a shared RFID card type tag of the LF band or HF band having a communication distance equivalent to the communication distance of each of the band and the UHF band, and the UHF band.
Furthermore, as compared with the configuration of the above-described second embodiment (FIG. 18), it is possible to reduce the number of parts and obtain a higher-performance wireless communication device.

Example 4
In the third embodiment, the spirally conductive object 2 is formed on both the front and back surfaces of the flat object 1, and the winding width of the spirally conductive objects 2a and 2b at the capacitive coupling portion is partially increased. However, as shown in FIGS. 27 and 28, the spiral conductive object 2 is formed only on the surface of the flat object 1, and the winding shape of the spiral conductive object 2 is partially used as capacitive coupling means. It may be deformed.

FIG. 27 is a plan view showing a wireless communication apparatus according to Embodiment 4 of the present invention. As another configuration example in which the windings of the spiral conductive body 2 are capacitively coupled in the first frequency band, capacitive coupling is performed. The case where the interdigital capacitor 16 is formed at the desired position is shown.
FIG. 28 is an enlarged plan view showing the interdigital capacitor 16. In FIG. 28, the interdigital capacitor 16 has a configuration in which a part of the spiral conductive object 2 is formed in a comb-like shape and is capacitively coupled by inserting each other.

27 and 28, the electrostatic capacitance between the windings of the spirally conductive object 2 can be partially increased.
Further, the conductive object 2a formed on the surface of the plate-like object 1 and the conductive object 2b formed on the back surface of the plate-like object 1 are connected as compared with the configuration of the above-described third embodiment (FIG. 25). The different interlayer connection portions 8a and 8b can be omitted, and the manufacturing cost can be reduced.

As described above, the capacitive coupling means of the wireless communication apparatus according to the fourth embodiment of the present invention is formed by partially deforming the winding shape of the spiral conductive object 2 as shown in FIGS. The interdigital capacitor 16 is formed between the lines.
That is, the spiral conductive body 2 is formed only on the surface of the flat object 1 as a structure having a frequency characteristic that allows the current in the first frequency band to pass and cuts off the current in the second frequency band. The winding shape of the sexual object 2 is partially deformed, and an interdigital capacitor 16 is partially formed between the windings.

As a result, the spiral conductive object 2 can be shared as an antenna conductor in both the first frequency band and the second frequency band.
As a result, as in the first to third embodiments, the coil conductor for the LF band or the HF band can be used as the antenna conductor for the UHF band, and the mounting area of each antenna is increased as much as possible. It is possible to obtain a wireless communication apparatus using a shared RFID card type tag of the LF band or the HF band and the UHF band, which has a communication distance equivalent to the communication distance of each of the HF band and the UHF band.
Further, the manufacturing cost can be reduced as compared with the configuration of the third embodiment (FIG. 25) described above.

(Example 5)
In the interdigital capacitor 16 of Example 4 (FIGS. 27 and 28), the capacitive coupling portion of the spiral conductive object 2 is formed in a comb-like shape, but a sufficient capacitance cannot be obtained with a small area. 29 and 30, the interwinding capacitive coupling means 18 may be configured by providing a conductive object 19 on the back surface of the flat object 1 as shown in FIGS.
FIG. 29 is a plan view showing a wireless communication apparatus according to Embodiment 5 of the present invention. 30 (a) and 30 (b) are an enlarged plan view and a cross-sectional view taken along the line CC ′ of the interwinding capacitive coupling means 18 in FIG.

In FIGS. 29 and 30, the interwinding capacitive coupling means 18 partially enlarges each winding of the spirally conductive object 2 formed on the surface of the flat object 1 and on the back surface of the part. It is configured by forming a conductive object 19.
Further, in FIGS. 30A and 30B, the conductive object 2c at the capacitive coupling portion is formed to be wider than the other portions, and the conductive object 19 on the back side of the flat plate-like object 1 includes a plurality of conductive objects 19a. It is formed in a size that covers all of the conductive object 2c.

  29 and 30, the inter-winding capacitor is configured in a parallel plate format without increasing the number of different interlayer connections without using the different interlayer connections 8a and 8b described above (FIG. 25). It becomes possible.

FIG. 31 is a characteristic diagram showing the radiation efficiency of the first center frequency f1 according to the fifth embodiment (FIGS. 29 and 30) of the present invention, and the capacitive coupling state by the interwinding capacitive coupling means 18 (capacitive coupling portion). The radiation efficiency at is compared with the radiation efficiency when the windings are short-circuited.
As can be seen from FIG. 31, the interwinding capacitive coupling means 18 can provide a radiation efficiency equivalent to that when the interwinding is short-circuited.

FIG. 32 is a characteristic diagram showing the input impedance (resistance value R, reactance X) of the spiral conductive body 2 at the second center frequency f2 with respect to the antenna configuration of the fifth embodiment of the present invention. It is shown in comparison with the input impedance value when the means 18 is not present.
As is clear from FIG. 32, it can be seen that the amount of impedance change due to the presence or absence of the interwinding capacitive coupling means 18 hardly occurs, and is within a problem-free range.

  Therefore, the antenna configuration shown in FIGS. 29 and 30 can partially increase the capacitance between the windings of the spiral conductive object 2, and further, compared with the configuration of the above-described fourth embodiment (FIG. 27). Thus, a higher inter-winding capacitance can be obtained with a smaller area.

As described above, the wireless communication apparatus according to the fifth embodiment of the present invention includes the conductive object 19 (as shown in FIG. 29) that is disposed so as to overlap a part of the spiral conductive object 2 with a predetermined interval. A fourth conductive object).
That is, after the spiral conductive object 2 is formed only on the surface of the flat object 1 as an antenna configuration having a frequency characteristic that allows the current in the first frequency band to pass and blocks the current in the second frequency band, The winding shape of the spiral conductive body 2 is partially deformed, and the interwinding capacitive coupling means 18 having the conductive body 19 on the back surface of the part is provided.

As a result, the spiral conductive object 2 can be shared as an antenna conductor in both the first frequency band and the second frequency band.
As a result, as in the first to fourth embodiments, the coil conductor for the LF band or the HF band can be used as the antenna conductor for the UHF band, and the mounting area of each antenna is ensured as large as possible. Alternatively, it is possible to obtain a wireless communication apparatus using a shared RFID card type tag of the LF band or the HF band and the UHF band, which has a communication distance equivalent to the communication distance of each of the HF band and the UHF band.

The interwinding capacitive coupling means 18 is not limited to the configuration shown in FIGS. 29 and 30. For example, as the conductive object 19, any shape such as a square, a circle, an ellipse, etc. can be selected. In addition, as shown in the plan view of FIG. 33, not only the conductive object 19 but also the integrated circuit 4 is arranged on the back surface of the flat object 1 and one end of the terminal of the integrated circuit 4 is connected to the conductive object 19. It is good also as composition to do.
Furthermore, if the desired inter-winding capacitive coupling is obtained, the winding shape of the spiral conductive body 2 does not necessarily have to be partially deformed.

In FIG. 33, the wireless communication device includes an integrated circuit 4 having a communication function in the first frequency band, a conductive object 3 connected to one of the input / output terminals of the integrated circuit 4, and a second frequency band. An integrated circuit 5 having a communication function, a spiral conductive object 2 connected between input and output terminals of the integrated circuit 5, and a conductive object 19 (third conductive object). The object 19 is arranged so as to overlap a part of the spiral conductive object 2 with a predetermined interval. The other input / output terminal of the integrated circuit 4 is connected to the conductive object 19.
The antenna configuration of FIG. 33 also provides the same operational effects as described above.

(Example 6)
In Examples 1 to 5 described above, only the conductive object 3 is provided for the spiral conductive object 2, but a conductive object 20 connected to the spiral conductive object 2 is further provided as shown in FIG. May be.
FIG. 34 is a plan view showing a wireless communication apparatus according to Embodiment 6 of the present invention. For example, FIG. 34 shows a case where a conductive object 20 is added to the configuration of Embodiment 5 (FIG. 29) described above.

In FIG. 34, in addition to the spiral conductive object 2 and the conductive object 3 described above, an L-shaped conductive object 20 is provided as an antenna main constituent conductor, and one end of the conductive object 20 is It is connected to the spiral conductive object 2.
With the antenna configuration of FIG. 34, the resonance mode determined by the shapes of the conductive object 3 and the spiral conductive object 2 and the shapes of the conductive object 20 and the spiral conductive object 2 are determined in the first frequency band. A plurality of resonance modes can be generated which are composed of the resonance modes determined and the resonance modes determined by the shapes of the conductive objects 3 and 20 and the spiral conductive object 2 (three conductive objects).

Accordingly, by optimizing the shapes of the respective conductive objects 3 and 20 and the spiral conductive object 2, not only the above-described effects but also the widening or multi-frequency sharing in the first frequency band is achieved. And practicality can be improved.
Further, the conductive object 20 is not necessarily connected to the spiral conductive object 2. For example, as shown in the plan view of FIG. 35, the conductive object 20 may be formed on the back surface of the flat object 1. Good. In this case, one end of the conductive object 20 is overlapped with a part of the spiral conductive object 2 at a predetermined interval, and is capacitively coupled to the spiral conductive object 2. In the configuration of FIG. 35, the same operational effects as described above can be obtained.

As described above, the wireless communication apparatus according to Embodiment 6 of the present invention further includes the conductive object 20 (fifth conductive object) as shown in FIG. 34, and one end of the conductive object 20 is It is connected to a part of the spiral conductive object 2.
Further, as shown in FIG. 35, one end of the conductive object 20 is overlapped with a part of the spiral conductive object 2 at a predetermined interval.

  As a result, a plurality of resonance modes are generated, and the shapes of the conductive objects 3 and 20 and the spiral conductive object 2 are optimized. In addition to the above-described effects, the first frequency band can be broadened or Multi-frequency sharing can be achieved and practicality can be improved.

(Example 7)
Referring to the antenna configuration of FIG. 10 in the first embodiment described above, when a magnetic field penetrating the closed circuit composed of the integrated circuit 4 and the conductive object 11 is generated in the second frequency band, the power in the second frequency band is generated. May be consumed by the resistance component of the communication integrated circuit 4 in the first frequency band, and the communication distance in the second frequency band may be reduced.

In order to avoid this problem, parallel plate capacitors 31 and 32 are electrically inserted in series between the input / output terminals of the integrated circuit 4 and the conductive object 11 as shown in the plan view of FIG. It is desirable to do.
In the antenna configuration of FIG. 36, if the capacitance of the parallel plate capacitors 31 and 32 is selected to an appropriate value, the second frequency band by the integrated circuit 4 is not adversely affected to the communication performance of the first frequency band. Power dissipation can be avoided, and the communication performance in the second frequency band can be kept good.

  Further, even when there is no adverse effect on the communication performance of the second frequency band, by inserting parallel plate capacitors 31 and 32 between the input / output terminals of the integrated circuit 4 and the conductive object 11 in series electrically. The parallel plate capacitors 31 and 32 can be used as an impedance matching circuit for the first frequency band, and the design freedom in the first frequency band is increased.

  As described above, the radio communication apparatus according to Embodiment 7 of the present invention includes an input / output terminal of the integrated circuit 4 and a conductive object (a spiral conductive object 2) connected to the input / output terminal as shown in FIG. Chip capacitor, parallel plate capacitor, or interdigital capacitor is inserted in series with any of the conductive objects 3, 11, and 19) and electrically connected to the input / output terminals of the integrated circuit 4. Capacitive reactances (parallel plate capacitors 31 and 32) are inserted in series.

Thereby, the power dissipation of the second frequency band in the integrated circuit 4 can be avoided, and the problem of a decrease in communication distance can be solved.
Further, the capacitive reactance (frequency selective coupling means) can be used as an impedance matching circuit for the first frequency band, and the degree of design freedom in the first frequency band can be increased.
As a result, it is possible to improve the communication performance of the wireless communication device described in the first to sixth embodiments.

  In FIG. 36, parallel plate capacitors 31 and 32 are shown as an example of the capacitive reactance electrically inserted in series between the integrated circuit 4 and the conductive object 11. However, the present invention is not limited to this. However, if the same effect as the parallel plate capacitors 31 and 32 can be obtained, an arbitrary configuration such as a chip capacitor or an interdigital capacitor can be applied. Also, the above-described resonators (dielectric resonators, ceramic resonators, piezoelectric resonators, etc.) may be used.

  FIG. 36 shows a case where the present invention is applied to the antenna configuration of FIG. 10 described above, but the same applies to other arbitrary antenna configurations by inserting capacitive reactances into the input / output terminals of the integrated circuit 4. The effect of this can be achieved.

(Example 8)
Although not specifically mentioned in the first to seventh embodiments, a card-type RFID capable of good communication in both the first and second frequency bands by integrating the first to seventh embodiments. Tags can be designed.

Hereinafter, a wireless communication apparatus according to an eighth embodiment of the present invention in which the first to seventh embodiments are integrated will be described with reference to FIGS.
Here, the center frequency of the first frequency band is 953 MHz, and the center frequency of the second frequency band is 13.56 MHz.

  FIG. 37 is a plan view showing a wireless communication apparatus according to Embodiment 8 of the present invention, and shows the surface structure of the designed tag. FIG. 38 is a plan view of the rear surface configuration of the tag designed as shown in FIG. 37 as seen through from the front surface side.

In FIG. 37, the wireless communication device includes a flat object 1, a spiral conductive object 2 having outer dimensions L and W, an L-shaped (extended shape) conductive object 3, integrated circuits 4 and 5, and , Conductive objects 7a and 7b, inter-layer connection portions 8a and 8b such as through holes, a closed loop conductive object 11, a chip capacitor (hereinafter simply referred to as “capacitor”) 25, and conductive objects 19 and 40. And.
The capacitor 25 functionally corresponds to the circuit element 15 described above (FIG. 18), and the conductive object 40 functionally corresponds to the conductive object 20 described above (FIGS. 34 and 35).

The capacitor 25 functionally corresponds to the parallel plate capacitor 30 described above (FIG. 18). Further, the conductive object 40 forms a parallel plate capacitor together with the portions of the spiral conductive object 2 facing each other, and functionally corresponds to the parallel plate capacitor 30 described above (FIG. 18).
The conductive object 19 forms a parallel plate capacitor together with the portions of the spiral conductive object 2 facing each other, and functionally corresponds to the circuit element 15 described above (FIG. 18).

  The spiral conductive object 2, the conductive object 3, the conductive object 7 a, and the conductive object 11 are disposed on the surface of the flat object 1. The conductive objects 19 and 40 are disposed on the back surface of the flat object 1. Further, the conductive object 7 b is formed on the front surface and the back surface of the flat object 1 via the different interlayer connection portion 8.

The external dimensions of the flat object 1 are in accordance with a practical card size standard, and the length in the z direction in FIG. 37 is 85.4 mm, and the length in the x direction is 54 mm.
In addition to the card size standard, the outer dimensions L and W of the spiral conductive object 2 are comprehensively considered for manufacturability and antenna performance in both the first and second frequency bands. L = 64 mm and W = 46 mm. Further, the number of turns of the spiral conductive object 2 is “3”.

The flat object 1 is constituted by a dielectric film substrate.
One integrated circuit 4 out of the integrated circuits 4 and 5 has characteristics and functions capable of satisfactorily communicating with an external communication device (reader / writer) in a frequency range of 860 MHz to 960 MHz.
The other integrated circuit 5 has a characteristic and a function capable of satisfactorily communicating with an external communication device in the 13.56 MHz band.

The conductive objects 7 a and 7 b connect the spiral conductive object 2 and the input / output terminals of the integrated circuit 5.
The different interlayer connection portion 8a connects the spiral conductive object 2 and the conductive object 7b, and the different interlayer connection portion 8b connects the front and back conductive objects 7b and the conductive object 7b and the conductive material. The object 40 is connected. Both ends of the conductive object 11 are connected to input / output terminals of the integrated circuit 4.

Further, as shown in the fifth embodiment (FIG. 29), the windings of the spiral conductive object 2 are capacitively coupled in the vicinity of the connection portion between the conductive object 3 and the spiral conductive object 2. For this purpose, the width of the winding of the spiral conductive object 2 is partially increased in the part, and the conductive object 19 is arranged on the back part of the opposing flat object 1 to constitute a parallel plate capacitor. ing.
Similarly, on the right side of the spiral conductive object 2, a parallel plate capacitor is configured using the conductive object 40, which corresponds to the parallel plate 30 in the above-described first to seventh embodiments.

The operating impedance of the integrated circuit 4 is 20−j190 [Ω].
As a method for matching the impedance between the integrated circuit 4 and the antenna, as described in the first embodiment, an electromagnetic coupling power feeding method using a micro loop is used.

  The input impedance of the antenna, that is, the impedance viewed from the terminal of the integrated circuit 4 on the antenna side is adjusted by adjusting the shape, size and position of the closed-loop conductive object 11 and the length of the conductive object 3, That is, it is designed to be a complex conjugate value of the operating impedance value of the integrated circuit 4.

  In the eighth embodiment (FIG. 37) of the present invention, a capacitor 25 is connected between the terminals of the integrated circuit 5 in addition to the parallel plate capacitor formed by the spiral conductive body 2 and the conductive body 40. .

The above configuration is intended to execute the UHF band antenna design and the HF band antenna design almost independently.
That is, the capacitance value of the parallel plate capacitor formed by the spiral conductive object 2 and the conductive object 40 is designed so that the antenna characteristics in the UHF band are good, and the capacitance of the capacitor 25 The values are designed so that the antenna characteristics of the HF band are good.

FIG. 39 is an explanatory diagram showing design results for the circuit configurations of FIGS. 37 and 38, and shows the frequency characteristics of the operating gain of the UHF band antenna.
In FIG. 39, the horizontal axis represents the frequency normalized at 960 MHz, and the vertical axis represents the operation gain [dBi].

  The operational gain shown on the vertical axis is based on the directivity gain determined only by the radiation pattern, and the radiation efficiency (loss due to antenna components such as conductor loss and dielectric loss) and mismatch loss (impedance between the antenna and the integrated circuit 4). It is defined as a value obtained by subtracting (loss due to mismatch). Further, the gain is evaluated by the value in the y direction (normal direction of the flat object 1) shown in FIG.

As is clear from FIG. 39, the specific bandwidth having an operation gain of 1 dBi or more is about 11% (0.95 to 1.06), and the specific bandwidth having an operation gain of 0 dBi or more is about 16% (0 .92 to 1.08), and it can be seen that a high operating gain is obtained over a wide band.
As a result of trial evaluation based on the design result according to Example 8 of the present invention, it was confirmed that a communication distance of 6.2 m was obtained in the UHF band, and the performance was sufficient for practical use.

  In general, the electromagnetic coupling power supply using the minute loop (closed loop-shaped conductive object 11) shown in FIG. 37 provides a wider band characteristic. However, when this power supply method is difficult to realize, FIG. As shown in FIG. 4, impedance matching with the integrated circuit 4 may be achieved by using a short stub 10 instead of the closed loop conductive object 11.

37 and 40, a parallel plate capacitor (conductive object 40) is used. However, when a chip capacitor can be easily mounted, a parallel plate capacitor (conductive) is used as shown in FIGS. It is also possible to use a capacitor 25 instead of the sex object 40).
Conversely, when it is difficult to mount a capacitor component such as a chip capacitor, the capacitor 25 may be replaced with a parallel plate capacitor (conductive object 40).

  In order to put the wireless communication device described in the first to eighth embodiments into practical use, for example, polypropylene (PP), polyethylene terephthalate (PET), polyimide (PI) or the like is used as the flat object 1. That's fine.

  The various conductive objects 2, 2a, 2b, 2c, 3, 10, 11, 19, and 40 are formed on the front surface or the back surface of the flat object 1, but can be formed by, for example, etching. Further, it can be formed by applying a printing technique such as ink jet printing or silk screen printing to attach a liquid containing metal particles to the flat object 1.

Further, by using an arbitrary double-sided substrate as the flat object 1, the flat object 1 and various conductive objects 2, 2 a, 2 b, 2 c, 3, 10, 11, 19, 40 may be formed by etching. .
Moreover, the different interlayer connection part 8 can be formed using a through hole processing technique etc., and the integrated circuits 4 and 5 and the circuit element (capacitor 25) use solder, a conductive adhesive, or an ultrasonic wave. It can be electrically coupled to various conductive objects.

  In addition, it is not particularly shown in the figure, by coating the surface of the electric / electronic circuit shown in Examples 1 to 8 (the surface or the back surface of the flat object 1 on which various conductive objects are formed) with a coating resin or the like. Furthermore, a practical antenna configuration can be realized. In this case, as the coating resin, it is preferable to use a material that can be printed / printed or a material that does not easily peel off even when a label is attached.

Furthermore, the wireless communication devices according to the first to eighth embodiments can be applied to wireless communication having a credit function or an authentication function.
Also, by including the first frequency band in the UHF band (300 MHz to 3000 MHz) and the second frequency band in the LF band (30 kHz to 300 kHz) or the HF band (3 MHz to 30 MHz), the mounting area of each antenna can be reduced. It is possible to obtain a wireless communication apparatus using a shared RFID card type tag of the LF band or the HF band and the UHF band, which is secured as large as possible and has a communication distance equivalent to each single communication distance.

Example 9
To summarize the main points of Examples 1 to 8, one main surface (the front side of the flat object 1 in FIGS. 1 to 42) and the other main surface (the back side of the flat object 1 in FIGS. 1 to 42) The spiral conductive object 2 is formed on one main surface of the flat object 1 having a perspective view), and the integrated circuit 5 is electrically connected to the spiral conductive object 2. Wireless communication with the conductive object 3 formed on one main surface or the other main surface of the flat plate-like object 1 on the outer periphery of the winding to be wound and directly or indirectly grounded by the spiral conductive object 2 It can be said that it is a device. The integrated circuit 4 is supplied with power from the conductive object 3.

  The above-described power supply method for the conductive object 3 is performed by connecting one end of the integrated circuit 4 to the outer periphery of the winding constituting the spiral conductive object 2 and electrically connecting the other end to the conductive object 3. Method, Method of Integrated Circuit 4 One End Connected to Conductive Object 19 That is Capacitance Coupling Means Between Windings (Other Main Surface Conductor Pattern), and Other End Electrically Connected to Conductive Object 3 Examples 1 to 8 disclose a method in which the circuit 4 is connected to a loop-shaped conductive object 11 and the loop-shaped conductive object 11 is coupled with a magnetic field generated by a current flowing through the conductive object 3. That is, by means of a spiral conductive object 2 that is a coil antenna (LF band or HF band) and a structure in which this coil antenna can be regarded as a ground conductor, this is directly (including “capacitive coupling”) or via an integrated circuit 5. Then, a conductive object 3 that is a monopole antenna (UHF band) connected to a coil antenna is placed on a flat object 1 that is a dielectric having one main surface (front surface) and another main surface (back surface). Examples 1 to 8 describe forming and obtaining a wireless communication device using a shared RFID card type tag of LF band or HF band and UHF band.

  Based on the above disclosure, in Example 9, the flat object 1 is a dielectric, the spiral conductive object 2 is a coil antenna 2, the conductive object 3 is a monopole antenna 3, and the conductive object 10 is a short stub. 10. Conductive object 11 is loop conductor pattern 11, conductive object 19 is another main surface conductor pattern 19 which is a capacitive coupling means between windings, integrated circuit 4 is an IC chip for monopole antenna 4, and integrated circuit 5 is a coil. The description will be made with the antenna IC chip 5 replaced. Needless to say, these replacements can also be performed in the first to eighth embodiments. The operating frequency band of the coil antenna IC chip is the LF band or the HF band, and the operating frequency band of the monopole antenna IC chip is the UHF band.

  Furthermore, the “rectangular shape” as used in the present specification includes those in which at least one of the four corners is cut (the number of cuts and angles are arbitrary), an arc shape, and those in which a part of the outer shape is cut off. Including. As for coil antennas, “rectangular” means that at least one of the four corners is arcuate or bent in two stages. Even if it is not the four corners, the coil antenna winding is bent at a right angle. It is not necessary to be bent in a circle, and it may be an arcuate one or a two-step bent one. In addition, the cards and card-type RFID tags referred to in this specification refer to those having dimensions that are standardized mainly by ISO, JIS, and the like. That is, it refers to a size generally used for business cards and commuter passes. In Examples 1 to 9 and Example 10 to be described later, the number of turns of the coil antenna 2 is described using three turns, but is not limited thereto. The outer periphery of the coil antenna 2 refers to the outermost conductor wire (conductor pattern), and the inner periphery of the coil antenna 2 refers to the innermost conductor wire (conductor pattern). However, in this case, the connection point between the monopole antenna 3 or the IC chip 4 for the monopole antenna and the coil antenna 2 is not necessarily the outermost conductor wire (conductor pattern) of the coil antenna 2. The outer periphery of the coil antenna 2 simply refers to the outer periphery of the entire winding.

  In the ninth embodiment, an example will be described in which the monopole antenna 3 is configured by a meander line to reduce the size. The meander line constituting this monopole antenna can also be applied to the monopole antenna 3 (conductive object 3) described in the first to eighth embodiments. In the ninth embodiment, a typical configuration / structure is used. The wireless communication apparatus according to the ninth embodiment will be described with reference to FIGS. 43 to 48, reference numerals 3a, 3b, and 3c denote monopole antennas with meander lines, which are replaced with the monopole antenna 3. This replacement allows the coil antenna 2 to be disposed also in the region of the dielectric 1 occupied by the monopole antenna 3 in Examples 1 to 8, and the amount (area) of the coil antenna 2 can be increased. Therefore, the communication distance characteristics of the LF band or HF band can be further improved. The monopole antennas 3a, 3b, 3c can be replaced with each other.

  This is because, when the dielectric body 1 having a rectangular outer shape is used for the wireless communication apparatus and the winding shape of the winding is a rectangular coil antenna 2, the monopole antenna is provided at the position of the dielectric body 1 corresponding to the hollow portion. 3 (refer to FIGS. 43 to 48). In Examples 1-8, the winding of the coil antenna 2 was arrange | positioned to the vicinity of two corners among the four corners in the rectangular dielectric 1, but in Example 9, the rectangular dielectric 1 Of the four corners in FIG. 5, the winding of the coil antenna 2 can be arranged up to the vicinity of the three corners. A monopole antenna 3 is disposed at the remaining corner of the rectangular dielectric 1. Therefore, as described above, in this case, it can be said that one corner of the coil antenna 2 having a rectangular winding shape is recessed, and the monopole antenna 3 is disposed in the recessed portion. Further, the monopole antenna 3 is configured with a meander line on the distal end side and a linear conductor pattern or an L-shaped conductor pattern on the proximal end side. When the dimensions of the rectangular dielectric 1 are limited, the monopole antenna 3 has a freedom in designing the radio communication device when the distal end side is configured with a meander line and the proximal end side selects an L-shaped conductor pattern. (For example, the wireless communication device described in FIGS. 43 to 48). In addition, you may interpret that an L-shaped conductor pattern is comprised from the L-shaped part and the linear part.

  In the winding shape (winding shape) of the coil antenna 2, a hollow portion where one corner is recessed is a part of the winding constituting the coil antenna 2, and the winding constituting the coil antenna 2 is bent toward the inner peripheral side. It may be interpreted as a wound winding portion. In addition, the monopole antenna 3 is disposed with the region from the winding bent portion (the recessed portion) toward the end of the dielectric 1 as a monopole antenna placement region. However, in the dielectric 1, when the coil antenna 2 and the monopole antenna 3 are not formed on the same surface, for example, when the coil antenna 2 is formed on one main surface and the monopole antenna 3 is formed on the other main surface, An area from the line bent portion (the recessed portion) toward the end of the dielectric 1 is a surface of the surface on which the coil antenna 2 of the opposing dielectric 1 is formed when the dielectric 1 is viewed in plan in the Y-axis direction on the drawing. The opposite surface (other main surface) is a monopole antenna arrangement region.

  In summary, when the monopole antenna 3 is disposed in the hollow portion (winding bent portion), the wireless communication apparatus according to the ninth embodiment has the following configuration. Dielectric 1 formed on one main surface of dielectric 1 having one main surface and another main surface, and on the outer periphery of a winding constituting rectangular coil antenna 2 to which coil antenna IC chip 5 is electrically connected. A monopole antenna IC chip 4 formed on one main surface or the other main surface and fed by a monopole antenna 3 grounded by the coil antenna 2, and a part of a winding constituting the coil antenna 2. In addition, a winding bending portion in which the winding constituting the coil antenna 2 is bent toward the inner peripheral side, and a meander line 3a constituting the monopole antenna 3 is disposed at the winding bending portion of the coil antenna 2.

  Hereinafter, a specific configuration of the ninth embodiment will be described using the wireless communication devices illustrated in FIGS. The wireless communication device shown in FIG. 43 is formed on one main surface of the dielectric 1 and connected to the outer periphery of the winding constituting the coil antenna 2 to which the coil antenna IC chip 5 is electrically connected. The monopole antenna IC chip 4 is electrically connected to the loop conductor pattern 11 that is coupled to the magnetic field generated by the current flowing in the monopole antenna 3a composed of the meander line, at least part of which is formed on one main surface. Is.

  43, the loop conductor pattern 11 to which the IC chip 4 for monopole antenna is connected is disposed in the space formed by the L-shaped conductor pattern, the meander line, and the coil antenna 2 of the monopole antenna 3a. Therefore, the area of the dielectric 1 can be used effectively. The basic configuration is the same as that of the wireless communication apparatus shown in FIG. 37, and the winding constituting the coil antenna 2 is the other main surface conductor pattern 19 formed on the other main surface of the dielectric 1 on the outer periphery. This is a conductor pattern in which the portion opposite to is widened. As for the winding which comprises the coil antenna 2, the winding inside a widened conductor pattern is also widened. Since the winding is wound three times in the drawing, the widened conductor pattern is formed at three locations. Therefore, the dimension of the other main surface conductor pattern 19 is substantially the same as the three widened conductor patterns. The description of the connection relationship between the coil antenna 2 and the coil antenna IC chip 5 is the same as in FIG.

  The wireless communication device shown in FIG. 44 is formed on one main surface of the dielectric 1 and has one end connected to the outer periphery of the winding constituting the coil antenna 2 to which the coil antenna IC chip 5 is electrically connected. The monopole antenna 3 a is electrically connected to the other end of the monopole antenna IC chip 4 and formed on one main surface of the dielectric 1. 43 is different from the radio communication device shown in FIG. 43 in that the method of feeding power to the IC chip 4 for monopole antenna is coupled to the magnetic field generated by the current flowing through the monopole antenna 3a in the radio communication device shown in FIG. The monopole antenna IC chip 4 is electrically connected to the conductor pattern 11. However, in the wireless communication apparatus shown in FIG. 44, the monopole antenna IC chip 4 has one end connected to the monopole antenna 3a. The other end is connected to the coil antenna 2 (the ground conductor for the monopole antenna 3a) and power is supplied.

  44 does not require the loop conductor pattern 11 to be disposed in the space formed by the L-shaped conductor pattern, the meander line, and the coil antenna 2 of the monopole antenna 3a. Therefore, the area of the dielectric 1 is reduced. It can be used effectively. The basic configuration is the same as that of the wireless communication apparatus shown in FIG. 43 (FIG. 37), and the windings constituting the coil antenna 2 are the other main parts formed on the other main surface of the dielectric 1 on the outer periphery. This is a conductor pattern in which a portion facing the surface conductor pattern 19 is widened. As for the winding which comprises the coil antenna 2, the winding inside a widened conductor pattern is also widened. Since the winding is wound three times in the drawing, the widened conductor pattern is formed at three locations. Therefore, the dimension of the other main surface conductor pattern 19 is substantially the same as the three widened conductor patterns. The description of the connection relationship between the coil antenna 2 and the coil antenna IC chip 5 is the same as in FIG.

  The wireless communication device shown in FIG. 45 is obtained by forming the short stub 10 for short-circuiting the monopole antenna 3a and the coil antenna 2 on the wireless communication device shown in FIG. This corresponds to the monopole antenna 3 replaced with the monopole antenna 3a. The radio communication device shown in FIG. 44 can effectively use the area of the dielectric 1 because the meander line of the monopole antenna 3a can be arranged in the space between the short stub 10 and the coil antenna 2. be able to. The basic configuration is the same as that of the wireless communication apparatus shown in FIG. 40, and the winding constituting the coil antenna 2 is the other main surface conductor pattern 19 formed on the other main surface of the dielectric 1 on the outer periphery. This is a conductor pattern in which the portion opposite to is widened. As for the winding which comprises the coil antenna 2, the winding inside a widened conductor pattern is also widened. Since the winding is wound three times in the drawing, the widened conductor pattern is formed at three locations. Therefore, the dimension of the other main surface conductor pattern 19 is substantially the same as the three widened conductor patterns. The description of the connection relationship between the coil antenna 2 and the coil antenna IC chip 5 is the same as in FIG.

  The wireless communication device shown in FIG. 46 has a meander line of the monopole antenna 3a arranged in the space between the short stub 10 and the coil antenna 2 in the wireless communication device shown in FIG. And a meander line of the monopole antenna 3b corresponding to that moved to the position toward the outer periphery of the dielectric 1. Therefore, with respect to the monopole antenna 3a, the monopole antenna 3b can shorten or eliminate the L-shaped conductor pattern, and most of the monopole antenna 3b can be configured with meander lines. . The basic configuration is the same as that of the wireless communication apparatus described in FIG. 45 (FIG. 40), and the windings constituting the coil antenna 2 are the outer periphery and the other main body formed on the other main surface of the dielectric 1. This is a conductor pattern in which a portion facing the surface conductor pattern 19 is widened. As for the winding which comprises the coil antenna 2, the winding inside a widened conductor pattern is also widened. Since the winding is wound three times in the drawing, the widened conductor pattern is formed at three locations. Therefore, the dimension of the other main surface conductor pattern 19 is substantially the same as the three widened conductor patterns. The description of the connection relationship between the coil antenna 2 and the coil antenna IC chip 5 is the same as in FIG.

  The wireless communication device shown in FIG. 47 corresponds to the wireless communication device shown in FIG. 37, in which the monopole antenna 3 is replaced with a monopole antenna 3c in which the meander line folding pitch changes midway. The basic configuration is the same as that of the wireless communication apparatus shown in FIG. 37, and the winding constituting the coil antenna 2 is the other main surface conductor pattern 19 formed on the other main surface of the dielectric 1 on the outer periphery. This is a conductor pattern in which the portion opposite to is widened. As for the winding which comprises the coil antenna 2, the winding inside a widened conductor pattern is also widened. Since the winding is wound three times in the drawing, the widened conductor pattern is formed at three locations. Therefore, the dimension of the other main surface conductor pattern 19 is substantially the same as the three widened conductor patterns. The description of the connection relationship between the coil antenna 2 and the coil antenna IC chip 5 is the same as in FIG.

  In the wireless communication device shown in FIG. 47, since the meander line folding pitch constituting the monopole antenna 3c changes midway, a space can be provided around the monopole antenna 3c formed on the dielectric 1. . For example, the short stub 10 for short-circuiting the monopole antenna 3a and the coil antenna 2 can be formed without increasing the size of the dielectric 1. This case corresponds to a structure in which the monopole antenna 3a and the monopole antenna 3b described in FIGS. 45 and 46 are combined. 43 is arranged in the space around the monopole antenna 3c formed on the dielectric 1, and the method of feeding power to the IC chip 4 for monopole antenna is changed to the monopole antenna 3c. It is also easy to select the loop conductor pattern 11 that is coupled to the magnetic field generated by the current flowing through

  The wireless communication device shown in FIG. 48 corresponds to the wireless communication device shown in FIG. 12 in which the monopole antenna 3 is replaced with a monopole antenna 3a. The description of the connection relationship between the coil antenna 2 and the coil antenna IC chip 5 is the same as in FIG. 48, the loop conductor pattern 11 coupled to the magnetic field generated by the current flowing through the monopole antenna 3a is arranged on the inner peripheral side of the windings constituting the coil antenna 2, and the monopole antenna 3a is Since the meander line is provided, the area of the dielectric 1 outside the outer peripheral side of the coil antenna 2 can be reduced.

  As described above, the ninth embodiment has been described with reference to FIGS. 43 to 48. However, in the wireless communication device illustrated in FIGS. The monopole antennas 3a, 3b, 3c of the wireless communication apparatus according to the ninth embodiment are applied to the wireless communication apparatus shown in FIG. Electrically connected to the other end of the monopole antenna IC chip 5 formed on the other main surface of the body 1 and having one end connected to the other main surface conductor pattern 19 that capacitively couples the windings constituting the coil antenna 2 Alternatively, a monopole antenna 3a (may be a monopole antenna 3b or a monopole antenna 3c) formed on the other main surface of the dielectric 1 may be used.

  1 .... Plate-like object (dielectric) 2 .... Spiral conductive object (coil antenna) 3..Conductive object (monopole antenna), 3a, 3b, 3c..Conductive object (with meander line) Monopole antenna), 7a, 7b, 20, 40 ... Conductive object, 10 ... Conductive object (short stub), 11 ... Conductive object (loop conductor pattern), 19 ... Conductive object (winding) Other main surface conductor pattern which is a capacitive coupling means), 4 .. Integrated circuit (IC chip for monopole antenna), 5.. Integrated circuit (IC chip for coil antenna), 8. ..Circuit elements, 25..Chip capacitors, 30a, 30b..Plates, 30..Parallel plate capacitors.

Claims (12)

  A dielectric having one main surface and another main surface; a coil antenna formed on one main surface of the dielectric and electrically connected to an IC chip for a coil antenna; and a winding constituting the coil antenna A monopole antenna formed on one outer surface or the other main surface of the dielectric on the outer periphery and grounded by the coil antenna, a meander line constituting the monopole antenna, and a monopole fed by the monopole antenna A wireless communication device comprising an antenna IC chip.   A dielectric having one main surface and another main surface; a coil antenna formed on one main surface of the dielectric and electrically connected to an IC chip for a coil antenna; and a winding constituting the coil antenna A monopole antenna which is an outer periphery and is grounded to the coil antenna and formed on one main surface of the dielectric, a meander line constituting the monopole antenna, and a monopole antenna fed by the monopole antenna A wireless communication device comprising an IC chip.   A dielectric having one main surface and another main surface; a coil antenna formed on one main surface of the dielectric and electrically connected to an IC chip for a coil antenna; and a winding constituting the coil antenna A monopole antenna connected to the outer periphery and formed on one main surface of the dielectric, a meander line constituting the monopole antenna, and an inner circumference side of a winding constituting the coil antenna, A wireless communication apparatus comprising: a loop conductor pattern coupled to a magnetic field generated by a current flowing through a pole antenna; and a monopole antenna IC chip electrically connected to the loop conductor pattern.   A dielectric having one main surface and another main surface; a coil antenna formed on one main surface of the dielectric and electrically connected to an IC chip for a coil antenna; and a winding constituting the coil antenna A monopole antenna IC chip having one end connected to the outer periphery, a monopole antenna electrically connected to the other end of the monopole antenna IC chip, and formed on one main surface of the dielectric, and the monopole antenna A wireless communication device comprising a meander line constituting a pole antenna.   The wireless communication apparatus according to claim 4, wherein the monopole antenna has a short stub that is short-circuited with the coil antenna.   A dielectric having one main surface and another main surface; a coil antenna formed on one main surface of the dielectric and electrically connected to an IC chip for a coil antenna; and a winding constituting the coil antenna A monopole antenna connected to the outer periphery and formed on one main surface of the dielectric, a meander line constituting the monopole antenna, and an outer peripheral side of a winding constituting the coil antenna, the monopole A wireless communication apparatus comprising: a loop conductor pattern coupled to a magnetic field generated by a current flowing through an antenna; and a monopole antenna IC chip electrically connected to the loop conductor pattern.   The portion of the winding constituting the coil antenna where the IC chip for monopole antenna or the monopole antenna is connected is a widened conductor pattern, and the other main part of the dielectric facing the widened conductor pattern. The wireless communication device according to claim 4, further comprising a conductor pattern on the other principal surface that is formed on a surface and capacitively couples between windings constituting the coil antenna.   A dielectric having one main surface and another main surface, a coil antenna formed on one main surface of the dielectric and electrically connected with an IC chip for coil antenna, and the dielectric facing the coil antenna Another main surface conductor pattern formed on the other main surface and capacitively coupling between the windings constituting the coil antenna, a monopole antenna IC chip having one end connected to the other main surface conductor pattern, A wireless communication apparatus comprising a monopole antenna electrically connected to the other end of the IC chip for a pole antenna and formed on the other main surface of the dielectric, and a meander line constituting the monopole antenna.   The wireless communication device according to claim 8, wherein the winding constituting the coil antenna is a conductor pattern having a wider outer periphery and a portion facing the other main surface conductor pattern.   The wireless communication device according to claim 7 or 9, wherein at least one of the windings constituting the coil antenna is widened inside the widened conductor pattern.   The radio communication apparatus according to any one of claims 1 to 10, wherein the monopole antenna has a distal end side constituted by the meander line and a proximal end side constituted by a linear conductor pattern or an L-shaped conductor pattern.   The wireless communication device according to claim 1, wherein the monopole antenna is disposed in a hollow portion of the coil antenna having a rectangular winding shape.

Images