JP2010276482A - Position detection device - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To provide a position detection device which can measure a correct position without being influenced by a temperature characteristic by a differential transformer. <P>SOLUTION: This position detection device includes a sine wave generation circuit 101, a D/A conversion circuit 102, A/D conversion circuits 103, 106, 107, a comparison circuit 104, a correction circuit 105, LPF (low pass filter) circuits 108, 109, 114, 115, center value correction circuits 110, 111, full-wave rectifying circuits 112, 113, averaging circuits 116, 117, a ratio operation circuit 118, and a position information output circuit 119. <P>COPYRIGHT: (C)2011,JPO&INPIT

Description

  The present invention relates to a position detection device using a differential transformer.

  As a position detection device using a differential transformer, it consists of an iron core that moves according to the position of the object to be measured, a primary winding that excites the iron core, and two secondary windings arranged in the direction of movement of the iron core. The input voltage of the primary winding is kept constant, the output voltage generated in each secondary winding is measured and the difference is obtained to detect the displacement of the iron core, and the position of the object to be measured There is an apparatus for measuring (see, for example, Patent Document 1).

The equivalent circuit of the differential transformer, replacing the transformer as shown in Figure 5, the output voltage V _S1 and V _S2 generated in the secondary winding of the formula (1), expressed as (2).
V _S1 = jωM ₁ I _P + jωL _S1 I _S1 (1)
V _S2 = jωM ₂ I _P + jωL _S2 I _S2 (2)
V _S1 , V _S2 : Output voltage [V] of the secondary winding
M ₁ and M ₂ : mutual inductance [H]
I _P : Primary winding input current [A]
I _S1 , I _S2 : Input current of secondary winding [A]
L _S1 , L _S2 : Inductance [H] of secondary winding
In equations (1) and (2), if the secondary side is set to high impedance, the secondary side input currents I _S1 and I _S2 can be regarded as zero. For this reason, Formula (1), (2) is represented like Formula (3), (4).
V _S1 = jωM ₁ I _P (3)
_{V S2 = jωM 2 I P ···} (4)
In the expressions (3) and (4), the mutual inductances M ₁ and M ₂ are expressed as the expressions (5) and (6).
M ₁ = k ₁ √ (L _P L _S1 ) (5)
M ₂ = k ₂ √ (L _P L _S2 ) (6)
k ₁ , k ₂ : coupling coefficient L _P : inductance of primary winding [H]
In addition, since the magnetic resistance R is expressed as in Expression (7), the self-inductance L is expressed as in Expression (8).
R = 1 / (μS) [Ω] (7)
μ: Core permeability [H / m]
S: Cross-sectional area of the core [m ² ]
l: Magnetic path length [m]
L = N ² / R
= ΜN ² S / l (8)
N: Number of turns [t]
From equation (8), equation (5), self-inductance _L P of _(6), L _{S1, L S2} is represented as the respective formulas (9) to (11).
L _P = μN _P ² S / l (9)
L _S1 = μN _S1 ² S / l (10)
L _S2 = μN _S2 ² S / l (11)
N _P : number of turns of primary winding [t]
N _S1 , N _S2 : Number of turns of secondary winding [t]
When Expressions (5), (6), and (9) to (11) are substituted into Expressions (3) and (4), they are expressed as Expressions (12) and (13).
V _S1 = jωM ₁ I _P
= Jω (k ₁ √ (L _P L _S1 )) I _P
= Jω (k ₁ √ ((μN _P ² S / l) × (μN _S1 ² S / l))) I _P
= Jωk ₁ (μN _P N _S1 S / l) I _P (12)
V _S2 = jωM ₂ I _P
= Jω (k ₂ √ (L _P L _S2 )) I _P
= Jω (k ₂ √ ((μN _P ² S / l) × (μN _S2 ² S / l))) I _{P
= Jωk 2 (μN P N S2} S / l) I P ··· (13)
From Expressions (12) and (13), the difference between the output voltages generated in the secondary winding is expressed as Expression (14).
_{V S1 -V S2 = jωI P ×} μN P S (k 2 N S1 -k 2 N S2) / l ··· (14)

JP-A-7-270178

In the formula (14), the difference between the output voltage includes a magnetic permeability μ of the input current I _P and the core of the primary winding. However, the input current I _P of the primary winding has a temperature dependence since the value of the winding resistance varies with temperature changes, since the more permeability μ having a temperature dependence, according to the difference between the output voltage Temperature Will be affected. Therefore, the above-described conventional technique has a problem in that the position of the object to be measured obtained by measurement is affected by the input current and temperature of the primary side winding, and the correct position cannot be measured.

  The present invention has been made in view of the above problems, and an object of the present invention is to provide a position detection device capable of measuring a correct position without being affected by temperature characteristics.

The present invention relates to a position detection device using a differential transformer including a primary winding, two secondary windings, and a movable iron core.
Center value correcting means for correcting the center value of each output of the secondary winding;
Full wave rectification means for full wave rectification of each output of the center value correction means;
Averaging means for averaging the outputs of the full-wave rectifying means;
Based on each output signal of the averaging means, ratio calculating means for calculating the ratio of each coupling coefficient between the primary winding and the two secondary windings;
And a position calculating means for calculating the position of the movable iron core using the ratio obtained by the ratio calculating means.

  Further, the present invention is characterized in that each output of the secondary winding is A / D converted and input to the center value correcting means.

  According to the present invention, after digitizing the output voltage of the secondary winding of the differential transformer, the position is calculated based on the ratio of the digitized output voltage of the secondary winding. It is possible to provide a position detecting device that can measure the correct position without being affected by the temperature characteristic and the influence of the magnetic permeability and the input current of the primary side winding without being affected by the temperature characteristics.

It is a circuit block diagram of the position detection apparatus which concerns on embodiment of this invention. It is a wave form diagram which shows the input waveform to the position detection apparatus which concerns on embodiment of this invention, the waveform after LPF, and the waveform after center correction | amendment. It is a wave form diagram which shows the waveform input into the full wave rectifier circuit which concerns on embodiment of this invention, the wall after full wave rectification, the waveform after ripple removal, and the waveform after averaging. It is a figure which shows the calibration method of the position detection hand which concerns on embodiment of this invention. It is a circuit block diagram of the position detection apparatus which concerns on the conventional embodiment.

  Hereinafter, embodiments of the present invention will be described in detail with reference to FIGS. In addition, this invention is not limited to the embodiment which concerns, A various change is possible within the range of the technical thought.

FIG. 1 is a circuit configuration diagram of a position detection device using a differential transformer according to the present embodiment.
As shown in FIG. 1, the differential transformer 1 includes a movable iron core 11, a primary side winding 12, and two secondary side windings 13 and 14.
The movable iron core 11 is moved by the control device 7 and excited by the primary side winding 12 to generate an output voltage in each of the secondary side windings 13 and 14. In the primary side winding 12, the output of the buffer circuit 2 and the input of the buffer circuit 3 are connected to one side of the winding, and the other winding is grounded.
The secondary winding 13 has one winding connected to the input of the buffer circuit 4 and the other winding grounded. The secondary winding 14 has one winding connected to the input of the buffer circuit 5 and the other winding grounded. The input of the buffer circuit 2 is connected to the output of the D / A conversion circuit 102 of the position detection device 10, and the output of the buffer circuit 2 is connected to the primary winding 12 of the differential transformer 1. The input of the buffer circuit 3 is connected to the primary winding 12 of the differential transformer 1, and the output of the buffer circuit 3 is connected to the input of the A / D conversion circuit 103 of the position detection device 10. The input of the buffer circuit 4 is connected to the secondary winding 13 of the differential transformer 1, and the output of the buffer circuit 4 is connected to the input of the A / D conversion circuit 106 of the position detection device 10. The input of the buffer circuit 5 is connected to the secondary winding 14 of the differential transformer 1, and the output of the buffer circuit 5 is connected to the input of the A / D conversion circuit 107 of the position detection device 10.

  The position detection device 10 includes a sine wave generation circuit 101, a D / A conversion circuit 102, A / D conversion circuits 103 and 106 and 107, a comparison circuit 104, a correction circuit 105, and an LPF (Low Pass Filter) circuit 108 and 109 and 114. 115, center value correction circuits 110 and 111, full wave rectification circuits 112 and 113, averaging circuits 116 and 117, a ratio calculation circuit 118, and a position information output circuit 119.

 The sine wave generation circuit 101 generates a digital sine wave and outputs it to the D / A conversion circuit 102 and the comparison circuit 104. The sine wave generation circuit 101 adjusts the peak value of the generated digital sine wave based on the peak value control signal from the correction circuit 105.

  The D / A conversion circuit 102 receives the digital sine wave generated by the sine wave generation circuit 101, converts the digital signal into an analog signal, and outputs the analog signal to the buffer circuit 2.

  The A / D conversion circuit 103 converts the input signal from the buffer circuit 3 from an analog signal to a digital signal and outputs the converted signal to the comparison circuit 104.

  The comparison circuit 104 compares the peak value of the input signal from the A / D conversion circuit 103 with the peak value of the input signal from the sine wave generation circuit 101 and outputs the comparison value to the correction circuit 105.

  The correction circuit 105 is based on the comparison value from the comparison circuit 104, and the peak value of the input signal from the A / D conversion circuit 103 to the comparison circuit 104 and the peak value of the input signal from the sine wave generation circuit 101 to the comparison circuit 104. Are generated, and a peak value control signal for controlling the sine wave generation circuit 101 is generated and output to the sine wave generation circuit 101.

The A / D conversion circuit 106 outputs a signal Vb ′ obtained by converting the output signal of the buffer circuit 4 from an analog signal to a digital signal to the LPF circuit 108. The A / D conversion circuit 107 outputs a signal V _c ′ obtained by converting the output signal of the buffer circuit 5 from a digital signal to an analog signal to the LPF circuit 109.

The LPF circuit 108 removes the high frequency noise component of the signal V _b ′ output from the A / D conversion circuit 106, and outputs the signal after the noise removal to the center value correction circuit 110. Further, the LPF circuit 109 removes the high frequency noise component of the signal V _c ′ output from the A / D conversion circuit 107 and outputs the signal after the noise removal to the center value correction circuit 111.

The center value correction circuit 110 generates V _bT −V _bB that is Peak-to-Peak of the output signal of the LPF circuit 108. Next, the center value correction circuit 110 generates the center value V _bA by (V _bT −V _bB ) / 2. The center value correction circuit 110 generates a difference ΔV _bA between the generated center value V _bA and the ground G that is a reference voltage, and performs center value correction for offsetting the generated difference ΔV _bA . The center value correction circuit 110 outputs the output voltage V _bc subjected to the center value correction to the full wave rectification circuit 112.

The center value correction circuit 111 generates V _cT −V _cB that is Peak-to-Peak of the output signal of the LPF circuit 109. Further, the center value correction circuit 111 generates a center value V _cA by (V _cT −V _cB ) / 2. The center value correction circuit 111 generates a difference ΔV _cA between the generated center value V _cA and the ground G, and performs center value correction for offsetting the generated difference ΔV _bA . Further, the center value correction circuit 111 outputs the signal V _{cc subjected} to the center value correction to the full wave rectification circuit 113.

FIGS. 2A, 2B, and 2C are diagrams for explaining the operations of the LPF circuit 108 and the center value correction circuit 110, and the signals are shown as analog waveforms for convenience.
FIG. 2A shows the waveform of the signal V _b ′ input from the A / D conversion circuit 106. The signal V _b ′ has a noise component due to a D / A conversion error by the D / A conversion circuit 102 and an A / D conversion error by the A / D conversion circuit 106, and is a center value that is an average value with respect to the ground G The value is off. FIG. 2B shows a waveform after the noise is removed from the signal V _b ′ by the LPF circuit 108. FIG. 2 (c), after the noise removal in the LPF circuit 108, a signal _{V bc} after the center value correction at the center value correction circuit 110.

The full-wave rectification circuit 112 performs full-wave rectification of the voltage V _bc output from the center value correction circuit 110 and outputs a signal V _br subjected to full-wave rectification to the LPF circuit 114. The full wave rectification circuit 113 performs full wave rectification of the voltage V _cc output from the center value correction circuit 111 and outputs a signal V _cr subjected to full wave rectification to the LPF circuit 115.

The LPF circuit 114 removes the ripple component of the signal V _br output from the full-wave rectifier circuit 112 and outputs the signal V _br ′ after the ripple removal to the averaging circuit 116. The LPF circuit 115 removes the ripple component of the signal V _cr output from the full-wave rectifier circuit 113 and outputs the signal V _cr ′ after the ripple removal to the averaging circuit 117.

The averaging circuit 116 averages the voltage V _br ′ output from the LPF circuit 114 by time averaging calculation. In the time average calculation, a signal for one period of the averaging circuit 116 necessary for the calculation is acquired, and the average voltage of the acquired signal for one period is calculated and averaged. For this reason, after the completion of the averaging of the first period, since a first-in first-out process is performed thereafter, it is not necessary to newly acquire a signal for one period and average it again. The averaging circuit 116 outputs the averaged output voltage _Vba to the ratio calculation circuit 118.
The averaging circuit 117 averages the voltage V _cr ′ output from the LPF circuit 115 by time averaging, and outputs the averaged output voltage V _ca to the ratio calculation circuit 118.

FIG. 3 is a diagram for explaining operations of the full-wave rectifier circuit 112, the LPF circuit 114, and the averaging circuit 116, and the signals are shown as analog waveforms for convenience.
FIG. 3A shows the signal V _bc input to the full wave rectifier circuit 112. FIG. 3B shows the signal V _br after full-wave rectification is performed by the full-wave rectification circuit 112. FIG. 3C shows the signal V _br ′ after the ripple removal by the LPF circuit 114. FIG. 3D shows the signal V _ba after the averaging is performed by the averaging circuit 116.

The ratio calculation circuit 118 calculates the ratio V _p between V _ba and V _ca output from the averaging circuits 116 and 117. The ratio V _p between V _ba and V _ca is given by equation (18) from equations (12), (13), and (14).
V _ba = jωk ₁ (μN _a N _b S / l) I _a (16)
V _ca = jωk ₂ (μN _a N _c S / l) I _a (17)
N _a : Number of turns of primary winding [t]
N _b , N _c : number of turns of secondary winding [t]
_Vp = _Vb / _Vc
= Jωk ₁ (μN _a N _b S / l) I _a / jωk ₂ (μN _a N _c S / l) I _a
= K ₁ / k ₂ (N _b / N _c ) (18)
In Expression (18), in the case of a differential transformer, N _b and N _c which are secondary side turns are the same, and therefore, N _b = N _c . For this reason, the ratio V _p between V _ba and V _ca is expressed only by the ratio of the coupling coefficient as shown in equation (19).
V _p = k ₁ / k ₂ (19)
Further, the ratio calculation circuit 118 outputs the calculated ratio V _p between V _ba and V _ca to the position information output circuit 119.

The position information output circuit 119 is stored in the position information output circuit 119 as a table in which the ratio V _p and the position of the movable iron core 11 are associated with each other using the ratio V _p output from the ratio calculation circuit 118. For example, the ratio V _p = 1 is set as the physical null position of the position of the movable core 11, that is, 0 [mm], and the ratio V _p = 0.9 is set as the position 0.05 [mm] of the movable core 11. Further, the position information output circuit 119 outputs the associated position information to the control device 7.

  The control device 7 receives the position information output from the position information output circuit 119 of the position detection device 10. The control device 7 controls the position of the movable iron core 11 of the differential transformer 1 by controlling the actuator 8 connected to the movable iron core 11.

Next, an example of a position detection calibration method and a position detection method using the differential transformer 1, the position detection device 10, and the control device 7 will be described with reference to FIG.
The user controls the actuator 8 connected to the movable iron core 11 from the control device 7 to display the position of the movable iron core 11 of the differential transformer 1 while visually checking the position display unit 201 (for example, a scale). The unit 201 moves to a physical null position (Null Position) where 0 [mm] is displayed. When the electrical null position where _Vba and _Vca are the same and the physical null position of the movable iron core 11 are the same, the output voltage _{Vb of the} secondary winding is as shown in _FIGS. Since V _c and V _c are the same value, the ratio of V _ba and V _ca generated for digitization and ratio calculation is V _p = 1, and the position information output circuit 119 outputs 0 [mm] to the control device 7. To do.

However, in manufacturing, the electrical null position may be different from the physical null position of the secondary winding of the movable iron core 11 due to variations in the attachment position of the secondary winding and the like. In such a case, it is necessary to perform calibration, and an example of a calibration method will be described below.
First, the user controls the actuator 8 connected to the movable iron core 11 from the control device 7 to bring the movable iron core 11 of the differential transformer 1 to the physical null position while visually checking the position display unit 201. Move. When the coupling coefficient k ₁ = 0.81 and k ₂ = 0.9 due to variations in the mounting position of the secondary winding, etc., the secondary output voltage is V _b as shown in FIG. And V _c have different values, and V _b = 0.9 [V] and V _c = 1.0 [V]. Therefore, the ratio V _p = 0.9 (= 0.81 / 0.9) between the coupling coefficients k ₁ and k ₂ is obtained. Position information output circuit of the position detecting device 10 119 outputs the coupling coefficient _{k 1} and position information 0.05 corresponding to a ratio _V p = 0.9 for _{k 2} [mm] to the control device 7.

  Next, the user controls the actuator 8 connected to the movable iron core 11 using the control device 7, and the position information 0.05 [mm] output from the position information output circuit 119 of the position detection device 10. , The position of the movable iron core 11 is adjusted to be 0 [mm].

  Next, the user adjusts the position information output from the position information output circuit 119 of the position detection device 10 to 0 [mm], and then the movable iron core 11 indicated by the position display unit 201 of the differential transformer 1. Read position. In the example of FIG. 4, it is assumed that the position information 0 [mm] output from the position information output circuit 119 of the position detection device 10 is obtained at the position of +0.05 [mm]. In this case, the user records +0.05 [mm] read from the position display unit 201 of the position detection device 10 as a calibration value of the position of the movable core 11 in a memo or the like.

Next, an example of the position detection method will be described.
For example, when the user wants to move the movable iron core 11 to a position of +7 [mm], the user corrects the calibration value +0.05 [mm] to +7.05 [mm] and corrects the position display unit 201. While visually confirming, the control device 7 is used to control and adjust the actuator 8 connected to the movable iron core 11.

Furthermore, for example, when the movable iron core 11 is mounted on a detection float that floats on the surface of the liquid, the position of the movable iron core 11 changes according to the amount of liquid. A configuration method and a position detection method in such a usage method will be described below.
In this case, calibration at the electrical null position is performed first. The user connects the position of the movable iron core 11 to the movable iron core 11 using the control device 7 so that the position information output from the position information output circuit 119 of the position detection device 10 becomes 0 [mm]. The actuator 8 is controlled and adjusted. After the adjustment, the position display unit 201 of the differential transformer 1 is visually confirmed, and the display value is read. For example, when the position display unit 201 indicates +0.05 [mm], +0.05 [mm] is recorded as a calibration value of the position of the movable core 11 in a memo or the like. Next, the position information output from the position information output circuit 119 of the position detection device 10 is corrected based on this calibration value. For example, when the position information output from the position information output circuit 119 of the position detection device 10 is +7.05 [mm], the correction to subtract the calibration value 0.05 [mm] to +7 [mm] is controlled. The user of the device 7 or the control device 7 corrects and uses it.

  In the present embodiment, in the comparison circuit 104, the ratio between the peak value of the input signal from the A / D conversion circuit 103 and the peak value of the input signal from the sine wave generation circuit 101 is input to the correction circuit 105 as a comparison value. Although an example of output has been described, the difference between the peak value of the input signal from the A / D conversion circuit 103 and the peak value of the input signal from the sine wave generation circuit 101 is output to the correction circuit 105 as a comparison value. May be.

In the present embodiment, the center value correction circuits 110 and 111 generate a difference ΔV _bA or ΔV _cA between the center value V _bA or V _cA and the ground G as the reference voltage, and the generated difference ΔV _bA or ΔV. _Although an example of performing center value correction for offsetting _cA has been described, the same effect can be obtained even when the reference voltage is, for example, 2.5 [V], which is the midpoint potential, depending on the circuit configuration.

  Furthermore, in the present embodiment, an example in which one of the primary windings 12 of the differential transformer 1 is grounded and a signal is input has been described. However, a signal may be input to both ends of the primary winding 12. good. Similarly, one of the secondary windings 13 and 14 may not be grounded, and the output of the secondary winding may be input to, for example, each D / A conversion circuit.

Furthermore, in this embodiment, the position information output circuit 119 outputs the coupling coefficient ratio V _p corresponding to the position information input from the ratio calculation circuit 118 to the control device 7 as a voltage value corresponding to the ratio V _p. However, the current value may be used, and the numerical value of the calculation result input from the ratio calculation circuit 118 may be directly output as a digital signal.

  Furthermore, in the present embodiment, the example in which the signals from the secondary windings 13 and 14 of the differential transformer 1 are received by the separate A / D conversion circuits 106 and 107 has been described. A signal from the secondary windings 13 and 14 may be alternately received by the / D conversion circuit.

  Furthermore, in the present embodiment, an example in which there are two systems for the LPF circuit, the center value correction circuit, the full-wave rectifier circuit, and the averaging circuit of the position detection device 10 has been described, but the signals from the secondary windings 13 and 14 Similarly to the A / D conversion circuit that receives the signal, one circuit may be used by time-division processing.

  Note that all or some of the functions of the embodiment of FIG. 1 are implemented by a ROM (Read Only Memory), HDD (Hard Disk Drive) connected to a CPU (Central Processing Unit) (not shown) in the position detection device 10. Alternatively, the program can be executed by a program stored in a USB memory or the like connected via a USB (Universal Serial Bus) I / F.

  As described above, in the present invention, since the output voltage of the secondary side winding of the differential transformer is digitized, the position is calculated based on the digitized output ratio of the secondary side winding. Therefore, a position detecting device capable of measuring a correct position without being affected by temperature characteristics is eliminated. Also, in the present invention, a digital circuit using a filter circuit such as noise removal and a full-wave rectifier circuit for obtaining the output ratio of the secondary winding with respect to the digitized output voltage of the secondary winding of the differential transformer. Since signal processing is performed, it is possible to realize a position detection device capable of measuring a correct position without being affected by temperature characteristics due to temperature dependence by a rectifying element or the like.

DESCRIPTION OF SYMBOLS 1 ... Differential transformer 11 ... Movable iron core 12 ... Primary side windings 13, 14 ... Secondary side windings 2, 3, 4, 5 ... Buffer circuit 7 ... Control device 8 ... Actuator 10 ... Position detection device 101 ... Sine wave generation circuit 102 ... D / A conversion circuit 103, 106, 107 ... A / D conversion circuit 104 ... Comparison circuit 105- .. Correction circuits 108, 109, 114, 115 ... LPF circuits 110, 111 ... Center value correction circuits 112, 113 ... Full wave rectification circuits 116, 117 ... Averaging circuit 118 ... Ratio Arithmetic circuit 119 ... Position information output circuit 201 ... Position display section

Claims (2)

In a position detection device using a differential transformer having a primary winding, two secondary windings, and a movable iron core,
Center value correcting means for correcting the center value of each output of the secondary winding;
Full wave rectification means for full wave rectification of each output of the center value correction means;
Averaging means for averaging the outputs of the full-wave rectifying means;
Based on each output signal of the averaging means, ratio calculating means for calculating the ratio of each coupling coefficient between the primary winding and the two secondary windings;
And a position calculating means for calculating the position of the movable iron core using the ratio obtained by the ratio calculating means. The position detection device according to claim 1, wherein each output of the secondary winding is A / D converted and input to the center value correction unit.

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