JP2010207087A - Controller of motor for electric power steering - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To provide a controller of a motor that detects a current with high accuracy using an amplifier with general accuracy, and also, prevents the accuracy of current detection from being deteriorated even when the temperature changes. <P>SOLUTION: The controller includes: a switch circuit 10 for supplying a driving current to a motor 17, a resistor 7 for detecting the driving current, an amplifying circuit 2 for amplifying the potential difference between the ends of the resistor 7, an input-unit switching means 15 provided in the input unit of the amplifying circuit 2 to change the direction of the potential difference between two sides, an output-unit switching means 20 provided in the output unit of the amplifying circuit 2 to change the direction of the output voltage of the amplifying circuit 2 between two sides, and a CPU 50 for averaging the two voltages obtained when the direction of the output voltage of the amplifying circuit 2 is switched between the two sides. <P>COPYRIGHT: (C)2010,JPO&INPIT

Description

  The present invention relates to a motor control device, and more particularly to a motor control device for a three-phase brushless DC motor used for an assist motor or the like of an electric power steering device.

  In recent years, for the purpose of improving fuel consumption by reducing the weight of a vehicle, a technique for performing torque assist using a motor instead of a conventional hydraulic power assist device has been introduced.

  For example, as a motor for assisting an electric power steering device (EPS), a three-phase brushless DC motor that is relatively agile and can generate high torque and is easy to control is used. In this three-phase brushless DC motor, the torque varies in proportion to the current. Therefore, in order to accurately control the motor, it is necessary to accurately detect the current flowing through the motor.

  For this reason, conventionally, for example, a method described in Patent Document 1 (Japanese Patent Application Laid-Open No. 2004-117070) has been adopted. That is, an external resistor (shunt resistor) for current detection is added, the potential difference generated by the motor drive current is amplified by an amplifier circuit such as an operational amplifier, and taken into the microcomputer using an A / D conversion function. Using this data, the motor is driven by PWM control by performing current value feedback so that the flowing current matches the target current.

JP 2004-1117070 A

  However, normally, an amplifier such as an operational amplifier has an input offset. In an operational amplifier generally used, the input offset is about 10 mV at maximum. Since this includes fluctuation due to temperature, it is necessary to consider an offset deviation of about 10 mV at the maximum when the temperature changes.

  On the other hand, when controlling a motor for electric power steering, it is necessary to control a current exceeding 100 A at the maximum. In this case, it is necessary to use a shunt resistor having a resistance of about 1 mΩ in consideration of heat generation.

  If the accuracy deteriorates, there is a possibility that the person who is operating is uncomfortable as described above. Therefore, the current detection accuracy is required to be within ± several percent. If an input offset occurs about ± 10 mA, using a shunt resistor of 1 mΩ corresponds to an error of 10 A. For this reason, an error of about 10% is included in the control current of 100 A, which may cause problems such as torque ripple. In particular, when a minute current flows, the influence of the offset deviation on the control current becomes large, and this tendency becomes remarkable.

  Also, using an operational amplifier with a small input offset to increase accuracy leads to an increase in cost, and there are many cases where other options such as temperature conditions cannot be satisfied because there are fewer choices for the operational amplifier.

  In addition, since this problem depends on the input offset inherent in the amplifier circuit, it cannot be solved by increasing the A / D accuracy of the CPU.

  Further, there is a problem that even if the initial offset correction of the input offset is performed by the initial calibration, the offset shift due to the temperature cannot be dealt with.

  In recent years, in order to reduce costs, a current drive circuit, a current detection circuit, and the like are integrated and integrated into an IC. In this case, since the performance of a circuit such as an operational amplifier depends on the device and process characteristics in the case of making an IC, there may be a case where a highly accurate amplifier cannot be realized or a case where the cost increases due to an increase in chip size.

  An object of the present invention is to provide a motor control device that does not deteriorate accuracy due to offset deviation even when an amplifier circuit such as an operational amplifier having a normal input offset is used.

  It is another object of the present invention to provide a motor control device that is not affected by any device or process characteristics even when the current detection circuit is integrated into an IC.

  A typical motor control device according to the present invention includes a switch circuit for supplying a drive current to a motor, a current detection circuit for detecting the drive current and converting it to a voltage, and a current detection circuit. And an amplifier circuit for amplifying the converted voltage, and provided with means for correcting an input offset of the amplifier circuit.

  Another representative one of the motor control devices according to the present invention is a switch circuit having a high-side switch and a low-side switch for supplying a drive current to a three-phase motor, and a resistor for detecting the drive current. And an amplifier circuit for amplifying the potential difference between both ends of the resistor, an input unit switch means for switching the potential difference so as to rotate forward or reverse, and an output circuit of the amplifier circuit. Output unit switch means for switching the output voltage of the amplifier circuit to normal or reverse, the first output voltage when the output voltage of the amplifier circuit is normal, and the output voltage of the amplifier circuit are inverted And an arithmetic processing unit for averaging the second output voltage.

  ADVANTAGE OF THE INVENTION According to this invention, a low-cost and accurate motor control apparatus can be provided.

1 is a circuit block diagram illustrating a first embodiment. The timing chart explaining operation | movement of a 1st Example. 3 is a flowchart for explaining an example of a calculation operation in the CPU of FIG. The circuit block diagram explaining the 2nd example. The timing chart explaining operation | movement of a 2nd Example. The circuit diagram which shows an example of the voltage smoothing means in a 2nd Example. The circuit block diagram explaining the 3rd example. The timing chart explaining operation | movement of a 3rd Example. The current-voltage characteristic view explaining the effect of the third embodiment. The timing chart explaining the other Example in the structure similar to FIG. The flowchart explaining another Example in the structure similar to FIG. The circuit block diagram explaining the 4th example. The timing chart explaining operation | movement of a 4th Example. The timing chart explaining the operation | movement of another effect in a 4th Example. The timing chart explaining the other Example in the structure similar to FIG. The circuit block diagram explaining the 5th example. The block diagram explaining the structure of the duty restriction | limiting means in a 5th Example. The timing chart explaining operation | movement of a 5th Example.

  Hereinafter, embodiments of the present invention will be described in detail with reference to FIGS.

  FIG. 1 is a block diagram showing a motor drive current detection circuit according to a first embodiment of the present invention.

  In FIG. 1, reference numeral 1 denotes an amplifying means for amplifying the voltage difference 9 across the shunt resistor 7, which amplifies the difference between two inputs, + and −, + side input signal 3 and − side input of the amplifier circuit. An input switch means 15 for alternately switching the connection of the signal 4, the positive gain output 18, the negative gain output 19, the shunt resistance voltage 5, 6 and the amplifying means to the + side input signal 3 and the-side input signal 4; And an output switch means 20 for switching between a positive gain output 18 and a negative gain output 19. Reference numeral 16 denotes an input offset voltage Vofs of the amplifier circuit 2.

  7 is a shunt resistor for detecting the drive current 8 for driving the motor 17, 5 and 6 are voltage across the shunt resistor 7, and 9 is the potential difference. Reference numeral 10 denotes a drive switch circuit such as a MOS transistor for driving a motor 17 by causing a current to flow through the motor 17, and ON / OFF switching control is performed by a PWM control signal from a CPU or the like. 11 is a motor drive signal, 12 is an amplified output signal from the amplification means 1, 13 is a high-side switch drive signal for ON / OFF control of the drive switch circuit 10, 14 is a low-side switch drive signal, and 17 is actually driven It is a three-phase motor.

  Reference numeral 40 denotes an amplifying means switching signal output from the CPU 50 in synchronization with the PWM cycle, and the input switch means 15 and the output switch means 20 in the amplifying means 1 are switched by this signal. A CPU 50 generates a high-side switch drive signal 13, a low-side switch drive signal 14, and an amplification means switching signal 40, which are output from the PWM signal generation unit 50a of the CPU 50.

  Reference numeral 90 denotes PWM frequency dividing means that divides the high-side switch drive signal 13, and a PWM frequency division signal 91 that is an output signal of the frequency dividing means is input to the amplification means 1. The input switch means 15 and the output switch means 20 are configured to be switched according to the PWM frequency division signal 91. Reference numeral 51 denotes a power supply, and 52 denotes GND.

  In the present embodiment, a, b, and c added after the numbers are similar circuits in the current detection circuit that detects currents driving the U, V, and W phases of the three-phase motor 17, respectively. It shows that it is a means.

  Next, the operation of this embodiment will be described with reference to FIGS.

  FIG. 2 is a timing chart for explaining the operation of FIG. In FIG. 2, 60 indicates a PWM cycle for driving the motor, and the amplifying means switching signal 40 is switched between high and low at a timing synchronized with the PWM cycle. 61 and 62 are both-end voltages generated at both ends of the current detection means (shunt resistor), 63 and 65 are values obtained by multiplying the input offset 16 of the amplification means by a predetermined gain value of the amplification circuit 2, and 64 and 66 are both ends of the shunt resistance. This is a value obtained by multiplying the voltages 61 and 62 by a predetermined gain value of the amplifier circuit 2.

  Reference numeral 69 denotes a sampling timing signal indicating the A / D timing of the CPU 50, and the amplifier means output signal 12 is sampled at the timing of this signal. Reference numeral 67 denotes a sampling value obtained by sampling the amplifier output voltage 12 at the timing of the sampling timing signal 69, and 68 is an average of the sampling value 67.

  The operation of the first embodiment is as follows.

  In the circuit having the configuration shown in FIG. 1, the high-side switch drive signal 13 and the low-side switch drive signal 14 are output from the CPU 50 in synchronization with the PWM cycle 60. As a result, the drive switch circuit 10 is turned on / off, and a drive current is supplied to the U, V, and W motor drive signals 11a, 11b, and 11c connected to the three-phase motor 17. When the high-side switch drive signal 13 is high, a current flows from the power source 51 toward the motor 17, and when the low-side switch drive signal is high, a current flows from the motor 17 toward the GND 52.

  In the case of the first embodiment, since the current detecting shunt resistor 7 is added to the downstream side of the low-side switch of the drive switch circuit 10, as shown in FIG. The voltage flows through the shunt resistor only during the period, and a voltage 9 is generated at both ends of the shunt resistor. In FIG. 2, 61 and 62 indicate voltage levels appearing at both ends of the shunt resistor in each of the cycles 60a and 60b, and the potential difference 9 is a value calculated by (shunt resistance value × current amount).

  Voltages 5 and 6 across the shunt resistor 7 are input to the amplifying means 1 and current is detected by the following operation. First, in the period 60a, since the amplification means switching signal 40 is high, the input switch means 15 and the output switch means 20 are switched to the (A) side (this is called the normal rotation side). In this case, the voltages 5 and 6 across the shunt resistor are connected to the + side input signal 3 and the − side input signal 4, respectively, and are connected to the + and − input terminals of the amplifier circuit 2, respectively. The amplification circuit 2 multiplies by a predetermined gain and outputs a plus gain output 18 (gain: GA) and a minus gain output 19 (gain: -GA). Since the output switch means 20 is also switched to the (A) side, the plus gain output 18 is output to the amplification means output 12 and input to the CPU. At this time, since the voltage across the shunt resistor is 61 and the input offset 16 of the amplifier circuit 2 is + Vofs, the voltage input to the amplifier circuit is (61 + Vofs). Therefore, the positive gain output 18 of the amplifier circuit is (61 + Vofs) × GA.

  On the other hand, in the cycle 60b, the amplification means switching signal becomes low, and the input switch means 15 and the output switch means 20 of the amplification means 1 are switched to the (B) side (this is called the inverting side). In this case, the voltages 5 and 6 across the shunt resistor are connected to the negative side input signal 4 and the positive side input signal 3, respectively, and are connected to the negative and positive input terminals of the amplifier circuit 2, respectively. Similarly, the amplification circuit 2 multiplies a predetermined gain, outputs a positive gain output 18 (gain: GA) and a negative gain output 19 (gain: -GA), and the output switch means 20 is also switched to the (B) side. Therefore, a negative gain output 18 is output to the amplification means output 12 and input to the CPU 50. At this time, since the voltage across the shunt resistor is 62 and the input offset 16 of the amplifier circuit 2 is + Vofs, the voltage input to the amplifier circuit is − (62−Vofs). Therefore, the plus gain output 18 of the amplifier circuit is (−62 + Vofs) × (−GA).

  The output voltage of the amplifying means is indicated by 63 to 66 in the amplifying means output voltage 12 of FIG. That is, in the period 60a, 64 = input voltage 61 × GA, and a value obtained by adding 63 = Vofs × GA obtained by multiplying the input offset Vofs by gain is the amplification unit output 12. Similarly, in the period 60b, 66 = input voltage 62 × GA, and a value obtained by adding 65 = −Vofs × GA obtained by multiplying the input offset Vofs by gain is the amplification unit output 12.

  When the amplifying means output voltage 12 is sampled at the CPU sampling timing 69, the sampling values of the periods 60a and 60b become 67a and 67b, respectively. When the sampling value is calculated by the CPU in the flowchart as shown in FIG. 3 and the average value is taken, the average voltage 68 is as follows.

Average voltage 68 = (67a + 67b) / 2
Average voltage 68 = ((61 × GA + Vofs × GA) + (62 × GA−Vofs × GA)) / 2
Average voltage 68 = (61 × GA + 62 × GA) / 2
Thus, the average voltage 68 does not include the input offset component of the amplifier circuit, and is a value obtained by multiplying the voltage across the shunt resistor by the predetermined gain GA of the amplifier circuit. Therefore, accurate current detection without an offset error can be performed.

  FIG. 3 is an example of a flowchart for calculating the average voltage performed in the CPU 50. By such calculation, the average voltage value is calculated for each PWM cycle and the detected voltage value is updated, so that the drive current flowing through the motor 17 can be detected with high accuracy, and motor drive control with high accuracy can be performed.

  Although the present embodiment has been described based on the configuration of the electric power steering, even when used in a system such as an electric brake using the same three-phase DC motor and current detection resistor, it is similarly highly accurate. Current detection can be performed.

  Next, another effect of the present embodiment will be described with reference to the timing chart of FIG.

  The drive switch circuit 10 is turned on / off by the high-side switch drive signal 13 and the low-side switch drive signal 14 in order to pass a drive current to the motor 17. At this time, the PWM frequency dividing means 90 divides the high side switch drive signal 13 and outputs a PWM frequency divided signal 91. Thereby, the input switch means 15 and the output switch means 20 of the amplifying means 1 are switched as in the other embodiments, and the signals on the normal rotation side and the inversion side are output. The CPU 50 can perform sampling and detect the average current.

  As a result, there is a limitation on the function or speed of the CPU, and even when a CPU that cannot output the amplification means switching signal 40 for switching the amplification means 1 in synchronization with the PWM cycle is used, the high synchronization synchronized with the PWM drive cycle of the motor is used. By using the side switch drive signal 13 to switch the amplification means between the normal rotation side and the reverse rotation side, current detection without offset deviation can be performed.

  In this embodiment, the amplifying means is switched using the frequency-divided signal of the high-side switch drive signal 13, but the same effect can be obtained by using the low-side switch drive signal 14.

  FIG. 4 is a block diagram showing a motor drive current detection circuit according to the second embodiment of the present invention. In the description of the second embodiment, the description of the same parts as those of the first embodiment is omitted.

  In FIG. 4, 21 is a voltage smoothing means for smoothing the amplification means output voltage 12 output from the amplification means 1, and 68 is an average voltage. The current detecting shunt resistor 7 is disposed between the high-side switch and the low-side switch of the drive switch circuit 10, and the voltage at both ends is input to the amplifier 1.

  The operation of this embodiment will be described with reference to FIG.

  As shown in FIG. 5, when a drive current for driving the motor 17 is supplied by turning on / off the drive switch circuit 10 using the high-side switch drive signal 13 and the low-side switch drive signal 14, the drive current flows through the shunt resistor 7. 8 flows, and the waveform indicated by the voltage 9 across the current detection means is detected across the shunt resistor 7. When this is input to the amplifying means 1 and the input signal and the output signal are switched by the amplifying means switching signal 40, the amplifying means output voltage 12 shown in FIG. As described in the first embodiment, the input offset Vofs of the amplifier circuit is multiplied by a predetermined gain with respect to the output voltage 70 by the original drive current, and is added on the normal rotation side and subtracted on the inversion side every PWM cycle. Output. This signal is input to the voltage smoothing means 21.

  The voltage smoothing means 21 is, for example, a low-pass filter (LPF) constituted by a resistor and a capacitor shown in FIG. 6 and smoothes the output voltage of the amplifying means and outputs an average voltage 68. The CPU 50 can perform A / D conversion on this signal, perform sampling, and detect the drive current of the motor 17. In the case of the present embodiment, since the average value of the voltage is calculated by a voltage smoothing circuit outside the CPU 50, it is not necessary to perform an operation as shown in the flowchart of FIG. 3 by the CPU, and can be applied to a circuit using a CPU with poor processing capability. There is a merit.

  FIG. 7 is a block diagram showing a motor drive current detection circuit according to a third embodiment of the present invention. A description of the same parts as those of the embodiment already described is omitted. In FIG. 7, reference numeral 24 denotes voltage shift means, which is arranged between the output voltage 12 of the amplification means 1 and the CPU 50.

  FIG. 8 is a timing chart showing the operation of the motor drive current detection circuit of the third embodiment.

  When the driving switch circuit 10 is turned on / off by the high-side switch driving signal 13 and the low-side switch driving signal 14 and a driving current is caused to flow, the driving current 8 flows through the shunt resistor 7. A voltage waveform indicated as a voltage 9 across the current detection means is detected. When this voltage is very small and smaller than the input offset Vofs16 of the amplifier circuit, the signal output from the amplifying unit 1 may be 0 V or less as indicated by 12 in FIG.

  Normally, since the voltage range that can be sampled by the CPU 50 is 0 or more, normal current values cannot be sampled. Therefore, the amplification means output voltage 12 is input to the voltage shift means 24, the voltage is boosted by a predetermined voltage 71, the voltage is shifted, and the voltage shift means output 23 is output. As a result, the voltage input to the CPU is always 0 V or higher, and even when the current is small and the output of the amplifier circuit is 0 V or lower on the inverting side, the signal input to the CPU can be 0 V or higher. For this reason, it is possible to detect a normal current value and control the drive current of the motor.

  FIG. 9 is a graph showing the relationship between the motor drive current 8 and the voltage shift means output 23 in the third embodiment.

  The relationship between the motor drive current 8 and the voltage shift means output 23 is a straight line that rises to the right as the motor drive current 8 increases and the output voltage 23 increases. At this time, when the drive current 8 becomes 0, for example, the output voltage of the amplification means also becomes 0. For example, when there is a potential difference between the GND 52 to which the motor 17 and the shunt resistor 7 are connected and the GND to which the CPU is connected, the output of the amplifying unit 1 is 0 before the motor driving current 8 becomes 0 completely. Therefore, there is a possibility that a small current cannot be detected normally.

  In the present embodiment, the output voltage input to the CPU is raised by the shift voltage 71 by the voltage shift means, so that even when the drive current 8 is completely zero, the predetermined shift voltage amount 71 is secured, and the CPU It becomes possible to perform A / D conversion normally, and drive current detection with high accuracy can be performed.

  FIG. 12 is a block diagram showing an example of a motor drive current detection circuit for explaining a fourth embodiment of the present invention. A description of the same parts as those of the embodiment already described is omitted.

  In FIG. 12, reference numeral 80 denotes a frequency dividing means, which divides the amplifying means switching signal 40 input from the CPU, outputs an amplifying means switching frequency dividing signal 81, and is input to the amplifying means 1. The amplification means switching frequency division signal 81 is also input to the CPU at the same time.

  The operation of the present embodiment will be described as follows with reference to FIGS. 13 and 14.

  Depending on the CPU or software, the inversion timing of the amplifying means switching signal 40 may be inverted at half the PWM cycle as shown in the timing chart of FIG. In this case, the amplifying means switching signal is divided by the frequency dividing means 80 to generate the amplifying means switching divided signal 81, and the amplifying means is switched by this signal, so that normal rotation and inversion are performed every PWM period, and the average Current can be detected.

  FIG. 14 is a timing chart for explaining another effect in the present embodiment. In FIG. 14, the amplifying means switching signal 40 inputted from the CPU is divided by 3 by the dividing means to generate an amplifying means switching frequency dividing signal 81, thereby switching the amplifying means 1.

  At the same time, since the amplification means switching frequency division signal 81 is input to the CPU 50, the CPU 50 can generate a sampling timing pulse 69 at a timing synchronized with the amplification means switching frequency division signal 81 and perform sampling. Thereby, after switching of the amplifying means 1, it is possible to perform sampling by the CPU after a sufficient time, so that a normal average current can be obtained by sampling the PWM cycle once every odd number of times. Can do. In addition, there is an advantage that sampling can be performed without being affected by noise or the like due to switching.

  FIG. 16 is a block diagram showing an example of a motor drive current detection circuit for explaining the fifth embodiment of the present invention. A description of the same parts as those of the embodiment already described is omitted.

  In FIG. 16, reference numeral 92 denotes a duty limiting unit, 93 denotes a duty limiting signal, the high-side drive signal 13 is input to the duty limiting unit 92, and the duty limiting signal 93 is input to the frequency dividing unit 90.

  17 and 18 explain the operation of this embodiment.

  FIG. 17 is a block diagram showing the internal configuration of the duty limiting means. In FIG. 17, 110 is an edge detection means for detecting the edge of an input signal, 111 is an edge signal, 112 is an OR circuit, 114 is a count circuit, and is reset by an OR circuit output reset signal 113. Reference numeral 117 denotes a register that holds a predetermined set value, and the held predetermined value can be varied according to the period of the PWM period 60.

  The set value output 118 and the counter output 121 are compared by the comparison unit 119, and the comparison unit output 115 is output at a predetermined count value. The comparing means output 115 resets the counting means 114 via the OR circuit 112. At the same time, the comparison means output 115 is ANDed with the input high-side drive signal 13 by the AND circuit 120, and a duty limiting means output signal 93 is output.

  This operation will be described with reference to the timing chart of FIG.

  The edge of the input high side switch drive signal 13 is detected, and the counting means operating at a predetermined clock is reset. As a result, the count means output 121 is reset every time the edge signal 111 is input and returns to the zero value. Since the PWM signal is input once every PWM cycle 60 except in the case of Duty 0% and 100%, the PWM signal is divided to generate a frequency dividing means output signal 91 that is inverted every PWM cycle, Current detection can be performed.

  When the duty is 0% or 100%, the PWM signal is not input in the PWM cycle. Therefore, the counter is not reset by the edge signal 111, and the count value continues to increase. When the setting signal 118 set by the predetermined setting value 117 matches the value of the counting means output 121, the comparison means output 115 is outputted from the comparison means 119 and is inputted to the frequency dividing means 90 to generate a frequency division signal. be able to. For this reason, even when the duty of the PWM signal becomes 0% or 100%, the frequency division signal can be inverted at each cycle, and the frequency dividing means output 91 that is inverted every PWM cycle can be generated. The switch means can be reversed to accurately detect the current.

  In this embodiment, the high-side switch drive signal 13 is input to the duty limiting means 92. However, the same effect can be obtained even if the low-side switch drive signal 14 is input.

  10 and 11 are a timing chart and a flowchart showing another embodiment in the same circuit configuration as that of the first embodiment.

  In FIG. 10, when the drive switch circuit 10 is turned on / off by the high-side switch drive signal 13 and the low-side switch drive signal 14 and a drive current is supplied, the drive current 8 flows through the shunt resistor 7, and both ends of the shunt resistor 7 are connected. The voltage waveform shown as the voltage 9 across the current detection means is detected.

  When this is input to the amplifying means 1 and switched by the amplifying means switching signal 40, a voltage signal such as the amplifying means output voltage 12 in the figure is output on each of the forward rotation side and the reverse rotation side. Since the amplifying means switching signal 40 is alternately inverted every PWM cycle, the amplifying means output voltage 12 also repeats the normal rotation side and the inversion side alternately. At this time, if the CPU 50 performs sampling according to the flowchart of FIG. 11, the sampling is performed once every odd number of times, and the sampling timing indicated by 69 in FIG. Thereafter, similarly, the average voltage can be obtained using the sampled data (67a to 67d), and the motor can be driven and controlled based on the average data.

  As described above, when the output repeats normal rotation and inversion every PWM cycle, even when sampling of the PWM cycle is difficult and sampling is difficult every time, the sampling is performed once every odd number of times. A normal average voltage can be obtained. For this reason, it becomes possible to control the motor drive current by detecting the average current based thereon.

  According to these embodiments, even if an operational amplifier having a normal offset is used, the motor drive current can be accurately performed. In addition, since it is not affected by external factors such as temperature fluctuations, a motor control device without torque ripple can be provided. The motor control apparatus described in these embodiments can be applied not only to an electric power steering apparatus but also to other applications using a motor, such as a brake control apparatus and a vehicle drive control apparatus.

  DESCRIPTION OF SYMBOLS 1 ... Amplifying means, 2 ... Amplifying circuit, 7 ... Shunt resistance, 10 ... Drive switch circuit, 15 ... Input switch means, 17 ... Motor, 20 ... Output switch means, 21 ... Voltage smoothing means, 24 ... Voltage shift means, 40 ... amplifying means switching signal, 50 ... CPU, 51 ... power source, 52 ... GND, 90 ... PWM frequency dividing means, 92 ... Duty limiting means.

Claims (17)

A switch circuit for supplying drive current to the motor;
A current detection circuit for detecting the drive current and converting it into a voltage;
A motor control device having an amplifier circuit for amplifying the voltage converted by the current detection circuit,
The motor control device includes means for correcting an input offset of the amplifier circuit. The motor control device according to claim 1,
The motor control device, wherein the current detection circuit is constituted by a shunt resistor. The motor control device according to claim 1,
The amplifier circuit has input unit switch means provided at an input unit of the amplifier circuit, and output unit switch means provided at an output unit of the amplifier circuit,
The motor control apparatus, wherein the input unit switch unit and the output unit switch unit are controlled to be switched at a predetermined cycle. The motor control device according to claim 3, wherein
The motor control device calculates the drive current according to the output of the amplifier circuit, and outputs a PWM control signal for PWM control of rotation of the motor;
A switch switching unit that outputs a switch switching signal for switching the input unit switch unit and the output unit switch unit at the predetermined period;
The motor switching device, wherein the switch switching means switches the input switch means and the output switch means by outputting the switch switching signal in synchronization with the PWM control signal. The motor control device according to claim 4, wherein
The motor control device has frequency dividing means for dividing the PWM control signal,
A motor control device that switches between the input switch means and the output switch means on the basis of the frequency-divided signal divided by the frequency dividing means. The motor control device according to claim 5, wherein
The frequency-divided signal is input to the arithmetic processing unit,
The said arithmetic processing unit samples the output from the said amplifier circuit at the timing synchronized with the said frequency-divided signal, The motor control apparatus characterized by the above-mentioned. The motor control device according to claim 4, wherein
The input unit switch unit and the output unit switch unit are switched to take either the first state or the second state,
The arithmetic processing unit includes: a first sampling value captured when the input unit switch unit and the output unit switch unit are in the first state; and the input unit switch unit and the output unit switch unit in the second state. A motor control device that averages the second sampling value captured in the case of The motor control device according to claim 7, wherein
A motor control device that takes in the second sampling value when the input unit switch unit and the output unit switch unit are switched an odd number of times after the arithmetic processing unit has fetched the first sampling value. The motor control device according to claim 3, wherein
The switch circuit includes a high-side switch, and a low-side switch connected to the high-side switch via a first contact,
The current detection circuit is provided between the motor and the first contact;
The motor control device includes voltage flattening means for flattening an output voltage from the amplifier circuit. The motor control device according to claim 9, wherein
The motor control apparatus according to claim 1, wherein the voltage flattening means is a low-pass filter composed of a resistor and a capacitor. The motor control device according to claim 7, wherein
The motor control device includes voltage shift means for shifting an output voltage from the amplifier circuit. The motor control device according to claim 7, wherein
The motor control device has a duty limiting means for limiting the duty of the PWM control signal,
The duty limiting unit outputs the switch switching signal for switching the input unit switching unit and the output unit switching unit when the duty of the PWM control signal is 0% or 100%. Control device. A switch circuit having a high-side switch and a low-side switch for supplying a driving current to the three-phase motor;
A resistor for detecting the drive current;
An amplifier circuit for amplifying a potential difference between both ends of the resistor;
An input unit switch means provided at an input unit of the amplifier circuit, for switching the potential difference so as to rotate forward or reverse;
An output unit switching means provided at the output unit of the amplifier circuit, for switching the output voltage of the amplifier circuit so as to rotate forward or reverse;
An arithmetic processing unit for averaging the first output voltage when the output voltage of the amplifier circuit is rotated forward and the second output voltage when the output voltage of the amplifier circuit is inverted; A motor control device. The motor control device according to claim 13,
The motor control device PWM-controls the rotation of the three-phase motor,
The motor controller according to claim 1, wherein the input unit switch unit and the output unit switch unit are switched in synchronization with a PWM control signal. The motor control device according to claim 13,
The motor control device has PWM frequency dividing means,
The PWM frequency dividing means divides the PWM control signal to generate a frequency divided signal,
The motor control apparatus according to claim 1, wherein the input unit switch unit and the output unit switch unit are switched based on the frequency division signal. The motor control device according to claim 15, wherein
The motor control device includes voltage shift means for shifting an output voltage from the amplifier circuit. The motor control device according to claim 15, wherein
The motor control device has a duty limiting means for limiting the duty of the PWM control signal,
The duty limiting unit outputs the switch switching signal for switching the input unit switching unit and the output unit switching unit when the duty of the PWM control signal is 0% or 100%. Control device.

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