JP2009231904A - Phase shifter and phased array antenna - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To provide a phase shifter and a phased array antenna whose occupation areas and consumption power are small. <P>SOLUTION: The phase shifter includes a first transmission line TLa which transmits a signal of a first frequency, and a second transmission line TLb, and is configured such that a current having the first frequency flows in the second transmission line, and the current is controlled so as to adjust the phase of the signal transmitted via the first transmission line. <P>COPYRIGHT: (C)2010,JPO&INPIT

Description

  The present application relates to a phase shifter and a phased array antenna, and in particular, is radiated from a phase shifter that arbitrarily controls the phase of a high-frequency signal and a plurality of antenna units arranged using a plurality of phase shifters. The present invention relates to a phased array antenna that controls the directivity of an electromagnetic wave beam.

  Conventionally, a phased array antenna having a plurality of arranged antenna units, supplying signals of different phases controlled by a phase shifter to each antenna unit, and performing directivity control is known. Yes. This phased array antenna is used, for example, as a vehicle-mounted radar.

  By the way, with the recent progress of microfabrication technology of CMOS semiconductors, higher speed and higher integration of semiconductor devices are progressing. Even in a semiconductor integrated circuit device (LSI) using CMOS, it has become possible to handle a signal of several tens GHz which has been considered as a compound semiconductor or Bi-CMOS region. On the other hand, the increase in power consumption accompanying the increase in speed is a major problem, and there is a demand for circuit scale reduction and circuit sharing.

  FIG. 1 is a diagram for explaining the relationship between a radiation angle and a feeding phase in a phased array antenna.

  As shown in FIG. 1, the phased array antenna 1 includes phase shifters 111 to 115 that give different phases 2φ, φ, 0, −φ, and −2φ to signals from the signal source 100, and each phase shifter. Final stage amplifiers (power amplifiers) 121 to 125 that amplify the outputs of the devices 111 to 115, and antenna units 131 to 135 connected to the final stage amplifiers 121 to 125, respectively. Here, for example, the antenna units 131 to 135 are arranged so as to be separated from adjacent antenna units by a distance d.

  And the radiation energy from the arranged antenna units 131-135 by the signals of different phases 2φ, φ, 0, −φ, −2φ is spatially synthesized, and the directivity of the wavefront (electromagnetic wave) is controlled.

  In FIG. 1, the main lobe direction (θ) indicates the direction of a vector having the strongest energy among the electromagnetic waves radiated to the space, and the main lobe direction θ is the radiation angle of the electromagnetic wave beam.

  That is, when five antenna units 131 to 135 are used and a signal having a phase difference of φ is fed to each adjacent antenna unit, the main lobe direction is given by θ, and the phase difference φ is φ = d・ Sin θ. In addition, d shows the distance between each antenna unit, and is normally set to d = λ / 2 (λ is the wavelength of the signal).

  Specifically, when d = λ / 2 and a main lobe of θ = 10 ° is radiated, the phase difference φ is φ≈30 °, and when using five antenna units 131 to 135, for example, The antenna units 131 to 135 need to generate and feed signals having phases of 60 °, 30 °, 0 °, −30 °, and −60 °, respectively.

  In FIG. 1, the radiation angle of the electromagnetic wave beam is controlled using the five antenna units 131 to 135, but the number of the antenna units can be variously changed, and the planar shape is not linear. It can also be arranged (two-dimensionally).

2-4 is a figure which shows the example of the conventional phase shifter.
First, as shown in FIG. 2, a phase shifter 10 as an example of the prior art weights input signals Scos and Ssin whose phases are different by 90 ° by weighting circuits 10a and 10b, respectively, and the weighted signals Are added (vector synthesis) by the adding circuit 10c. As a result, a signal Sout having an arbitrary phase between the input signals Scos (for example, a signal having a phase of 0 °) and Ssin (for example, a signal having a phase of 90 °) input to the weighting circuits 10a and 10b is obtained. Be able to.

  As shown in FIG. 3, a phase shifter 20 as another conventional example is connected between series-connected inductors 20a to 20c and a connection node of each of the inductors 20a to 20c and the ground. It is configured as an LC circuit with variable capacitors 20d to 20f. Then, by adjusting the capacitances of the variable capacitors 20d to 20f, a signal Sout in which a predetermined phase delay is given to the input signal Sin can be obtained.

  Further, as shown in FIG. 4, the phase shifter 30 as another conventional example is connected between the inductors 30 a to 30 c connected in series and the connection node of each inductor 30 a to 30 c and the ground. The LC circuit includes the capacitors 30d to 30f and the switch circuit 30g. Then, by selecting an output of a connection node between adjacent inductors 30a to 30c by the switch circuit 30g, a signal Sout having a different phase delay with respect to the input signal Sin can be obtained.

  FIG. 5 is a diagram showing an example of a conventional phased array antenna (electronic scanning radar antenna), in which the phase shifters 10 (11a, 11b, 11c to 15a, 15b, 15c) shown in FIG. 2 are arranged. The five antenna units 131 to 135 are provided in correspondence with the five antenna units. In addition, 11d-15d has shown the mixer.

  As shown in FIG. 5, in an example of a conventional phased array antenna, each pair of weighting circuits 11a, 11b to 15a, 15b is, for example, a signal having a phase difference of 90 ° (local signal LO (Local Oscillator)). , And vector synthesis (addition) of the weighted signals by the adders 11c to 15c, thereby generating a signal having a predetermined phase.

  The outputs of the adders 11c to 15c of each phase shifter are mixed with the output signal IF (Intermediate Frequency) by the mixers 11d to 15d, respectively, and then supplied to the final stage amplifiers 121 to 125 via the matching circuits 141 to 145. The And the signal energy amplified by the last stage amplifiers 121-125 is radiated | emitted to space via the antenna units 131-135. Here, each of the antenna units 131 to 135 is arranged, for example, separated from the adjacent antenna unit by a distance d.

  In addition, the signal energy radiated | emitted to space through the arranged antenna units 131-135 has predetermined directivity according to the phase of the signal given to each antenna unit 131-135.

  Conventionally, in a phase shifter that changes the phase of a high-frequency signal, a signal whose phase is to be changed is divided into two paths by a distributor in order to achieve a wide band and high stability with a relatively simple configuration. It has been proposed that the output of a variable attenuator provided in each path is combined with a directional coupler with different phases (see, for example, Patent Document 1).

  Conventionally, an input signal is branched by a 90 ° hybrid, and the branched signal is supplied to two linear modulators controlled by a sine / cosine function type potentiometer, and the outputs of the two linear modulators are signals. A sine wave signal phase shifter that is synthesized by a synthesis circuit has also been proposed (for example, see Patent Document 2).

Japanese Patent Laid-Open No. 11-017464 Japanese Patent Laid-Open No. 53-121445

  First, the conventional phase shifter described with reference to FIG. 3 performs a delay using the fixed inductors 20a to 20c and the variable capacitors 20d to 20f. The variable capacitors 20d to 20f are, for example, semiconductors This is a capacitance by a MOS (namely, an element in which a conductive layer such as polysilicon is formed on a semiconductor substrate via an insulating film) which is internally called a varactor.

  The conventional phase shifter described with reference to FIG. 4 uses the fixed capacitors 30d to 30f, but selects the output extracted from the connection node between the adjacent inductors 30a to 30c by the switch circuit 30g. ing.

  That is, since the conventional phase shifter shown in FIGS. 3 and 4 uses an active device (MOS) for the varactor and the switch circuit, the influence of device noise is a problem in an RF circuit having a limitation on NF (negative feedback). Become.

  Furthermore, the conventional phase shifter (phased array antenna) that performs the vector synthesis described with reference to FIGS. 2 and 5 uses, for example, a signal having a phase difference of 90 ° in addition to a true signal. Is generated. That is, in order to generate a signal having an arbitrary phase, for example, signals of four phases (0 °, 90 °, 180 °, 270 °) are required.

  However, a local signal LO (for example, a voltage controlled oscillator (VCO)) of several tens of GHz used as a radar often uses an inductor, and in order to convert the local signal LO into a four-phase output, for example, double the area. And power is required.

  In order to make the local signal LO into a four-phase output, it is possible to divide the frequency from the double frequency LO, but it is difficult to design such a high-speed LO (VCO).

  Furthermore, since the vector synthesis method handles four-phase signals, it is very difficult to maintain the phase difference, and there is a problem that it is difficult to generate a signal having an arbitrary phase. Further, as shown in FIG. 5, there is a problem that it is necessary to prepare a plurality of mixers after shifting the LO output.

  This application aims at providing a phase shifter and a phased array antenna with a small occupation area and low power consumption in view of the above-described problems of the prior art.

  According to the first embodiment, a first transmission line for transmitting a signal having a first frequency, and a second transmission line, and passing a current having the first frequency through the second transmission line, A phase shifter is provided that controls a current to adjust a phase of the signal transmitted through the first transmission line.

  According to the second embodiment, there is provided a phased array antenna comprising a plurality of antenna units arranged at predetermined intervals and a plurality of phase shifters for controlling the phases of signals supplied to the respective antenna units. Is done. Here, each phase shifter includes a first transmission line that transmits a signal having a first frequency, and a second transmission line, and allows a current having the first frequency to flow through the second transmission line, The phase of the signal transmitted through the first transmission line is adjusted by controlling the current.

  According to each embodiment, it is possible to provide a phase shifter and a phased array antenna with a small occupation area and power consumption.

  First, before detailed description of examples of the phase shifter and the phased array antenna, the principle of the present embodiment will be described in detail with reference to the accompanying drawings.

  FIG. 6 is a diagram schematically showing a transmission line, and FIG. 7 is a diagram schematically showing a coupled transmission line. In FIG. 6, reference numeral A is an amplifier, TL is a transmission line, and so on. ANT indicates an antenna.

In general, the propagation velocity V of a signal transmitted through a transmission line as shown in FIG. 6 (for example, a coplanar waveguide or a microstrip line) is V∝ (LC). ^-1/2 . By controlling L and C, the propagation speed can be controlled to control the arrival time of the signal, and a phase shift can be realized.

  In this embodiment, a pair of transmission lines (coupled transmission lines) TLa and TLb arranged in parallel as shown in FIG. 7 is used, and electromagnetic coupling (M) between the pair of transmission lines TLa and TLb is used. To generate an arbitrary phase difference.

  FIG. 8 is a diagram for explaining the relationship between the coupled transmission line and the current. Here, FIG. 8A shows a case where currents Ia and Ib are passed from right to left in the drawing with respect to the pair of transmission lines TLa and TLb, and FIG. A case where currents Ia and Ib are supplied in the right direction from the right is shown. FIG. 8C illustrates electromagnetic coupling M when a current is passed in the same direction with respect to the pair of transmission lines TLa and TLb.

  As shown in FIG. 8A and FIG. 8B, when it is desired to delay the phase of the signal, the current in the same direction in the transmission line TLb arranged in parallel to the transmission line TLa through which the true signal flows is shown. Shed.

  That is, as shown in FIG. 8C, the magnetic field generated by the transmission line TLa through which the true signal flows is hindered by the magnetic field generated by the current in the same direction flowing through the transmission line TLb arranged in parallel. As a result, a signal phase delay appears at the signal arrival point. This realizes phase shift by so-called electromagnetic induction.

  On the other hand, when it is desired to realize phase advance, on the contrary, it is realized by setting the current flowing through the transmission line TLb arranged in parallel to the direction opposite to the transmission line TLa through which the true signal flows. .

  Hereinafter, embodiments of the phase shifter and the phased array antenna will be described in detail with reference to the accompanying drawings.

FIG. 9 is a diagram for explaining an embodiment of the phase shifter.
As shown in FIG. 9, the phase shifter P of the present embodiment is a current amplifier having a gain of 1 with respect to the input end of the transmission line TLa that transmits a true signal among the coupled transmission lines TLa and TLb. gm amplifier) A local signal LO (or high frequency signal RF) is supplied via Aa. Further, a local signal LO (or a high frequency signal RF) is supplied to a transmission line (phase adjustment transmission line) TLb arranged in parallel with the transmission line TLa via a current amplifier Ab having a gain of k. .

  Here, a load L is provided at the output end of the phase adjustment transmission line TLb. In addition, the load L can be comprised by a capacity | capacitance or resistance, for example.

  The phase shifter P of this embodiment shown in FIG. 9 propagates the local signal LO or the high frequency signal RF to the coupled transmission lines TLa and TLb via the current amplifiers Aa and Ab, and transmits a true signal by mutual inductance. The phase shift is controlled at the output end of the transmission line TLa.

At this time, the signal propagation speed V (V ′) is proportional to V′∝ ((L + kM) C) ^−1/2 , unlike V∝ (LC) ^−1/2 . M represents the mutual inductance between the coupled transmission lines, and k represents the sign and strength of the current flowing through the phase adjustment transmission line TLb.

  Thus, according to the phase shifter of the present embodiment, for example, signals that are 90 ° different in phase are not required, and only a differential signal is required. And according to the phase shifter of a present Example, the signal which has arbitrary phase differences with respect to a true signal can be produced | generated by the structure of said coupling transmission line TLa, TLb and current amplifier Aa, Ab. it can.

  As described above, only a differential signal is sufficient to generate a signal having an arbitrary phase, and there is no frequency limitation on the coupled transmission line.

  FIG. 10 is a diagram for explaining the operation of the phase shifter of FIG. Here, FIG. 10A shows the time change of the output voltage of the signal at the output end of the transmission line TLa that transmits a true signal when different currents are passed through the phase adjustment transmission line TLb. 10 (b) shows the relationship between the magnitude of the current flowing through the phase adjustment transmission line TLb and the phase difference of the signal at the output end of the transmission line TLa that transmits the true signal.

  When no current is passed through the phase adjusting transmission line TLb in FIG. 10A (curve C0), when a current of 4 mA is passed (curve C4), when a current of 8 mA is passed (curve C8),... , When a current of 20 mA is applied (curve C20), when a signal in phase with the true signal in the transmission line TLa is applied to the phase adjustment transmission line TLb, the phase adjustment transmission is performed. It can be seen that the true signal phase at the output end of the transmission line TLa is delayed as the current (in-phase current) flowing through the line TLb increases.

  When a signal having a phase opposite to that of the true signal in the transmission line TLa is supplied to the phase adjustment transmission line TLb, as the current flowing in the phase adjustment transmission line TLb (an opposite phase current) increases. The phase of the true signal at the output end of the transmission line TLa advances.

  That is, as shown in FIG. 10B, by changing the direction and magnitude of the current flowing through the phase adjustment transmission line TLb, the true signal at the output end of the transmission line TLa is transmitted to the phase adjustment transmission line. The phase of the signal can be arbitrarily set (so as to have various phase delays and leads) with respect to the case where no current is passed through the line TLb.

  In FIG. 10, as an example, a simulation result when a 60 GHz signal is given to two microstrip lines having a width of about 5 μm arranged in parallel by a length of about 4 mm at intervals of about 5 μm. This shows that by changing various conditions such as the frequency of the signal to be used, the configuration of the coupled transmission line arranged in parallel, and the magnitude of the current flowing through the phase adjustment transmission line TLb, Needless to say, this embodiment can be widely applied.

  FIG. 11 is a diagram showing an embodiment of a phased array antenna, and FIG. 12 is a diagram for explaining the phased array antenna of FIG.

  As shown in FIG. 11, the phased array antenna according to the present embodiment includes a CPU 211, a memory (MEM) 212, a digital / analog converter (DAC) 213, RF provided on a semiconductor integrated circuit device (monolithic IC) 210. The front end unit 214, the matching unit 215, and the patch antenna 220 provided outside the semiconductor integrated circuit device 210 are provided.

  The phased array antenna shown in FIG. 11 is configured such that a patch antenna (antenna unit) 220 is provided outside the semiconductor integrated circuit device 210. However, the phased array antenna of the present embodiment has an antenna connected to the semiconductor integrated circuit device 210. The unit can also be formed integrally.

  FIG. 12 is a diagram showing an embodiment in which a phased array antenna is integrated with a semiconductor integrated circuit device.

  As shown in FIG. 12A, the phased array antenna of this embodiment is configured such that a patch antenna 221 is formed on a semiconductor integrated circuit device 210.

  Further, as shown in FIG. 12B, the phased array antenna of this embodiment can also form a monopole antenna 222 on the semiconductor integrated circuit device 210.

  Further, as shown in FIG. 12C, the phased array antenna of this embodiment may form a MEMS antenna 223 on the semiconductor integrated circuit device 210.

  Thus, by forming each antenna (a plurality of antenna units) integrally on the semiconductor integrated circuit device 210, the phased array antenna can be further reduced in size.

  FIG. 13 is a diagram schematically showing the RF front end unit 214 in one embodiment of the phased array antenna.

  Here, reference numerals 431a to 435a and 431b to 435b in FIG. 13 correspond to the current amplifiers Aa and Ab in FIG. 9, and reference numerals 441a to 445a and 441b to 445b in FIG. Corresponding to the transmission line TLa and the phase adjusting transmission line TLb for transmission, reference numerals 451 to 455 in FIG. 13 correspond to the load (capacitance) L in FIG.

  As is clear from the comparison between FIG. 13 and FIG. 9 described above, the RF front end unit 214 includes, for example, five sets of the phase shifters P shown in FIG. 9 corresponding to the five antenna units, and the phase of each set. The phase and the magnitude of the current flowing through the adjustment transmission lines 441b to 445b (TLb) are changed, and different phases (for example, 60 °, 30 °, for example) from the output ends of the transmission lines 441a to 445a (TLa) that transmit true signals, respectively. , 0 °, −30 °, −60 °). The positive sign of the phase difference indicates that the true signal transmitted through the transmission lines 441a to 445a is delayed, and the negative sign of the phase difference indicates that the true signal transmitted through the transmission lines 441a to 445a is advanced. Yes.

  That is, as conceptually shown in FIG. 13, in the phase adjustment transmission lines 441b to 445b in each set of phase shifters, for example, the phase adjustment transmission line 441b has a transmission line 441a for transmitting a true signal. By flowing a large current (for example, currents of substantially the same magnitude) in the same direction, a signal supplied to the final stage amplifier 461 (PA) via the transmission line 441a is greatly delayed (for example, 60 °).

  In addition, for example, a small current (for example, about half of the current) flows in the phase adjustment transmission line 442b in the same direction as the transmission line 442a that transmits a true signal, so that the final amplifier 462 is transmitted via the transmission line 442a. Is slightly delayed (for example, 30 °), and the current supplied to the final amplifier 463 via the transmission line 443a is kept in phase by passing no current through the phase adjustment transmission line 442b. For example, 0 °).

  Then, for example, a small current (approximately half the current) is passed through the phase adjustment transmission line 444b in the opposite direction to the transmission line 444a that transmits a true signal, thereby passing through the transmission line 444a to the final amplifier 464. The supplied signal is advanced a little (for example, 30 °), and the phase adjusting transmission line 445b has a large current (for example, a current having substantially the same magnitude) in the opposite direction to the transmission line 445a that transmits the true signal. The signal supplied to the final stage amplifier 465 via the transmission line 445a is greatly advanced (for example, 60 °).

  The five signals having different phases obtained in this way are integrated with the semiconductor integrated circuit device via the final stage amplifiers 461 to 465 and the matching unit 215 or the like, or are supplied to the five antenna units provided outside thereof. Supplied.

  As is clear from FIG. 13, according to the phased array antenna of this embodiment, the mixer 42 is only required to add the LO signal (41) and the IF signal, that is, as shown in FIG. Unlike a phased array antenna, it is not necessary to provide each antenna unit.

  In FIG. 13, for example, the lengths of transmission lines (coupled transmission lines) 441a, 441b to 445a, 445b arranged in parallel to control the phase are set to 1 mm, and further, the adjacent final stage amplifiers 461 to 465 are arranged. When the interval between the output lines is 0.2 mm, the size occupied by the RF front end portion 214 can be approximately 1 mm × 1 mm. This means, for example, that the occupied area and the power consumption can be reduced to about half compared to the case where a plurality of signals having different phase differences as shown in FIG. 5 are generated by vector synthesis.

  FIG. 14 is a flowchart for explaining an example of the control process of the phased array antenna. As an example, the control process when the phased array antenna is mounted as an in-vehicle radar is described. Here, the CPU includes an omnidirectional scan mode for searching for an obstacle and a specific location scan mode for obtaining detailed information of the obstacle when the obstacle is found.

  That is, as shown in FIG. 14, the control processing of the phased array antenna starts with the omnidirectional scan in step ST1 or the specific location scan in step ST2 of the electromagnetic wave beam radiated from the phased array antenna in step ST3. Determine the radiation angle.

  Furthermore, it progresses to step ST4, the electric current value (logic) with respect to the radiation angle of the electromagnetic wave beam radiated | emitted from a phased array antenna is determined, and it progresses to step ST5. The determination of the current value with respect to the radiation angle in step ST4 is performed by referring to a memory (MEM) provided with a table of the current intensity and the phase difference of the generated signal.

  In step ST5, the current value (logic) is converted into a current value (analog). That is, the CPU controls the digital / analog converter (DAC) to generate a phase difference between signals radiated from each antenna unit in accordance with the table referenced in step ST4.

  In step ST6, each current amplifier is controlled by the current value (analog). That is, by activating the current amplifier in the RF front end unit, a signal having a phase difference required by each antenna unit is obtained at the output end of the transmission line TLa that transmits a true signal in the coupled transmission line. The current amplifier of the transmission line TLa that transmits the true signal and the current amplifier of the phase adjustment transmission line TLb are controlled.

  Each signal having a required phase difference (a signal at the output end of the transmission line TLa) is radiated from each antenna unit via a final amplifier PA, and the signals are spatially synthesized to radiate an electromagnetic wave beam. The angle is controlled.

  Here, as described above, each antenna unit can be provided outside the semiconductor integrated circuit device (monolithic IC), but can also be provided integrally within the IC.

  In addition, the above-described phase shifter is applied to, for example, a phased array antenna that is an antenna of an electronic scan radar mounted on a vehicle, that is, an electromagnetic wave beam by spatially combining energy radiated from a plurality of antenna units. As an example, the phase shifter of the present embodiment is not limited to the phased array antenna, and generates a signal having a predetermined phase difference with respect to the true signal. Therefore, it can be widely applied to various circuits or devices.

Regarding the embodiment including the above examples, the following supplementary notes are further disclosed.
(Appendix 1)
A first transmission line for transmitting a signal having a first frequency;
A second transmission line, a current flowing through the second transmission line having the first frequency, and controlling the current to adjust a phase of the signal transmitted through the first transmission line. Phaser.

(Appendix 2)
In the phase shifter described in appendix 1,
The second transmission line is a phase shifter arranged in parallel with the first transmission line.

(Appendix 3)
In the phase shifter according to appendix 1 or 2,
The control of the current is a phase shifter that controls the direction and magnitude of the current flowing through the second transmission line.

(Appendix 4)
In the phase shifter described in appendix 3,
A first current amplifier for flowing a true signal to the first transmission line;
A phase shifter comprising: a second current amplifier configured to flow the current according to a phase difference required for the second transmission line.

(Appendix 5)
In the phase shifter described in appendix 4,
A phase shifter comprising a load element provided at the other end of the second transmission line, the second current amplifier being connected to one end.

(Appendix 6)
A plurality of antenna units arranged at a predetermined interval; and a plurality of phase shifters for controlling the phases of signals supplied to the respective antenna units. A phased array antenna which is the phase shifter according to claim 1.

(Appendix 7)
In the phased array antenna according to attachment 6,
The plurality of antenna units are phased array antennas formed outside a semiconductor integrated circuit device in which the plurality of phase shifters are formed.

(Appendix 8)
In the phased array antenna according to attachment 6,
The plurality of antenna units are phased array antennas formed on the semiconductor integrated circuit device integrally with the semiconductor integrated circuit device in which the plurality of phase shifters are formed.

(Appendix 9)
In the phased array antenna according to any one of appendices 6 to 8,
The phased array antenna is a phased array antenna that is an antenna of an electronic scanning radar.

It is a figure for demonstrating the relationship between the radiation angle in a phased array antenna, and a feed phase. It is a figure which shows an example of the conventional phase shifter. It is a circuit diagram which shows the other example of the conventional phase shifter. It is a circuit diagram which shows the other example of the conventional phase shifter. It is a figure which shows an example of the conventional phased array antenna. It is a figure which shows a transmission line schematically. It is a figure which shows a coupling transmission line schematically. It is a figure for demonstrating the relationship between a coupled transmission line and an electric current. It is a figure for demonstrating the phase shifter which concerns on this embodiment. It is a figure for demonstrating the operation | movement in the phase shifter of FIG. It is a figure which shows one Example of a phased array antenna. It is a figure which shows the Example which integrated the phased array antenna with the semiconductor integrated circuit device. It is a figure which shows schematically the RF front end part in one Example of a phased array antenna. It is a flowchart for demonstrating an example of the control processing of a phased array antenna.

Explanation of symbols

DESCRIPTION OF SYMBOLS 1 Phased array antenna 10a, 10b Weighting circuit 10c Adder circuit 10, 20, 30, P Phase shifter 20a-20c; 30a-30c Inductor 20d-20f Variable capacity 30d-30f Capacity 30g Switch circuit 41 LO signal (local signal)
42 mixer 100 signal source 111-115 phase shifter 121-125, 461-465 amplifier (final stage amplifier)
131 to 135 Antenna unit 210 Semiconductor integrated circuit device (monolithic IC)
211 CPU
212 Memory (MEM)
213 Digital / analog converter (DAC)
214 RF front end section 215 Matching section 220, 221 Patch antenna 222 Monopole antenna 223 MEMS antenna 431a-435a, 431b-435b, Aa, Ab Current amplifier (gm amplifier)
441a to 445a, TLa Transmission line for transmitting a true signal (coupled transmission line)
441b to 445b, TLb Phase adjustment transmission line (coupled transmission line)
451-455 L Load (capacity)
P phase shifter

Claims (5)

A first transmission line for transmitting a signal having a first frequency;
A second transmission line, a current flowing through the second transmission line having the first frequency, and controlling the current to adjust a phase of the signal transmitted through the first transmission line. Phaser. The phase shifter according to claim 1, wherein
The second transmission line is a phase shifter arranged in parallel with the first transmission line. The phase shifter according to claim 1 or 2,
The control of the current is a phase shifter that controls the direction and magnitude of the current flowing through the second transmission line. The phase shifter according to claim 3, further comprising:
A first current amplifier for flowing a true signal to the first transmission line;
A phase shifter comprising: a second current amplifier configured to flow the current according to a phase difference required for the second transmission line.   A plurality of antenna units arranged at a predetermined interval, and a plurality of phase shifters for respectively controlling phases of signals supplied to the respective antenna units, wherein each of the phase shifters comprises: A phased array antenna, which is the phase shifter according to any one of the above items.

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