JP2009135999A - Orthogonal frequency division multiplexing device and orthogonal frequency division multiplexing method - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To compensate deterioration in modulation characteristics caused by the difference in the operation time of in-phase and orthogonal signals in a digital orthogonal modulator. <P>SOLUTION: A transmission signal generating device has: a signal point setting means 12 for setting a compensation signal point for correcting a position error in signal point arrangement caused by an operation timing error in a digital orthogonal modulator according to the position error in signal point arrangement; and a data mapping means 11 for allocating a digital information signal to be transmitted based on the signal point setting means. Based on the signal point information allocated by the data mapping means, digital modulation 13 and digital orthogonal modulation 15 are performed in the transmission signal generating device. <P>COPYRIGHT: (C)2009,JPO&INPIT

Description

  The present invention relates to an orthogonal digital modulation system that modulates two orthogonal digital information signals with one carrier, and more particularly, an orthogonal modulation signal that generates distortion such as interference and crosstalk between the two modulated digital information signals. The present invention relates to a method for compensating for a phase error, and an orthogonal frequency multiplex division apparatus and an orthogonal frequency multiplex division method having means for compensating for the phase error.

  In recent years, with the advancement of digital signal processing technology, it has been desired to realize a high-efficiency digital modulation method for transmitting digital information with high efficiency for transmitting digital video and audio that have been highly-efficiently compressed and encoded. The high-efficiency digital modulation method is a modulation / demodulation method that can transmit a digital signal having as much information as possible within a predetermined frequency band with a small error rate.

  One of them is a two-phase modulation method that modulates one carrier signal with two types of information signals. The modulation method is used to transmit two color difference signals in the current NTSC analog television system. Two types of color signals are transmitted by one subcarrier.

  A method in which these two kinds of color signals are regarded as two kinds of digital signals and one subcarrier signal is modulated in the amplitude modulation direction and the phase modulation direction and transmitted is known as QAM (quadrature amplitude modulation). Yes.

  Here, a method of transmitting each of a large number of subcarriers by performing QAM modulation with a large number of two kinds of digital signals is called an orthogonal frequency division multiplexing modulation method (OFDM), and the frequency of the digital modulation signal made here Can be lowered by the number of subcarriers, so that even if a guard interval period is provided, a decrease in transmission efficiency can be kept small, and a wireless transmission path that is not affected by multipath distortion can be secured. .

  Since this OFDM system can reduce the frequency of the digital modulation signal, the transmission frequency spectrum can be made rectangular, and interference with adjacent channels can be reduced, thus realizing a highly efficient digital modulation system with good bandwidth utilization. it can.

  Realizing modulation schemes with these characteristics on a small circuit scale is important for mobile communication applications using these modulation schemes, and analog quadrature modulation circuits that have been conventionally used are digital quadrature modulation circuits. If this can be realized, the digitized modulation circuit can be made into an LSI, and the modulation circuit can be reduced in size and power consumption.

  In August 1999, the present applicant filed an application for digital quadrature modulation technology as “Orthogonal Frequency Division Multiplexing Modulation Method and Orthogonal Frequency Division Multiplexing Modulator” (Japanese Patent Application No. H11-238098). The multiplication of the sine wave and cosine wave performed in step 1 can be performed using values of 1, 0, and -1, and thus has a feature that the circuit configuration can be simplified.

JP-A-8-102766

By the way, digital quadrature modulators using LSIs that are small and power-saving in this way are suitable for miniaturization and power-saving of LSIs as the frequency of signals handled is small, and the operating frequency is made as low as possible. Although an attempt has been made to implement a circuit, in such a quadrature digital modulation circuit with a low frequency, an error is caused by setting the operating frequency low, and the characteristics of the modulation circuit are deteriorated.
The reason why the modulation characteristic deteriorates will be described.
In a multi-carrier transmission system typified by the OFDM transmission system, a signal that is in phase with a subcarrier and a signal that is orthogonal to the subcarrier are generated as time-series signals by inverse Fourier transform, and when these signals are generated A signal indicated by the series is supplied to a digital quadrature modulation circuit.

The in-phase signal and quadrature signal generated here are obtained as sampling data at the same time, and these signals are signals having a phase difference of 90 degrees from the signal corresponding to the modulation frequency in the digital quadrature modulator. Therefore, a timing phase difference corresponding to one sample of the signal expressing the modulation frequency is generated.
This timing phase difference is also described in JP-A-8-102766, a digital processing quadrature modulator, and a digital filter is used to realize a high-efficiency digital modulator to solve the problem of this timing phase difference. .
However, the digital filter that compensates for the timing phase difference generated in this way requires high-accuracy calculation, which increases the complexity and cost of the device. For example, when a digital filter is inserted only on the quadrature signal side, the timing phase difference can be absorbed, but it is difficult to flatten the amplitude frequency characteristic of the filter, and the digital modulation characteristic is deteriorated due to the disturbance of the amplitude characteristic. It has not been used effectively.

In order to solve the above-described problem, the orthogonal frequency division multiplexing apparatus according to the present invention provides a phase between an I signal that is a real part signal generated by digital quadrature modulation and a Q signal that is an imaginary part signal generated by digital quadrature modulation. A mapping table in which correction data for correcting the time error caused by the error and the amplitude error between the I signal and the Q signal is stored in advance, and the digital signal is input to perform predetermined digital modulation and the i signal And the q signal are generated, and the i signal and the q signal are corrected by correcting the time error and the amplitude error between the i signal and the q signal based on the correction data stored in the mapping table. Data mapping means, and the i signal and q signal output after correction from the data mapping means are subjected to fast inverse Fourier transform (IFFT) to obtain an I signal IFFT arithmetic means for outputting a Q signal, and the I signal and Q signal outputted from the IFFT arithmetic means are inputted, and the signal is digitally converted into a signal in a new frequency band centered on the frequency oscillated by the intermediate frequency oscillator. A digital quadrature modulation means for performing quadrature modulation and outputting a signal in a new frequency band; and a DA conversion means for performing DA conversion on the signal in the new frequency band output from the digital quadrature modulation means. It is an orthogonal frequency multiplexing division apparatus.
Here, the data mapping means may be an orthogonal frequency multiplex division apparatus that inputs digital data and performs predetermined QPSK modulation, multilevel PSK modulation, or multilevel QAM modulation to generate an i signal and a q signal. good.
Further, the orthogonal frequency division division method of the present invention inputs digital data and performs predetermined digital modulation to generate an i signal and a q signal, and based on the correction data stored in the mapping table, A time error caused by a phase error between an I signal that is a real part signal generated by digital quadrature modulation and a Q signal that is an imaginary part signal caused by digital quadrature modulation, and the amplitudes of the I signal and the Q signal Based on the correction data stored in the mapping table in which correction data for correcting the error is stored in advance, the i signal and q corrected for time error and amplitude error between the i signal and the q signal A signal, a step of fast inverse Fourier transform (IFFT) of the i signal and the q signal to output an I signal and a Q signal, and the I signal Inputting a Q signal, digitally quadrature-modulating a signal in a new frequency band centered on a frequency oscillated by the intermediate frequency oscillator, and outputting a signal in the new frequency band; and And a D / A conversion of the signal.
Here, the data mapping may be an orthogonal frequency division division method in which digital data is input and predetermined QPSK modulation, multilevel PSK modulation, or multilevel QAM modulation is performed to generate i and q signals. .

1 is a schematic block diagram of an orthogonal frequency division multiplexing modulator according to an embodiment of the present invention. It is a figure which shows the structure of an analog quadrature modulator. It is a figure which shows the structure of the quadrature modulator comprised with a digital circuit. It is a figure which shows the operation | movement timing of a digital quadrature modulator with a chart. It is a figure which shows the operation | movement timing of a digital quadrature modulator with a short sample period with a chart. The state of a subcarrier having an α phase angle and an amplitude of A rotating at an angular velocity + ω _n is shown in a two-dimensional plane with imaginary and real axes. Equations (6) to (9) indicating signal vectors are shown. The vectors of terms 61 and 63 in equation (6) are shown in a two-dimensional plane with imaginary and real axes. The vectors of terms 62 and 64 in equation (6) are shown in a two-dimensional plane with imaginary and real axes. The vectors of terms 72 and 74 in equation (7) are shown on a two-dimensional plane with imaginary and real axes. The vectors of terms 71 and 73 in equation (7) are shown in a two-dimensional plane with imaginary and real axes. It is a figure which shows the mapping point for obtaining the signal output of the angular frequency (omega) t compensated from the digital quadrature modulator. It is a figure which shows the mapping point for obtaining the signal output of the angular frequency -omegat compensated from the digital quadrature modulator. 10 is a table for obtaining a compensated mapping point when each of positive and negative subcarriers having the same frequency is modulated by the QPSK method and each carrier is designated with 4 signal points.

The embodiment of the present invention comprises the following means 1) to 5) in order to solve the above problems.
That is,

1) A two-dimensional plane having the real part signal and the imaginary part signal as axes is divided into a plurality of areas, and a central position for designating the area is determined as a signal point for each of the divided areas. The digital information signal to be transmitted is sequentially assigned to a specific signal point among the plurality of signal points according to the contents thereof, and a signal comprising a real part signal and an imaginary part signal at each of the sequentially assigned signal points In a transmission signal generation method for generating a transmission signal obtained by converting point information into a high-frequency signal by performing digital modulation and digital quadrature modulation,
A modulation signal point obtained by performing digital modulation and digital quadrature modulation on the signal point information assigned to the signal point position is used as a compensation signal point at a point target position with respect to the signal point position. A first step (12) for defining;
A second step (11) for assigning the digital information signal to be transmitted to the compensation signal points defined in the first step;
A transmission signal comprising at least a third step (13, 15) for generating a high-frequency signal by digital modulation and digital quadrature modulation of signal point information at the compensation signal point allocated in the second step Generation method.

2) The position of the compensation signal point in the first step depends on the phase difference, amplitude difference between the in-phase signal and the quadrature signal generated by the digital modulation and digital quadrature modulation, or the quadrature difference of the digital quadrature modulator. A method of generating a transmission signal, characterized in that the position is a signal point compensated for an error that occurs.

3) The position of the compensation signal point in the first step is a position of a signal point that compensates for an error caused by a difference in timing between the in-phase signal and the quadrature signal processed by the digital quadrature modulation. A transmission signal generation method.

4) A two-dimensional plane having the real part signal and the imaginary part signal as axes is divided into a plurality of areas, and a central position for designating the area is determined as a signal point for each of the divided areas. The digital information signal of the first system to be transmitted is sequentially assigned to specific signal points among the plurality of signal points according to the contents, and the real part signal and the imaginary part signal at each of the sequentially assigned signal points, The first signal point information is generated as the first modulated signal by the first carrier frequency, and the second digital information signal to be transmitted is selected from among the plurality of signal points according to the contents thereof The second signal point information consisting of the real part signal and the imaginary part signal at each of the assigned signal points is assigned to the second signal point information having the same frequency and the same polarity as the first carrier frequency. 2 Using digital modulation means that generates as a second modulation signal by the carrier frequency,
In a transmission signal generation method for generating a transmission signal obtained by digitally quadrature-modulating the first and second modulation signals generated by the digital modulation means and converting into a high-frequency signal,
First and second obtained by performing digital modulation and digital quadrature modulation on the signal point information assigned to the position of each signal point related to the first and second digital information signals to be transmitted A first step (12) for defining a modulation signal point as a first and second compensation signal point at a position to be pointed with respect to the position of each signal point;
A second step (11) for assigning the first and second systems of digital information signals to be transmitted to the first and second compensation signal points determined in the first step;
At least a third step (13, 15) for generating the high-frequency signal by digitally and digitally modulating each signal point information at the first and second compensation signal points assigned in the second step. A method of generating a transmission signal, comprising:

5) A two-dimensional plane having the real part signal and the imaginary part signal as axes is divided into a plurality of areas, and a central position for designating the area is determined as a signal point for each of the divided areas. The digital information signal to be transmitted is sequentially assigned to a specific signal point among the plurality of signal points according to the contents thereof, and a signal comprising a real part signal and an imaginary part signal at each of the sequentially assigned signal points In a transmission signal generation device that generates a transmission signal obtained by converting point information into a high-frequency signal by performing digital modulation and digital quadrature modulation,
A modulation signal point obtained by performing digital modulation and digital quadrature modulation on the signal point information assigned to the signal point position is used as a compensation signal point at a point target position with respect to the signal point position. Compensation signal point setting means (12) to be determined;
Mapping means (11) for assigning the digital information signal to be transmitted to the compensation signal points set by the compensation signal point setting means;
High-frequency signal generation means (13, 15) for generating a high-frequency signal by digitally and digitally quadrature-modulating signal point information at the compensation signal point assigned by the mapping means, and generating a transmission signal apparatus.

Hereinafter, preferred embodiments of the transmission signal generation method and the transmission signal generation apparatus according to the present invention will be described.
FIG. 1 is a schematic configuration of an orthogonal frequency division multiplex modulation apparatus according to the embodiment, and the configuration and operation will be outlined.

  This orthogonal frequency division multiplex modulation apparatus includes a data mapping circuit 11, a mapping table 12, an IFFT arithmetic circuit 13, a digital orthogonal modulation circuit 15, an intermediate frequency oscillator 16, and a DA converter 17.

  The operation of the orthogonal frequency division multiplex modulation apparatus configured as described above will be described. Digital data to be modulated is supplied to the data mapping circuit 11, where the data is transmitted from each carrier wave constituting the orthogonal frequency division multiplex signal. Of which carrier wave is allocated and transmitted, the position of signal points of the carrier wave to be QAM modulated is determined according to the value of the digital data to be modulated for each carrier wave, and the position of these signal points Signals i and q corresponding to the position in the amplitude direction and the angle direction corresponding to are generated and supplied to the IFFT arithmetic circuit 13.

Here, according to the supplied signals i and q, each carrier wave constituting orthogonal frequency division multiplexing is subjected to orthogonal frequency modulation at a given signal point position, and each carrier wave is synthesized as a real part signal R and an imaginary part signal I. The obtained baseband signal outputs are obtained, and these baseband signal outputs are supplied to the digital quadrature modulator 15.
Here, the real part signal R and the imaginary part signal I, which are the baseband signal outputs, are converted into signals in a frequency band centered on the frequency oscillated by the intermediate frequency oscillator 16 and converted into signals in a new frequency band. The digital quadrature modulation signal is converted into an analog signal by the DA converter 17 and output.

  Here, the mapping table 12 connected to the data mapping circuit 11 is a table in which data for correcting characteristic errors caused by a digital quadrature modulator described later is stored in advance. The characteristic error of the digital quadrature modulator is corrected by correcting the mapped signal according to a predetermined law, thereby realizing a digital modulation device with good characteristics.

  The transmission signal generated in this manner is supplied to a receiving device, and the supplied high-frequency signal is demodulated to obtain the transmitted signal point information, and the transmitted digital signal is transmitted from the obtained signal point information. The information signal is decoded and obtained.

Here, a change in characteristics caused by the digital quadrature modulation circuit will be described by comparison with a conventionally used analog quadrature modulator.
First, in the case of a conventional analog quadrature modulator, a signal output from the IFFT calculator 13 in the form of a digital signal is converted into an analog signal by a DA converter 17 in the analog quadrature modulator. A signal is supplied, and the supplied signal is converted into a signal in a frequency band centered on an intermediate frequency oscillation frequency supplied from an intermediate frequency oscillator.

FIG. 2 shows a circuit of the analog quadrature modulator.
In the figure, for example, the baseband signal supplied from the IFFT calculator 13 is converted into an analog signal by the DA converter 17, and the converted real part signal R has an angular frequency ωt supplied from the intermediate frequency oscillator 16. The cosine signal is multiplied by a 90-degree phase shifter with a sine wave signal whose angular frequency is ωt, and the imaginary part signal (I) converted into an analog signal has an angular frequency supplied from the intermediate frequency oscillator 16 of ωt. The arithmetic outputs obtained from these two multipliers are added by an adder and output as a quadrature modulation output signal.

  Here, the sine wave output signal corresponding to the cosine wave output signal supplied from the intermediate frequency oscillator is generated by using a 90 degree phase shifter, and the characteristics of the 90 degree phase shifter are circuit constants of analog circuits constituting them. The characteristics are likely to fluctuate due to fluctuations, and the analog multipliers also tend to fluctuate in high frequency characteristics, making it difficult to obtain a stable quadrature modulation output signal over a long period of time. It has been desired to realize a difficult digitized quadrature modulation circuit.

FIG. 3 shows a configuration of a quadrature modulator constituted by a digital circuit.
In the figure, I is a real part signal supplied from IFFT 13, Q is an imaginary part signal, and each I and Q signal is indicated as an amplifier having an amplification factor of 1 and an amplification factor of -1. The four signals I, -Q, -I, and Q are obtained from these amplifiers.

  These four signals are supplied to the data selector, and the data selector outputs the four signals while sequentially switching them according to the period of the oscillation frequency supplied from the intermediate frequency oscillator. That is, the operation of outputting signal I first, then -Q, next -I, and finally Q is repeated.

FIG. 4 shows a timing chart of the digital quadrature modulator operating in this way.
In the figure, the time interval described as the sampling period is a period corresponding to the sampling frequency of the orthogonal frequency division multiplexed signal, and the period corresponds to 1 / n of the window period for operating the n-point IFFT circuit.

  In this figure, the signal circle 1 is indicated by a subscript with the real part output signal from the IFFT calculator 13 as I and the calculation intervals in units of sample periods as n−1, n, n + 1. Similarly, the imaginary part output signal Q from the IFFT calculator 13 is shown with the same subscripts of n-1, n, n + 1.

A signal circle 3 indicates a signal I when the signal I is amplified by an amplifier and an inverted and amplified signal -I are switched a plurality of times within a sample period by the data selector. _{I n, 0, -I n,} 0, I n ,, 0, -I n, are repeated as ..., the signal is 90 degrees every other value of the cosine function I _n, 1, It is a value obtained by multiplying 0, −1, 0,.

Similarly, the signal circle 4 is 0, −Qn, 0, Qn, 0, −Qn, 0,.
The signal circle 3 is obtained by adding the signal circle 3 and the signal circle 4 obtained in this way, and the signal circle 5 is I _n , −Q _n , −I _n , Q _n , I _n , −Q _n. , −I _n ,..., And this is an output signal of this quadrature modulator.

  Here, as shown in this example, when a signal is repeatedly switched many times within one sample period, the difference in modulation characteristics given to the I and Q signals due to the switching order of the signal is small, but the sample period is If the number of signal switching repetitions cannot be made many times in the case of a small time, there will be a difference in the characteristics of the modulation signal obtained from the digital quadrature modulation circuit, and signal processing to correct the difference characteristics Is required.

The present embodiment realizes a digital quadrature modulator with good characteristics by correcting such a difference in characteristics. The correction of the characteristics is performed by the signal appearing at the start point of the sample period in FIG. The signal phase shift related to the time error caused by the real part signal always appearing before the imaginary part signal so that the real part signal I _n and then the imaginary part Q _n signal appear. It compensates for the difference in characteristics due to.

  The data mapping circuit 11 defines the characteristic deviation in the digital modulation signal output caused by such a time difference, corrects the relationship between the i signal and q signal supplied to the IFFT, performs IFFT conversion with the corrected signal, The digital quadrature modulated modulation signal is compensated so as to become a regular modulation signal.

  That is, the difference in characteristics caused by the time difference between the I signal and the Q signal generated in the digital quadrature modulator at this time is a timing error of the sine wave of the digital quadrature modulation unit, and as a result, I, Q for the quadrature modulated signal. It is also an error for the orthogonality of the signal vector. This orthogonality error is caused by the sidebands of the modulated signal that are separated from each other by the same frequency, positive and negative, with respect to the frequency of the intermediate frequency oscillator. The signal leaks as a crosstalk component, and the frequency spectrum component of the modulated wave signal changes, so that the leaked signal level is canceled out.

This crosstalk component also exists from a negative frequency sideband to a positive frequency sideband.
Therefore, the data mapping characteristic that corrects these crosstalk in advance has the same frequency difference with respect to the center carrier, and the data mapping characteristics are also applied to the subcarriers corresponding to the phases having different polarities. It is necessary to perform characteristic compensation.

  As a method of performing signal point arrangement in data mapping for generating a modulation signal having a frequency that is a positive / negative pair, for example, when the signal point arrangement is expressed by coordinates on a complex plane, the real part signal and the imaginary part signal are in phase with each other. For a signal to be assigned with equal (1, 1), the real part signal is given x and the imaginary part signal is given y different coordinates as in (1 + x, 1 + y).

In this way, the real part and imaginary part signals for the corresponding subcarriers having positive and negative frequencies are expressed as follows.
(Real number of positive frequency, imaginary number of positive frequency, real number of negative frequency, imaginary number of negative frequency) = (d1 + x, d2 + y, d3 + x ′, d4 + y ′)

Here, d1, d2, d3, and d4 are values for giving a regular signal point arrangement. For example, in the case of a digital modulation system based on QPSK (quadrature phase shift keying), these d1, d2, d3, and d4 are Takes a value of either +1 or -1.
The values of the compensation signals indicated by x, x ′, y, and y ′ will be described in detail.

  Further, as shown in FIG. 4 described above, the output signal circle 5 of the quadrature modulator is the hardware that controls the operation of the digital quadrature modulator at the position where the I and Q signals appear relative to the start position of the sample period. Or the configuration of the control program software for controlling the operation of the digital modulator, and the order is generally fixed.

For example, there is a method in which the appearance order is random, but in this case, the difference in characteristics as described above is obtained as noise with respect to the modulation signal, which is not preferable.
In addition, there is a method of reversing the appearance order of the I signal and the Q signal. In this case, an error signal having a reverse polarity is generated, and in any case, the modulation signal needs to be compensated.

  As described above, since the I signal and Q signal, which are data at the same time, are processed by the digital quadrature modulator as data at different times, the orthogonality of the R signal and the I signal is one sample time of the modulation frequency. It will be different by the amount, and it is necessary to compensate for the time difference.

  Compensation of the time difference at this time has a small sample period, and when the digital modulation circuit cannot take many I / Q signal switching repetitions within that period, the ratio of the appearance time difference of the I and Q signals to the sample period increases. Also, the modulation error compensation signal level increases.

FIG. 5 shows a specific example of the operation.
In the figure, the sample period is 19.5 nsec, that is, the sample frequency is 51.2 MHz, and the IFFT arithmetic circuit calculates the real part signal circle 1 which is the calculation result and the signal circle 2 which is the imaginary part signal every 19.5 nsec. Output.

I _n , I _{n + 1} , I _{n + 2} , I _{n + 3} ,..., And Q _n , Q _{n + 1} , Q _{n + 2} , Q obtained at every sample period of this IFFT arithmetic circuit _{n + 3} ,... are regarded as sampling data of the modulation signal, that is, the sampling data is a baseband signal including a signal component from DC to a maximum of 16 MHz, and this signal component is used as the oscillation frequency of the intermediate frequency oscillator. To a signal in a frequency band centered on 25.6 MHz.

  The band of the frequency-converted signal at this time is 25.6 ± 16 MHz, the sampling frequency of the converted data string is 102.4 MHz, and the orthogonality error generated at this time is about 9.8 ns ( 1 / 102.4 MHz).

  Therefore, this orthogonality error is a phase delay of π / 4 radians for a subcarrier having a frequency of 38.4 MHz, which is 12.8 MHz higher than the center frequency of 25.6 MHz. For subcarriers with a frequency of .8 MHz lower, the phase advance is π / 4 radians, and the digital quadrature modulation circuit needs to be equipped with a compensation function for correcting the phase difference generated in this way.

Here, the necessary compensation amount will be described.
First, the compensation amount is expressed by a two-dimensional plane composed of a real axis and an imaginary axis.
FIG. 6 shows a state of a subcarrier having a phase angle of α, rotating at an angular velocity + ω _n and having an amplitude of A on a two-dimensional plane with imaginary and real axes.
That is, the subcarrier signal is expressed as shown in Equation (1).
A × cos (+ ω _n t + α) + j × A × sin (+ ω _n t + α) (1)

  Here, when the subcarrier is QPSK (quadrature phase shift keying), A is 1.41 (square root of 2), and α is π / 4, 3π / 4, 5π / 4, 7π / 4. Take one of the values.

Similarly, a subcarrier signal that rotates at an angular velocity of −ω _n , an amplitude of B, and a phase angle of β is expressed as Equation (2).
B × cos (−ω _n t + β) + j × B × sin (−ω _n t + β) (2)

Here, subcarriers when there is an error in the amplitude and phase of the imaginary part signal with respect to the real part signal will be described. That is, the amplitude change of the imaginary part signal is λ times and the phase angle deviation is γ radians.
Subcarrier angular velocity at this time is + omega _n in equation (3) shows a subcarrier angular velocity is - [omega] _n in formula (4).

A × cos (+ ω _n t + α) + j × λ × A × sin (+ ω _n t + α−γ) (3)
B × cos (−ω _n t + β) + j × λ × B × sin (−ω _n t + β + γ) (4)
Here, γ is a calculation error generated based on the above-described sampling period (about 9.8 ns), and this error needs to be compensated.

Next, these subcarrier signals are represented by an exponential function and will be further described.
First, when Expression (1) is expressed by an exponential function, Expression (5) is obtained.
(A + jb) × e ^j ω ^nt (5)
Here, a = A × cos α and b = A × sin α.

Next, when the trigonometric function of Expression (3) is expanded and expressed by an exponential function, Expression (6) shown in FIG. 7 is obtained. Similarly, expression (4) is developed to obtain expression (7) shown in FIG.
Each of these formulas is composed of four terms 61, 62, 63, 64 and 71, 72, 73, 74.

In equation (6), terms 61 and 63 are vectors rotating at an angular velocity ωt, and the vectors are shown in FIG.
In the figure, the vector 61 has an amplitude (vector length) of A / 2 and the angle from the real axis is shown as α, and similarly, the vector 63 has an amplitude of λ × A / 2 and a real axis. The angle from is α−γ.

  Thick lines 62 and 64 shown in FIG. 9 are vectors rotating at an angular velocity of −ωt, and the angle from the real axis is the vector 62 −α, and the vector 64 is a negative vector having an angle of − (α−γ). There is a second quadrant vector.

Also, the vector 72 in FIG. 10 and the vector 71 in FIG. 11 represent the real part signal, and the vector 73 in FIG. 11 and the vector 74 in FIG. 10 represent the imaginary part signal.
Similarly, in Equation (7), terms 71 and 73 are vectors that rotate at an angular velocity of -ωt, and the vectors are shown in FIG.

Also, terms 72 and 74 in equation (7) are vectors that rotate at the angular velocity ωt, and the vectors are shown in FIG.
The vector 61 in FIG. 8 and the vector 62 in FIG. 9 represent the real part signal of the above-described equation 1, and the vector 63 in FIG. 8 and the vector 64 in FIG. 9 represent the imaginary part signal.

In this way, the error of the modulation signal caused by the fact that the computation time is not the same between the real part signal and the imaginary part signal of the digital quadrature modulator is represented by terms 63 and 64 in Equation 6 and λ is a number other than 1. It was described that γ takes a number other than 0.
Compensating the error of the modulation signal based on the operation timing of the digital quadrature modulator is to provide means for canceling such an error generated in the digital quadrature modulator, and the method will be described next.

Specifically, if a signal having an amplitude of 1 / λ times and a phase advanced by γ is given to the term 63, the amplitude is multiplied by λ by the digital quadrature modulator and the phase is delayed by γ. Thus, a signal in which λ and γ are eliminated is obtained.
It is the equation (8) for the equation (6) shown in FIG. 7 and the equation (9) for the equation (7) that gives such a signal for compensating λ and γ. .

  It is a signal having a characteristic in which the amplitude λ and the phase angle γ are canceled with respect to the characteristics according to the above equations (3) and (4), and the digital quadrature modulation is given by the above equations (1) and (2). This is because an error signal component generated by signal processing of the real part and the imaginary part at different times by a digital quadrature modulator is equivalently canceled. .

FIG. 12 shows mapping points for obtaining a signal output of the angular frequency ωt compensated by the digital quadrature modulator.
In the figure, but is seeking a vector 101 to be set by combining the vector of 81,83,92,94, vector 81 and 83, a term containing e ^j omega ^t in equation (8), the vector 92 and 94 is such that in the section including e ^j omega ^t in equation (9), the vector 101 is obtained by combining the vector rotating at an angular velocity + .omega.t.

  That is, the vector 101 is obtained by synthesizing both a vector obtained by synthesizing the vector 81 and the vector 92 and a vector obtained by synthesizing the vector 83 and the vector 94, and the obtained vector 101 is expressed by the angular velocity ωt. This is the correction position of the signal point to be given to the rotating subcarrier.

FIG. 13 shows mapping points for obtaining a signal output having an angular frequency −ωt compensated by the digital quadrature modulator.
In the figure, signal points 102 to be set (8), which was determined by combining the vectors 82,84,91,93 corresponding to the term including e ^-j omega ^t in (9), angular This gives a corrected signal point for modulating the subcarrier rotating at the frequency −ωt.

In this way, the subcarrier whose angular frequency is ω _n
A × cos (+ ω _n t + α) + j × A × sin (+ ω _n t + α)
And subcarrier B × cos (−ω _n t + β) + j × B × sin (−ω _n t + β) whose angular frequency is −ω _n
To obtain a subcarrier whose angular frequency is ω _n
A × cos (+ ω _n t + α) + j × (1 / λ) × A × sin (+ ω _n t + α + γ)
A subcarrier having an angular frequency of −ω _n is represented by B × cos (−ω _n t + β) + j × (1 / λ) × B × sin (−ω _n t + β−γ).
Thus, the amplitude and phase of the Q signal may be corrected.

Next, when subcarrier signal components related to each frequency + ω _n are selected in the above-described equations (8) and (9), a combined signal of the selected signal components is obtained as follows.
(A / 2) × e ^j α + (B / 2) × e ^-j β + (1 / λ) × (A / 2) × e ^{j (} α ⁺ γ ⁾
− (1 / λ) × (B / 2) × e ^{-j (} β ^- γ ⁾
= (A / 2) × (cosα + jsinα) + (B / 2) × (cosβ−jsinβ)
+ (1 / λ) × (A / 2) × (cos (α + γ) + jsin (α + γ))
− (1 / λ) × (B / 2) × (cos (β−γ) −jsin (β−γ))
= (A / 2) × cosα + (B / 2) × cosβ + (1 / λ) × (A / 2) × cos (α + γ)
− (1 / λ) × (B / 2) × cos (β−γ) Expression (10)
+ J × ((A / 2) × sinα− (B / 2) × sinβ + (1 / λ) × (A / 2) × sin (α + γ)
+ (1 / λ) × (B / 2) × sin (β−γ))... Formula (11)

Similarly, subcarrier signal components related to each frequency −ω _n in equations (8) and (9) are selected, and a combined signal of the selected signal components is obtained as follows.
(B / 2) x e ^j β + (A / 2) x e ^-j α + (1 / λ) x (B / 2) x e ^{j (} β ^- γ ⁾
− (1 / λ) × (A / 2) × e ^{-j (} α ⁺ γ ⁾
= (B / 2) × (cosβ + jsinβ) + (A / 2) × (cosα−jsinα)
+ (1 / λ) × (B / 2) × (cos (β−γ) + jsin (β−γ))
− (1 / λ) × (A / 2) × (cos (α + γ) −jsin (α + γ))
= (B / 2) × cosβ + (A / 2) × cosα + (1 / λ) × (B / 2) × cos (β−γ)
− (1 / λ) × (A / 2) × cos (α + γ) (12)
+ J × ((B / 2) × sinβ− (A / 2) × sinα + (1 / λ) × (B / 2) × sin (β−γ)
+ (1 / λ) × (A / 2) × sin (α + γ)) (13)
It becomes.

here,
Equation (10) is a numerical value assigned to the real part of the + ω _n subcarrier component,
Equation (11) is a numerical value assigned to the imaginary part of the + ω _n subcarrier component,
Equation (12) is a numerical value assigned to the real part of the −ω _n subcarrier component,
Equation (13) is a numerical value assigned to the imaginary part of the −ω _n subcarrier component.

In this way, the signal levels of the real part component and the imaginary part component of the subcarriers whose angular frequencies are + ω _n and −ω _n were obtained.
However, since the error component of the digital quadrature modulator shown in FIG. 3 described above relates to the calculation time of the imaginary part signal, no error related to the amplitude occurs. Therefore, λ = 1 and γ has a predetermined value other than 0.

  When the digital quadrature modulator shown in this example is QPSK, A and B have the same value. Therefore, assuming that A = B, equations (10) to (13) can be expressed by equations (14) to (17), respectively. It becomes like this.

(A / 2) × (cosα + cosβ + cos (α + γ) −cos (β−γ)) (14)
+ J × (A / 2) × (sin α−sin β + sin (α + γ) + sin (β−γ)) (15)
(A / 2) × (cosβ + cosα + cos (β−γ) −cos (α + γ)) (16)
+ J × (A / 2) × (sinβ−sinα + sin (β−γ) + sin (α + γ)) (17)

  Further, the modulation angle given in the case of the QPSK modulation method is any one of four of π / 4, 3π / 4, 5π / 4, and 7π / 4, and the angles α and β are combinations of 4 × 4. Will be selected.

  The table shown in FIG. 14 shows that when the frequencies of such positive and negative subcarriers are modulated by the QPSK method, each carrier is designated with 4 signal points, and 16 types of cases can be classified. Are shown for each of the 16 types.

  That is, in the table, the four formulas in each frame indicate values corresponding to formulas (14), (15), (16), and (17) from the top, and γ represents each subcarrier. Different values are taken depending on the frequency.

  In this embodiment, in order to make the explanation easy to understand, the example applied to QPSK modulation is described. However, the modulation method is not limited to this, and it is needless to say that the present invention can be applied to BPSK modulation, multilevel QAM modulation, and the like.

  In addition, the compensation of the difference in characteristics due to the difference in the operation timing is not limited to the technique for multicarrier, but sets a positive frequency and a negative frequency with respect to the center carrier, The present invention can also be applied to a modulation scheme in which signal point arrangement is determined for each subcarrier frequency and information is transmitted.

  Further, in this embodiment, as an example when there is no amplitude error, the table shown in FIG. 14 is limited to λ = 1. However, even when there is an amplitude error, a setting for correcting the same is performed. The signal point to be obtained is obtained, and the phase difference can be compensated simultaneously with the amplitude difference.

  As described above, according to the apparatus of the present embodiment, the base part signals of the real part and the imaginary part obtained by digital quadrature modulation using, for example, IFFT are subjected to digital quadrature frequency division multiplexing modulation of the intermediate frequency band with the digital signal as it is. Even when the digital quadrature modulator alternately calculates the real part signal and the imaginary part signal from the IFFT arithmetic unit to generate a digital quadrature modulation signal, the real part signal and Since the error signal generated due to the difference in the calculation timing of the imaginary part signal is subjected to IFFT calculation by giving a signal point arrangement for canceling the calculation error when the signal of the real part and the imaginary part is generated in advance by IFFT, It is possible to obtain a stable and highly accurate digital orthogonal division multiplexed signal by digital quadrature modulation signal generation processing that does not include a signal.

  Furthermore, it is also possible to compensate for a position error caused by a phase difference, an amplitude difference between the in-phase signal and the quadrature signal generated by the digital modulation and the digital quadrature modulation, or a quadrature difference by the digital modulation and the digital quadrature modulation.

  Furthermore, the positional error caused by interference between two subcarriers set with the same frequency interval in the positive direction and the negative direction with respect to the center carrier used when transmitting the modulated signal is also shown in FIG. According to the table shown, the digital quadrature modulation signal compensated for the position error caused by the interference between both carriers by performing digital modulation using the mapping table value set according to the modulation signal given to the opposite subcarrier. Can be generated.

  Although the digital quadrature modulator in the above embodiment has been described as having a configuration in which digital modulation is performed using the data of the Q signal following the I signal, the signal processing sequence of the digital quadrature modulator performs arithmetic processing of the Q signal. The same effect can be obtained by performing the calculation processing using the I signal data first and then using the I signal data.

  According to one aspect of the present invention, the base part signals of the real part and imaginary part obtained by digital quadrature modulation using IFFT, for example, are converted into digital quadrature frequency division multiplex modulated signals in the intermediate frequency band without changing the digital signals. When the digital quadrature modulator generates a digital quadrature modulation signal by alternately calculating the real part signal and the imaginary part signal from the IFFT computing unit, the real part signal and the imaginary part signal Error signal generated due to difference in calculation timing is included in IFFT calculation by giving signal point arrangement for canceling the calculation error when generating signal of real part and imaginary part by IFFT in advance There is an advantage that it is possible to provide a method for obtaining a stable and highly accurate digital quadrature modulation signal by the digital quadrature modulation signal generation processing.

  According to another aspect of the present invention, in particular, a signal point arrangement caused by a position error caused by a phase difference, an amplitude difference between the in-phase signal and the quadrature signal generated by the digital quadrature modulation, or a quadrature difference by the digital quadrature modulation. In addition to the above-mentioned effects, stable and accurate digital quadrature that operates by compensating for the signal point position error that accompanies the operation error of the circuit of the actual digital quadrature modulator. There is an effect that a method for obtaining a modulation signal can be provided.

  According to another aspect of the present invention, since the error of the circuit operation inherently possessed by the digital quadrature modulator is compensated, in addition to the above effect, it occurs with the arithmetic processing operation possessed by the digital quadrature modulator. There is an effect that it is possible to provide a method of obtaining a stable and highly accurate digital quadrature modulation signal that operates by compensating for the error of the signal point position.

  In addition, according to another aspect of the present invention, position error compensation is performed also for two subcarriers arranged in the positive direction and the negative direction by the same frequency, particularly with respect to the center carrier frequency. In addition to the above effect, it is possible to provide a method for obtaining a stable and highly accurate digital quadrature modulation signal that operates by compensating for an error in signal point position caused by interference between two subcarriers arranged at the same frequency, positive and negative. effective.

  Further, according to another aspect of the present invention, the base part signal of the real part and the imaginary part obtained by digital quadrature modulation, for example, using IFFT, for example, is subjected to digital quadrature frequency division multiplex modulation of the intermediate frequency band while maintaining the digital signal Even when the digital quadrature modulator alternately calculates the real part signal and the imaginary part signal from the IFFT arithmetic unit to generate the digital quadrature modulation signal when converting to the signal, the real part signal and the imaginary number Since the error signal generated by the difference in the calculation timing of the partial signal is subjected to IFFT calculation by giving a signal point arrangement for canceling the calculation error when the signal of the real part and the imaginary part is generated in advance by IFFT, the error signal A transmission signal generation apparatus that generates a stable and accurate digital quadrature modulation signal by digital quadrature modulation signal generation processing can be configured. There is a result.

11 Data Mapping Circuit 12 Mapping Table 13 IFFT Operation Circuit 15 Digital Quadrature Modulation Circuit 16 Intermediate Frequency Oscillator 17 DA Converter

Claims (5)

A time error caused by a phase error between an I signal that is a real part signal generated by digital quadrature modulation and a Q signal that is an imaginary part signal caused by digital quadrature modulation, and the amplitudes of the I signal and the Q signal A mapping table in which correction data for correcting errors is stored in advance;
The digital data is input and predetermined digital modulation is performed to generate the i signal and the q signal, and the time between the i signal and the q signal is determined based on the correction data stored in the mapping table. Data mapping means for outputting an i signal and a q signal in which an error and an amplitude error are corrected;
IFFT operation means for outputting the I signal and the Q signal by performing a fast inverse Fourier transform (IFFT) on the i signal and the q signal that have been corrected and output from the data mapping means;
The I signal and Q signal output from the IFFT calculation means are input, digital quadrature modulation is performed on a signal in a new frequency band centered on the frequency oscillated by the intermediate frequency oscillator, and a signal in the new frequency band is obtained. Digital quadrature modulation means for outputting,
DA conversion means for DA-converting and outputting the signal of the new frequency band output from the digital quadrature modulation means;
An orthogonal frequency multiplexing and dividing apparatus. The orthogonal frequency division multiplexing apparatus according to claim 1, wherein
The data mapping means includes
An orthogonal frequency multiplex division apparatus that inputs digital data and performs predetermined QPSK modulation to generate an i signal and a q signal. The orthogonal frequency division multiplexing apparatus according to claim 1, wherein
The data mapping means includes
An orthogonal frequency multiplexing / dividing apparatus that inputs digital data and performs predetermined multilevel PSK modulation to generate an i signal and a q signal. The orthogonal frequency division multiplexing apparatus according to claim 1, wherein
The data mapping means includes
An orthogonal frequency multiplexing / dividing apparatus that inputs digital data and performs predetermined multilevel QAM modulation to generate an i signal and a q signal. Input digital data and perform predetermined digital modulation to generate i signal and q signal, and based on the correction data stored in the mapping table, I is a real part signal generated by digital quadrature modulation Correction data for correcting a time error caused by a phase error between the signal and a Q signal that is an imaginary part signal generated by digital quadrature modulation and an amplitude error between the I signal and the Q signal are stored in advance. Outputting an i signal and a q signal corrected for a time error and an amplitude error between the i signal and the q signal based on the correction data stored in the mapping table,
Performing an inverse Fourier transform (IFFT) on the i signal and the q signal to output an I signal and a Q signal;
Inputting the I signal and the Q signal, performing digital quadrature modulation on a signal in a new frequency band centered on the frequency oscillated by the intermediate frequency oscillator, and outputting a signal in the new frequency band;
DA converting the signal of the new frequency band;
An orthogonal frequency division division method comprising:

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