JP2008219665A - Orthogonal harmonic mixer - Google Patents

Orthogonal harmonic mixer Download PDF

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JP2008219665A
JP2008219665A JP2007056408A JP2007056408A JP2008219665A JP 2008219665 A JP2008219665 A JP 2008219665A JP 2007056408 A JP2007056408 A JP 2007056408A JP 2007056408 A JP2007056408 A JP 2007056408A JP 2008219665 A JP2008219665 A JP 2008219665A
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differential
local oscillation
cmos inverter
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Hideyuki Kokatsu
秀行 小勝
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Toshiba Corp
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Abstract

<P>PROBLEM TO BE SOLVED: To provide an orthogonal harmonic mixer which is small in current consumption. <P>SOLUTION: In the orthogonal harmonic mixer 1, a positive-polarity signal of a differential input signal and an I-phase local oscillation signal are input to CMOS inverters IV1 and IV2 of a differential pair 11A respectively, and the I-phase local oscillation signal and a negative-polarity signal of the differential input signal are input to CMOS inverters IV1 and IV2 of a differential pair 11B respectively; and the negative-polarity signal of the differential input signal and a Q-phase local oscillation signal which is 90° out of phase with the I-phase local oscillation signal are input to CMOS inverters IV1 and IV2 of a differential pair 11C respectively, and the Q-phase local oscillation signal and the positive-polarity signal of the differential input signal are input to CMOS inverters IV1 and IV2 of a differential pair 11D respectively, so that a positive-polarity signal and a negative-polarity signal of a differential output signal are output from common output terminals OUTP and OUTN of the CMOS inverters IV1 and IV2 respectively. <P>COPYRIGHT: (C)2008,JPO&INPIT

Description

本発明は、直交高調波ミキサに関する。   The present invention relates to a quadrature harmonic mixer.

携帯電話などの小型の受信装置では、入力された無線周波数の高周波信号（ＲＦ信号）をベースバンド信号に変化する周波数変換器として、回路の小型化、集積化に適したダイレクトコンバージョン方式のミキサが用いられる。   In a small receiver such as a cellular phone, a direct conversion mixer suitable for miniaturization and integration of a circuit is used as a frequency converter that changes an input radio frequency high frequency signal (RF signal) into a baseband signal. Used.

しかし、従来のダイレクトコンバージョン方式のミキサでは、ミキサへ入力されるＲＦ信号と局部発振器出力信号（ローカル信号）の周波数が一致しているため、ローカルリークや２次歪みなどで生じるＤＣオフセット成分が自身の出力信号と一致し、出力信号の純度が低下するという問題があった。   However, in the conventional direct conversion type mixer, the frequency of the RF signal input to the mixer and the frequency of the local oscillator output signal (local signal) coincide with each other, so that the DC offset component caused by local leak or second-order distortion is itself And the purity of the output signal is reduced.

そこで、本願発明者は、スプリアス発生を小さくすることのできるダイレクトコンバージョン方式のミキサとして直交偶高調波ミキサを提案した（特許文献１）。この提案した直交偶高調波ミキサでは、それぞれが１対のトランジスタで構成される４組の差動増幅器に、差動で供給されるＲＦ信号と、９０度の位相差を有する直交ローカル信号を入力する。このとき、直交ローカル信号の周波数をＲＦ信号の周波数の半分とすることにより、ローカル信号の２倍の周波数とＲＦ信号を結合させ、入力信号と同じ周波数のスプリアスの発生を抑制している。   Therefore, the inventor of the present application has proposed a quadrature even harmonic mixer as a direct conversion mixer capable of reducing spurious generation (Patent Document 1). In this proposed quadrature even harmonic mixer, four sets of differential amplifiers each composed of a pair of transistors are inputted with RF signals supplied differentially and quadrature local signals having a phase difference of 90 degrees. To do. At this time, the frequency of the orthogonal local signal is made half of the frequency of the RF signal, so that the frequency twice the frequency of the local signal and the RF signal are combined to suppress the occurrence of spurious having the same frequency as the input signal.

しかし、提案した直交偶高調波ミキサでは、それぞれの差動増幅器の負荷として抵抗やキャパシタあるいはインダクタなどの受動素子を必要とし、通常のミキサと同様これら受動素子はチップサイズの増大を招き、またこれらの受動素子をドライブするために、電流が増大するという問題があった。
特開２００４−１８００９８号公報 （第８ページ、図１） However, the proposed quadrature even harmonic mixers require passive elements such as resistors, capacitors, and inductors as the load of each differential amplifier. Like ordinary mixers, these passive elements increase the chip size, and these In order to drive the passive elements, there is a problem that the current increases.
JP 2004-180098 A (Page 8, FIG. 1)

そこで、本発明の目的は、消費電流の少ない直交高調波ミキサを提供することにある。   Therefore, an object of the present invention is to provide a quadrature harmonic mixer with low current consumption.

本発明の一態様によれば、第１のＣＭＯＳインバータおよび第２のＣＭＯＳインバータにより構成される差動対を４つ備え、その第１の差動対の、前記第１のＣＭＯＳインバータへ差動入力信号の正極性信号を入力し、前記第２のＣＭＯＳインバータへＩ相局部発振信号を入力し、その第２の差動対の、前記第１のＣＭＯＳインバータへ前記Ｉ相局部発振信号を入力し、前記第２のＣＭＯＳインバータへ前記差動入力信号の負極性信号を入力し、その第３の差動対の、前記第１のＣＭＯＳインバータへ前記差動入力信号の前記負極性信号を入力し、前記第２のＣＭＯＳインバータへ前記Ｉ相局部発振信号に対して９０°の位相差を有するＱ相局部発振信号を入力し、その第４の差動対の、前記第１のＣＭＯＳインバータへ前記Ｑ相局部発振信号を入力し、前記第２のＣＭＯＳインバータへ前記差動入力信号の前記正極性信号を入力し、前記第１乃至第４の差動対のそれぞれの前記第１のＣＭＯＳインバータの出力を共通に接続して差動出力信号の正極性信号とし、前記第１乃至第４の差動対のそれぞれの前記第２のＣＭＯＳインバータの出力を共通に接続して前記差動出力信号の負極性信号とすることを特徴とする直交高調波ミキサが提供される。   According to one aspect of the present invention, four differential pairs each including a first CMOS inverter and a second CMOS inverter are provided, and the first differential pair is differentially connected to the first CMOS inverter. Input a positive polarity signal of the input signal, input an I-phase local oscillation signal to the second CMOS inverter, and input the I-phase local oscillation signal to the first CMOS inverter of the second differential pair. The negative polarity signal of the differential input signal is input to the second CMOS inverter, and the negative polarity signal of the differential input signal is input to the first CMOS inverter of the third differential pair. Then, a Q-phase local oscillation signal having a phase difference of 90 ° with respect to the I-phase local oscillation signal is input to the second CMOS inverter, and the fourth differential pair is input to the first CMOS inverter. Q phase local oscillation signal , The positive polarity signal of the differential input signal is input to the second CMOS inverter, and the outputs of the first CMOS inverters of the first to fourth differential pairs are connected in common. The positive output signal of the differential output signal is used, and the outputs of the second CMOS inverters of the first to fourth differential pairs are connected in common to form the negative polarity signal of the differential output signal. An orthogonal harmonic mixer is provided.

本発明によれば、受動素子負荷を必要としないので、消費電流を少なくすることができる。   According to the present invention, since a passive element load is not required, current consumption can be reduced.

以下、本発明の実施例を図面を参照して説明する。   Embodiments of the present invention will be described below with reference to the drawings.

図１は、本発明の実施例１に係る直交高調波ミキサの構成の例を示す回路図である。また、図２は、本実施例で用いる差動対の構成の例を示す回路図である。   1 is a circuit diagram illustrating an example of the configuration of an orthogonal harmonic mixer according to a first embodiment of the present invention. FIG. 2 is a circuit diagram showing an example of the configuration of the differential pair used in this embodiment.

まず、図２に示す差動対１１について説明する。   First, the differential pair 11 shown in FIG. 2 will be described.

図２に示す差動対１１は、ＰＭＯＳトランジスタＭ１１およびＮＭＯＳトランジスタＭ１２からなるＣＭＯＳインバータＩＶ１と、ＰＭＯＳトランジスタＭ２１およびＮＭＯＳトランジスタＭ２２からなるＣＭＯＳインバータＩＶ２により構成される。   The differential pair 11 shown in FIG. 2 includes a CMOS inverter IV1 including a PMOS transistor M11 and an NMOS transistor M12, and a CMOS inverter IV2 including a PMOS transistor M21 and an NMOS transistor M22.

この差動対１１の入出力信号の関係は、次のようになる。   The relationship between the input / output signals of the differential pair 11 is as follows.

いま、ＣＭＯＳインバータＩＶ１の入力端子をＩＮ１、出力端子をＯ１、ＣＭＯＳインバータＩＶ２の入力端子をＩＮ２、出力端子をＯ２として、入力端子ＩＮ１、ＩＮ２へ入力信号ＩｎＡ、ＩｎＢをそれぞれ入力し、出力端子Ｏ１、Ｏ２から出力信号ＯｕｔＡ、ＯｕｔＢがそれぞれ出力されたとすると、ＣＭＯＳインバータＩＶ１およびＩＶ２の入出力特性が非線形であるため、差動対１１の入出力信号の関係は、次の式で表される。   Now, assuming that the input terminal of the CMOS inverter IV1 is IN1, the output terminal is O1, the input terminal of the CMOS inverter IV2 is IN2, and the output terminal is O2, the input signals InA and InB are input to the input terminals IN1 and IN2, respectively, and the output terminal O1 If the output signals OutA and OutB are respectively output from O2, the input / output characteristics of the CMOS inverters IV1 and IV2 are non-linear. Therefore, the relationship between the input / output signals of the differential pair 11 is expressed by the following equation.

ＯｕｔＡ−ＯｕｔＢ＝ａ１（ＩｎＡ−ＩｎＢ）＋ａ３（ＩｎＡ−ＩｎＢ）３
＋ａ５（ＩｎＡ−ＩｎＢ）５＋・・・ （１）
ここで、ａ１、ａ３、ａ５、・・・は、回路の非線形性を表現する係数である。 OutA−OutB = a 1 (InA−InB) + a 3 (InA−InB) 3
+ A 5 (InA-InB) 5 + (1)
Here, a 1 , a 3 , a 5 ,... Are coefficients that express the nonlinearity of the circuit.

図１に示す本実施例の直交高調波ミキサ１は、上述したような入出力特性が非線形である差動対１１を４つ備えており、それぞれを差動対１１Ａ、差動対１１Ｂ、差動対１１Ｃ、差動対１１Ｄと表す。   The quadrature harmonic mixer 1 of the present embodiment shown in FIG. 1 includes four differential pairs 11 having nonlinear input / output characteristics as described above, each of which includes a differential pair 11A, a differential pair 11B, and a difference. It represents a moving pair 11C and a differential pair 11D.

直交高調波ミキサ１は、入力端子として、差動形式で入力される入力信号の正極性信号入力端子ＩＮＰ、負極性信号入力端子ＩＮＮ、および直交形式の局部発振信号のＩ相入力端子ＬＩ、Ｑ相入力端子ＬＱを有し、出力端子としてＯＵＴＰおよびＯＵＴＮを有する。   The quadrature harmonic mixer 1 has, as input terminals, a positive signal input terminal INP and a negative signal input terminal INN for an input signal input in a differential format, and I-phase input terminals LI and Q for a local oscillation signal in an orthogonal format. It has a phase input terminal LQ and has OUTP and OUTN as output terminals.

また、差動対１１Ａ〜１１ＤのＰＭＯＳトランジスタＭ１１、Ｍ２１が接続される電源端子ＶＣＣと、ＮＭＯＳトランジスタＭ１２、Ｍ２２が接続される接地電位端子ＧＮＤを有する。   The power supply terminal VCC to which the PMOS transistors M11 and M21 of the differential pairs 11A to 11D are connected and the ground potential terminal GND to which the NMOS transistors M12 and M22 are connected.

差動対１１Ａは、ＣＭＯＳインバータＩＶ１の入力端子ＩＮ１を差動入力信号の正極性信号入力端子ＩＮＰに接続し、ＣＭＯＳインバータＩＶ２の入力端子ＩＮ２を局部発振信号のＩ相入力端子ＬＩに接続する。   The differential pair 11A connects the input terminal IN1 of the CMOS inverter IV1 to the positive signal input terminal INP of the differential input signal, and connects the input terminal IN2 of the CMOS inverter IV2 to the I-phase input terminal LI of the local oscillation signal.

差動対１１Ｂは、ＣＭＯＳインバータＩＶ１の入力端子ＩＮ１を局部発振信号のＩ相入力端子ＬＩに接続し、ＣＭＯＳインバータＩＶ２の入力端子ＩＮ２を差動入力信号の負極性信号入力端子ＩＮＮに接続する。   The differential pair 11B connects the input terminal IN1 of the CMOS inverter IV1 to the I-phase input terminal LI of the local oscillation signal, and connects the input terminal IN2 of the CMOS inverter IV2 to the negative polarity signal input terminal INN of the differential input signal.

差動対１１Ｃは、ＣＭＯＳインバータＩＶ１の入力端子ＩＮ１を差動入力信号の負極性信号入力端子ＩＮＮに接続し、ＣＭＯＳインバータＩＶ２の入力端子ＩＮ２を局部発振信号のＱ相入力端子ＬＱに接続する。   The differential pair 11C connects the input terminal IN1 of the CMOS inverter IV1 to the negative polarity signal input terminal INN of the differential input signal, and connects the input terminal IN2 of the CMOS inverter IV2 to the Q-phase input terminal LQ of the local oscillation signal.

差動対１１Ｄは、ＣＭＯＳインバータＩＶ１の入力端子ＩＮ１を局部発振信号のＱ相入力端子ＬＩに接続し、ＣＭＯＳインバータＩＶ２の入力端子ＩＮ２を差動入力信号の正極性信号入力端子ＩＮＰに接続する。   The differential pair 11D connects the input terminal IN1 of the CMOS inverter IV1 to the Q-phase input terminal LI of the local oscillation signal, and connects the input terminal IN2 of the CMOS inverter IV2 to the positive signal input terminal INP of the differential input signal.

また、差動対１１Ａ〜１１ＤのＣＭＯＳインバータＩＶ１の出力端子Ｏ１は、共通に出力端子ＯＵＴＰに接続し、ＣＭＯＳインバータＩＶ２の出力端子Ｏ２は、共通に出力端子ＯＵＴＮに接続する。   Further, the output terminal O1 of the CMOS inverter IV1 of the differential pairs 11A to 11D is commonly connected to the output terminal OUTP, and the output terminal O2 of the CMOS inverter IV2 is commonly connected to the output terminal OUTN.

次に、本実施例の直交高調波ミキサ１の動作について説明する。   Next, the operation of the quadrature harmonic mixer 1 of the present embodiment will be described.

いま、差動入力信号の正極性信号入力端子ＩＮＰ、負極性信号入力端子ＩＮＮに入力する信号を正極性差動入力信号ｆ、負極性差動入力信号−ｆとし、局部発振信号のＩ相入力端子ＬＩ、Ｑ相入力端子ＬＱに入力する信号をＩ相局部発振信号ｆＬＩ、Ｑ相局部発振信号ｆＬＱとし、出力端子ＯＵＴＰ、ＯＵＴＮ間に出力される差動出力信号をｆＯＵＴとすると、差動出力信号ｆＯＵＴは、各差動対の出力を（１）式で求め、その結果を加算することにより、次のように表される。なお、ここでは、５次以降の項の詳細な表記は省略している。 Now, the signals input to the positive signal input terminal INP and the negative signal input terminal INN of the differential input signal are defined as the positive differential input signal f and the negative differential input signal −f, and the I-phase input of the local oscillation signal A signal input to the terminal LI and the Q-phase input terminal LQ is an I-phase local oscillation signal f LI and a Q-phase local oscillation signal f LQ, and a differential output signal output between the output terminals OUTP and OUTN is f OUT . The differential output signal f OUT is expressed as follows by obtaining the output of each differential pair by Equation (1) and adding the results. It should be noted that detailed description of the fifth and subsequent terms is omitted here.

ｆＯＵＴ＝ａ１（ｆ−ｆＬＩ）＋ａ３（ｆ−ｆＬＩ）３＋５次以降の項
＋ａ１（ｆＬＩ＋ｆ）＋ａ３（ｆＬＩ＋ｆ）３＋５次以降の項
＋ａ１（−ｆ−ｆＬＱ）＋ａ３（−ｆ−ｆＬＱ）３＋５次以降の項
＋ａ１（ｆＬＱ−ｆ）＋ａ３（ｆＬＱ−ｆ）３＋５次以降の項 （２） f OUT = a 1 (f−f LI ) + a 3 (f−f LI ) 3 + 5th and subsequent terms + a 1 (f LI + f) + a 3 (f LI + f) 3 + 5th and subsequent terms + a 1 (−f −f LQ ) + a 3 (−f−f LQ ) 3 + 5th and subsequent terms + a 1 (f LQ −f) + a 3 (f LQ −f) 3 + 5th and subsequent terms (2)

この（２）式を、次数ごとにまとめると次のように表される。
ｆＯＵＴ＝ａ１｛（ｆ−ｆＬＩ）＋（ｆＬＩ＋ｆ）＋（−ｆ−ｆＬＱ）＋（ｆＬＱ−ｆ）｝
＋ａ３｛（ｆ−ｆＬＩ）３＋（ｆＬＩ＋ｆ）３＋（−ｆ−ｆＬＱ）３＋（ｆＬＱ−ｆ）３｝
＋５次以降の項 （３） The formula (2) is summarized as follows for each order.
f OUT = a 1 {(f−f LI ) + (f LI + f) + (− f−f LQ ) + (f LQ −f)}
+ A 3 {(f−f LI ) 3 + (f LI + f) 3 + (− f−f LQ ) 3 + (f LQ −f) 3 }
+ 5th and subsequent terms (3)

（３）式で、１次の項は互いに打ち消される。また、３次の項を展開して整理すると、（３）式は次のように表される。
ｆＯＵＴ＝ａ３（３ｆ・ｆＬＩ ２＋３ｆ・ｆＬＩ ２−３ｆ・ｆＬＱ ２−３ｆ・ｆＬＱ ２）
＋５次以降の項
＝６ａ３ｆ（ｆＬＩ ２−ｆＬＱ ２）＋５次以降の項 （４） In equation (3), the first order terms cancel each other. Further, when the third-order terms are expanded and arranged, the expression (3) is expressed as follows.
f OUT = a 3 (3f · f LI 2 + 3f · f LI 2 −3f · f LQ 2 −3f · f LQ 2 )
+ Fifth and subsequent terms = 6a 3 f (f LI 2 −f LQ 2 ) + Fifth and subsequent terms (4)

この（４）式が、本実施例の直交高調波ミキサ１の周波数変換のメカニズムを表現しており、周波数変換に寄与しない１次の項などが打ち消されていることからもわかるように、出力に不要成分が現れていないことがわかる。   This equation (4) expresses the frequency conversion mechanism of the quadrature harmonic mixer 1 of the present embodiment, and as can be seen from the fact that the first-order terms that do not contribute to the frequency conversion are canceled, the output It can be seen that no unnecessary components appear.

ここで、（４）式の意味を具体的に考察するために、本実施例の直交高調波ミキサ１に入力される正極性差動入力信号ｆを、振幅Ａ、角周波数ω、位相φの正弦波として、時間ｔに対して、
ｆ＝Ａｃｏｓ（ωｔ＋φ）
と表し、
局部発信信号の角周波数をωＬとして、互いに直交する関係のＩ相局部発振信号ｆＬＩ、Ｑ相局部発振信号ｆＬＱを、それぞれ
ｆＬＩ＝ｃｏｓωＬｔ
ｆＬＱ＝ｓｉｎωＬｔ
と表して、（４）式に代入すると、直交高調波ミキサ１の出力信号ｆＯＵＴは次のように表される。
ｆＯＵＴ＝６ａ３Ａｃｏｓ（ωｔ＋φ）（ｃｏｓ２ωＬｔ−ｓｉｎ２ωＬｔ）＋５次以降の項
＝６ａ３Ａｃｏｓ（ωｔ＋φ）ｃｏｓ２ωＬｔ＋５次以降の項
＝３ａ３Ａｃｏｓ｛（ω＋２ωＬ）ｔ＋φ｝＋３ａ３Ａｃｏｓ｛（ω−２ωＬ）ｔ＋φ｝
＋５次以降の項 （５） Here, in order to specifically consider the meaning of the equation (4), the positive differential input signal f input to the quadrature harmonic mixer 1 of the present embodiment is expressed by the amplitude A, the angular frequency ω, and the phase φ. As a sine wave, for time t
f = Acos (ωt + φ)
And
When the angular frequency of the local oscillation signal is ω L , the I-phase local oscillation signal f LI and the Q-phase local oscillation signal f LQ that are orthogonal to each other are respectively expressed as f LI = cos ω L t
f LQ = sinω L t
And substituting into the equation (4), the output signal f OUT of the quadrature harmonic mixer 1 is expressed as follows.
f OUT = 6a 3 A cos (ωt + φ) (cos 2 ω L t-sin 2 ω L t) + fifth term or later = 6a 3 A cos (ωt + φ) cos 2ω L t + fifth term or later = 3a 3 A cos {(ω + 2ω L ) t + φ} + 3a 3 Acos {(ω−2ω L ) t + φ}
+ 5th and subsequent terms (5)

この（５）式の意味するところは、角周波数ωの入力信号が、互いに直交する角周波数をωＬの局部発信信号によって、
ω＋２ωＬ
ω−２ωＬ
の２つの角周波数を持つ信号に周波数変換されることを意味している。 The meaning of this equation (5) is that the input signals of the angular frequency ω are orthogonal to each other by the local transmission signal of ω L.
ω + 2ω L
ω-2ω L
This means that the signal is converted into a signal having two angular frequencies.

すなわち、本実施例の直交高調波ミキサ１は、入力された信号に対して、入力信号の周波数と局部発振信号の周波数の２倍の周波数との和、または差、の周波数を有する信号を出力する周波数変換動作を行う。   That is, the quadrature harmonic mixer 1 of the present embodiment outputs a signal having a frequency that is the sum or difference of the frequency of the input signal and twice the frequency of the local oscillation signal with respect to the input signal. Perform frequency conversion operation.

このような本実施例によれば、４対の差動対がＣＭＯＳインバータのみで構成でき、負荷としての受動素子を必要としない。そのため、周波数変換動作時の消費電流の発生を少なくすることができる。   According to such a present Example, four differential pairs can be comprised only by a CMOS inverter, and the passive element as a load is not required. Therefore, the generation of current consumption during the frequency conversion operation can be reduced.

上述したように、実施例１の直交高調波ミキサ１は、従来に比べて消費電流の発生を少なくすることができる。ただし、入力信号の振幅などにより、消費電流が大きく変化することがある。そのため、携帯電話等の電池駆動機器の場合、電池寿命の見積もりなどが困難になることが考えられる。   As described above, the quadrature harmonic mixer 1 according to the first embodiment can reduce the generation of current consumption compared to the conventional case. However, the current consumption may change greatly depending on the amplitude of the input signal. For this reason, in the case of a battery-driven device such as a mobile phone, it may be difficult to estimate the battery life.

そこで、本実施例では、動作時の消費電流が一定となる直交高調波ミキサの回路構成の例を示す。   Therefore, in this embodiment, an example of a circuit configuration of an orthogonal harmonic mixer in which current consumption during operation is constant is shown.

図３は、本発明の実施例２に係る直交高調波ミキサの構成の例を示す回路図である。   FIG. 3 is a circuit diagram showing an example of the configuration of the quadrature harmonic mixer according to the second embodiment of the present invention.

本実施例の直交高調波ミキサ２は、実施例１の直交高調波ミキサ１と同じ構成の差動対１１Ａ〜１１Ｄを備え、さらに、差動対１１Ａ〜１１Ｄに接続される定電流源２１１〜２４２を備えるものである。   The quadrature harmonic mixer 2 of the present embodiment includes the differential pairs 11A to 11D having the same configuration as the quadrature harmonic mixer 1 of the first embodiment, and further, constant current sources 211 to 11D connected to the differential pairs 11A to 11D. 242 is provided.

このうち、定電流源２１１、２２１、２３１、２４１は、電源端子ＶＣＣと差動対１１Ａ、１１Ｂ、１１Ｃ、１１Ｄとの間にそれぞれ接続され、差動対１１Ａ、１１Ｂ、１１Ｃ、１１Ｄのそれぞれへ定電流を供給する。それに対して、定電流源２１２、２２２、２３２、２４２は、差動対１１Ａ、１１Ｂ、１１Ｃ、１１Ｄと接地電位端子ＧＮＤとの間にそれぞれ接続され、差動対１１Ａ、１１Ｂ、１１Ｃ、１１Ｄのそれぞれから定電流を引き出す。   Among these, the constant current sources 211, 221, 231, and 241 are respectively connected between the power supply terminal VCC and the differential pairs 11A, 11B, 11C, and 11D, and to the differential pairs 11A, 11B, 11C, and 11D, respectively. Supply constant current. On the other hand, the constant current sources 212, 222, 232, and 242 are connected between the differential pairs 11A, 11B, 11C, and 11D and the ground potential terminal GND, respectively, and the differential pairs 11A, 11B, 11C, and 11D are connected. A constant current is drawn from each.

この定電流源２１１〜２４２の働きにより、本実施例の直交高調波ミキサ２は、動作時の消費電流が一定になる。   Due to the operation of the constant current sources 211 to 242, the orthogonal harmonic mixer 2 of this embodiment has a constant current consumption during operation.

なお、差動対１１Ａ〜１１Ｄの動作は、実施例１と同じであるので、ここでは、その詳細な説明を省略する。   Since the operations of the differential pairs 11A to 11D are the same as those in the first embodiment, detailed description thereof is omitted here.

このような本実施例によれば、入力条件が変化しても消費電流が変動しないので、消費電流の見積りなどを容易にすることができる。   According to this embodiment, since the consumption current does not vary even if the input condition changes, it is possible to easily estimate the consumption current.

図４は、本発明の実施例３に係る直交高調波ミキサの構成の例を示す回路図である。   FIG. 4 is a circuit diagram illustrating an example of the configuration of the quadrature harmonic mixer according to the third embodiment of the present invention.

本実施例の直交高調波ミキサ３は、実施例１の直交高調波ミキサ１を２つ備え、それぞれへ入力する直交局部発振信号を差動形式信号としたものである。なお、図４では、２つの直交高調波ミキサ１を、直交高調波ミキサ１Ａ、直交高調波ミキサ１Ｂと表す。   The quadrature harmonic mixer 3 of the present embodiment is provided with two quadrature harmonic mixers 1 of the first embodiment, and the quadrature local oscillation signal input to each is a differential signal. In FIG. 4, the two orthogonal harmonic mixers 1 are represented as an orthogonal harmonic mixer 1A and an orthogonal harmonic mixer 1B.

本実施例の直交高調波ミキサ３は、直交高調波ミキサ１Ａおよび直交高調波ミキサ１Ｂを備える。   The quadrature harmonic mixer 3 of the present embodiment includes a quadrature harmonic mixer 1A and a quadrature harmonic mixer 1B.

直交高調波ミキサ１Ａの正極性信号入力端子ＩＮＰ、負極性信号入力端子ＩＮＮは、それぞれ、直交高調波ミキサ１Ｂの正極性信号入力端子ＩＮＰ、負極性信号入力端子ＩＮＮと並列に接続される。この正極性信号入力端子ＩＮＰおよび負極性信号入力端子ＩＮＮへは、差動形式で入力される入力信号の正極性信号ＩＮＰおよび負極性信号ＩＮＮが、それぞれ入力される。   The positive signal input terminal INP and the negative signal input terminal INN of the orthogonal harmonic mixer 1A are connected in parallel with the positive signal input terminal INP and the negative signal input terminal INN of the orthogonal harmonic mixer 1B, respectively. The positive polarity signal input terminal INP and the negative polarity signal input terminal INN are respectively supplied with the positive polarity signal INP and the negative polarity signal INN of the input signals inputted in a differential format.

また、直交高調波ミキサ１ＡのＩ相入力端子ＬＩへは、差動形式の直交局部発振信号の正極性Ｉ相局部発振信号ＬＩＰが入力され、Ｑ相入力端子ＬＱへは、差動形式の直交局部発振信号の正極性Ｑ相局部発振信号ＬＱＰが入力される。   Further, a positive I-phase local oscillation signal LIP of a differential orthogonal local oscillation signal is inputted to the I-phase input terminal LI of the quadrature harmonic mixer 1A, and a differential orthogonality is inputted to the Q-phase input terminal LQ. A positive Q phase local oscillation signal LQP of the local oscillation signal is input.

一方、直交高調波ミキサ１ＢのＩ相入力端子ＬＩへは、差動形式の直交局部発振信号の負極性Ｉ相局部発振信号ＬＩＮが入力され、Ｑ相入力端子ＬＱへは、差動形式の直交局部発振信号の負極性Ｑ相局部発振信号ＬＱＮが入力される。   On the other hand, the negative-polarity I-phase local oscillation signal LIN of the differential orthogonal local oscillation signal is input to the I-phase input terminal LI of the orthogonal harmonic mixer 1B, and the differential orthogonality is input to the Q-phase input terminal LQ. A negative Q phase local oscillation signal LQN of the local oscillation signal is input.

また、直交高調波ミキサ１Ａの出力端子ＯＵＴＰ、ＯＵＴＮは、直交高調波ミキサ１Ｂの出力端子ＯＵＴＰ、ＯＵＴＮと、それぞれ並列に接続される。   Further, the output terminals OUTP and OUTN of the quadrature harmonic mixer 1A are connected in parallel with the output terminals OUTP and OUTN of the quadrature harmonic mixer 1B, respectively.

なお、直交高調波ミキサ１Ａ、１Ｂの動作は、実施例１と同じであるので、ここでは、その詳細な説明を省略する。   Since the operations of the orthogonal harmonic mixers 1A and 1B are the same as those in the first embodiment, detailed description thereof is omitted here.

一般に、差動形式の信号は、同相ノイズに対する耐性が強く、外乱や変動に強い信号であることが知られている。したがって、本実施例の場合、直交局部発振信号を差動形式の信号とすることにより、直交局部発振信号のノイズ耐性を強くすることができ、雑音特性を向上させることができる。   In general, it is known that a differential signal is a signal that is highly resistant to common-mode noise and is resistant to disturbances and fluctuations. Therefore, in this embodiment, by making the orthogonal local oscillation signal a differential signal, the noise tolerance of the orthogonal local oscillation signal can be increased, and the noise characteristics can be improved.

また、本実施例を携帯電話で使用されているダイレクトコンバージョン受信方式に用いた場合、局部発振信号がＲＦ信号入力端に漏洩しても、差動信号であるため互いに打ち消し合い、その影響を除去することができる。   In addition, when this embodiment is used for the direct conversion reception system used in a mobile phone, even if the local oscillation signal leaks to the RF signal input terminal, it is a differential signal and cancels each other out. can do.

このような本実施例によれば、直交局部発振信号を差動形式の信号とすることにより、外来ノイズに対する特性の向上、および外部へ影響を及ぼすノイズの抑制を図ることができる。   According to the present embodiment, by making the orthogonal local oscillation signal a differential signal, it is possible to improve characteristics against external noise and suppress noise that affects the outside.

また、直交高調波ミキサ３は、実施例２の直交高調波ミキサ２を２つ備える構成としてもよい。直交高調波ミキサ２を用いることにより、動作時の消費電流を一定にすることができる。   The quadrature harmonic mixer 3 may be configured to include two quadrature harmonic mixers 2 of the second embodiment. By using the quadrature harmonic mixer 2, current consumption during operation can be made constant.

本発明の実施例１に係る直交高調波ミキサの構成の例を示す回路図。1 is a circuit diagram showing an example of a configuration of an orthogonal harmonic mixer according to Embodiment 1 of the present invention. 本発明の実施例の差動対の構成の例を示す回路図。The circuit diagram which shows the example of a structure of the differential pair of the Example of this invention. 本発明の実施例２に係る直交高調波ミキサの構成の例を示す回路図。The circuit diagram which shows the example of a structure of the orthogonal harmonic mixer which concerns on Example 2 of this invention. 本発明の実施例３に係る直交高調波ミキサの構成の例を示す回路図。The circuit diagram which shows the example of a structure of the orthogonal harmonic mixer which concerns on Example 3 of this invention.

符号の説明Explanation of symbols

１、２、２Ａ、２Ｂ、３ 直交高調波ミキサ
１１、１１Ａ〜１１Ｄ 差動対
２１１、２２１、２３１、２４１、２１２、２２２、２３２、２４２ 定電流源
ＩＶ１、ＩＶ２ ＣＭＯＳインバータ
Ｍ１１、Ｍ２１ ＰＭＯＳトランジスタ
Ｍ１２、Ｍ２２ ＮＭＯＳトランジスタ 1, 2, 2A, 2B, 3 Quadrature harmonic mixer 11, 11A to 11D Differential pair 211, 221, 231, 241, 212, 222, 232, 242 Constant current source IV1, IV2 CMOS inverter M11, M21 PMOS transistor M12 M22 NMOS transistor

Claims (3)

第１のＣＭＯＳインバータおよび第２のＣＭＯＳインバータにより構成される差動対を４つ備え、
その第１の差動対の、前記第１のＣＭＯＳインバータへ差動入力信号の正極性信号を入力し、前記第２のＣＭＯＳインバータへＩ相局部発振信号を入力し、
その第２の差動対の、前記第１のＣＭＯＳインバータへ前記Ｉ相局部発振信号を入力し、前記第２のＣＭＯＳインバータへ前記差動入力信号の負極性信号を入力し、
その第３の差動対の、前記第１のＣＭＯＳインバータへ前記差動入力信号の前記負極性信号を入力し、前記第２のＣＭＯＳインバータへ前記Ｉ相局部発振信号に対して９０°の位相差を有するＱ相局部発振信号を入力し、
その第４の差動対の、前記第１のＣＭＯＳインバータへ前記Ｑ相局部発振信号を入力し、前記第２のＣＭＯＳインバータへ前記差動入力信号の前記正極性信号を入力し、
前記第１乃至第４の差動対のそれぞれの前記第１のＣＭＯＳインバータの出力を共通に接続して差動出力信号の正極性信号とし、
前記第１乃至第４の差動対のそれぞれの前記第２のＣＭＯＳインバータの出力を共通に接続して前記差動出力信号の負極性信号とする
ことを特徴とする直交高調波ミキサ。 Comprising four differential pairs composed of a first CMOS inverter and a second CMOS inverter;
A positive polarity signal of a differential input signal is input to the first CMOS inverter of the first differential pair, and an I-phase local oscillation signal is input to the second CMOS inverter;
The I-phase local oscillation signal is input to the first CMOS inverter of the second differential pair, and the negative polarity signal of the differential input signal is input to the second CMOS inverter.
The negative polarity signal of the differential input signal is input to the first CMOS inverter of the third differential pair, and the second CMOS inverter has a position of 90 ° with respect to the I-phase local oscillation signal. Input Q-phase local oscillation signal with phase difference,
The Q phase local oscillation signal is input to the first CMOS inverter of the fourth differential pair, and the positive polarity signal of the differential input signal is input to the second CMOS inverter,
The outputs of the first CMOS inverters of the first to fourth differential pairs are connected in common to form a positive polarity signal of the differential output signal,
An orthogonal harmonic mixer, wherein the outputs of the second CMOS inverters of the first to fourth differential pairs are connected in common to form a negative signal of the differential output signal. 前記第１乃至第４の差動対のそれぞれへ定電流を供給する第１乃至第４の定電流源と、
前記第１乃至第４の差動対のそれぞれから定電流を引き出す第５乃至第８の定電流源と、をさらに備える
ことを特徴とする請求項１に記載の直交高調波ミキサ。 First to fourth constant current sources for supplying a constant current to each of the first to fourth differential pairs;
The quadrature harmonic mixer according to claim 1, further comprising fifth to eighth constant current sources that draw a constant current from each of the first to fourth differential pairs. 請求項１または２に記載の直交高調波ミキサを２つ備え、
そのうちの１つの直交高調波ミキサへ入力する前記Ｉ相局部発振信号および前記Ｑ相局部発振信号を差動信号の正極性信号とし、
もう１つの直交高調波ミキサへ入力する前記Ｉ相局部発振信号および前記Ｑ相局部発振信号を差動信号の負極性信号とし、
前記２つの直交高調波ミキサのそれぞれの前記差動出力信号の前記正極性信号および前記負極性信号をそれぞれ共通に接続する
ことを特徴とする直交高調波ミキサ。 Two quadrature harmonic mixers according to claim 1 or 2,
The I-phase local oscillation signal and the Q-phase local oscillation signal input to one of the quadrature harmonic mixers are set as positive signals of differential signals,
The I-phase local oscillation signal and the Q-phase local oscillation signal input to another quadrature harmonic mixer are set as a negative signal of a differential signal,
The quadrature harmonic mixer, wherein the positive polarity signal and the negative polarity signal of the differential output signal of each of the two quadrature harmonic mixers are connected in common.
JP2007056408A 2007-03-06 2007-03-06 Orthogonal harmonic mixer Pending JP2008219665A (en)

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