JP2007068197A - Receiving method and receiving system using the same, radio mobile station equipped with receiving system, and radio device equipped with receiving system - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To reduce a processing delay of a receiving system equipped with an adaptive array antenna. <P>SOLUTION: A BB inputting section 116 inputs base band reception signals 300. An initial weight data setting section 12 sets a weighting factor 322 used for a training signal 302 zone as an initial weighting factor 320. A gap correcting section 16 corrects a control weighting factor 310 using a gap error signal 316 and outputs the result which is an updated weighting factor 318. A weight switching section 18 selects the initial weighting factor 320 in the training signal 302 zone while selecting the updated weighting factor 318 in a data signal zone, and then outputs the selected weighting factor as the weighting factor 322. A combining section 118 weighs the base band reception signals 300 by the weighting factor 322 and then adds them up. <P>COPYRIGHT: (C)2007,JPO&INPIT

Description

  The present invention relates to reception technology. Equipped with a receiving method for controlling weighting factors, a receiving method using the same, a receiving device using the same, a radio mobile station equipped with the receiving device, and a receiving device, especially for combining radio signals received by a plurality of antennas Relates to a wireless device.

  In wireless communication, effective use of limited frequency resources is generally desired. In order to effectively use frequency resources, for example, radio waves of the same frequency are repeatedly used at a distance as close as possible. However, in that case, communication quality deteriorates due to co-channel interference from a nearby radio base station or radio mobile station using the same frequency. One technique for preventing degradation of communication quality due to co-channel interference is the adaptive array antenna technique.

In the adaptive array antenna technique, signals received by a plurality of antennas are weighted with different weighting factors and combined. The weighting factor is adaptively updated so that an error signal between the signal to be transmitted determined from the combined signal and the combined signal becomes small. For adaptive updating of the weighting factor, for example, an adaptive algorithm such as an RLS (Recursive Least Squares) algorithm or an LMS (Least Mean Squares) algorithm is used. The RLS algorithm generally converges at a high speed, but since the calculation is complicated, a high-speed arithmetic circuit or a large-scale arithmetic circuit is required. The LMS algorithm can be realized with a simpler arithmetic circuit than the RLS algorithm, but its convergence speed is slow (see, for example, Patent Document 1).
JP 2002-26788 A

  When an adaptive array antenna is used for a wireless mobile station, it is desirable that the arithmetic circuit is small. Therefore, the LMS algorithm is suitable for updating the weighting factor. However, since the LMS algorithm generally has a slow convergence, if the received signal to be synthesized is delayed until it converges, the processing delay becomes large, and a real time in which an allowable delay time such as a video conference is specified. Processing applications may not be available. On the other hand, if reception processing is performed using a weighting factor at a stage where the LMS algorithm has not converged in order to reduce processing delay, reception characteristics generally deteriorate.

  The present inventor has recognized the above situation and made the present invention, and an object of the present invention is to provide a simple arithmetic circuit receiver having a small processing delay. Another object of the present invention is to provide a receiving apparatus in which the degradation of reception characteristics is small even when the weighting factor is not converged. Another object of the present invention is to provide a receiving apparatus that smoothly switches a plurality of types of weighting factors.

One embodiment of the present invention is a receiving device. The apparatus includes an input unit that inputs a plurality of signals to be processed, and a plurality of weighting factors that are multiplied by the plurality of input signals, and a plurality of first weighting factors that are temporarily used. A switching unit that switches with a plurality of second weighting factors having high adaptability, a control unit that instructs the switching unit to switch between a plurality of first weighting factors and a plurality of second weighting factors, and a plurality of input signals And a combining unit that combines the multiplication results after multiplying each of the plurality of weighting factors.
In the “multiple weighting factors”, when the input signals are (X1, Y1) and (X2, Y2), the multiplication results are (AX1, BY1) and (CX2, DY2). (A, B, C, D) having the same number of terms as the plurality of signals, or having a different number of terms from the plurality of signals such that the multiplication results are (AX1, AY1) and (BX2, BY2) ( A, B).
By switching the weighting factors having different characteristics by the above apparatus, characteristics suitable at that time can be obtained.

Another embodiment of the present invention is also a receiving device. The apparatus includes an input unit that inputs a plurality of signals to be processed, and a plurality of weight coefficients that are multiplied by the plurality of input signals, as a plurality of first weight coefficients and a plurality of second weight coefficients. When a switching unit and a plurality of signals are continuously input in a predetermined section, the switching unit is instructed to switch between the plurality of first weight coefficients and the plurality of second weight coefficients in the middle of the section. A control unit; and a synthesis unit that synthesizes the multiplication results after multiplying the plurality of input signals and the plurality of weighting coefficients, respectively.
“Continuous” does not need to be continuous for a long time, but may be continuous for a short time. Further, if the device recognizes the regularity, it includes a discrete case, that is, includes everything that the device can recognize as “continuous”.

The plurality of first weighting factors may be set so that only a result of multiplication of one of the plurality of input signals is valid as a result of multiplication with the plurality of input signals. One of the plurality of input signals may be a signal having the largest value among the plurality of input signals. The plurality of first weighting factors may be determined using the plurality of second weighting factors set in the past.
Based on a plurality of input signals, a weighting factor updating unit that adaptively updates a plurality of third weighting factors, and correlating at least one of the plurality of input signals with a known signal, A gap estimator for estimating a gap between the plurality of first weighting factors and the plurality of third weighting factors, and correcting the plurality of third weighting factors based on the estimated gap, thereby And a gap correction unit that generates the second weighting coefficient.

The signals that are continuously input in the predetermined section include signals having different properties, and the control unit detects the first change point of the properties of the plurality of input signals, Switching between the weighting factor and the second weighting factor may be instructed. The control unit sequentially inputs a plurality of third weighting factors updated by the weighting factor updating unit, and when the variation of the plurality of third weighting factors converges within a predetermined range, Switching between the first weighting factor and the second weighting factor may be instructed.
By switching different weighting factors in the middle of the section by the above apparatus, characteristics suitable at that time can be obtained.

Yet another embodiment of the present invention is a reception method. In this method, a step of inputting a plurality of signals to be processed and a plurality of weighting factors multiplied by the plurality of inputted signals are more adapted to a plurality of first weighting factors to be temporarily used. A step of switching with a plurality of second weighting factors having a high probability, a step of instructing switching between a plurality of first weighting factors and a plurality of second weighting factors, and a plurality of input signals and a plurality of weighting factors, respectively Synthesizing multiplication results after multiplication.
Yet another embodiment of the present invention is also a reception method. In this method, a step of inputting a plurality of signals to be processed and a plurality of weighting factors multiplied by the plurality of inputted signals are switched between a plurality of first weighting factors and a plurality of second weighting factors. And a step of instructing switching between the plurality of first weighting factors and the plurality of second weighting factors in the middle of the section when a plurality of signals are continuously input in the predetermined section And multiplying a plurality of signals by a plurality of weighting factors, respectively, and then combining the multiplication results.

The plurality of first weighting factors may be set so that only a result of multiplication of one of the plurality of input signals is valid as a result of multiplication with the plurality of input signals. One of the plurality of input signals may be a signal having the largest value among the plurality of input signals. The plurality of first weighting factors may be determined using a plurality of second weighting factors set in the past.
Based on the plurality of input signals, adaptively updating the plurality of third weighting factors, and correlating at least one of the plurality of input signals with a known signal, thereby performing a plurality of first processes. Estimating a gap between one weighting factor and a plurality of third weighting factors, and correcting each of the plurality of third weighting factors based on the estimated gap, thereby providing a plurality of second weighting factors. Generating a coefficient.

  The signals continuously input in the predetermined section include signals having different properties, and the step of instructing switching between the plurality of first weighting factors and the plurality of second weighting factors includes the plurality of input signals. When the signal characteristic change point is detected, switching between the first weighting factor and the second weighting factor may be instructed. In the step of instructing switching between the plurality of first weighting factors and the plurality of second weighting factors, the plurality of third weighting factors to be updated are sequentially input, and the variation of the plurality of third weighting factors is determined in advance. When convergence is within the range, switching between the first weighting factor and the second weighting factor may be instructed.

Yet another embodiment of the present invention is a program. In this program, a step of inputting a plurality of signals to be processed and a plurality of weighting factors multiplied by the inputted plurality of signals are more adapted to a plurality of first weighting factors to be temporarily used. A step of switching with a plurality of second weighting factors having a high probability, a step of instructing switching between a plurality of first weighting factors and a plurality of second weighting factors, and a plurality of input signals and a plurality of weighting factors, respectively Synthesizing multiplication results after multiplication.
Yet another embodiment of the present invention is also a program. In this program, a step of inputting a plurality of signals to be processed and a plurality of weighting factors multiplied by the plurality of inputted signals are switched between a plurality of first weighting factors and a plurality of second weighting factors. And a step of instructing switching between the plurality of first weighting factors and the plurality of second weighting factors in the middle of the section when a plurality of signals are continuously input in the predetermined section And multiplying a plurality of signals by a plurality of weighting factors, respectively, and then combining the multiplication results.

The plurality of first weighting factors may be set so that only a result of multiplication of one of the plurality of input signals is valid as a result of multiplication with the plurality of input signals. One of the plurality of input signals may be a signal having the largest value among the plurality of input signals. The plurality of first weighting factors may be determined using a plurality of second weighting factors set in the past.
Based on the plurality of input signals, adaptively updating the plurality of third weighting factors, and correlating at least one of the plurality of input signals with a known signal, thereby performing a plurality of first processes. Estimating a gap between one weighting factor and a plurality of third weighting factors, and correcting each of the plurality of third weighting factors based on the estimated gap, thereby providing a plurality of second weighting factors. Generating a coefficient.

The signals continuously input in the predetermined section include signals having different properties, and the step of instructing switching between the plurality of first weighting factors and the plurality of second weighting factors includes the plurality of input signals. When the signal characteristic change point is detected, switching between the first weighting factor and the second weighting factor may be instructed. In the step of instructing switching between the plurality of first weighting factors and the plurality of second weighting factors, the plurality of third weighting factors to be updated are sequentially input, and the variation of the plurality of third weighting factors is determined in advance. When convergence is within the range, switching between the first weighting factor and the second weighting factor may be instructed.
It should be noted that any combination of the above-described constituent elements and a conversion of the expression of the present invention between a method, an apparatus, a system, a recording medium, a computer program, etc. are also effective as an aspect of the present invention.

  According to the present invention, a simple arithmetic circuit with a small processing delay can be realized. Further, even when the weighting factor is not converged, the degradation of the reception characteristics can be reduced. In addition, a plurality of types of weighting factors can be switched smoothly.

(Embodiment 1)
The first embodiment relates to a receiving apparatus including an adaptive array antenna that receives a radio signal of a burst signal with a plurality of antennas, and weights and combines the received signals with different weighting factors. The burst signal is composed of a known training signal arranged at the head portion and other data signals. In order to reduce the processing delay, the receiving apparatus according to Embodiment 1 synthesizes the received signal by weighting it with a weighting coefficient with little delay. Although the weighting factor is sequentially updated by the LMS algorithm, there are many cases where the weighting factor is not converged at the initial stage of the training signal interval. . As the weighting coefficient in the data signal section, the weighting coefficient of the adaptive array antenna pattern updated by the LMS algorithm is used.

  FIG. 1 shows a communication system including a transmission apparatus 100 and a reception apparatus 106 according to Embodiment 1. The transmission apparatus 100 includes a modulation unit 102, an RF unit 104, and an antenna 132. The receiving apparatus 106 includes a first antenna 134a, a second antenna 134b, an nth antenna 134n, an RF unit 108, a signal processing unit 110, and a demodulation unit 112. Here, the first antenna 134a, the second antenna 134b, and the nth antenna 134n are collectively referred to as the antenna 134.

  Modulation section 102 modulates an information signal to be transmitted and generates a transmission signal (hereinafter, one signal included in the transmission signal is also referred to as “symbol”). The modulation method may be an arbitrary Q such as QPSK (Qudri Phase Shift Keying), 16 QAM (16 Quadrature Amplitude Modulation), GMSK (Gaussian filtered Minimum Shift Keying), or the like. Further, in the case of multicarrier communication, the transmitter 100 is provided with a plurality of modulation units 102 or inverse Fourier transform units, and in the case of spread spectrum communication, the modulation unit 102 is provided with a spreading unit.

The RF unit 104 converts the transmission signal into a radio frequency signal. A frequency converter, a power amplifier, a frequency oscillator, and the like are included.
The antenna 132 of the transmission device 100 transmits a radio frequency signal. The antenna directivity and the number of antennas may be arbitrary.

The antenna 134 of the reception device 106 receives a radio frequency signal. In the present embodiment, when the number of antennas is n and “nth” is written in the constituent elements, the constituent elements exist as many as the number of antennas, and these basically execute the same operation in parallel.
The RF unit 108 converts a radio frequency signal into a baseband received signal 300. The RF unit 108 is provided with a frequency oscillator or the like, a Fourier transform unit is provided in the case of multicarrier communication, and a despreading unit is provided in the case of spread spectrum communication.

The signal processing unit 110 weights and combines the baseband received signals 300 with weighting factors, and adaptively controls each weighting factor.
The demodulator 112 demodulates the combined signal and determines the transmitted information signal. The demodulation unit 112 may be provided with a delay detection circuit and a carrier recovery circuit for synchronous detection.

  2 and 3 correspond to the communication system of FIG. 1, but are burst formats used in different communication systems, and training signals and data signals included therein are also shown. FIG. 2 is a burst format used in a call channel of a simple telephone system. A preamble for use in timing synchronization is arranged between four symbols from the beginning of the burst. Since the preamble and unique word signals are known signals to the signal processing unit 110, the signal processing unit 110 can use the preamble and unique word as training signals. The data and CRC following the preamble and the unique word are signals unknown to the signal processing unit 110 and correspond to data signals.

  FIG. 3 shows a burst format used in an IEEE802.11a speech channel of a wireless LAN (Local Area Network). IEEE802.11a uses an OFDM (Orthogonal Frequency Division Multiplexing) modulation scheme, and the OFDM modulation scheme generally uses the sum of the size of the Fourier transform and the number of symbols in the guard interval as one unit. This one unit is an OFDM symbol in this embodiment. A preamble mainly used for timing synchronization and carrier reproduction is arranged between 4 OFDM symbols from the head of the burst. Since the preamble signal is a known signal to the signal processing unit 110, the signal processing unit 110 can use the preamble as a training signal. Subsequent headers and data are signals unknown to the signal processing unit 110 and correspond to data signals.

  FIG. 4 shows the configuration of the receiving apparatus 106 shown in FIG. The RF unit 108 includes a first pre-processing unit 114a, a second pre-processing unit 114b, and an n-th pre-processing unit 114n that are collectively referred to as a pre-processing unit 114. The signal processing unit 110 is a first BB that is collectively referred to as a BB input unit 116. Input unit 116a, second BB input unit 116b, nBB input unit 116n, combining unit 118, weight calculation unit 120, first weight calculation unit 120a, second weight calculation unit 120b, nth weight calculation unit 120n, rise detection Unit 122, control unit 124, training signal storage unit 126, antenna determination unit 10, initial weight data setting unit 12, gap measurement unit 14, gap correction unit 16, weight switching unit 18, and demodulation unit 112 includes a synchronous detection unit 20, a determination unit 128, and an addition unit 130.

  Further, as signals, a first baseband received signal 300a, a second baseband received signal 300b, an nth baseband received signal 300n, a training signal 302, a control signal 306, an error signal 308, a control, which are collectively referred to as a baseband received signal 300, are provided. The first control weight coefficient 310a, the second control weight coefficient 310b, the nth control weight coefficient 310n, the antenna selection signal 314, the gap error signal 316, and the update weight coefficient 318, collectively referred to as the weight coefficient 310 , Second update weighting factor 318b, nth updating weighting factor 318n, first initial weighting factor 320a collectively referred to as initial weighting factor 320, second initial weighting factor 320b, nth initial weighting factor 320n, and weighting factor 322. 1 weight coefficient 322a, 2nd weight coefficient 322b, nth weight coefficient 322n Including.

The preprocessing unit 114 converts the radio frequency signal into the baseband reception signal 300.
The rising edge detection unit 122 detects the head of the burst signal that triggers the operation of the signal processing unit 110 from the baseband received signal 300. The start timing of the detected burst signal is reported to the control unit 124, and the control unit 124 calculates the end timing of the training signal 302 section from the start timing, and uses these timings as the control signal 306 to each unit as necessary. Notice.

  The antenna determination unit 10 measures the power of the baseband received signal 300 after starting the training signal 302 section in order to select one antenna 134 to be enabled in the training signal 302 section, and then selects one antenna that has the maximum power. Baseband received signal 300 is determined. Further, this information is output as an antenna selection signal 314.

  The initial weight data setting unit 12 sets the weighting coefficient 322 used in the training signal 302 section as the initial weighting coefficient 320. The initial weight data setting unit 12 validates only one initial weight coefficient 320 by setting only one value in the initial weight coefficient 320 to 1 and setting the remaining value to 0. One initial weighting factor 320 to be validated is determined corresponding to the antenna selection signal 314.

The training signal storage unit 126 stores the training signal 302 and outputs the training signal 302 as necessary.
The weight calculation unit 120 updates the control weight coefficient 310 by the LMS algorithm based on the baseband received signal 300 and an error signal 308 described later.

ここで、ｈｉは、無線区間の応答特性、Ｓ（ｔ）は送信信号、Δωは送信装置１００と受信装置１０６の周波数発振器の周波数偏差、ｎｉ（ｔ）は雑音を示す。一方、バースト信号の先頭から更新した制御重み係数３１０ｗｉは、以下の通りである。ここで、制御重み係数３１０は十分収束しているものとする。

これをもとに、合成処理を行うと、合成結果は、以下の通りである。

これらを比較すると、ギャップ誤差信号３１６Ｃは以下の通り表される。

ギャップ補正部１６は、制御重み係数３１０をギャップ誤差信号３１６で補正して、その結果の更新重み係数３１８を出力する。 Based on the baseband received signal 300 and the training signal 302, the gap measuring unit 14 uses the initial weighting coefficient 320 in the combining process with the baseband received signal 300 in the combining unit 118 described later, and the control weight. Predict gaps in the resulting composite when using coefficient 310. The synthesis result when the initial weighting factor 320 is used is the baseband reception signal 300 itself for one antenna 134, and is as follows. Here, let one antenna 134 be the i-th antenna 134.

Here, hi is a response characteristic in a radio section, S (t) is a transmission signal, Δω is a frequency deviation of the frequency oscillators of the transmission device 100 and the reception device 106, and ni (t) is noise. On the other hand, the control weight coefficient 310wi updated from the head of the burst signal is as follows. Here, it is assumed that the control weight coefficient 310 has sufficiently converged.

Based on this, when the synthesis process is performed, the synthesis result is as follows.

When these are compared, the gap error signal 316C is expressed as follows.

The gap correction unit 16 corrects the control weight coefficient 310 with the gap error signal 316 and outputs an update weight coefficient 318 as a result.

Based on the instruction of the control signal 306, the weight switching unit 18 selects the initial weight coefficient 320 in the training signal 302 section, selects the update weight coefficient 318 in the data signal section, and outputs it as the weight coefficient 322.
The synthesizer 118 weights the baseband received signal 300 with the weighting coefficient 322 and then adds them.

The synchronous detection unit 20 performs synchronous detection on the synthesized signal and also performs carrier regeneration necessary for synchronous detection.
The determination unit 128 determines the transmitted information signal by comparing the synchronously detected signal with a predetermined threshold value. The determination may be a hard determination or a soft determination.
The adder 130 generates an error signal 308 for use in the LMS algorithm of the weight calculator 120 based on the difference between the signal determined to be the synchronously detected signal and the signal. Since the LMS algorithm controls the control weighting factor 310 so that the error signal 308 is small, in an ideal state, the error signal 308 is zero.

  5 to 7 show various configurations of the first preprocessing unit 114a. Differences between the different communication systems shown in FIG. 2 and FIG. 3 are absorbed by the first preprocessing unit 114a in the receiving apparatus 106, and the subsequent signal processing unit 110 generally operates without being aware of the difference in the communication systems. It becomes possible. The first preprocessing unit 114a in FIG. 5 corresponds to the single carrier communication system such as the simple telephone system and the mobile phone shown in FIG. 2, and includes a frequency conversion unit 136, a quasi-synchronous detection unit 138, and an AGC 140 (Automatic Gain Control). , An AD converter 142, and a timing detector 144. 6 corresponds to a spread spectrum communication system such as a wireless LAN compliant with W-CDMA (Wideband-Code Division Multiple Access) or IEEE802.11b, and a despreading unit 172 is added. . 7 corresponds to a multicarrier communication system such as IEEE802.11a or HiperLAN / 2 shown in FIG. 3, and a Fourier transform unit 174 is added.

The frequency converter 136 converts a radio frequency signal into one or a plurality of intermediate frequency signals.
The quasi-synchronous detection unit 138 performs quadrature detection of the intermediate frequency signal using a frequency oscillator, and generates a baseband analog signal. Since the frequency oscillator included in the quasi-synchronous detection unit 138 operates independently of the frequency oscillator in the transmission apparatus 100, the frequency between the two frequency oscillators is generally different.

The AGC 140 automatically controls the gain in order to make the amplitude of the baseband analog signal within the dynamic range of the AD conversion unit 142.
The AD conversion unit 142 converts a baseband analog signal into a digital signal. The sampling interval for converting to a digital signal is usually set shorter than the symbol interval in order to suppress signal degradation due to digitization. Here, the sampling interval is ½ of the symbol interval (hereinafter, a signal digitized at this sampling interval is referred to as a “high-speed digital signal”).

The timing detection unit 144 selects the baseband reception signal 300 having the optimum sampling timing from the high-speed digital signal. Alternatively, processing such as synthesis is performed on the high-speed digital signal, and the baseband reception signal 300 having the optimum sampling timing is generated.
The despreading unit 172 in FIG. 6 performs correlation processing on the baseband received signal 300 with a predefined code sequence. The Fourier transform unit 174 in FIG. 7 performs Fourier transform on the baseband received signal 300.

  FIG. 8 shows a configuration of the timing detection unit 144. The timing detection unit 144 includes a first delay unit 146a, a second delay unit 146b, an n-1 delay unit 146n-1, a first multiplication unit 150a, and a second multiplication unit, which are collectively referred to as a delay unit 146. 150b, n-1th multiplication unit 150n-1, nth multiplication unit 150n, first data storage unit 152a, second data storage unit 152b, n-1th data storage unit 152n-1, collectively referred to as data storage unit 152, An n-th data storage unit 152n, an addition unit 154, a determination unit 156, a main signal delay unit 158, and a selection unit 160 are included.

The delay unit 146 delays the input high-speed digital signal for correlation processing. The sampling interval of the high-speed digital signal is ½ of the symbol interval, but since the delay amount of the delay unit 146 is set to the symbol interval, every other high-speed digital signal is output to the multiplier unit 150.
The data storage unit 152 stores one symbol of each preamble signal for timing synchronization.
The multiplier 150 multiplies the high-speed digital signal and the preamble signal, and the result is added by the adder 154.

  The determination unit 156 selects an optimal sampling timing based on the addition result. The sampling interval of the high-speed digital signal is 1/2 of the symbol interval, and the interval of the high-speed digital signal used for addition is the symbol interval, so the addition result for every other high-speed digital signal shifts one sampling timing. There are two types. The determination unit 156 compares the two types of addition results, and determines the timing with the larger addition result as the optimum sampling timing. Note that this determination need not be made by a single comparison, but may be made based on the results of several comparisons.

The main signal delay unit 158 delays the high-speed digital signal until the determination unit 156 determines the optimum sampling timing.
The selection unit 160 selects the baseband reception signal 300 corresponding to the optimum sampling timing from the high-speed digital signal. Here, one of two consecutive high-speed digital signals is sequentially selected.

FIG. 9 shows the configuration of the rising edge detection unit 122 included in the signal processing unit 110. The rising edge detection unit 122 includes a power calculation unit 162 and a determination unit 164.
The power calculation unit 162 calculates the received power of each baseband received signal 300 and sums them to obtain the power of signals received by all the antennas 134.
The determination unit 164 compares the received power with a predetermined condition, and determines that the head of the burst signal has been detected when the condition is satisfied.

  FIG. 10 shows the operation of the rising edge detection unit 122. The determination unit 164 sets the internal counter T to zero (S10). The power calculator 162 calculates received power from the baseband received signal 300 (S12). The determination unit 164 compares the received power with a threshold value, and if greater than the threshold value (Y in S14), adds 1 to T (S16). When T becomes larger than the prescribed value τ (Y in S18), it is assumed that the head of the burst signal is detected. The above processing is repeated until the head of the burst signal is detected (N in S14, N in S18).

FIG. 11 shows the configuration of the antenna determination unit 10. The antenna determination unit 10 includes a first level measurement unit 22a, a second level measurement unit 22b, an nth level measurement unit 22n, and a selection unit 24, which are collectively referred to as a level measurement unit 22.
The level measuring unit 22 recognizes the start timing of the burst signal from the control signal 306, and measures the power of the baseband received signal 300 for a predetermined period from the start timing.

The selection unit 24 selects the baseband reception signal 300 having the maximum power by comparing the power with respect to each baseband reception signal 300, and outputs the result as the antenna selection signal 314.
FIG. 12 shows the configuration of the first weight calculation unit 120a. The first weight calculation unit 120a includes a switching unit 48, a complex conjugate unit 50, a main signal delay unit 52, a multiplication unit 54, a step size parameter storage unit 56, a multiplication unit 58, an addition unit 60, and a delay unit 62.

The switching unit 48 recognizes the start timing of the burst signal and the end timing of the training signal 302 section from the control signal 306, thereby selecting the training signal 302 in the training signal 302 section and selecting the error signal 308 in the data signal section. .
The main signal delay unit 52 delays the first baseband reception signal 300a in order to synchronize with the timing detected by the rising edge detection unit 122.

The multiplier 54 multiplies the training signal 302 or the error signal 308 complex-conjugate-transformed by the complex conjugate unit 50 and the first baseband received signal 300a delayed by the main signal delay unit 52, and the first multiplication result is obtained. Generate.
The multiplication unit 58 multiplies the first multiplication result by the step size parameter stored in the step size parameter storage unit 56 to generate a second multiplication result. The second multiplication result is fed back by the delay unit 62 and the addition unit 60 and then added to the new second multiplication result, and the addition result is sequentially updated by the LMS algorithm. The addition result is output as the first control weight coefficient 310a.

FIG. 13 shows the configuration of the gap measuring unit 14. The gap measurement unit 14 includes a complex conjugate unit 44, a selection unit 64, a buffer unit 66, and a multiplication unit 68.
Based on the antenna selection signal 314, the selection unit 64 selects the baseband received signal 300 corresponding to one initial weight coefficient 320 that is enabled in the training signal 302 section.

The buffer unit 66 recognizes the start timing of the burst signal from the control signal 306 and outputs the baseband reception signal 300 at the start timing.
The multiplier 68 multiplies the training signal 302 that has been subjected to the complex conjugate process by the complex conjugate unit 44 and one baseband received signal 300 output from the buffer unit 66, and outputs a gap error signal 316. Here, it is assumed that the training signal 302 and the baseband received signal 300 are both head signals of the burst signal.

FIG. 14 shows the configuration of the gap correction unit 16. The gap correction unit 16 includes a first multiplication unit 70a, a second multiplication unit 70b, and an nth multiplication unit 70n collectively referred to as a multiplication unit 70.
The multiplier 70 recognizes the end timing of the training signal 302 section from the control signal 306, multiplies the control weight coefficient 310 and the gap error signal 316 in the data signal section, and outputs an update weight coefficient 318.

  FIG. 15 shows the configuration of the synthesis unit 118. The combining unit 118 includes a first delay unit 166a, a second delay unit 166b, an n-th delay unit 166n, and a multiplication unit 168, which are collectively referred to as a delay unit 166, a first multiplication unit 168a, a second multiplication unit 168b, and an n-th multiplication. Part 168n and adding part 170.

The delay time of the delay unit 166 is a time from when the leading edge of the burst signal is detected by the rising edge detection unit 122 to when the weighting coefficient 322 is set via the weight switching unit 18 from the initial weight data setting unit 12. The processing delay is not a problem. For this reason, a compositing process with a small processing delay is realized.
Multiplier 168 multiplies baseband received signal 300 delayed by delay unit 166 and weighting factor 322. Adder 170 adds all the multiplication results.

  The operation of the receiving apparatus 106 configured as above is as follows. Signals received by the plurality of antennas 134 are converted into a baseband received signal 300 by quadrature detection or the like. When the rising edge detection unit 122 detects the start timing of the burst signal from the baseband received signal 300, the training signal 302 section is started. At the start timing of the training signal 302 section, the antenna determining unit 10 selects one baseband received signal 300, and the initial weight data setting unit 12 invalidates other than the initial weight coefficient 320 corresponding to the selected baseband received signal 300. The initial weight coefficient 320 is set.

  In the training signal 302 section, the weight switching unit 18 outputs the initial weighting factor 320 as the weighting factor 322, and the synthesizing unit 118 adds the baseband received signal 300 weighted by the weighting factor 322. During this time, the weight calculation unit 120 updates the control weight coefficient 310 using the LMS algorithm. In the data signal section, the gap correction unit 16 corrects the control weight coefficient 310 with the gap error signal 316 calculated by the gap measurement unit 14 and outputs it as an update weight coefficient 318. Further, the weight switching unit 18 outputs the update weighting factor 318 as the weighting factor 322, and the synthesizing unit 118 adds the weighted baseband received signal 300 with the weighting factor 322.

  According to the first embodiment, the processing delay can be reduced because the synthesizing process is executed in the training signal section regardless of the convergence of the weighting factor. Moreover, since the omni antenna pattern is used for the weighting coefficient of the training signal section, it is possible to communicate with surrounding radio stations. In addition, the switching of the weighting factor between the omni antenna pattern and the adaptive antenna pattern can be performed smoothly.

(Embodiment 2)
In the second embodiment, similarly to the first embodiment, the weighting coefficient for weighting the received signal is changed by switching the prepared omni antenna pattern and the adaptive array antenna pattern updated by the LMS algorithm. Are weighted with a weighting coefficient with almost no delay. In the first embodiment, switching between the two types of weighting factors is performed uniformly at the timing when the training signal included in the burst signal ends. On the other hand, in the second embodiment, switching between the two types of weighting factors is adaptively performed at a timing when the LMS algorithm converges to a predetermined range.

  FIG. 16 shows the configuration of receiving apparatus 106 according to Embodiment 2. The configuration is almost the same as that of the receiving apparatus 106 in FIG. 4, but includes first convergence information 324a, second convergence information 324b, and nth convergence information 324n, which are collectively referred to as convergence information 324, as signals.

  The weight switching unit 18 in FIG. 4 selects the initial weighting coefficient 320 in the training signal 302 section and performs the switching operation using the end timing of the initial weighting coefficient 320 section as a trigger so as to select the update weighting coefficient 318 in the data signal section. Is going. The weight switching unit 18 in FIG. 16 sets the trigger of the switching operation as the timing when the control weight coefficient 310 in the weight calculation unit 120 converges. This convergence timing is generated by the control unit 124 when a range with respect to the fluctuation of the control weight coefficient 310 is determined in advance, and the fluctuation due to the update of the control weight coefficient 310 converges within the range. Alternatively, the convergence timing may be generated by the control unit 124 when a range for the error signal 308 is determined in advance and the updated error signal 308 falls within the range.

The control unit 124 notifies the convergence timing to each unit as necessary, and each unit executes each operation based on the timing.
FIG. 17 shows the configuration of the antenna determination unit 10. The antenna determination unit 10 includes a switching unit 72, a level measurement unit 74, a storage unit 76, and a selection unit 24.

The switching unit 72 sequentially switches a plurality of baseband reception signals 300 at a predetermined timing, and outputs one baseband reception signal 300. This switching may be performed across a plurality of burst signals.
The level measuring unit 74 measures the power of the baseband received signal 300 selected by the switching unit 72. Unlike the antenna determination unit 10 in FIG. 11, the power of the plurality of baseband reception signals 300 is not measured at the same time, but is measured one by one, so the arithmetic circuit for the level measurement unit 74 becomes small.
The storage unit 76 stores the calculated power of the baseband received signal 300.

  FIG. 18 shows the configuration of the gap measuring unit 14. The gap measurement unit 14 in FIG. 18 includes a frequency error estimation unit 78, a period measurement unit 80, a multiplication unit 82, a complex number conversion unit 84, a complex conjugate unit 86, and a multiplication unit 88 in addition to the gap measurement unit 14 in FIG. Yes.

ここで、ｓＴは、ショートプリアンブル区間の時間を示す。これをもとに、合成処理を行うと、合成結果は、以下の通りである。

これらを比較すると、ギャップ誤差信号３１６Ｃは以下の通り表される。

周波数誤差推定部７８は、ベースバンド受信信号３００をもとに周波数誤差Δωを推定する。期間測定部８０は、トレーニング信号３０２からショートプリアンブルの区間の時間ｓＴを測定する。 The second embodiment is different from the first embodiment in that the timing at which the weight calculation unit 120 starts updating the control weight coefficient 310 is the head of the long preamble in the burst format shown in FIG. The control weighting coefficient 310wi updated from the head of the long preamble is as follows. Here, it is assumed that the control weight coefficient 310 has sufficiently converged.

Here, sT indicates the time of the short preamble section. Based on this, when the synthesis process is performed, the synthesis result is as follows.

When these are compared, the gap error signal 316C is expressed as follows.

The frequency error estimator 78 estimates the frequency error Δω based on the baseband received signal 300. The period measuring unit 80 measures the time sT of the short preamble section from the training signal 302.

The multiplier 82 multiplies the frequency error and the time of the short preamble section to obtain a phase error in the short preamble section. This phase error is converted into a complex number by the complex number conversion unit 84, and complex conjugate processing is performed by the complex conjugate unit 86.
Multiplier 88 multiplies the multiplication result of one baseband received signal 300 and training signal 302 that has been subjected to complex conjugate processing, and the above-described converted phase error to generate gap error signal 316.

  FIG. 19 shows the configuration of the frequency error estimator 78. The frequency error estimation unit 78 includes a first main signal delay unit 26a, a second main signal delay unit 26b, an n-th main signal delay unit 26n, and a first multiplication unit 28a, which are collectively referred to as a main signal delay unit 26. , Second multiplier 28b, nth multiplier 28n, first delay unit 30a collectively referred to as delay unit 30, second delay unit 30b, nth delay unit 30n, and first complex conjugate unit 32a collectively referred to as complex conjugate unit 32. , Second complex conjugate unit 32b, nth complex conjugate unit 32n, first multiplication unit 34a, second multiplication unit 34b, nth multiplication unit 34n, averaging unit 36, phase conversion unit 38, training signal. A storage unit 42 is included.

ここで、雑音は十分小さいとして、雑音に関する項を無視した。 The multiplier 28 multiplies the baseband received signal 300 delayed by the main signal delay unit 26 and the training signal subjected to complex conjugate transformation to obtain a received signal Zi (t) that does not include a transmission signal component.

Here, assuming that the noise is sufficiently small, the term relating to noise was ignored.

ここで、遅延部３０の遅延時間をシンボル間隔Ｔとした。
平均部３６は、各アンテナに対応する乗算結果を平均する。さらに、時間をシフトさせた乗算結果を使用してもよい。 The delay unit 30 and the complex conjugate unit 32 delay Zi (t) and then convert it into a complex conjugate. The converted signal and Zi (t) are multiplied by the multiplication unit 34. The multiplication result Ai is as follows.

Here, the delay time of the delay unit 30 is defined as a symbol interval T.
The averaging unit 36 averages the multiplication results corresponding to the respective antennas. Further, a multiplication result obtained by shifting the time may be used.

図２０は、図１８と異なるギャップ測定部１４の構成を示す。図２０のギャップ測定部１４は、図１８のギャップ測定部１４に、カウンタ部９０、乗算部９２、複素数変換部９４、積算部９６、積算部９８、除算部４０が付加されている。ベースバンド受信信号３００とトレーニング信号３０２の乗算が、図１８のギャップ測定部１４においては、バースト信号の先頭信号のみで実行されるのに対して、図２０のギャップ測定部１４においては、所定時間実行され、その結果が平均化される。 The phase conversion unit 38 converts the averaged multiplication result A into a phase signal B using an arctangent ROM.

FIG. 20 shows a configuration of the gap measuring unit 14 different from that in FIG. A gap measuring unit 14 in FIG. 20 includes a counter unit 90, a multiplying unit 92, a complex number converting unit 94, an integrating unit 96, an integrating unit 98, and a dividing unit 40 in addition to the gap measuring unit 14 in FIG. While the multiplication of the baseband received signal 300 and the training signal 302 is executed only with the head signal of the burst signal in the gap measuring unit 14 in FIG. 18, the gap measuring unit 14 in FIG. And the results are averaged.

The integration unit 98 integrates the multiplication results for a predetermined time (hereinafter referred to as “averaged time”) in order to average the multiplication results of the baseband reception signal 300 and the training signal 302.
The counter unit 90 counts up the symbol interval in order to obtain the phase error corresponding to the averaging time from the frequency error output from the frequency error estimation unit 78. The multiplier 92 multiplies the counter value by the frequency error for each counter value to obtain a phase error for each counter value. The phase error is converted into a complex number by the complex number conversion unit 94 and accumulated by the accumulation unit 96 during the averaging time.
The division unit 40 divides the multiplication result accumulated by the accumulation unit 98 by the phase error accumulated by the accumulation unit 96. The subsequent steps are the same as those of the gap measuring unit 14 in FIG.

  The operation of the receiving apparatus 106 configured as above is as follows. Signals received by the plurality of antennas 134 are converted into a baseband received signal 300 by quadrature detection or the like. When the rising edge detection unit 122 detects the leading timing of the burst signal from the baseband received signal 300, the training signal 302 section is started. At the start timing of the training signal 302 section, the antenna determining unit 10 selects one baseband received signal 300, and the initial weight data setting unit 12 invalidates other than the initial weight coefficient 320 corresponding to the selected baseband received signal 300. The initial weight coefficient 320 is set. Thereafter, the weight switching unit 18 outputs the initial weighting coefficient 320 as the weighting coefficient 322, and the synthesizing unit 118 adds the weighted baseband received signal 300 with the weighting coefficient 322.

  During this time, the weight calculation unit 120 updates the control weight coefficient 310 using the LMS algorithm. When the control weight coefficient 310 converges to a predetermined range, the gap correction unit 16 corrects the control weight coefficient 310 with the gap error signal 316 calculated by the gap measurement unit 14 in accordance with an instruction from the control unit 124, and serves as an update weight coefficient 318. Output. Further, the weight switching unit 18 outputs the update weighting factor 318 as the weighting factor 322, and the synthesizing unit 118 adds the weighted baseband received signal 300 with the weighting factor 322.

According to the second embodiment, the processing delay can be reduced because the synthesizing process is executed in the training signal section regardless of the convergence of the weighting factor. In addition, since switching between the two types of weighting factors is performed based on the convergence timing of the adaptive algorithm, when the adaptive algorithm converges during the training signal period, it can be reflected in the weighting factors to improve reception characteristics.
The present invention has been described based on the embodiments. This embodiment is an exemplification, and it will be understood by those skilled in the art that various modifications can be made to combinations of the respective constituent elements and processing processes, and such modifications are also within the scope of the present invention. is there.

  In the embodiment, the initial weight data setting unit 12 sets an effective value for the initial weighting coefficient 320 corresponding to one baseband reception signal 300 having the maximum power selected by the antenna determination unit 10, The rest set invalid values. However, the value of the initial weight coefficient 320 need not be set based on the power. For example, one initial weight coefficient 320 may be fixedly set to an effective value, and the rest may be set to an invalid value. In that case, the antenna determination unit 10 becomes unnecessary.

  In the embodiment, the initial weight data setting unit 12 sets an effective value for the initial weighting coefficient 320 corresponding to one baseband reception signal 300 having the maximum power selected by the antenna determination unit 10, The rest set invalid values. However, the initial weighting coefficient 320 may not be set to have a weight that provides an omni antenna pattern. For example, the update weighting factor 318 or the control weighting factor 310 used for the already received burst signal may be set. When the fluctuation of the radio propagation environment is small, it is considered that there is little deterioration in reception characteristics even with such a setting.

  In the embodiment, the weight calculation unit 120 uses an LMS algorithm as an adaptive algorithm. However, other RLS algorithms or the like may be used, and the weighting coefficient may not be updated. In other words, the selection may be made according to the assumed radio propagation environment, arithmetic circuit scale, and the like.

  In the first embodiment, the rising edge detection unit 122 calculates the power of the baseband received signal 300 and detects the rising edge of the burst signal based on the calculated power. However, the rising edge detection of the burst signal may be realized by a configuration other than this. For example, it can be detected by a matched filter shown as the configuration of the timing detection unit 144. That is, it is only necessary to accurately detect the rising edge of the burst signal.

  In the first embodiment, the time when the initial weighting factor 320 is the weighting factor 322 is set as the training signal interval. However, the present invention is not limited to this. For example, the time may be shorter than the training signal interval. That is, it may be set according to the length of the training signal section and the required estimation accuracy.

  In the second embodiment, the delay time of the delay unit 30 included in the frequency error estimation unit 78 is one symbol. However, this delay time is not limited to this. For example, the interval between two symbols or the first and last symbols of the training signal may be used. That is, the delay time of the delay unit 30 may be optimized depending on the stability of the frequency oscillator and the required frequency deviation estimation accuracy.

1 is a configuration diagram showing a communication system according to Embodiment 1. FIG. 6 is a diagram showing a burst format according to Embodiment 1. FIG. 6 is a diagram showing a burst format according to Embodiment 1. FIG. 2 is a diagram illustrating a configuration of a receiving apparatus according to Embodiment 1. FIG. It is a figure which shows the structure of the 1st pre-processing part of FIG. It is a figure which shows the structure of the 1st pre-processing part of FIG. It is a figure which shows the structure of the 1st pre-processing part of FIG. It is a figure which shows the structure of the timing detection part of FIG. It is a figure which shows the structure of the standup detection part of FIG. It is a figure which shows the procedure of operation | movement of the standup detection part of FIG. It is a figure which shows the structure of the antenna determination part of FIG. It is a figure which shows the structure of the 1st weight calculation part of FIG. It is a figure which shows the structure of the gap measurement part of FIG. It is a figure which shows the structure of the gap correction | amendment part of FIG. It is a figure which shows the structure of the synthetic | combination part of FIG. 6 is a diagram showing a configuration of a receiving apparatus according to Embodiment 2. FIG. It is a figure which shows the structure of the antenna determination part of FIG. It is a figure which shows the structure of the gap measurement part of FIG. It is a figure which shows the structure of the frequency error estimation part of FIG. It is a figure which shows the structure of the gap measurement part of FIG.

Explanation of symbols

  DESCRIPTION OF SYMBOLS 10 Antenna determination part, 12 Initial weight data setting part, 14 Gap measurement part, 16 Gap correction part, 18 Weight switching part, 20 Synchronous detection part, 100 Transmission apparatus, 102 Modulation part, 104 RF part, 106 Reception apparatus, 108 RF 110, signal processing unit, 112 demodulating unit, 114 preprocessing unit, 116 BB input unit, 118 synthesis unit, 120 weight calculation unit, 122 rise detection unit, 124 control unit, 126 training signal storage unit, 128 determination unit, 130 Adder, 132 antenna, 134 antenna, 300 baseband received signal, 302 training signal, 306 control signal, 308 error signal, 310 control weight factor, 314 antenna selection signal, 316 gap error signal, 3 18 update weighting factor, 320 initial weighting factor, 322 weighting factor, 324 convergence information.

Claims (12)

A first signal from the first antenna terminal, a second signal from the second antenna terminal, and a first signal and a second signal that are at least one burst signal having a training portion and a data portion. Inputting each from the transmitting device;
Using the first combination of weighting factors to select the first signal or the second signal;
Determining a second combination of weighting factors in a period of using the first combination of weighting factors;
Applying a second combination of weighting factors to array synthesis after a period of using the first combination of weighting factors;
A receiving method comprising: Detecting a first rising edge from the first signal;
Detecting a second rising edge from the second signal;
Generating a timing control signal based on the first rising edge or the second rising edge;
The receiving method according to claim 1, further comprising: Measuring the channel response of the first signal or the second signal;
Using the measured channel response to generate a gap error signal to correct the phase gap in the output signal of the array synthesizer;
The receiving method according to claim 1, further comprising:   4. The receiving method according to claim 3, further comprising the step of updating the second combination of weighting factors based on the gap error signal. A first signal from a first antenna and a second signal from a second antenna, and a first signal and a second signal which are at least one burst signal having a training portion and a data portion. Receiving each from
Using the first combination of weighting factors to select the first signal or the second signal;
Determining a second combination of weighting factors in a period of using the first combination of weighting factors;
Applying a second combination of weighting factors to array synthesis after a period of using the first combination of weighting factors;
A receiving method comprising: A first signal from the first antenna terminal, a second signal from the second antenna terminal, and a first signal and a second signal that are at least one burst signal having a training portion and a data portion. An input unit for inputting from each transmission device;
An initial weight data setting unit that uses the first combination of weighting factors to select the first signal or the second signal;
A weight calculation unit that determines a second combination of weighting factors in a period in which the first combination of weighting factors is used;
A weight switching unit that applies the second combination of weighting factors to array synthesis after the period of using the first combination of weighting factors;
A receiving apparatus comprising:   A rising edge detection unit that detects a first rising edge from the first signal, detects a second rising edge from the second signal, and generates a timing control signal based on the first rising edge or the second rising edge; The receiving device according to claim 6, further comprising:   A gap measuring unit that uses the measured channel response to measure a channel response of the first signal or the second signal and generate a gap error signal to correct a phase gap in the output signal of the array synthesizer; The receiving apparatus according to claim 6.   9. The receiving apparatus according to claim 8, further comprising a gap correction unit that updates the second combination of weighting factors based on the gap error signal. A first antenna and a second antenna;
A first signal from the first antenna, a second signal from the second antenna, and a first signal and a second signal that are at least one burst signal having a training portion and a data portion. An input unit respectively receiving from the transmission device;
An initial weight data setting unit that uses the first combination of weighting factors to select the first signal or the second signal;
A weight calculation unit that determines a second combination of weighting factors in a period in which the first combination of weighting factors is used;
A weight switching unit that applies the second combination of weighting factors to array synthesis after the period of using the first combination of weighting factors;
A receiving apparatus comprising: A first antenna and a second antenna;
A first signal from the first antenna, a second signal from the second antenna, and a first signal and a second signal that are at least one burst signal having a training portion and a data portion. An input unit respectively receiving from the transmission device;
An initial weight data setting unit that uses the first combination of weighting factors to select the first signal or the second signal;
A weight calculation unit that determines a second combination of weighting factors in a period in which the first combination of weighting factors is used;
A weight switching unit that applies the second combination of weighting factors to array synthesis after the period of using the first combination of weighting factors;
A wireless mobile station equipped with a receiving device. A first antenna and a second antenna;
A first signal from the first antenna, a second signal from the second antenna, and a first signal and a second signal that are at least one burst signal having a training portion and a data portion. An input unit respectively receiving from the transmission device;
An initial weight data setting unit that uses the first combination of weighting factors to select the first signal or the second signal;
A weight calculation unit that determines a second combination of weighting factors in a period in which the first combination of weighting factors is used;
A weight switching unit that applies the second combination of weighting factors to array synthesis after the period of using the first combination of weighting factors;
A wireless device equipped with a receiving device.

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