JP2006288182A - Electric power supply circuit of three-phase four-wire type distribution line equipped with harmonic reduction circuit and harmonic reduction method - Google Patents

Electric power supply circuit of three-phase four-wire type distribution line equipped with harmonic reduction circuit and harmonic reduction method Download PDF

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JP2006288182A
JP2006288182A JP2005213515A JP2005213515A JP2006288182A JP 2006288182 A JP2006288182 A JP 2006288182A JP 2005213515 A JP2005213515 A JP 2005213515A JP 2005213515 A JP2005213515 A JP 2005213515A JP 2006288182 A JP2006288182 A JP 2006288182A
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JP4801390B2 (en
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Tadayoshi Aizawa
愛澤忠良
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Nihon University
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    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02E—REDUCTION OF GREENHOUSE GAS [GHG] EMISSIONS, RELATED TO ENERGY GENERATION, TRANSMISSION OR DISTRIBUTION
    • Y02E40/00—Technologies for an efficient electrical power generation, transmission or distribution
    • Y02E40/30—Reactive power compensation
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02E—REDUCTION OF GREENHOUSE GAS [GHG] EMISSIONS, RELATED TO ENERGY GENERATION, TRANSMISSION OR DISTRIBUTION
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    • Y02E40/40—Arrangements for reducing harmonics

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Abstract

<P>PROBLEM TO BE SOLVED: To simplify the configuration of a harmonic reduction circuit for reducing the distorted wave current, on the basis of tertiary harmonic current of neutral line in a three-phase four-wire distribution line, and manufacture the harmonic reduction circuit at a low cost. <P>SOLUTION: Loads 7 are connected between distribution lines U, V, W for U-phase, V-phase, W-phase and a neutral line N. The loads 7 include capacitor input type rectifier circuit in which capacitors (smoothing capacitor) are connected to rectifying circuits 71. To the load 7, the harmonic reduction circuit 6 is connected in parallel. A harmonic reduction circuit 6 has thyristors SCR1, 2, a resistance rc, an inductance Lc, a capacitor C connected in series. The inductance Lc, the capacitor C constitute a resonance circuit. The resonance frequency of the resonance circuit, which is generated by the loads 7, is set at the same one as a frequency of a harmonic current flowing through the neutral line N. In addition, the phase of the current of the harmonic reduction circuit 6 is set to be reverse phase to tertiary harmonic current generated by the loads 7, by adjsuting the firing angles of the thyristors SCR1, 2. <P>COPYRIGHT: (C)2007,JPO&INPIT

Description

本願発明は、三相４線式配電線の中性線のひずみ波電流を低減して受電端電圧の波形ひずみを低減する高調波低減回路を備えた三相４線式配電線の電力供給回路と高調波低減方法に関する。   The present invention relates to a power supply circuit for a three-phase four-wire distribution line including a harmonic reduction circuit that reduces the distortion wave current of the neutral wire of the three-phase four-wire distribution line to reduce the waveform distortion of the receiving end voltage. And a harmonic reduction method.

三相４線式配電線には、半導体回路を内蔵した家電製品、パソコン等の電子機器、サイリスタ等を用いた位相制御型調光回路等が接続されている。半導体回路は、一般に交流を整流して得た直流電源により駆動しているが、その整流には、コンデンサ（平滑コンデンサ）を接続した整流回路、いわゆるコンデンサ入力型整流回路が用いられている。コンデンサ入力型整流回路の電流は、正弦波の中央部分（振幅のピーク付近）の比較的狭い範囲において流れるため、電流の通流幅が狭くなる。そのため高調波電流が発生し、その同相分の高調波電流が三相４線式配電線の中性線を流れるため電圧降下が生じ、受電端電圧に波形ひずみを生じる。そこでその高調波電流を低減するため、従来アクティブフィルタが用いられている（例えば特許文献１参照）。   Connected to the three-phase four-wire distribution line are home appliances with built-in semiconductor circuits, electronic devices such as personal computers, phase control type dimming circuits using thyristors and the like. A semiconductor circuit is generally driven by a direct current power source obtained by rectifying alternating current, and a rectifier circuit connected to a capacitor (smoothing capacitor), a so-called capacitor input type rectifier circuit, is used for the rectification. Since the current of the capacitor input type rectifier circuit flows in a relatively narrow range in the central part of the sine wave (near the peak of amplitude), the current flow width becomes narrow. Therefore, a harmonic current is generated, and the harmonic current of the same phase flows through the neutral line of the three-phase four-wire distribution line, so that a voltage drop occurs, and a waveform distortion occurs in the receiving end voltage. Therefore, in order to reduce the harmonic current, a conventional active filter has been used (see, for example, Patent Document 1).

図１１により従来のアクティブフィルタを用いた三相４線式配電線の電力供給回路を説明する。
図１１（ａ）は、三相交流電源に負荷とアクティブフィルタを接続した三相４線式配電線の電力供給回路を示し、図１１（ｂ）は、図１１（ａ）の一相分の電力供給回路を示す。
図１１（ａ）において、三相交流電源1は、Ｕ相、Ｖ相、Ｗ相の電源ｅU，ｅV，ｅWを有し、負荷３は、それらの電源から各相の配電線Ｕ，Ｖ，Ｗと中性線Ｎにより電力が供給される。負荷３の近傍には、アクティブフィルタ２を接続してある。アクティブフィルタ２は、波形変換回路２１、電流出力回路２２、補助電源回路２３、制御回路２４等を備えている。制御回路２４は、負荷電流検出部４１の検出電流から３次高調波成分を抽出して電流出力回路２２の制御信号を発生し、その制御信号により電流出力回路２２のＩＧＢＴ等のスイッチ素子の導通、非導通を制御する。電流出力回路２２は、補助電源回路２３を電源として矩形波を発生する。波形変換回路２１は、その矩形波を正弦波状の電流に変換して配電線Ｕ，Ｖ，Ｗと中性線Ｎの間に供給する。その正弦波状の電流は、負荷３を流れる電流に含まれる３次高調波電流に近似している。 A conventional power supply circuit for a three-phase four-wire distribution line using an active filter will be described with reference to FIG.
FIG. 11A shows a power supply circuit of a three-phase four-wire distribution line in which a load and an active filter are connected to a three-phase AC power source, and FIG. 11B shows one phase of FIG. 1 shows a power supply circuit.
In FIG. 11A, a three-phase AC power source 1 has U-phase, V-phase, and W-phase power sources e U , e V , and e W , and a load 3 receives a distribution line U for each phase from these power sources. , V, W and neutral wire N supply power. An active filter 2 is connected in the vicinity of the load 3. The active filter 2 includes a waveform conversion circuit 21, a current output circuit 22, an auxiliary power circuit 23, a control circuit 24, and the like. The control circuit 24 extracts a third-order harmonic component from the detection current of the load current detection unit 41 to generate a control signal for the current output circuit 22, and the control signal causes conduction of a switch element such as an IGBT of the current output circuit 22. Control non-conduction. The current output circuit 22 generates a rectangular wave using the auxiliary power supply circuit 23 as a power source. The waveform conversion circuit 21 converts the rectangular wave into a sinusoidal current and supplies it between the distribution lines U, V, W and the neutral line N. The sinusoidal current approximates the third harmonic current included in the current flowing through the load 3.

図１１（ｂ）において、制御回路２４は、負荷電流検出部４１の出力から３次高調波成分を抽出する３次高調波成分抽出回路２４１、出力電流検出部４２の出力と３次高調波成分抽出回路２４１の出力と補助制御回路２４２の出力とを演算する演算回路２４３、増幅回路２４４、増幅回路２４４の出力と三角波発生回路２４５の出力とを比較する比較回路２４６等を備えている。比較回路２４６の出力は、電流出力回路２２のＩＧＢＴ２２１へ直接供給するとともに、位相を反転してＩＧＢＴ２２２へ供給する。補助電源回路２３は、２個のコンデンサからなり、波形変換回路２１は、コンデンサとインダクタンスからなる。   In FIG. 11B, the control circuit 24 extracts a third harmonic component from the output of the load current detection unit 41, a third harmonic component extraction circuit 241, an output of the output current detection unit 42, and a third harmonic component. An arithmetic circuit 243 that calculates the output of the extraction circuit 241 and the output of the auxiliary control circuit 242, an amplifier circuit 244, a comparison circuit 246 that compares the output of the amplifier circuit 244 and the output of the triangular wave generation circuit 245 are provided. The output of the comparison circuit 246 is directly supplied to the IGBT 221 of the current output circuit 22 and is supplied to the IGBT 222 with the phase inverted. The auxiliary power supply circuit 23 includes two capacitors, and the waveform conversion circuit 21 includes a capacitor and an inductance.

特開２００２−１１８９６４号公報JP 2002-118964 A

図１１のように従来の三相４線式配電線の電力供給回路は、中性線の高調波電流を低減するためにアクティブフィルタを用いているが、アクティブフィルタは構成が複雑で高価になる。
本願発明は、この点に鑑み三相４線式配電線の電力供給回路において、中性線の高調波電流を低減する回路を簡単な構成の回路で実現し、安価に作製することを目的とする。 As shown in FIG. 11, the power supply circuit of the conventional three-phase four-wire distribution line uses an active filter to reduce the harmonic current of the neutral wire. However, the active filter is complicated and expensive. .
In view of this point, the invention of the present application aims to realize a circuit for reducing the harmonic current of a neutral wire in a power supply circuit of a three-phase four-wire distribution line with a simple configuration circuit and to manufacture it at low cost. To do.

本願発明は、その目的を達成するため、請求項１に記載の三相４線式配電線の電力供給回路は、スイッチング素子、抵抗、インダクタンス及びコンデンサを直列に接続してなり、負荷により発生する高調波電流と逆相の電流を発生する高調波低減回路を負荷に並列に接続してあることを特徴とする。
請求項２に記載の三相４線式配電線の電力供給回路は、請求項１に記載の電力供給回路において、前記スイッチング素子はサイリスタであることを特徴とする。
請求項３に記載の三相４線式配電線の電力供給回路は、請求項１又は請求項２に記載の電力供給回路において、前記スイッチング素子の点弧角を調整して前記高調波低減回路の電流の位相を調整できることを特徴とする。
請求項４に記載の三相４線式配電線の電力供給回路は、請求項１、請求項２又は請求項３に記載の電力供給回路において、前記高調波低減回路の共振回路の共振周波数を電源電圧の周波数より高い周波数に設定してあることを特徴とする。
請求項５に記載の三相４線式配電線の電力供給回路は、請求項４に記載の電力供給回路において、前記共振周波数を電源電圧の周波数の３倍の周波数に設定してあることを特徴とする。
請求項６に記載の三相４線式配電線の電力供給回路は、請求項４に記載の電力供給回路において、前記共振周波数を電源電圧の周波数の３倍以外の周波数に設定してあることを特徴とする。
請求項７に記載の三相４線式配電線の電力供給回路は、請求項４、請求項５又は請求項６に記載の電力供給回路において、前記高調波低減回路にバイアス回路を付加してあることを特徴とする。
請求項８に記載の三相４線式配電線の電力供給回路の高調波低減方法は、スイッチング素子、抵抗、インダクタンス及びコンデンサを直列に接続してなり、負荷に並列に接続した高調波低減回路の共振回路の共振周波数を電源電圧の周波数より高い周波数に設定し、負荷により発生する高調波電流と逆相の電流を発生して負荷により発生する高調波電流を打ち消すことを特徴とする。
請求項９に記載の三相４線式配電線の電力供給回路の高調波低減方法は、請求項８に記載の高調波低減方法において、前記スイッチング素子の点弧角を調整して前記高調波低減回路の電流の位相を調整することを特徴とする。
請求項１０に記載の三相４線式配電線の電力供給回路の高調波低減方法は、請求項８又は請求項９に記載の高調波低減方法において、前記共振周波数を電源電圧の周波数の３倍の周波数に設定することを特徴とする。
請求項１１に記載の三相４線式配電線の電力供給回路の高調波低減方法は、請求項８又は請求項９に記載の高調波低減方法において、前記共振周波数を電源電圧の周波数の３倍以外の周波数に設定することを特徴とする。
請求項１２に記載の三相４線式配電線の電力供給回路の高調波低減方法は、請求項８、請求項９、請求項１０又は請求項１１に記載の高調波低減方法において、前記高調波低減回路にバイアス回路を付加してあることを特徴とする。 In order to achieve the object of the present invention, a power supply circuit for a three-phase four-wire distribution line according to claim 1 is formed by connecting a switching element, a resistor, an inductance and a capacitor in series, and is generated by a load. A harmonic reduction circuit that generates a current having a phase opposite to that of the harmonic current is connected in parallel to the load.
The power supply circuit of the three-phase four-wire distribution line according to claim 2 is the power supply circuit according to claim 1, wherein the switching element is a thyristor.
The power supply circuit of the three-phase four-wire distribution line according to claim 3 is the power supply circuit according to claim 1 or 2, wherein the harmonic reduction circuit is configured by adjusting an ignition angle of the switching element. The phase of the current can be adjusted.
The power supply circuit of the three-phase four-wire distribution line according to claim 4 is the power supply circuit according to claim 1, 2, or 3, wherein the resonance frequency of the resonance circuit of the harmonic reduction circuit is set. The frequency is higher than the frequency of the power supply voltage.
The power supply circuit of the three-phase four-wire distribution line according to claim 5 is the power supply circuit according to claim 4, wherein the resonance frequency is set to a frequency that is three times the frequency of the power supply voltage. Features.
The power supply circuit of the three-phase four-wire distribution line according to claim 6 is the power supply circuit according to claim 4, wherein the resonance frequency is set to a frequency other than three times the frequency of the power supply voltage. It is characterized by.
The power supply circuit of the three-phase four-wire distribution line according to claim 7 is the power supply circuit according to claim 4, 5, or 6, wherein a bias circuit is added to the harmonic reduction circuit. It is characterized by being.
The harmonic reduction method of the power supply circuit of the three-phase four-wire distribution line according to claim 8, wherein a switching element, a resistor, an inductance, and a capacitor are connected in series and connected to a load in parallel. The resonance frequency of this resonance circuit is set to a frequency higher than the frequency of the power supply voltage, and a harmonic current generated by the load is generated in a phase opposite to that of the harmonic current generated by the load to cancel the harmonic current generated by the load.
The harmonic reduction method for the power supply circuit of the three-phase four-wire distribution line according to claim 9 is the harmonic reduction method according to claim 8, wherein the harmonic is adjusted by adjusting an ignition angle of the switching element. The phase of the current of the reduction circuit is adjusted.
The harmonic reduction method for the power supply circuit of the three-phase four-wire distribution line according to claim 10 is the harmonic reduction method according to claim 8 or 9, wherein the resonance frequency is 3 times the frequency of the power supply voltage. The frequency is set to double.
The harmonic reduction method for the power supply circuit of the three-phase four-wire distribution line according to claim 11 is the harmonic reduction method according to claim 8 or 9, wherein the resonance frequency is 3 times the frequency of the power supply voltage. The frequency is set to a frequency other than double.
The harmonic reduction method of the power supply circuit of the three-phase four-wire distribution line according to claim 12 is the harmonic reduction method according to claim 8, 9, 10, or 11, wherein A bias circuit is added to the wave reduction circuit.

本願発明は、高調波低減回路を、サイリスタ等のスイッチング素子、抵抗、インダクタンス及びコンデンサによって構成できるから、高調波低減回路は、従来のアクティブフィルタに比べて、構成が簡単になり安価に作製することができる。また本願発明の三相４線式配電線の電力供給回路は、高調波低減回路を負荷と並列に接続するだけで、負荷によって発生する高調波電流の打消し用電流を発生することができ、その高調波電流を打ち消すために高調波電流成分を抽出するための高調波電流成分抽出回路を設ける必要がない。   In the present invention, the harmonic reduction circuit can be configured by a switching element such as a thyristor, a resistor, an inductance, and a capacitor. Therefore, the harmonic reduction circuit is simpler and less expensive than a conventional active filter. Can do. In addition, the power supply circuit of the three-phase four-wire distribution line of the present invention can generate a current for canceling the harmonic current generated by the load by simply connecting the harmonic reduction circuit in parallel with the load. There is no need to provide a harmonic current component extraction circuit for extracting a harmonic current component in order to cancel the harmonic current.

本願発明は、高調波低減回路を構成するサイリスタの点弧角を変えるだけで、高調波電流打消し用電流の位相、即ち負荷からの高調波電流とのタイミングを簡単に調整することができる。
本願発明は、高調波低減回路の共振回路の共振周波数を、電源電圧の周波数の３倍又は３倍以外の周波数に設定することにより正弦波又は非正弦波の高調波電流打消し用電流を発生することができる。また高調波低減回路にバイアス回路を付加することにより、半波の立ち上り部分と下降部分とが非対称になる高調波電流打消し用電流を発生することができる。 In the present invention, the phase of the harmonic current cancellation current, that is, the timing of the harmonic current from the load, can be easily adjusted by simply changing the firing angle of the thyristor constituting the harmonic reduction circuit.
The present invention generates a sine wave or non-sinusoidal harmonic current canceling current by setting the resonance frequency of the resonance circuit of the harmonic reduction circuit to a frequency other than three times or three times the frequency of the power supply voltage. can do. Further, by adding a bias circuit to the harmonic reduction circuit, it is possible to generate a harmonic current canceling current in which the rising and falling portions of the half wave are asymmetric.

本願発明は、前記のように高調波低減回路を負荷と並列に接続して、その高調波低減回路の共振回路の共振周波数の設定値を変えるだけで、正弦波又は非正弦波の高調波電流打消し用電流を発生することができ、かつ高調波低減回路にバイアス回路を付加するだけで、それらの正弦波又は非正弦波を半波の立ち上り部分と下降部分とを非対称にすることもできる。したがって本願発明は、負荷によって発生する高調波電流の波形に応じて多様の波形の高調波電流打消し用電流を発生することがでる。   In the present invention, a harmonic current of a sine wave or non-sinusoidal wave can be obtained by simply connecting a harmonic reduction circuit in parallel with a load as described above and changing the set value of the resonance frequency of the resonance circuit of the harmonic reduction circuit. A cancellation current can be generated, and by adding a bias circuit to the harmonic reduction circuit, the rising part and the falling part of the half-wave can be made asymmetric with respect to those sine waves or non-sine waves. . Therefore, the present invention can generate harmonic current cancellation currents having various waveforms according to the waveform of the harmonic current generated by the load.

図１〜図１０により本願発明の実施例を説明する。なお各図に共通の部分は同じ符号を使用している。   An embodiment of the present invention will be described with reference to FIGS. In addition, the same code | symbol is used for the part common to each figure.

図１〜図４により実施例１を説明する。
図１（ａ）は、本願発明の実施例１に係る高調波低減回路を接続した三相４線式配電線の電力供給回路を示し、負荷にコンデンサ入力型整流回路が接続されている。図１（ｂ）は、図１（ａ）の一相分の高調波低減回路例を示す。
図１において、１は３相交流電源、６は高調波低減回路、７はコンデンサ入力型整流回路が接続されている負荷、Ｕ，Ｖ，Ｗは、Ｕ相、Ｖ相、Ｗ相の配電線、Ｎは中性線である。３相交流電源１は、Ｕ相、Ｖ相、Ｗ相の電源ｅU，ｅV，ｅWを有し、負荷７は、各相の配電線Ｕ，Ｖ，Ｗと中性線Ｎにより各電源に接続されている。負荷７は、半導体回路駆動用の整流回路（ダイオードブリッジ）７１、コンデンサ（平滑コンデンサ）Ｃｄ、半導体回路の等価負荷抵抗Ｒｄからなる。Ｌｌは、配電用変圧器の漏れリアクタンス、Ｌ0とｒ0は、配電線のインピーダンス、ｉcは高調波低減回路６の電流、ｉlは負荷７の入力電流、Ｖｌは受電端電圧である。
なお図１（ａ）は、符号６，７をＵ相にのみ付してあるが、Ｖ相、Ｗ相も同様である。
図１（ａ）の負荷７は、整流回路７１とコンデンサＣｄからなるコンデンサ入力型整流回路を用いている。そのため中性線Ｎには、３次高調波電流をベースとするひずみ波電流が流れる。そこで図１（ａ）は、そのひずみ波電流を低減するため各相の負荷７と並列に高調波低減回路６を接続してある。 A first embodiment will be described with reference to FIGS.
FIG. 1A shows a power supply circuit of a three-phase four-wire distribution line connected with a harmonic reduction circuit according to Embodiment 1 of the present invention, and a capacitor input rectifier circuit is connected to a load. FIG. 1B shows an example of a harmonic reduction circuit for one phase of FIG.
In FIG. 1, 1 is a three-phase AC power source, 6 is a harmonic reduction circuit, 7 is a load to which a capacitor input rectifier circuit is connected, U, V, and W are U-phase, V-phase, and W-phase distribution lines. , N is a neutral wire. The three-phase AC power source 1 has U-phase, V-phase, and W-phase power sources e U , e V , and e W , and the load 7 is connected to each phase by distribution lines U, V, W and neutral wires N. Connected to power. The load 7 includes a rectifier circuit (diode bridge) 71 for driving a semiconductor circuit, a capacitor (smoothing capacitor) Cd, and an equivalent load resistance Rd of the semiconductor circuit. Ll is the leakage reactance of the distribution transformer, L 0 and r 0 is the impedance of the distribution line, ics current harmonics reduction circuit 6, il is the input current of the load 7, Vl is the voltage at reception end.
In FIG. 1A, reference numerals 6 and 7 are attached only to the U phase, but the same applies to the V phase and the W phase.
The load 7 in FIG. 1A uses a capacitor input type rectifier circuit including a rectifier circuit 71 and a capacitor Cd. Therefore, a distorted wave current based on the third harmonic current flows through the neutral wire N. Therefore, in FIG. 1A, a harmonic reduction circuit 6 is connected in parallel with the load 7 of each phase in order to reduce the distortion wave current.

図１（ｂ）は、図１（ａ）の高調波低減回路６の具体例を示す。
高調波低減回路６は、スイッチング素子として逆阻止サイリスタＳＣＲ１，２の逆並列接続を用い、これと直列に抵抗ｒｃ、インダクタンスＬｃ、コンデンサＣを接続してある。インダクタンスＬｃ、コンデンサＣは、共振回路を形成している。その共振回路の共振周波数ｆ0は、電源電圧の周波数ｆの３倍（ｆ0＝３ｆ）に設定してある。このように設定することにより、各相の高調波低減回路６から中性線Ｎに流れる合成電流Σｉｃの周波数は、負荷７によって発生する３次高調波電流の周波数と同じになる。 FIG.1 (b) shows the specific example of the harmonic reduction circuit 6 of Fig.1 (a).
The harmonic reduction circuit 6 uses a reverse parallel connection of reverse blocking thyristors SCR1 and SCR2 as switching elements, and a resistor rc, an inductance Lc, and a capacitor C are connected in series therewith. The inductance Lc and the capacitor C form a resonance circuit. The resonance frequency f 0 of the resonance circuit is set to three times the frequency f of the power supply voltage (f 0 = 3f). By setting in this way, the frequency of the combined current Σic flowing from the harmonic reduction circuit 6 of each phase to the neutral line N becomes the same as the frequency of the third harmonic current generated by the load 7.

各相の高調波低減回路６の電流ｉｃは、サイリスタＳＣＲ１，２がターンオンした時に流れ始めるから、中性線Ｎを流れる各相の電流ｉｃの合成電流Σｉｃの位相は、サイリスタＳＣＲ１，２がターンオンする時期（位相）、即ち点弧角αによって決まる。また各相の電流ｉｃが流れる期間（通流幅或いは通流角）は、共振周波数ｆ0によって決まり、電流ｉｃの大きさは、主として抵抗ｒｃによって決まる。したがって中性線Ｎの合成電流Σｉｃの位相は、各相の高調波低減回路６のサイリスタＳＣＲ１，２の点弧角αによって決まるから、その点弧角αを調整することにより、負荷７によって発生する３次高調波電流と逆相にすることができる。なお負荷７により発生する３次高調波電流の大きさや位相は、負荷の出力が変動してもほとんど変わらないが、サイリスタＳＣＲ１，２の点弧角αを調整することにより、負荷の種類が変わった際の３次高調波電流の位相の変化に対応して各相の高調波低減回路６の電流ｉｃの位相を調整することができる。本実施例は、高調波低減回路６にサイリスタＳＣＲ１，２を用いているから、駆動回路が簡単になる。
各相の電源電圧ｅU，ｅV，ｅW、各相の高調波低減回路６の電流（各相の高調波低減回路６の電流ｉｃ）ｉCU，ｉCV，ｉCW、それらの電流の和である中性線Ｎの電流ｉCN（＝Σｉｃ）は、図２のようになる。中性線Ｎの電流ｉCNは、高調波低減回路６の共振回路の共振周波数ｆ0が、電源電圧の周波数ｆの３倍（ｆ0＝３ｆ）のときには、図２のｉCNのように、３次高調波電流と同じ周波数の正弦波となる。 Since the current ic of the harmonic reduction circuit 6 of each phase starts to flow when the thyristors SCR1 and SCR2 are turned on, the phase of the combined current Σic of the current ic of each phase flowing through the neutral line N is turned on by the thyristors SCR1 and SCR2 The timing (phase) to be performed, that is, the firing angle α. Further, the period (current width or current angle) in which the current ic of each phase flows is determined by the resonance frequency f 0 , and the magnitude of the current ic is mainly determined by the resistance rc. Therefore, since the phase of the composite current Σic of the neutral line N is determined by the firing angle α of the thyristors SCR1 and SCR2 of the harmonic reduction circuit 6 of each phase, it is generated by the load 7 by adjusting the firing angle α. Can be out of phase with the third harmonic current. The magnitude and phase of the third harmonic current generated by the load 7 hardly change even if the output of the load fluctuates, but the type of the load changes by adjusting the firing angle α of the thyristors SCR1 and SCR2. The phase of the current ic of the harmonic reduction circuit 6 of each phase can be adjusted in response to the change in the phase of the third harmonic current at the time. In this embodiment, since the thyristors SCR1 and SCR2 are used for the harmonic reduction circuit 6, the drive circuit is simplified.
Power supply voltage e U , e V , e W of each phase, current of harmonic reduction circuit 6 of each phase (current ic of harmonic reduction circuit 6 of each phase) i CU , i CV , i CW , The current i CN (= Σic) of the neutral line N which is the sum is as shown in FIG. The current i CN of the neutral line N is as shown by i CN in FIG. 2 when the resonance frequency f 0 of the resonance circuit of the harmonic reduction circuit 6 is three times the frequency f of the power supply voltage (f 0 = 3f). It becomes a sine wave having the same frequency as the third harmonic current.

以上のように高調波低減回路６は、負荷７によって発生する３次高調波電流と周波数が同じで、逆相の電流ｉｃを発生できるから、それらの合成電流Σｉｃによって中性線Ｎの３次高調波電流を打ち消すことができる。したがって図１（ａ）のように、Ｕ相、Ｖ相、Ｗ相毎に高調波低減回路６を接続することにより、各相の負荷７により発生して中性線Ｎを流れる３次高調波電流をベースとするひずみ波電流を低減することができる。
なお高調波低減回路６の共振回路の共振周波数ｆ0は、ｆ0＝３ｆの例について説明したが、負荷７によって発生する高調波電流の周波数成分は、３次以上の高調波成分が多く含まれる場合があり、その場合、共振周波数ｆ0を３ｆ以外の適当な値に設定することにより３ｆ以外の高調波成分も低減することができる。 As described above, the harmonic reduction circuit 6 has the same frequency as the third-order harmonic current generated by the load 7 and can generate a reverse-phase current ic. Therefore, the third-order of the neutral line N is generated by the combined current Σic. Harmonic current can be canceled out. Therefore, as shown in FIG. 1A, by connecting the harmonic reduction circuit 6 for each of the U phase, V phase, and W phase, the third harmonic generated by the load 7 of each phase and flowing through the neutral line N The distortion wave current based on the current can be reduced.
Although the example in which the resonance frequency f 0 of the resonance circuit of the harmonic reduction circuit 6 is f 0 = 3f has been described, the frequency component of the harmonic current generated by the load 7 includes many higher-order harmonic components. it is subject, in which case, it is also possible to reduce the harmonic components other than 3f by setting the resonance frequency f 0 to a suitable value other than 3f.

図１（ｂ）の高調波低減回路６は、サイリスタ、抵抗、インダクタンス及びコンデンサによって形成できるから、従来のアクティブフィルタに比べて、構成が簡単になり安価に作製することができる。また図１の三相４線式配電線の電力供給回路は、高調波低減回路６を負荷７と並列に接続するだけで、負荷７によって発生する高調波電流を打ち消すことができ、その高調波電流を打ち消すために高調波電流成分を抽出するための高調波電流成分抽出回路を設ける必要がない。
なおスイッチング素子は、サイリスタに限らず、ＩＧＢＴ、バイポーラトランジスタ、パワーＭＯＳＦＥＴ等のスイッチング素子であってもよい。 Since the harmonic reduction circuit 6 of FIG. 1B can be formed by a thyristor, a resistor, an inductance, and a capacitor, the configuration is simpler and can be manufactured at a lower cost than a conventional active filter. The power supply circuit of the three-phase four-wire distribution line in FIG. 1 can cancel the harmonic current generated by the load 7 only by connecting the harmonic reduction circuit 6 in parallel with the load 7. There is no need to provide a harmonic current component extraction circuit for extracting a harmonic current component in order to cancel the current.
The switching element is not limited to a thyristor, and may be a switching element such as an IGBT, a bipolar transistor, or a power MOSFET.

ここで、図３、図４により図１の三相４線式配電線の電力供給回路のシミュレーションの結果について説明する。
シミュレーションに用いた図１（ａ）の対称三相電源と回路定数は、ｅU＝Ｅｍｓｉｎωｔ、ｅV＝Ｅｍｓｉｎ(ωｔ−１２０°)、ｅW＝Ｅｍｓｉｎ(ωｔ−240°)、Ｅｍ＝１４１[Ｖ]、ｆ＝５０[Ｈｚ]、Ｌｌ＝０．２[ｍＨ]、Ｌ0＝０．２[ｍＨ]、ｒ0＝０．１[Ω]、Ｒｄ＝１〜４０[Ω]（この範囲内で可変）に設定し、三相平衡負荷としてシミュレーションを実施した。ただし、負荷の時定数(Ｒｄ×Ｃｄ)を約１００[ｍｓ](一定)に保ちながらRdに対応してＣｄも可変した。
また図１（ｂ）の回路定数は、サイリスタ点弧角α＝４〜１８[°]、ｒｃ＝０.５５〜７.１[Ω]、Ｌ＝１０[ｍＨ]、Ｃ=１００[μＦ]に設定した。
なおシミュレーションには、パワーエレクトロニクスの分野で一般に使用されているシミュレーションソフトＰＳＩＭ（発売元：マイウェイ技研株式会社）を使用した。 Here, the result of the simulation of the power supply circuit of the three-phase four-wire distribution line in FIG. 1 will be described with reference to FIGS.
The symmetrical three-phase power source and circuit constants of FIG. 1A used for the simulation are e U = Esin ωt, e V = Emsin (ωt−120 °), e W = Emsin (ωt−240 °), Em = 141 [ V], f = 50 [Hz], Ll = 0.2 [mH], L 0 = 0.2 [mH], r 0 = 0.1 [Ω], Rd = 1 to 40 [Ω] (this range The simulation was carried out as a three-phase balanced load. However, Cd was also varied corresponding to Rd while keeping the load time constant (Rd × Cd) at about 100 [ms] (constant).
The circuit constants in FIG. 1B are as follows: thyristor firing angle α = 4 to 18 [°], rc = 0.55 to 7.1 [Ω], L = 10 [mH], C = 100 [μF] Set to.
In the simulation, simulation software PSIM (release source: Myway Giken Co., Ltd.) generally used in the field of power electronics was used.

まず図３について説明する。なお、Ｒｄ＝７[Ω]、Ｃｄ＝１３４２９[μＦ]、サイリスタ点弧角α＝１１[°]に設定した。
図３（ａ）は、中性線電流を示し、図３（ｂ）は、受電端電圧を示す。なお比較のため電源電圧（周波数ｆ）の正弦半波（破線）を併記してある。なお図３において、イは、高調波低減回路を接続した場合の中性線電流と受電端電圧を示し、ロは、高調波低減回路を接続しない場合の中性線電流と受電端電圧を示す。 First, FIG. 3 will be described. Note that Rd = 7 [Ω], Cd = 13429 [μF], and thyristor firing angle α = 11 [°].
FIG. 3A shows the neutral line current, and FIG. 3B shows the receiving end voltage. For comparison, a half sine wave (broken line) of the power supply voltage (frequency f) is also shown. In FIG. 3, A indicates the neutral line current and the receiving end voltage when the harmonic reduction circuit is connected, and B indicates the neutral line current and the receiving end voltage when the harmonic reduction circuit is not connected. .

図３（ａ）によると、三相４線式配電線に図１の高調波低減回路を接続すると、中性線電流の３次高調波電流をベースとするひずみ波電流イは、高調波低減回路を接続しない場合のひずみ波電流ロに比べて非常に小さくなり、図３（ｂ）のように高調波低減回路を接続した場合の受電端電圧イは、立ち上り部分と降下部分のスロープが正弦波に近付いており、受電端電圧中の高調波の含有量が低減していることが分かる。したがって図１の高調波低減回路は、中性線電流の３次高調波電流をベースとするひずみ波電流を低減する効果がある。
コンデンサ入力型整流回路は、整流回路入力電流の通流幅が狭いため、波高値が実効値の３〜５倍程度になることもある。そのため、線路インピーダンスの関係で正弦波のピークの頭部分がカットされて電圧降下が生じ、受電端電圧の波形ひずみを生じるが、三相４線式配電線に図１の高調波低減回路を用いることにより、図３（ｂ）のように、波高以外部分の形状を含めてその受電端電圧の波形ひずみは、改善される。 According to FIG. 3 (a), when the harmonic reduction circuit of FIG. 1 is connected to a three-phase four-wire distribution line, the distortion wave current a based on the third harmonic current of the neutral wire current is reduced by harmonics. The distortion wave current b when the circuit is not connected is much smaller than the distortion wave current b. When the harmonic reduction circuit is connected as shown in FIG. It is close to the wave, and it can be seen that the harmonic content in the receiving end voltage is reduced. Therefore, the harmonic reduction circuit of FIG. 1 has an effect of reducing the distortion wave current based on the third harmonic current of the neutral line current.
Since the capacitor input type rectifier circuit has a narrow rectifier circuit input current flow width, the peak value may be about 3 to 5 times the effective value. Therefore, the peak portion of the sine wave is cut due to the line impedance, resulting in a voltage drop and a waveform distortion of the receiving end voltage. However, the harmonic reduction circuit of FIG. 1 is used for the three-phase four-wire distribution line. As a result, as shown in FIG. 3B, the waveform distortion of the receiving end voltage including the shape of the portion other than the wave height is improved.

次に図４について説明する。
図４（ａ）は、負荷電力（負荷容量）と中性線電流を示し、図４（ｂ）は、負荷電力（負荷容量）と受電端電圧ひずみ率を示し、図４（ｃ）は、負荷電力（負荷容量）と直流出力電圧（整流回路の直流出力電圧）を示す。なお図４において、実線は、高調波低減回路を接続した場合の特性を示し、破線は、高調波低減回路を接続しない場合の特性を示す。
三相４線式配電線に図１の高調波低減回路を接続すると、中性線のひずみ波電流は、図４（ａ）のように負荷の容量の広い範囲において大幅に低減できる。その結果三相４線式配電線に図１の高調波低減回路を接続すると、受電端電圧ひずみ率は、図４（ｂ）のように改善でき、直流出力電圧の低下は、図４（ｃ）のように小さくなる。 Next, FIG. 4 will be described.
4A shows the load power (load capacity) and the neutral line current, FIG. 4B shows the load power (load capacity) and the receiving-end voltage distortion rate, and FIG. The load power (load capacity) and the DC output voltage (DC output voltage of the rectifier circuit) are shown. In FIG. 4, the solid line indicates the characteristic when the harmonic reduction circuit is connected, and the broken line indicates the characteristic when the harmonic reduction circuit is not connected.
When the harmonic reduction circuit of FIG. 1 is connected to the three-phase four-wire distribution line, the distorted wave current of the neutral wire can be greatly reduced in a wide range of load capacity as shown in FIG. As a result, when the harmonic reduction circuit of FIG. 1 is connected to the three-phase four-wire distribution line, the receiving-end voltage distortion rate can be improved as shown in FIG. 4B, and the decrease in the DC output voltage is shown in FIG. ) Becomes smaller.

図５〜図８により実施例２を説明する。
図５は、本願発明の実施例２に係る高調波低減回路を接続した三相４線式配電線の電力供給回路を示し、負荷に位相制御型調光回路が接続されている。負荷以外は、図１と同じである。
各相の負荷８は、ＳＣＲ３，４を逆並列接続した位相制御用スイッチ８１に電球の抵抗Ｒｂを接続してある。
中性線Ｎには、実施例１で説明したように、各相の高調波低減回路６の電流ｉｃの合成電流Σｉｃ（中性線Ｎの電流ｉCN）が流れ、その合成電流Σｉｃは、各相の高調波低減回路６の共振回路の共振周波数ｆ0を電源電圧の周波数ｆの３倍（ｆ0＝３ｆ）に設定すると正弦波の３次高調波電流となる。一方負荷８に位相制御用スイッチ８１を用いた場合には、負荷８により発生して中性線Ｎを流れる３次高調波電流をベースとしたひずみ電流は、非正弦波となる。したがって負荷８により発生して中性線Ｎを流れる３次高調波電流をベースとしたひずみ電流を、中性線Ｎの合成電流Σｉｃで完全に相殺することは困難である。 A second embodiment will be described with reference to FIGS.
FIG. 5 shows a power supply circuit of a three-phase four-wire distribution line to which a harmonic reduction circuit according to Embodiment 2 of the present invention is connected, and a phase control type dimming circuit is connected to a load. Except for the load, it is the same as FIG.
The load 8 of each phase is connected to a bulb resistance Rb to a phase control switch 81 in which SCRs 3 and 4 are connected in antiparallel.
As described in the first embodiment, the neutral line N is supplied with the combined current Σic (current i CN of the neutral line N) of the current ic of the harmonic reduction circuit 6 of each phase. When the resonance frequency f 0 of the resonance circuit of the harmonic reduction circuit 6 for each phase is set to three times the frequency f of the power supply voltage (f 0 = 3f), a sine wave third harmonic current is obtained. On the other hand, when the phase control switch 81 is used for the load 8, the distortion current based on the third harmonic current generated by the load 8 and flowing through the neutral line N becomes a non-sinusoidal wave. Therefore, it is difficult to completely cancel the distortion current based on the third harmonic current generated by the load 8 and flowing through the neutral line N with the combined current Σic of the neutral line N.

そこで本実施例は、中性線Ｎの合成電流Σｉｃを非正弦波化することを試み、各相の高調波低減回路６の共振回路の共振周波数ｆ0を、電源電圧の周波数ｆの３倍（ｆ0＝３ｆ）以外の周波数に設定することにより非正弦波化できることを見出した。
図６は、中性線Ｎの合成電流Σｉｃを三角波化する例である。
各相の高調波低減回路６の共振回路の共振周波数ｆ0を、電源電圧の周波数ｆの１．５倍（ｆ0＝１．５ｆ）に設定すると、各相の高調波低減回路６の電流ｉｃは、ｉCU，ｉCV，ｉCWのように繰り返し周波数１．５ｆの正弦パルス状の電流になるが、中性線Ｎの合成電流Σｉｃは、ｉCNのように繰り返し周波数３ｆの三角波になる。即ち三相４線式の電力供給回路は、各相の共振周波数ｆ0を１．５ｆに設定すると、各相の電流ｉｃは１．５ｆの正弦パルス状となるが、合成電流Σｉｃ（中性線Ｎの電流ｉCN）は３次高調波電流と同一周期（同一の繰り返し周波数）の三角波になる。 In this embodiment, therefore, an attempt is made to make the combined current Σic of the neutral line N non-sinusoidal, and the resonance frequency f 0 of the resonance circuit of the harmonic reduction circuit 6 of each phase is three times the frequency f of the power supply voltage. It has been found that a non-sinusoidal wave can be obtained by setting a frequency other than (f 0 = 3f).
FIG. 6 shows an example in which the combined current Σic of the neutral line N is converted into a triangular wave.
When the resonance frequency f 0 of the resonance circuit of the harmonic reduction circuit 6 of each phase is set to 1.5 times the frequency f of the power supply voltage (f 0 = 1.5f), the current of the harmonic reduction circuit 6 of each phase ic becomes a sinusoidal current with a repetition frequency of 1.5 f as i CU , i CV , i CW , but the synthesized current Σic of the neutral line N becomes a triangular wave with a repetition frequency of 3 f as i CN. Become. That is, in the three-phase four-wire power supply circuit, when the resonance frequency f 0 of each phase is set to 1.5f, the current ic of each phase becomes a sine pulse of 1.5f, but the combined current Σic (neutral) The current i CN of the line N becomes a triangular wave having the same period (same repetition frequency) as the third harmonic current.

図７は、各相の高調波低減回路６の共振回路の共振周波数ｆ0を変えたときの合成電流Σｉｃの波形を示す。なお図７（ａ）には、比較のため周波数ｆの電源電圧の波形を併記してある。
図７（ｂ）〜（ｆ）は、共振周波数ｆ0が、ｆ0＝１．５ｆ（図６と同じ）、ｆ0＝２ｆ、ｆ0＝２．５ｆ、ｆ0＝３ｆ（図２と同じ）、ｆ0＝５ｆのときの合成電流Σｉｃの波形を示す。共振周波数ｆ0を変えると、合成電流Σｉｃの波形は、図７（ｂ）〜（ｆ）のように変化するが、合成電流Σｉｃの周期（或いは繰り返し周波数）は、いずれの場合も３次高調波電流と同じになる。
以上のように合成電流Σｉｃは、共振周波数ｆ0を変えるとことにより、正弦波にも非正弦波にもなる。なおこの点は、図１（負荷７の場合）についても同様である。
図７（ｂ）〜（ｆ）は、３次高調波電流と同一周期となる合成電流Σｉｃのみを図示してあるが、合成電流Σｉｃには３次高調波電流以外の高調波電流も含まれている。 FIG. 7 shows the waveform of the combined current Σic when the resonance frequency f 0 of the resonance circuit of the harmonic reduction circuit 6 of each phase is changed. In FIG. 7A, the waveform of the power supply voltage at the frequency f is also shown for comparison.
7B to 7F, the resonance frequency f 0 is f 0 = 1.5f (same as FIG. 6), f 0 = 2f, f 0 = 2.5f, f 0 = 3f (FIG. 2 and FIG. The same shows the waveform of the combined current Σic when f 0 = 5f. When the resonance frequency f 0 is changed, the waveform of the composite current Σic changes as shown in FIGS. 7B to 7F, but the period (or repetition frequency) of the composite current Σic is the third harmonic in any case. Same as wave current.
As described above, the combined current Σic becomes a sine wave or a non-sine wave by changing the resonance frequency f 0 . This also applies to FIG. 1 (in the case of load 7).
FIGS. 7B to 7F show only the combined current Σic having the same period as the third harmonic current, but the combined current Σic includes harmonic currents other than the third harmonic current. ing.

そこで図８により３次高調波以外の高調波電流の含有率を説明する。
図８は、電源電圧の周波数ｆ＝５０［Ｈｚ］における高調波低減回路６の共振周波数ｆ0と合成電流Σｉｃのｎ次高調波電流の含有率との関係を示す。図８において、縦軸は、３次高調波電流に対するｎ次高調波電流の含有率を、横軸は、高調波低減回路６の共振周波数ｆ0を示す。図８は、ｎ＝３以外のｎ＝９，１５，２１，３３の高調波電流を図示してある。なおｎ＝２７等の高調波電流も現れるが、含有量が少ないので省略してある。
以上のように本実施例の電力供給回路は、高調波低減回路６を用いることにより、中性線Ｎの合成電流Σｉｃは、３次高調波電流をベースとする高調波電流からなるから、負荷８により発生して中性線Ｎを流れる３次高調波電流をベースとするひずみ波電流を低減することができる。
なお実施例２は、高調波低減回路６のサイリスタＳＣＲ１，２の点弧角αを変えることにより各相の３次高調波電流の位相を変えることができる。即ち実施例２の各相の３次高調波電流の位相は、実施例１の高調波低減回路６の電流の位相に相当する。したがって本願発明は、実施例２の３次高調波電流を含めて高調波低減回路の電流と呼ぶ。
また実施例２で説明した各相の高調波低減回路からの合成電流Σｉｃの波形は、図１の場合（負荷７の場合）についても同様である。 Therefore, the content of harmonic currents other than the third harmonic will be described with reference to FIG.
FIG. 8 shows the relationship between the resonance frequency f 0 of the harmonic reduction circuit 6 and the content ratio of the n-th harmonic current of the combined current Σic at the power supply voltage frequency f = 50 [Hz]. In FIG. 8, the vertical axis represents the content of the nth harmonic current with respect to the third harmonic current, and the horizontal axis represents the resonance frequency f 0 of the harmonic reduction circuit 6. FIG. 8 illustrates harmonic currents of n = 9, 15, 21, 33 other than n = 3. Although harmonic currents such as n = 27 also appear, they are omitted because the content is small.
As described above, the power supply circuit of the present embodiment uses the harmonic reduction circuit 6 so that the combined current Σic of the neutral line N is composed of a harmonic current based on the third harmonic current. 8 can reduce the distorted wave current based on the third-order harmonic current generated by 8 and flowing through the neutral wire N.
In the second embodiment, the phase of the third harmonic current of each phase can be changed by changing the firing angle α of the thyristors SCR1 and SCR2 of the harmonic reduction circuit 6. That is, the phase of the third harmonic current of each phase of the second embodiment corresponds to the phase of the current of the harmonic reduction circuit 6 of the first embodiment. Therefore, the present invention is called the current of the harmonic reduction circuit including the third harmonic current of the second embodiment.
The waveform of the combined current Σic from the harmonic reduction circuit for each phase described in the second embodiment is the same as in the case of FIG. 1 (in the case of the load 7).

図９、図１０により実施例３を説明する。
図９（ａ）は、本願発明の実施例３に係る高調波低減回路を接続した三相４線式配電線の電力供給回路を示し、各相の高調波低減回路にバイアス回路を付加してある。バイアス回路以外は、図５と同じである。
実施例１、実施例２の中性線Ｎの高調波低減回路６からの電流ｉCN（合成電流Σｉｃ）の波形は、正弦波、非正弦波いずれの場合にも、半波の立ち上り部分と下降部分とが対称であるが、負荷の種類により非対称の電流を必要とする場合がある。例えば、図１０（ａ）の三角波ロは、半波の立ち上り部分と下降部分とが対称であるが、負荷の種類によりイのような非対称の電流を必要とする場合がある。同様に図１０（ｂ）の正弦波ロは、半波の立ち上り部分と下降部分とが対称であるが、負荷の種類によりイのような非対称の電流を必要とする場合がある。
そこで実施例３は、それらの非対称波形に対応して、中性線Ｎの電流ｉCN（合成電流Σｉｃ）の波形を非対称にするため、高調波低減回路６にバイアス回路９を付加してある。 A third embodiment will be described with reference to FIGS.
FIG. 9A shows a power supply circuit of a three-phase four-wire distribution line connected with a harmonic reduction circuit according to Embodiment 3 of the present invention, and a bias circuit is added to the harmonic reduction circuit of each phase. is there. Except for the bias circuit, it is the same as FIG.
The waveform of the current i CN (synthetic current Σic) from the harmonic reduction circuit 6 of the neutral line N of the first and second embodiments is a half-wave rising portion in both cases of a sine wave and a non-sine wave. Although it is symmetrical with the descending portion, an asymmetrical current may be required depending on the type of load. For example, in the triangular wave B of FIG. 10A, the rising and falling portions of the half wave are symmetric, but an asymmetrical current such as A may be required depending on the type of load. Similarly, in the sine wave b in FIG. 10B, the rising and falling parts of the half wave are symmetric, but an asymmetrical current such as A may be required depending on the type of load.
Accordingly, in the third embodiment, a bias circuit 9 is added to the harmonic reduction circuit 6 in order to make the waveform of the current i CN (combined current Σic) of the neutral line N asymmetric corresponding to these asymmetric waveforms. .

各相のバイアス回路９は、図９（ｂ）のようにバイアス電圧発生回路９１とトランス９２からなり、バイアス電圧発生回路９１のバイアス電圧は、トランス９２により高調波低減回路６の出力に結合されている。
高調波低減回路６の電流ｉCの波形は、無バイアス時、例えば図９（ｃ）イの波形に設定する。一方バイアス電圧発生回路９１のバイアス電圧の波形は、図９（ｃ）ロのように傾斜特性を有する波形に設定する。高調波低減回路６の電流ｉCの波形は、バイアス電圧を印加すると図９（ｃ）ハのようになる。したがって中性線Ｎの高調波低減回路６からの電流ｉCN（合成電流Σｉｃ）の波形は、波形ロのバイアス電圧を印加すると半波の立ち上り部分と下降部分とが非対称になる。
バイアス電圧の波形は、図９（ｃ）ロ以外の波形に設定することもできる。
バイアス電圧発生回路９１は、スイッチング素子を用いたインバータ等によって構成することができる。
なお実施例３は、高調波低減回路６のサイリスタＳＣＲ１，２の点弧角αを変えることにより各相の３次高調波電流の位相を変えることができる。即ち実施例３の各相の３次高調波電流の位相は、実施例１の高調波低減回路６の電流の位相に相当する。したがって本願発明は、実施例３の３次高調波電流を含めて高調波低減回路の電流と呼ぶ。
また実施例３で説明した各相の高調波低減回路からの合成電流Σｉｃの波形の非対称化は、図１の場合（負荷７の場合）についても同様である。 The bias circuit 9 for each phase includes a bias voltage generation circuit 91 and a transformer 92 as shown in FIG. 9B. The bias voltage of the bias voltage generation circuit 91 is coupled to the output of the harmonic reduction circuit 6 by the transformer 92. ing.
The waveform of the current i C of the harmonic reduction circuit 6 is set to the waveform shown in FIG. On the other hand, the bias voltage waveform of the bias voltage generation circuit 91 is set to a waveform having a slope characteristic as shown in FIG. When the bias voltage is applied, the waveform of the current i C of the harmonic reduction circuit 6 becomes as shown in FIG. Accordingly, the waveform of the current i CN (combined current Σic) from the harmonic reduction circuit 6 of the neutral line N becomes asymmetrical between the rising and falling portions of the half-wave when a bias voltage of waveform b is applied.
The waveform of the bias voltage can also be set to a waveform other than that shown in FIG.
The bias voltage generation circuit 91 can be configured by an inverter or the like using a switching element.
In the third embodiment, the phase of the third harmonic current of each phase can be changed by changing the firing angle α of the thyristors SCR1 and SCR2 of the harmonic reduction circuit 6. That is, the phase of the third harmonic current of each phase of the third embodiment corresponds to the phase of the current of the harmonic reduction circuit 6 of the first embodiment. Therefore, the present invention is called the current of the harmonic reduction circuit including the third harmonic current of the third embodiment.
Further, the asymmetry of the waveform of the combined current Σic from the harmonic reduction circuit of each phase described in the third embodiment is the same in the case of FIG. 1 (in the case of the load 7).

本願発明の実施例１に係る三相４線式配電線の電力供給回路で、負荷にコンデンサ入力型整流回路を接続してある。In the power supply circuit of the three-phase four-wire distribution line according to the first embodiment of the present invention, a capacitor input rectifier circuit is connected to the load. 図１の電力供給回路において、高調波低減回路の共振回路の共振周波数を電源電圧の周波数の３倍に設定したときの各相の電源電圧、各相の高調波低減回路の電流、中性線の電流の波形を示す。In the power supply circuit of FIG. 1, when the resonance frequency of the resonance circuit of the harmonic reduction circuit is set to three times the frequency of the power supply voltage, the power supply voltage of each phase, the current of the harmonic reduction circuit of each phase, the neutral line The waveform of current is shown. 図１の三相４線式配電線の電力供給回路のシミュレーション結果例（中性線電流波形と受電端電圧波形）を示す。The simulation result example (neutral wire current waveform and receiving end voltage waveform) of the power supply circuit of the three-phase four-wire distribution line in FIG. 1 is shown. 図１の三相４線式配電線の電力供給回路のシミュレーション結果例（負荷電力（負荷容量）に対する中性線電流、受電端電圧ひずみ率及び整流回路の直流出力電圧）を示す。The example of the simulation result (Neutral line current with respect to load electric power (load capacity), receiving-end voltage distortion factor, and DC output voltage of a rectifier circuit) of the power supply circuit of the three-phase four-wire distribution line in FIG. 1 is shown. 本願発明の実施例２に係る三相４線式配電線の電力供給回路で、負荷に位相制御型調光回路を接続してある。In the power supply circuit of the three-phase four-wire distribution line according to the second embodiment of the present invention, a phase control dimmer circuit is connected to the load. 図５の電力供給回路において、高調波低減回路の共振回路の共振周波数を電源電圧の周波数の１．５倍に設定したときの各相の電源電圧、各相の高調波低減回路の電流、中性線の電流の波形を示す。In the power supply circuit of FIG. 5, when the resonance frequency of the resonance circuit of the harmonic reduction circuit is set to 1.5 times the frequency of the power supply voltage, the power supply voltage of each phase, the current of the harmonic reduction circuit of each phase, The waveform of the current of the sex line is shown. 図１、図５の電力供給回路において、高調波低減回路の共振回路の共振周波数を種々変えたときの中性線の電流の波形を示す。In the power supply circuit of FIG. 1 and FIG. 5, the waveform of the neutral current when the resonance frequency of the resonance circuit of the harmonic reduction circuit is variously changed is shown. 高調波低減回路の共振回路の共振周波数を種々変えたときの中性線電流中の含有量が大きいｎ次高調波の含有率を示す。The content rate of the n-th order harmonic with a large content in the neutral wire current when the resonance frequency of the resonance circuit of the harmonic reduction circuit is variously changed is shown. 本願発明の実施例３に係る三相４線式配電線の電力供給回路で、高調波低減回路にバイアス回路を付加してある。In the power supply circuit of the three-phase four-wire distribution line according to Embodiment 3 of the present invention, a bias circuit is added to the harmonic reduction circuit. 中性線の電流波形が半波の立ち上り部分と降下部分とで非対称になる場合の波形を示す。The waveform in the case where the current waveform of the neutral line becomes asymmetric between the rising part and the falling part of the half wave is shown. 従来のアクティブフィルタを接続した三相４線式配電線の電力供給回路を示す。The power supply circuit of the three-phase four-wire distribution line which connected the conventional active filter is shown.

符号の説明Explanation of symbols

１ ３相交流電源
６ 高調波低減回路
７ コンデンサ入力型整流回路を用いた負荷
７１ ダイオードブリッジ整流回路
８ 位相制御型調光回路を用いた負荷
８１ 位相制御用スイッチ
９ バイアス回路
９１ バイアス電圧発生回路
９２ トランス
Ｕ，Ｖ，Ｗ Ｕ相、Ｖ相、Ｗ相の配電線
Ｎ 中性線
Ｖｌ 受電端電圧
ｉｃ 高調波低減回路の電流
ｉｌ 負荷の入力電流 DESCRIPTION OF SYMBOLS 1 3 phase alternating current power supply 6 Harmonic reduction circuit 7 Load 71 using capacitor input type rectifier circuit Diode bridge rectifier circuit 8 Load 81 using phase control type dimmer circuit Phase control switch 9 Bias circuit 91 Bias voltage generation circuit 92 Transformer U, V, W U phase, V phase, W phase distribution line N Neutral line Vl Receiving end voltage ic Harmonic reduction circuit current il Load input current

Claims (12)

スイッチング素子、抵抗、インダクタンス及びコンデンサを直列に接続してなり、負荷により発生する高調波電流と逆相の電流を発生する高調波低減回路を負荷に並列に接続してあることを特徴とする三相４線式配電線の電力供給回路。   A switching element, a resistor, an inductance, and a capacitor are connected in series, and a harmonic reduction circuit that generates a current in a phase opposite to that of the harmonic current generated by the load is connected in parallel to the load. Power supply circuit for phase 4-wire distribution lines. 請求項１に記載の電力供給回路において、前記スイッチング素子はサイリスタであることを特徴とする三相４線式配電線の電力供給回路。   2. The power supply circuit according to claim 1, wherein the switching element is a thyristor. 3. 請求項１又は請求項２に記載の電力供給回路において、前記スイッチング素子の点弧角を調整して前記高調波低減回路の電流の位相を調整できることを特徴とする三相４線式配電線の電力供給回路。   The power supply circuit according to claim 1 or 2, wherein the phase of the current of the harmonic reduction circuit can be adjusted by adjusting the firing angle of the switching element. Power supply circuit. 請求項１、請求項２又は請求項３に記載の電力供給回路において、前記高調波低減回路の共振回路の共振周波数を電源電圧の周波数より高い周波数に設定してあることを特徴とする三相４線式配電線の電力供給回路。   4. The power supply circuit according to claim 1, wherein the resonance frequency of the resonance circuit of the harmonic reduction circuit is set to a frequency higher than the frequency of the power supply voltage. Power supply circuit for 4-wire distribution lines. 請求項４に記載の電力供給回路において、前記共振周波数を電源電圧の周波数の３倍の周波数に設定してあることを特徴とする三相４線式配電線の電力供給回路。   5. The power supply circuit according to claim 4, wherein the resonance frequency is set to a frequency that is three times the frequency of the power supply voltage. 請求項４に記載の電力供給回路において、前記共振周波数を電源電圧の周波数の３倍以外の周波数に設定してあることを特徴とする三相４線式配電線の電力供給回路。   The power supply circuit according to claim 4, wherein the resonance frequency is set to a frequency other than three times the frequency of the power supply voltage. 請求項４、請求項５又は請求項６に記載の電力供給回路において、前記高調波低減回路にバイアス回路を付加してあることを特徴とする三相４線式配電線の電力供給回路。   The power supply circuit according to claim 4, 5 or 6, wherein a bias circuit is added to the harmonic reduction circuit. スイッチング素子、抵抗、インダクタンス及びコンデンサを直列に接続してなり、負荷に並列に接続した高調波低減回路の共振回路の共振周波数を電源電圧の周波数より高い周波数に設定し、負荷により発生する高調波電流と逆相の電流を発生して負荷により発生する高調波電流を打ち消すことを特徴とする三相４線式配電線の電力供給回路の高調波低減方法。   Harmonics generated by the load by setting the resonance frequency of the harmonic reduction circuit connected to the load in parallel with the switching element, resistor, inductance, and capacitor in series, and higher than the frequency of the power supply voltage. A method for reducing harmonics in a power supply circuit for a three-phase four-wire distribution line, wherein a current having a phase opposite to that of the current is generated to cancel a harmonic current generated by a load. 請求項８に記載の高調波低減方法において、前記スイッチング素子の点弧角を調整して前記高調波低減回路の電流の位相を調整することを特徴とする三相４線式配電線の電力供給回路の高調波低減方法。   9. The harmonic supply method according to claim 8, wherein the phase of the current of the harmonic reduction circuit is adjusted by adjusting the firing angle of the switching element. Circuit harmonic reduction method. 請求項８又は請求項９に記載の高調波低減方法において、前記共振周波数を電源電圧の周波数の３倍の周波数に設定することを特徴とする三相４線式配電線の電力供給回路の高調波低減方法。   10. The harmonic reduction method according to claim 8, wherein the resonance frequency is set to a frequency that is three times the frequency of the power supply voltage. Wave reduction method. 請求項８又は請求項９に記載の高調波低減方法において、前記共振周波数を電源電圧の周波数の３倍以外の周波数に設定することを特徴とする三相４線式配電線の電力供給回路の高調波低減方法。   The harmonic reduction method according to claim 8 or 9, wherein the resonance frequency is set to a frequency other than three times the frequency of the power supply voltage. Harmonic reduction method. 請求項８、請求項９、請求項１０又は請求項１１に記載の高調波低減方法において、前記高調波低減回路にバイアス回路を付加してあることを特徴とする三相４線式配電線の電力供給回路の高調波低減方法。   The harmonic reduction method according to claim 8, claim 9, or claim 11, wherein a bias circuit is added to the harmonic reduction circuit of the three-phase four-wire distribution line. Harmonic reduction method for power supply circuit.
JP2005213515A 2005-03-08 2005-07-22 Power supply circuit and harmonic reduction method for three-phase four-wire distribution line with harmonic reduction circuit Expired - Fee Related JP4801390B2 (en)

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Cited By (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2014027716A (en) * 2012-07-24 2014-02-06 Odakyu Dentetsu Kk Power supply circuit, vehicle having power supply circuit, and power supply method
JP2015126678A (en) * 2013-12-27 2015-07-06 株式会社志賀機能水研究所 Electric power facility
CN105629087A (en) * 2014-10-17 2016-06-01 国家电网公司 Improved inverter anti-island detection method
JP2018137953A (en) * 2017-02-23 2018-08-30 株式会社志賀機能水研究所 Higher harmonic generator

Cited By (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JP2014027716A (en) * 2012-07-24 2014-02-06 Odakyu Dentetsu Kk Power supply circuit, vehicle having power supply circuit, and power supply method
JP2015126678A (en) * 2013-12-27 2015-07-06 株式会社志賀機能水研究所 Electric power facility
CN105629087A (en) * 2014-10-17 2016-06-01 国家电网公司 Improved inverter anti-island detection method
JP2018137953A (en) * 2017-02-23 2018-08-30 株式会社志賀機能水研究所 Higher harmonic generator

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