JP2005210794A - Linear electromagnetic actuator - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To provide a linear electromagnetic actuator increased in thrust per cubic volume. <P>SOLUTION: The linear electromagnetic actuator comprises: an armature 550 constituted by arranging one or more core units 504 to 506 each composed of a core that is formed of a magnetic body and has an almost H-shaped cross section and, a coil that is wound around to the central main part of the core and energized with an AC current; and field yokes 650A, 650B that are arranged so that N and S poles of the field yokes 650A, 650B are alternately and cyclically disposed in the axial direction of the coil so that the N and S poles face the cores via a space. The armature 550 and the field yoke 650A, 650B are movable with respect to the axial direction of the coil. <P>COPYRIGHT: (C)2005,JPO&NCIPI

Description

  The present invention relates to a linear electromagnetic actuator having an iron core in an armature, and more particularly to an improvement for improving thrust generation efficiency in a linear electromagnetic actuator.

FIG. 18 is a block diagram of a general cored linear motor showing the first prior art.
This linear motor is composed of an armature 100 and a field element 200, both of which are opposed to each other with a gap. The armature 100 includes a coil 103, and the field element 200 includes a magnetic pole 202 in which N and S poles of permanent magnets are alternately arranged. In the armature 100, 101 indicates a core, 102 indicates a tooth, and in the field element 200, 201 indicates a field element yoke.
Here, there are two types of armatures: those having an iron core (core) (with a core) and those having no core (coreless). In the present invention, the armature with a core is targeted.

In FIG. 18, a relative thrust is generated between the armature 100 and the field element 200 due to the interaction between the magnetomotive force of the coil 103 and the magnetic flux from the magnetic pole 202.
In addition, as the field element 200, it is also possible to form a field by a coil instead of the magnetic pole 202 by a permanent magnet. In addition, if the field element has a ladder-shaped conductor surrounded by an iron core, it is an induction motor. Further, if the field element has a periodic row of protrusions on the surface facing the armature, a reluctance motor. Each functions.
For details on the thrust generation principle of this type of linear motor with core, see Shiraki and Miyao, “Illustrations and Linear Servo Motors and System Design”, General Electronic Publishing (published on March 20, 1986, 1st edition), etc. Since it is widely known, detailed description is omitted.

FIG. 19 is a configuration diagram of a suction force canceling type linear motor with a core showing the second prior art.
In a linear motor with a core, a magnetic attractive force acting between the armature core and the field element becomes a problem. In general, it is not uncommon for this attractive force to reach 10 times the relative thrust between the armature and the field element. In order to maintain the gap length between the armature and the field element at a predetermined length under such a strong attractive force, the armature and the field element are held relatively movable. For this reason, it is required that the mechanism for this is extremely robust, which causes a problem that the apparatus becomes large and expensive.

As a countermeasure, there is a method of offsetting the attractive force between the field element and the armature by arranging an armature between two opposingly arranged field elements.
The prior art in FIG. 19 is based on the above idea, and an armature 103 is arranged between two field elements 200, 200 arranged opposite to each other so as to face the magnetic poles 202. Reference numeral 104 denotes a core of the armature 103, and 105 denotes a coil.

With such a configuration, the magnetic attractive force can be significantly reduced by appropriately maintaining the gap length between both sides (upper and lower in the figure) of the armature 103 and the field elements 200, 200. A simpler holding mechanism can also be used. This type of configuration is also described in the above-mentioned known literature.
An example in which the attractive force between the field element and the armature is offset similarly is shown in Patent Document 1, although the configuration is different from that in FIG.

Furthermore, FIG. 20 is a block diagram of a linear motion mechanism (rack & pinion) showing the third prior art.
In FIG. 20, 301 is a rotary motor, 302 is a pinion, 401 is a rack, and 402 is an operated part. The rotational movement of the motor 301 is converted into linear movement of the operated part 402 via the pinion 302 and the rack 401. The

  In general, as a linear motion mechanism, a configuration in which various mechanisms (for example, a rack and pinion, a belt, a ball screw, etc.) are driven by a rotary motor to obtain a linear motion is often used. However, this type of linear motion mechanism requires maintenance, and it is difficult to increase the precision due to backlash and belt slack, and there is a problem that it is difficult to increase the speed of the linear motion portion due to the limitations of the mechanism portion.

JP-A-60-98863

Compared with the linear motion mechanism of FIG. 20, the linear motor does not have the above-described drawbacks, and has the advantage of being able to perform high-speed and high-precision operation and greatly contribute to the improvement of productivity.
However, the linear motor generally has a lower thrust generation efficiency than the rotary motor + linear motion mechanism. To obtain the required thrust, the motor becomes larger or the loss increases due to an increase in coil current. In addition, there is a problem that the calorific value increases as a result.
Therefore, the present invention is intended to provide a linear electromagnetic actuator capable of improving the thrust generation efficiency without causing an increase in size, loss, or heat generation of the apparatus.

In order to solve the above problems, the invention described in claim 1 is a core comprising a substantially H-shaped core made of a magnetic material, and a coil wound around a central trunk of the core and through which an alternating current is passed. A first component formed by arranging one or more units in the axial direction of the coil;
A second component formed by arranging two magnetic bodies each having a surface having periodic magnetic characteristics in the axial direction of the coil so that the surfaces face the core via a gap;
The first component and the second component are relatively movable in the axial direction of the coil.

The invention described in claim 2 comprises a core unit comprising a core made of a magnetic material and having a substantially H-shaped cross section, and a coil wound around a central trunk portion of the core and through which an alternating current flows. A first component formed by arranging one or more in the axial direction of the coil;
A second component formed by arranging two magnetic bodies in which N and S magnetic poles are alternately and periodically arranged in the axial direction of the coil so that the N and S magnetic poles face each other through a gap. With
The first component and the second component are relatively movable in the axial direction of the coil.

The invention described in claim 3 is the linear electromagnetic actuator according to claim 1 or 2,
The electrical angle with respect to the periodic magnetic characteristics of the second component of the coil constituting the core unit of each phase using k core units of n phases (k and n are both natural numbers). The first component is configured so that the average value of the phase is distributed at (360 / n) °, and n-phase AC power is supplied to the coil, thereby forming an n-phase linear motor.

The invention described in claim 4 is the linear electromagnetic actuator described in claim 3,
The first component is characterized in that a single-phase core unit group in which k core units are arranged adjacent to each other is arranged side by side for n phases.

The invention described in claim 5 is the linear electromagnetic actuator according to claim 3,
The first component is characterized in that k core units are arranged side by side, and n core units arranged one by one for each phase.

The invention described in claim 6 is the linear electromagnetic actuator described in claim 5,
The length of the core unit along the moving direction is an electrical angle of (360 ° -180 ° / n) or less.

The invention described in claim 7 is the linear electromagnetic actuator described in any one of claims 1 to 6,
The core is configured by combining two core members having a substantially T-shaped cross section divided by the central trunk.

The invention described in claim 8 is the linear electromagnetic actuator described in any one of claims 1 to 6,
The core is configured by combining core members having a substantially T-shaped cross section and a substantially I-shaped cross section.

The invention described in claim 9 is the linear electromagnetic actuator described in any one of claims 1 to 8,
A through hole is formed in a portion of the core near the central trunk where the coil is not wound, and both holding members are sandwiched by the first and second holding members from both sides centering on the axis of the coil and through the through hole. Are fastened with bolts.

  According to the present invention, it is possible to realize a linear electromagnetic actuator that can reduce the copper loss and the amount of heat generation, and have a large thrust per volume and can be miniaturized by a structure in which unnecessary coil portions are substantially removed.

Hereinafter, embodiments of the present invention will be described with reference to the drawings. First, FIG. 1 is a conceptual explanatory diagram of each embodiment of the present invention, and corresponds to the invention of claim 1.
FIG. 1A is an enlarged view of two teeth of an armature in a general linear motor with a core, wherein 501 is an armature core, 502 is a tooth, 503 is a coil wound around the tooth 502, and 602. Indicates a magnetic pole of a field element made of a permanent magnet.

In the above configuration, the magnetic flux from the magnetic pole 602 enters from one of the adjacent teeth 502, and the magnetic flux exits from the other tooth 502. When the field element moves relative to the armature, the magnetic flux passing through the teeth 502 alternates. When this alternating magnetic flux is linked to the coil 503 wound around each tooth 502 in an intensive manner, an induced voltage is generated in the coil 503.
Now, when the motor is a multiphase motor and the electrical angle of the teeth 502 with respect to the magnetic pole 602 is appropriately changed for each phase, an appropriate phase difference is generated in the induced voltage of the coil 503 of each phase. Therefore, continuous thrust can be obtained by passing a multiphase alternating current corresponding to the relative position of the armature and the field element through each phase coil 503.

  Here, the magnetic flux that passes through the tooth 502 of an armature becomes maximum when the tooth 502 faces the magnetic pole 602. For the shape of a certain tooth, the maximum magnetic flux depends on the thickness of the magnetic pole 602 and the gap length. Determined by. Now, considering that the pitch of the adjacent teeth 502 is substantially equal to the pitch of the magnetic poles 602, in this case, the magnetic fluxes of the two magnetic poles 602 passing through both teeth 502 are opposite but take the maximum value at the same time.

  At this time, even if the two teeth 502 are separated from the other teeth as shown in FIG. 1B and the magnetic flux is returned by the two teeth 502, the maximum value of the magnetic flux remains unchanged. Since the maximum thrust generated by one tooth 502 for a certain coil current value is proportional to the maximum value of the linkage flux caused by the magnetic pole 602 as a general tendency, the maximum thrust generated by the two teeth 502 is The case of FIG. 1A is the same as the case of FIG.

In FIG.1 (b), the coil 503 is separately wound by both teeth 502, respectively. Here, since the core is separated for every two teeth, the coil part 503a passing outside the two teeth 502 does not contribute to the generation of thrust, and the coil part contributing to the generation of thrust is sandwiched between the two teeth 502. (In contrast, in FIG. 1 (a), since the core is connected across many teeth, the two coil parts in each slot all generate thrust.) Contributes to).
Therefore, although it can be said that the coil part 503a is unnecessary from the viewpoint of thrust generation, since the coil 503 is wound around each tooth 502, in this configuration, the coil part 503a does not exist on the outside. The two outer coil portions 503a cannot simply be removed.

Therefore, a structure in which the structure of FIG. 1B is arranged on the top and bottom and the upper sides of the two cores are overlapped as shown in FIG. In FIG. 1C, 501A and 501B are cores, and 602A and 602B are magnetic poles.
At this time, in order to obtain the thrust in the same direction by the upper and lower cores 501A and 501B, the direction of the magnetic flux by the magnetic poles 602A and 602B is the upper and lower objects. There is a need to. Therefore, the coil portions 503x and 503y in the upper and lower slots may be formed by one coil.

That is, a configuration (core unit) in which a coil is intensively wound around a central trunk portion of a core having a substantially H-shaped cross section (consisting of the cores 501A and 501B) as a result can be considered as a one-phase thrust generation unit. . Here, the end faces of both sides orthogonal to the central trunk of the H-shaped core are opposed to the magnetic poles 602A and 602B through a gap.
In this structure, since the field elements are present on both the upper and lower sides of the armature, it can be understood that the linear motor is an attractive force canceling type.
In the case of a single-phase motor, it is possible to use only one core unit shown in FIG. 1C as a vibration actuator.

FIG. 2 shows an example in which a multiphase linear motor is constructed by integrating a plurality of core units based on the structure shown in FIG. 1C in the axial direction of the coil. 550 is an armature, and 650A and 650B. Is a field element, and 601A and 601B are field element yokes.
In the case of a multiphase motor, the core unit may be assigned to each phase and the relative position with respect to the magnetic pole may be appropriately changed for each phase. For example, FIG. 2 shows a configuration example of a three-phase motor, and the core units 504, 505, and 506 assigned to the three-phase phases are arranged with an electrical angle of 60 °. 504C, 505C, and 506C are H-shaped cores, and 507, 508, and 509 are coils.

In FIG. 2, if the polarities of the left and right coils 507 and 509 are reversed with respect to the polarity of the central coil 508, the induced voltage caused by the magnetic poles 602A and 602B of the three coils 507 to 509 is 120 ° in electrical angle. It will be distributed with a phase difference, and it turns out that it functions as a three-phase motor.
Also, the shapes of the cores 504C, 505C, and 506C are different from the conceptual diagram of FIG. 1C, and the tip portions of the facing surfaces of the field elements 650A and 650B (magnetic poles 602A and 602B) are on the side as shown in FIG. The shape may warp in the direction.

The advantages of the H-core linear motor shown in FIG. 2 are as follows.
(1) As described in the description with reference to FIGS. 1A to 1C, this corresponds to a structure in which a coil portion unnecessary for thrust generation is removed, so that copper loss can be reduced. This means a reduction in the amount of heat generated. When heat generation similar to that in the prior art is allowed, a larger amount of current can be passed and the thrust per volume can be increased.
(2) Since there are no unnecessary coil parts, the cores 504C, 505C, and 506C can be arranged close to each other as shown in FIG. 2, so that the thrust per volume of the armature can be increased.

  In the configuration of FIG. 2, the armature 550 including a core having a substantially H-shaped cross section and a coil wound around the core is referred to as a first component for convenience, and the armature 550 is provided with a magnetic pole via a gap. For convenience, the field elements 650A and 650B facing each other 602A and 602B (so-called magnetic body having a surface having periodic magnetic characteristics in the axial direction of the coil) are referred to as second constituent elements.

Next, FIG. 3 is a configuration diagram of a main part showing a second embodiment of the present invention, and corresponds to the invention of claim 2.
The main feature of the present invention resides in the armature. On the other hand, various structures of the field element are conceivable as in a general motor. First, as described above, a configuration in which a permanent magnet is used as the magnetic pole of the field element is conceivable. In this case, since the magnetic flux of the permanent magnet is used, there is a feature of high efficiency and large thrust.

  When using a permanent magnet in this way, as shown in FIG. 3, N and S magnetic poles 604 and protrusions 605 made of permanent magnets are alternately and periodically arranged on the surface of the field element yoke 606. May be. Further, although not shown, it is a matter of course that a so-called IPM type in which a magnetic pole made of a permanent magnet is embedded in an iron core may be used.

FIG. 4 is a configuration diagram of a main part showing a third embodiment of the present invention.
In this embodiment, a field pole 608 is formed by winding a field coil 607 around a protrusion of a field element yoke 606, and a field pole 608 facing an armature core (H-shaped core) (not shown). A magnetic pole surface having periodic magnetic characteristics is formed by the surface of the magnetic field.

FIG. 5 is a block diagram showing a fourth embodiment of the present invention.
The field element in this embodiment has a plurality of protrusions 609 arranged in parallel on the opposing surfaces of the field element yokes 601A and 601B, thereby periodically forming the surface of the protrusion 609 facing the H-shaped cores 504C, 505C and 506C. A magnetic pole surface having magnetic characteristics is formed, and a motor using reluctance force is constituted by the armature 550 and the field elements 651A and 651B. The configuration of the armature 550 is substantially the same as that shown in FIG.
Any field element may be used as long as it has a periodic magnetic characteristic in the longitudinal direction. Therefore, not only the protrusion 609 as shown in FIG. It may be configured to increase the magnetic resistance.

FIG. 6 is a block diagram showing a fifth embodiment of the present invention.
In this embodiment, a plurality of child teeth 611 are formed on the opposing surfaces of the field element yokes 610A and 610B to form the field elements 652A and 652B, and the field elements of the cores 510C, 511C, and 512C of the armature 551 are formed. Small teeth 513 having a substantially equal pitch are also provided on the surface facing 652A and 652B, whereby the actuator can be operated on the principle of a stepping motor.
At this time, it is also possible to constitute a hybrid stepping motor by arranging permanent magnets in either or both of the field element and the armature.

FIG. 7 is a top view and a side view of a field element showing a sixth embodiment of the present invention.
In this embodiment, an inductive field element 653 is configured by combining a flat iron core 654 and a ladder-shaped conductor 655. Such a configuration is known as an induction type linear motor, and a typical application is a linear motor for driving a railway.

  It should be noted that any of the above-described embodiments of FIGS. 4 to 7 is included in the invention of claim 1.

FIG. 8 is a block diagram showing a seventh embodiment of the present invention, and corresponds to the invention of claim 3.
When a multiphase linear motor is realized by the linear electromagnetic actuator according to the present invention, it is necessary to appropriately perform the relative position and connection of each core unit. This method will be described here.

  FIG. 8 shows an example of a three-phase motor, in which two cores U1, V1, W1, U2, V2, and W2 are used for each phase. Here, the six core units U 1, V 1, W 1, U 2, V 2, W 2 are integrally formed as a whole to constitute one armature 552. In other words, two armatures 550 shown in FIG. 2 are connected to form the armature 552 shown in FIG.

  In FIG. 8, the positions of the core units U1, V1, W1, U2, V2, W2 (coils 507, 508, 509, 514, 515, 516) are 60 °, 0 °, −60 ° in electrical angle, respectively. -90 °, 210 °, and 150 °. Since all the coils 507, 508, 509, 514, 515, and 516 are integrally fixed by means (not shown), when the relative positions of the armature 552 and the field elements 650A and 650B change, each core unit U1. , V1, W1, U2, V2, and W2 remain unchanged and the positions of all core units change equally.

In general, in the motor, the electrical angle phase is changed by 180 ° by reversing the polarity of the coil. Therefore, in this embodiment, the polarity of every other coil 507, 509, 515 is changed to the polarity of the other coils 508, 514, 516. , The phases of the coils 507, 508, 509, 514, 515, 516 are respectively
It can be set to −120 °, 0 °, 120 °, −90 °, 30 °, and 150 °.

Therefore, as shown in FIG. 9, if the coils 508 and 515, 509 and 516, and 507 and 514 are connected in series, and each series circuit is Y-connected or Δ-connected, the average phase of each phase is −105 °. , 15 °, 135 °, and so on, with a 120 ° interval distribution, a three-phase motor can be configured.
From the above explanation, the following can be said inductively. That is, when the number of phases is n and the number of coils per each phase (number of core units) is k (n and k are natural numbers), the average value of the electrical angle phases of k coils in each phase is ( If it is configured to be distributed at 360 / n) °, an n-phase linear motor can be configured.

Next, FIG. 10 is a configuration diagram of a main part showing an eighth embodiment of the present invention.
This embodiment relates to the structure of the H-shaped core. As shown in FIG. 10, the H-shaped core is divided at the central trunk portion, and the core members 517A and 517B having the same structure and having substantially T-shaped cross sections are joined. Composed. Reference numeral 520 denotes a coil.

With the above configuration, the space factor of the coil can be improved. That is, when the H-shaped core is non-divided and the slot opening is narrow, the coil is wound around the central trunk portion by inserting a nozzle inside the slot. Therefore, the space factor cannot be increased. On the other hand, when the H-shaped core is divided as shown in FIG. 10, a bobbin coil having a high space factor or an air-core coil using a self-bonding wire can be used.
By increasing the coil space factor in this way, it is possible to reduce the generation loss when the current necessary for generating the thrust is passed, so that the thrust generation efficiency of the motor can be increased. Further, since two core members having the same structure may be used, the number of types of parts may be reduced.

FIG. 11 and FIG. 12 are configuration diagrams of main parts showing a ninth embodiment of the present invention, and correspond to the invention of claim 8.
In this embodiment, the H-shaped core 518 is realized by a coupling structure of a core member 518A having a substantially T-shaped cross section and a core member 518B having a substantially I-shaped cross section as shown in FIG. In this embodiment, as shown in FIG. 12 as a modification of FIG. 11, the mechanical strength can be increased by configuring the core 519 by connecting two core members 519 </ b> A and 519 </ b> B with a fitting structure.

FIG. 13 is a top view and a side view of a main part showing a tenth embodiment of the present invention, and corresponds to the invention of claim 6. This embodiment relates to fixing means for the H-shaped core.
As shown in FIG. 13, a through-hole 523 that penetrates the H-shaped cross section on the front and back sides is provided at a site where the coil 520 is not wound in the vicinity of the central trunk portion of the H-shaped core 522 constituting the core unit 521. Note that when the core 522 is formed of a laminated steel plate, it is only necessary to provide the through-hole 523 when the steel plate is punched, and thus no additional processing is necessary.
The position of the through hole 523 is desirably as far as possible on the extension line of the center of the central trunk. This is because the magnetic flux flow is hindered to cause local magnetic saturation regardless of whether it is shifted from the extension line of the central trunk portion or inward.

  On the other hand, 524 and 525 are first and second holding members for sandwiching and fixing a plurality of core units 521, and a bolt 526 is inserted into the second holding member 525. The first holding member 524 can be fastened to the first holding member 524 with the core unit 521 sandwiched therebetween. A recess 527 for receiving the coil 520 is formed on the inner surface of each holding member 524, 525.

According to this embodiment, the two holding members 524 and 525 are used, fastened by the bolts 526 with the plurality of core units 521 sandwiched from both sides around the axis of the coil, and the whole is integrated. An armature with high mechanical rigidity can be formed.
In addition, after fastening using the bolt 526, a mold that fills the gap between the armatures can be applied. In this case, the mechanical strength is further increased, and the coil 520 can be efficiently dissipated by using a molding material having a high thermal conductivity.
The fixing means for the H-shaped core shown in FIG. 13 can be applied to the above-described embodiments.

  Now, in the linear motor having the three-phase configuration as shown in FIG. 8, various methods can be considered for arranging the core units, and each has advantages and disadvantages. Below, each embodiment which has the characteristic in how to arrange a core unit is described.

First, FIG. 14 is a block diagram showing an eleventh embodiment of the present invention, which corresponds to the invention of claim 4 although it is around.
FIG. 14 shows an example in which the total number of core units is six, i.e., n = 3, k = 2, and U1, V1, W1, U2, V2, and W2 are core units, 507, 508, and 509 in the same manner as described above. , 514, 515, 516 denote coils.

Two core units belonging to each phase are arranged so as to be adjacent to each other (U1 and U2, V1 and V2, W1 and W2), and core unit groups U0, V0, and W0 of each phase are sequentially arranged. Thus, an armature (first component) 553 is configured. In FIG. 14, the electrical angles of the coils 508, 515, 509, 516, 507, and 514 belonging to the core unit groups U0, V0, and W0 of each phase are equal to each other, and are shifted from each other by 120 ° in three phases. (By reversing the polarity of the V-phase coils 509 and 516 with respect to the U and W phases).
According to this configuration, since the coils of the respective phases are close to each other, there is an advantage that wiring is facilitated when connecting as shown in FIG. 9 described above.

FIG. 15 is a block diagram showing a twelfth embodiment of the present invention, and corresponds to the invention of claim 4 as in the eleventh embodiment.
In this embodiment, the electrical angles of the coils 508, 515, 509, 516, 507, and 514 belonging to the core unit groups U0, V0, and W0 of each phase of the armature 554 have a phase difference of 30 °, respectively. . Such a configuration is effective when it is desired to smooth the thrust by reducing the harmonics and cogging force included in the induced voltage.

FIG. 16 is a block diagram showing a thirteenth embodiment of the present invention, and corresponds to the invention of claim 5.
This embodiment is an example in which n = 3 and k = 2 as in FIGS. Similarly to FIG. 8, the core units U1, V1, W1, U2, V2, and W2 belonging to each phase are arranged adjacent to each other to form two three-phase core unit groups G1 and G2. In the individual core unit groups G1 and G2, the electrical angles of the coils are shifted from each other by 120 °. (By reversing the polarity of the U-phase coil with respect to the W and V phases). An armature 555 is configured by arranging the core unit groups G1 and G2. In the example of FIG. 16, the electrical angles of the two core unit groups G1, G2 are equal.

In this embodiment, only a single core unit group functions as a three-phase linear motor. Therefore, this can be set as the minimum structural unit, and when it is desired to increase the generated thrust, a required number of core unit groups are selected. Since they only need to be connected, products can be grouped at low cost.
The configuration shown in FIG. 8 is also included in claim 8. In the example of FIG. 8, the electrical angle is shifted by 30 ° between the two core unit groups, which is effective in suppressing harmonics and cogging force included in the induced voltage.

FIG. 17 is a configuration diagram showing a fourteenth embodiment of the present invention, and corresponds to the invention of claim 6.
According to the configuration of FIG. 16, an n-phase (for example, three-phase) linear motor is configured by one core unit group. Therefore, the electrical angle of each phase core unit (coil) belonging to the core unit group depends on the number of phases. It is necessary to distribute.

  Specifically, when the number of phases is an odd number, an angle obtained by dividing 360 ° by the number of phases (360 ° / n), and when the number of phases is an even number, an angle obtained by dividing 180 ° by the number of phases ( At 180 ° / n), it is necessary to distribute each. However, as described above, these electrical angles can be changed by 180 ° by reversing the coil polarity. Therefore, even if n is an odd number, it may be distributed at (180 ° / n).

For example, n is an odd number, and the electrical angle of the coil of each phase core unit is respectively
180 ° / n, 2 × 180 ° / n, 3 × 180 ° / n, ..., (n-1) × 80 ° / n, 180 °
Then, by reversing the polarity of the coil of the odd-numbered core unit and changing it by 180 °,
{(N + 1) / 2} × 360 ° / n, 360 ° / n, {(n + 3) / 2} × 360 ° / n,..., {(2n−1) / 2} × 360 ° / n, 180 °
And rearranging this,
360 ° / n, 2 × 360 ° / n,…, 180 °,…, {(2n−1) / 2} × 360 ° / n
And distributed at (360 ° / n).

  Therefore, if the phase shift between adjacent coils is 180 ° / n, the phase angles of all the coils are sequentially shifted by a predetermined electrical angle, which is convenient. In order to realize this, the electrical angle phase difference when adjacent core units are closely arranged must not be less than 180 ° / n. This means that the length along the moving direction of the core unit must be not more than (360 ° -180 ° / n) in electrical angle.

On the other hand, if the length of the core unit in the moving direction is longer than this, the core units cannot be closely arranged in order to make the electrical angle phases of the coils have a predetermined relationship. As a result, it is necessary to provide between the core units, resulting in an increase in the size of the apparatus.
Here, since the example of FIG. 17 has three phases, as shown in the figure, the upper limit of the moving direction length of the core units U1, V1, and W1 is 360 ° −180 ° / 3 = 300 °. If this condition is satisfied, the core units W1, U1, and V1 can be disposed without waste so that the electrical angles of the coils 507, 508, and 509 have a predetermined relationship.

14 to 17, the structure of the H-shaped core shown in FIGS. 10 to 12 and the fixing means for the H-shaped core shown in FIG. 13 can be applied.
Furthermore, the arrangement of the core units shown in FIGS. 14 to 17 is naturally applicable to cases other than n = 3 and k = 2.

It is a conceptual explanatory view of the first embodiment of the present invention. It is a block diagram of the multiphase linear motor by 1st Embodiment of this invention. It is a block diagram of the principal part which shows 2nd Embodiment of this invention. It is a block diagram of the principal part which shows 3rd Embodiment of this invention. It is a block diagram which shows 4th Embodiment of this invention. It is a block diagram which shows 5th Embodiment of this invention. It is the top view and side view of a field element which show 6th Embodiment of this invention. It is a block diagram which shows 7th Embodiment of this invention. FIG. 9 is a connection diagram of coils of each phase in FIG. 8. It is a block diagram of the principal part which shows 8th Embodiment of this invention. It is a block diagram of the principal part which shows 9th Embodiment of this invention. It is a block diagram of the principal part which shows 9th Embodiment of this invention. It is the top view and side view of the principal part which show 10th Embodiment of this invention. It is a block diagram which shows 11th Embodiment of this invention. It is a block diagram which shows 12th Embodiment of this invention. It is a block diagram which shows 13th Embodiment of this invention. It is a block diagram which shows 14th Embodiment of this invention. It is a block diagram which shows 1st prior art. It is a block diagram which shows a 2nd prior art. It is a block diagram which shows a 3rd prior art.

Explanation of symbols

501, 501A, 501B: Core 502: Teeth 503, 507, 508, 509, 514, 515, 516, 520: Coil 503a, 503x, 503y: Coil parts 504, 505, 506, 510, 511, 512, 521, U1 , U2, V1, V2, W1, W2: Core units U0, V0, W0, G1, G2: Core unit groups 504C, 505C, 506C, 510C, 511C, 512C, 517, 518, 519, 522: Core 509: Small Teeth 517A, 517B, 518A, 518B, 519A, 519B: Core member 523: Through hole 524, 525: Holding member 526: Bolt 527: Recess 550-556: Armature 601A, 601B, 606A, 610A, 610B: Field element Yoke 602, 602A, 602B: magnetic pole 6 07: Field coil 608: Field magnetic pole 605, 609: Projection 611: Small teeth 650A, 650B, 651A, 651B, 652A, 652B, 653: Field element 654: Conductor 655: Ladder-shaped conductor

Claims (9)

One or more core units including a core having a substantially H-shaped cross section made of a magnetic material and a coil that is wound around the central trunk of the core and through which an alternating current flows are arranged in the axial direction of the coil. A first component;
A second component formed by arranging two magnetic bodies each having a surface having periodic magnetic characteristics in the axial direction of the coil such that the surfaces face the core with a gap therebetween; Prepared,
The linear electromagnetic actuator, wherein the first component and the second component are relatively movable in the axial direction of the coil. One core unit made of a magnetic material and having a substantially H-shaped cross section and a coil wound around the central trunk of the core and through which an alternating current flows is provided in the axial direction of the coil. A first component arranged as described above;
A second magnetic body in which N and S magnetic poles are alternately and periodically arranged in the axial direction of the coil is disposed so that the N and S magnetic poles face the core with a gap therebetween. A component, and
The linear electromagnetic actuator, wherein the first component and the second component are relatively movable in the axial direction of the coil. The linear electromagnetic actuator according to claim 1 or 2,
The electrical angle with respect to the periodic magnetic characteristics of the second component of the coil constituting the core unit of each phase using k core units of n phases (k and n are both natural numbers). A linear electromagnetic actuator comprising: a first component configured to distribute an average value of phases at (360 / n) ° and supplying n-phase AC power to the coil. The linear electromagnetic actuator according to claim 3,
The first component is a linear electromagnetic actuator characterized in that one phase of a core unit group in which k core units are arranged adjacent to each other is arranged side by side for n phases. The linear electromagnetic actuator according to claim 3,
The first component element is a linear electromagnetic actuator characterized in that k core units arranged in a row are arranged side by side, one for each phase. The linear electromagnetic actuator according to claim 5,
The linear electromagnetic actuator characterized in that the length along the moving direction of the core unit is an electrical angle of (360 ° -180 ° / n) or less. In the linear electromagnetic actuator according to any one of claims 1 to 6,
A linear electromagnetic actuator characterized in that the core is composed of two core members each having a substantially T-shaped cross section divided by the central trunk. In the linear electromagnetic actuator according to any one of claims 1 to 6,
A linear electromagnetic actuator characterized in that the core is configured by combining core members having a substantially T-shaped cross section and a substantially I-shaped cross section. The linear electromagnetic actuator according to any one of claims 1 to 8,
A through hole is formed in a portion of the core where the coil near the central trunk is not wound, and the coil unit is sandwiched by first and second holding members from both sides centering on the coil axis. A linear electromagnetic actuator characterized in that both holding members are fastened by bolts via a bolt.

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