JP2004208200A - Radio receiving device and antenna verification method - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To provide a radio receiving device and an antenna verification method wherein antenna verification is enabled even if the number of pilot symbols of DPCCH is one. <P>SOLUTION: A rotation part 110 performs rotation of ±π/2 to a CPICH-Ant#2 phase estimation and computes phase estimations in which rotation Ψ is performed, respectively and which are hypotheses of phase rotation which are used by a base station instrument. An addition part 111 adds a CPICH-Ant#1 phase estimation and a phase estimation output from the rotation part 110. An inner product calculation part 112 computes inner product of a DPCCH pilot-Ant#1 phase estimation and output of the addition part 111. A maximum detection part 113 detects the maximum of computed each inner product value and outputs Ψ corresponding to the maximum as a phase rotation estimation used in the base station instrument. <P>COPYRIGHT: (C)2004,JPO&NCIPI

Description

と表される。ここで、ｍはスロット番号、α₁及びα₂は、送信アンテナ１、２から受信側までの各パスの伝搬路係数、Ａ_dpcchPilot1、Ａ_dpcchPilot2は、ＤＰＣＣＨのパイロットの送信アンテナ１、２の各パイロットシンボルを示している。また、φ(ｍ)は、基地局が送信アンテナ２のＤＰＣＨ信号に対し回転させた回転角を意味し、具体的にはπ／４、３／４π、５／４π、７／４πのいずれかである。また、β_DPCCHは、ＤＰＣＣＨの送信信号の振幅を意味する。
【００４９】
先に述べたように送信アンテナ２の送信シンボルを送信アンテナ１の送信シンボルに位相回転の複素ウェイトを乗じたものとみなすと、
【数２】

のようになる。なお、ここでｅ±^jπ^/2の項の回転角は、スロット番号で一意に決まる値であり、以後これをλ(ｍ)とする。（式２）を（式１）に代入すると、
【数３】

となる。よって、ＤＰＣＣＨの位相推定値は、
【数４】

と表される。ここで、Ａ^* _dpcchPilot1はＡ_dpcchPilot1の複素共役である。
【００５０】
回転部１１０は、スロット番号ｍに応じて、基地局装置の送信アンテナ２から送信されたＣＰＩＣＨの位相推定値に対し、λ(ｍ)＝±π／２の回転を行う。次に、φ(ｍ)の候補として、ψ_n＝１／４π，３／４π，５／４π，７／４π（ただし、ｎ＝１，２，３，４）の回転をそれぞれ行った位相推定値を算出し、加算部１１１に出力する。
【００５１】
加算部１１１は、位相推定部１０３−１から出力された、基地局装置の送信アンテナ１から送信されたＣＰＩＣＨの位相推定値と、回転部１１０から出力された位相回転後の位相推定値（基地局装置の送信アンテナ２から送信）とをベクトル加算し、
【数５】

を算出し、内積算出部１１２に出力する。ただし、ξ_CP1(ｍ)、ξ_CP2(ｍ)は、送信アンテナ１、２それぞれのＣＰＩＣＨ位相推定値である。
【００５２】
内積算出部１１２は、上記の４通りのψについて、ξ_DP(ｍ)とξ_CP(ｍ,ｎ)の内積を算出し、最大値検出部１１３に出力する。
【００５３】
このように、本実施の形態によれば、ＤＰＣＣＨのパイロットシンボル数が１の場合でもアンテナベリフィケーションを行うことができ、無線受信装置の受信性能を向上させることができる。
【００５４】
なお、ここでは、ＲＡＫＥ合成のフィンガが１０系統の場合を例にとって説明したが、ＲＡＫＥ合成のフィンガの数はこれに限定されない。
【００５５】
また、ここでは、送信アンテナ２のパイロットシンボルを送信アンテナ１のパイロットシンボルを回転したものとみなす場合を例にとって説明したが、逆に送信アンテナ１のパイロットシンボルを送信アンテナ２のものが回転したものと考えて計算しても良い。
【００５６】
（実施の形態２）
本発明の実施の形態２に係る無線受信装置は、図１に示した無線受信装置と同様の構成を採るので、実施の形態１と異なるアンテナベリフィケーション部１０４ａの構成のみを図４に示す。なお、図２に示したアンテナベリフィケーション部１０４と同一の構成要素には同一の符号を付し、その説明を省略する。
【００５７】
本実施の形態の特徴は、正規化部２０１をさらに有することである。
【００５８】
図４において、正規化部２０１は、加算部１１１において、ＣＰＩＣＨのアンテナ１とアンテナ２の位相推定値をベクトル加算した（式５）に示されるベクトルの大きさを１となるように正規化を行う。すなわち、
【数６】

を算出する。ここで、ξ_CP(ｍ,ｎ)は、ＣＰＩＣＨ位相推定値のアンテナ１、２のベクトルの向きにより大きさが変化し、また、ξ_DP(ｍ)とξ_CP(ｍ,ｎ)の内積値は、ξ_CP(ｍ,ｎ)の大きさに応じて変化する。よって、ξ_CP(ｍ,ｎ)自体の大きさの影響が大きい場合、内積値の最大値判定において誤判定が発生するおそれがあるが、ξ_CP(ｍ,ｎ)の大きさを１とする正規化を行えば、このような誤判定をなくすことができる。
【００５９】
このように、本実施の形態によれば、ξ_CP(ｍ,ｎ)の大きさを１とする正規化を行うことにより、内積値の最大値判定において誤判定をなくすことができ、無線受信装置の受信性能を向上させることができる。
【００６０】
（実施の形態３）
本発明の実施の形態３に係る無線受信装置は、図１に示した無線受信装置と同様の構成を採るので、実施の形態１と異なるアンテナベリフィケーション部１０４ｂの構成のみを図５に示す。なお、図２に示したアンテナベリフィケーション部１０４と同一の構成要素には同一の符号を付し、その説明を省略する。
【００６１】
本実施の形態の特徴は、位相差算出部３０１および最小値検出部３０２を有することである。
【００６２】
図５において、位相差算出部３０１は、加算部１１１において、ＣＰＩＣＨのアンテナ１とアンテナ２の位相推定値をベクトル加算した（式５）に示されるベクトルと（式４）に示されるＤＰＣＣＨの位相推定値のベクトルとの位相差を算出する。最小値検出部３０２は、各ψにおけるＣＰＩＣＨ位相推定値とＤＰＣＣＨ位相推定値との位相差から最も位相差が小さいものを検出し、そのψを基地局での位相回転推定量として結果を出力する。
【００６３】
例えば、実施の形態１では、ξ_CP(ｍ,ｎ)は、ＣＰＩＣＨ位相推定値のアンテナ１、２のベクトルの向きにより大きさが変化し、また、ξ_DP(ｍ)とξ_CP(ｍ,ｎ)の内積値は、ξ_CP(ｍ,ｎ)の大きさに応じて変化する。よって、ξ_CP(ｍ,ｎ)自体の大きさの影響が大きい場合、内積値の最大値判定において誤判定が発生するおそれがあるが、上記のように位相差の最小値からψの推定を行うことにより誤判定をなくすことができる。
【００６４】
このように、本実施の形態によれば、ψの推定において誤判定をなくすことができ、無線受信装置の受信性能を向上させることができる。
【００６５】
（実施の形態４）
本発明の実施の形態４に係る無線受信装置は、図１に示した無線受信装置と同様の構成を採るので、実施の形態１と異なるアンテナベリフィケーション部１０４ｃの構成のみを図６に示す。なお、図２に示したアンテナベリフィケーション部１０４と同一の構成要素には同一の符号を付し、その説明を省略する。
【００６６】
本実施の形態の特徴は、送信アンテナ１、２それぞれのパイロットパターンで位相を推定し、送信アンテナ１、２それぞれのパターンで位相推定を行った位相推定値を合成することである。これは、パイロットのシンボル数が２以上の場合と同様である。実施の形態１、２、３では、アンテナ１のパイロットパターンのみを用いて位相推定を行っていた。
【００６７】
位相推定部１０３は、パイロットシンボル数が２以上の場合と同様に、送信アンテナ１、２それぞれのＤＰＣＣＨのパイロットパターンで位相を推定し、アンテナベリフィケーション部１０４内の加算部４０１に出力する。加算部４０１は、アンテナ１、２それぞれのパターンで位相推定を行った位相推定値を合成する。この場合、アンテナ１のパターンより得られる位相推定値は、
【数７】

であり、アンテナ２のパターンより得られる位相推定値は、
【数８】

となる。よって、これらを合成すると、
【数９】

と表される。
【００６８】
一方、合成部４０２は、ＣＰＩＣＨの送信アンテナ１の位相推定値と、送信アンテナ２の位相推定値を回転部１１０でψだけ回転させたベクトルを基に
【数１０】

を算出する。
【００６９】
内積算出部１１２は、４通りのψについてξ_DP(ｍ)とξ"_CP(ｍ,ｎ)の内積を算出し、最大値検出部１１３は、各内積値の最大値を検出し、そのψを基地局での位相回転推定量として結果を出力する。
【００７０】
このように、本実施の形態によれば、実施の形態１と同様の作用効果を得ることができる。
【００７１】
なお、実施の形態２のようにξ"_CP(ｍ,ｎ)を正規化してもよい。また、実施の形態３のようにξ_DP1(ｍ)＋ξ_DP2(ｍ)とξ"_CP(ｍ,ｎ)の位相差から推定しても良い。
【００７２】
【発明の効果】
以上説明したように、本発明によれば、ＤＰＣＣＨのパイロットシンボル数が１の場合のように、パイロットパターンが送信アンテナ１、２で直交していない場合でも、アンテナベリフィケーションを行うことができ、無線受信装置の受信性能を向上させることができる。
【００７３】
また、本発明によれば、ＣＰＩＣＨ位相推定値の加算ベクトルの大きさを正規化することにより、ＣＰＩＣＨの位相推定値自体の大きさから起こる誤判定を防ぐことができる。
【００７４】
さらに、本発明によれば、ＤＰＣＨ位相推定値とＣＰＩＣＨ位相推定値の位相差の最小値から回転角を推定することにより、ＣＰＩＣＨの位相推定値自体の大きさから起こる誤判定を防ぐことができる。
【図面の簡単な説明】
【図１】本発明の実施の形態１に係る無線受信装置の構成を示すブロック図
【図２】本発明の実施の形態１に係るアンテナベリフィケーション部の内部構成を示すブロック図
【図３】本発明の実施の形態１に係るアンテナベリフィケーション方法の手順の一例を示すフロー図
【図４】本発明の実施の形態２に係るアンテナベリフィケーション部の内部構成を示すブロック図
【図５】本発明の実施の形態３に係るアンテナベリフィケーション部の内部構成を示すブロック図
【図６】本発明の実施の形態４に係るアンテナベリフィケーション部の内部構成を示すブロック図
【符号の説明】
１００ 無線受信部
１０１ Ａ／Ｄコンバータ
１０２ 逆拡散部
１０３ 位相推定部
１０４ アンテナベリフィケーション部
１０５ 位相推定値算出部
１０６ 同期検波部
１０７ ＲＡＫＥ合成部
１０８ チャネルデコーダ
１１０ 回転部
１１１、４０１ 加算部
１１２ 内積算出部
１１３ 最大値検出部
２０１ 正規化部
３０１ 位相差算出部
３０２ 最小値検出部
４０２ 合成部[0001]
TECHNICAL FIELD OF THE INVENTION
The present invention relates to a radio receiving apparatus adopting a code division multiple access (CDMA) scheme and an antenna verification method used in the apparatus.
[0002]
[Prior art]
In recent years, the demand for land mobile communications such as automobiles and mobile phones has increased remarkably, and effective use of frequency is important to secure more subscriber capacity in a limited frequency band along with high-speed and high-quality transmission. Has become.
[0003]
A CDMA system has been drawing attention as one of the multiple access systems for effective frequency utilization. The CDMA system is a multiple access using spread spectrum communication technology, has a feature that it is hardly affected by multipath distortion, and a diversity effect can be expected by performing RAKE reception.
[0004]
In a mobile communication receiving station, a direct wave directly arriving from a transmitting station and a reflected wave arriving after being reflected by a building or the like are combined and received. At this time, since there are many paths of reflected waves, reflected waves of many paths (multipaths) are received. Therefore, the receiving station receives a composite wave of the received signals passing through many paths, and these received signals have a propagation delay time due to each path. Therefore, the reception signals cause interference between the received signals and cause fading.
[0005]
The spreading code of the CDMA method has a property that the autocorrelation is small when it is offset in time (the same spreading code is received with different delay times through multipath). Utilizing this property, in the despreading unit, a phase offset corresponding to each propagation delay time is given to the spreading code, and when the despreading is performed by the spreading code, the received signal of the propagation delay time corresponding to the phase offset is given. Can be obtained. That is, by giving a phase offset corresponding to the propagation delay time to the phase of the spread code, each signal can be obtained without causing interference between the received signals. Therefore, by providing a plurality of despreading units in parallel and performing despreading processing in each despreading unit using a spreading code to which a phase offset corresponding to the propagation delay time of the received signal is given, a plurality of despreading paths (multi-paths) are obtained. Path) can be independently obtained.
[0006]
A good demodulated signal can be obtained by adding and combining a plurality of received signals obtained in this way with a predetermined weight in the combining unit. The method of receiving in this manner is called RAKE reception, which is equivalent to path diversity reception because signals received from a plurality of paths can be selectively despread and combined.
[0007]
At present, in a CDMA communication system in which standardization activities are being promoted in the 3GPP (3rd Generation Partnership Project), a channel called a common pilot channel (CPICH) exists. This is a channel that constantly transmits a signal (pilot signal) of known information. By using this channel, the mobile station performs channel estimation even on a communication channel that does not include pilot symbols, and performs synchronous detection. It is possible to do.
[0008]
One of the physical channels is a channel called DPCH (Dedicated Physical CHannel). In this channel, three types of transmission diversity methods are defined: STTD (Space Time Transmit Diversity), CL1 (Closed Loop mode 1), and CL2 (Closed Loop mode 2). CL1 is a method of controlling the transmission carrier phase of the DPCH of the transmission antenna 2 with the resolution of the carrier phase of π / 4 such that the reception signal from the transmission antenna 2 becomes almost the same phase in the reception at the mobile station. , Π / 4 carrier phase resolution, the transmission carrier phase of the DPCH of the transmission antenna 2 is controlled, and the transmission power ratio of the transmission signal of the transmission signal from the transmission antenna 2 is selected and controlled from two patterns. is there.
[0009]
When the transmission diversity method is CL1, when receiving the DPCH, the mobile station estimates the amount of phase rotation performed on the DPCH signal on the transmission antenna 2 side by the base station, that is, the mobile station. Then, by adding the above estimated phase rotation amount to the phase estimation value calculated based on the CPICH having a good SNR due to high transmission power and using it for synchronous detection of the DPCH, the reception performance is improved. An example of this antenna verification method is described in 3GPP (see Non-Patent Document 1).
[0010]
[Non-patent document 1]
3GPP TS 25.214: "Physical layer procedures (FDD)" Annex A
[0011]
[Problems to be solved by the invention]
However, the conventional apparatus has a problem that when the number of pilot symbols of the DPCCH is one, antenna verification cannot be performed. That is, when the number of pilot symbols of the DPCCH is one, the pilot patterns of the transmitting antenna 1 and the transmitting antenna 2 are not orthogonal in principle, and the conventional apparatus uses the phase estimation value of the transmitting antenna 2 to perform antenna verification. If the pilot pattern of the DPCCH (channel for control information of the DPCH) is orthogonal between the transmitting antenna 1 and the transmitting antenna 2 and the mobile station cannot separately calculate the phase estimation value from each antenna, the antenna verification is performed. Unable to perform verification. In such a case, if RAKE combining is performed using a phase estimation value for which antenna verification is not performed, the reception characteristics may be significantly deteriorated.
[0012]
The present invention has been made in view of the above point, and even when the number of pilot symbols of the DPCCH is one, it is possible to perform antenna verification and improve a reception performance and a radio reception apparatus. An object is to provide an antenna verification method used in an apparatus.
[0013]
[Means for Solving the Problems]
A radio receiving apparatus according to the present invention includes a first DPCH transmitted from a first antenna of a radio transmitting apparatus, and a second DPCH transmitted from a second antenna of the radio transmitting apparatus, wherein a pilot signal of the first DPCH and π / A radio receiver for receiving a second DPCH obtained by further performing a predetermined amount of phase rotation on a DPCH having a pilot signal having a phase difference relationship of 2 and a CPICH transmitted from the radio transmitter, wherein the first DPCH And / or a phase estimation value calculating means for calculating a phase estimation value of the phase variation received by the second DPCH in the propagation path, and a pseudo phase estimation value of the phase variation received by the second DPCH in the propagation path in the order of π / 2. A pseudo phase estimated value calculating means for calculating from the CPICH using a phase difference relationship, and a phase calculated by the phase estimated value calculating means. Comparing means for comparing the estimated value with the quasi-phase estimated value calculated by the quasi-phase estimated value calculating means; and estimating a predetermined amount of phase rotation performed by the radio transmitting apparatus based on a comparison result of the comparing means. And a phase rotation estimating means.
[0014]
In the wireless receiving device according to the present invention, in the above-described configuration, the pseudo phase estimation value calculating means may include a candidate for a predetermined amount of phase rotation performed by the wireless transmitting device, in addition to the relationship of the phase difference of π / 2. Is used to calculate the pseudo phase estimation value.
[0015]
In the wireless receiving apparatus according to the present invention, in the above-described configuration, the comparing unit includes an inner product of the phase estimated value calculated by the phase estimated value calculating unit and the pseudo phase estimated value calculated by the pseudo phase estimated value calculating unit. , And the phase rotation estimating means detects the maximum value of the inner product calculated by the comparing means.
[0016]
According to these configurations, even when the number of pilot symbols of the DPCCH is 1, antenna verification can be performed, and the reception performance of the wireless reception device can be improved.
[0017]
In the wireless receiving device according to the present invention, in the above-described configuration, the quasi-phase estimated value calculating unit normalizes the quasi-phase estimated value such that the magnitude of the calculated quasi-phase estimated value becomes 1. A configuration further including means is adopted.
[0018]
According to this configuration, by performing normalization with the magnitude of the quasi-phase estimated value being 1, erroneous determination can be eliminated in determining the maximum value of the inner product value, and the reception performance of the wireless receiver can be improved. it can.
[0019]
In the radio receiving apparatus according to the present invention, in the above-described configuration, the comparing unit may include a phase estimation value calculated by the phase estimation value calculation unit and a position of the pseudo phase estimation value calculated by the pseudo phase estimation value calculation unit. The phase difference is calculated, and the phase rotation estimating means detects the minimum value of the phase difference calculated by the comparing means.
[0020]
According to this configuration, it is possible to reduce an estimation error when estimating the phase rotation performed by the wireless transmission device, and to improve the reception performance of the wireless reception device.
[0021]
In the radio receiving apparatus according to the present invention, in the above configuration, the phase estimation value calculated by the phase estimation value calculation means is a phase estimation value of a phase variation received by the first DPCH and the second DPCH in each propagation path. A configuration that is a composite value is adopted.
[0022]
According to this configuration, even when the number of pilot symbols of the DPCCH is 1, antenna verification can be performed, and the reception performance of the wireless reception device can be improved.
[0023]
A communication terminal device according to the present invention employs a configuration including any one of the wireless receiving devices described above.
[0024]
According to this configuration, it is possible to provide a communication terminal device having the same functions and effects as described above.
[0025]
An antenna verification method according to the present invention is characterized in that a first DPCH transmitted from a first antenna of a wireless transmission device, and a second DPCH transmitted from a second antenna of the wireless transmission device and a pilot signal of the first DPCH. An antenna used in a radio receiving apparatus for receiving a second DPCH obtained by further performing a predetermined amount of phase rotation on a DPCH having a pilot signal having a phase difference of π / 2 and a CPICH transmitted from the radio transmitting apparatus A verification method, comprising: a phase estimation value calculating step of calculating a phase estimation value of a phase variation received by the first DPCH and / or the second DPCH on a propagation path; A pseudo phase estimation value is calculated from the CPICH using the relationship of the phase difference of π / 2. A quasi phase estimation value calculation step, a comparison step of comparing the phase estimation value calculated by the phase estimation value calculation step with the quasi phase estimation value calculated by the quasi phase estimation value calculation step, and a comparison of the comparison step A phase rotation estimating step of estimating a predetermined amount of phase rotation performed by the wireless transmission device based on the result.
[0026]
According to this method, even when the number of pilot symbols of the DPCCH is 1, antenna verification can be performed, and the reception performance of the wireless reception device can be improved.
[0027]
BEST MODE FOR CARRYING OUT THE INVENTION
The gist of the present invention is that, when receiving a radio signal transmitted by diversity using two transmission antennas, even if the number of symbols of the pilot pattern included in the DPCCH signal transmitted from each transmission antenna is one, Utilizing the relationship that the original phase difference of the pilot pattern is π / 2, calculating a pseudo phase estimation value of the DPCCH signal from the received CPICH signal, and comparing this with the phase estimation value of the received DPCCH signal Thus, antenna verification of a DPCCH signal is enabled.
[0028]
Hereinafter, embodiments of the present invention will be described in detail with reference to the drawings.
[0029]
(Embodiment 1)
FIG. 1 is a block diagram showing a configuration of the radio receiving apparatus according to Embodiment 1 of the present invention. Here, a case will be described as an example where the radio receiving apparatus is a mobile station apparatus that receives a radio signal transmitted from a base station apparatus.
[0030]
The radio reception apparatus shown in FIG. 1 includes a radio reception section 100, an A / D converter 101, a despreading section 102 for CPICH and DPCH, a phase estimation section 103, an antenna verification section 104, a phase estimation value calculation section 105, It has a synchronous detector 106, a RAKE combiner 107, and a channel decoder.
[0031]
Wireless receiving section 100 performs predetermined wireless receiving processing such as down-conversion on the wireless signal received via the receiving antenna, and outputs the result to A / D converter 101. A / D converter 101 converts an analog signal received via wireless receiving section 100 into a digital signal, and outputs the digital signal to despreading sections 102-1 to 102-10.
[0032]
Despreading sections 102-1 to 102-10 despread the received signal using spreading codes for the respective channels, and output the resulting signals to phase estimating sections 103-1 to 103-10. Of the despreading units 102-1 to 102-10, those with odd numbers at the end of the codes are for CPICH, and those with even numbers are for DPCH. The despreading unit for DPCH also outputs the despread received signal to synchronous detection unit 106.
[0033]
Phase estimating sections 103-1 to 103-10 average the symbols of the received signals output from despreading sections 102-1 to 102-10 in one or more symbol intervals, and obtain phase estimation values of DPCH and CPICH, respectively. , To the antenna verification sections 104-1 to 104-5 and the phase estimation value calculation sections 105-1 to 105-5.
[0034]
Antenna verification sections 104-1 to 104-5 perform later-described antenna verification based on the DPCH and CPICH phase estimation values output from phase estimation sections 103-1 to 103-10, and transmit the base station apparatus. The phase rotation angle multiplied by the DPCH signal transmitted from the antenna 2 is estimated and output to the phase estimation value calculation units 105-1 to 105-5.
[0035]
The phase estimation value calculation units 105-1 to 105-5 rotate the CPICH phase estimation value of the transmission antenna 2 by the phase rotation angle estimated by the antenna verification units 104-1 to 104-5. Processing is performed, and a phase estimation value for DPCH synchronous detection is calculated and output to the synchronous detectors 106-1 to 106-5.
[0036]
Synchronous detectors 106-1 to 106-5 perform synchronous detection on the despread signal of the DPCH using the phase estimation values output from phase estimation value calculators 105-1 to 105-5, and rake combiner 107 Output to RAKE combining section 107 RAKE combines the outputs of the weighted signals output from the respective fingers (synchronous detection sections 106-1 to 106-5) and outputs the result to channel decoder 108. Channel decoder 108 performs processing such as error correction on the demodulated data output from RAKE combining section 107 to obtain final received data.
[0037]
FIG. 2 is a block diagram showing an internal configuration of the antenna verification unit 104.
[0038]
Rotating section 110 rotates ± π / 2 with respect to the CPICH phase estimation value (CPICH-Ant # 2 phase estimation value) transmitted from transmitting antenna 2 of the base station apparatus according to slot number m. Next, a phase estimation value obtained by performing a rotation の described later, which is a candidate for the phase rotation used by the base station apparatus, is calculated and output to the adding section 111.
[0039]
Addition section 111 includes a phase estimation value of CPICH (CPICH-Ant # 1 phase estimation value) transmitted from transmitting antenna 1 of the base station apparatus and a phase estimation value after phase rotation output from rotating section 110 (base station apparatus). (Transmitted from the transmitting antenna 2) to the inner product calculation unit 112.
[0040]
The inner product calculation section 112 calculates the phase estimation value (DPCCH pilot-Ant # 1 phase estimation value) as a result of performing the phase estimation in the phase estimation section 103 using the DPCCH pilot signal of the transmission antenna 1 and the addition section 111 Is calculated and output to the maximum value detection unit 113. Maximum value detection section 113 detects the maximum value of the calculated inner product values, and outputs ψ corresponding to this maximum value as the phase rotation estimation amount used in the base station apparatus.
[0041]
FIG. 3 is a flowchart showing an example of the procedure of the antenna verification method according to the present embodiment. Here, the antenna verification section 104-1 will be described as an example.
[0042]
Phase estimating section 103-1 acquires a CPICH-Ant # 2 phase estimation value (ST1010). Rotating section 110 performs rotation of ± π / 2 with respect to the CPICH-Ant # 2 phase estimation value (ST1020), and performs phase estimation described below, which is a candidate for phase rotation used by the base station apparatus. A value is calculated (ST1030).
[0043]
Further, phase estimating section 103-1 acquires a CPICH-Ant # 1 phase estimation value (ST1040). Adding section 111 performs vector addition on the CPICH-Ant # 1 phase estimated value and the phase estimated value after the phase rotation output from rotating section 110 (ST1050).
[0044]
On the other hand, phase estimating section 103-2 acquires a DPCCH pilot-Ant # 1 phase estimation value (ST1060).
[0045]
Then, inner product calculating section 112 calculates the inner product of the DPCCH pilot-Ant # 1 phase estimated value and the phase estimated value output from adding section 111 (ST1070). Maximum value detection section 113 detects the maximum value from the calculated inner product values (ST1080), and outputs ψ corresponding to the maximum value as the phase rotation estimation amount used by the base station apparatus (ST1090).
[0046]
Next, the principle of the antenna verification method according to the present embodiment will be described below.
[0047]
When the transmission diversity method adopts CL1 and the number of pilot symbols is one, the pilots of the transmitting antenna 1 and the transmitting antenna 2 of the base station apparatus are not orthogonal to each other, and thus the receiving side receives The phase estimation value corresponding to each of the transmitting antenna 1 and the transmitting antenna 2 cannot be separately calculated from the pilot signal of the DPCCH. In this case, only the combined phase estimation value obtained by combining the phase estimation values of both antennas can be estimated. However, as described in 3GPP TS 25.211, the pilot pattern of the DPCCH has the same value for either the I component or the Q component between the transmission antenna 1 and the transmission antenna 2, and therefore, the pilot symbol of the antenna 1 and the antenna 2 Are always in a relation of a rotation difference of ± π / 2. By utilizing this, the combined phase estimation value of the transmitting antenna 1 and the transmitting antenna 2 can be obtained as follows.
[0048]
First, the DPCCH despread signal d_corr-DPIs
(Equation 1)

It is expressed as Here, m is the slot number, α₁And α_TwoIs the channel coefficient of each path from the transmitting antennas 1 and 2 to the receiving side, A_dpcchPilot1, A_dpcchPilot2Indicates pilot symbols of the transmitting antennas 1 and 2 of the DPCCH pilot. Also, φ (m) means a rotation angle rotated by the base station with respect to the DPCH signal of the transmission antenna 2, and specifically, any one of π / 4, 3 / 4π, 5 / 4π, and 7 / 4π It is. Also, β_DPCCHMeans the amplitude of the DPCCH transmission signal.
[0049]
As described above, assuming that the transmission symbol of transmission antenna 2 is the transmission symbol of transmission antenna 1 multiplied by the complex weight of phase rotation,
(Equation 2)

become that way. Here, e ±^jπ^{/ 2}Is a value uniquely determined by the slot number, and is hereinafter referred to as λ (m). By substituting (Equation 2) into (Equation 1),
(Equation 3)

Becomes Therefore, the DPCCH phase estimate is
(Equation 4)

It is expressed as Where A^* _dpcchPilot1Is A_dpcchPilot1Is the complex conjugate of
[0050]
Rotating section 110 rotates λ (m) = ± π / 2 with respect to the CPICH phase estimation value transmitted from transmitting antenna 2 of the base station apparatus according to slot number m. Next, as candidates for φ (m), ψ_n= 1 / 4π, 3 / 4π, 5 / 4π, and 7 / 4π (where n = 1, 2, 3, 4) are calculated as phase estimation values, and output to the addition unit 111.
[0051]
The adding section 111 outputs the phase estimated value of the CPICH transmitted from the transmitting antenna 1 of the base station apparatus output from the phase estimating section 103-1 and the phase estimated value after the phase rotation output from the rotating section 110 (base station). And transmitted from the transmitting antenna 2 of the station device).
(Equation 5)

Is calculated and output to the inner product calculation unit 112. However, ξ_CP1(m) 、 ξ_CP2(m) is a CPICH phase estimation value of each of the transmission antennas 1 and 2.
[0052]
The inner product calculation unit 112 calculates the ψ_DP(m) and ξ_CPThe inner product of (m, n) is calculated and output to the maximum value detection unit 113.
[0053]
As described above, according to the present embodiment, even when the number of pilot symbols of the DPCCH is 1, antenna verification can be performed, and the reception performance of the wireless reception device can be improved.
[0054]
Here, the case has been described as an example where the number of RAKE-combined fingers is ten, but the number of RAKE-combined fingers is not limited to this.
[0055]
Also, here, the case where the pilot symbol of the transmitting antenna 2 is regarded as a rotation of the pilot symbol of the transmitting antenna 1 has been described as an example. You may calculate by thinking.
[0056]
(Embodiment 2)
Since the radio receiving apparatus according to the second embodiment of the present invention has the same configuration as the radio receiving apparatus shown in FIG. 1, only the configuration of antenna verification section 104a different from that of the first embodiment is shown in FIG. . Note that the same components as those of the antenna verification unit 104 shown in FIG. 2 are denoted by the same reference numerals, and description thereof will be omitted.
[0057]
A feature of the present embodiment is that a normalization unit 201 is further provided.
[0058]
In FIG. 4, normalization section 201 normalizes in addition section 111 such that the magnitude of the vector shown in (Equation 5) obtained by vector addition of the phase estimation values of CPICH antennas 1 and 2 becomes 1. Do. That is,
(Equation 6)

Is calculated. Where ξ_CP(m, n) changes in magnitude depending on the directions of the vectors of the antennas 1 and 2 of the CPICH phase estimation value._DP(m) and ξ_CPThe inner product of (m, n) is ξ_CPIt changes according to the magnitude of (m, n). Therefore, ξ_CPWhen the influence of the size of (m, n) itself is large, erroneous determination may occur in determining the maximum value of the inner product value._CPSuch erroneous determination can be eliminated by normalizing the magnitude of (m, n) to 1.
[0059]
As described above, according to the present embodiment,_CPBy performing the normalization with the magnitude of (m, n) as 1, it is possible to eliminate erroneous determination in determining the maximum value of the inner product value, and improve the reception performance of the wireless receiver.
[0060]
(Embodiment 3)
Since the radio receiving apparatus according to Embodiment 3 of the present invention has the same configuration as the radio receiving apparatus shown in FIG. 1, only the configuration of antenna verification section 104b different from that of Embodiment 1 is shown in FIG. . Note that the same components as those of the antenna verification unit 104 shown in FIG. 2 are denoted by the same reference numerals, and description thereof will be omitted.
[0061]
A feature of the present embodiment is that it has a phase difference calculation unit 301 and a minimum value detection unit 302.
[0062]
In FIG. 5, phase difference calculation section 301 adds vector obtained by adding vectors of the phase estimation values of antennas 1 and 2 of CPICH in addition section 111 and the phase of DPCCH shown in (Equation 4). The phase difference between the estimated value and the vector is calculated. The minimum value detection unit 302 detects a phase difference having the smallest phase difference from the phase difference between the CPICH phase estimation value and the DPCCH phase estimation value in each ψ, and outputs the result as the phase rotation estimation amount in the base station. .
[0063]
For example, in the first embodiment,_CP(m, n) changes in magnitude depending on the directions of the vectors of the antennas 1 and 2 of the CPICH phase estimation value._DP(m) and ξ_CPThe inner product of (m, n) is ξ_CPIt changes according to the magnitude of (m, n). Therefore, ξ_CPIf the influence of the magnitude of (m, n) itself is large, an erroneous determination may occur in the determination of the maximum value of the inner product value. However, by performing the estimation of ψ from the minimum value of the phase difference as described above, Judgment can be eliminated.
[0064]
As described above, according to the present embodiment, erroneous determination can be eliminated in estimating ψ, and the receiving performance of the wireless receiving apparatus can be improved.
[0065]
(Embodiment 4)
Since the radio receiving apparatus according to Embodiment 4 of the present invention has the same configuration as the radio receiving apparatus shown in FIG. 1, only the configuration of antenna verification section 104c different from that of Embodiment 1 is shown in FIG. . Note that the same components as those of the antenna verification unit 104 shown in FIG. 2 are denoted by the same reference numerals, and description thereof will be omitted.
[0066]
A feature of the present embodiment is that the phase is estimated using the pilot patterns of the transmission antennas 1 and 2 and the phase estimation values obtained by performing the phase estimation using the patterns of the transmission antennas 1 and 2 are combined. This is similar to the case where the number of pilot symbols is two or more. In Embodiments 1, 2, and 3, phase estimation is performed using only the pilot pattern of antenna 1.
[0067]
Phase estimating section 103 estimates the phase based on the DPCCH pilot pattern of each of transmission antennas 1 and 2 and outputs the result to addition section 401 in antenna verification section 104, as in the case where the number of pilot symbols is two or more. The adder 401 combines the phase estimation values obtained by performing the phase estimation with the patterns of the antennas 1 and 2 respectively. In this case, the phase estimation value obtained from the pattern of the antenna 1 is
(Equation 7)

And the phase estimate obtained from the pattern of the antenna 2 is
(Equation 8)

Becomes Therefore, when these are synthesized,
(Equation 9)

It is expressed as
[0068]
On the other hand, combining section 402 uses the phase estimated value of transmitting antenna 1 of CPICH and the vector obtained by rotating phase estimated value of transmitting antenna 2 by ψ in rotating section 110 based on the vector.
(Equation 10)

Is calculated.
[0069]
The inner product calculation unit 112 calculates four types of ψ_DP(m) and ξ "_CPThe inner product of (m, n) is calculated, and the maximum value detection unit 113 detects the maximum value of each inner product value, and outputs the result as the estimated phase rotation amount in the base station.
[0070]
As described above, according to the present embodiment, it is possible to obtain the same operation and effect as in the first embodiment.
[0071]
Note that, as in the second embodiment, ξ ″_CP(m, n) may be normalized. Also, as in the third embodiment,_DP1(m) + ξ_DP2(m) and ξ "_CPIt may be estimated from the phase difference of (m, n).
[0072]
【The invention's effect】
As described above, according to the present invention, antenna verification can be performed even when pilot patterns are not orthogonal between transmitting antennas 1 and 2, such as when the number of pilot symbols of the DPCCH is one. As a result, the reception performance of the wireless reception device can be improved.
[0073]
Further, according to the present invention, by normalizing the magnitude of the addition vector of the CPICH phase estimation value, it is possible to prevent an erroneous determination caused by the magnitude of the CPICH phase estimation value itself.
[0074]
Further, according to the present invention, by estimating the rotation angle from the minimum value of the phase difference between the DPCH phase estimation value and the CPICH phase estimation value, it is possible to prevent erroneous determination that occurs from the magnitude of the CPICH phase estimation value itself. .
[Brief description of the drawings]
FIG. 1 is a block diagram showing a configuration of a wireless receiving apparatus according to Embodiment 1 of the present invention.
FIG. 2 is a block diagram showing an internal configuration of an antenna verification unit according to the first embodiment of the present invention.
FIG. 3 is a flowchart showing an example of a procedure of an antenna verification method according to the first embodiment of the present invention.
FIG. 4 is a block diagram showing an internal configuration of an antenna verification unit according to Embodiment 2 of the present invention.
FIG. 5 is a block diagram showing an internal configuration of an antenna verification unit according to Embodiment 3 of the present invention.
FIG. 6 is a block diagram showing an internal configuration of an antenna verification unit according to Embodiment 4 of the present invention.
[Explanation of symbols]
100 wireless receiver
101 A / D converter
102 despreading unit
103 Phase estimation unit
104 Antenna Verification Unit
105 Phase estimation value calculation unit
106 Synchronous detector
107 RAKE synthesis unit
108 channel decoder
110 Rotating part
111, 401 Adder
112 Inner product calculator
113 Maximum value detector
201 Normalization unit
301 Phase difference calculator
302 Minimum value detection unit
402 synthesis unit

Claims (8)

A first DPCH transmitted from a first antenna of a wireless transmission device and a second DPCH transmitted from a second antenna of the wireless transmission device, the pilot signal having a phase difference of π / 2 with a pilot signal of the first DPCH; A wireless receiving apparatus that receives a second DPCH obtained by further performing a predetermined amount of phase rotation on a DPCH having a signal and a CPICH transmitted from the wireless transmitting apparatus,
Phase estimation value calculating means for calculating a phase estimation value of a phase variation received by the first DPCH and / or the second DPCH in a propagation path;
Quasi-phase estimation value calculating means for calculating a quasi-phase estimation value of the phase variation received by the second DPCH in the propagation path from the CPICH using the relationship of the phase difference of π / 2;
Comparison means for comparing the phase estimation value calculated by the phase estimation value calculation means and the pseudo phase estimation value calculated by the pseudo phase estimation value calculation means,
Phase rotation estimation means for estimating a predetermined amount of phase rotation performed by the wireless transmission device based on a comparison result of the comparison means,
A wireless receiving device comprising: The pseudo phase estimation value calculation means,
Calculating the pseudo phase estimation value using a predetermined amount of phase rotation candidates performed by the wireless transmission device, in addition to the relationship of the phase difference of π / 2,
The wireless receiving device according to claim 1, wherein: The comparing means includes:
Calculating the inner product of the phase estimation value calculated by the phase estimation value calculation means and the pseudo phase estimation value calculated by the pseudo phase estimation value calculation means,
The phase rotation estimating means includes:
Detecting the maximum value of the inner product calculated by the comparing means,
The wireless receiving device according to claim 1, wherein: The pseudo phase estimation value calculation means,
4. The radio receiving apparatus according to claim 3, further comprising a normalizing means for normalizing the pseudo phase estimation value so that the calculated pseudo phase estimation value becomes 1. The comparing means includes:
Calculating a phase difference between the phase estimation value calculated by the phase estimation value calculation means and the pseudo phase estimation value calculated by the pseudo phase estimation value calculation means,
The phase rotation estimating means includes:
Detecting the minimum value of the phase difference calculated by the comparing means,
The wireless receiving device according to claim 1, wherein: The phase estimation value calculated by the phase estimation value calculation means is a composite value of the phase estimation values of the phase fluctuations received by the first DPCH and the second DPCH in respective propagation paths.
The wireless receiving device according to claim 1, wherein: A communication terminal device comprising the wireless receiving device according to claim 1. A first DPCH transmitted from a first antenna of the wireless transmission device, and a second DPCH transmitted from a second antenna of the wireless transmission device, the pilot having a phase difference of π / 2 with a pilot signal of the first DPCH. An antenna verification method used in a wireless receiving device that receives a second DPCH obtained by further performing a predetermined amount of phase rotation on a DPCH having a signal and a CPICH transmitted from the wireless transmitting device,
A phase estimation value calculating step of calculating a phase estimation value of a phase variation received by the first DPCH and / or the second DPCH in a propagation path;
A quasi-phase estimation value calculating step of calculating a quasi-phase estimation value of a phase variation received by the second DPCH in a propagation path from the CPICH using the relationship of the π / 2 phase difference;
A comparison step of comparing the phase estimation value calculated by the phase estimation value calculation step with the pseudo phase estimation value calculated by the pseudo phase estimation value calculation step;
A phase rotation estimating step of estimating a predetermined amount of phase rotation performed by the wireless transmission device based on a comparison result of the comparing step;
An antenna verification method comprising:

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