JP2004096853A - Noncontact power unit - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To provide a noncontact power unit which possesses a protective function of blocking overvoltage, for surely deterring overvoltage from occurring by the counter electromotive force, when an inductive load is connected to the secondary side. <P>SOLUTION: In the noncontact power unit 1, which supplies power in noncontact by electromagnetic inductive action from a primary unit to a secondary unit, the primary unit is equipped with a first rectifying and smoothing circuit 2 which rectifies and smoothes the output voltage of a commercial power source and a drive circuit 3, which chopper-controls the output voltage of the first rectifying and smoothing circuit 2 and applies a harmonic AC to the primary winding of a coupling transformer 4, with the secondary unit possesses a second rectifying and smoothing circuit 5, which rectifies and smoothes an induced current flowing to the secondary winding of the coupling transformer 4 prior to output; an inverter circuit, which is connected in series to the output side of the second rectifying and smoothing circuit 5; an operation circuit 7 which outputs AC voltage from the inverter circuit 6; and a resistor R3 which consumes a regenerative current, flowing to the inverter circuit 6, in the vicinity of zero cross of the output voltage of the inverter circuit 6. <P>COPYRIGHT: (C)2004,JPO

Description

[0001]
TECHNICAL FIELD OF THE INVENTION
The present invention particularly relates to a contactless power supply device having an overvoltage protection function capable of reliably preventing an overvoltage from being generated by a back electromotive force when an inductive load is connected to the secondary side.
[0002]
[Prior art]
Conventionally, a primary side unit including a primary side of a coupling transformer and a secondary side unit including a secondary side of the coupling transformer are configured to be separable, and an inverter is connected to a secondary side output of the coupling transformer. A so-called non-contact power supply device is well known. The non-contact power supply device inserts a power supply cord connected to the primary unit into a fixed power supply such as an indoor outlet, and the secondary unit connects the primary unit with an intervening object such as a window glass or a door. It is placed outdoors by being placed facing the side unit.
[0003]
Then, electric power is supplied from the primary unit to the secondary unit in a non-contact and non-contact manner using an electromagnetic induction action, and a load such as a motor or an electric decoration connected to the secondary unit disposed outdoors. Is driven. That is, according to such a non-contact power supply device, a commercial power supply installed indoors can be easily and reliably used outdoors in a state where indoors and outdoors are closed without opening a window glass or a door. is there.
[0004]
[Problems to be solved by the invention]
However, when the load connected to the secondary unit is an inductive load, a back electromotive force is generated near the zero crossing of the AC output of the inverter, and the regenerative current is supplied to the DC input of the inverter. As a result, there has been a problem that the DC voltage rises abnormally and causes a circuit failure.
[0005]
Therefore, in order to solve the above-described problem, the present invention has an object to provide a non-contact power supply device that includes a resistor that consumes the regenerative current in the vicinity of a zero cross of an AC output of an inverter and that reliably prevents an overvoltage from occurring. And
[0006]
[Means for Solving the Problems]
In order to achieve this object, a non-contact power supply device according to claim 1 is configured such that a primary unit accommodating a primary winding and a secondary unit accommodating a secondary winding can be separated. A coupling transformer is formed from the primary winding and the secondary winding by approaching the unit, and power is supplied from the primary unit to the secondary unit in a non-contact and non-contact manner by electromagnetic coupling of the coupling transformer. A primary rectifying / smoothing circuit for rectifying and smoothing an output voltage of a commercial power supply, and a chopper control of an output voltage of the first rectifying / smoothing circuit. A driving circuit for applying a high-frequency alternating current to a primary winding of the coupling transformer, wherein the secondary unit rectifies and smoothes an induced voltage flowing in the secondary winding and outputs the rectified and smoothed voltage. A rectifying / smoothing circuit and the second rectifying / smoothing circuit; And an inverter circuit configured by connecting two sets of two switching elements connected in series to the output side of the inverter in parallel, and alternately turning on or off the two sets of switching elements to output an AC voltage from the inverter circuit. And a resistor that consumes a regenerative current flowing through the inverter circuit near the zero crossing of the output voltage of the inverter circuit.
[0007]
According to the first aspect of the present invention, the regenerative current flowing through the DC input of the inverter circuit when an inductive load is connected to the output of the secondary unit is consumed near the zero cross of the AC output of the inverter circuit. Therefore, abnormal increase of the DC input voltage of the inverter circuit can be completely prevented.
[0008]
3. The non-contact power supply device according to claim 2, wherein the primary unit accommodating the primary winding and the secondary unit accommodating the secondary winding are separable, and the primary unit is brought close by both units. A non-contact power supply device that forms a coupling transformer from a side winding and a secondary winding and supplies electric power from the primary unit to the secondary unit in a non-contact and non-contact manner by electromagnetic coupling of the coupling transformer. The primary unit includes a first rectifying / smoothing circuit for rectifying / smoothing an output voltage of a commercial power supply, and a chopper control of an output voltage of the first rectifying / smoothing circuit to couple the high-frequency alternating current to the coupling. A driving circuit for applying a voltage to the primary winding of the transformer; the secondary unit rectifying an induced voltage flowing through the secondary winding; and removing a high-frequency component from an output voltage of the rectifying circuit. Low pass filter and before A zero-cross detection circuit that outputs a zero-cross signal at a timing when the output voltage of the low-pass filter becomes zero volts, and an inverter configured by connecting two sets of two switching elements connected in series to the output side of the low-pass filter in parallel An operation circuit that alternately turns on or off two sets of switching elements constituting the inverter circuit in response to the zero-cross signal, and outputs an alternating voltage having the same frequency as a commercial power supply from the inverter circuit; A resistor is provided which consumes a regenerative current flowing through the inverter circuit near the zero crossing of the output voltage of the inverter circuit.
[0009]
According to the non-contact power supply device of the second aspect, when an inductive load is connected to the output of the secondary unit, the regenerative current flowing to the DC input of the inverter circuit is reliably consumed, and the occurrence of overvoltage is completely prevented. The inverter circuit can output an AC voltage having the same frequency and waveform as the commercial power supply connected to the primary unit and can be used for various general home appliances driven by the commercial power supply. Becomes possible.
[0010]
According to a third aspect of the present invention, in the non-contact power source apparatus according to the first or second aspect, the secondary unit has a primary-side current frequency of a coupling transformer equal to a secondary-side resonance frequency. A resonance circuit that adjusts the number of turns of the secondary winding and the capacitance of the capacitor so that the oscillation frequency of the primary unit deviates from the resonance frequency of the secondary unit. A means was provided.
[0011]
According to the third aspect of the present invention, since the oscillation frequency of the primary unit can be changed by operating the first switch, for example, the distance between the primary unit and the secondary unit When there is a danger that an excessive voltage is supplied to the secondary unit, the first switch means is operated to deviate the oscillation frequency of the primary unit from the resonance frequency of the secondary unit. Thus, it is possible to appropriately adjust such that an appropriate voltage is supplied to the secondary side.
[0012]
According to a fourth aspect of the present invention, in the non-contact power supply device according to any one of the first to third aspects, the operation circuit is configured such that when the zero-cross signal is output two or more within a predetermined time from the zero-cross detection circuit, the operation circuit performs the second operation. A double pulse prevention circuit for reliably absorbing the subsequent zero-cross signal in the operation circuit is provided.
[0013]
According to the fourth aspect of the present invention, even if two or more zero-cross signals are output from the zero-cross detection circuit within a predetermined time, the double-pulse prevention circuit operates the second and subsequent zero-cross signals. The input to the switching element of the inverter circuit is prevented even if the output of the zero-cross signal is output twice or more due to the influence of disturbance of the voltage waveform, noise, or the like. ON or OFF timing can be maintained normally, and a stable output of the alternating voltage can be maintained.
[0014]
According to a fifth aspect of the present invention, there is provided the non-contact power supply device according to any one of the first to fourth aspects, wherein the primary unit includes a second switch for switching between driving and stopping the primary unit. The secondary unit is provided with a receiving groove for receiving the second switch when the secondary unit is in contact with the primary unit without being turned on.
[0015]
According to the non-contact power supply device of claim 5, when the primary unit and the secondary unit are in direct contact with each other without any intervening object, the second switch is not turned on and the second unit is not turned on. Even if the primary unit and the secondary unit are in direct contact with each other, the primary unit is driven and an overvoltage occurs in the secondary unit because the secondary unit is completely accommodated in the accommodation groove formed in the secondary unit. This can reliably eliminate the occurrence of such a problem that the user does
[0016]
The non-contact power supply device according to claim 6 is the non-contact power supply device according to claim 1, wherein the secondary unit includes a permanent magnet, and the primary unit is connected to the secondary unit. A third switch is provided for switching on / off of the primary unit by performing on / off operation depending on presence / absence of magnetic sensing of the provided permanent magnet.
[0017]
According to the non-contact power supply device of the sixth aspect, the primary unit is driven only when the magnetism of the permanent magnet attached to the secondary unit is detected by the third switch means attached to the primary unit. As long as the primary unit and the secondary unit are not arranged facing each other, the primary unit is not driven simply by connecting the primary unit to the commercial power supply, and power is wasted unnecessarily. Can be reliably prevented from being performed.
[0018]
BEST MODE FOR CARRYING OUT THE INVENTION
Hereinafter, preferred embodiments of the present invention will be described with reference to the accompanying drawings. FIG. 1 is a circuit diagram showing a non-contact power supply device 1 of the present invention. The non-contact power supply device 1 includes a first rectifying / smoothing circuit 2, a driving circuit 3, a coupling transformer 4, and a second rectifying / smoothing circuit 5. It is roughly composed of an inverter circuit 6 and an operation circuit 7.
[0019]
The first rectifying / smoothing circuit 2 is a circuit that rectifies and smoothes an AC voltage supplied from a commercial power supply (not shown) via a power outlet 11 to DC and outputs the DC voltage. The first rectifying / smoothing circuit 2 includes a diode bridge DB1 and a smoothing capacitor C1. It is configured.
[0020]
The plus terminal of the first rectifying / smoothing circuit 2 is connected to a center tap 41e provided on a primary winding 41c (see FIG. 2) constituting a main transformer TR1 of the coupling transformer 4 described later. Both ends of the primary winding 41c are connected to the drain terminals of the N-MOS switching devices Q1 and Q2 of the drive circuit 3, respectively.
[0021]
The drive circuit 3 is a circuit for supplying an alternating current to the primary winding 41c constituting the main transformer TR1 of the coupling transformer 4, and has a source terminal connected to the minus terminal of the first rectifying and smoothing circuit 2. A drive IC 33 in which output terminals Out1 and Out2 are respectively connected to devices Q1 and Q2 and gate terminals of the switching devices Q1 and Q2 via resistors R4 and R5 for limiting a drive current of the switching devices Q1 and Q2; One end is connected to the input terminal Cin of the driving IC 33, the timing generating capacitor C2, the timing generating resistors R1, R2 connected in series to the input terminal Rin of the driving IC 33, and the timing generating resistor R2 are connected in parallel. It comprises a correction switch 32.
[0022]
The other end of the timing generation capacitor C2 having one end connected to the input terminal Cin of the drive IC 33 and the other end of the timing generation resistors R1 and R2 connected in series to the input terminal Rin of the drive IC 33 are both connected to the other end. 1 is connected to the negative terminal of the rectifying / smoothing circuit 2.
[0023]
The drive IC 33 is an element for alternately turning on and off the switching devices Q1 and Q2 connected to the two output terminals Outl and Out2. For example, a switching regulator controller TL494 manufactured by Texas Instruments is used.
[0024]
The ON / OFF cycle of the switching devices Q1 and Q2 is determined by the capacitance of the capacitor C2 connected to the input terminal Cin of the drive IC 33 and the resistance value of the resistors R1 and R2 connected to the input terminal Rin. Is determined by
[0025]
Therefore, when the correction switch 32 is turned on, the resistance value connected to the input terminal Rin changes, so that the on / off cycle of the switching devices Q1 and Q2 (the oscillation frequency of the driving IC 33) naturally changes.
[0026]
The correction switch 32 is provided when an interval between the primary side and the secondary side of the coupling transformer 4 is excessively narrow, that is, an interposition 50 such as a window glass or a wall sandwiched between the primary side and the secondary side (see FIG. 3) is a switch used to prevent the output voltage on the secondary side of the coupling transformer 4 from becoming abnormally high when the thickness is small, and the switch remains on even after the operation is released. Alternatively, it is configured by a switch that holds an OFF operation state.
[0027]
The correction switch 32 is a switch that changes the oscillation frequency of the drive IC 33 in accordance with the thickness of an interposition 50 such as a window glass or a wall sandwiched between the primary side and the secondary side of the coupling transformer 4. Therefore, instead of a switch that switches between ON and OFF as described above, a variable resistor whose resistance value can be changed from 0Ω to several kiloΩ may be used.
[0028]
If the correction switch 32 is constituted by a variable resistor, the oscillation frequency of the drive IC 33 is appropriately adjusted according to the thickness of the interposition 50 such as a window glass or a wall sandwiched between the primary side and the secondary side, The power supply from the primary side to the secondary side of the coupling transformer 4 can be optimized.
[0029]
The coupling transformer 4 includes a main transformer TR1 having a primary winding 41c (see FIG. 2) and a center tap 41e (see FIG. 1), and a secondary winding 42c of the main transformer TR1 (see FIG. 2). , And a resonance capacitor C3 connected in parallel.
[0030]
The resonance capacitor C3 forms a resonance circuit together with the secondary winding 42c, and has a capacitance so that the frequency of the primary current of the coupling transformer 4 becomes equal to the resonance frequency of the secondary side. Has been adjusted. That is, the capacitance of the resonance capacitor C3 is adjusted so that the oscillation frequency of the drive IC 33 and the secondary resonance frequency when the correction switch 32 of the drive circuit 3 is off are equal. Then, by the resonance action of the resonance circuit, the secondary side impedance of the coupling transformer 4 is lowered to make the current easier to flow, and sufficient power is supplied to the secondary side.
[0031]
The second rectifying / smoothing circuit 5 is a circuit that rectifies and smoothes the AC voltage output from the coupling transformer 4 to DC and outputs the DC voltage, and includes a diode bridge DB2 and a smoothing capacitor C4.
[0032]
The inverter circuit 6 includes a bridge circuit 6a formed by connecting two sets (Q3 to Q6) of two switching elements connected in series to the output of the second rectifying / smoothing circuit 5 in parallel. The rectifying / smoothing circuit 5 includes a regenerative current absorbing circuit 6b including a resistor R3 and a switching element Q7 connected between the plus terminal and the minus terminal of the output of the rectifying / smoothing circuit 5. Incidentally, parasitic diodes D1 to D4 existing in the MOSFET are connected in anti-parallel between the drain and source of the switching elements Q3 to Q6.
[0033]
The operation circuit 7 connects the output of the square wave oscillator OSC1 to the clock terminal G of the D-type flip-flop IC1, and the data terminal D of the D-type flip-flop IC1 is connected to the plus terminal of a DC power supply (not shown). The Q output terminal of the D-type flip-flop IC1 is connected to the clock terminal G of the frequency divider IC2 and to the gate of the switching element Q7 via the resistor R7.
[0034]
A resistor R8 is connected between the gate and the source of the switching element Q7, and a Q output terminal of the D-type flip-flop IC1 is connected to a ground terminal of a DC power supply (not shown) via a series circuit of a resistor R6 and a capacitor C5. I have. The connection point between the resistor R6 and the capacitor C5 is connected to the reset terminal R of the D-type flip-flop IC1, and the Q-bar output terminal of the D-type flip-flop IC1 is connected to one input terminal of each of the AND gates IC3 and IC4. I have. The set terminal S of the D-type flip-flop IC1 is connected to a ground terminal of a DC power supply (not shown).
[0035]
The set terminal S and the reset terminal R of the frequency divider IC2 are both connected to the ground terminal of a DC power supply (not shown), and the data terminal D of the frequency divider IC2 is connected to the Q bar output terminal of the frequency divider IC2. ing. The Q output terminal of the frequency divider IC2 is connected to the other input terminal of the AND gate IC3, and the Q bar output terminal of the frequency divider IC2 is connected to the other input terminal of the AND gate IC4. .
[0036]
The output terminal of the AND gate IC3 is connected to the gate terminals of the switching elements Q4 and Q5 via respective drivers Dr4 and Dr5, and the output terminal of the AND gate IC4 is connected to the gate terminals of the switching elements Q3 and Q6. , Dr6.
[0037]
FIG. 2 is a side sectional view showing the structure of the coupling transformer 4 in the non-contact power supply device 1 configured as described above. The coupling transformer 4 has a primary iron core having a C-shaped side sectional shape, for example. 41b, a secondary core 42b, and a primary winding 41c and a secondary winding 42c wound around the primary core 41b and the secondary core 42b, respectively.
[0038]
The primary iron core 41b around which the primary winding 41c is wound and the secondary iron core 42b around which the secondary winding 42c is wound are each formed of a resin material such as plastic formed in a housing shape. In a state of being individually accommodated in the casings 41a and 42a, a pair of upper and lower end surfaces of the primary iron core 41b and the secondary iron core 42b are arranged to face each other so as not to cross each other.
[0039]
Further, cover bodies 41f, 42f made of non-magnetic metal having high conductivity are attached to the casings 41a, 42a, respectively, with the sides facing the other casings 42a, 41a open.
[0040]
Further, the primary iron core 41b and the secondary iron core 42b are formed from the primary winding 41c wound around the primary iron core 41b by sufficiently increasing the lengths of the yoke portions 41d and 42d. Power is efficiently supplied to the secondary winding 42c wound around the secondary iron core 42b by electromagnetic induction.
[0041]
That is, it is preferable that the length L of the yoke portions 41d and 42d be at least twice as long as the gap length G between the primary unit 41 and the secondary unit 42. The length of the yoke portions 41d and 42d may be set in advance, assuming the thickness of a window glass, a wall or the like interposed between the units 42.
[0042]
The shapes of the primary iron core 41b and the secondary iron core 42b are not limited to the C-shape but may be, for example, E-shapes. In this case, the primary-side iron core 41b and the secondary-side iron core 42b are opposed to each other without intersecting the end faces provided in the upper, middle, and lower three stages.
[0043]
When power is supplied by electromagnetic induction between the primary unit 41 and the secondary unit 42 configured as described above, as shown in FIG. Are arranged opposite to each other, and power is supplied to the primary unit 41 via the power outlet 11 so that the primary unit 41 is moved from the primary iron core 41d shown in FIG. The magnetic flux is linked to the secondary iron core 42d via the inclusion 50 to generate a voltage in the secondary winding 42c, so that the load 60 such as an electric device connected to the secondary unit 42 can be driven favorably. You do it.
[0044]
When magnetic flux links from the primary iron core 41d to the secondary iron core 42d, the magnetic flux induced in the primary iron core 41d is applied to the cover 41f provided in the primary unit 41 shown in FIG. From the outside through the casing 41a, but because the cover body 41f is formed of a non-conductive metal having high conductivity, when the magnetic flux passes through the cover body 41f, the cover body 41f Generates an eddy current in a direction that impedes the leakage magnetic flux.
[0045]
Due to the generation of the eddy current, a magnetic flux in the opposite direction to the leakage magnetic flux is induced in the cover 41f, so that the magnetic flux leaking outside through the cover 41f is surely reduced. As a result, the primary iron core The magnetic flux induced in 41b can be efficiently linked to the secondary core 42b, so that electric power can be satisfactorily supplied from the primary unit 41 to the secondary unit 42.
[0046]
The primary-side iron core 41d and the secondary-side iron core 42d are formed such that the distance L between the legs is at least twice the gap length G between the primary-side unit 41 and the secondary-side unit 42. Therefore, the magnetic flux induced in the primary-side core 41d reliably links to the secondary-side core 42d without straddling the legs of the primary-side core 41d, and satisfactorily supplies power to the secondary-side unit 42. can do.
[0047]
Next, the operation of various circuits (see FIG. 1) constituting the non-contact power supply device 1 will be described. First, when the power outlet 11 shown in FIG. 3 is connected to a commercial power supply (AC power supply), the AC voltage supplied from the commercial power supply is rectified and smoothed by the diode bridge DB1 of the first rectifying and smoothing circuit 2 and the smoothing capacitor C1. And output as a DC voltage.
[0048]
At the same time, a drive voltage is also supplied from a DC power supply (not shown) to the drive IC 33 of the drive circuit 3, and the output terminals Outl, Outl, at the oscillation frequency (period) of the drive IC 33 determined by the timing generation capacitor C2 and the series resistance of the resistors R1, R2. The switching devices Q1 and Q2 are alternately turned on and off from Out2 via the resistors R4 and R5.
[0049]
Since the switching devices Q1 and Q2 are alternately turned on and off, an alternating current having a frequency determined by the capacitor C2 and the resistors R1 and R2 flows through the primary winding 41c of the main transformer TR1 of the coupling transformer 4. .
[0050]
Then, when an alternating current flows through the primary winding 41c of the main transformer TR1 of the coupling transformer 4, the magnetic flux interlinks with the secondary winding 42c, thereby causing the secondary winding 42c of the main transformer TR1 to flow. Voltage is generated. At this time, the capacitance of the resonance capacitor C3 is adjusted in advance so that the frequency of the current flowing through the primary winding 41c of the coupling transformer 4 and the secondary resonance frequency are equal. The power supply from the primary side to the secondary side of the coupling transformer 4 is optimized by the resonance action of the resonance circuit composed of the secondary winding 42c.
[0051]
The voltage supplied from both ends of the resonance capacitor C3 of the coupling transformer 4 is converted again to a DC voltage by the diode bridge DB2 of the second rectifying / smoothing circuit 5 and the capacitor C4, and then output from both ends of the capacitor C4. Is done. The DC positive voltage output from the capacitor C4 is output to the inverter circuit 6 and supplied to a DC power supply (not shown) to generate a control power supply (not shown) for the inverter circuit 6.
[0052]
When a control power supply (not shown) is generated by the output of the second rectifying / smoothing circuit 5, the inverter circuit 6 starts operating. Hereinafter, the operation of the inverter circuit 6 will be described with reference to the waveform diagram of FIG.
[0053]
When power for driving is supplied from the control power supply, the rectangular wave oscillator OSC1 shown in FIG. 1 starts oscillating at a predetermined frequency and outputs a rectangular pulse (FIG. 4A). The output of the square-wave oscillator OSC1 is input to the clock terminal G of the D-type flip-flop IC1, and the data terminal D of the D-type flip-flop IC1 is connected to the plus terminal of a DC power supply (not shown). A high-level signal is output from the Q output terminal of the IC 1 (FIG. 4B).
[0054]
Then, the output is applied to the series circuit of the resistor R6 and the capacitor C4, so that the voltage at the connection point between the resistor R6 and the capacitor C5 gradually increases with a time constant determined by the resistor R6 and the capacitor C4 (FIG. 4 (d)). ). That is, the output of the Q output terminal of the D-type flip-flop IC1 is integrated by the resistor R6 and the capacitor C5.
[0055]
When the voltage at the connection point of the resistor R6 and the capacitor C5 reaches the threshold voltage of the reset terminal R of the D-type flip-flop IC1, the D-type flip-flop IC1 is reset, and the output of the Q output terminal becomes low level. As a result, a pulse having a time constant determined by the resistor R6 and the capacitor C5 is output from the Q output terminal of the D-type flip-flop IC1.
[0056]
On the other hand, the pulse output from the Q output terminal of the D-type flip-flop IC1 is input to the clock terminal G of the frequency divider IC2, and the output of the frequency divider IC2 is the output determined by the level of the data terminal D. Output from the output terminal and Q bar output terminal. Here, since the Q bar output terminal of the frequency divider IC2 is connected to the data terminal D of the frequency divider IC2, every time a pulse signal is input to the frequency divider IC2 from the Q output terminal of the D-type flip-flop IC1. In addition, the outputs of the Q output terminal and the Q bar output terminal of the frequency divider IC2 invert the high level and the low level (FIGS. 4E and 4F).
[0057]
The Q output terminal and the Q bar output terminal of the frequency divider IC2 are connected to one input terminals of AND gates IC3 and IC4, respectively, and the other input terminals of the AND gates IC3 and IC4 are collectively connected to a D-type flip-flop IC1. And the outputs of the AND gates IC3 and IC4 are equal to the output of the Q-bar output terminal of the D-type flip-flop IC1 from the outputs of the Q-output terminal and the Q-bar output terminal of the frequency divider IC2. The high level is obtained only during the subtracted time (FIGS. 4 (g) and 4 (h)).
[0058]
The outputs of the AND gates IC3 and IC4 are output to the respective drivers Dr3 to Dr6, and the switching elements Q4, Q5 or Q3, Q6 are driven by the driver drivers Dr3 to Dr6. As a result, the switching elements Q3 to Q6 are all turned off while the Q bar output terminal of the D-type flip-flop IC1 is at a low level, and are repeatedly turned on / off each time the Q bar output terminal of the D-type flip-flop IC1 is at a high level. It is.
[0059]
On the other hand, the D-type flip-flop IC1 turns on the switching element Q7 only when all the switching elements Q3 to Q6 of the inverter circuit 6 are turned off by driving the switching element Q7 via the resistor R7 connected to the Q output terminal. I do.
[0060]
Hereinafter, the operation of the resistor R3 and the switching element Q7 will be described with reference to FIG. For ease of explanation, the symbols shown in FIG. 5 are the same as those in FIG. 1, and the description of the operation circuit 7 is omitted.
[0061]
An example in which the output of the inverter circuit 6 is connected to an inductive load L1 such as a capacitor motor or a shaded motor, the switching elements Q3 and Q6 are on, and the switching elements Q4 and Q5 are off will be described as an example. At this time, since the switching elements Q3 and Q6 are on, a current flows through the inductive load L1 from left to right as shown in FIG.
[0062]
Even if all the switching elements Q3 to Q6 are turned off after a lapse of a predetermined time, the current flowing through the inductive load L1 continues to flow due to the presence of the electromagnetic energy stored in the inductive load L1. .
[0063]
Therefore, the current of the inductive load L1 flows through the path of the inductive load L1 → the parasitic diode D3 of the switching element Q5 → the capacitor C4 of the second rectifying / smoothing circuit 5 → the parasitic diode D2 of the switching element Q4 → the inductive load L1. The flow continues until the electromagnetic energy stored in the inductive load L1 is released. As a result, charge is accumulated in the capacitor C4, and the voltage across the capacitor C4 increases (FIG. 5B).
[0064]
Here, by turning on the switching element Q7 at the moment when the switching elements Q3 to Q6 are all turned off, the current of the inductive load L1 is changed to the inductive load L1 → the parasitic diode D3 of the switching element Q5 → the resistor R3 → the switching. The current flows through the path of element Q7 → parasitic diode D2 of switching element Q4 → inductive load L1, and the electromagnetic energy stored in inductive load L1 is surely consumed by resistor R3. It is possible to completely prevent the voltage from rising abnormally.
[0065]
Next, an operation in the case where the thickness of the inclusion 50 such as a window glass or a wall sandwiched between the primary unit 41 and the secondary unit 42 shown in FIG. 3 will be described. When the thickness of the interposition 50 such as a window glass or a wall sandwiched between the primary iron core 41b and the secondary iron core 42b is small, the primary winding 41c and the secondary winding 42c of the coupling transformer 4 are connected to each other. Increases, the output voltage of the secondary winding 42c abnormally increases. In this case, in order to prevent an accident such as a fire caused by the increase in the output voltage, the correction switch 32 of the drive circuit 3 is turned on to prevent the output voltage of the secondary winding 42c from excessively increasing. It must be surely suppressed.
[0066]
In operation, when the correction switch 32 shown in FIG. 1 is turned on, the resistor R2 is short-circuited, and the oscillation frequency of the driving IC 33 increases. As a result, the frequency of the alternating current flowing through main transformer TR1 also increases. The secondary winding 42c of the main transformer TR1 is set in advance to resonate with the oscillation frequency of the drive IC 33 together with the resonance capacitor C3. Therefore, when the correction switch 32 is turned on, the oscillation frequency of the drive IC 33 changes. Thus, the voltage generated in the secondary winding 42c of the main transformer TR1 does not excessively rise outside the resonance frequency determined by the secondary winding 42c of the main transformer TR1 and the resonance capacitor C3.
[0067]
Note that the correction switch 32 used here is a switch that is turned on and off according to the thickness of the inclusion 50 such as a window glass or a wall. A switch capable of holding an OFF operation state is used.
[0068]
FIG. 6 is a circuit diagram of a non-contact power supply device 400 according to another embodiment of the present invention. In FIG. 6, the difference from the non-contact power supply device 1 shown in FIG. Although the power supply device outputs a rectangular wave AC voltage having a half frequency of the wave oscillator OSC1, the non-contact power supply device 400 can output an AC voltage having the same frequency as the commercial power supply. It is. Hereinafter, the configuration of the contactless power supply device 400 shown in FIG. 6 will be described. In the contactless power supply device 400, the same components as those of the contactless power supply device 1 shown in FIG.
[0069]
As shown in FIG. 6, the non-contact power supply device 400 forms a rectifier circuit 2a by removing the smoothing capacitor C1 from the first rectifier smoother circuit 2 shown in FIG. The operation circuit 7a is divided into a second rectifier circuit 5a composed of a bridge DB2 and a low-pass filter 401 composed of a capacitor C4, and has a zero-cross detection circuit 402 in place of the rectangular wave oscillator OSC1.
[0070]
The low-pass filter 401 is provided for removing a high-frequency component of an output wave of the diode bridge DB2, and is configured by connecting a capacitor C4 in parallel to an output of the diode bridge DB2. The low-pass filter 401 removes a high-frequency component from the output voltage (FIG. 7E) rectified by the diode bridge DB2, and a full-wave rectified waveform of the AC voltage of the commercial power supply shown in FIG. And
[0071]
Then, at the timing when the output voltage of the low-pass filter 401 becomes the threshold voltage of the hysteresis buffer IC5 (timing immediately before zero-crossing), the output voltage is alternately output from the output terminals 404 and 405, so that the output voltage is supplied from the power outlet 11. It is possible to output an AC voltage having the same frequency and waveform as a commercial power supply.
[0072]
The zero-cross detection circuit 402 is provided to detect the timing at which the output voltage of the low-pass filter 401 becomes the threshold voltage of the hysteresis buffer IC5 (timing immediately before zero-crossing), and detects the timing from the resistors R41 and R42 and the constant voltage diode ZD. It is configured.
[0073]
Specifically, one end of the resistor R41 is connected to the positive output of the low-pass filter 401, and the other end of the resistor R41 is connected to one end of the resistor R42 and the cathode of the constant voltage diode ZD61. The other end of the resistor R42 is connected to the negative output of the low-pass filter 401 together with the anode of the constant voltage diode ZD61.
[0074]
Then, the zero-crossing detection circuit 402 configured as described above outputs a high-pulse as a zero-crossing signal at the timing when the output voltage of the low-pass filter 401 becomes the threshold voltage of the hysteresis buffer IC5 (timing immediately before zero-crossing) (FIG. 7 (g)). ).
[0075]
The output of the hysteresis buffer IC5 is input to the clock terminal G of the D-type flip-flop IC1, and the data terminal D of the D-type flip-flop IC1 is connected to a positive terminal of a DC power supply (not shown). Accordingly, the output of the Q output terminal of the D-type flip-flop IC1 becomes high level, and the output is applied to a series circuit of the resistor R6 and the capacitor C5, and the voltage at the connection point between the resistor R6 and the capacitor C5 is changed by the resistor R6 And a time constant determined by the capacitor C5.
[0076]
That is, the output of the Q output terminal of the D-type flip-flop IC1 is integrated by the resistor R6 and the capacitor C5. Then, when the voltage at the connection point between the resistor R6 and the capacitor C5 reaches the threshold voltage of the reset terminal R of the D-type flip-flop IC1, the D-type flip-flop IC1 is reset to set the output of the Q output terminal to low level.
[0077]
As a result, a pulse having a time constant determined by the resistor R6 and the capacitor C5 is output from the Q output terminal of the D-type flip-flop IC1, and the D-type flip-flop IC1 outputs a high pulse having a constant width. It functions as a vibrator.
[0078]
On the other hand, the pulse signal output from the Q output terminal of the D-type flip-flop IC1 is input to the clock terminal G of the frequency divider IC2, and the frequency divider IC2 is determined by the signal level input to the data terminal D. The output is output from the Q output terminal and the Q bar output terminal.
[0079]
Here, since the Q bar output terminal of the frequency divider IC2 is connected to the data terminal D of the frequency divider IC2, a pulse appearing at the output of the Q output terminal of the D-type flip-flop IC1 is input to the frequency divider IC2. Every time, the output signals of the Q output terminal and the Q bar output terminal of the frequency divider IC2 are inverted between the high level and the low level (FIGS. 7 (i), (j)).
[0080]
Here, there is a case where the zero-cross signal is output from the zero-cross detection circuit 402 two or more times for one zero-cross detection due to the influence of disturbance of the voltage waveform or noise. At this time, if the zero-cross detection circuit 402 and the frequency divider IC2 are directly connected without passing through the D-type flip-flop IC1 (monostable multivibrator), the inverter circuit 6 is additionally switched by the double pulse described above. This causes a problem that a stable sine wave cannot be obtained.
[0081]
Therefore, in this embodiment, a D-type flip-flop IC1 (monostable multivibrator) is provided between the zero-cross detection circuit 402 and the frequency divider IC2 so that even if a double-pulse of a zero-cross signal is generated, the double-pulse Is reliably absorbed by the D-type flip-flop IC1 (monostable multivibrator) to completely prevent the double pulse from being input to the frequency divider IC2.
[0082]
Thus, even if a zero-cross signal is input (double pulse) while the D-type flip-flop IC1 (monostable multivibrator) outputs a high pulse, the D-type flip-flop IC1 (monostable multivibrator) newly outputs a high pulse. , The switching of the inverter circuit 6 can be controlled appropriately.
[0083]
On the other hand, the Q output terminal and the Q bar output terminal of the frequency divider IC2 are connected to one input terminal of the AND gates IC3 and IC4, respectively, and the other input terminals of the AND gates IC3 and IC4 are collectively connected to the other input terminals. The Q bar output terminal of the D-type flip-flop IC1 is connected.
[0084]
As a result, the outputs of the AND gates IC3 and IC4 are at a high level only during the time obtained by subtracting the output of the Q output terminal of the D-type flip-flop IC1 from the output of the Q output terminal and the Q output terminal of the frequency divider IC2. .
[0085]
The outputs of the AND gates IC3 and IC4 drive the switching elements Q4 and Q5 or Q3 and Q6 via the drivers Dr3 to Dr6. That is, the switching elements Q3 to Q6 are all turned off while the output of the Q bar output terminal of the D-type flip-flop IC1 is at the low level, and are turned on each time the output of the Q bar output terminal of the D-type flip-flop IC1 is at the high level. It repeats turning off.
[0086]
On the other hand, since the Q output terminal of the D-type flip-flop IC1 is connected to the switching element Q7 via the resistor R7, the switching element Q7 is turned on only when all the switching elements Q3 to Q6 of the inverter circuit 6 are turned off. I do.
[0087]
When the inductive load L1 such as a motor is connected to the inverter circuit 6 and the switching elements Q3 and Q6 are turned on and the switching elements Q4 and Q5 are turned off, the inductive load L1 is connected to the inductive load L1 as shown in FIG. As shown, when the switching elements Q3 and Q6 are on, a current flows from left to right.
[0088]
After that, even if all the switching elements Q3 to Q6 are turned off after a lapse of a predetermined time, since the electromagnetic energy is accumulated in the inductive load L1, the current of the inductive load L1 continues to flow, and FIG. As shown in b), the electromagnetic energy accumulated in the inductive load L1 on the path of the inductive load L1 → the parasitic diode D3 of the switching element Q5 → the capacitor C4 → the parasitic diode D2 of the switching element Q4 → the inductive load L1. Continue to flow until is released.
[0089]
As a result, charge is accumulated in the capacitor C4 of the second rectifier circuit 5a, and the voltage across the capacitor C4 increases. Here, when the switching element Q7 is turned on at the moment when all of the switching elements Q3 to Q6 are turned off, the current flowing through the inductive load L1 is changed from the inductive load L1 to the switching element as shown in FIG. The current flows through the path of the parasitic diode D3 of Q5 → the resistor R3 → the switching element Q7 → the parasitic diode D2 of the switching element Q4 → the inductive load L1. As a result, the electromagnetic energy stored in the inductive load L1 is reliably consumed by the resistor R3, and it is possible to completely prevent the output voltage of the second rectifier circuit 5a from abnormally increasing.
[0090]
Next, the operation of the contactless power supply device 400 will be described with reference to FIG. FIG. 7 is a waveform diagram individually showing the output voltage of each component circuit of the non-contact power supply device 400. The AC voltage of the commercial power supply is supplied to the first rectifier formed by the diode bridge DB1 via the power outlet 11 shown in FIG. Rectification is performed by the circuit 2a as shown in FIG.
[0091]
At the same time, power is supplied to the drive circuit 3 from a DC power supply (not shown), and signals are oscillated from the output terminals Out1 and Out2 of the drive IC 33 at a period determined by a capacitor C2 for timing generation and a series resistance of the resistors R1 and R2. The switching devices Q1 and Q2 are alternately driven (chopper control) via the resistors R4 and R5 (FIGS. 7B and 7C).
[0092]
When the switching devices Q1 and Q2 are alternately driven, an alternating current having a frequency determined by the capacitor C2 and the resistors R1 and R2 flows through the primary winding 41c of the main transformer TR1 of the coupling transformer 4, and the coupling transformer 4 Output the alternating voltage shown in FIG. At this time, since the output voltage of the diode bridge DB1 is not smoothed as shown in FIG. 7A, the envelope of the alternating voltage (output voltage) of the coupling transformer 4 follows the voltage waveform of the commercial power supply. It becomes.
[0093]
The alternating voltage output from the coupling transformer 4 is rectified by the diode bridge DB2 forming the second rectifier circuit 5a as shown in FIG. 7 (e), and is rectified by the low-pass filter 401 as shown in FIG. 7 (f). A high-frequency component is removed, and a waveform wave obtained by full-wave rectifying the AC voltage of the commercial power supply is obtained.
[0094]
On the other hand, the zero-cross detection circuit 402 detects the timing at which the waveform wave shown in FIG. 7 (f) becomes the threshold voltage of the hysteresis buffer IC5, and at that timing, as shown in FIG. 7 (g), outputs a high pulse as a zero-cross signal. Output.
[0095]
Then, the D-type flip-flop IC1 (monostable multivibrator) outputs a high pulse having a constant width shown in FIG. 7 (h) from the Q output terminal to the next-stage frequency divider IC2 at the rising timing of the zero-cross signal. At the rising timing of the high pulse, the outputs of the Q output terminal and the Q bar output terminal of the frequency divider IC2 are inverted as shown in FIGS. 7 (i) and 7 (j), respectively.
[0096]
By this inversion of the output, switching elements Q3 to Q6 are turned on or off, respectively, and output AC voltage Vy having the same frequency and waveform as the commercial power supply from output terminals 404 and 405 of contactless power supply device 400 (FIG. 7 (k )).
[0097]
Further, in the vicinity of the zero crossing of the AC power source, the switching element Q7 is turned on, so that the regenerative current flows through the resistor R3, thereby reliably consuming the regenerative current, and the output of the second rectifier circuit 5a abnormally rises. This can be completely prevented as described above.
[0098]
As described above, according to the non-contact power supply device 400 shown in FIG. 6, the regenerative current generated in the vicinity of the zero cross of the AC power supply can be reliably consumed by the resistor R3 to prevent the occurrence of overvoltage, and the commercial power supply and the frequency can be prevented. And output the same AC voltage Vy having the same waveform. If the output terminals 404 and 405 are used as outlets, various electric devices driven by a commercial frequency AC power supply can be used outdoors while isolating the indoors and the outdoors. Can be used at
[0099]
FIGS. 8 and 9 are diagrams showing a non-contact power supply device 10 configured by adding a new function to the non-contact power supply devices 1 and 400, which can eliminate the disadvantages of the non-contact power supply devices 1 and 400. It is.
[0100]
In other words, according to the non-contact power supply device 1400 having the configuration shown in FIGS. 1 and 6, when the power outlet 11 of the primary unit 41 is connected to the commercial power source, regardless of whether the secondary unit 42 is attached or not. However, the drive circuit 3 operates automatically, and the exciting current flows as a standby current to the primary side winding 41c of the coupling transformer 4, so that a constant power is always consumed.
[0101]
On the other hand, in the non-contact power supply device 10 shown in FIGS. 8 and 9, power is not consumed in the primary unit 41 unless the secondary unit 42 is attached to face the primary unit 41. Absent.
[0102]
That is, in the non-contact power supply device 10 shown in FIG. 8A, a push button switch (second switch means) is provided on a surface of the primary unit 41 facing the secondary unit 42, and A push button is provided on a surface of the secondary unit 42 facing the primary unit 41 and at a position facing the push button switch 65 of the primary unit 41 when the two units 41 and 42 are arranged to face each other. A recess 66 sufficiently larger than the switch 65 is formed.
[0103]
The push button switch 65 is a switch that maintains an ON state only while the switch 65 is pressed, and turns off when the switch is released. As shown, it is disposed between the power outlet 11 and the first rectifying / smoothing circuit 2. Further, the recess 66 is formed in a size that can accommodate the push button switch 65 therein while maintaining its off state.
[0104]
According to the non-contact power supply device 10, the AC voltage is supplied from the commercial power supply to the diode bridge DB1 and the drive circuit 3 only when the push button switch 65 is pressed while the power outlet 11 is connected to the commercial power supply. Supplied to
[0105]
In other words, when the push button switch 65 is not pressed, the AC voltage from the commercial power supply is not supplied to the diode bridge DB1 and the drive circuit 3 even if the power outlet 11 is plugged into the commercial power supply. The unit 41 is not driven and power is not wasted.
[0106]
Therefore, as shown in FIG. 9A, the primary unit 41 and the secondary unit 42 of the non-contact power supply device 10 are normally attached via the interposition 50 such as a window glass or a wall. In this case, the push button switch 65 is turned on by the inclusion 50, an AC voltage is supplied to the diode bridge DB1 and the drive circuit 3, and the primary unit 41 operates.
[0107]
On the other hand, as shown in FIG. 9B, when the primary unit 41 is detached from the inclusion 50, the push button switch 65 is not turned on, so that an AC voltage is supplied to the diode bridge DB1 and the drive circuit 3. No power is consumed by the primary unit 41.
[0108]
Also, as shown in FIG. 9C, when the primary unit 41 and the secondary unit 42 are directly opposed to each other without any intervening object 50, the push button switch 65 In this case, no AC voltage is supplied to the diode bridge DB1 and the drive circuit 3 and the primary unit 41 does not consume power.
[0109]
Normally, when the primary unit 41 is operated in a state as shown in FIG. 9C, an extremely high voltage is induced in the secondary unit 42 because the interval between the two units 41 and 42 is extremely narrow, and a fire such as a fire may occur. Risk of accident. However, in the contactless power supply device 10, the operation of the primary unit 41 is prohibited in such a situation (the primary unit 41 does not operate), so that an abnormally high voltage is induced in the secondary unit 42. The occurrence of fire or the like can be completely prevented.
[0110]
FIG. 10 shows that the primary unit 41 operates as long as the primary unit 41 and the secondary unit 42 do not face each other just by pointing the power outlet 11 to the commercial power supply, similarly to the non-contact power supply device 10. FIG. 2 is a perspective view showing a non-contact power supply device 100 having a configuration that does not cause a problem.
[0111]
In the non-contact power supply device 100, a reed switch 71 (third switch means) is disposed inside a surface of the primary unit 41 facing the secondary unit 42. A magnetic force sufficient to turn on the reed switch 71 at a position opposing the reed switch 71 of the primary unit 41 when the two units 41 and 42 are arranged opposite to each other on the surface facing the secondary unit 41. Are provided.
[0112]
The reed switch 71 is always off and is turned on by the magnetic force when the permanent magnet 72 approaches. The reed switch 71 once turned on is turned off by being separated from the permanent magnet 72.
[0113]
The reed switch 71 may be disposed at the same position (on the circuit) as the push button switch 65 of the non-contact power supply device 10 (see FIG. 8B), and the power outlet 11 is inserted into a commercial power supply. In this state, the AC voltage of the commercial power supply is supplied to the diode bridge DB1 and the drive circuit 3 only when the reed switch 71 is turned on.
[0114]
Therefore, when the reed switch 71 is off, the AC voltage from the commercial power supply is not supplied to the diode bridge DB1 and the drive circuit 3 even if the power outlet 11 is plugged into the commercial power supply. No power is consumed.
[0115]
As described above, in the non-contact power supply device 100 shown in FIG. 10, power is supplied to the primary unit 41 only when the primary unit 41 and the secondary unit 42 are opposed to each other. When the unit 41 and the secondary unit 42 are normally mounted via the interposition 50 such as a window glass or a wall, the reed switch 71 is turned on by the magnetic force of the permanent magnet 72, and the diode bridge DB1 and the An AC voltage is supplied to the drive circuit 3 so that the primary unit 41 can operate satisfactorily.
[0116]
On the other hand, when the secondary unit 42 is removed, the magnetic force of the permanent magnet 72 does not act on the reed switch 71, so that the reed switch 71 is not turned on. Therefore, in such a case, no AC voltage is supplied to the diode bridge DB1 and the drive circuit 3, and the primary unit 41 does not wastefully consume power.
[0117]
Note that the push button switch 65 and the recess 66 shown in FIG. 8A, the reed switch 71 and the permanent magnet 72 may be mounted together on one non-contact power supply device. FIG. 11A is a circuit diagram extracting and showing a power outlet 11 and a diode bridge DB1 portion of a non-contact power supply device 200 in which both switches 65 and 71 are connected in series and mounted together.
[0118]
This non-contact power supply device 200 has the primary unit 41 only when the primary unit 41 and the secondary unit 42 are opposed to each other with the inclusion 50 interposed therebetween, as shown in FIG. Is turned on, as shown in FIG. 11C, when only the primary unit 41 abuts on the inclusion 50 and the secondary unit 42 is removed, or as shown in FIG. 11D. When the primary unit 41 and the secondary unit 42 are directly opposed to each other without the interposition of the inclusion 50, the primary unit 41 is turned off.
[0119]
In other words, when only the primary unit 41 is attached, or when both the primary unit 41 and the secondary unit 42 are aligned and the two units 41 and 42 are directly opposed to each other, The primary unit 41 is not turned on, so that wasteful power consumption in the primary unit 41 and generation of an abnormally high voltage in the secondary unit 42 can be reliably prevented.
[0120]
【The invention's effect】
According to the non-contact power supply device of the first aspect, the regenerative current generated when an inductive load is connected to the AC output can be surely consumed in the vicinity of the zero cross of the AC output. Can be prevented from rising abnormally.
[0121]
According to the non-contact power supply device of the second aspect, it is possible to reliably consume the regenerative current generated in the vicinity of the zero cross of the AC power supply and to prevent the occurrence of overvoltage, and to reduce the AC voltage having the same frequency and waveform as the commercial power supply. Since the power can be output, it can be used as a power supply for various electric devices driven by an AC power supply having a commercial frequency.
[0122]
According to the non-contact power supply device of the third aspect, in addition to the effects of the non-contact power supply device of the first and second aspects, by providing the resonance circuit on the secondary side, the impedance of the secondary winding is increased. , The current can easily flow through the secondary winding, the power supply from the primary unit to the secondary unit can be optimized, and the power supply between the primary unit and the secondary unit can be reduced. By operating the switch means in accordance with the thickness of the inclusion, the oscillation frequency of the primary unit deviates from the resonance frequency of the secondary unit, thereby reliably preventing an overvoltage from being generated in the secondary unit. Can be convenient.
[0123]
According to the non-contact power supply device of the fourth aspect, in addition to the effects of the non-contact power supply device of the first to third aspects, a zero-cross detection circuit is provided for one zero-cross detection due to the influence of a voltage waveform, noise, or the like. Therefore, even when the zero-cross signal is output twice or more, the on / off timing of the switching element of the inverter circuit can be always kept normal, and the alternating current can be stably supplied, which is effective.
[0124]
According to the non-contact power supply device of the fifth aspect, in addition to the effect of the non-contact power supply device of the first to fourth aspects, the primary unit and the secondary unit are directly opposed to each other without any intervening object. In this case, the driving of the primary unit is reliably prevented, and the output of the secondary unit can be completely prevented from abnormally increasing, which is convenient.
[0125]
According to the non-contact power supply device of the sixth aspect, in addition to the effects of the non-contact power supply device of the first to fourth aspects, as long as the primary unit and the secondary unit are not arranged to face each other, the primary side Simply connecting the unit to a commercial power supply does not drive the primary unit, and it is possible to reliably prevent unnecessary power consumption in the primary unit, which is convenient.
[Brief description of the drawings]
FIG. 1 is a circuit diagram of a non-contact power supply device according to a first embodiment of the present invention.
FIG. 2 is a side sectional view of a coupling transformer included in the non-contact power supply device.
FIG. 3 is a diagram illustrating a use state of the non-contact power supply device.
FIG. 4 is a waveform diagram of each circuit constituting the non-contact power supply device.
FIG. 5 is a circuit diagram for explaining an effect of a switching element and a resistor constituting the contactless power supply device.
FIG. 6 is a circuit diagram of a non-contact power supply device according to a second embodiment of the present invention.
FIG. 7 is a waveform diagram showing output voltage waveforms of respective parts constituting a circuit provided for outputting an AC voltage in the contactless power supply device of the second embodiment.
FIG. 8A is a perspective view showing an example of the external appearance of the non-contact power supply device, and FIG. 8B is a circuit diagram extracting and showing a power outlet and a diode bridge portion of the non-contact power supply device. is there.
FIG. 9 is a use state diagram of the non-contact power supply device shown in FIG. 8;
FIG. 10 is a perspective view showing an example of an appearance of the non-contact power supply device.
11 (a) is a circuit diagram extracting and showing a power outlet and a diode bridge portion of the non-contact power supply device shown in [FIG. 10], and (b) to (d) are the non-contact power supply devices; FIG.
[Explanation of symbols]
1,10,100,200,400 Non-contact power supply
2 First rectifying and smoothing circuit
2a First rectifier circuit
3 Drive circuit
4 coupling transformer
5. Second rectifying and smoothing circuit
5a Second rectifier circuit
6. Inverter circuit
7,7a operation circuit
11 Power outlet
32 Correction switch
33 Drive IC
41 Primary unit
65 push button switch (second switch means)
71 Reed switch (third switch means)
72 permanent magnet
DB1, DB2 diode bridge
C1, C4 smoothing capacitor
C2 Timing generation capacitor
C3 resonance capacitor
R1 to R6, R41, R42 Resistance
Q1, Q2 switching device
Q3 ~ Q6 Switching element
OSC1 Square wave oscillator
IC1 D-type flip-flop (monostable multivibrator)
IC2 frequency divider
IC3, IC4 AND gate
IC5 hysteresis buffer
TR1 main transformer
L1 Inductive load
ZD61 constant voltage diode

Claims (6)

The primary unit accommodating the primary winding and the secondary unit accommodating the secondary winding are separable, and are coupled from the primary winding and the secondary winding by approaching both units. In a non-contact power supply device that forms a transformer and supplies electric power from the primary unit to the secondary unit in a non-contact and non-contact manner by electromagnetic coupling of the coupling transformer, the primary unit includes an output of a commercial power supply. A first rectifying / smoothing circuit for rectifying and smoothing a voltage, and a drive circuit for applying a high-frequency alternating current to a primary winding of the coupling transformer by chopper-controlling an output voltage of the first rectifying / smoothing circuit, The secondary unit includes a second rectifying / smoothing circuit that rectifies and smoothes an induced voltage flowing through the secondary winding and outputs the rectified / smoothed circuit, and two units connected in series to an output side of the second rectifying / smoothing circuit. Switching elements in parallel An inverter circuit configured in succession, an operation circuit for alternately turning on or off the two sets of switching elements to output an AC voltage from the inverter circuit, and the inverter circuit near a zero crossing of an output voltage of the inverter circuit. A non-contact power supply device comprising a resistor that consumes a regenerative current flowing through a circuit. The primary unit accommodating the primary winding and the secondary unit accommodating the secondary winding are separable, and are coupled from the primary winding and the secondary winding by approaching both units. In a non-contact power supply device that forms a transformer and supplies electric power from the primary unit to the secondary unit in a non-contact and non-contact manner by electromagnetic coupling of the coupling transformer, the primary unit includes an output of a commercial power supply. A first rectifier circuit for rectifying a voltage; and a drive circuit for chopper-controlling an output voltage of the first rectifier circuit to apply a high-frequency alternating current to a primary winding of the coupling transformer. The side unit includes a rectifier circuit that rectifies an induced voltage flowing through the secondary winding, a low-pass filter that removes high-frequency components from an output voltage of the rectifier circuit, and a tie that reduces the output voltage of the low-pass filter to zero volts. A zero-crossing detection circuit that outputs a zero-crossing signal by switching, an inverter circuit configured by connecting two sets of two switching elements connected in series on the output side of the low-pass filter in parallel, and according to the zero-crossing signal, An operation circuit that alternately turns on or off two sets of switching elements that constitute the inverter circuit, and outputs an alternating voltage having the same frequency as the commercial power supply from the inverter circuit; and an operation circuit near the zero crossing of the output voltage of the inverter circuit. A non-contact power supply device comprising a resistor that consumes a regenerative current flowing through an inverter circuit. The secondary unit includes a resonance circuit in which the number of turns of a secondary winding and a capacitor capacity are adjusted so that the frequency of the primary current of the coupling transformer and the resonance frequency of the secondary become equal. 3. The non-contact power supply device according to claim 1, wherein the circuit includes first switching means for causing the oscillation frequency of the primary unit to deviate from the resonance frequency of the secondary unit. The operation circuit includes a double pulse prevention circuit that absorbs the second and subsequent zero-cross signals in the operation circuit when two or more zero-cross signals are output from the zero-cross detection circuit within a predetermined time. 4. The non-contact power supply according to claim 1, wherein: The primary unit includes second switch means for switching between driving and stopping the primary unit. When the secondary unit is opposed to the primary unit and is in contact with the primary unit, the secondary unit is connected to the primary unit. 5. A non-contact power supply device according to claim 1, wherein a housing groove capable of housing without turning on said second switch means is formed. The secondary unit is provided with a permanent magnet, and the primary unit is turned on / off according to the presence / absence of magnetic sensing of the permanent magnet provided in the secondary unit, and drives / stops the primary unit. 5. The wireless power feeding device according to claim 1, further comprising a third switch for switching the power supply.

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