JP2002026630A - Adaptive array antenna - Google Patents
Adaptive array antennaInfo
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- JP2002026630A JP2002026630A JP2000205056A JP2000205056A JP2002026630A JP 2002026630 A JP2002026630 A JP 2002026630A JP 2000205056 A JP2000205056 A JP 2000205056A JP 2000205056 A JP2000205056 A JP 2000205056A JP 2002026630 A JP2002026630 A JP 2002026630A
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- Prior art keywords
- reception
- transmission
- antenna
- antenna element
- elements
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Abstract
Description
【０００１】[0001]
【発明の属する技術分野】この発明は例えば移動通信シ
ステムの基地局に使用され、移動局の移動に伴いアンテ
ナ指向特性の主ビーム方向をそれに追尾させたり、干渉
局からの電波到来方向がアンテナ指向特性のナル方向と
なるように、特に受信アンテナ指向特性及び送信アンテ
ナ指向特性を適応制御するアダプティブアレーアンテナ
に関する。BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention is used in, for example, a base station of a mobile communication system. The main beam direction of the antenna directivity is tracked with the movement of the mobile station, and the direction of arrival of a radio wave from an interference station is directed to the antenna. In particular, the present invention relates to an adaptive array antenna that adaptively controls a reception antenna directional characteristic and a transmission antenna directional characteristic so that the characteristic becomes a null direction.
【０００２】[0002]
【従来の技術】移動通信システムの基地局にアダプティ
ブアレーアンテナを導入することにより、回線容量の増
大を計る場合、上り回線だけではなく、下り回線におけ
る干渉波抑圧が必要である。このような点からアダプテ
ィブアレーアンテナを送信と受信とに兼用し、受信信号
から求めた各アンテナ素子と対応する重みを、送信信号
に対する重みとして利用することが行われていた。2. Description of the Related Art In order to increase the line capacity by introducing an adaptive array antenna into a base station of a mobile communication system, it is necessary to suppress interference waves not only in the uplink but also in the downlink. From such a point, the adaptive array antenna is used for both transmission and reception, and the weight corresponding to each antenna element obtained from the received signal is used as the weight for the transmission signal.
【０００３】つまり、図５に示すように、アンテナ素子
Ａ１〜Ａ８が等間隔ｄで配列される。受信キャリア周波
数ｆｒ、その波長をλｒ、送信キャリア周波数ｆｔ、そ
の波長をλｔとすると、ｄ＝λｒ／２＝λｔ／（２
Ｒ）、Ｒ＝λｔ／λｒとされる。アンテナ素子Ａ１〜Ａ
８はそれぞれ送受共用器ＤＵＸ１〜ＤＵＸ８と接続さ
れ、これら送受共用器ＤＵＸ１〜ＤＵＸ８にはそれぞれ
送信機Ｔｘ１〜Ｔｘ８と、受信機Ｒｘ１〜Ｒｘ８が接続
される。That is, as shown in FIG. 5, antenna elements A1 to A8 are arranged at equal intervals d. Assuming that the reception carrier frequency fr, its wavelength is λr, the transmission carrier frequency ft, and its wavelength is λt, d = λr / 2 = λt / (2
R), R = λt / λr. Antenna elements A1 to A
8 are respectively connected to the duplexers DUX1 to DUX8, and the duplexers DUX1 to DUX8 are connected to the transmitters Tx1 to Tx8 and the receivers Rx1 to Rx8, respectively.
【０００４】受信機Ｒｘ１〜Ｒｘ８の受信出力信号（ベ
ースバンド信号）は重み決定回路１１で各アンテナ素子
Ａ１〜Ａ８について、アンテナ指向特性の主ローブの方
向が信号波の到来方向となり、ナル方向が干渉波の到来
方向となるように重みＷ１〜Ｗ８が計算され、これら重
みＷ１〜Ｗ８が、受信機Ｒｘ１〜Ｒｘ８の各出力信号に
対し、受信用重み付与回路Ｍｒ１〜Ｍｒ８で受信機Ｒｘ
１〜Ｒｘ８の各出力受信信号に重み付けがなされ、つま
り振幅と位相が制御され、これら受信用重み付与回路Ｍ
ｒ１〜Ｍｒ８の出力が合成回路１２で合成されて、受信
信号が出力される。この受信信号は、アンテナ指向特性
の主ローブが信号（希望）波方向に向き、ナル方向が干
渉波方向に向いた状態の受信信号となる。The reception output signals (baseband signals) of the receivers Rx1 to Rx8 are determined by a weight determination circuit 11 for the antenna elements A1 to A8, in which the direction of the main lobe of the antenna directivity becomes the arrival direction of the signal wave, and the null direction becomes Weights W1 to W8 are calculated so as to be directions of arrival of the interference waves, and these weights W1 to W8 are applied to the output signals of the receivers Rx1 to Rx8 by receiving weighting circuits Mr1 to Mr8.
1 to Rx8 are weighted, that is, the amplitude and the phase are controlled.
The outputs of r1 to Mr8 are combined by the combining circuit 12, and a received signal is output. This reception signal is a reception signal in which the main lobe of the antenna directivity is oriented in the signal (desired) wave direction and the null direction is oriented in the interference wave direction.
【０００５】送信信号のアンテナ指向特性の主ローブが
希望局の方向に向き、ナル方向が干渉源になる方向とな
るようにするため、従来においては、送信信号（ベース
バンド信号）を分配回路１３で、この例では８分配し
て、各分配された送信信号に対し、送信用重み付与回路
Ｍｔ１〜Ｍｔ８でそれぞれ重みＷ１〜Ｗ８が与えられ、
送信用重み付与回路Ｍｔ１〜Ｍｔ８の各出力はそれぞれ
送信機Ｔｘ１〜Ｔｘ８に入力され、高周波送信信号とし
て、アンテナＡ１〜Ａ８へ給電される。Conventionally, the transmission signal (baseband signal) is distributed to the distribution circuit 13 so that the main lobe of the antenna directivity of the transmission signal is directed to the desired station and the null direction is the direction of the interference source. In this example, weights W1 to W8 are given to the divided transmission signals by transmission weighting circuits Mt1 to Mt8, respectively.
The outputs of the transmission weighting circuits Mt1 to Mt8 are input to the transmitters Tx1 to Tx8, respectively, and supplied to the antennas A1 to A8 as high-frequency transmission signals.
【０００６】このようにして上り回線の改善に用いた重
みを用いて下り回線の信号に重みも与えて、下り回線の
改善を行っていた。なお、アンテナ素子間隔を等比間隔
とするアレーアンテナとして、対数周期アンテナ（ログ
ペリアンアンテナ）がある。このアンテナは素子間隔が
等比であり、かつ素子長もまた等比構造をなし、給電点
は１箇所であり、アレー構造であるが、各素子に任意の
重みで給電するマルチポートアンテナではないので任意
の指向特性のビームを生成することはできない。[0006] In this manner, the weight of the downlink signal is also given by using the weight used for the improvement of the uplink to improve the downlink. Note that a log-periodic antenna (log-perian antenna) is an example of an array antenna in which antenna element intervals are set at equal ratio intervals. This antenna has an equidistant element spacing and an equidistant element length, has a single feed point, and has an array structure, but is not a multiport antenna that feeds each element with an arbitrary weight. Therefore, it is not possible to generate a beam having an arbitrary directional characteristic.
【０００７】[0007]
【発明が解決しようとする課題】アレーアンテナにおい
ては、送信搬送波周波数と、受信搬送波周波数とでは、
本来は送信と受信それぞれの周波数に対応した波長で規
格化した素子間隔として、各素子ごとに重みを与えて、
指向特性の制御をすべきであるが、図５に示した従来の
アダプティブアレーアンテナにおいては、送信時も、受
信時も、アンテナ素子間隔は同一としているため、図６
に示すように、水平面指向特性は受信時は曲線１４とな
り、送信時は曲線１５となり、可成り異なったものとな
り、下り回線と上り回線とを同一の放射パターンとする
ことはできなかった。SUMMARY OF THE INVENTION In an array antenna, the transmission carrier frequency and the reception carrier frequency are:
Originally, weighting was given to each element as the element spacing standardized by the wavelength corresponding to each frequency of transmission and reception,
Although the directivity should be controlled, the conventional adaptive array antenna shown in FIG. 5 has the same antenna element spacing at the time of transmission and at the time of reception.
As shown in the figure, the horizontal plane directivity becomes curve 14 at the time of reception and curve 15 at the time of transmission, which are considerably different from each other, and the downlink and uplink cannot have the same radiation pattern.
【０００８】このような場合、仮に上り回線で干渉局か
らの電波を十分抑圧しても、下り回線での干渉は抑圧で
きないため、結局、回線容量を増大することはできな
い。この不一致を解消するために、図７に示すように、
上り回線用重みＷ１〜Ｗ８を、補正回路１６で、送信周
波数と受信周波数との周波数偏差の分だけ数値演算的に
補正を行い、これら補正した重みＷ１′〜Ｗ８′を送信
用重み付与回路Ｍｔ１〜Ｍｔ８にそれぞれ与えることが
考えられる。しかしこの場合は特定のビームや零点のみ
にしか適用できない。更に余分な処理時間がかかり、適
応性に問題があり、必ずしも正しい制御を行うことがで
きない。なお図７において、受信用重み付与回路Ｍｒ１
〜Ｍｒ８、合成回路１２は、図を簡略するため省略して
示した。In such a case, even if the radio wave from the interference station is sufficiently suppressed on the uplink, the interference on the downlink cannot be suppressed, so that the line capacity cannot be increased after all. To resolve this mismatch, as shown in FIG.
The uplink weights W1 to W8 are numerically corrected by the correction circuit 16 by the frequency deviation between the transmission frequency and the reception frequency, and the corrected weights W1 'to W8' are transmitted to the transmission weighting circuit Mt1. To Mt8. However, in this case, it can be applied only to a specific beam or zero. Furthermore, extra processing time is required, there is a problem in adaptability, and correct control cannot always be performed. In FIG. 7, the receiving weighting circuit Mr1
To Mr8 and the synthesis circuit 12 are omitted for simplification of the drawing.
【０００９】この発明の目的は、受信アンテナ指向特性
パターンと送信アンテナ指向特性パターンとを、時間遅
れを伴うことなく、一致させることができるアダプティ
ブアレーアンテナを提供することにある。An object of the present invention is to provide an adaptive array antenna capable of matching a receiving antenna directional pattern with a transmitting antenna directional pattern without a time delay.
【００１０】[0010]
【課題を解決するための手段】この発明によれば、複数
のアンテナ素子が送受信搬送波周波数比に等しい等比間
隔で配列され、アンテナ素子配列方向において、その全
素子数Ｎより少ない、つまりＮ−１以下で２分の１より
多い、つまり（Ｎ／２）＋１以上の連続したアンテナ素
子が受信用とされ、これら受信用アンテナ素子に対し、
その素子配列方向にずらされた、全素子数Ｎより少ない
（Ｎ−１以下）が２分の１より多い（（Ｎ／２）＋１以
上）連続したアンテナ素子が送信用とされ、従って少な
くとも１つのアンテナ素子が送信用と受信用とに共用さ
れ、受信信号から求めた各アンテナ素子の受信信号に対
して与える重みを、受信用アンテナ素子配列と送信用ア
ンテナ素子配列とのずれだけずらして送信用アンテナ素
子への各送信信号に対して重みを与える。According to the present invention, a plurality of antenna elements are arranged at equal intervals equal to the transmission / reception carrier frequency ratio, and are smaller than the total number N of antenna elements in the antenna element arrangement direction, that is, N- The number of continuous antenna elements less than 1 and more than one half, that is, (N / 2) +1 or more, is determined to be for reception. For these reception antenna elements,
A continuous antenna element shifted in the element array direction and less than the total number N of elements (N-1 or less) but more than half ((N / 2) +1 or more) is used for transmission. One antenna element is shared for transmission and reception, and the weight given to the reception signal of each antenna element obtained from the reception signal is shifted by the difference between the reception antenna element array and the transmission antenna element array. A weight is given to each transmission signal to the trusted antenna element.
【００１１】[0011]
【発明の実施の形態】図１にこの発明の実施例を示し、
図５と対応する部分に同一参照記号を付けてある。この
例は１次元アレーの場合である。この発明ではアンテナ
素子Ａ１〜Ａ８は、送信搬送波周波数ｆｔ（波長λｔ）
と受信搬送波周波数ｆｒ（波長λｒ）との比に等しい等
比間隔で配列される。また受信用アンテナ素子列と送信
用アンテナ素子列は、その素子配列方向においてずらさ
れているが、少くとも１つのアンテナ素子は受信用と送
信用とに兼用される。FIG. 1 shows an embodiment of the present invention.
Parts corresponding to those in FIG. 5 are given the same reference symbols. This example is for a one-dimensional array. In the present invention, the antenna elements A1 to A8 are provided at the transmission carrier frequency ft (wavelength λt).
And the received carrier frequency fr (wavelength λr). Although the receiving antenna element row and the transmitting antenna element row are shifted in the element arrangement direction, at least one antenna element is used for both reception and transmission.
【００１２】また受信用素子配列と送信用素子配列との
ずらされたアンテナ素子数をｎ、Ｒ＝λｔ／λｒ＝ｆｒ
／ｆｔ、σ＝Ｒ1/nとすると、図１において中央部のア
ンテナ素子Ａ４とＡ５の間隔はｄ、それより図１におい
て右側の各隣接アンテナ素子間隔はそれぞれ中央部から
離れるに従ってｄ／σ、ｄ／σ2，ｄ／σ3とされ、左側
の各隣接アンテナ素子間隔はそれぞれ中央部から離れる
に従ってσｄ、σ2ｄ，σ3ｄとされる。Further, the number of antenna elements shifted between the receiving element array and the transmitting element array is n, and R = λt / λr = fr.
Assuming that / ft and σ = R 1 / n , the distance between the central antenna elements A4 and A5 in FIG. 1 is d, and the distance between each adjacent antenna element on the right side in FIG. , D / σ 2 , d / σ 3, and the distance between adjacent antenna elements on the left side becomes σd, σ 2 d, σ 3 d as the distance from the center increases.
【００１３】この実施例では、送受信搬送波周波数比ｆ
ｒ／ｆｔ＝０．９のＦＤＤ（周波数分割半二重通信）方
式において８素子アレーアンテナ構成とした場合で、ア
ンテナ素子Ａ２〜Ａ８が受信用とされ、アンテナ素子Ａ
１〜Ａ７が送信用とされ、つまりこれら受信用アンテナ
素子列と送信用アンテナ素子列とのずれｎは１の場合で
ある。アンテナ素子間隔をＲとｄにより示すと、左から
Ｒ3ｄ，Ｒ2ｄ，Ｒｄ，ｄ，ｄ／Ｒ，ｄ／Ｒ2，ｄ／Ｒ3と
なる。受信機Ｒｘ２〜Ｒｘ８の受信出力信号（ベースバ
ンド信号）が重み決定回路１１に入力され、受信用重み
付与回路Ｍｒ２〜Ｍｒ８にそれぞれ与える重みＷ２〜Ｗ
８が計算される。受信機Ｒｘ２〜Ｒｘ８の受信出力信号
に対し、回路Ｍｒ２〜Ｍｒ８でそれぞれ重みＷ２〜Ｗ８
が与えられ、これら重みが与えられた信号が合成回路１
２で合成された受信信号として出力される。In this embodiment, the transmission / reception carrier frequency ratio f
In an FDD (frequency division half-duplex communication) system with r / ft = 0.9, an eight-element array antenna configuration is used, and antenna elements A2 to A8 are used for reception, and antenna element A
1 to A7 are used for transmission, that is, the shift n between the reception antenna element row and the transmission antenna element row is one. When the antenna element intervals are indicated by R and d, they are R 3 d, R 2 d, Rd, d, d / R, d / R 2 , and d / R 3 from the left. The reception output signals (baseband signals) of the receivers Rx2 to Rx8 are input to the weight determination circuit 11, and the weights W2 to W given to the reception weighting circuits Mr2 to Mr8, respectively.
8 is calculated. The circuits Mr2 to Mr8 respectively apply weights W2 to W8 to the reception output signals of the receivers Rx2 to Rx8.
Are given, and the signal given these weights is
2 is output as the received signal synthesized.
【００１４】一方、送信信号は分配回路１３で７分配さ
れ、送信用重み付与回路Ｍｔ１〜Ｍｔ７に入力され、そ
れぞれ前記重みＷ２〜Ｗ８が補正されることなくそのま
ま付与され、これら送信用重み付与回路Ｍｔ１〜Ｍｔ７
の出力が送信機Ｔｘ１〜Ｔｘ７で高周波信号とされてア
ンテナ素子Ａ１〜Ａ７に給電される。つまり受信用アン
テナ素子Ａ２〜Ａ８の受信信号に対して与える重みＷ２
〜Ｗ８を、その配列関係を保ったまま、受信用アンテナ
素子列と送信用アンテナ素子列とのずれだけずらして、
送信用アンテナ素子Ａ１〜Ａ７への送信信号に対して重
みを与える。On the other hand, the transmission signal is divided into seven by the distribution circuit 13 and input to the transmission weighting circuits Mt1 to Mt7, where the weights W2 to W8 are respectively applied without correction, and these transmission weighting circuits are provided. Mt1 to Mt7
Are converted into high-frequency signals by the transmitters Tx1 to Tx7 and supplied to the antenna elements A1 to A7. That is, the weight W2 given to the reception signals of the reception antenna elements A2 to A8
ＷW8 are shifted by the shift between the receiving antenna element row and the transmitting antenna element row while maintaining the arrangement relationship,
Weights are given to the transmission signals to the transmission antenna elements A1 to A7.
【００１５】いま図２Ａ，Ｂに示すようにアンテナ素子
間隔を送受信搬送波周波数比に等しい等比間隔で配列
し、受信アンテナ素子列と送信アンテナ素子列とのずれ
であるアンテナ素子数ｎ＝１の場合、各アンテナ素子間
隔を受信搬送波周波数で規格化すると、つまり受信波長
λｒで割算すると、図２Ｃに示すようになり、また送信
搬送波周波数で規格化すると図２Ｄに示すようになる。
これら規格化アンテナ素子間隔は受信波長λｒで規格化
したもの（図２Ｃ）を、送受信用のアンテナ素子のずれ
数ｎ＝１だけ図２において左にずらすと、つまり送信用
アンテナ素子列側に移動すると、送信波長λｔで規格化
した間隔（図２Ｄ）と同一になる。Now, as shown in FIGS. 2A and 2B, the antenna element intervals are arranged at equal intervals equal to the transmission / reception carrier frequency ratio, and the number of antenna elements, n = 1, which is the difference between the reception antenna element row and the transmission antenna element row. In this case, when the antenna element spacing is normalized by the reception carrier frequency, that is, when divided by the reception wavelength λr, the result becomes as shown in FIG. 2C, and when normalized by the transmission carrier frequency, it becomes as shown in FIG. 2D.
These normalized antenna element intervals, which are normalized by the reception wavelength λr (FIG. 2C), are shifted to the left in FIG. 2 by the number of shifts n = 1 of the transmitting and receiving antenna elements, that is, they move toward the transmitting antenna element row. Then, the interval becomes the same as the interval standardized by the transmission wavelength λt (FIG. 2D).
【００１６】従って、図１に示すように受信用アンテナ
素子Ａ２〜Ａ８の受信信号に対し与える重みＷ２〜Ｗ８
を、送信用アンテナ素子Ａ１〜Ａ７の送信信号に与える
と、受信アンテナ指向特性と、送信アンテナ指向特性と
が同一パターンとなる。図１に示した実施例において、
電子計算機シュミレーションにより求めた水平面指向特
性は図３に示すようになり、受信パターン曲線１７と送
信パターン曲線１８とはほぼ一致し、干渉波方向を完全
に一致させることができる。Therefore, as shown in FIG. 1, the weights W2 to W8 given to the reception signals of the reception antenna elements A2 to A8 are set.
Is given to the transmission signals of the transmission antenna elements A1 to A7, the reception antenna directivity and the transmission antenna directivity have the same pattern. In the embodiment shown in FIG.
The horizontal plane directivity obtained by the computer simulation is as shown in FIG. 3, and the reception pattern curve 17 and the transmission pattern curve 18 substantially match, and the interference wave direction can be completely matched.
【００１７】ちなみに、受信アンテナ素子列と送信アン
テナ素子列とのずれのアンテナ素子数をｎ＝３とした場
合、σ＝Ｒ1/3となり、受信波長λｒで規格化したアン
テナ素子間隔は図２Ｅに示すようになり、送信波長λｔ
で規格化したアンテナ素子間隔は図２Ｆに示すようにな
る。この場合も図２Ｅの各値をずれのアンテナ素子数ｎ
＝３だけ図において左へずらせば、アンテナ素子間隔は
同一となる。つまり受信用アンテナ素子Ａ４〜Ａ９の受
信信号に対し与える重みＷ４〜Ｗ９を、送信用アンテナ
素子Ａ０〜Ａ６への送信信号にそれぞれ与えればよい。Incidentally, when the number of antenna elements of the shift between the reception antenna element row and the transmission antenna element row is n = 3, σ = R 1/3 , and the antenna element spacing normalized by the reception wavelength λr is shown in FIG. And the transmission wavelength λt
The antenna element spacing standardized as shown in FIG. 2F is as shown in FIG. 2F. Also in this case, the respective values of FIG.
= 3, the antenna element intervals are the same. That is, the weights W4 to W9 given to the reception signals of the reception antenna elements A4 to A9 may be given to the transmission signals to the transmission antenna elements A0 to A6, respectively.
【００１８】この発明は２次元アレーアンテナにも適用
できる。図４にその実施例を示す。ここでは説明のため
送受信搬送波周波数比ｆｒ／ｆｔ＝０．９のＦＤＤ方式
システムにおいて、８素子×１０素子アレーアンテナ構
成の場合である。この場合は図１に示したと同様に水平
方向アレーにこの発明を適用すると共に垂直方向アレー
にも適用している。受信用アンテナ素子としてＡ２２〜
Ａ２８，Ａ３２〜Ａ３８，…Ａ１０２〜Ａ１０８が用い
られ、送信用アンテナ素子としてＡ１１〜Ａ１７，Ａ２
１〜Ａ２７，…Ａ１０１〜Ａ１０７が用いられる。これ
ら受信用２次元アレーアンテナ２１の各隣接素子間隔
を、受信波長λｒで規格化したものと、送信用２次元ア
レーアンテナ２２の隣接素子間隔を送信波長λｔで規格
化したものとは互いに等しいものとなる。よって図１に
示した実施例と同様に、受信用２次元アレーアンテナの
各受信信号に対して与えた重みを、送信用２次元アレー
アンテナの対応するアンテナ素子に対する送信信号に対
し与えれば、受信パターンと同一の送信パターンを３次
元的に生成することができる。The present invention can be applied to a two-dimensional array antenna. FIG. 4 shows the embodiment. Here, for the sake of explanation, a case of an 8 element × 10 element array antenna configuration in an FDD system in which the transmission / reception carrier frequency ratio fr / ft = 0.9 is used. In this case, the present invention is applied not only to the horizontal array but also to the vertical array as shown in FIG. A22 ~ as receiving antenna element
A28, A32 to A38,... A102 to A108 are used, and A11 to A17, A2 are used as transmitting antenna elements.
A101 to A107 are used. The two adjacent two-dimensional array antennas 21 for receiving are normalized by the reception wavelength λr, and the two adjacent two-dimensional array antennas 22 for transmission are normalized by the transmission wavelength λt. Becomes Therefore, similarly to the embodiment shown in FIG. 1, if the weight given to each reception signal of the two-dimensional array antenna for reception is given to the transmission signal to the corresponding antenna element of the two-dimensional array antenna for transmission, the reception The same transmission pattern as the pattern can be generated three-dimensionally.
【００１９】この２次元アレーアンテナにおいても、受
信用２次元アレーアンテナと送信用２次元アレーアンテ
ナとのずれは、１アンテナ素子に限らないがアンテナ素
子配列方向（水平方向又は垂直方向）において少くとも
１つのアンテナ素子を共用するようにする。Also in this two-dimensional array antenna, the deviation between the two-dimensional array antenna for reception and the two-dimensional array antenna for transmission is not limited to one antenna element, but at least in the antenna element arrangement direction (horizontal direction or vertical direction). One antenna element is shared.
【００２０】[0020]
【発明の効果】以上述べたように、この発明によれば、
送信パターンを受信パターンと同一にすることができ、
しかも、受信パターンを得るために用いた重みをそのま
ま用いて、送信パターン形成に利用できるため、送信パ
ターンの制御を、受信パターンの制御と同時に行うこと
ができ、送受信の干渉改善のバランスが良くなる。従っ
て回線容量の大幅な増加を実現することができる。As described above, according to the present invention,
The transmission pattern can be the same as the reception pattern,
In addition, since the weight used for obtaining the reception pattern can be used as it is to form the transmission pattern, the transmission pattern can be controlled simultaneously with the control of the reception pattern, and the balance of transmission and reception interference improvement is improved. . Therefore, a large increase in the line capacity can be realized.
【図１】この発明を１次元アレーアンテナに適用した実
施例を示す図。FIG. 1 is a diagram showing an embodiment in which the present invention is applied to a one-dimensional array antenna.
【図２】等比アンテナ間隔と、その受信波長で規格化し
た値と、送信波長で規格化した値の例を示す図。FIG. 2 is a diagram showing an example of equi-ratio antenna intervals, values normalized by a reception wavelength thereof, and values normalized by a transmission wavelength.
【図３】この発明の実施例における受信アンテナと送信
アンテナの各水平面指向性を示す図。FIG. 3 is a diagram showing horizontal plane directivities of a receiving antenna and a transmitting antenna in the embodiment of the present invention.
【図４】この発明を２次元アレーアンテナに適用した実
施例を示す図。FIG. 4 is a diagram showing an embodiment in which the present invention is applied to a two-dimensional array antenna.
【図５】従来の送受信兼用アダプティブアレーアンテナ
を示す図。FIG. 5 is a diagram showing a conventional transmission / reception adaptive array antenna.
【図６】図５に示したアレーアンテナの送信時と受信時
における各水平面指向性を示す図。FIG. 6 is a diagram showing each horizontal plane directivity at the time of transmission and reception of the array antenna shown in FIG. 5;
【図７】従来の送受信兼用アダプティブアレーアンテナ
の他の例を示す図。FIG. 7 is a diagram showing another example of a conventional transmission / reception adaptive array antenna.
───────────────────────────────────────────────────── フロントページの続き (72)発明者 野島 俊雄 東京都千代田区永田町二丁目11番１号 株 式会社エヌ・ティ・ティ・ドコモ内 Ｆターム(参考） 5J021 AA05 AA06 CA06 DB01 FA32 GA01 GA06 GA08 HA03 5K059 CC02 CC03 CC04 DD35 5K067 AA03 CC24 EE10 HH21 KK02 ────────────────────────────────────────────────── ─── Continuing on the front page (72) Inventor Toshio Nojima 2-1-1, Nagatacho, Chiyoda-ku, Tokyo F-term in NTT DoCoMo, Inc. (reference) 5J021 AA05 AA06 CA06 DB01 FA32 GA01 GA06 GA08 GA08 HA03 5K059 CC02 CC03 CC04 DD35 5K067 AA03 CC24 EE10 HH21 KK02
Claims (2)
数比に等しい等比間隔で配列され、 アンテナ素子配列方向において、その全素子数より少な
いが２分の１より多い連続したアンテナ素子が受信用と
され、これら受信用アンテナ素子に対しその素子配列方
向にずらされた、全素子数より少ないが２分の１より多
い連続したアンテナ素子が送信用とされ、少くとも１つ
のアンテナ素子が送受共用とされ、 各受信用アンテナ素子の受信信号に対し、それぞれ指向
特性制御用の重みを与える受信用重み付与回路が設けら
れ、 各送信用アンテナ素子の送信信号に対し、それぞれ指向
特性制御用の重みを与える送信用重み付与回路が設けら
れ、 受信信号から各受信用重み付与回路に与える重みを適応
的に求める重み決定回路を備え、 アンテナ素子配列方向において、その受信用重み付与回
路に与えられた各重みが、上記受信用アンテナ素子配列
と送信用アンテナ素子配列とのずれの関係を保持した状
態で送信用重み付与回路にそれぞれ与えられることを特
徴とするアダプティブアレーアンテナ。A plurality of antenna elements are arranged at equal intervals equal to the transmission / reception carrier frequency ratio. In the antenna element arrangement direction, continuous antenna elements less than the total number of elements but more than half are used for reception. With respect to these receiving antenna elements, continuous antenna elements that are shifted in the element arrangement direction and that are less than the total number but more than half are used for transmission, and at least one antenna element is used for transmission and reception. A reception weighting circuit is provided for assigning a weight for directional control to the reception signal of each reception antenna element, and a directional control weight is assigned to each transmission signal of each transmission antenna element. A weighting circuit for determining the weight of each of the receiving weighting circuits based on the received signal. In the column direction, each weight given to the reception weighting circuit is given to the transmission weighting circuit while maintaining the relationship between the deviation between the reception antenna element array and the transmission antenna element array. An adaptive array antenna characterized by the following.
信搬送波周波数の波長をλｔ、Ｒ＝λｔ／λｒ、上記受
信用アンテナ素子配列と送信用アンテナ素子配列との上
記ずらされたアンテナ素子数をｎ、ｄ＝λｒ／２，σ＝
Ｒ1/nとすると、アンテナ素子配列における中央の隣接
アンテナ素子の間隔はｄであり、これより一方側におけ
る隣接アンテナ素子間隔はその中央から遠去かるに従っ
て、順次σｄ，σ2ｄ，σ3，…とされ、他方側において
ｄ／σ，ｄ／σ2，ｄ／σ3，…とされていることを特徴
とする請求項１記載のアダプティブアレーアンテナ。2. The wavelength of the receiving carrier frequency is λr, the wavelength of the transmitting carrier frequency is λt, R = λt / λr, and the number of shifted antenna elements between the receiving antenna element array and the transmitting antenna element array is n, d = λr / 2, σ =
Assuming that R 1 / n , the distance between adjacent central antenna elements in the antenna element array is d, and the distance between adjacent antenna elements on one side is σd, σ 2 d, σ 3 as the distance from the center increases. 2. The adaptive array antenna according to claim 1, wherein d / σ, d / σ 2 , d / σ 3 ,... On the other side.
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|---|---|---|---|
| JP2000205056A JP3736735B2 (en) | 2000-07-06 | 2000-07-06 | Adaptive array antenna |
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| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP2000205056A JP3736735B2 (en) | 2000-07-06 | 2000-07-06 | Adaptive array antenna |
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| Publication Number | Publication Date |
|---|---|
| JP2002026630A true JP2002026630A (en) | 2002-01-25 |
| JP3736735B2 JP3736735B2 (en) | 2006-01-18 |
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Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP2005244853A (en) * | 2004-02-27 | 2005-09-08 | Kyocera Corp | Adaptive array antenna system, adaptive array antenna control method, and wireless device |
| WO2005091435A1 (en) * | 2004-03-19 | 2005-09-29 | Brother Kogyo Kabushiki Kaisha | Wireless tag communication apparatus |
| JP2006174108A (en) * | 2004-12-16 | 2006-06-29 | Mitsubishi Electric Corp | Array antenna, and its layout method |
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|---|---|---|---|---|
| JPH05199029A (en) * | 1991-07-26 | 1993-08-06 | Alcatel Thomson Espace | Microwave array antenna |
| JPH0758544A (en) * | 1993-08-13 | 1995-03-03 | Nec Corp | Localizer antenna system |
| JPH07273530A (en) * | 1993-11-02 | 1995-10-20 | Thomson Csf | Emission device array antenna |
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPH05199029A (en) * | 1991-07-26 | 1993-08-06 | Alcatel Thomson Espace | Microwave array antenna |
| JPH0758544A (en) * | 1993-08-13 | 1995-03-03 | Nec Corp | Localizer antenna system |
| JPH07273530A (en) * | 1993-11-02 | 1995-10-20 | Thomson Csf | Emission device array antenna |
Cited By (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP2005244853A (en) * | 2004-02-27 | 2005-09-08 | Kyocera Corp | Adaptive array antenna system, adaptive array antenna control method, and wireless device |
| JP4489460B2 (en) * | 2004-02-27 | 2010-06-23 | 京セラ株式会社 | Adaptive array antenna system, adaptive array antenna control method, and radio apparatus |
| WO2005091435A1 (en) * | 2004-03-19 | 2005-09-29 | Brother Kogyo Kabushiki Kaisha | Wireless tag communication apparatus |
| JP2005269403A (en) * | 2004-03-19 | 2005-09-29 | Brother Ind Ltd | Wireless tag communication system |
| US7573389B2 (en) | 2004-03-19 | 2009-08-11 | Brother Kogyo Kabushiki Kaisha | Radio-frequency identification tag communication device |
| JP2006174108A (en) * | 2004-12-16 | 2006-06-29 | Mitsubishi Electric Corp | Array antenna, and its layout method |
| JP4515897B2 (en) * | 2004-12-16 | 2010-08-04 | 三菱電機株式会社 | Array antenna and its placement method |
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| Publication number | Publication date |
|---|---|
| JP3736735B2 (en) | 2006-01-18 |
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