JP2001308617A - Resonator device, oscillator, filter, duplexer and communications apparatus - Google Patents

Abstract

PROBLEM TO BE SOLVED: To provide a resonator device designed to easily improve the strength of coupling between a resonator and an excitation probe, an oscillator capable of obtaining high power, a filter duplexer having less insertion loss, and a communications apparatus using these devices. SOLUTION: In this arrangement, there are formed electrodes 2 and 3 having their own electrode opening sections H faced each other on the top and bottom planes of a board for resonator 1 to build a TE010 mode resonator on the electrode opening sections, then there is formed a coplanar line-structured excitation probe 5 and a stub S on the upper side electrode 2. Between the coupling section of this excitation probe 5 and resonator, there is disposed the excitation probe against the resonator so that the phase difference on the resonator is matched with the one on the excitation probe.

Description

DETAILED DESCRIPTION OF THE INVENTION

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a resonator device having an excitation probe coupled to a resonator, an oscillator, a filter, a duplexer, and a communication device using the same.

[0002]

2. Description of the Related Art FIG. 15 shows an example of the configuration of a resonator device comprising a resonator and a probe provided on a dielectric substrate. FIG. 15 is an exploded perspective view thereof. Here, reference numeral 1 denotes a resonator substrate made of a high dielectric constant dielectric material, and forms an upper electrode 2 and a lower electrode 3 having circular electrode openings Ha and Hb, respectively. With such an electrode structure, the electrode openings Ha and Hb function as a TE010 mode dielectric resonator. Reference numeral 4 denotes a probe substrate made of a low dielectric material, on which excitation probes 5 and 6 made of linear strip conductors are formed. The probe substrate 4 is placed on the upper surface of the resonator substrate 1 and the probe substrate 4
In addition, an upper shield plate 7 and a lower shield plate 8 are arranged at positions separated from the resonator substrate 1 by a predetermined distance.

In the following description, the description of the upper shield plate and the lower shield plate will be basically omitted.

[0004]

In a conventional resonator device which is coupled to a resonator using such a linear excitation probe, a resonator using a TE010 mode and a resonance mode similar thereto is particularly desirable. , When the excitation is performed using an excitation probe with a strip conductor, the phase of the electromagnetic wave propagating in the strip cannot be ignored depending on how the dimensions are selected, and the coupling between the excitation probe and the resonator is weakened. Was caused.
Therefore, it is difficult to obtain a small external Q (Qe),
There is a problem that it is difficult to obtain a low insertion loss filter or a high output oscillator.

SUMMARY OF THE INVENTION An object of the present invention is to provide a resonator device, an oscillator, a filter, a duplexer, and a use thereof which solve the above-mentioned problems by easily increasing the coupling strength between the resonator and the excitation probe. To provide a communication device.

[0006]

The present invention comprises a resonator,
What is claimed is: 1. A resonator device comprising: an excitation probe coupled to a plurality of coupling points with respect to the resonator, wherein a phase difference on the resonator between the plurality of coupling points and an excitation between the plurality of coupling points The resonator and the excitation probe are arranged so that the phase difference on the probe substantially matches. With this structure, when the resonator and the excitation probe are coupled at a plurality of locations, the resonator and the excitation probe are coupled in the same phase, and the degree of coupling between the two is improved.

As the above-mentioned resonator, a TE mode or a quasi-TE mode in which the phase does not change over one round of the electric field vector is used, and the phase difference between the coupling points on the resonator and the excitation probe is electrically substantially reduced. The wavelength is set to one wavelength, and the coupling point of the excitation probe is arranged away from the resonator. If the TE mode or the quasi-TE mode is used, the phase does not change over one round of the resonator.
Only the arrangement of the excitation probe needs to be considered, and the phase difference on the excitation probe is coupled to the resonator at a different interval of approximately one wavelength at the operating frequency, so that an appropriate phase can be taken into account in consideration of the phase on the resonator. Strong coupling is obtained without extending the excitation probe to a position and without unnecessarily lengthening the excitation probe.

A phase shifter is connected between a certain connection point of the excitation probe and another connection point. As a result, the distance on the excitation probe between the coupling points is reduced, and the overall size of the resonator device is reduced.

Further, the phase is adjusted by making the phase shift amount of the phase shifter variable, and as a result, the degree of coupling between the resonator and the excitation probe can be adjusted.

Further, the present invention forms a band reflection type oscillator in which a resonator is strongly coupled by coupling a reflection amplifier circuit to the resonator. This improves the oscillation output.

According to the present invention, a filter or a duplexer is formed by using a structure in which the excitation probe and the resonator are coupled.

Further, the present invention constitutes a communication device including the above-mentioned resonator device, oscillator, filter or duplexer.

[0013]

DESCRIPTION OF THE PREFERRED EMBODIMENTS The structure of a resonator device according to a first embodiment will be described with reference to FIGS. First TE01
FIG. 1 shows the structure of a 0-mode resonator and an example of its resonance mode.
Shown in In FIG. 1, reference numeral 1 denotes a resonator substrate made of a high dielectric constant dielectric material, and an upper electrode 2 having a circular electrode opening H and a lower electrode having a similar electrode opening at a position facing the electrode opening H. 3 are formed respectively.
With such an electrode structure, the electrode opening portion H of the resonator substrate functions as a dielectric resonator. The solid line in the figure indicates the electric field distribution of the TE010 mode, and the broken line indicates the magnetic field distribution. As described above, the electromagnetic field distribution of the TE010 mode is symmetric with respect to the central axis of the resonator. Therefore, the current excited by the magnetic field flows along the circumferential direction of the electrode opening H, and furthermore, The displacement current does not change.

As an excitation probe for exciting an electromagnetic wave to the resonator, a strip line is generally used. When this kind of resonator is handled in the microwave band, the resonator diameter (the inner diameter of the electrode opening H) is usually smaller than the wavelength at the frequency on the strip line,
In a high frequency region such as a millimeter wave, the diameter of the resonator is substantially equal to the wavelength. Therefore, there is a problem that Qe is difficult to take (external coupling is difficult to take). this is,
This is because the current flowing in the strip conductor is a steady current and there is a phase change, whereas the current flowing in the resonator is a displacement current and there is no phase change.

Next, the coupling between the resonator and the strip line will be described. First, TE010 shown in FIG.
The electromagnetic field outside the mode resonator is equivalent to that in which a magnetic dipole moment is placed at the center instead of the resonator as shown in FIG. 2B. Therefore, it is also equivalent to an arrangement in which the loop antenna is arranged at the center such that the normal line on the surface of the loop antenna coincides with the central axis of the resonator.

In consideration of such a model, the strength of coupling between the strip line and the resonator is expressed by the number of interlinkage magnetic fluxes passing through the plane of the loop antenna when a current flows through the strip line. Can be.

Next, consider the case where the loop antenna and the strip lines a, b, and c are coupled as shown in FIG. In FIG. 3, the electromagnetic field propagating through the strip line generates a linkage magnetic flux as shown in FIG. 3, and is coupled to the loop antenna. However, since the current directions of the line a and the line b are reversed, it can be considered that the line b acts to weaken the coupling between the lines a and c and the loop antenna. Therefore, as shown in FIG.
The line b is separated from the loop antenna to form a coarse coupling. Thereby, the overall coupling between the strip line and the loop antenna can be strengthened.

Next, the actual structure and experimental results will be described. FIG. 4 is an exploded perspective view showing the structure of the resonator device.
Here, reference numeral 1 denotes a resonator substrate having a thickness of 1.0 mm and a relative permittivity εr of 30, forming an upper electrode 2 and a lower electrode 3 each having a circular electrode opening H. The upper and lower electrodes 2 and 3 are Au thin film electrodes. Reference numeral 4 denotes a probe substrate on which excitation probes 5 and 6 as strip lines are formed. The resonator substrate is formed by stacking the probe substrate 4 on the upper surface of the resonator substrate 1 and disposing the upper and lower shield plates 7 and 8 above and below the resonator substrate 1 with an interval of 1.0 mm. For this structural parameter, the resonance frequency is 20 GHz
z. In the structure shown in FIG. 4, the excitation probe 5 is coupled to the resonator at two points, and the distance between the coupling points on the excitation probe is one wavelength at the operating frequency.

FIG. 5 is an exploded perspective view of a resonator device as a comparative example of the above-mentioned resonator device. In the example shown in FIG. 5, the excitation probe 5 is coupled to the resonator at three points, and the distance between the coupling points on the excitation probe is a half wavelength at the operating frequency.

FIG. 6 shows the transmission characteristics of the above two resonator devices. Here, a curve drawn with a series of triangular marks indicates the characteristics of the resonator device of FIG. 4, and the other curve indicates the characteristics of the resonator device of FIG. Thus, when the excitation probe having the shape shown in FIG. 4 is used, the coupling degree is higher than when the excitation probe having the shape shown in FIG. can get.

From these results, it can be confirmed that, when the excitation probe is coupled to the resonator at two places on the excitation probe, which are separated by a half wavelength at the operating frequency, the coupling acts in directions weakening each other.

Next, as a second embodiment, FIG. 7 shows examples of various resonance modes and an excitation probe capable of obtaining strong coupling with a resonator of the mode. These figures are top views of the resonator portion. (A) shows the electromagnetic field distribution of the HE11δ mode. (B) shows the arrangement of the excitation probe coupled to the HE11δ mode. At the two coupling points of the excitation probe close to the resonator, the excitation probe is HE
Coupling with 11δ mode magnetic field. Here, the length between the coupling points on the excitation probe is a half wavelength at the operating frequency, and the phase difference between the coupling points on the resonator has a relationship of π radian (opposite phase). Therefore, the phase difference on the resonator between the two coupling points matches the phase difference on the excitation probe, and this excitation probe is strongly coupled to the HE11δ mode.

FIG. 7C shows the electromagnetic field distribution in the HE21δ mode. (D) shows the arrangement of the excitation probe coupled to the HE21δ mode. At three coupling points of the excitation probe close to the resonator, the excitation probe couples with the HE21δ mode magnetic field. The length between two adjacent coupling points on the excitation probe is half a wavelength, and the phase difference between two adjacent coupling points on the resonator has a relationship of π radian (opposite phase). Therefore, the phase difference on the resonator between the two coupling points matches the phase difference on the excitation probe, and this excitation probe is strongly coupled to the HE21δ mode.

Note that in FIGS. 7B and 7D,
One end of the excitation probe is defined as an open end, and the length from the open end to the joint near the open end is approximately 1/4.
The wavelength allows coupling to the resonator at the point where the magnetic field strength is maximum.

Next, the configuration of a resonator device according to a third embodiment will be described with reference to FIGS. 8, 9 and 10. FIG. 8 shows a configuration in which a stub is provided at a predetermined position of the excitation probe. FIG. 9 shows the effect of shortening one wavelength line by the parallel stub. When stubs having open ends are provided at both ends of the line, and the impedance is Z 'and a 1/4 wavelength line is equivalently constructed, as shown in FIG. , Impedance Zs
By connecting a stub having an electrical length of θs and using the stub as a capacitor in a lumped manner, the line length can be reduced to less than １ ／ wavelength. Specifically, the line and the stub may be selected so that the following relationship is satisfied: Zs = Za / sinθ1 / Za = (1 / Z ′ − (1 / Zs) tanθs).

FIG. 8 shows a structure in which the shortened two lines are connected in series to each other by using the central line b shown in FIG.
It is applied to Here, since the center stub is obtained by superposing two stubs, its impedance is Zs / 2. Also, the electrical length θ of the line is equivalent to 波長 wavelength, but since the physical length is shortened,
The space for keeping the predetermined portion of the excitation probe away from the resonator is reduced, and the overall size can be reduced. Also,
Even when the line is coupled to the resonator, energy is transmitted to the stub as compared with the case shown in FIG. 3A, so that the effect of weakening the coupling is suppressed, and strong coupling is obtained as a whole.

As the phase shifter connected between the lines, in addition to the stub, a 90 ° hybrid phase shifter,
An 80 ° hybrid phase shifter, a phase shifter using a circulator, or the like may be used.

FIG. 10 is a diagram showing a specific example of a resonator device for shortening the line length by the stub. In this example, an upper surface electrode 2 and a lower surface electrode 3 having opposing electrode openings H are formed on the upper and lower surfaces of the resonator substrate 1, respectively.
An E010 mode resonator is configured. An excitation probe 5 and a stub S having a grounded coplanar structure are formed on the upper surface electrode 2.

In this example, a land is provided at the tip of the stub S, and the electric length θs of the stub is obtained by removing the electrode of the land or connecting the end of the stub and the land with a wire. And the equivalent line length between the two stubs can be adjusted. As a result, the electrical length between two coupling points of the excitation probe to the resonator is adjusted, and as a result, the degree of coupling (adjustment of Qe) can be adjusted.

FIG. 11 is a perspective view of a main part of a resonator device according to a fourth embodiment. This example is an example in which each stub shown in FIG. 10 is configured by a plurality of stubs. With such a structure, a predetermined number of stubs are cut out of a plurality of branched stubs to thereby reduce the impedance Z of the stub.
s, which, as in the above case,
e can be adjusted.

Next, an example of the configuration of an oscillator according to a fifth embodiment will be described with reference to FIG. FIG. 12 is a perspective view of the main part. Electrodes 2 and 3 having electrode openings facing each other are formed on the upper and lower surfaces of the resonator substrate 1, respectively.
This constitutes a TE010 mode resonator. A portion indicated by reference numeral 10 in the drawing is a substrate superposed on the resonator substrate 1, on which an excitation probe 5 as a main line is formed, and a terminating resistor is provided at one end thereof. The FET is a negative resistance element, and is connected to the other end of the excitation probe 5 to form a reflection amplification circuit. The above resonator is coupled to two locations of the excitation probe 5 separated by a predetermined electrical length. The coupling structure between this resonator and the excitation probe is shown in FIG.
Is the same as that shown in FIG. By configuring a band reflection type oscillator using the line strongly coupled to the resonator in this manner, a high oscillation output and excellent C / N ratio characteristics can be obtained.

If another excitation probe is coupled to the resonator as a sub-line and a variable reactance element is loaded on the excitation probe, a voltage-controlled oscillator whose oscillation frequency changes according to a control voltage applied to the variable reactance element. A VCO can be configured.

Next, as a sixth embodiment, an example of a band-pass filter and a duplexer is shown in FIG. An upper surface electrode 2 having two electrode openings Ha and Hb is formed on the upper surface of the resonator substrate 1, and a lower surface electrode 3 having an electrode opening respectively opposed to the two electrode openings is formed on the lower surface. I have. With this structure, two TE010 mode resonators are formed. Excitation probes 5 and 6 with stubs similar to those shown in FIG. 10 are formed on the upper surface electrode 2. With this structure, the excitation probe 5 is strongly coupled to the resonator generated at the electrode opening Ha, and the excitation probe 6
Strongly couples with the resonator generated in the electrode opening Hb.
The two resonators are magnetically coupled to each other, so that the entire device acts as a band-pass filter in which two resonators are coupled.

As described above, by increasing the degree of coupling between the excitation probe and the resonator, a filter characteristic with low insertion loss is obtained.

Similarly, if a plurality of filters are formed using a single resonator substrate 1 and input / output terminals for antenna connection are provided, a duplexer having a coupling structure between the resonator and the excitation probe is provided. Can be configured.

In the above-described resonator device, an example in which a resonator is formed on a dielectric resonator substrate has been described. However, a dielectric in which a dielectric core or a dielectric pillar having a predetermined shape is disposed in a cavity is used. When coupling the excitation probe to the resonator,
The present invention is similarly applicable. Further, the present invention can be similarly applied to a case where an excitation probe is coupled to a cavity resonator. In the above-described resonator device, an example is shown in which the pattern of the excitation probe is formed on the substrate. However, the present invention can be similarly applied to a case where an excitation probe using a conductor wire or a conductor plate is used.

Next, the configuration of a communication device using the above filter or oscillator will be described with reference to FIG. In FIG. 14, ANT is a transmitting / receiving antenna, DPX is a duplexer, BPFa and BPFb are band-pass filters, respectively.
AMPa and AMPb are amplifier circuits, MIXa and M, respectively.
IXb is a mixer, OSC is an oscillator, SYN
Is a frequency synthesizer, and VCO is a voltage controlled oscillator. MIXa converts the frequency signal output from SYN to VC
The signal is modulated by the output signal IF of O, the BPFa passes only the band of the transmission frequency, and the AMPa
Sent from ANT via X. BPFb allows only the reception frequency band of the signal output from DPX to pass,
MPb amplifies it. MIXb mixes the frequency signal output from the SYN with the received signal and outputs an intermediate frequency signal IF.

The band pass filter BPF shown in FIG.
For a and BPFb, the dielectric filters having the various structures described above can be used. Further, the oscillator having the structure described with reference to FIG. 12 can be used as the voltage controlled oscillator VCO.

In this manner, a communication device having excellent communication performance using the low insertion loss filter and the high C / N ratio oscillator is constructed.

[0040]

According to the present invention, when the resonator and the excitation probe are coupled at a plurality of locations, the resonator and the excitation probe are coupled in the same phase, so that both can be easily and strongly coupled. .

When the TE mode or the quasi-TE mode is used, the phase does not change over one round of the resonator. Therefore, only the arrangement of the excitation probe with respect to the resonator needs to be considered, and the phase difference on the excitation probe is approximately By coupling the resonator to the resonator at a distance different by one wavelength, strong coupling can be easily obtained without unnecessarily lengthening the excitation probe in consideration of the phase on the resonator.

Further, by connecting a phase shifter between a certain coupling point of the excitation probe and another coupling point, the distance on the excitation probe between the coupling points can be reduced, and the entire resonator device can be reduced. It can be easily miniaturized.

Further, by making the phase shift amount of the phase shifter variable and performing phase adjustment, it becomes possible to adjust the degree of coupling between the resonator and the excitation probe.

Further, according to the present invention, a reflection amplifier circuit is coupled to the above-described resonator to form a band reflection type oscillator in which the resonator is strongly coupled, whereby a small-sized oscillator having a high oscillation output can be obtained. .

Further, by configuring a filter and a duplexer having a structure in which the excitation probe and the resonator are coupled, it is possible to easily provide a characteristic with low insertion loss.

Further, by configuring a communication device including the above-described resonator device, oscillator, filter or duplexer, it is possible to configure a communication device having excellent communication performance with low loss and high gain.

[Brief description of the drawings]

FIG. 1 is a diagram showing a configuration of a resonator portion of a resonator device according to a first embodiment.

FIG. 2 is a diagram showing an equivalent configuration of the resonator.

FIG. 3 is a diagram showing a relationship between coupling between the resonator and an excitation probe.

FIG. 4 is an exploded perspective view showing a specific configuration of the resonator device.

FIG. 5 is an exploded perspective view of a resonator device as a comparative example.

FIG. 6 is a diagram showing transmission characteristics of a resonator device;

FIG. 7 is a diagram showing a relationship between a resonance mode of the resonator device according to the second embodiment and an excitation probe.

FIG. 8 is a diagram showing a configuration of an excitation probe of a resonator device according to a third embodiment.

FIG. 9 is a diagram showing a line length shortening effect of a stub of the excitation probe.

FIG. 10 is a perspective view showing a specific configuration example of the resonator device.

FIG. 11 is a perspective view of a resonator device according to a fourth embodiment.

FIG. 12 is a perspective view of an oscillator according to a fifth embodiment.

FIG. 13 is a perspective view of a main part of a filter according to a sixth embodiment.

FIG. 14 is a block diagram showing a configuration of a communication device according to a seventh embodiment.

FIG. 15 is an exploded perspective view showing the configuration of a conventional resonator device.

[Explanation of symbols]

 1-resonator substrate 2-upper surface electrode 3-lower surface electrode 4-probe substrate 5,6-excitation probe 7-upper shield plate 8-lower shield plate 10-substrate H-electrode opening S-stub

 ──────────────────────────────────────────────────続 き Continued on the front page F term (reference) 5J006 HC03 HC12 LA02 NA08 5J012 GA11 5J081 AA11 CC11 CC21 CC42 DD04 EE10 GG06 LL07 MM06 MM09

Claims (8)

[Claims] 1. A resonator device comprising: a resonator; and an excitation probe coupled to the resonator at a plurality of coupling points, wherein a phase difference on the resonator between the plurality of coupling points is provided. A resonator device in which the resonator and the excitation probe are arranged such that a phase difference on the excitation probe between the plurality of coupling points substantially matches. 2. The resonator resonates in a mode in which an electric field vector rotates. The phase does not change over one round of the electric field vector. 2. An excitation probe between coupling points, which is one wavelength, and which is arranged away from the resonator.
3. The resonator device according to claim 1. 3. The resonator device according to claim 1, wherein a phase shifter is connected between coupling points of the excitation probe. 4. The resonator device according to claim 3, wherein a phase shift amount of said phase shifter is variable. 5. An oscillator comprising a reflection amplifier circuit coupled to the excitation probe of the resonator device according to claim 1. 6. A filter comprising the resonator device according to claim 1. 7. A duplexer comprising the resonator device according to claim 1. 8. A communication device comprising the resonator device according to claim 1, the oscillator according to claim 5, the filter according to claim 6, or the duplexer according to claim 7.