JP2001285165A - Radio equipment - Google Patents

Abstract

PROBLEM TO BE SOLVED: To provide a radio equipment for an adaptive array radio base station that can adopt a small-sized reception terminal with low power consumption and high reception quality. SOLUTION: An adaptive array reception section 1030 extracts a signal received from a desired terminal 1100 from signals received by an array antenna 1010 and a frequency offset compensation unit 1032 calculates a frequency offset. In this case, a frequency offset inverse compensation section 1042 applies phase rotation to a transmission signal from a transmission signal modulation section 1040 on the basis of an inverse compensation amount (transmission state phase rotation amount) θOUT and an adaptive antenna transmission section 1044 transmits the resulting signal from the array antenna 1010 to a terminal 1100. The terminal 1100 applies synchronization detection to the signal without recovering a carrier.

Description

DETAILED DESCRIPTION OF THE INVENTION

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a configuration of a radio device used for a base station in radio communication such as a portable telephone, and more particularly to a configuration of compensation control of a frequency offset of a radio device in a base station. .

[0002]

2. Description of the Related Art FIG. 14 shows a portable telephone base station 2000 using a conventional adaptive array and this base station 200.
1 is a schematic block diagram showing a configuration of a communication system including a communication terminal 2100 that performs communication with the communication terminal 2;

Referring to FIG. 14, adaptive array base station 2000 includes a transmitting / receiving section 2002, an adaptive array antenna 2010, and a switch 2020 for switching a path for connecting to adaptive array antenna 2010 in accordance with a transmission / reception mode. Prepare.

The transmitting / receiving section 2002 receives a signal from the adaptive array antenna 2010 in the reception mode, and superimposes a predetermined weight vector on a reception signal from each of the array antennas to extract a signal from a desired direction. An adaptive array receiving unit 2030,
A frequency offset compensator 2032 for performing frequency offset compensation on a signal received from adaptive array unit 2030, and a frequency offset compensator 203
2 and a transmission signal modulation unit 2040 for demodulating a reception signal and a transmission signal modulation unit 2040 for modulating a baseband signal to be transmitted in a transmission mode.
And an adaptive array transmission unit 2042 for receiving an output of the transmission signal modulation unit 2040 and generating a signal to be given to each antenna of the adaptive array antenna 2010 according to the weight vector from the adaptive array reception unit 2030. Including.

That is, in the conventional adaptive array base station 2000, frequency offset compensation is performed on an uplink signal (received signal).

FIG. 15 is a schematic block diagram showing an example of the configuration of adaptive array base station 2000 shown in FIG.

[0007] The configuration shown in FIG. 15 shows the configuration of a transmission / reception unit 2002 for transmitting / receiving data to / from one user, for example.

Therefore, in order to perform transmission and reception with a plurality of users, in order to identify each user, FIG.
A plurality of transmission / reception units 2002 having the configuration shown in FIG.

In the example shown in FIG. 15, four antennas # 1- # 4 are provided to extract a desired user signal from an input signal including a plurality of user signals. Note that, more generally, the array antenna 2010 may be configured with n antennas. FIG.
The switch 2020 shown in FIG.
10 to 10-4.

The signals from the array antennas # 1 to # 4 are
The received weight vector calculator 11 and the multipliers 12-1 to 12-4 are provided via the switch circuits 10-1 to 10-4.

The reception weight vector calculator 11 includes an input signal, a training signal corresponding to a specific user signal stored in advance in a memory (not shown), and an adder 13.
And the weight vectors wrx _{1i to} wrx
Calculate _4i . Here, the subscript i indicates that it is a weight vector used for transmission and reception with the i-th user.

[0012] The multipliers 12-1 to 12-4 are provided with input signals from the antennas # 1 to # 4 and a weight vector wrx _1i.
.. Wrx _4i, and the result is supplied to the adder 13.
The adder 13 adds the output signals of the multipliers 12-1 to 12-4 and outputs the sum as a received signal S _RX (t). The received signal S _RX (t) is also sent to the reception weight vector calculator 11. Given.

The frequency offset compensator 2032 receives the output from the adder 13 and performs offset compensation.
The signal is given to the received signal demodulation unit 2034.

On the other hand, according to the output signal S _TX (t) given from the transmission signal modulator 2040 and the weight vector value from the reception weight vector calculator 11, the weight vector wtx _1i calculated by the transmission weight vector calculator 14 is calculated. Ｗｔwtx _4i are multiplied and output, respectively. Outputs of the multipliers 15-1 to 15-4 are provided to switch circuits 10-1 to 10-4, respectively.

That is, the switch circuits 10-1 to 10-4
When receiving signals, the signals given from adaptive array antennas # 1 to # 4 are multiplied by multipliers 12-1 to 12-1.
2-4, and when transmitting a signal, the multiplier 15-
Signals from 1 to 15-4 are applied to array antennas # 1 to # 4.

[Operation Principle of Adaptive Array]
The operation principle of the transmission / reception unit 2002 shown in FIG. 15 will be briefly described.

In the following, for simplicity of explanation, the number of users PS simultaneously communicating with four antenna elements
To two people. At this time, the signal given to the receiving unit from each antenna is represented by the following equation.

[0018]

(Equation 1)

Here, the signal RX _j (t) is the j-th signal (j
= 1, 2, 3, 4) of indicates the reception signal of the antenna, the signal Srx _i (t) represents a signal transmitted by the user of the i-th (i = 1, 2).

Further, the coefficient h _ji indicates the complex coefficient of the signal from the i-th user received by the j-th antenna, and n _j (t) indicates the noise contained in the j-th received signal. ing.

When the above equations (1) to (4) are expressed in a vector format, they are as follows.

[0022]

(Equation 2)

In the equations (6) to (8), [...] ^T
Indicates transposition of [...]. Here, X (t) indicates an input signal vector, _Hi indicates a received signal coefficient vector of the i-th user, and N (t) indicates a noise vector.

As shown in FIG. 15, the adaptive array antenna multiplies input signals from the respective antennas by weighting factors wrx _{1i to} wrx _ni and outputs a signal as a received signal S _RX (t). (Number of antennas n =
4. Now, with the above preparation, the operation of the adaptive array in the case of extracting the signal Srx ₁ (t) transmitted by the _first user, for example, is as follows.

The output signal of the adaptive array reception unit 2030 y1 (t) is the multiplication of the vector of received weight vector W ₁ and the input signal vector X (t), it can be represented by the following formula.

[0026]

(Equation 3)

That is, the reception weight vector W ₁ is
This is a vector having as an element a weighting coefficient wrx _j1 (j = 1, 2, 3, 4) multiplied by the j-th input signal RX _j (t).

Here, y1 expressed as in equation (9)
Substituting the input signal vector X (t) expressed by equation (5) into (t) yields the following.

[0029]

(Equation 4)

Here, adaptive array receiving section 203
When 0 operates ideally, the weight vector W ₁ is sequentially controlled by the reception weight vector calculator 11 by a known method so as to satisfy the following simultaneous equations.

[0031]

(Equation 5)

When the weight vector W ₁ is completely controlled so as to satisfy the equations (12) and (13), the output signal y 1 (t) from the adaptive array receiver 2030 is obtained.
Is eventually expressed as the following equation.

[0033]

(Equation 6)

That is, by taking the ensemble average, a signal Srx ₁ (t) transmitted by the first user of the two users is obtained as the output signal y1 (t).

On the other hand, in FIG.
Input signal S to the transmission unit 2042_TX(T) is multiplication
Input of one of the units 15-1, 15-2, 15-3, 15-4
Given to. By the reception weight vector calculator 11
Calculated based on the received signal as described above
Weight vector wrx_1i, Wrx_2i, Wrx_3i, Wr
x_4iIs copied to the transmission weight vector calculator 14
And transmitted from the transmission weight vector calculator 14.
Weight vector wtx_1i, Wtx_2i, Wtx _3i, Wt
x_4iAre applied to the other inputs of these multipliers, respectively.
You.

The input signals weighted by these multipliers are applied to the corresponding switches 10-1, 10-2, 10
-3, 10-4, the corresponding antenna {1,}
2, $ 3, $ 4.

Here, identification of the users PS1 and PS2 is performed as described below. That is, the radio signal of the mobile phone is transmitted in a frame configuration. A radio signal of a mobile phone is mainly composed of a preamble composed of a signal sequence known to the radio base station and data (such as voice) composed of a signal sequence unknown to the radio base station.

The signal sequence of the preamble includes a signal sequence of information for identifying whether the user is a desired user to talk to the radio base station. The reception weight vector calculator 11 of the adaptive array radio base station 2000 compares the training signal corresponding to the user PS1 fetched from the memory with the received signal sequence,
Weight vector control (determination of a weight coefficient) is performed so as to extract a signal considered to include a signal sequence corresponding to the user PS1.

[Configuration of Receiving Terminal 2100] In general, the modulation scheme used for transmission and reception in a cellular phone or the like is P
BPSK (Binary PSK) modulation and QPSK (Quadri-PSK), which are modulation schemes based on SK (Phase Shift Keying) modulation
Modulation or the like is used.

In PSK modulation, synchronous detection is generally performed in which detection is performed by integrating a signal synchronized with a carrier into a received signal.

FIG. 16 is a circuit diagram for explaining the configuration of a so-called Costas loop performed for such synchronous detection.

The received signal is supplied to the variable frequency local oscillator 210
2 is multiplied by a multiplier 2104,
The output of the local oscillator 2102 is 90
The signal whose phase is shifted by ° is also multiplied by the multiplier 2108.

The output of the multiplier 2104 passes through a low-pass filter 2110, and the output of the multiplier 2108 passes through a low-pass filter 2112. The result of this multiplication is provided as a control signal for local oscillator 2102.

On the other hand, the output of low-pass filter 2110 is subjected to a positive / negative determination by determiner 2116 to determine the reception level.

In synchronous detection as shown in FIG.
A complex conjugate carrier synchronized with the modulation wave center frequency is generated based on the output of the local oscillator 2102.

However, in mobile communication in which the propagation path fluctuates significantly, it is difficult to locally reproduce a complex conjugate carrier synchronized with the modulated wave center frequency in a receiver. Differential detection is often used.

[Delay Detection in PSK Modulation] FIG.
FIG. 2 is a schematic block diagram showing a configuration for performing such delay detection.

The received signal is first passed through the bandpass filter 22
02, the signal is supplied to a delay unit 2204 having a delay time of one symbol. Bandpass filter 220
2 and the output of delay 2204 are coupled to multiplier 220
After being multiplied by 6, the detection result is output from the low-pass filter 2208 receiving the output of the multiplier 2206.

That is, in the delay detection, a complex conjugate wave of the received signal one symbol before is used instead of a carrier wave that is difficult to reproduce when demodulating the received signal.

Here, in synchronous detection, since a carrier locally reproduced in a receiver is used for demodulation, noise superimposed on a received signal on a propagation path is a signal multiplied by the received signal during such demodulation. Is not included. However, in delay detection, since a multiplication operation for detection is performed using a received signal containing such noise, there is a problem that noise resistance is deteriorated as compared with synchronous detection.

For details of the synchronous detection and the delay detection as described above, see “Digital Modulation / Demodulation Technology for Mobile Communication”, pp. 53-60.

[0052]

Problems to be solved when synchronous detection is performed include the following.

That is, usually, a frequency error called a frequency offset exists in the oscillators on the transmission side and the reception side. Due to this error, on the receiver side, when the received signal is represented on the IQ plane, the position of the received signal point is rotated. Therefore, it is difficult to perform synchronous detection without compensating for the frequency offset.

When performing synchronous detection on the terminal side in mobile communication, it is necessary to provide a device for compensating for the frequency offset on the terminal side, but this increases the size of the terminal. Not preferred.

That is, in a configuration in which frequency offset compensation is performed on the uplink as in the base station 2000 described with reference to FIG. 14, there is a problem that it is not possible to compensate for propagation fluctuation due to fading. For this reason, on the terminal side, it is difficult to reproduce the carrier wave due to the random phase rotation due to fading, so that only the differential detection can be used. Further, when affected by the co-channel interference wave, it is more difficult to recover the carrier wave on the terminal side.

That is, in the configuration of the conventional base station, when performing synchronous detection on the terminal side, frequency offset compensation and fading compensation must be performed on the terminal side.
There is a problem that the terminal device becomes large.

On the other hand, when frequency offset compensation or fading compensation is not performed on the terminal side, synchronous detection cannot be performed due to phase rotation due to frequency offset or random phase rotation due to fading. For this reason,
In the delay detection, there is a problem that the noise resistance is deteriorated.

The present invention has been made to solve the above problems, and an object of the present invention is to improve the reception performance of a terminal device such as small size, low power consumption, and noise resistance. To provide a wireless device used for a wireless base station capable of performing the above.

[0059]

According to a first aspect of the present invention, a radio apparatus receives an array antenna and a signal received from the array antenna, separates a signal from a desired terminal, and compensates for a frequency offset of the received signal. Receiving section, a receiving signal demodulating section for demodulating an output from the receiving section, a transmitting signal modulating section for modulating a transmitting signal, and calculating a frequency offset inverse compensation amount based on a frequency offset of the receiving signal. A transmission unit that compensates the frequency of the signal from the transmission signal modulation unit and supplies a transmission signal to a desired terminal to the array antenna.

According to a second aspect of the present invention, in addition to the configuration of the first aspect, the receiving section multiplies a reception signal from the array antenna by a reception weight vector, thereby obtaining a signal from a desired terminal. An adaptive array receiving section for separating a signal, and a frequency offset compensating section for compensating for a frequency offset of a signal from the adaptive array receiving section and providing the signal to a received signal demodulating section.

According to a third aspect of the present invention, in addition to the configuration of the second aspect of the present invention, the transmitting section determines a frequency offset inverse compensation amount based on the frequency offset amount from the offset compensating section. A compensation offset calculator, a frequency offset decompensator that changes the phase of the output signal of the transmission signal modulator according to the frequency offset decompensation amount, and an output of the frequency offset decompensator based on the reception weight vector. An adaptive array transmission unit that multiplies the calculated transmission weight vector to provide a transmission signal for a desired terminal to the array antenna.

According to a fourth aspect of the present invention, in addition to the configuration of the second aspect of the present invention, the transmitting section determines a frequency offset inverse compensation amount based on the frequency offset amount from the offset compensating section. The compensation offset calculator and the phase of the reception weight vector from the adaptive array receiver are calculated based on the output from the frequency offset inverse compensator and the frequency offset inverse compensator to be changed according to the frequency offset inverse compensation amount. By multiplying the output of the transmission signal modulator by the transmission weight vector
An adaptive array transmission unit that supplies a transmission signal for a desired terminal to the array antenna.

According to a fifth aspect of the present invention, in addition to the configuration of the second aspect of the present invention, the transmission unit determines a frequency offset inverse compensation amount based on the frequency offset amount from the offset compensation unit. A compensation offset calculator, a transmission weight vector calculator that calculates a transmission weight vector based on the reception weight vector from the adaptive array receiver, and a phase of the transmission weight vector from the transmission weight vector calculator, the frequency offset inverse compensation amount. And a frequency offset decompensation unit that multiplies the output of the transmission signal modulation unit and provides a transmission signal for a desired terminal to the array antenna.

According to a sixth aspect of the present invention, in addition to the configuration of the second aspect of the present invention, the transmission unit determines the frequency offset inverse compensation amount based on the frequency offset amount from the offset compensation unit. A compensation offset calculation unit, an adaptive array transmission unit that multiplies the output of the transmission signal modulation unit by a transmission weight vector calculated based on the reception weight vector from the adaptive array reception unit, and a phase of the output of the adaptive array transmission unit. And a frequency offset inverse compensator that changes the frequency offset inverse compensation amount to provide a transmission signal for a desired terminal to the array antenna.

According to a seventh aspect of the present invention, in addition to the configuration of the second aspect of the present invention, the transmitting section determines a frequency offset inverse compensation amount based on the frequency offset amount from the offset compensating section. A compensation offset calculator, an adaptive array transmitter that multiplies the output of the transmission signal modulator by a transmission weight vector calculated based on the reception weight vector from the adaptive array receiver, and superimposed on the output of the adaptive array transmitter. And a frequency up-conversion unit that changes a local oscillation frequency for up-conversion according to the frequency offset reverse compensation amount, and provides a transmission signal for a desired terminal to the array antenna.

According to an eighth aspect of the present invention, in addition to the configuration of the first aspect of the present invention, the receiving section further comprises a receiving weight for compensating a phase of the received signal from the array antenna to compensate for a frequency offset. An adaptive array receiver for separating a signal from a desired terminal by multiplying the vector.

According to a ninth aspect of the present invention, in addition to the configuration of the wireless device of the eighth aspect, the transmitting section determines the frequency offset inverse compensation amount based on the frequency offset amount from the offset compensating section. A compensation offset calculator, a frequency offset decompensator that changes the phase of the output signal of the transmission signal modulator according to the frequency offset decompensation amount, and an output of the frequency offset decompensator based on the reception weight vector. An adaptive array transmission unit that multiplies the calculated transmission weight vector to provide a transmission signal for a desired terminal to the array antenna.

According to a tenth aspect of the present invention, in addition to the configuration of the wireless device according to the eighth aspect, the transmitting section determines the frequency offset inverse compensation amount based on the frequency offset amount from the offset compensating section. The compensation offset calculator and the phase of the reception weight vector from the adaptive array receiver are calculated based on the output from the frequency offset inverse compensator and the frequency offset inverse compensator to be changed according to the frequency offset inverse compensation amount. By multiplying the output of the transmission signal modulator by the transmission weight vector
An adaptive array transmission unit that supplies a transmission signal for a desired terminal to the array antenna.

In the wireless device according to the eleventh aspect, in addition to the configuration of the wireless device according to the eighth aspect, the transmitting unit determines the frequency offset inverse compensation amount based on the frequency offset amount from the offset compensating unit. A compensation offset calculator, a transmission weight vector calculator that calculates a transmission weight vector based on the reception weight vector from the adaptive array receiver, and a phase of the transmission weight vector from the transmission weight vector calculator, the frequency offset inverse compensation amount. And a frequency offset decompensation unit that multiplies the output of the transmission signal modulation unit and provides a transmission signal for a desired terminal to the array antenna.

According to a twelfth aspect of the present invention, in addition to the configuration of the wireless device according to the eighth aspect, the transmitting section determines a frequency offset inverse compensation amount based on the frequency offset amount from the offset compensating section. A compensation offset calculation unit, an adaptive array transmission unit that multiplies the output of the transmission signal modulation unit by a transmission weight vector calculated based on the reception weight vector from the adaptive array reception unit, and a phase of the output of the adaptive array transmission unit. And a frequency offset inverse compensator that changes the frequency offset inverse compensation amount to provide a transmission signal for a desired terminal to the array antenna.

According to a thirteenth aspect of the present invention, in addition to the configuration of the wireless device according to the eighth aspect, the transmitting section determines a frequency offset reverse compensation amount based on the frequency offset amount from the offset compensating section. A compensation offset calculator, an adaptive array transmitter that multiplies the output of the transmission signal modulator by a transmission weight vector calculated based on the reception weight vector from the adaptive array receiver, and superimposed on the output of the adaptive array transmitter. And a frequency up-conversion unit that changes a local oscillation frequency for up-conversion according to the frequency offset reverse compensation amount, and provides a transmission signal for a desired terminal to the array antenna.

[0072]

Embodiment 1 [Configuration of SDMA base station 1000] FIG. 1 shows an SDMA base station 1000 and a receiving terminal 1 according to Embodiment 1 of the present invention.
FIG. 1 is a schematic block diagram illustrating a configuration of a communication system including an H.100.

[0073] The SDMA base station 1000
02, array antenna 1010, and array antenna 1
010 and a switch 1020 for switching the connection between the transmission unit and the reception unit of the transmission / reception unit 1002.

In the receiving operation, the transmitting / receiving section 1002
By receiving a signal from array antenna 1010 and performing an adaptive array operation, terminal 1 of a desired user is
Adaptive array receiving section 1030 for receiving a signal from
And a frequency offset compensator 1032 for compensating for a frequency offset in response to the output from the receiver, and a received signal demodulator 1034 for receiving the output of the frequency offset compensator 1032 and demodulating the received signal.

The SDMA base station 1000 further includes a frequency offset reverse compensation amount calculation unit 1036 for calculating the frequency offset reverse compensation amount based on the phase rotation amount θ _in calculated by the frequency offset compensator 1032;
A transmission signal modulator 1040 for modulating the baseband signal of the transmission signal, and receiving the output of the transmission signal modulator 1040, inversely compensates the frequency offset according to the output from the frequency offset inverse compensation amount calculator 1036. To transmit a signal to the terminal 1100 of a desired user based on the weight vector information from the adaptive array receiving unit 1030 after receiving the output of the frequency offset decompensating unit 1042 and the frequency offset decompensating unit 1042 And an adaptive array transmitting unit 1044 that generates signals to be provided to the array antenna 1010.

FIG. 2 is a schematic block diagram for explaining the configuration of the SDMA base station shown in FIG. 1 in more detail.
FIG. 16 is a diagram to be compared with the configuration of the conventional SDMA base station shown in FIG. 15.

FIG. 2 is a schematic block diagram showing an example of the configuration of transmitting / receiving section 1002 of adaptive array base station 1000 shown in FIG.

The configuration shown in FIG. 2 also shows the configuration of transmission / reception section 1002 for transmitting / receiving one user, for example. Therefore, in order to perform transmission and reception with a plurality of users, a plurality of transmission / reception units 1002 having a configuration as shown in FIG. 2 are provided in parallel in order to identify each user.

Referring to FIG. 2, transmitting / receiving section 1002 includes
In order to extract a desired user signal from an input signal including a plurality of user signals, four antennas # 1 to # 4 are provided. Note that, more generally, the array antenna 2010 may be configured with n antennas. The switch 2020 shown in FIG. 14 includes switch circuits 10-1 to 10-4.

Signals from array antennas # 1 to # 4 are
The received weight vector calculator 11 and the multipliers 12-1 to 12-4 are provided via the switch circuits 10-1 to 10-4. The reception weight vector calculator 11 includes an input signal and a training signal corresponding to a specific user signal stored in advance in a memory (not shown) and an adder 13.
And the weight vectors wrx _{1i to} wrx
Calculate _4i . Here, the subscript i indicates that it is a weight vector used for transmission and reception with the i-th user.

Multipliers 12-1 to 12-4 respectively provide input signals from antennas # 1 to # 4 and weight vector wrx _1i
.. Wrx _4i, and the result is supplied to the adder 13.
The adder 13 adds the output signals of the multipliers 12-1 to 12-4 and outputs the sum as a received signal S _RX (t). The received signal S _RX (t) is also sent to the reception weight vector calculator 11. Given.

The frequency offset compensator 1032 receives the output from the adder 13 and performs offset compensation.
In addition to the received signal demodulation unit 1034, the phase offset amount θin of the received signal and the phase rotation amount Δθ per symbol of the received signal are calculated by the frequency offset inverse compensation amount calculation unit 103.
6 is output. Frequency offset inverse compensation amount calculation unit 103
6, based on the received phase rotation amount theta _in the phase rotation amount [Delta] [theta], when sending the phase rotation amount (frequency offset reverse compensation amount) is calculated theta _out.

On the other hand, transmission signal modulating section 1040 modulates the applied signal and outputs it as output signal S _TX (t). The frequency offset inverse compensator 1042 outputs the output signal S
The phase of _TX (t) is shifted by the phase rotation amount during transmission (frequency offset reverse compensation amount) θout and output.

The multipliers 15-1 to 15-4 are provided with weight vectors wtx _{1i to} wtx _4i calculated by the transmission weight vector calculator 14 in accordance with the weight vector value from the reception weight vector calculator 11, and a frequency offset inverse compensator. And the output of the controller 1042. Outputs of the multipliers 15-1 to 15-4 are provided to switch circuits 10-1 to 10-4, respectively.

That is, the switch circuits 10-1 to 10-4
When receiving signals, the signals given from adaptive array antennas # 1 to # 4 are multiplied by multipliers 12-1 to 12-1.
2-4, and when transmitting a signal, the multiplier 15-
Signals from 1 to 15-4 are applied to array antennas # 1 to # 4.

Therefore, the configuration of SDMA base station 1000 according to the first embodiment shown in FIG. 2 is based on frequency offset reverse compensation amount calculation for calculating the frequency offset reverse compensation amount upon receiving the output from frequency offset compensator 1032. Unit 1036 and the frequency offset inverse compensation amount calculating unit 10
36, a frequency offset decompensator 1 for performing a phase rotation corresponding to the frequency offset decompensation amount on the signal from the transmission signal modulating unit 1040 based on the calculation result of 36.
042 is different from the configuration of the conventional SDMA base station 2000 shown in FIG.

When adaptive array reception is performed in the adaptive array base station as shown in FIG. 2, the adaptive array receives the received SINR (Signal to Interferor).
ence and noise ratio), so that the effects of fading and co-channel interference can be reduced. At this time, since the transmission is performed using the weight determined at the time of base station reception, the effect of reducing the effects of fading and co-channel interference is similarly obtained on terminal 1100 side.

Next, the operation of the frequency offset inverse compensation amount calculator 1036 shown in FIG. 2 will be described in further detail.

In base station 1000, frequency offset compensation amount θ _in (phase rotation amount) and phase rotation amount Δθ (n) per symbol calculated by frequency offset compensator 1032, and frequency offset inverse compensation amount calculation unit 1036 frequency offset reverse compensation amount calculated for the relation between (transmission-time phase rotation amount) theta _out will be described below by.

Frequency offset inverse compensation amount calculator 1036
The phase rotation amount θ from the frequency offset compensator 1032
_in , the phase rotation amount Δθ (n) per symbol is input (n is an integer: symbol number).

The phase rotation amount θ _in may be input to the frequency offset inverse compensation amount calculator 1036 at an arbitrary position _in the frame. Frequency offset inverse compensation amount calculator 103
In step 6, the amount of inverse compensation θ _out is calculated based on the following equation.

[0092]

(Equation 7)

Here, k is a symbol number when θ _in is input, and N is a symbol number when θ _out is output.

Also, θ _in is the value at the head of the frame (θ _in =
0), the input of θ _in becomes unnecessary, and the amount of inverse compensation θ
_out is represented by the following equation.

[0095]

(Equation 8)

In particular, the phase rotation amount Δθ per symbol
If (t) is time-invariant, then Δθ (t) = Δθ
, The inverse compensation amount θ _out is expressed as follows.

[0097]

(Equation 9)

Based on the frequency offset inverse compensation amount calculated as described above, a signal whose frequency offset has been compensated for a transmission signal is transmitted from the array antenna to the terminal 1.
Sent to 100. When the time at the time of reception and the time at the time of transmission are distant, for example, using an extrapolation technique
Calculate _out .

FIG. 3 is a schematic block diagram showing an example of the configuration of the detection circuit of terminal 1100 shown in FIG.

The signal received at terminal 1100 is
The signal from the local oscillator 1102 is multiplied by a multiplier 1104 and applied to a low-pass filter 1106.

By determining whether output level from low-pass filter 1106 is positive or negative, determination section 1108 makes terminal 1100 determine the level of the received signal.

As shown in FIG. 3, although terminal 1100 performs synchronous detection, it is not necessary for receiving terminal 1100 to perform carrier recovery.

Therefore, a comparison between the case where synchronous detection is performed on the receiving terminal 1100 side without performing carrier recovery and the case where delay detection as described in FIG. 17 is performed will be compared below.

On the base station side, fading and co-channel interference wave compensation are performed in advance by performing transmission using an adaptive array.
To perform frequency offset reverse compensation by
Even when the terminal performs synchronous detection without carrier recovery, it is possible to obtain reception characteristics equivalent to those of synchronous detection with carrier recovery.

In the delay detection, the error rate and the like are deteriorated as compared with the synchronous detection. Therefore, the terminal 1100 can be downsized while suppressing the error rate as compared with the case where the conventional delay detection is performed. . Also, the carrier recovery circuit is connected to the terminal 110.
Since there is no need to provide on the 0 side, power consumption in the terminal 1100 is also reduced.

[Modification of First Embodiment] FIG. 4 is a schematic block diagram showing a modification of the configuration of SDMA base station 1000 of the first embodiment shown in FIG.

The difference from the configuration shown in FIG. 2 is that the reception weight vector calculator 16 uses the array antenna # 1
When calculating the weight vector based on the signals from # 4 to # 4, the phase rotation amount θ _in of the received signal is estimated.

In response, the frequency offset inverse compensation amount calculator 1036 calculates the inverse compensation amount θ _out based on the phase rotation amount θ _in given from the reception weight vector calculator 16.
Is calculated.

The other configuration is the same as the configuration of SDMA base station 1000 of Embodiment 1 shown in FIG.
The same portions are denoted by the same reference characters, and description thereof will not be repeated.

[Second Embodiment] FIG. 5 is a schematic block diagram for describing a configuration of transmitting / receiving section 1200 of an SDMA base station according to a second embodiment of the present invention, and is a diagram compared with FIG. .

The difference from the configuration of the SDMA base station 1000 of the first embodiment shown in FIG. 2 is that the reception weight vector calculated by the reception weight vector calculator 11 is replaced with the inverse weight calculated by the frequency offset inverse compensation calculator 1036. After giving the phase rotation for the compensation amount (the phase rotation amount at the time of transmission) θ _out by the frequency offset inverse compensator 1042,
The point is that the configuration is given to the transmission weight vector calculator 14.

That is, S in the first embodiment shown in FIG.
In the configuration of the DMA base station 1000, the frequency offset inverse compensator 1042 gives the signal from the transmission signal modulator 1040 a phase rotation of the amount of the inverse compensation θ _out, and then gives the signal to the adaptive array transmitter. On the other hand, in the transmitting / receiving section 1200 of the SDMA base station according to the second embodiment shown in FIG. 5, instead of directly applying the phase rotation of the reverse compensation amount to the output from the transmission signal modulating section 1040, The point is that the phase amount of the transmission weight vector output from the transmission weight vector calculator 14 is rotated by the inverse compensation amount.

The configuration shown in FIG. 5 can provide the same effect as the configuration shown in FIG. [Modification of Second Embodiment] FIG. 6 is a schematic block diagram showing a transmitting / receiving section 1200 'of a modification of the transmitting / receiving section 1200 of the SDMA base station according to the second embodiment of the present invention.

The difference from the configuration of the SDMA base station of the second embodiment shown in FIG. 5 is that the phase rotation amount θ _in of the received signal and the phase rotation amount Δθ per symbol are based on the output from adder 13. This is a point that the reception weight vector calculator 16 does not perform the calculation but calculates based on the signals from the array antennas # 1 to # 4.

Other points are the same as those of the second embodiment shown in FIG.
Is the same as that of SDMA base station 1200, and the same portions are denoted by the same reference characters and description thereof will not be repeated.

[Embodiment 3] FIG. 7 is a schematic block diagram for describing a configuration of transmitting / receiving section 1300 of an SDMA base station according to Embodiment 3 of the present invention, and is a diagram compared with FIG. .

The difference from the configuration of the transmitting / receiving section 1200 of the SDMA base station of the second embodiment shown in FIG. 5 is that the transmitting / receiving section 1200 of the second embodiment is based on the output from the frequency offset inverse compensation calculator 1036. 7, the frequency offset inverse compensator 1042 applies a phase rotation to the reception weight from the reception weight vector calculator 11 and then applies the phase rotation to the transmission weight vector calculator 15. In SDMA base station 1300 of mode 3, frequency offset inverse compensator 1042 gives phase rotation to the transmission weight vector output from transmission weight vector calculator 14 based on the output from frequency offset inverse compensation amount calculator 1036. In addition, the configuration is such that the configuration is applied to the multipliers 15-1 to 15-4. .

Other points are the same as those of the second embodiment shown in FIG.
Is the same as that of the SDMA base station, and the same portions are denoted by the same reference characters and description thereof will not be repeated.

[Modification of Third Embodiment] FIG. 8 is a block diagram showing a transmitting / receiving section 130 of the SDMA base station according to the third embodiment shown in FIG.
It is a schematic block diagram which shows the structure of the transmission / reception part 1300 'of the modification of No. 0.

The configuration of the SDMA base station shown in FIG. 8 differs from the configuration of transmission / reception section 1300 of the SDMA base station shown in FIG. Phase rotation θ _in and 1
Instead of calculating the amount of phase rotation per symbol Δθ,
The reception weight vector calculator 16 is configured to calculate a frequency offset value, that is, a phase rotation amount θ _in and a phase rotation amount Δθ per symbol, based on the reception signals from the array antennas # 1 to # 4. It is a point.

Other points are the same as those of the third embodiment shown in FIG.
Is the same as the configuration of SDMA base station 1300, the same portions are denoted by the same reference characters and description thereof will not be repeated.

[Embodiment 4] FIG. 9 is a schematic block diagram illustrating a configuration of an SDMA base station 1400 according to Embodiment 4 of the present invention, and is a block diagram of Embodiment 2 of the present invention shown in FIG. 21 is a diagram contrasted with the configuration of the SDMA base station 1200 of FIG.

In the transmitting / receiving section 1200 of the SDMA base station according to the second embodiment shown in FIG. 5, based on the output from the frequency offset inverse compensation calculator 1036, the data is transferred from the receiving weight vector calculator 11 to the transmitting weight vector calculator 15. The frequency offset inverse compensator 1042 is configured to apply a phase rotation to the received weight, whereas the transmitting / receiving section 1400 of the SDMA base station according to the fourth embodiment shown in FIG. 11 is transmitted directly to the transmission weight vector calculator 15 from the multipliers 15-1 to 15-4 based on the transmission phase rotation amount θ _out given from the frequency offset inverse compensation amount calculator 1036. The frequency offset decompensator 1042 gives phase rotation to the signal, Is a point that has a configuration to be supplied to the switch 10-1 to 10-4.

Other points are the same as those of the second embodiment shown in FIG.
Since the configuration is the same as that of transmitting / receiving section 1200 of the SDMA base station, the same portions are denoted by the same reference characters and description thereof will not be repeated.

[Modification of Embodiment 4] FIG.
The transmitting and receiving unit 14 of the SDMA base station according to the fourth embodiment shown in FIG.
It is a schematic block diagram for demonstrating the structure of the transmission / reception part 1400 'of the modification of 00.

The difference from the configuration of the transmitting / receiving section 1400 of the SDMA base station according to the fourth embodiment shown in FIG.
From the frequency offset compensator 203
2 calculates the phase rotation amount θ _in and the phase rotation amount Δθ per symbol, but the reception weight vector calculator 16 calculates the phase rotation amount of the reception signal based on the signals from the array antennas # 1 to # 4. The point is that θ _in and the phase rotation amount Δθ per symbol are calculated and provided to the frequency offset inverse compensation amount calculator 1036.

Other points are the same as those of the fourth embodiment shown in FIG.
Since the configuration is the same as that of transmitting / receiving section 1400 of the SDMA base station, the same portions are denoted by the same reference characters and description thereof will not be repeated.

[Fifth Embodiment] FIG. 11 is a schematic block diagram illustrating a configuration of an SDMA base station 1500 according to a fifth embodiment of the present invention.

The difference from the configuration of SDMA base station 1000 of Embodiment 1 shown in FIG. 1 is based on phase rotation amount θ _in output from frequency offset compensator 1032 and phase rotation amount Δθ per symbol. The frequency offset compensation amount calculator 1038 calculates the frequency offset amount Δf instead of the transmission phase rotation amount θ _out , and the frequency offset compensation unit 1046 receives the output from the transmission signal modulation unit 1040 accordingly. In this case, the frequency offset is compensated for and then provided to the adaptive array transmitting section 1044.

Other points are the same as those of the first embodiment shown in FIG.
Is the same as that of SDMA base station 1000, and therefore, the same portions are denoted by the same reference characters and description thereof will not be repeated.

FIG. 12 is a block diagram for describing the configuration of SDMA base station 1500 shown in FIG. 11 in more detail.

Referring to FIG. 12, in frequency offset compensation amount calculator 1038, frequency offset amount Δf
Is calculated according to a procedure described later, and is provided to the oscillation frequency control device 32 in the frequency up-conversion unit 30.

The frequency up-conversion unit includes a multiplier 15
It receives baseband frequency signals from -1 to 15-4 and performs processing for converting the signals to RF frequencies. Therefore, although the frequency up-conversion unit 30 originally exists in the configuration shown in FIGS.
10 to 10 are not shown.

The oscillation frequency control device 32 responds to the frequency offset amount Δf from the frequency offset compensation amount calculator 1038 as described above in addition to the transmission frequency information which is a control signal for up-converting to a predetermined RF frequency. Thus, the oscillation frequency of the oscillator 34 is controlled.

The oscillator 34 converts the signals of the frequency controlled by the oscillation frequency control device into multipliers 36-1 to 36-36, respectively.
-4.

The signals from the multipliers 15-1 to 15-4 are
Signals from the oscillator 34 are multiplied by the multipliers 36-1 to 36-4, respectively, and supplied to the array antennas # 1 to # 4 as RF frequency signals.

Next, the frequency offset compensation amount calculator 10
The operation of 38 will be described in more detail.

Frequency offset compensation amount calculator 1038
Calculates the frequency offset Δf (n) at the n-th symbol according to the following equation.

[0139]

(Equation 10)

Here, T is the period of one symbol. In this way, by directly fine-tuning the control voltage of the transmitter 34 of the up-converting unit 30 in the base station 1500, it is possible to compensate for the frequency offset between the base station and the terminal regardless of whether it is going up or down.

[Modification of Embodiment 5] FIG.
FIG. 21 is a schematic block diagram for explaining a transmitting / receiving section 1502 ′ of a modified example of the transmitting / receiving section 1502 of the SDMA base station 1500 according to the fifth embodiment shown in FIG.

The difference from the configuration of SDMA base station 1500 of the fifth embodiment shown in FIG. 12 is that frequency offset compensator 1032 outputs phase rotation amount θ _in and phase per symbol based on output from adder 13. Rotation amount Δθ
Is calculated, but the phase rotation amount delta θ per symbol is calculated directly from the signals from the array antennas # 1 to # 4 in the reception weight calculator 16.

Since the other points are the same as those of the configuration of the SDMS base station of the fifth embodiment shown in FIG. 12, the same portions are denoted by the same reference characters and description thereof will not be repeated.

The embodiments disclosed this time are to be considered in all respects as illustrative and not restrictive. The scope of the present invention is defined by the terms of the claims, rather than the description above, and is intended to include any modifications within the scope and meaning equivalent to the terms of the claims.

[0145]

As described above, according to the present invention, the adaptive array base station performs inverse compensation in advance in the adaptive array base station and performs adaptive array transmission even in mobile communication in which the fluctuation of propagation is severe.
The transmission radio wave in which the fading is reduced and the frequency offset is compensated is given to the receiving terminal, so that the receiving terminal can perform synchronous detection with a simple configuration. In addition, with adaptive array transmission,
The transmission and reception characteristics are greatly improved because the transmission is less affected by co-channel interference waves.

As described above, since the configuration of the receiving terminal can be simplified, the quality of the downlink signal can be improved without complicating (enlarging) the receiving terminal.

[Brief description of the drawings]

FIG. 1 is a schematic block diagram illustrating a configuration of a communication system including an SDMA base station 1000 and a receiving terminal 1100 according to a first embodiment.

FIG. 2 is a schematic block diagram for describing the configuration of the SDMA base station shown in FIG. 1 in more detail.

FIG. 3 is a schematic block diagram illustrating an example of a configuration of a detection circuit of terminal 1100 illustrated in FIG.

FIG. 4 is a schematic block diagram showing a modification of the configuration of the SDMA base station 1000 according to the first embodiment shown in FIG.

FIG. 5 is a schematic block diagram illustrating a configuration of a transmitting / receiving section 1200 of an SDMA base station according to Embodiment 2 of the present invention.

FIG. 6 shows a transmitting / receiving section 1 of the SDMA base station according to the second embodiment.
FIG. 20 is a schematic block diagram showing a transmitting / receiving section 1200 ′ of a modified example of 200.

FIG. 7 is a schematic block diagram illustrating a configuration of a transmitting / receiving section 1300 of an SDMA base station according to a third embodiment of the present invention, and is a diagram compared with FIG.

FIG. 8 shows a transmitting / receiving section 1 of an SDMA base station according to a third embodiment.
It is a schematic block diagram which shows the structure of the transmission / reception part 1300 'of the modification of 300.

FIG. 9 is a schematic block diagram illustrating a configuration of an SDMA base station 1400 according to a fourth embodiment.

FIG. 10 is a schematic block diagram illustrating a configuration of a transmitting / receiving section 1400 ′ of a modification of the transmitting / receiving section 1400 of the SDMA base station according to the fourth embodiment.

FIG. 11 is an SDMA base station 1 according to a fifth embodiment of the present invention.
FIG. 3 is a schematic block diagram for explaining the configuration of the 500.

FIG. 12 is a block diagram for describing a configuration of SDMA base station 1500 shown in FIG. 11 in more detail.

FIG. 13 is a schematic block diagram for explaining a transmitting / receiving section 1502 ′ of a modified example of the transmitting / receiving section 1502 of the SDMA base station 1500 according to the fifth embodiment.

FIG. 14 is a schematic block diagram showing a configuration of a communication system including a conventional mobile phone base station 2000 using an adaptive array and a communication terminal 2100 that performs communication with the base station 2000.

15 is a schematic block diagram illustrating an example of a configuration of an adaptive array base station 2000 illustrated in FIG.

FIG. 16 is a circuit diagram illustrating a configuration of a so-called Costas loop performed for synchronous detection.

FIG. 17 is a schematic block diagram showing a configuration for performing differential detection.

[Explanation of symbols]

10-1 to 10-4 switch, 11 reception weight vector calculator, 12-1 to 12-4 multiplier, 13 adder, 14 transmission weight vector calculator, 15-1 to
15-4 multiplier, 16 reception weight vector calculator, 30 up-converter, 32 oscillation frequency controller, 34 oscillator, 36-1 to 36-4 multiplier, 10
00,1500 SDMA base station, 1002,1002
', 1200, 1200', 1300, 1300 ', 1
400, 1400 ', 1502, 1502' transmitting / receiving section, 1010 array antenna, 1020 switch circuit, 1030 adaptive array receiving section, 1032
Frequency offset compensator, 1034 reception signal demodulation unit,
1036 Frequency offset inverse compensation amount calculation unit, 1040
Transmission signal modulator 1042 Frequency offset decompensator 1044 Adaptive array transmitter 1100
Terminal.

──────────────────────────────────────────────────続 き Continued on the front page (51) Int.Cl. ⁷ Identification symbol FI Theme coat ゛ (Reference) H04J 3/00 H04J 15/00 5K067 15/00 H04L 27/18 Z H04L 27/36 H04B 7/26 B 27 / 18 H04L 27/00 F 27/22 27/22 F F term (reference) 5J021 AA05 AA06 CA06 DB02 DB03 DB04 EA04 FA05 FA17 FA20 FA26 FA29 FA31 FA32 GA02 HA05 HA10 5K004 AA05 FA03 FA05 FE00 FF00 FG00 FJ16 5K022 AA04 AA10A FF01 FF02 FF04 5K028 AA07 BB06 CC03 HH02 HH03 NN31 TT02 5K059 AA08 BB08 CC03 CC04 DD33 DD37 5K067 AA02 BB04 EE02 EE10 KK02 KK03

Claims (13)

[Claims] An array antenna, a receiving unit for receiving a signal received from the array antenna, separating a signal from a desired terminal, and compensating for a frequency offset of the received signal, A reception signal demodulation unit for demodulating an output, a transmission signal modulation unit for modulating a transmission signal, and calculating a frequency offset inverse compensation amount based on a frequency offset of the reception signal. A transmission unit for compensating the frequency of the signal and providing a transmission signal to the desired terminal to the array antenna. 2. An adaptive array receiving section for separating a signal from a desired terminal by multiplying a received signal from the array antenna by a received weight vector, wherein the adaptive array receiving section 2. The radio apparatus according to claim 1, further comprising: a frequency offset compensating unit that compensates for a frequency offset of the signal and supplies the frequency offset to the received signal demodulation unit. 3. The transmission unit, comprising: a frequency inverse compensation offset calculation unit that calculates a frequency offset inverse compensation amount based on the frequency offset amount from the offset compensation unit; and a phase of an output signal of the transmission signal modulation unit. A frequency offset decompensation unit to be changed according to the frequency offset decompensation amount; and multiplying an output of the frequency offset decompensation unit by a transmission weight vector calculated based on the reception weight vector. The wireless device according to claim 2, further comprising: an adaptive array transmitting unit that supplies a transmission signal for the terminal to the array antenna. 4. The transmission unit, comprising: a frequency inverse compensation offset calculating unit for obtaining a frequency offset inverse compensation amount based on the frequency offset amount from the offset compensating unit; and a reception weight vector of the reception weight vector from the adaptive array receiving unit. A phase, a frequency offset inverse compensation unit that changes in accordance with the frequency offset inverse compensation amount, and a transmission weight vector calculated based on an output from the frequency offset inverse compensation unit, an output of the transmission signal modulation unit. The radio apparatus according to claim 2, further comprising: an adaptive array transmission unit that multiplies the transmission signal for the desired terminal to the array antenna. 5. The transmission unit, comprising: a frequency inverse compensation offset calculating unit that determines a frequency offset inverse compensation amount based on the frequency offset amount from the offset compensating unit; and a reception weight vector from the adaptive array receiving unit. A transmission weight vector calculation unit that calculates a transmission weight vector based on the transmission weight vector from the transmission weight vector calculation unit, and changes the phase of the transmission weight vector in accordance with the frequency offset inverse compensation amount, and outputs the transmission signal modulation unit. The wireless device according to claim 2, further comprising: a frequency offset decompensation unit that gives a transmission signal to the desired terminal to the array antenna by multiplying. 6. The transmission unit, comprising: a frequency inverse compensation offset calculating unit that calculates a frequency offset inverse compensation amount based on the frequency offset amount from the offset compensating unit; and a receiving weight vector from the adaptive array receiving unit. An adaptive array transmitting unit that multiplies the transmission weight vector calculated based on the output of the transmission signal modulating unit, and changing the phase of the output of the adaptive array transmitting unit according to the frequency offset inverse compensation amount. The radio apparatus according to claim 2, further comprising: a frequency offset decompensation unit that supplies a transmission signal to the desired terminal to the array antenna. 7. The transmission unit, comprising: a frequency inverse compensation offset calculating unit that calculates a frequency offset inverse compensation amount based on the frequency offset amount from the offset compensating unit; and a receiving weight vector from the adaptive array receiving unit. An adaptive array transmitting unit that multiplies an output of the transmission signal modulating unit by a transmission weight vector calculated based on the local weighting frequency, and a local oscillation frequency for up-converting by superimposing on an output of the adaptive array transmitting unit, the frequency offset. The radio apparatus according to claim 2, further comprising: a frequency up-converting unit that changes a transmission signal for the desired terminal to the array antenna by changing according to an amount of reverse compensation. 8. The receiving unit for separating a signal from a desired terminal by multiplying a reception signal from the array antenna by a reception weight vector whose phase has been compensated for compensating for a frequency offset. The wireless device according to claim 1, further comprising: an adaptive array receiving unit. 9. The transmission unit, comprising: a frequency inverse compensation offset calculating unit that determines a frequency offset inverse compensation amount based on the frequency offset amount from the offset compensating unit; and a phase of an output signal of the transmission signal modulation unit. A frequency offset decompensation unit to be changed according to the frequency offset decompensation amount; and multiplying an output of the frequency offset decompensation unit by a transmission weight vector calculated based on the reception weight vector. The radio apparatus according to claim 8, further comprising: an adaptive array transmission unit that supplies a transmission signal to the array antenna to the array antenna. 10. The transmission unit, comprising: a frequency inverse compensation offset calculating unit for obtaining a frequency offset inverse compensation amount based on the frequency offset amount from the offset compensating unit; and a reception weight vector of the reception weight vector from the adaptive array receiving unit. A phase, a frequency offset inverse compensation unit that changes in accordance with the frequency offset inverse compensation amount, and a transmission weight vector calculated based on an output from the frequency offset inverse compensation unit, an output of the transmission signal modulation unit. The radio apparatus according to claim 8, further comprising: an adaptive array transmission unit that multiplies the transmission signal for the desired terminal to the array antenna. 11. The transmission unit, comprising: a frequency inverse compensation offset calculating unit for obtaining a frequency offset inverse compensation amount based on the frequency offset amount from the offset compensating unit; and a receiving weight vector from the adaptive array receiving unit. A transmission weight vector calculation unit that calculates a transmission weight vector based on the transmission weight vector from the transmission weight vector calculation unit, and changes the phase of the transmission weight vector in accordance with the frequency offset inverse compensation amount, and outputs the transmission signal modulation unit. The radio apparatus according to claim 8, further comprising: a frequency offset decompensation unit that multiplies the transmission signal for the desired terminal to the array antenna. 12. The transmission unit, comprising: a frequency inverse compensation offset calculating unit for obtaining a frequency offset inverse compensation amount based on the frequency offset amount from the offset compensating unit; and a receiving weight vector from the adaptive array receiving unit. An adaptive array transmitting unit that multiplies the transmission weight vector calculated based on the output of the transmission signal modulating unit, and changing the phase of the output of the adaptive array transmitting unit according to the frequency offset inverse compensation amount. The radio apparatus according to claim 8, further comprising: a frequency offset decompensation unit that supplies a transmission signal to the desired terminal to the array antenna. 13. The transmission unit, comprising: a frequency inverse compensation offset calculating unit for obtaining a frequency offset inverse compensation amount based on the frequency offset amount from the offset compensating unit; and a receiving weight vector from the adaptive array receiving unit. An adaptive array transmitting unit that multiplies an output of the transmission signal modulating unit by a transmission weight vector calculated based on the local weighting frequency, and a local oscillation frequency for up-converting by superimposing on an output of the adaptive array transmitting unit, the frequency offset. 9. The radio apparatus according to claim 8, further comprising: a frequency up-converting unit that changes a transmission signal for the desired terminal to the array antenna by changing according to an amount of reverse compensation.