GB2492495A - Quadrature downconversion of non-contiguous carrier aggregation signals - Google Patents

Quadrature downconversion of non-contiguous carrier aggregation signals Download PDF

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Publication number
GB2492495A
GB2492495A GB201215802A GB201215802A GB2492495A GB 2492495 A GB2492495 A GB 2492495A GB 201215802 A GB201215802 A GB 201215802A GB 201215802 A GB201215802 A GB 201215802A GB 2492495 A GB2492495 A GB 2492495A
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Prior art keywords
radio frequency
text
receiver
quadrature components
inphase
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GB201215802A
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GB201215802D0 (en
GB2492495B (en
Inventor
Jouni Kristian Kaukovuori
Aarno Tapio Pa Rssinen
Antti Oskari Immonen
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Renesas Electronics Corp
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Renesas Mobile Corp
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Priority claimed from GBGB1119888.4A external-priority patent/GB201119888D0/en
Application filed by Renesas Mobile Corp filed Critical Renesas Mobile Corp
Publication of GB201215802D0 publication Critical patent/GB201215802D0/en
Priority to US13/677,776 priority Critical patent/US8483647B2/en
Priority to CN201280056648.XA priority patent/CN103947121A/en
Priority to PCT/IB2012/056440 priority patent/WO2013072864A1/en
Publication of GB2492495A publication Critical patent/GB2492495A/en
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Publication of GB2492495B publication Critical patent/GB2492495B/en
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    • HELECTRICITY
    • H04ELECTRIC COMMUNICATION TECHNIQUE
    • H04BTRANSMISSION
    • H04B1/00Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
    • H04B1/06Receivers
    • H04B1/16Circuits
    • H04B1/26Circuits for superheterodyne receivers
    • H04B1/28Circuits for superheterodyne receivers the receiver comprising at least one semiconductor device having three or more electrodes
    • HELECTRICITY
    • H04ELECTRIC COMMUNICATION TECHNIQUE
    • H04LTRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L27/00Modulated-carrier systems
    • H04L27/26Systems using multi-frequency codes
    • H04L27/2601Multicarrier modulation systems
    • H04L27/2647Arrangements specific to the receiver only
    • HELECTRICITY
    • H04ELECTRIC COMMUNICATION TECHNIQUE
    • H04LTRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
    • H04L5/00Arrangements affording multiple use of the transmission path
    • H04L5/0001Arrangements for dividing the transmission path
    • H04L5/0003Two-dimensional division
    • H04L5/0005Time-frequency
    • H04L5/0007Time-frequency the frequencies being orthogonal, e.g. OFDM(A), DMT
    • H04L5/001Time-frequency the frequencies being orthogonal, e.g. OFDM(A), DMT the frequencies being arranged in component carriers

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  • Engineering & Computer Science (AREA)
  • Signal Processing (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Power Engineering (AREA)
  • Superheterodyne Receivers (AREA)

Abstract

Data is received that has been transmitted via a combination of radio frequency signals using non-contiguous carrier aggregation. Desired signals are transmitted over two non-adjacent groups of carriers (532, 534, Fig. 9). The first of the two groups (532, Fig. 9) occupies a wider frequency region than the second group (534, Fig. 9). For example, the first group may include multiple bands of carrier frequencies (524, 502, Fig. 9) and the second group only a single band of carrier frequencies (504, Fig. 9) and the first and second groups may be separated by an unwanted frequency band (518, Fig. 9). Frequency signals are downconverted using quadrature mixing (906a, 906b, 906c, 906d) to give two identical sets of inphasc (I) and quadrature (Q) components. The first set of I and Q components is filtered using a first bandpass filter bandwidth (902a, 902b) and the second set is filtered using a second bandpass filter bandwidth (904a, 904b), different from the first bandpass filter bandwidth. A reconfigurable receiver is also disclosed, which may switch between a first mode, as described above, and a second mode. The second mode may use only one set of I and Q components, and these are lowpass filtered (900a, 900b) rather than bandpass filtered.

Description

Methods of Receiving and Receivers
Technical Field
The present invention relates to methods of receiving and receivers for radio communication systems, and in particular, but not exclusively, to non-contiguous carrier aggregation schemes.
Background
Long Term Evolution (LTE) Advanced is a mobile telecommunication standard proposed by the 3 Generation Partnership Project (3GPP) and first 0 standardised in 3GPP Release O. In order to provide the peak bandwidth requirements of a 4th Generation system as defined by the International Telecommunication Union Radioeommunication (ITU-R) Sector, while maintaining compatibility with legacy mobile communication equipment, LTE Advanced proposes the aggregation of multiple carrier signals in order to provide a higher aggregate bandwidth than would be available if transmitting via a single carrier signal. This technique of Carrier Aggregation (CA) requires each utilised carrier signal to be demodulated at the receiver, whercafter the message data from each of the signals can be combined in order to reconstruct the original data. Carrier Aggregation can be used also in other radio communication protocols such as High Speed Packet Access (HSPA).
Carrier signals are typically composed of a carrier frequency that is modulated to occupy a respective radio frequency carrier signal band.
Contiguous Carrier Aggregation involves aggregation of carrier signals that occupy contiguous radio frequency carrier signal bands. Contiguous radio frequency carrier signal bands may be separated by guard bands, which are small unused sections of the frequency spectrum designed to improve the case with which individual signals can be selected by filters at the receiver by reducing the likelihood of interference between signals transmitted in adjacent bands. Non-contiguous Carrier Aggregation comprises aggregation of carrier signals that occupy non-contiguous radio frequency carrier signal bands, and may comprise aggregation of clusters of one or more contiguous carrier signals.
The non-contiguous radio frequency carrier signal bands are typically separated by a frequency region which is not available to the operator of the network comprising the carrier signals, and may be allocated to another operator. This situation is potentially problematic for the reception of the carrier signals, since there may be signals in the frequency region that separates the non-contiguous carriers which are at a higher power level than the wanted carrier signals.
A Direct Conversion Receiver (DCR) is typically employed to receive cellular radio signals, and typically provides an economical and power efficient implementation of a receiver. A DCR uses a local oscillator placed within the radio frequency bandwidth occupied by the signals to bc rcccived to directly concert the signals to baseband. Signals on the high side of the local oscillator are mixed to the same baseband frequency band as signals on the low side of the local oscillator, and in order to separate out the high and low side signals, it is necessary to mix the signal with two components of the local oscillator in quadrature (i.e. 90 degrees out of phase with one another) to produce inphase (I) and quadrature (Q) signal components at baseband. The I and Q components are digitised separately, and may be processed digitally to reconstruct the separate high side and low side signals. The reconstructed high and low side signals may be filtered in the digital domain to separate carrier signals received within the receiver bandwidth of the DCL The presence of a higher power signal in the region separating non-contiguous carrier clusters poses particular problems if a DCR is to be used to receive a band of frequencies comprising non-contiguous Carrier Aggregation signals. In particular, since the higher power signal is within the receiver bandwidth, the dynamic range of the receiver need to encompass the powers of the wanted carrier signals, which are typically received at a similar power to each other, and the higher power signal. This may place severe demands on the dynamic range of the analogue to digital converter (AID) in particular.
Furthermore, due to inevitable imbalances between the amplitudes and phases of the I and Q channels, the process of reconstructing the separate high side and low side signals suffers from a limited degree of cancellation of the image component; that is to say, some of the high side signals break through onto the reconstructed low side signals, and vice versa. The degree of rejection of the image signal may be termed the Image Reject Ratio (IRR). If the higher power signal is a high side signal, it may cause interference to received low side signals due to the finite JIR, and similarly if the higher power signal is a low side signal, it may cause interference to received high side signals.
One conventional method of receiving Non-contiguous Carrier Aggregation signals is to provide two DCR receiver stages, each having a local oscillator tuned to receive a cluster of contiguous carriers, and so rejecting signals in the frequcncy region between the clustcrs before digitisation.
However, this approach is potentially expensive and power consuming, and may suffer from interference between the closely spaced local oscillators.
It is an object of the invention to address at least some of the limitations
of the prior art systems.
Summaiy in accordance with a first exemplary embodiment of the present invention, there is provided a method of receiving data transmitted via a combination of at least a plurality of radio frequency signals using carrier aggregation, each radio frequency signal occupying a respective band of a plurality of radio frequency bands, the plurality of radio frequency bands being arranged in two groups separated in frequency by a first frequency region, the first of the two groups occupying a wider frequency region than the second group, the method comprising: downeonverting said plurality of radio frequency signals using quadrature mixing to give inphase and quadrature components; filtering said inphase and quadrature components using a first bandpass filter bandwidth to give first bandpass filtered inphase and quadrature components; and filtering said inphase and quadrature components using a second bandpass filter bandwidth, diffcrcnt from the first bandpass filter bandwidth, to give second bandpass filtered inphase and quadrature components.
In accordance with a second exemplary embodiment of the prescnt invcntion, there is provided a receiver for receiving data transmitted via a combination of at least a plurality of radio frequency signals, each radio frequency signal occupying a respective band of a plurality of radio frequency bands, the plurality of radio frequency bands being arranged in two groups separated in frequency by a first frequency region, the first of the two groups occupying a wider frequency region than the second group, the receiver comprising: at least one downconverter configured to downconvert said plurality of radio frequency signals using quadrature mixthg to give inphase and quadrature components; at least one first bandpass filter configured to filter said inphase and quadrature components using a first bandpass filter bandwidth to give first bandpass filtered inphase and quadrature components and at least one second bandpass filter configured to filter said inphase and quadrature components using a second bandpass filter bandwidth, different from the first bandpass filter bandwidth, to give second bandpass filtered inphase and quadrature components.
In accordance with a third exemplary embodiment of the present invention, there is provided a reconfigurable receiver capable of receiving data transmitted via a combination of at least a plurality of radio frequency signals using carrier aggregation, each radio frequency signal occupying a respective band of a plurality of radio frequency bands, the receiver being configurable to a first mode to receive radio signals in which the plurality of radio frequency bands are arranged in two groups separated in frequency by a first frequency region, the first of the two groups occupying a wider frequency region than the second group, and to at least a second mode,, the receiver comprising: at least one downconvertcr configured to downconvcrt said plurality of radio frequency signals using quadrature mixing to give inphase and quadrature components; at least one first filter arranged to be configured, in the first mode, to filter said inphase and quadrature components using a first bandpass filter bandwidth to give first bandpass filtered inphase and quadrature components and, in the second mode to filter said inphase and quadrature components using a first lowpass filter bandwidth to give first lowpass filtered inphase and quadrature components; at least one second filter arranged to be configured, in the first mode, to filter said inphasc and quadrature components using a second bandpass filter bandwidth, different from the first bandpass filter bandwidth, to give second bandpass filtered inphasc and quadrature components.
Further features and advantages of the invention will be apparent from the following description of preferred embodiments of the invention, which are given by way of example only.
Brief Description of the Drawings
Figure 1 is a schematic diagram showing the transmission of carrier aggregation signals by thc radio access network of a first operator and transmission of a signal from another a radio access nctwork; Figure 2 is amplitude-frequency diagram showing carriers in a non-contiguous carricr aggregation method and a carrier from anothcr opcrator received at a higher level; Figure 3 is a schematic diagram showing a conventional direct conversion receiver; Figure 4 is a diagram illustrating an effect of a finite image rejection ratio in a direct conversion receiver; Figure 5 is a diagram illustrating reception of non-contiguous aggregated carriers in a low IF receiver.
Figure 6 is a schematic diagram showing a conventional low IF receiver; Figure 7 is a diagram illustrating problems with rcception of non-contiguous aggregated carriers in a direct conversion receiver; Figure 8 is an amplitude-frequency diagram illustrating reception of non-contiguous aggregated carriers in a direct conversion receiver in an embodiment of the invention; Figure 9 is an amplitude-frequency diagram illustrating reception of non-contiguous aggregated carriers in an receiver having different passband filters for the high side and low side signals in an embodiment of the invention; Figure 10 is a schcmatic diagram showing a receiver having two zero IF branches each having different bandpass filters in an embodiment of the invention; Figure 11 is a schematic diagram showing an alternative receiver having two zero IF branches each having different bandpass filters in an embodiment of the invention; Figure 12 is a diagram illustrating a conventional direct conversion receiver as implemented in an RFIC; Figure 13 is a frequency-amplitude diagram illustrating problems with reception of non-contiguous aggregated carriers in a direct conversion receiver, showing image frequencies at the equivalent position in RE frequency; Figure 14 is a frequency-amplitude diagram illustrating a conventional solution for the reception of non-contiguous aggregated carriers, by the use of two receivers, each having a different local oscillator frequency; Figure 15 is a schematic diagram illustrating an RE IC: implementation for the reception of non-contiguous aggregated carriers, by the use of two receivers, each having a separate RFIC and a different local oscillator frequency; Figure 16 is a schematic diagram illustrating an RE IC implementation for the reception of non-contiguous aggregated carriers, by the use of two receivers, each having a different local oscillator frequency on a single RFIC; Figure 17 is an amplitude-frequency diagram illustrating reception of non-contiguous aggregated carriers, with a single signal from another operator between the wanted carrier signals in an embodiment of the invention; Figure 18 is an amplitude-frequency diagram illustrating the reception of non-contiguous aggregated carriers, showing a single signal from another operator between carrier aggregation clusters and the effect of image frequencies in an embodiment of the invention; Figure 19 is an amplitude-frequency diagram illustrating the reception of non-contiguous aggregated carriers, showing two signals from another operator between carrier aggregation clusters and the effect of image frequencies in an embodiment of the invention Figure 20 is an amplitude-frequency diagram illustrating thc reception of non-contiguous aggregated carriers, showing three signals from another operator between carrier aggregation clusters and the effect of image frequencies in an embodiment of the invention; Figure 21 is an amplitude-frequency diagram illustrating the reception of non-contiguous aggregated carriers, showing a different filter bandwidth used for the reception of high side and low side signals in an embodiment of the invention; Figure 22 is an amplitude-frequency diagram illustrating the reception of non-contiguous aggregated carriers, showing a) the use of a complex filter characteristic b) the effect of the complex filter characteristic shown with a digital filter characteristic superimposed and c) the combined effect of the complex and digital filters; Figure 23 (upper part) is schematic diagram showing a receiver architecture having complex filters and a digital data path; Figure 23 (lower part) is schematic diagram showing a receiver architecture having real filters and a digital data path having image reject mixing; Figure 24 is a schematic diagram showing a reconfigurable receiver having two branches, a first branch having a filter with a selectable low pass or band pass characteristic and a second branch having a band pass characteristic; and Figure 25 is a schematic diagram showing an alternative reconfigurable receiver having two branches, a first branch having a filter with a seectabe ow pass or band pass characteristic and a second branch having a band pass characteristic, the two branches sharing the same I and Q mixers.
Detailed Description
By way of example an embodiment of the invention will now be described in the context of a wireless communications system supporting conmmnication using E-UTRA radio access technology, as associated with E-UTRAN radio access networks in LTE systems. However, it will be understood that this is by way of example only and that other embodiments may involve wireless networks using other radio access technologies, such as IJIRAN, GERAN or IEEE8O2.16 WiMax systems.
Figure 1 shows the transmission of radio frequency signal signals lOa, lOb and lOe by the radio access network to a receiver 8. The radio frequency signals each occupy a respective carrier signal band, as shown in the amplitude-frequency diagram of Figure 2. A carrier signal band is the part of the radio frequency spectrum occupied by a modulated radio frequency carrier comprising the radio frequency signal. Radio frequency signals lOa, lOb, and lOe occupy radio frequency bands 14a, 14b and 14e as shown in Figure 2. Data is received using the combination of the radio frequency signals lOa, lOb and lOc, and the bands 14a, 14b and I 4e shown in Figure 2 represent a set of radio frequency signals, that may be referred to as component carriers, transmitted using Carrier Aggregation. It can be seen from Figure 2 that non-contiguous Carrier Aggregation is used, since a radio frequency signal from another operator, other than the operator sending the data, is present in a frequency region separating bands 14b and 14c. In Figure 1, the radio frequency signals are sent from a first base station 4, operated by Operator A. A second base station 6, operated by a different operator, Operator B, is situated within the area of coverage 2 of the first base station 4, and transmits a radio frequency signal 12 that is received by the user equipment 8. It can be seen that the second base station is closer to the user equipment 8 than is the first base station. As a result, it can be seen from Figure 2 that the radio frequency signal is received at the user equipment 8 at a significantly higher power level, as shown by the amplitude of the band 16 transmitted by operator B. Figure 3 is a schematic diagram showing a conventional direct conversion receiver. A signal is received by an antenna 100, and filtered by a front end filter 102, which removes out of band signals, protecting the Low Noise Amplifier (LNA) 104 from saturation by strong out of band signals. A local oscillator 106 is typically set to a frequency in the centre of a desired radio frequency (RF) band. RE signals that arc both higher than (high side) and lower than (low side) the local oscillator frequency are mixed with the local oscillator to downconvert the RF signals to baseband frequencies, which are the difference between the RE and local oscillator frequencies. These difference frequencies, for signals within an intended receive band, are arranged to fall within the passband of the low pass filters 114, 116 of the direct conversion receiver. In order to distinguish between RF signals that originated on the high side of the local oscillator and RE signals that originated on the high side of the local oscillator, it is necessary to mix the RF signal with two components of the local oscillator which are in quadraturc (i.e. 90 degrees out of phase with one another) to produce inphase (I) and quadrature (Q) signal components at baseband. As shown in figure 3, the local oscillator is split into 0 and -90 degree components in a splitter 108 and each component is mixed with the incoming R.F signal in a respective mixer 110, 112. The I and Q components are separately filtered low pass filtered, and each filtered signal is converted to the digital domain in an Analogue to digital converter (AID) 118, 120, to produce a data stream with I and Q components 122, 124. The I and Q components may be processed digitally to reconstruct the separate high side and low side signals. The reconstructed high and low side signals may be filtered in the digital domain to separate carrier signals received within the receiver bandwidth of the DCR.
However, as already mentioned, due to imbalances between the amplitudes and phases of the I and Q channels, the process of reconstructing the separate high side and low side signals suffers from a limited degree of cancellation of the image component, so that some of the high side signals break through onto the reconstructed low side signals, and vice versa. The degree of rejection of the image signal may be termed the Image Reject Ratio (IRR).
Figure 4 shows the effect of a finite image rejection ratio in a direct conversion receiver, in the ease where two bands 202, 204 are received at approximately the same power level at radio frequency. As can be seen, the two bands are mixed with a local oscillator 206 and downconvcrtcd to a band encompassing zero frequency, which may be referred to as DC (Direct Current).
In figure 4, the high side signal 204 is shown as being downconvcrted to positive frequency 210, and the low side signal 202 is shown as being downconverted to a negative frequency 208. This is a matter of convention, and the designation of positive and negative frequencies may be transposed. The concept of positive and negative frequencies has meaning only within the complex signal domain, in which signals are represented by I and Q components. A negative frequency has a phasor defined by its I and Q components that rotates in the opposite direction to the phasor of a positive frequency. By distinguishing between positive and negative frequencies by signal processing, for example using a Fast Fourier Transform (FFT) or a complex digital mixer, signals originating as high side RI signals may be separately received from signals originating as low side RE signals. So, as shown in Figure 4, data may be extracted from two received carrier signal bands, provided that the signal to noise ratio (SNR) is not degraded unacceptably by the image component 214 of the high side signal 204 that is in the same band 208 as the downeonverted low side signal 202, and the image component 212 of the low side signal 202 that is in the same band 210 as the downconverted high side signal 204. For signals received at approximately the same power level, SNR is not usually degraded unacceptably by the finite image reject ratio.
Figure 5 is a diagram illustrating reception of non-contiguous aggregated carricrs. In this example. wanted component signal bands 302 and 302 are separated by a higher power radio frequency signal 318, which may originate from another operator. As can be seen from Figurc 5, a local oscillator 306 may be placed in the middle of a receive band defined by the three component signal bands 302, 304, 318. As can be seen from Figure 5, images of the higher power radio frequency signal resulting from the finite image reject ratio do not fall on top of the downconverted weaker signals in this case, but fall within the downconverted components 320 of the higher power radio frequency signal.
Figure 6 is a schcmatic diagram showing a conventional low IF receiver that may be used to receive the signals illustrated in Figure 5. It can be seen that the low IF rcccivcr differs from a conventional DCR receiver in that the low pass filters of a conventional DCR receiver, as shown in Fig 3, have been replaced by bandpass filters 114, 118, to filter the I and Q signals respectively.
The band pass characteristics of the band pass filters have been shown on Figure 5, as the dashed lines 324, 322, around the wanted component signal bands 308, 322. It can be seen that the downconverted components 320 of the higher power radio frequency signal are rejected by the band pass filters in the I and Q signal paths, so that saturation of the AID converter by the unfiltered downconverted components 320 of the higher power radio frequency signal may be avoided.
Figure 7 is a diagram illustrating problems with reception of non-contiguous aggregated carriers in a direct conversion receiver. This illustrates the situation shown in Figure 2, in which component signals bands 524, 502, 504 in a non-contiguous carrier aggregation system are arranged in two groups, or clusters, the first group occupying a wider frequency region than the second group. A higher power signal 518 is located between in a frequency region between the first group and the second group. In this case, by contrast to the situation shown in Figure 5, it can be seen that the images 528 of the higher power radio frequency signal that result from the finite image reject ratio fall directly in the same band as one of the downconverted component signal bands 508. Depending on the difference between the received power of the higher power signa', the received power of the wanted received signals, and the image reject ration, this situation may prevent reliable transmission of the signals in band 508.
Figure 8 shows a solution to the problems illustrated by Fig 7 in an embodiment of the invention. As can be seen, the local oscillator is offset from the centre of the band encompassing the wanted signals, that is to say offset from the centre of the band 530 defined by a combination of the frequency regions occupied by the two groups of signals and the frequency region in between, i.e offset from the centre of a band defined by outer edges of the frequency regions occupied by the two groups.
When the [0 frequency is set as shown in Figure 8, it can be seen that the images 528 of the higher power radio frequency signal that result from the finite image reject ratio is only partly overlapping the downconverted component signal band 508. As can be seen, part of the bands are affected by the image while other parts are not. Due to interleaving of subcarriers and the use of error correction coding, a typical modulation format, such as Orthogonal Frequency Division Multiplexing (OFDM), may be tolerant to the degradation of a proportion of the band, whereas it would not be tolerant if the degradation were applied to the whole band. Therefore, the situation in Figure 8 may allow acceptable reception of component signal band 508, whereas the situation in Figure 7 may not. As can be seen from Figure 8, preferably the LO is set such that the distance from the LO to the centre of each of the two wanted clusters 532, 534 is equal. Setting the local oscillator in this way has the advantage of minimising intcrference due to finite image rejection ratio resulting from both an unwanted signal between the wanted signal clusters, and also minimising interference from unwanted signals adjacent to the wanted signal clusters situated away from the local oscillator frequency. In an embodiment of the invention, the offset of the local oscillator frequency may be determined in dependence on a measurement of signal quality, such as signal to noise plus interference ratio, of at least one of the plurality of radio frequency signals. For example, if an unwanted signal adjacent to the wanted signal clusters situated away from the local oscillator frequency on the high frequency side is greater than another unwanted signal adjacent to the wanted signal clusters situated away from the local oscillator frequency on the low frequency side, it may be determined that the local oscillator offset should be set at a position that causes the least total interference with the wanted signals. This may be determined on the basis of signal to noise plus interference ratio measurements for each of the wanted signals.
Figure 9 shows that that setting of the local oscillator may be used in conjunction with a receiver having two bandpass filter characteristics 540, 538 one of which 538 is wider than the other 540. The bandpass characteristics may be set to be appropriate to receive the component signal bands in the respective groups of signals.
Figure 10 is a schematic diagram showing a receiver having two bandpass filter characteristics as illustrated in Figure 9 in an embodiment of the invention. The receiver has two branches. A first branch is a low IF receiver having I and Q channels, each of which has a bandpass filters 814, 816 with a first bandwidth. A second branch is also configured as a low IF receiver as shown in Figure 10, and also has I and Q channels, each of which has a bandpass filters 814, 816 with a second bandwidth, different from the first bandwidth. A first subset of downconverted radio signals may be received using the first branch, and a second subset of downeonverted radio signals may be received using the second branch.
Figure 11 is a schematic diagram showing an alternative receiver having two branches each having different bandpass filters in an embodiment of the invention, in which a single set of quadrature mixers is shared between the two branches.
Embodiments of the invention will now be described in more detail.
Embodiments of the invention relate to multi-carrier wireless systems, using carrier aggregation. Operators may own non-contiguous allocation of spectrum this may come about, for example, if an operator buys another operator's businesses. If the spectrums happen to be non-adjacent then the allocation is non-contiguous. Operators typically wish to exploit their spectrum as effectively as possible, so the need for non-contiguous multi-carrier systems is increasing. An example of such scenario is presented in Figure 2. In a scenario such as that illustrated in Figure 2, there may be a problem with single receiver chain architecture in that it may not be known or guaranteed a priori what is allocated in the gap between the two non-contiguous carriers. Typically, another operator's licensed spectrum may be present in the gap. Furthermore, it cannot be guaranteed that the other operator's signal, that is to say deployed spectrum, is not significantly stronger than the wanted signal at the receiver input. This may place large demands on the recciver performance in terms of dynamic range and image rejection performance.
Table 1 below gives example of possible allocations of blocks of carriers within a single band. In table 1, in the column headed "configuration", "C" represents a 5 MHz component carrier and the gap length is expressed as a numberin MHz.
Table 1. Summary of operators' scenarios.
Number of Scenario Band Gap Component Configuration ____________ __________ Ieugth Carriers A 1 5 2 C-S-C B 1 5 3 C-s-CC C 1 10 4 C-l0-CCC D IV 5 2 C-S-C E IV 10 3 C-lu-CC F IV 15 4 CC-IS-CC G IV 20 3 CC-20-C H IV 25 4 CC-25-CC The reception of two or more non-contiguous component carriers causes several design challenges for a receiver containing one reception branch only.
The simplified block diagram of a typical direct-conversion receiver (DCR) is presented in Figure 12. The signal is amplified in the low-noise amplifier (LNA) before being down-converted to zero intermediate frequency (IF). For phase-and frequency-modulated signals, the down-conversion must be performed with quadrature local oscillator (LO) signals to prevent signal sidebands from aliasing on one another. Prior to analogue-to-digital conversion, the signal is low-pass filtered and amplified such that the signal for the ADC is at sufficient level. A DCR is typically used in cellular user equipments (liEs) in, for example, OSM, WCDMA, HSPA, and single-carrier LTE modes, for example in Release 7, 8 or 9 LTE. From the point of view of integrated circuit development, DCR has several advantages compared to other receiver types, such as low complexity and power consumption, small silicon area, and a low number of off-chip components.
For a single receiver UE comprising conventional DRC hardware as shown in Figure 12, the scenario shown in Figure 2 is challenging. Firstly, since deployed spectrum of operator B shown is located in the wanted channel, it passes through the analogue circuitry without any filtering. Thus, the dynamic range of the analogue-to-digital converter (ADC) needs to be increased by the amount of power difference between the unwanted and wanted carriers. In addition to the increased bandwidth required to receive non-contiguous aggregated carriers, the dynamic range requirement makes ADC design even more challenging and power consuming.
Secondly, the gain control of the receiver becomes more challenging, since the maximum gain setup in different RF front-end blocks (LNA, Mixer, filters) is dominated by the strong unwanted carrier to prevent the receiver from saturation and/or clipping. As a result, the gain may be set to a lower value than would be ideally required for the weaker carriers, thus deteriorating the signal-to-noise performance of the weaker carriers.
Thirdly, in practice, due to imperfections such as component mismatch in down-conversion mixers and analogue baseband filters and the quality of quadrature signals from the local oscillator, there is a finite amplitude and phase balance between the in-phase (I) and quadrature phase (Q) branches. That is to say, there are errors in matching between the phase and amplitude of the inphase and quadrature signals paths. As has been already mentioned, this leads to a finite image reject ratio (IIR).
Figure 13 depicts a case, such as, for example, may result from 4C-HSDPA (4 Carrier High Speed Downlink Packet Access) with a strong unwanted carrier received and down-converted with a demodulator having a finite IQ performance. Due to the finite image-reject ratio (IRR), the more powerful unwanted carrier will generate a strong image signal overlapping the weaker carrier locating at opposite side of the LO. This may not achieve sufficient signal-to-noise ratio (SNR) to receive the weaker carrier.
So, as has been mentioned, the reception of non-contiguous CA signals in a conventional DCR receiver presents challenges regarding the ADC design (dynamic range vs. powcr consumption), RF/analogue gain control, and RF images. These challenges apply to both the reception of non-contiguous (NC) carrier aggregation in HSDPA and LTE, and to the use of non-contiguous carrier aggregation for future standards to achieve high peak data rates. Furthermore, high SNR figures are needed to be able to operate with 64QAM modulation to reach the highest data rates. As a result, a small impairment in signal quality or dynamic range caused by the presence of the operator B signa' can have a significant effect.
It is preferable that a single direct-conversion receiver is utilised in user equipment intended to receive NC-HSDPA (or non-contiguous LTE), as the user equipment may also be configured for lower data rates and single carrier operation, and user expectations would be for similar or bcttcr battery life than legacy UEs when operating at lower data rates (i.c. in non-carrier aggregation mode). However, as already mentioned, a UE with a conventional single receiver path is unlikely to be able to receive intra-band non-contiguous carriers with maximal SNR.
One potentia' method of receiving non-contiguous carrier aggregation signals is to receive separate clusters of component carriers in separate receiver chains, each having a LO signal of its own. This is depicted in Figure 15, where Clusterl and Cluster2 are each handled by a separate respective receiver chain, as shown in Figure 15. However, the solution illustrated by Figure 15 may increase the complexity of the Front End Module (FEM), due to the need for signal splitting and the need to minimise local oscillator coupling between channels, which in turn may lead to a higher cost and increased insertion loss.
In addition, in the solution presented in Figure 16, having two LO synthesizers operating at frequencies close each other might suffer from LO pulling, which can lead to increased phase noise, instability and presence of sideband tones.
Within a single die it is challenging to achieve sufficient isolation between two LOs having a small frequency separation between each other. Possibly, two simultaneously running synthesisers could operate at two completely different RF frequencies but the final LO frequency could be generated with different frequency division ratios (e.g. 4 GHz divided by 2 and 6 GHz divided by 3).
That solution, however, may lead to complicated design (either fractional or odd frequency division ratios could bc needed) and would possibly generate unwanted tones.
In an embodiment of the invention, a DCR is configured such that it is able to handle two non-contiguous clusters with improved SNR with a single Radio Frequency Integrated Circuit (RFIC). In an embodiment of the invention, two clusters are each received with a different bandwidth filter.
Figure 17 presents a scenario similar to one shown in Figure 13, except the first and second adjacent channels arc now presented. In an embodiment of the invention, the LO signal is placed offset from the centre of the illustrated band to be received, as shown in Figure 17. This has thc advantage that the cffcct of resulting imagcs signals is minimized, as illustratcd in Figure 18. After the LO frequency is placed as shown in Figure 18, the images of the unwanted adjacent channels are only partly overlapping with wanted channels in Clusterl as shown. The average SNR impairment across a band due to image signal folding, that is to say due to finite image reject ratio, is thus reduced in the worst affected bands at the expense of degrading the SNR impairment in bands that were not affected with a conventional placing of the local osciUator. As can be seen, part of the bands are affected by signal folding while other parts are not.
As has already been mentioned, due to interleaving of subcarriers and the use of error correction coding, a typical modulation format, such as OFDM, may be tolerant to the degradation of a proportion of the band, whereas it would not be tolerant if the degradation were applied to the whole band.
An additional example is presented in Figure 19. The scenario is similar to the previous one but now there are two carriers deployed by the other operator in the centre of the band, as shown in Figure 1 9(a). A conventional approach to the reception of the signals shown in Figure 19(a) is shown in Figure 19(b), in which the LO is placed between the two unwanted carriers, but as a result, one of the wanted carriers suffers from image signal due to the first adjacent high side channel. In an embodiment of the invention, this is mitigated by placing the LO such that thc distance from the LO to thc centre of each of the two wanted clusters is equal, as shown in Figure 19 (c). As a result, after down-conversion the image of the wantcd carrier in the narrow cluster is located between the two wanted carriers, as shown in Figure 19 (d). Now, image signals due to adjacent channels overlap the wanted carriers only partly and SNR degradation is averaged over the channel. As already mentioned, a typical modulation and coding format may be tolerant of a reduced SNR over a part of the band.
Figure 20 gives an example of a scenario in which there are three unwanted carriers between the wanted clusters. As shown in Figures 20(a) and 20(b), a conventional LO location may be at the centre of the most powerful carrier. Then, the image due this most powerful carrier would be placed on top of the most powerful carrier itself, as shown in Figure 20 (b). However, the SNR degradation due to image folding is minimized in an embodiment of the invention, when thc LU is placed substantially half way between the centres of the clusters, as shown in Figure 10(e), or at least within approximately an eighth of a carrier bandwidth of this position.
In an embodiment of the invention, the improved positioning of the LU may be used advantageously in combination with a low IF receiver. A low IF receiver may be realised as illustrated in Figure 6 by the substitution of a band pass filter for the low pass filter of a conventional direct conversion receiver.
Figures 20(a) and 20(c) show the passband filter characteristic of a low IF receiver, shown referred to RF frequencies. As may be seen from a comparison of Figure 20 (a) with Figure 20 (c), the passband filter in the case illustrated by Figure 20(c) attenuates adjacent channels of Cluster2 more efficiently than that in the case illustrated by Figure 20 (a).
In an embodiment of the invention, the improved positioning of the LO may be used advantageously in combination with a low IF receiver, having two receiver branches, one receiver branch having a different bandpass filter characteristic from the other. Such a two-branch low IF receiver is shown in Figures 10, and an alternative implementation is shown in Figure 11. As shown in Figure 21(b), the use of a narrower bandpass filter to filter the narrower cluster, Clustcr2, improves the rejection of adjacent channels, as compared to the case with a the use of the same filter bandit to receive high and low side signals, as in the case shown in Figure 21(a). Figure 21 (a) may represent the case, for example, in which a single branch low IF receiver used.
The use of analogue bandpass filters may reduce the dynamic range required by the A/D converter, since interfering signals may be removed before conversion.
In an embodiment of the invention, the analogue, typically bandpass filters, are implemented using a complex filtering method, that is to say each filter may process components of both the I and Q channels. Then, the filter response is asymmetric in respect to zero frequency as shown in Figure 22(a).
In this case, the image signal located at the opposite side of the zero frequency can be filtered out. As a result, carrier separation in the digital domain could be implemented with typical digital down-conversion mixers as shown in the upper part of Figure 23. Alternatively, if conventional real-only analogue filters are used, the digital down-conversion could comprise a complex scheme to attenuate the image signal, as shown in the lower part of Figure 23.
it is advantageous to provide a receiver that may be reconfigurable, to optimally receive signals that may be received using non-contiguous carrier aggregation as already described, but also configurable to receive signals received using contiguous carrier aggregation, or legacy signals not using carrier aggregation. Preferably, the receiver may be configured with the optimum trade off between image reject and dynamic range performance and power consumption, appropriate to the type of signal format to be received.
Figure 24 is a schematic diagram showing a reconfigurable receiver having two branches, a first branch having a filter in each of the I and Q channels with a selectable low pass 900a, 900b or band pass 902a, 902b characteristic and a sccond branch having a filter in each of the I and Q channels with a band pass 904a, 904b characteristic. The bandwidth of the bandpass filters in the first branch may be different to the bandwidth of the bandpass filters in the second branch, similar to the arrangement in Figure 10. Selection of the bandpass filter may be appropriate for reception of non-contiguous carrier aggregation signals arranged in groups of different bandwidths. Selection of the low pass characteristic may be appropriate for receiving legacy systems without carrier aggregation, or contiguous carrier aggregation. In this case, the second branch may be tuned off to save power.
in the receiver shown in Figure 24, in an embodiment of the invention, in the first branch there may be either separate low-pass and band-pass filters such that the non-active is turned off when not needed or some of the blocks or components, such as for example op-amps or capacitors arc re-used between the configurations. Figure 24 shows a second branch (within the dashed line), containing down-conversion mixers 906c, 906d, analogue pass-band filters 904a, 904b, and analogue to digital converters (AIDs) 910a, 910b. Analogue filters 900a, 900b, 902a, 902b, 904a, 904b and AIDs 908a, 908b, 910a, 910b in one or both branches may also comprise a complex band-pass scheme providing lower IIQ imbalance. That would efficiently decrease the levels of folded images shown in figures in Figure 22.
As a variant to the topology shown in Figure 24, the division into different receiver branches may be provided in the LNA if it contains several stages. In Figure 24 the switch 51 may be turned off when the second branch, the additional low-IF branch, is not needed it can be turned off such that is has a minimal effect on the first branch when it is configured as a conventional low pass DCR branch.
Figure 25 is a schematic diagram showing an alternative embodiment of the invention in which the two branches sharing the same I and Q mixers. As shown in Figure 25, only one set of IQ-mixers is used and the division between the branches is performed after the mixers. In contrast to the topology shown in Figure 24, the LNA/mixer interface is unchanged compared to a conventional single branch DCR design and the DCRIIow-IF mode interface is moved to after down-conversion mixers. The design of the mixer/filter interface may be more demanding in the case of the receiver shown in Figure 25 as compared with the receiver of Figure 24.
In the rcconfigurable receiver of either Figure 24 or Figure 25, both branches may be configured to having independcnt gain, bandwidth, and/or current consumption setups and the wanted configuration may be set with minimal effect on the other branch, so that the signal levels can be independently set to optimum level in each paths. The signal levels may depend on the presence of blocking signals within the passband, and the gains and signal levels may be set to maximum SNR to set an optimum AID input. As shown in Figures 24 and 25, the controllable gain stage presents an exemplary arrangement; the gain control can be implemented in any block in the receiver.
Since good sensitivity is required from both branches and the signal is split, there may be a need to increase the gain of the LNA (this is also nue for topology shown in Figure 16). Thus, higher transconductance is required from the LNA than would be the case with a single branch receiver.
Both the analogue filter and the ADC in the second branch branch may be either a passband type or could be designed to operate with a wide reception bandwidth setup. The analogue passband filters and ADCs in the additional branch may also comprise a complex bandpass scheme providing lower I/Q imbalance. In addition, the digital part following the ADC may typically include additional filtering, level shifting, IQ compensation, DC offiet compensation etc. In the case of low-IF reception, the digital data can be down-converted to around zero fltquency for further signal processing, for example using complex mixers. Modem DSP based IJQ compensation schemes may be used to provide excellent performance.
When the clusters have unequal bandwidths, the choice of bandwidth (BW) setups for both receiver chains may be perfbrmed in order to reconfigure the receiver such that receiver performance is optimal. Typically, the first branch may be configured in a first mode to have a first bandpass filter bandwidth to give first bandpass filtered inphase and quadrature components, and may be configured in a second mode to have a first Lowpass filter bandwidth to give first lowpass ffltcrcd inphase and quadrature components. In the first mode, a second branch may be configured, for example as shown in Figure 24 within the dashed lines, and for example as shown in Figure 10 or Figure II, to have a second bandpass ifiter bandwidth, different from the first bandpass ifiter bandwidth, to give second bandpass ifitered inphase and quadrature components. In the second mode, the first branch may be used as a conventional DCR receiver, for example to receive single carrier or contiguous carrier signals, and the second branch, also referred to as an additional branch, may be not used, for example by being disconnected or turned oft In a variation of the second mode, that may be referred to as a third mode, the first branch may be configured as a tow-IF receiver, to operate for example as shown in Figure 6 with a bandpass characteristic, and the second branch may be not used. This variation of the second mode may be used, for example, to receive non-contiguous carriers aggregated as in two groups, i.e. clusters, or bands having the same bandwidth, as shown in Figure 5.
Inthesecondmode,inwhichtheflrstbranchmaybcconflguredtohave a low pass DCR characteristic, the first branch may configured to support wider bandwidths than the second branch, the wider bandwidths being typically 2x2OMHz in some cases, for example in the case of 3GPP Rd 10 contiguous intra-band LTE carrier aggregation. This maximum BW of 2x2OMHz may not increase in Ret!!. Therefore, in an embodiment of the invention, the ADC supports a BW of 20 MHz even in the typical DCR mode. In NC-HSDPA, the maximum BW of the clusters is typically 15 MHz (scenario 3 in Table 1). Tn NC-LTE, the envisioned maximum bandwidths of non-contiguous clusters are probably in the order of 10 MHz. Therefore, to limit the maximum BW of the ADC in the additional receiver branch, the BWs exceeding 10 MHz may be handled by the first branch. In some cases, as is shown in Figure 1, the receiver chain handling the narrower cluster may suffer less from image signals.
In this case, the receiver may be configured such that the first branch (configured to bandpass, Low-IF mode) handles the narrow cluster and the wider cluster (for example max 10 MHz) may be handled by the second, i.e. additional, low-IF branch. Then, the additional branch could comprise a complex signal processing scheme to improve the TQ performance, i.e. the image reject ratio, and less stringent TQ requirements are required by configurable DRC branch. In general, the optimal receiver configuration depends on several factors, for instance abovementioned image issues and energy consumption. The optimal receiver configuration for each reception scenario can be considered case by case.
in a further embodiment a receiver may be reconfigured according to the quality of received radio frequency signals, the radio frequency signals typically using carrier aggregation, with the carriers aggregated into non-contiguous groups. The receiver, as for example shown in figurc 24, may be initially set to the second mode, as already described, in which a first branch (including analogue to digital (AID) converters 908a, 908b) is configured as a conventional direct conversion receiver having low pass filters and a second branch (including AID converters 91 Oa and 91 Ob) is not used. The second branch may be disconnected or turned off Accordingly, the received radio frequency signals are received in a single receiver branch, which has the advantage of lower power consumption than if both receiver branches were used. As long as the received signal quality is at or above an acceptable threshold in the second mode, the receiver may remain set to the second mode. However, if the received signal quality falls below the acceptable threshold, the receiver may be set to the first mode. As already discussed, there may be an advantage in terms of signal quality, and in particular in terms of improved signal to noise and interference ratio as a result of the finite image reject ratio, to reconfiguring the receiver to the first mode, in which the first branch is configured as a low-IF receiver having band pass filters and the second branch is also configured as a low-IF receiver having band pass filters with a different bandwidth than the band pass filters of the first branch.
So, referring to figure 24, the receiver may be arranged to determine a measure of quality relating to the radio frequency signals received through the low pass filters 900a, 900b in the first branch of the receiver when the receiver is set to the second mode. In the second mode, thc second branch is disconnected or turned off.
If the determined measure of quality is less than a prcdctcrmincd threshold, which may be a threshold related to an acceptable signal quality, then the receiver may be set to the first mode. In the first mode, both first and second branches of the receiver are enabled, with first band pass filters 902a, 902b enabled in the first branch and second band pass filters 904a, 904b enabled in the second branch.
The measure of quality may be based on a measure that is typically measured in a receiver in a cellular radio system, for example for use in handover or network management. Typical measures include signal to noise plus interference ratio (SNIR) and bit error rate (BER). The term "signal to noise ratio" (SNR) is often used as an alternative to SNIR, in which both thermal noise and interference may be referred to as "noise". These measures of quality arc well known, and are typically dctcrmined in a radio receiver by processing the received signal. This would typically be in the digital domain, after the AID converters. The measure of quality may be based on a combination of respective measures of quality of each of the plurality of radio signals, typically for each of the carriers that are aggregated. The measure of quality determined when the receiver is set to the second mode would be typically determined on the basis of signals received in the first branch and converted to the digital domain by AID converters 908a and 908b.
Although at least some aspects of the embodiments described herein with refrrence to the drawings comprise computer processes performed in processing systems or processors, the invention also extends to computer programs, particularly computer programs on or in a carrier; adapted for putting the invention into practice. The program may be in the form of non-transitory source code, object code, a code intermediate source and object code such as in partially compiled form, or in any other non-transitory form suitable for use in the implementation of processes according to the invention. The carrier may be any entity or device capable of carrying the program. For example, the carrier may comprise a storage medium, such as a solid-state drive (SSD) or other semiconductor-based RAM; a ROM, for example a CD ROM or a semiconductor ROM; a magnetic recording medium, for example a floppy disk or hard disk; optical memory devices in general; etc. It will be understood that the processor or processing system or circuitry referred to herein may in practice be provided by a single chip or integrated circuit or plural chips or integrated circuits, optionally provided as a chipset, an application-specific integrated circuit (ASIC), field-programmable gate array (FPGA), etc. The chip or chips may comprise circuitry (as well as possibly firmware) for embodying at least one or more of a data processor or processors, a digital signal processor or processors, baseband circuitry and radio frequency circuitry, which are configurable so as to operate in accordance with the exemplary embodiments. In this regard, the exemplary embodiments may be implemented at least in part by computer software stored in (non-transitory) memory and executable by the processor, or by hardware, or by a combination of tangibly stored sofiware and hardware (and tangibly stored firmware).
The above embodiments are to be understood as illustrative examples of the invention. It is to be understood that any feature described in relation to any one embodiment may be used alone, or in combination with other features described, and may also be used in combination with one or more features of any other of the embodiments, or any combination of any other of the embodiments. Furthermore, equivalents and modifications not described above may also be employed without departing from the scope of the invention, which is defined in the accompanying claims.

Claims (1)

  1. <claim-text>Claims I. A method of receiving data transmitted via a combination of at least a plurality of radio frequency signals using carrier aggregation, each radio frequency signal occupying a respective band of a plurality of radio frequency bands, the plurality of radio frequency bands being arranged in two groups separated in frequency by a first frequency region, the first of the two groups occupying a wider frequency region than the second group, the method comprising: downconverting said plurality of radio frcqucncy signals using quadrature mixing to give inphase and quadrature components; ifitering said inphase and quadrature components using a find bandpass ifiter bandwidth to give first bandpass filtered inphasc and quadrature components; and filtering said inphase and quadrature components using a second bandpass filter bandwidth, different from the first bandpass filter bandwidth, to give second bandpass ifitered inphase and quadrature components.</claim-text> <claim-text>2. A method according to claim I, wherein the first frequency region comprises a radio frequency band occupied by a radio frequency signal that is not aggregated with one of said plurality of radio frequency signals.</claim-text> <claim-text>3. A method according to claim I or claim 2, the method comprising using a complex filter to perform at least one of the steps of: ifitering said inphase and quadrature components to give first bandpass filtered inphase and quadrature components using a first complex filter; and filtering said inphase and quadrature components to give second bandpass filtered inphase and quadrature components using a second complex ifiter.</claim-text> <claim-text>4. A method according to any preceding claim, further comprising: receiving a first subset of the downeonverted plurality of radio frequency signals using the first bandpass ifitered inphase and quadrature components; and receiving a second subset of the downconverted plurality of radio frequency signals using the second bandpass filtered inphase and quadrature components.</claim-text> <claim-text>5. A method according to claim 4, wherein: the first subset of the downconverted plurality radio frequency signals are downconverted from radio frequency bands in the first group; and the second subsct of the downconverted plurality radio frequency signals are downconverted from radio frequency bands in the second group.</claim-text> <claim-text>6. A method according to any preceding claim, wherein said downeonverting comprises: downeonverting said plurality of radio frequency signals using a local oscillator; setting the local oscillator, during said downconverting, to a frequency that is offset from the centre of a band defined by outer edges of the frequency regions occupied by the two groups.</claim-text> <claim-text>7. A method according to claim 6, wherein the frequency to which the local oscillator is set is within one quarter of the bandwidth of one of the plurality of radio frequency bands from a frequency mid-way between the centre of the frequency region occupied by the first group and the centre of the frequency region occupied by the second group.</claim-text> <claim-text>8. A method according to claim 7, wherein the frequency to which the local oscillator is set is substantially mid-way between the centre of the frequency region occupied by the first group and the centre of the frequency region occupied by the second group.</claim-text> <claim-text>9. A method according to claim 6, the method comprising: determining the offset in dependence on a measurement of signal quality of at least one of the plurality of radio frequency signals.</claim-text> <claim-text>10. A receiver for receiving data transmitted via a combination of at least a plurality of radio frequency signals, each radio frequency signal occupying a respective band of a plurality of radio frequency bands, the plurality of radio frequency bands being arranged in two groups separated in frequency by a first frequency region, the first of the two groups occupying a wider frcquency region than thc sccond group, the receiver comprising: at least one downconverter configured to downconvert said plurality of radio frequency signals using quadrature mixing to give inphase and quadrature components; at least one first bandpass filter configured to ifiter said inphase and quadrature components using a first bandpass filter bandwidth to give first bandpass ifitered inphase and quadrature components; and at least one second bandpa.ss filter configured to ifiter said inphase and quadrature components using a second bandpass filter bandwidth, different from the first bandpass filter bandwidth, to give second bandpass filtered inphase and quadrature components.</claim-text> <claim-text>11. A method according to claim 10, wherein the first frequency region comprises a radio frequency band occupied by a radio frequency signal that is not one of said plurality of radio frequency signals.</claim-text> <claim-text>12. A receiver according to claim 10 or claim 11, wherein: said at least one first bandpass ifiter and said at least one second bandpass ifiter are complex filters arranged to process both inphase and quadrature components.</claim-text> <claim-text>13. A receiver according to any of claim 10 to claim 12, the receiver being configured to: downconvert the first subset of the downconverted plurality radio frequency signals from radio frequency bands in the first group; downconvert the second subset of the downconverted plurality radio frequency signals from radio frequency bands in the second group; receive a first subset of the downeonverted plurality of radio frequency signals using the first bandpass filtered inphase and quadrature components; and receive a second subset of the downconverted plurality of radio frcquency signals using the sccond bandpass filtered inphasc and quadrature components.</claim-text> <claim-text>14. A receiver according to claim 13, wherein the receiver comprises: at least two first analogue to digital converters configured to digitise the respective first bandpass filtered inphase and quadrature components; at least two second analogue to digital converters configured to digitise the respective second bandpass filtered inphase and quadrature components; and at least one digital image reject mixer to downconvert the digitised bandpass filtered inphase and quadrature components, wherein said first analogue to digital convcrtcrs have a broader bandwidth than said second analogue to digital convcrtcrs.</claim-text> <claim-text>15. A receiver according to any of claims 10 to 14, wherein the downconverter is configured to downconvcrt said plurality of radio frequency signals using a local oscillator and wherein the receiver comprises a controller configured to set the local oscillator, during downconversion of said plurality of radio frequency signals, to a frequency that is offset from the centre of a band defined by outer edges of the frequency regions occupied by the two groups, 16. A reconfigurabic receiver capable of receiving data transmitted via a combination of at least a plurality of radio frequency signals using carrier aggregation, each radio frequency signal occupying a respective band of a plurality of radio frequency bands, the receiver being configurable to a first mode to receive radio signals in which the plurality of radio frequency bands are arranged in two groups separated in frequency by a first frequency region, thc first of the two groups occupying a wider frequency region than the second group, and to at least a second mode, the receiver comprising: at least onc downconverter configurcd to downconvert said plurality of radio frequency signals using quadrature mixthg to give inphasc and quadrature components; at least one first filter arranged to be configured, in the first mode, to filter said inphase and quadrature components using a first bandpass filter bandwidth to give first bandpass filtered inphase and quadrature components and, in the second mode to filter said inphase and quadrature components using a first lowpass filter bandwidth to give first lowpass filtered inphasc and quadrature components; at least one sccond filtcr arranged to be configured, in the first mode, to filter said inphase and quadrature components using a second bandpass filter bandwidth, different from the first bandpass filter bandwidth, to give second bandpass filtered inphase and quadrature components.17. A reconfigurable receiver according to claim 16, wherein: said at least one second filter is a complex filter arranged to process both inphase and quadrature components.18. A reeonfigurable receiver according to claim 16 or claim 17, the receiver further comprising: at least two first analogue to digital converters configured to digitise the respective first bandpass filtered or first lowpass filtered inphasc and quadrature components; at least two second analogue to digital converters configured to digitise the respective second bandpass filtered inphase and quadrature components, wherein said first analogue to digital converters have a broader bandwidth than said second analogue to digital converters.19. A reconfigurable receiver according to any of claim 16 to 18, wherein the receiver is configured to: determine a measure of quality relating to said plurality of radio frequency signals, when said receiver is set to the second mode; and set the receiver to the first mode dependent on the determined measure being less than a predetermined threshold.20. A reconfigurable receiver according to any of claim 16 to 19, wherein the receiver is configured to use the first filter and not the second filter in the second mode.</claim-text>
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* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US20110268232A1 (en) * 2010-05-03 2011-11-03 Chester Park Inter-carrier bandwidth control for mitigating iq imbalance

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Patent Citations (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
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Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
ZTE, "Handling the interferences in the NC_GAP in NC_4C_HSDPA" 3GPP Draft R4-113494, 27 June - 1 July 2011. *

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