FR3069987A1 - RECTIFIER ELEMENT AND VOLTAGE CONVERTER COMPRISING SUCH A MEMBER - Google Patents

Abstract

The invention relates to a rectifier element (21) comprising a MOS transistor (23) connected in series with a Schottky diode (25), configured to receive a substantially constant voltage (Vp) between the control terminal of the transistor and the terminal (29). ) of the Schottky diode opposite the transistor. The invention also relates to a voltage converter comprising such a rectifier element (21).

Description

RECTIFIER ELEMENT AND VOLTAGE CONVERTER INCLUDING SUCH

ELEMENT

Field

The present application relates, in general, to electronic circuits. It relates more particularly to rectifier elements or circuits and switching converters.

Presentation of the prior art

To supply a DC voltage to electronic devices from an AC voltage, for example the AC voltage of the electrical distribution network, AC-DC converters are used. Among these converters, chopper converters, or chopper converters, are preferred for their efficiency.

There is a need to improve the efficiency of switching converters.

summary

One embodiment provides a rectifier element with improved efficiency.

One embodiment provides a solution particularly suitable for a switching converter.

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One embodiment provides a particularly suitable solution for a switching converter with a rectifier half-bridge.

Thus, one embodiment provides a rectifier element comprising a MOS transistor connected in series with a Schottky diode, configured to receive a substantially constant voltage between the control terminal of the transistor and the terminal of the Schottky diode opposite the transistor.

According to one embodiment, a source of the transistor is connected to a cathode of the Schottky diode.

According to one embodiment, the constant voltage is chosen so that the transistor is on when the Schottky diode is on.

According to one embodiment, the transistor is of the N-channel type with enhancement.

Another embodiment provides a voltage converter comprising at least one rectifier element as defined above.

According to one embodiment, a first rectifier element is connected between a first input terminal of the converter and a first output terminal of the converter, the anode of the Schottky diode of the first rectifier element being connected to the first output terminal.

According to one embodiment, a second rectifier element is connected between a second input terminal of the converter and the first output terminal, the anode of the Schottky diode of the second rectifier element being connected to the first output terminal.

According to one embodiment, the converter further comprises a first inductive element and at least a first diode connected in series between the second input terminal of the converter and the second output terminal of the converter; and a first switch connecting the first output terminal to the midpoint between the first inductive element and the first diode.

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According to one embodiment, the converter further comprises a second inductive element and a second diode connected in series between the first input terminal and the second output terminal; and a second switch connecting the first output terminal to the midpoint between the second inductive element and the second diode.

According to one embodiment, the converter further comprises a second diode connected between the second input terminal and a terminal of the first inductive element opposite the first diode.

According to one embodiment, the converter further comprises a third diode connected between the first input and said terminal of the first inductive element. Brief description of the drawings

These characteristics and advantages, as well as others, will be explained in detail in the following description of particular embodiments made without implied limitation in relation to the attached figures, among which:

FIG. 1 represents an example of a switching converter;

FIG. 2 represents an embodiment of a rectifier element;

FIG. 3 represents an embodiment of a switching converter with rectifying elements such as the rectifying element shown in FIG. 2;

FIG. 4 represents an embodiment of a rectifier circuit;

FIG. 5 represents an alternative embodiment of the rectifier circuit of FIG. 4; and Figure 6 shows another embodiment of a rectifier circuit.

detailed description

The same elements have been designated by the same references in the different figures. For the sake of clarity, only the elements useful for understanding the modes of

B16128ER - 17-TO-0159 described embodiment have been shown and are detailed. In particular, the operation of the switching converters described has not been detailed, the embodiments described being compatible with the usual operations of such converters.

Unless otherwise specified, when reference is made to two elements connected to each other, this means directly connected without any intermediate element other than conductors, and when reference is made to two elements connected to each other, it means that these two elements can be directly connected (connected) or linked through one or more other elements.

Unless otherwise specified, the term substantially means to the nearest 10%, preferably to the nearest 5%.

Figure 1 shows an example of a switching converter.

The converter comprises two input terminals 1 and 3 intended to receive an alternating voltage Vin and two output terminals 5 and 7 intended to supply a direct voltage Vout referenced to terminal 7, typically ground. The input terminals 1 and 3 are connected to the input of a diode bridge 8 comprising, in parallel, two diode branches in series, respectively DI and D2, and D3 and D4. The anode of the diode DI is connected to the cathode of the diode D2 and the anode of the diode D3 is connected to the cathode of the diode D4. The midpoints 11 and 13 of the series associations of the diodes DI and D2, and of the diodes D3 and D4, are respectively connected to the terminals 1 and 3. A node 9 of the bridge output is connected to the output terminal 5 by an element inductive L (typically an inductor) and a diode D connected in series, the cathode of diode D being connected to terminal 5. The midpoint 15 of the series association of inductance L and diode D is connected to terminal 7 by a cutting switch 17. Switch 17, here a MOS transistor, is controlled in pulse width modulation (PWM-Pulse Width Modulation) by a signal Cmd to

B16128ER - 17-TO-0159 a frequency greater than that of the voltage Vin, typically in a ratio of at least 10, preferably at least 100. The signal Cmd is supplied by a control circuit 19 (CTRL). A capacitive element C (typically a capacitor) is connected between the output terminals 5 and 7 of the converter.

When the switch 17 is closed, the inductance L accumulates energy. During a positive alternation of the voltage Vin, a current flows from terminal 1 to terminal 3, through the diode Dl, the inductance L, the switch 17 and the diode D4. During a negative alternation of the voltage Vin, a current flows from terminal 3 to terminal 1, through diode D3, inductance L, switch 17 and diode D2.

When the switch 17 opens, the inductance L restores the energy accumulated at the capacitor C and a current flows, from one terminal to the other of the inductance L, by the freewheeling diode D, the capacitor C, and the diode bridge 8.

The drop in voltage in the on-state bipolar diodes affects the efficiency of the converter. This phenomenon is all the more troublesome at low power, that is to say when the power called by the load (not shown) connected to the output terminals of the converter is low and the voltage Vout is low.

This phenomenon occurs more generally in any voltage converter. In particular, this concerns voltage converters whether they are switching or not, whether they are full or half-bridge, whether they are mono or full wave, etc.

In the embodiments described, provision is made to replace one or more bipolar diodes of a converter with a rectifier element or circuit with a low voltage drop in the on state with respect to a bipolar diode, at least at low power.

FIG. 2 represents an embodiment of a rectifier element 21.

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The rectifier element 21 comprises a MOS transistor 23 and a Schottky diode 25 connected in series between two terminals 27 and 29. For example, the anode of the diode 25 is connected to the terminal 29. The transistor 23 is, preferably, an enrichment MOS transistor, blocked at rest and turned on by applying a gate-source voltage greater than its threshold voltage Vth. The transistor 23 is preferably an N channel. The transistor 23 is for example a power MOS transistor.

In operation, a substantially constant DC voltage Vp is applied between the gate of transistor 23 and terminal 29. The voltage Vp is chosen so that the voltage between the gate and the source of transistor 23 is greater than the threshold voltage Vth of transistor when the diode 25 in the on state, so that the transistor 23 is in the on state when the diode 25 is in the on state. When a current I flows from terminal 29 to terminal 27, the diode 25 and the transistor 23 are conducting and the voltage V21 between terminals 29 and 27 is positive. The voltage V21 is equal to the sum of the voltage drop in the diode 25 and the voltage drop between the conduction terminals (source-drain) of the transistor 23 which depends in particular on the voltage Vp. When the voltage V21 is negative, the diode 25 is blocked. The leakage current in the diode 25 is then regulated by the transistor 23, which prevents the breakdown of the diode. In the rectifier element 21, the compromise between the voltage drop in the on state and the leakage current in the off state is determined by the choice of the voltage Vp. It will be noted that the intrinsic diode (body) of the transistor 23 can contribute to ensuring the commissioning of the voltage source supplying the voltage Vp.

By replacing bipolar diodes of a converter with rectifier elements 21, the efficiency of the converter is improved, at least at low power. Indeed, at low power, the voltage drop in a bipolar diode is no longer negligible compared to the output voltage Vout of the converter, which leads to a reduction in the efficiency at

B16128ER - 17-TO-0159 low power compared to high power performance. We take advantage here of the fact that the threshold voltage of a Schottky diode is lower than that of a bipolar diode. Element 21 therefore makes it possible to limit this reduction in efficiency at low power, and therefore to improve the efficiency at low power of the converter compared to that of a bipolar diode converter. For example, for a current I equal to 1 A, the voltage V21 is 0.2 V lower than the voltage drop in a bipolar diode and, for a current of 100 mA, the voltage V21 is less than 0 , 7 V at the voltage drop in the bipolar diode.

One might have thought of simply replacing the bipolar diodes with Schottky diodes. However, this would only work at low voltage and not in power applications.

According to one embodiment, each of the diodes D2 and D4 of the lower half-bridge of the converter of FIG. 1 is replaced by a rectifier element 21, the terminal 29 of which is connected to the terminal 7, which improves the efficiency of the converter .

Note that it is generally not necessary to provide a specific voltage source to generate the voltage Vp. Indeed, it suffices to use the supply voltage of the control circuit (19, FIG. 1) of the converter.

As a variant, each rectifier element 21 further comprises a bipolar diode (in practice the diode D2 or D4) connected in parallel with the transistor 23 and the diode 25, the anode of the bipolar diode being for example connected to the terminal 29 of the rectifier element 21. This protects the rectifier element 21 against excessive current peaks liable to deteriorate it. The bipolar diode can further improve the efficiency of the converter, especially at high power.

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FIG. 3 represents an embodiment of a half-bridge switching converter with rectifying elements such as the rectifying element 21 represented in FIG. 2.

The converter comprises two input terminals 31 and 33 intended to receive an alternating voltage Vin, and two output terminals 35 and 37 intended to supply a direct voltage Vout, for example referenced to terminal 37, typically ground. The terminals 31 and 33 are connected to the terminal 37 by a lower half-bridge comprising two rectifying elements 21A and 21B, each identical to the rectifying element 21 of FIG. 2. Each of the elements 21A and 21B comprises the same components as the element 21, designated by the same references to which the respective letters A and B have been added. The terminals 29A and 29B are connected to terminal 37. Terminal 27A is connected to terminal 31 and terminal 27B is connected to terminal 33. The terminals 31 and 33 are further respectively connected to the terminal 35 by the association in series of an inductive element L1 (typically an inductance) and of a freewheeling diode D5, and by the association in series an inductive element L2 (typically an inductor) and a freewheeling diode D6. The cathode terminals of diodes D5 and D6 are connected to terminal 35. The midpoints 39 and 41 of the series associations of inductance L1 and diode D5, and of inductance L2 and diode D6, are respectively connected to terminal 37 by switching switches 43 and 45. The switches 43 and 45, here MOS transistors, are controlled by pulse width modulation, for example by the same signal Cmdl, at a frequency higher than that of the voltage Vin, typically in a ratio of at least 10, preferably at least 100. The signal Cmdl is supplied by a control circuit 47 (CTRL). A capacitive element C1 (typically a capacitor) is connected between the output terminals 35 and 37 of the converter.

In operation, as has been described in connection with FIG. 2, a substantially constant DC voltage Vp is applied to the rectifier elements 21A and 21B. Of

B16128EN - 17-TO-0159 preferably, a single voltage source makes it possible to supply the voltage Vp to the two rectifier elements 21A and 21B, for example the voltage source supplying the control circuit 47. During the positive alternations of the voltage Vin between terminal 31 and terminal 33, when the switch 43 is closed, the inductance LI accumulates energy and a current flows from terminal 31 to terminal 33, through the inductance Ll, the switch 43 and l element 21B. When the switch 43 opens, the inductance Ll restores this energy to the capacitor Cl and a current flows from one terminal to the other of the inductance Ll, by the diode D5, the capacitor Cl, and the element rectifier 21B. Symmetrically, during the negative half-waves of the voltage Vin, when the switch 45 is closed, the inductance L2 accumulates energy and a current flows from terminal 33 to terminal 31, through inductance L2, l 'switch 45 and the rectifier element 21A. When the switch 45 opens, the inductor L2 returns this energy to the capacitor Cl and a current flows from one terminal to the other of the inductor L2, through the diode D6, the capacitor Cl and the rectifier element 21A.

The converter of FIG. 3 has an improved efficiency compared to a similar converter with bipolar diodes, more particularly at low power.

FIG. 4 represents an embodiment of a rectifier circuit with a common anode.

The rectifier circuit comprises two cathode terminals 51A and 51B intended to receive an alternating voltage Vin, and an anode terminal 55, for example intended to be set to a reference potential such as ground. Two identical branches 57A and 57B are respectively connected between terminal 55 and terminals 51A and 51B. Each of the branches 57A and 57B comprises a Schottky diode, respectively 61A and 61B, and an MOS transistor, respectively 63A and 63B, connected in series. The common point or common node 67A between the diode 61A and the transistor 63A is connected to the gate of the transistor 63B. The midpoint or common node 67B between the diode 61B and the

B16128ER - 17-TO-0159 transistor 63B is connected to the gate of transistor 63A. The transistors 63A and 63B are, for example, N-channel enhancement transistors. The transistors 63A and 63B are for example power transistors. The anodes of diodes 61A and 61B are for example connected to terminal 55.

In operation, the voltage VgA between the gate and the source (node 67A) of the transistor 63A is equal to the voltage VdB between the node 67B and the terminal 55 minus the voltage VdA between the node 67A and the terminal 55. The voltage VgB between the gate and the source (node 67B) of transistor 63B is equal to -VgA. Thus, when the transistor 63A is on, the transistor 63B is blocked, and, conversely, when the transistor 63B is on, the transistor 63A is blocked. More particularly, during a negative alternation of the voltage Vin between the terminal 51A and the terminal 51B, the diode 61B is blocked. If the voltage VdB is sufficient for the voltage VgA to be greater than the threshold voltage Vth of the transistors 63A, the transistor 63A and the diode 61A are conducting and a current I flows from terminal 55 to terminal 51A. The branch 57A is then equivalent to a pass-through diode. Furthermore, in branch 57B, the transistor 63B is blocked because VgB = -VgA and the leakage current in the diode 61B is substantially equal to the leakage current in the transistor 63B. The branch 57B is then equivalent to a blocked diode. During a positive alternation of the voltage Vin, the operation of the rectifier circuit is symmetrical to that described above. In other words, when the voltage VdA is sufficient for the voltage VgB to be greater than the threshold voltage Vth of the transistor 63B, the branches 57B and 57A are respectively equivalent to a pass-through diode and to a blocked diode.

FIG. 5 represents an alternative embodiment of the rectifier circuit of FIG. 4.

This rectifier circuit is identical to that of FIG. 4 except that each of the branches 57A and 57B further comprises a resistor, respectively 65A and 65B,

B16128ER - 17-TO-0159 connected in parallel with its transistor 63A or 63B. This circuit operates in the same way as the circuit of FIG. 4 with the difference that, when the branch 57A is blocked, the leakage current of the blocked Schottky diode 61A circulates in whole or in part in the resistor 65A to fix the voltage at diode 61A terminals so that transistor 63B is on. Symmetrically, when the branch 57B is blocked, the leakage current of the Schottky diode 61B circulates in whole or in part in the resistor 65B to fix the voltage across the terminals of the diode 61B so that the transistor 63A is on.

When the rectifier circuit of FIG. 4 or 5 replaces bipolar diodes of a converter, for example the bipolar diodes of the lower half-bridge of the converter, the efficiency of the converter is thereby improved, at least at low power. Indeed, at low power, the voltage drop across a branch 57A or 57B pass is less than the voltage drop across a bipolar diode. As for the rectifier element of FIG. 2, one takes advantage here of the fact that the threshold voltage of a Schottky diode is lower than that of a bipolar diode.

According to one embodiment, the rectifier circuit of FIG. 4 or 5 replaces the lower half-bridge (diodes D2 and D4) of the converter of FIG. 1, the terminals 51A, 51B and 55 of the rectifier circuit being respectively connected to the terminals 1 , 3 and 7.

According to another embodiment, the rectifier circuit of FIG. 4 or 5 replaces the lower half-bridge (rectifier elements 21A and 21B) of the converter of FIG. 3, the terminals 51A, 51B and 55 of the rectifier circuit being respectively connected to the terminals 31, 33 and 37. The use of the rectifier circuit of FIG. 4 or 5 rather than rectifier elements 21 makes it possible to dispense with a possible voltage source Vp.

Alternatively, a bipolar diode is connected in parallel with each of the branches 57A and 57B of the circuit

B16128EN - 17-TO-0159 rectifier of Figure 4 or 5, the anode of the bipolar diode being connected to terminal 55. The bipolar diodes make it possible to protect this circuit against strong current peaks likely to deteriorate it. Bipolar diodes can further improve the efficiency of the converter, especially at high power.

FIG. 6 represents another embodiment of a rectifier circuit.

The rectifier circuit comprises two cathode terminals 71A and 71B intended to receive an alternating voltage Vin, and an anode terminal 75, for example intended to be set to a reference potential such as ground. Two identical branches 77A and 77B are respectively connected between terminal 75 and terminals 71A and 71B. Each of the branches 77A and 77B comprises, in parallel, a MOS transistor, respectively 81A and 81B, and a voltage divider, respectively 83A and 83B. Each of the voltage dividers 83A and 83B is for example a resistive voltage divider comprising two resistors in series, respectively 85A and 87A, and 85B and 87B. The transistors 81A and 81B are, for example, enhancement transistors. The transistors 81A and 81B are for example power transistors. Transistors 81A and 81B, for example with N channel, their sources then being connected to terminal 75. Each of branches 77A and 77B also comprises a component, respectively 89A and 89B, for example a resistor, connected between the gate and the source of the transistor 81A or 81B of this branch to allow the gate-source capacitor of the transistor to be discharged. Each of the branches 77A and 77B further comprises a switch, respectively 91A and 91B, for example a bipolar transistor of the NPN type. The transistors 91A and 91B are, in the example shown, in series between the gates of the transistors 81A and 81B. The midpoint 93 of this series association is intended to receive a continuous and substantially constant voltage Vp, referenced to earth 75. In this example, the collectors of the transistors 91A and 91B are on the side

B16128ER - 17-TO-0159 of node 93. The respective bases of transistors 91A and 91B are connected to nodes 95B and 95A, that is to say at the output of the voltage divider of the opposite branch.

The voltage Vp is chosen so that, when the switch 91A, 91B of a branch 77A, 77B is closed, the voltage between the gate and the source of the transistor 81A, 81B of this branch is greater than the threshold voltage Vth of the transistor.

In operation, during a negative alternation of the voltage Vin between the terminal 71A and the terminal 71B, the switch 91B, controlled by the voltage divider 83A from the voltage VA, is open. The transistor 81B is then blocked. In addition, the switch 91A of the branch 77A, controlled by the voltage divider 83B from the voltage VB, is closed if the voltage VB is sufficient. The transistor 81A is then on. Symmetrically, during a positive alternation of the voltage Vin, the transistor 81B is on if the voltage VA is sufficient, and the transistor 81A is blocked. In practice, the minimum value of the voltage VA, VB causing the closing of the corresponding switch 91B, 91A is determined by the voltage divider 83A, 83B controlling the switch, that is to say here by the values of the resistors 85A, 87A, and 85B, 87B. Furthermore, when the voltages VA and VB are such that the two switches 91A and 91B are open, the intrinsic diodes of the MOS transistors 81A and 81B can allow the circulation of a current from terminal 75 to terminal 71A or 71B.

The voltage drop in a branch 77A, 77B, in which the transistor 81A, 81B is on, is lower, at least at low power, than in an element 21 passing or in a branch 57A, 57B passing through the rectifier circuit of FIG. 4 or 5. Here, advantage is taken of the fact that the branches 77A and 77B do not include a Schottky diode. As a result, a converter comprising the rectifier circuit of FIG. 6 has an improved efficiency, at least at low power, compared to

B16128ER - 17-TO-0159 to that of a converter with rectifier elements 21 or of a converter comprising the rectifier circuit of FIG. 4 or

5.

According to one embodiment, the rectifier circuit of FIG. 6 replaces the lower half-bridge (diodes D2 and D4) of the converter of FIG. 1, for example by connecting the terminals 71A, 71B and 75 of the rectifier circuit to the respective terminals 1 , 3 and 7 of the converter.

According to another embodiment, the rectifier circuit of FIG. 6 replaces the lower half-bridge (elements 21A and 21B) of the converter of FIG. 3, for example by connecting the terminals 71A, 71B and 75 of the rectifier circuit to the respective terminals 31, 33 and 37 of the converter.

As a variant, a bipolar diode is connected in parallel with each of the branches 77A and 77B of the rectifier circuit, the anode of the bipolar diode being connected to terminal 75. The bipolar diodes make it possible to protect this circuit against strong current peaks liable to deteriorate it. Bipolar diodes can further improve the efficiency of the converter, especially at high power.

Note that it is generally not necessary to provide an additional source to generate the voltage Vp. Indeed, it suffices to use the supply voltage of the control circuit (19, FIG. 1; 47, FIG. 3) of the converter.

By way of example, in the embodiments described above in relation to FIGS. 1 to 6, the power MOS transistors support up to several hundred volts, for example 600 V, between their conduction terminals (drain-source ). Schottky diodes have for example a breakdown voltage lower than a few tens of volts, for example equal to 15 V, and are said to be at low voltage. The alternating voltage Vin applied to the converters and / or to the rectifier circuits has for example an amplitude which can reach one or several hundred volts.

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Particular embodiments have been described. Various variants and modifications will appear to those skilled in the art. In particular, the rectifier element 21 can be used to replace a bipolar diode in other electronic circuits than converters.

Switching converters have been described in which the input terminals are connected to the output terminals via one or more booster type circuits. The embodiments described are easily transposed to any type of AC / DC voltage converter, for example of step-down or Buck type, Buck-Boost type, Cùk type, Forward type, Flyback type etc. In addition, the described embodiments of rectifier element 21 are transposed to any type of AC / DC voltage converter, whether single-phase or three-phase.

The rectifier elements and circuits described above can also be used in chopper converters in which the freewheel diode (s) are replaced by switches controlled in synchronism with the chopper switch (s).

Various embodiments with various variants have been described above. Note that those skilled in the art can combine various elements of these various embodiments and variants without showing inventive step.

Claims (12)

1. Rectifier element (21) comprising a MOS transistor (23) connected in series with a Schottky diode (25), configured to receive a substantially constant voltage (Vp) between the control terminal of the transistor and the terminal (29) of the Schottky diode opposite the transistor. 2. Rectifier element according to claim 1, in which a source of the transistor (23) is connected to a cathode of the Schottky diode (25). 3. Rectifier element according to claim 1 or 2, wherein the constant voltage (Vp) is chosen so that the transistor (23) is on when the Schottky diode (25) is on. 4. Rectifier element according to any one of claims 1 to 3, in which the transistor (23) is of the N-channel type with enrichment. 5. Voltage converter comprising at least one rectifier element (21; 21A, 21B) according to any one of claims 1 to 4. 6. Converter according to claim 5, wherein a first rectifier element (21; 21B) is connected between a first input terminal (3; 33) of the converter and a first output terminal of the converter (7; 37), l the anode (29; 29B) of the Schottky diode (25; 25B) of the first rectifier element being connected to the first output terminal. 7. Converter according to claim 6 in its attachment to claim 2, wherein a second rectifier element (21; 21A) is connected between a second input terminal (1; 31) of the converter and the first output terminal (7 ; 37), the anode (29; 29A) of the Schottky diode (25; 25A) of the second rectifier element being connected to the first output terminal. 8. Converter according to claim 6 or 7, further comprising: B16128EN - 17-TO-0159 a first inductive element (L; Ll) and at least a first diode (D; D5) connected in series between the second input terminal (1; 31) of the converter and the second output terminal (5; 35) of the converter; and 5 a first switch (17; 43) connecting the first output terminal (7; 37) to the midpoint (15; 39) between the first inductive element and the first diode. 9. Converter according to claim 8, further comprising: A second inductive element (L2) and a second diode (D6) connected in series between the first input terminal (33) and the second output terminal (35); and a second switch (45) connecting the first output terminal (37) to the midpoint (41) between the second 15 inductive element and the second diode. 10. Converter according to claim 8, further comprising a second diode (Dl) connected between the second input terminal (1) and a terminal (9) of the first inductive element (L) opposite the first diode (D). 11. Converter according to claim 10, further comprising a third diode (D3) connected between the first input (3) and said terminal (9) of the first inductive element (L).