EP4091250A1 - Procédé d'actionnement d'un commutateur d'alimentation à semi-conducteur, circuit d'actionnement d'un commutateur d'alimentation à semi-conducteur et disjoncteur électronique - Google Patents

Procédé d'actionnement d'un commutateur d'alimentation à semi-conducteur, circuit d'actionnement d'un commutateur d'alimentation à semi-conducteur et disjoncteur électronique

Info

Publication number
EP4091250A1
EP4091250A1 EP21823774.1A EP21823774A EP4091250A1 EP 4091250 A1 EP4091250 A1 EP 4091250A1 EP 21823774 A EP21823774 A EP 21823774A EP 4091250 A1 EP4091250 A1 EP 4091250A1
Authority
EP
European Patent Office
Prior art keywords
current
circuit
voltage
value
time
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Pending
Application number
EP21823774.1A
Other languages
German (de)
English (en)
Inventor
Marvin TANNHÄUSER
Fabian Döbler
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Siemens AG
Original Assignee
Siemens AG
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Siemens AG filed Critical Siemens AG
Publication of EP4091250A1 publication Critical patent/EP4091250A1/fr
Pending legal-status Critical Current

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Classifications

    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/51—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used
    • H03K17/56—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices
    • H03K17/687—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being field-effect transistors
    • H03K17/6871—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being field-effect transistors the output circuit comprising more than one controlled field-effect transistor
    • H03K17/6874—Electronic switching or gating, i.e. not by contact-making and –breaking characterised by the components used by the use, as active elements, of semiconductor devices the devices being field-effect transistors the output circuit comprising more than one controlled field-effect transistor in a symmetrical configuration
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02H—EMERGENCY PROTECTIVE CIRCUIT ARRANGEMENTS
    • H02H9/00—Emergency protective circuit arrangements for limiting excess current or voltage without disconnection
    • H02H9/001—Emergency protective circuit arrangements for limiting excess current or voltage without disconnection limiting speed of change of electric quantities, e.g. soft switching on or off
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/08—Modifications for protecting switching circuit against overcurrent or overvoltage
    • H03K17/082—Modifications for protecting switching circuit against overcurrent or overvoltage by feedback from the output to the control circuit
    • H03K17/0822—Modifications for protecting switching circuit against overcurrent or overvoltage by feedback from the output to the control circuit in field-effect transistor switches
    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K2217/00—Indexing scheme related to electronic switching or gating, i.e. not by contact-making or -breaking covered by H03K17/00
    • H03K2217/0009—AC switches, i.e. delivering AC power to a load

Definitions

  • the invention relates to a method for driving a power semiconductor switch, a driving circuit for a power semiconductor switch and an electronic protective switch.
  • inrush currents When switching on electronic loads, such as loads that have switched-mode power supplies and/or rectifiers, to an AC voltage supply, high inrush currents often occur, which are also referred to as inrush currents. Current peaks of several hundred amperes can occur even in the case of switched-mode power supplies with a comparatively low rated power, for example switched-mode power supplies with a rated power of less than 100 W. These inrush currents can lead to the undesired triggering of conventional miniature circuit breakers (MCB for short).
  • MCP miniature circuit breakers
  • LED lamps which are increasingly displacing other lamps in households and in building technology.
  • LED lamps for operation on the 230V mains have, among other things, a power pack which has a capacitive behavior when it is switched on.
  • many of these light sources are often connected in parallel and are therefore switched on at the same time, which means that the inrush current is multiplied accordingly and can lead to an overload of the circuit and/or to the MCB being triggered undesirably.
  • the high inrush current load can also lead to increased wear in classic switching devices such as relays, Contactors or switches, for example when the high inrush current occurs in combination with the bouncing of a mechanical contact.
  • the bouncing in connection with the high current can then lead to short-term arcing at the switching contacts, which in turn result in contact erosion and corresponding wear of the switching element and, in extreme cases, cause the contacts to weld.
  • One object of the present invention is therefore to provide an improved method for driving a power semiconductor specify conductor switch and an improved control circuit for a power semiconductor switch and an improved electronic circuit breaker, which are suitable for use in circuits with potentially very high inrush currents.
  • An advantage of the invention can be seen in the fact that excessive inrush currents are suppressed by briefly interrupting the circuit when an inrush current that is too high is detected and then switching it on again, with the time between switching off and switching on again being a maximum of one period is equivalent to .
  • the inrush current that is limited by the method precharges the capacitive elements of the consumers, so that the inrush current is lower when the system is switched on again.
  • the circuit is switched on again before the next, d. H . before the zero crossing of the voltage following switch-off. In this way, the inrush current is additionally limited when switching on again.
  • inrush currents are reliably prevented by means of the present invention and, unlike in the prior art, it is not necessary to design the entire circuit for high inrush currents generated by permissible consumers. It is also not necessary to deliberately slow down protective switching devices, for example using a protective switching device with a C characteristic instead of a protective switching device with a B characteristic, in order to prevent the protective switching device from tripping incorrectly when a properly functioning consumer that is permissible for the circuit is connected.
  • the inrush current is advantageously limited centrally by the SCCB, so that special components for inrush current limitation such as DALI circuits and phase angle controls can be dispensed with, which means that costs can be saved on the consumer side.
  • the method according to the invention can advantageously ensure that an SCCB can be used at all without the risk of the SCCB being destroyed by excessively high inrush currents.
  • At least a given SCCB can be expanded by the method according to the invention and thus adapted to circuits with electrical loads that typically have a high inrush current and a low continuous current.
  • the method according to the invention can be scaled as desired and can be used in almost any voltage and current range.
  • a further advantage is that in modern SCCBs the necessary measuring equipment for detecting the instantaneous values for current and voltage is already available or can be implemented with very little additional effort. Furthermore, a controller is usually present anyway, so that the present invention can often be implemented with existing hardware.
  • Fig. 1 shows a schematic representation of a semiconductor circuit breaker according to an exemplary embodiment of the present invention
  • FIG. 2 shows an exemplary time course of current and voltage in connection with the application of an exemplary embodiment of the method according to the invention
  • FIG. 3 an exemplary sequence of an exemplary embodiment of the method according to the invention.
  • FIG. 4 shows an example of current and voltage over time in connection with the use of a further exemplary embodiment of the method according to the invention.
  • Fig. 1 shows a schematic representation of a semiconductor miniature circuit breaker (hereinafter: SCCB) 10 according to an embodiment of the present invention.
  • SCCB 10 has network-side terminals 11A, 11B, with which SCCB 10 can be connected to a power supply network (not shown).
  • a first line-side terminal 11A is used to connect to the neutral conductor N, and a second line-side terminal 11B is used to connect to the phase conductor L .
  • a voltage measuring device 12 serves to measure the voltage on the input side of the SCCB 10 .
  • the voltage values determined by the voltage measuring device 12 are sent to a controller 13 (represented by a dashed line). Included
  • the voltage measuring device 12 can be designed in such a way that a signal representing the voltage between the input-side terminals 11A and 11B is continuously fed to the controller 13 in analog form.
  • the voltage between the input-side terminals 11A and 11B is sampled by the voltage measuring device 12 at discrete points in time and supplied to the controller 13 as a time-discrete digital signal, with the sampling frequency being selected in relation to the mains frequency in such a way that the controller 13 can Signal follow the time course of the voltage present at the input-side terminals 11A, 11B, in particular the times of the zero crossings, can determine, if necessary. by interpolation.
  • the neutral conductor connected to the first mains-side terminal 11A is connected directly to a first output-side or connected to the load side terminal 18A of the SCCB 10 .
  • the applied to the second mains-side terminal 11B phase L is by means of a power semiconductor circuit 14A, 14B with a second output side or. consumer-side terminal 18B connected.
  • the power semiconductor circuit has in the example of FIG. 1 two self-commutated power semiconductor switches 14A, 14B, which are controlled by the controller 13 and the phase L to the second output side or. Switch through terminal 18B on the consumer side or switch off the connection between the second network-side terminal 11B and the second consumer-side terminal 18B.
  • power semiconductors connected in parallel can also be used (not shown).
  • the power semiconductor circuit 14A, 14B is connected in parallel with an energy absorber 16, which is connected between a mains-side bridging terminal 15A and a load-side bridging terminal 15B and serves to limit the voltage and thus protect the power semiconductor circuit during certain switching events.
  • a current measuring device 17 is arranged in the phase conductor between the power semiconductor circuit 14A, 14B and the second load-side terminal 18B and is used to measure the load current in the phase conductor.
  • the current measuring device 17 can be designed in such a way that a signal representing the current flowing in the phase conductor is continuously transmitted in analog form to the controller 13 (indicated by the dashed line between the current measuring device 17 and controller 13).
  • the current is recorded by the current measuring device 17 at discrete points in time and supplied to the controller 13 as a time-discrete digital signal, with the sampling frequency being selected so high that, for example, a sharply rising current curve caused by a short circuit is detected in good time for the respective application and can be translated into appropriate actions.
  • Three electrical loads 20 , 30 , 40 are connected to the load-side terminals 18A, 18B of the SCCB 10 .
  • Consumers 30 and 40 are any consumers, which are only shown to make it clear that the method described below for limiting the inrush current of the consumer 20 can also be carried out if other consumers 30, 40 in the respective circuit that is through the SCCB 10 is secured, are already active before the consumer 20 is turned on, which corresponds to a typical practical application.
  • Consumer 20 is in the example of FIG. 1 a consumer of the type described above, i. H . a consumer with low continuous power and high inrush current, for example LED lighting for a larger room comprising a plurality of individual LED light sources. This is indicated by a rectifier 21 and a capacitive load 22 . In exemplary embodiments of the invention, both the rectifier 21 and the capacitive load are representative of a plurality of rectifiers and capacitive loads connected in parallel, as is the case, for example, with LED lighting in FIG a large hall is the case. Consumer 20 can be switched on or off by a switch 23 . Switch 23 can be a mechanical wall switch that can be actuated by a user or an electronically controlled switch.
  • FIG. 2 shows in a single diagram an exemplary time profile 220 of the current I recorded by the current measuring device 17 (right scale axis of the diagram) and an exemplary time profile 210 of the voltage U recorded by the voltage measuring device 12 (left scale axis of the diagram).
  • controller 13 is set up in such a way that currents over 80 A are not permitted.
  • controller 13 controls the power semiconductor circuit in such a way that it blocks, the current flow in phase conductor L between input terminal 11B and output terminal 18B is interrupted, whereupon the current and also the measured current value drop to zero.
  • a zero-current phase 230 usually occurs around the voltage zero crossing due to the already partially charged capacitances. This circumstance and the term “zero current phase” are explained in detail further below.
  • the controller 13 decides that there was no short circuit.
  • the SCCB 10 continues to operate by monitoring the current.
  • the time described above with "shortly before reaching the zero crossing" for switching on the power semiconductor circuit again by the controller 13 can preferably be selected as the time at which the phase angle of the sinusoidal mains voltage, d. H . at the input terminals 11A, 11B of the SCCB 10, is between 160° and 170° or between 340° and 350°, depending on whether the interruption of the circuit by the controller during the positive or during the negative half-wave of the mains voltage.
  • the zero-current phase can be used in exemplary embodiments of the present invention to distinguish a short circuit from a switch-on process. This is because a short circuit typically shows a characteristic current-time profile and practically no zero-current phase, because a short circuit exhibits ohmic behavior, i. H . the current-time curve shows high values for the current and is very similar to the voltage-time curve. The case is different when a load 20 is switched on, which has capacitive elements and causes a very high inrush current 221: here the expected current-time curve around the zero crossing of the voltage is characterized by low current values, which can be zero if otherwise no consumers are switched on in the circuit - hence the term "zero current phase" used here for simplification.
  • Fig. 3 illustrates the above in connection with FIG. 2 described sequence of an exemplary embodiment of the method according to the invention.
  • the method starts with an initialization step 310, which provides a maximum current value, for example by reading it out from a memory, and makes it available for the monitoring step 320.
  • step 320 the current current value is compared with the maximum current value. If the current current value does not exceed the maximum current value, then the power semiconductor circuit 14A, 14B remains switched on, step 330, and the method continues with step 320.
  • step 340 the power semiconductor circuit 14A, 14B is switched off, step 340, and it is checked in step 350 whether the short circuit or Error can be detected because, for example, in step 340 incremented counter (not shown) exceeds a certain value n.
  • step 350 If it is determined in step 350 that there is a short circuit or an error, the method ends with step 370 and the power semiconductor circuit 14A, 14B remains switched off until, for example, the short circuit has been eliminated and it is switched on again manually (not shown).
  • a disconnector arranged in series with the power semiconductor switch can be switched off (not shown). This isolating switch is preferably arranged on the network side of the power semiconductor switch in the conductor LI, but can also be arranged on the load side of the power semiconductor switch. It is possible to use single-pole or two-pole disconnectors.
  • step 350 If it is determined in step 350 that the conditions for determining a short circuit or a fault have not been met, the power semiconductor circuit 14A, 14B is switched on again in step 360, with the above with reference to FIG. 2 made remarks apply.
  • re-entering monitoring step 320 from step 360 it can also be provided that another, for example a lower, maximum current value is used instead of the previous maximum current value. Additionally or alternatively, when re-entering monitoring step 320 from step 360, it can be provided that the presence of a zero-current phase as in connection with FIG. 2 is monitored and a short circuit or fault is detected and the method is terminated if no zero-current phase occurs (not shown).
  • FIG. 4 shows (like Fig. 2) in a single diagram an exemplary time profile 220A of the current I recorded by the current measuring device 17 (right-hand scale axis of the diagram) and an exemplary time profile 210 of the voltage U recorded by the voltage measuring device 12 (left-hand scale axis of the diagram).
  • a time profile 220A of the current I recorded by the current measuring device 17 (right-hand scale axis of the diagram)
  • an exemplary time profile 210 of the voltage U recorded by the voltage measuring device 12 left-hand scale axis of the diagram.
  • controller 13 is set up in such a way that currents over 50 A are initially not permitted. When a current value of 50 A is reached, controller 13 controls the power semiconductor circuit in such a way that it blocks, ie the current flow in the phase conductor is interrupted, whereupon the measured value for the current returns to zero.
  • the control signals output to the power semiconductor circuit are shown as a digital signal sequence 240 at the lower edge of the diagram in FIG.
  • Controller 13 thus controls the power semiconductor circuit again in such a way that it blocks the current flow in the phase conductor i.e. is interrupted, whereupon the current and its measured value return to zero.
  • the power semiconductor circuit can be switched on again immediately afterwards by the controller 13, still shortly before or even during the zero crossing of the voltage U (second switching on again), whereupon, due to the diodes in the rectifier 21 and/or the partially already precharged capacitance 22 a new increase in current 224 only occurs when the amount of the voltage exceeds the threshold voltage of the diodes in the rectifier and/or the voltage of the already partially charged capacitances.
  • the current also exceeds a maximum value at point 224 after the second switch-on, the maximum value on the second switch-on being selected to be lower than the maximum value on the first switch-on again in the illustrated exemplary embodiment and being, for example, 40 A.
  • the controller 13 controls the power semiconductor circuit again so that it blocks, the current flow in the phase conductor is thus interrupted, whereupon the current and its measured value return to zero.
  • the controller 13 switching the power semiconductor circuit on.
  • the same time interval before reaching the voltage zero crossing can be selected as when switching on again for the first time, or a somewhat later point in time, closer to the zero crossing of the voltage, can be selected for the third switching on again.
  • the controller 13 switching the power semiconductor circuit on.
  • the same time interval before reaching the voltage zero crossing can be selected as for the third restart, or a slightly later point in time, closer to the zero crossing of the voltage, can be selected for the fourth restart, or a slightly earlier point in time, further from the zero crossing, can also be selected the point in time away from zero voltage can be selected for the fourth switch-on again.
  • the controller 13 again controls the power semiconductor circuit in such a way that it blocks, the current flow in the phase conductor is thus interrupted, whereupon the current and its measured value go back to zero.
  • the controller 13 leaves the power semiconductor circuit in the switched-on state and continues the process with monitoring the current, using the original maximum value of 50 A instead of the modified maximum value of 40 A either immediately or after a definable time has elapsed.
  • the method consisting of the steps of switching the power semiconductor off and on again can be repeated up to n times. If, before the nth repetition is reached, the current no longer exceeds the maximum value, then the controller determines a normal switch-on process. If this case does not occur, ie if the maximum value for the current is also exceeded the nth time the process is repeated, the process is terminated and an error is detected and, if necessary, signaled to an operator.
  • the maximum value can be constant for each switch-on again or can be redefined for each switch-on again, for example reduced in order to limit the I 2 t load on the overall system.
  • the point in time for switching on again can be varied with respect to the zero crossing, for example by setting the point in time for switching on again closer to the zero crossing with each repetition, in order to achieve a lower inrush current simply because of the then lower absolute value of the voltage, which nevertheless loads on the consumer side, in particular the intermediate circuit capacitances of the rectifiers, or to to shift the restart to the zero-current phase expected for rectifier consumers and to determine the short-circuit case if unexpectedly high currents occur in this phase.
  • n for the number of repetitions depends on u . a. according to which other consumers 30, 40 are connected to the circuit secured by the SCCB 10 and in particular according to how many half-waves may fail without malfunctions or damage occurring to the other consumers. This can result from standards that apply to the respective circuit, or can be decided on a case-by-case basis based on the typically connected consumers.
  • n 5 .
  • n ⁇ 5 applies, and in still other exemplary embodiments, n ⁇ 10 applies.
  • the number n can depend not only on the type of consumer, as explained above, but also on the total load already present in the circuit in the specific case, which is caused by the other active consumers 30 , 40 .
  • the maximum current value can also be made dependent on this load that is already present, in particular the initial maximum current value and all other maximum current values can be selected to be smaller than the standard maximum current value if there is already a load in the circuit, especially if this existing load is more than 50% or more, for example more than 75% or more than 90% of the nominal load or . of the permissible continuous current of the circuit is .
  • the circuit when an error is detected, the circuit is switched on again automatically after a configurable waiting time, which can be several milliseconds to seconds or several seconds to minutes, and using the method described above, which then runs again, to determine whether the error is still present or has subsided, for example in the case of a thermally induced temporary malfunction of a consumer.
  • a configurable waiting time which can be several milliseconds to seconds or several seconds to minutes
  • the predefinable time can be, for example, one network period, ie 20 ms in the case of European household networks, or also several network periods up to several seconds.
  • the counter sc_cnt can be compared with another limit value k and restarting after a short-circuit current event or Error event is only suppressed when sc_cnt > k, so that events classified as short-circuit current events do not immediately lead to the detection of an error, but only when more than k short-circuit current events have been detected, an error is detected and output.
  • k 0 can be chosen, d . H . the first short-circuit current event already leads to the detection of a fault, or k>0 can be selected, preferably 0 ⁇ k ⁇ n. It can also be specified for the counter sc_cnt that it is decremented step by step after a definable time until it reaches its starting value, for example zero , has reached . This predefinable time can also be one mains period, for example, or it can be selected to be longer than the predefinable time after which the counter inr_cnt is decremented. The predefinable time that is awaited before the counter sc_cnt is decremented step by step is preferably several seconds and, in certain exemplary embodiments, also minutes.
  • the time period in which the load 20 that is equipped with a rectifier and is to be switched on does not consume any current because the forward voltage of the rectifier diodes was not reached is simply referred to as the “zero current phase”.
  • zero current phase is generally the period in which the situation in FIG. 1 circuit shown is not influenced by switch-on processes of the newly connected consumer 20, that is typically the period in which the consumer 20 has no or does not cause any significant additional current flow, for example because the capacitances 22 are already partially charged.
  • a current only begins to flow into the load 20 after switching on again when the instantaneous value of the voltage on the load side of the SCCB 10 exceeds the value of the voltage present on the DC voltage side at the rectifier 21, plus the threshold voltage of the diodes located in the current path. exceeds .
  • the zero-current phase results from the fact that no charge flows to a voltage of the capacitors 22 already defined by the previous current pulse(s) as long as the instantaneous value of the voltage fed into the consumer 20 is lower than this defined voltage.
  • this can also be easily expressed as a phase angle or time span using the sine relationship of the voltage curve, see below for details.
  • this defined voltage value can be determined or calculated at least approximately by measuring the voltage between the load-side terminals 18A, 18B. based on such a measurement as a comparison criterion.
  • the defined voltage value can be established based on an estimate, in particular based on an estimate based on the number of restart processes. This can be based on the regular switch-on behavior (e.g. course of current, voltage and number of required switch-on cycles) of typical loads 20 that can be connected to the specific AC circuit.
  • error detection can also be based on the current-time profile in the expected zero-current phase or as defined above, d. H .
  • the current time profile of the current is compared with the current-time profile.
  • This expected current-time profile can be, for example, the current-time profile of a short circuit or an impermissibly high load, and the short circuit or A fault is detected when the actual current-time profile corresponds at least approximately to such a short-circuit or impermissible overload profile.
  • the current time profile of the current is compared with a current-time profile that is expected when there is no short circuit or impermissible overload case.
  • a desired current-time profile can be predetermined for a specific AC circuit by configuration and can correspond, for example, to the current-time profile of the circuit loaded with its nominal load.
  • the target current-time profile can be selected as the current-time profile before the first determination that a predetermined maximum value, ie z. B. before the first inrush current event or Short-circuit current event 221, was present regularly.
  • “regularly” means the “regular case”, which can be determined in various ways. For example, the time course of the current between a selectable phase angle of the voltage before its zero crossing, z. B. - 10 °, up to a selectable phase angle of the voltage after crossing zero, e.g. B. + 10°, can be stored again as a reference for each zero crossing.
  • This reference is used when an inrush current event or Short-circuit current event was detected in order to compare the zero-current phase after this event with the reference and to exceed a certain tolerance tending deviation to make the determination that a short-circuit current event is present and otherwise, so if the current curve and the reference differ less than a certain tolerance, to make the determination that an inrush current event is present.
  • the phase angles mentioned are preferably selected in such a way that the absolute values of the voltage are suitable for charging the (possibly already pre-charged) capacitances in the consumer to be newly connected, i.e. by a certain amount higher than the voltage of these capacitances that has already been reached, which in turn, for example, comes from the previous course of the switch-on process can be derived.
  • the zero current phase is defined as a period of 0.5 milliseconds around the zero crossing of the voltage, this period preferably being placed symmetrically around the zero crossing, i.e. beginning 0.25 milliseconds before the zero crossing and ends 0.25 milliseconds after the zero crossing.
  • this period of time can be chosen to be longer in order to provide a higher voltage for further charging of the already partially precharged capacitances.
  • a zero-current phase of 1 millisecond can be selected, which is preferably in turn placed symmetrically around the zero crossing, ie begins 0.5 milliseconds before the zero crossing corresponding to a voltage value of approximately 50 V and ends 0.5 milliseconds after the zero crossing.
  • the zero-current phase can also be described as follows: abs (I (t) ) ⁇ l_Lim(t) .
  • I(t) is the value of the current in the SCCB 10 determined by the current measuring device 17
  • I_Lim(t) is the current expected during the zero current phase
  • abs( ) is the absolute value.
  • I_Lim(t) can be constant, i.e. independent of t.
  • I Lim(t) describes the expected course of the current mes in the considered time window around the zero crossing. A tolerance of, for example, 10% or 20% or 25% or 50% of the actually expected value can also be taken into account.
  • the value determined by the voltage measuring device 12 can be used without further ado for U(t), or an additional load-side voltage measuring device is used (not shown).
  • a capacitive load is slightly charged with each reclosing process, so that with an increasing number of reclosing processes, a slightly lower increase in the current-time curve can be assumed, while the same increase can always be expected in the case of a short circuit.
  • this consideration is extended to the curve shape of the current-time profile between switching the power semiconductor circuit on again and switching it off immediately thereafter because the maximum value .
  • the curve shape of the current-time profile is compared with a predefinable error curve shape. A fault/short-circuit event is recognized when the curve shape of the current-time curve runs at least predominantly above the fault curve shape. Otherwise an inrush current event is detected.

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  • Emergency Protection Circuit Devices (AREA)
  • Rectifiers (AREA)

Abstract

L'invention se rapporte à un procédé d'actionnement d'un commutateur d'alimentation à semi-conducteur (14A, 14B) d'un circuit CA pouvant être activé ou désactivé par le commutateur d'alimentation à semi-conducteur. Le procédé consiste : a) à déterminer la valeur de courant en cours et la valeur de tension en cours du circuit CA ; b) à déterminer si la valeur de courant en cours dépasse une valeur maximale pouvant être prédéfinie et si tel est le cas, c1) à générer un signal d'actionnement pour désactiver le circuit de courant, c2) à générer un signal d'actionnement pour activer le circuit de courant dans une période postérieure à la génération du signal d'actionnement pour désactiver le circuit de courant, la période étant inférieure ou égale à la durée de la période de la tension, et c3) à déterminer si la valeur de courant en cours dépasse une valeur maximale pouvant être prédéfinie, qui correspond à la valeur maximale précédente ou est inférieure à la valeur maximale précédente, après activation du circuit de courant. Si tel est le cas, les étapes c1), c2) et c3) sont répétées. Dans l'étape d), un dysfonctionnement est détecté, et le signal d'actionnement est émis en permanence afin de déconnecter le circuit de courant, et le procédé est arrêté si le nombre de répétitions des étapes c1), c2), et c3) dépasse une valeur n. Sinon, à l'étape e), la génération du signal d'actionnement pour activer le circuit de courant est poursuivie si, dans l'étape b) ou étape c3), il a été déterminé que la valeur de courant en cours dépasse la valeur maximale respective, et le procédé est poursuivi par l'étape a).
EP21823774.1A 2020-12-21 2021-11-22 Procédé d'actionnement d'un commutateur d'alimentation à semi-conducteur, circuit d'actionnement d'un commutateur d'alimentation à semi-conducteur et disjoncteur électronique Pending EP4091250A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE102020216405.3A DE102020216405A1 (de) 2020-12-21 2020-12-21 Verfahren zum Ansteuern eines Leistungshalbleiterschalters, Ansteuerschaltung für einen Leistungshalbleiterschalter sowie elektronischer Schutzschalter
PCT/EP2021/082506 WO2022135808A1 (fr) 2020-12-21 2021-11-22 Procédé d'actionnement d'un commutateur d'alimentation à semi-conducteur, circuit d'actionnement d'un commutateur d'alimentation à semi-conducteur et disjoncteur électronique

Publications (1)

Publication Number Publication Date
EP4091250A1 true EP4091250A1 (fr) 2022-11-23

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US (1) US20230344424A1 (fr)
EP (1) EP4091250A1 (fr)
CN (1) CN115244853A (fr)
DE (1) DE102020216405A1 (fr)
WO (1) WO2022135808A1 (fr)

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LU502584B1 (de) * 2022-07-28 2024-02-01 Phoenix Contact Gmbh & Co Gleichspannungsschaltgerät und Schaltvorrichtung insbesondere zur Erdschlusserkennung während eines Einschaltvorgangs zum Einschalten einer angeschlossenen Gleichspannungslast sowie ein Verfahren zum Betreiben des Gleichspannungsschaltgeräts bzw. der Schaltvorrichtung
DE102022209018A1 (de) * 2022-08-31 2024-02-29 Siemens Aktiengesellschaft Schutzschaltgerät und Verfahren

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US7369386B2 (en) * 2003-06-06 2008-05-06 Electronic Theatre Controls, Inc. Overcurrent protection for solid state switching system
JP2007236061A (ja) 2006-02-28 2007-09-13 Ntt Facilities Inc 過電流防止装置
JP5054928B2 (ja) * 2006-04-24 2012-10-24 株式会社オートネットワーク技術研究所 電力供給制御装置
DE102008018619B4 (de) 2008-04-11 2010-04-15 Siemens Aktiengesellschaft Einschaltstrombegrenzung bei Transformatoren
US20100328828A1 (en) 2009-06-26 2010-12-30 Jian Xu System and method for protecting a circuit
EP2355353A1 (fr) * 2010-02-05 2011-08-10 Siemens Aktiengesellschaft Procédé de commande destiné à la limitation de la surtension et du court-circuit d'un circuit de réglage de puissance et dispositif correspondant
JP6745478B2 (ja) * 2016-06-30 2020-08-26 パナソニックＩｐマネジメント株式会社 保護回路及び配線器具
EP3379725A1 (fr) * 2017-03-23 2018-09-26 Siemens Aktiengesellschaft Procédé de commande d'un commutateur à courant continu, commutateur à courant continu et système de tension continue
US10566787B2 (en) 2017-10-25 2020-02-18 Abb S.P.A. Inrush current detection and control with solid-state switching devices

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WO2022135808A1 (fr) 2022-06-30
DE102020216405A1 (de) 2022-06-23
CN115244853A (zh) 2022-10-25
US20230344424A1 (en) 2023-10-26

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