EP3739601B1 - Convertisseur llc entrelacé - Google Patents

Convertisseur llc entrelacé Download PDF

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Publication number
EP3739601B1
EP3739601B1 EP19175151.0A EP19175151A EP3739601B1 EP 3739601 B1 EP3739601 B1 EP 3739601B1 EP 19175151 A EP19175151 A EP 19175151A EP 3739601 B1 EP3739601 B1 EP 3739601B1
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Prior art keywords
coil
magnetic
core
core assembly
magnetic core
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German (de)
English (en)
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EP3739601A1 (fr
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Robert Weger
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Infineon Technologies Austria AG
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Infineon Technologies Austria AG
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01F—MAGNETS; INDUCTANCES; TRANSFORMERS; SELECTION OF MATERIALS FOR THEIR MAGNETIC PROPERTIES
    • H01F3/00—Cores, Yokes, or armatures
    • H01F3/10—Composite arrangements of magnetic circuits
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01F—MAGNETS; INDUCTANCES; TRANSFORMERS; SELECTION OF MATERIALS FOR THEIR MAGNETIC PROPERTIES
    • H01F27/00—Details of transformers or inductances, in general
    • H01F27/28—Coils; Windings; Conductive connections
    • H01F27/2866—Combination of wires and sheets
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01F—MAGNETS; INDUCTANCES; TRANSFORMERS; SELECTION OF MATERIALS FOR THEIR MAGNETIC PROPERTIES
    • H01F27/00—Details of transformers or inductances, in general
    • H01F27/40—Structural association with built-in electric component, e.g. fuse
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01F—MAGNETS; INDUCTANCES; TRANSFORMERS; SELECTION OF MATERIALS FOR THEIR MAGNETIC PROPERTIES
    • H01F27/00—Details of transformers or inductances, in general
    • H01F27/40—Structural association with built-in electric component, e.g. fuse
    • H01F2027/408—Association with diode or rectifier

Definitions

  • the present disclosure relates to the field of switching converters, in particular to an Interleaved LLC converter (ILLC converter).
  • ILLC converter Interleaved LLC converter
  • LLC resonant converters are commonly used in modern power supply designs due to their ability to operate with high efficiency at moderate complexity with regard to control circuitry. Furthermore, multiple LLC resonant converters may be combined in parallel to spread power losses and to decrease the size of output filters and thus the ripple of the output voltage. Such combinations of two or more LLC converter units are referred to as Interleaved LLC converter or ILLC converter.
  • Additional control circuitry is usually employed in ILLC converters, for example to balance the load (i.e. the output current) among the individual LLC converter units.
  • a misbalance/asymmetry of the output currents provided by the individual LLC converter units is, inter alia, caused by tolerances of circuit components used in the tank circuits (LC circuits) of the individual LLC converter units. Standard tolerances of, e.g. 5%, may lead to significantly differing resonance frequencies of the mentioned tank circuits and thus to the LLC converter units operating at different operating points.
  • One approach to balance the load among two or more LLC converter units includes using current-controlled variable inductors (CCVIs) in the tank circuits of the individual LLC converter units which allows to tune the resonance frequency of the tank circuits by adjusting the inductance of the CCVI.
  • CCIV current-controlled variable inductors
  • a CCIV is composed of a coil, which is would around a magnetic core with an air gap.
  • the coil has an inductance, which can be varied by generating a magnetic bias field in the magnetic core using a further coil, which is also would around the magnetic core.
  • the magnitude of the magnetic bias field depends on a control current passing through the further coil.
  • CCIVs may be implemented in various different ways, and one problem to be solved by the embodiments described herein can be regarded as how to improve an interleaved LLC converter by improving the CCIV with regards to, for example, efficiency (low losses), electromagnetic compatibility (low disturbing stray fields) and size.
  • EP 2 624 260 A1 discloses a magnetic component with first, second and third U/UR-cores.
  • the first U/UR-core and the second U/UR-core are magnetically coupled through gaps, wherein the legs of the U/UR-cores abut each other and form an O-core.
  • the third U/UR-core is magnetically coupled through gaps to the first and the second U/UR-core.
  • the legs of the third U/UR-core abut the legs of the first and the second U/UR-cores.
  • a first primary winding and a first secondary winding are arranged on a body section of the first U/UR-core.
  • a second primary winding and a second secondary winding are arranged on a body section of the second U/UR-core.
  • the O-core formed by the first and second U/UR-cores may be rotated by 90°, wherein the windings on the O-core are not rotated.
  • EP 2 299 456 A1 discloses magnetic components with first, second, third and fourth U/UR-cores. Free ends of the first and second U/UR-cores face each other and form an O-core which is arranged between the third and fourth U/UR-cores with the free ends of the third and fourth U/UR-cores facing toward the O-core. Between each of the free ends of the third and fourth U/UR-cores and the O-core an air gap is provided.
  • the magnetic components further include six windings: a first primary winding and a first secondary winding wound on the first U/UR-core, a second primary winding and a second secondary winding wound on the second U/UR-core, a third secondary winding wound on the third U/UR-core and a fourth secondary winding wound on the fourth U/UR-core.
  • the air gaps between each of the free ends of the third and fourth U/UR-cores and the O-core may be omitted.
  • EP 3 349 224 A1 discloses a magnetic component with four linearly stacked U-shaped core elements: A first transformer core element, a second transformer core element, a first filter core element and a second filter core element.
  • Each of the four core elements comprises a first and a second outer leg, and a flange.
  • the two transformer core elements are facing each other with their first outer legs and their second outer legs and form an O-like shaped transformer core section having an air gap between their first outer legs.
  • the O-like shaped transformer core section is arranged between the first filter core element and the second filter core element with the first and second outer legs of the first filter core element and the second filter core element facing the O-like shaped transformer core section.
  • the O-like shaped transformer core section has a window like opening which provides a transformer winding window for receiving turns of a first and a second lower current transformer winding part and of a first and a second higher current transformer winding part.
  • the higher current transformer winding parts and the lower current transformer winding parts are arranged on the first outer legs of the transformer core elements in a way that the lower current transformer winding parts are arranged between the higher current transformer winding parts.
  • a first filter winding is arranged on the first outer leg of the first filter core element and a second filter winding is arranged on the first leg of the second filter core element.
  • EP 3 133 614 A1 discloses a LLC resonant converter circuit having one resonant capacitor, one series resonant inductor, one parallel resonant inductor and a transformer comprising a primary winding, a first secondary winding and a second secondary winding.
  • RU 2 047 262 C1 describes a converter having a ring-shaped core with a center bar arranged between a first outer bar and a second outer bar.
  • a first winding of a primary coil is arranged on the first outer bar
  • a second winding of the primary coil is arranged on the second outer bar
  • a first winding of a secondary coil is arranged on the first outer bar
  • a second winding of the secondary coil is arranged on the second outer bar
  • a third winding of the secondary coil is arranged on the center bar.
  • US 4 563 731 A discloses a control transformer that has a variable inductance.
  • the transformer includes a ring core with a first outer leg and a second outer leg, and central leg disposed between the outer legs.
  • Two AC windings are provided on each of the outer legs.
  • the central leg is provided with a DC winding.
  • One of the AC windings on the first outer legs and one of the AC windings on the second outer legs are connected in series to thereby constitute a primary winding wound so as to cancel the magnetic flux induced in the central leg by an AC current through the primary winding.
  • a direct-current control circuit causes a direct-current through the DC winding in order to change the inductance value across the primary winding.
  • the inductive component includes a magnetic core assembly comprising at a first portion and a second portion, which is magnetically separated from the first portion of the magnetic core assembly via two or more air gaps.
  • the inductive component further includes an inductor with a variable inductance including a first coil that is arranged on the first portion of the magnetic core assembly, a second coil arranged on the second portion of the magnetic core assembly and configured to generate a bias magnetic field in the second portion of the magnetic core assembly.
  • the first coil is configured to generate a magnetic flux in a magnetic path that includes the first portion of the magnetic core assembly, the two or more air gaps and a part of the second portion of the magnetic core assembly.
  • multiphase LLC switching converter which includes the above-mentioned inductive component is described herein.
  • a multiphase LLC switching converter is described herein which includes at least two LLC switching converter units, each including a tank circuit and each tank circuit including an inductor as mentioned above.
  • the method includes supplying an AC current to the first coil, which is arranged on the first portion of a magnetic core assembly.
  • the method further includes generating the bias magnetic field in the second portion of the magnetic core assembly by supplying a DC current to the second coil that is arranged on the second portion of the magnetic core assembly.
  • the second portion of the magnetic core assembly is magnetically separated from the first portion of the magnetic core assembly via the two or more air gaps.
  • the method includes controlling the inductance of the first coil by adjusting the DC current supplied to the second coil.
  • the AC current when passing through the first coil, generates the magnetic flux in the magnetic path that includes the first portion of the magnetic core assembly, the two or more air gaps and the part of the second portion of the magnetic core assembly.
  • Fig. 1 illustrates one example of an Interleaved LLC (ILLC) converter, also referred to as multi-phase LLC converter.
  • the ILLC converter is composed of two LLC converter units 10 and 20 whose outputs are coupled in parallel. However, dependent on the application more than two LLC converter units may be coupled in parallel.
  • a balancing of the output currents of the individual LLC converter units is achieved by using a current-controlled variable inductor (CCVI) in the tank circuits of the LLC converter units.
  • CCVI current-controlled variable inductor
  • the first LLC converter unit 10 includes a tank circuit that is composed of a capacitor C IN1 an inductor L V1 and a further inductor L P1
  • the inductance of the inductor L V1 can be varied by applying a control current, and the inductor L P1 , either as a whole or parts thereof, forms the primary winding of a transformer.
  • the respective secondary winding is represented by inductor Lsi, which has a middle-tap in the present example.
  • Diodes D 11 and D 12 form a rectifier, which rectifies the current induced in the secondary winding Lsi, wherein the diodes D 11 and D 12 are connected between the outer taps of the secondary winding Lsi and an output node of the first LLC converter unit 10.
  • a current sense resistor Rsi may be connected between the middle tap of the secondary winding Lsi and a reference node (e.g. ground node GND) of the first LLC converter unit 10.
  • the voltage drop across the current sense resistor Rsi may be tapped to obtain a voltage signal representative of the output current of the first LLC converter unit 10.
  • the alternating input voltage V IN1 applied across the tank circuit which is a series resonance circuit formed by the series circuit of capacitor C IN1 , inductor Lvi, and inductor L P1 , is usually provided by a transistor H-bridge circuit or, alternatively, by a transistor half-bridge circuit (not shown in Fig. 1 ) dependent on the actual implementation. It is understood that the transistor bridge circuits may be implemented using MOS transistors that provide a current sensing function in order to obtain current information. In this case, the current sense resistor Rsi can be omitted.
  • the second LLC converter unit 20 is substantially identical with the first LLC converter unit 10.
  • the second LLC converter unit 20 includes a tank circuit, which is a series resonance circuit formed by the series circuit of capacitor C IN2 , inductor L V2 , and inductor L P2 , wherein the latter represents the primary winding of a further transformer.
  • the respective secondary winding is represented by inductor L S2 , which has a middle-tap, and diodes D 21 and D 22 form a rectifier, which rectifies the current induced in the secondary winding L S2 .
  • Diodes D 11 and D 12 are connected between the outer taps of the secondary winding L S2 and an output node of the second LLC converter unit 20.
  • a current sense resistor R S2 may be connected between the middle tap of the secondary winding L S2 and a reference node (e.g. ground node GND) of the second LLC converter unit 20.
  • a reference node e.g. ground node GND
  • the outputs of both LLC converter units 10 and 20 are connected in parallel, wherein an output capacitor C OUT may be provided to reduce the ripple of the common output voltage V OUT .
  • the input voltage V IN2 applied across the tank circuit may also be provided by a transistor bridge circuit. Usually, the alternating input voltages V IN1 and V IN2 are phase shifted with respect to each other.
  • the ILLC converter includes a regulator circuit 30 that is configured to provide control currents for the inductors L V1 and L V2 (which are CCVIs) so as to tune the respective inductances such that the two LLC converter unit 10 and 20 are at least approximately equally loaded. Accordingly, a mismatch between the inductances of inductor L V1 and L V2 can be compensated for. It is noted, that in case of an ILLC converter with two converter units it would be sufficient if only one of the two LLC converter units includes a CCVI whereas the corresponding inductance in the other LLC converter unit may be fixed.
  • N -1 LLC converter units must be equipped with a CCVI in order to be able to balance the loads.
  • the depicted example in which each LLC converter has a CCVI, provides somewhat more flexibility.
  • the variable inductance (L V1 or L V2 ) of that LLC converter unit which provides the lower output current, is decreased in order to increase the resonance frequency (f R1 or f R2 ) and thus also the output current of the respective LLC converter unit and to reduce the mismatch between the output currents.
  • the first converter unit's tank circuit as shown in Fig. 1 has two resonance frequencies, one being associated with capacitance C IN1 and inductance L V1 , and a further one being associated with capacitance C IN1 and inductance L V1 +L P1 . The same applies for the second converter unit's tank circuit.
  • Fig. 2 shows the characteristic curve of the resonance of the tank circuit used in the LLC converter unit that provides the lower output current.
  • the regulator circuit 30 controls the CCVI of the respective LLC converter unit to lower values thus shifting the resonance frequencies and hence shifting the respective characteristic curve (solid line) to higher frequencies (dashed line).
  • the operating point is shifted, for a given operating frequency f OP from point A to point B, i.e. towards higher output voltages and hence increasing the output current.
  • f OP operating frequency
  • a CCVI is implemented by a coil (referred to as "AC coil”) wound around a magnetic core.
  • a control current is fed into a further coil (referred to as “DC coil”) that is also wound around the magnetic core.
  • the control current passing through the DC coil is a direct current (DC)
  • the input current supplied to an LLC converter unit e.g. using a transistor bridge
  • AC coil alternating current
  • the control current passing through the DC coil causes a magnetic bias field in the magnetic core, and the relative permeability of the magnetic core decreases as the bias field increases and the magnetic core gradually saturates.
  • the relative permeability of the magnetic core reaches its minimum (relative permeability of one).
  • the inductance of the AC coil depends on (and is approximately proportional to) the relative permeability of the magnetic core. Accordingly, an increasing control current passing through the DC coil causes the inductance of the AC coil to decrease and vice versa.
  • the inductance of the AC coil reaches its maximum at a control current of zero and its minimum when the control current is so high that the magnetic core is fully saturated.
  • the general principle of a CCVI is as such known and thus not explained herein in more detail.
  • the CCVI When using a CCVI in a switching converter it is desirable that the CCVI is designed to be efficient in terms of low power losses and low electromagnetic emissions (mainly caused by stray fields). Further, the CCVI should be able to be operated as high frequencies which, in turn, allows the magnetic core to be small.
  • Some known CCVI concepts exhibit the problem that the AC currents passing through the AC coil can induce comparably high voltages in the DC coil, in particular when the DC-coil has a high number of windings in order to keep the control currents low. The induced voltages may be so high that a breakthrough may occur between neighboring windings of the DC coil.
  • Fig. 3 illustrates a not claimed embodiment of a CCVI that may be used to improve performance of an ILLC converter.
  • a so-called COC core assembly is used as magnetic core for the AC coil 6 that forms the CCVI and the DC coil 5 that is used to control the inductance of the AC coil 6 as explained above.
  • the COC core assembly is composed of several core elements, in the present example an O-shaped core 2 (that may be formed by two opposing C-shaped cores 2a and 2b) and two C-shaped cores 1 and 4 that are arranged at opposing sides of the O-shaped core 2 so that air gaps ⁇ remain between the vertical segments of the O-shaped core 2 and the adjacent (but magnetically separated therefrom by the air gaps) front sides of the horizontal segments of the C-shaped cores 1 and 3.
  • the O-shaped core 2 is arranged between the two opposing C-shaped cores 1 and 3.
  • O-shaped core basically denotes a ring core, i.e. a magnetic core that provides a closed, gap-free magnetic path for the magnetic field generated by a coil would around one or more segments of the ring core.
  • An O-shaped core may be composed of two or more parts, e.g. by two adjoining C-cores (cf. example of Fig. 3 or 5 ) or by a C-core and an adjoining I-core (cf. example of Fig. 5 ).
  • the AC coil 6 is split into two partial coils 6a and 6b which are wound around C-shaped core 1 and, respectively, C-shaped core 3, and which are electrically connected in series, wherein partial coil 6a has a winding direction (winding sense) opposite to the winding direction of partial coil 6b.
  • the partial coils 6a and 6b may be wound on both horizontal segments of the C-shaped cores 1 and 3, respectively, with an equal number of turns around the upper horizontal segments and the lower horizontal segments.
  • the vertical segments of the C-shaped cores 3 and 1 may be used to arrange the turns of the coils 6a and 6b, respectively.
  • the arrows indicate the orientation of the resulting magnetic field obtained for positive inductor currents.
  • the dash-dotted lines illustrate schematically the magnetic (main) paths for the magnetic flux generated by the partial coils 6a and 6b during operation.
  • This magnetic paths which includes the C-shaped cores 1 and 3, the air gaps and parts (vertical segments) of the O-shaped core 2, is further explained later with reference to Fig. 7 .
  • the DC coil 5 is wound around the O-shaped core 2 which forms a closed magnetic path for the resulting bias magnetic field.
  • the DC coil 5 has a comparably high number of turns so that even small currents will cause a magnetic field that is high enough to change the inductance of the AC coil 6.
  • the magnetic path of coil 6a is formed by the C-shaped core 3, the two air gaps with width ⁇ and the right vertical segment of the O-shaped core 2.
  • the magnetic path of coil 6b is formed by the C-shaped core 1, the two air gaps with width ⁇ and the left vertical segment of the O-shaped core 2.
  • the magnetic paths of AC coils 6a and 6b are formed basically by the C-shaped cores 1 and 3 and the adjacent vertical segments of the O-shaped core 2. However, a part of the (alternating) magnetic field generated by the AC coils 6a and 6b will also pass the horizontal segments of the O-shaped core 2. Due to the symmetric arrangement of the AC coils 6a and 6b and due to the fact that they have opposite winding directions, the AC fields in the horizontal segments of the O-shaped core 2 caused by AC coil 6a and AC coil 6b at least approximately compensate. Thus only little (and ideally no) AC currents are induced in the DC coil 5. Furthermore, the series connection of the AC-coils in combination with their opposite winding directions result in an improved linearity of the CCVI.
  • the example of Fig. 4 is almost identical to the example of Fig. 3 .
  • the only difference is that the widths d 2 of the left and right vertical segments of the O-shaped core 2 are smaller than the corresponding width di in the example of Fig. 3 (and thus the respective cross-section area is smaller).
  • the cross-section areas of the vertical segments of the O-shaped core 2 are between 0.5 to 0.9 times the cross-section area of the C-shaped cores 1 and 3.
  • the smaller cross-section ensures that the magnetic bias field caused by the DC current i DC passing through the DC coil 5 is substantially kept inside the horizontal segments of the O-shaped core 2 even when the vertical segments reach magnetic saturation. Consequently, the magnetic flux is better focused to the vertical segments of the O-shaped core and hence the required maximum control current i DC can be reduced.
  • Fig. 5 illustrates an embodiment according to the present invention of a CCVI that may be used to improve performance of an ILLC converter.
  • a so-called ICIICI core assembly is used as magnetic core for the AC coil 6 that forms the CCVI and the DC coil 5 that is used to control the inductance of the AC coil 6.
  • the magnetic arrangement of Fig. 5 is similar to the example of Fig. 3 . However, the positions of AC coil and DC coil are interchanged.
  • the AC coil 6 is arranged between the outer coils 5a and 5b, which are connected in series and form the DC coil 5, whereas, in contrast, the outer coils are the AC coils in the previous example of Fig. 3 .
  • the outer C-shaped cores 9 and 11 are each completed by a respective vertical I-shaped core 9b, 11b and are thus effectively O-shaped cores, that are arranged side-by side with two horizontal I-shaped cores 7 and 8 in between, wherein air gaps ⁇ remain between the right and left front sides of the I-shaped cores 7 and 8 and the adjacent C-shaped cores 9 and 11.
  • the AC coil 6 is formed by partial coils 6a, and 6b, which are would around the I-shaped cores 8 and 7, respectively.
  • the dash-dotted line illustrates schematically the magnetic (main) path for the magnetic flux generated by the AC coil 6 during operation. This magnetic path, which includes the I-shaped cores 7 and 8, the air gaps and parts (segments 9a, 11a) of the outer ring cores 9, 9a, 11, 11a, is further explained later with reference to Fig. 8 .
  • the O-shaped cores 9, 9a and 11, 11a each form a closed magnetic path for the partial coils 5b and 5a, respectively, which together form the DC coil 5.
  • the vertical segments 11a and 9a of the C-shaped cores 11 and 9 are part of the magnetic path of the partial DC coils 5a and 5b as well as part of the magnetic part of the AC coil 6, which is formed by the vertical segments 9a and 11a, the air gaps ⁇ as well as the vertical I-shaped cores 7 and 8.
  • the vertical segments 11a and 9a of the C-shaped cores 11 and 9 are magnetized by the resulting magnetic bias field which causes a respective increase of the magnetic resistance of the magnetic path associated with the AC coil 6 and a corresponding decrease of the inductance.
  • the width d 3 of the vertical segments 11a and 9a may be lower than the width di of the other segments (and the respective cross-sections area as well).
  • the cross-section area of the vertical segments 11a and 9a may be a factor 0.5 to 0.9 of the cross-section area of the other segments of the C-shaped cores 9 and 11.
  • Fig. 6 is substantially identical to the example of Fig. 5 but additionally includes the mentioned short circuit windings which are denoted with numerals 12a and 12b.
  • the CCVI described herein allow lower loss and low electromagnetic emissions. Furthermore, the CCVI described herein allow operation of the ILLC switching converter at a comparable high frequency and therefore the size of the CCVI can be reduced.
  • One feature that is (at least in part) responsible for the comparably low losses is the division of the total air gap in the magnetic path of the AC flux into four smaller air gaps ⁇ . As a consequence the parasitic stray fields are lower and also the parasitic eddy currents resulting from the stray fields. Furthermore, losses are further reduced due to the symmetric arrangement of the coils. Accordingly, only a small portion of the core segments that form the magnetic path for the AC flux is premagnetized (which entails enhanced core losses) by the magnetic bias field.
  • EMI electromagnetic emissions
  • the relevant core segments are strongly magnetized (up to saturation) by the magnetic bias field.
  • the ICIICI-CCVI of Fig. 5 basically produces a magnetic quadrupole field when the vertical core segments are magnetized up to saturation by the bias field.
  • the (approximate) quadrupole field is generated because the AC coil 6 is composed of two partial coils with I-shaped cores (see Fig. 5 horizontal cores 7, 8) arranged anti-parallel closely adjacent to each other. Such an arrangement is also more efficient in terms of losses.
  • Figures 7 and 8 includes magnetic circuit diagrams illustrating the equivalent magnetic paths of the examples shown in Figs. 3 and 4 and, respectively, the embodiments shown in Figs. 5 and 6
  • Both diagrams illustrate the magnetic resistances (often referred to as reluctances) of the components (air gaps and cores) that form the magnetic paths for a magnetic flux as well as the sources of magnetomotive force (corresponding to the DC coils generating the magnetic biasing field). It can be seen that the four magnetic resistances R ⁇ are symmetrically arranged with respect to the cores the form the magnetic core assembly.
  • the magnetic circuit of Fig. 7 represents the the not claimed examples of Fig. 3 and 4 .
  • the AC coil is formed by series circuit of a two partial coils 6a, 6b (not shown in Fig. 7 ), which are arranged side by side with the DC coil 5 in between.
  • the magnetic core assembly includes one ring core 2 (composed of C-shaped core elements 2a and 2b), around which the DC coil 5 is wound, and two further cores 1 and 3, around which the two partial coils 6a, 6b of the first coil are wound.
  • the two further cores 1 and 3 are arranged on opposing sides of the ring core 2 so that two air gaps ⁇ are formed between the ring core 2 and each one of the two further cores 1 and 3.
  • the air gaps are represented by magnetic resistances R ⁇
  • the (O-shaped) ring core 2 is represented by the magnetic resistances R 2a and R 2b .
  • R 2a and R 2b in fact represent only the vertical segments of the ring core 2 (cf. Fig. 4 ), which is a simplification because the magnetic resistance of the horizontal segments of the ring core 2 is comparably small.
  • the DC coil 5 is represented by the source MMFs of magnetomotive force generating the DC flux (representing the magnetic bias field).
  • the magnetic resistances R 2a and R 2b are variable and depend on the magnetic flux generated by the source MMFs of magnetomotive force (DC coil 5) as explained above.
  • the further cores 1 and 3 are represented by magnetic resistances R 1 and R 3 which are, however, negligibly small as compared to the magnetic resistance R ⁇ of an air gap.
  • the magnetic resistance of the magnetic path of the AC coils 6a and 6b, which determines the inductance of the CCVI, basically depends on the air gaps (magnetic resistances R ⁇ ) and the magnetic resistances R 2a and R 2b that depend on the DC flux generated by the DC coil 5.
  • the magnetic circuit of Fig. 8 represents the embodiment of Fig. 5 and 6 .
  • the DC coil 5 is a series circuit of a two partial coils 5a and 5b, which are arranged side by side with the AC coil 6 in between.
  • the magnetic core assembly includes two ring cores (see Fig. 5 , cores 9 and 9b and cores 11 and 11b), around which the two partial coils 5a and 5b of the DC coil 5 are wound.
  • the magnetic core assembly further includes a further core comprising two core segments (see Fig. 5 , I-shaped cores 7 and 8), around which the AC coil 6 is wound.
  • the further core segments 7 and 8 are arranged between the two ring cores leaving an air gap ⁇ between each one of the two core segments 7, 8 and each one of the two ring cores.
  • the magnetic resistances of the outer ring cores are essentially determined by the magnetic resistances R 9 and R 11 of the vertical segments 9a and 11a (see Fig. 5 ), whose magnetic resistances depends on the magnetomotive force generated by the sources MMFsa and MMFsb (representing partial coils 5a and 5b) and on the resulting DC flux.
  • the magnetic resistance of the magnetic path of the AC coil which determines the inductance of the CCVI, basically depends on the air gaps (magnetic resistances R ⁇ ) and the magnetic resistances R 9 and R 11 .
  • the magnetic resistances R 8 and R 7 are negligible as compared to the magnetic resistances of the air gaps.

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  • Power Engineering (AREA)
  • Chemical & Material Sciences (AREA)
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  • Dc-Dc Converters (AREA)

Claims (10)

  1. Composant inductif comportant :
    un ensemble à noyau magnétique comportant une première partie (7, 8) et une deuxième partie (9, 9a, 9b ; 11, 11a, 11b) qui est magnétiquement séparée de la première partie (7, 8) de l'ensemble à noyau magnétique par deux ou plus entrefers (δ), la deuxième partie (9, 9a, 9b ; 11, 11a, 11b) de l'ensemble à noyau magnétique comportant un premier noyau (11, 11a, 11b) annulaire sans entrefer et un deuxième noyau (9, 9a, 9b) annulaire sans entrefer, qui sont montés sur des côtés opposés de la première partie (7, 8) de l'ensemble à noyau magnétique,
    la première partie (7, 8) étant séparée de la deuxième partie (11, 11a, 11b) en ce que les au moins deux entrefers (δ) sont prévus entre le premier noyau (11, 11b) annulaire et la première partie (7, 8), et la première partie (7, 8) étant séparée de la deuxième partie (9, 9a, 9b) en ce que les au moins deux entrefers (δ) sont prévus entre le deuxième noyau (9, 9b) annulaire et la première partie (7, 8) ;
    un inducteur ayant une inductance variable comportant une première bobine (6 ; 6a, 6b), qui est montée sur la première partie (7, 8) de l'ensemble à noyau magnétique ;
    une deuxième bobine (5, 5a, 5b) montée sur la deuxième partie (9, 11) de l'ensemble à noyau magnétique et configurée pour produire un champ magnétique de polarisation dans la deuxième partie (9, 9a, 9b ; 11, 11a, 11b) de l'ensemble à noyau magnétique,
    dans lequel la première bobine (6) est configurée pour produire un flux magnétique dans un chemin magnétique, qui comporte la première partie (7, 8) de l'ensemble à noyau magnétique, les deux ou plus entrefers (δ) et une partie de la deuxième partie (9a, 11a) de l'ensemble à noyau magnétique.
  2. Composant inductif suivant la revendication 1,
    dans lequel la première bobine comporte une première bobine (6a) partielle et une deuxième bobine (6b) partielle montée en série avec la première bobine (6a) partielle, et
    dans lequel la première bobine (6a) est montée sur un premier segment (7) de noyau et la deuxième bobine (6b) partielle est montée sur un deuxième segment (8) de noyau de la première partie de l'ensemble à noyau magnétique.
  3. Composant inductif suivant la revendication 1 ou 2,
    dans lequel le premier noyau (11, 11a, 11b) annulaire et le deuxième noyau (9, 9a, 9b) annulaire de la deuxième partie de l'ensemble à noyau magnétique sont disposés symétriquement par rapport à la première partie (7, 8) de l'ensemble à noyau magnétique.
  4. Composant inductif suivant l'une quelconque des revendications précédentes,
    dans lequel la deuxième bobine (5) comporte une première bobine (5a) partielle et une deuxième bobine (5b) partielle montée en série avec la première bobine (5a) partielle, et
    dans lequel la première bobine (5a) partielle de la deuxième bobine (5) est montée sur le premier noyau (11, 11b) annulaire et la deuxième bobine (5b) partielle de la deuxième bobine (5) est montée sur le deuxième noyau (9, 9b) annulaire.
  5. Composant inductif suivant l'une quelconque des revendications précédentes,
    dans lequel la première partie de l'ensemble à noyau magnétique comporte un premier noyau (8) formé en I et un deuxième noyau (7) formé en I disposé substantiellement parallèlement au premier noyau (8) formé en I.
  6. Composant inductif suivant l'une quelconque des revendications précédentes,
    dans lequel la partie de la deuxième partie de l'ensemble à noyau magnétique, faisant partie du chemin magnétique du flux produit par la première bobine (6), est formée par un segment (11a) du premier noyau (11, 11a, 11b) annulaire et un segment (9a) du deuxième noyau (9, 9a, 9b) annulaire.
  7. Composant inductif suivant l'une quelconque des revendications précédentes,
    dans lequel un premier enroulement (12a) de court-circuit est monté sur le premier noyau (11, 11b) annulaire et un deuxième enroulement (12b) de court-circuit est monté sur le deuxième noyau (9, 9b) annulaire.
  8. Composant inductif suivant l'une quelconque des revendications précédentes,
    dans lequel la partie de la deuxième partie de l'ensemble à noyau magnétique, faisant partie du chemin magnétique du flux produit par la première bobine (6), a une surface de section efficace magnétique plus petite que le reste de la deuxième partie de l'ensemble à noyau magnétique, ne faisant pas partie du chemin magnétique du flux produit par la première bobine (6).
  9. Convertisseur à découpage LLC à plusieurs phases comportant :
    au moins deux unités de convertisseur à découpage LLC, comportant chacune un circuit LC comportant un composant inductif suivant la revendication 1.
  10. Procédé pour commander un composant inductif suivant la revendication 1, comportant des stades dans lesquels :
    on alimente la première bobine (6, 6a, 6b), qui est montée sur la première partie de l'ensemble à noyau magnétique, en un courant alternatif, et
    on produit le champ magnétique de polarisation dans la deuxième partie de l'ensemble à noyau magnétique en alimentant la deuxième bobine (5, 5a, 5b) , qui est montée dans la deuxième partie (2a, 2b ; 9, 11) du noyau magnétique, en un courant continu ;
    on commande l'inductance de la première bobine en réglant le courant continu alimentant la deuxième bobine (5, 5a, 5b) ;
    dans lequel le courant alternatif, lorsqu'il passe dans la première bobine (6; 6a, 6b), produit un flux magnétique dans un chemin magnétique qui comporte la première partie de l'ensemble à noyau magnétique, les deux ou plus entrefers (δ) et une partie de la deuxième partie de l'ensemble à noyau magnétique.
EP19175151.0A 2019-05-17 2019-05-17 Convertisseur llc entrelacé Active EP3739601B1 (fr)

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Publication number Priority date Publication date Assignee Title
US11502614B2 (en) * 2020-01-15 2022-11-15 Raytheon Company Magnetic components with electrically variable characteristics
EP4388564A1 (fr) * 2022-01-05 2024-06-26 Telefonaktiebolaget LM Ericsson (publ) Inducteur pour supprimer le bruit en mode commun (cm) et en mode différentiel (dm)

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* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4563731A (en) * 1982-01-07 1986-01-07 Matsushita Electric Industrial Co., Ltd. Resonant type constant voltage supply apparatus
RU2047262C1 (ru) * 1993-04-14 1995-10-27 Азово-Черноморский Институт Механизации Сельского Хозяйства Преобразователь однофазного напряжения в трехфазное
EP2299456B1 (fr) * 2009-09-17 2016-08-24 DET International Holding Limited Composant magnétique intégré
EP2624260B1 (fr) * 2012-02-02 2018-04-04 DET International Holding Limited Convertisseur à serrage actif, avec composant magnétique
EP3133614B1 (fr) * 2015-08-18 2019-11-20 Delta Electronics (Thailand) Public Co., Ltd. Composant magnétique intégré
EP3699936A1 (fr) * 2017-01-12 2020-08-26 Delta Electronics (Thailand) Public Co., Ltd. Composant magnétique intégré et convertisseur de puissance à mode commuté

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