EP3363071A1 - Appareil et procédés de génération d'ondes électromagnétiques sur un support de transmission - Google Patents

Appareil et procédés de génération d'ondes électromagnétiques sur un support de transmission

Info

Publication number
EP3363071A1
EP3363071A1 EP16785674.9A EP16785674A EP3363071A1 EP 3363071 A1 EP3363071 A1 EP 3363071A1 EP 16785674 A EP16785674 A EP 16785674A EP 3363071 A1 EP3363071 A1 EP 3363071A1
Authority
EP
European Patent Office
Prior art keywords
wave
electromagnetic waves
guided
waveguide
transmission medium
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP16785674.9A
Other languages
German (de)
English (en)
Inventor
Paul Shala Henry
Thomas M WILLIS, III.
Robert Bennett
Farhad Barzegar
Irwin Gerszberg
Donald J. Barnickel
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
AT&T Intellectual Property I LP
Original Assignee
AT&T Intellectual Property I LP
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Priority claimed from US14/885,463 external-priority patent/US9722318B2/en
Priority claimed from US14/965,523 external-priority patent/US10033107B2/en
Priority claimed from US15/274,987 external-priority patent/US10170840B2/en
Application filed by AT&T Intellectual Property I LP filed Critical AT&T Intellectual Property I LP
Priority claimed from PCT/US2016/057161 external-priority patent/WO2017066654A1/fr
Publication of EP3363071A1 publication Critical patent/EP3363071A1/fr
Withdrawn legal-status Critical Current

Links

Classifications

    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P3/00—Waveguides; Transmission lines of the waveguide type
    • H01P3/16—Dielectric waveguides, i.e. without a longitudinal conductor
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/16—Auxiliary devices for mode selection, e.g. mode suppression or mode promotion; for mode conversion
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P5/00—Coupling devices of the waveguide type
    • H01P5/08—Coupling devices of the waveguide type for linking dissimilar lines or devices
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04B—TRANSMISSION
    • H04B3/00—Line transmission systems
    • H04B3/52—Systems for transmission between fixed stations via waveguides
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q13/00—Waveguide horns or mouths; Slot antennas; Leaky-waveguide antennas; Equivalent structures causing radiation along the transmission path of a guided wave
    • H01Q13/02—Waveguide horns
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q19/00—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic
    • H01Q19/06—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using refracting or diffracting devices, e.g. lens
    • H01Q19/08—Combinations of primary active antenna elements and units with secondary devices, e.g. with quasi-optical devices, for giving the antenna a desired directional characteristic using refracting or diffracting devices, e.g. lens for modifying the radiation pattern of a radiating horn in which it is located
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/06—Arrays of individually energised antenna units similarly polarised and spaced apart
    • H01Q21/20—Arrays of individually energised antenna units similarly polarised and spaced apart the units being spaced along or adjacent to a curvilinear path
    • H01Q21/205—Arrays of individually energised antenna units similarly polarised and spaced apart the units being spaced along or adjacent to a curvilinear path providing an omnidirectional coverage
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/02—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system using mechanical movement of antenna or antenna system as a whole
    • H01Q3/08—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system using mechanical movement of antenna or antenna system as a whole for varying two co-ordinates of the orientation
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
    • H01Q3/30—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array
    • H01Q3/34—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array by electrical means
    • H01Q3/36—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the relative phase between the radiating elements of an array by electrical means with variable phase-shifters

Definitions

  • the subject disclosure relates to apparatus and methods for generating electromagnetic waves on a transmission medium.
  • Broadband access networks include satellite, 4G or 5G wireless, power line communication, fiber, cable, and telephone networks.
  • FIG. 1 is a block diagram illustrating an example, non-limiting embodiment of a guided-wave communications system in accordance with various aspects described herein.
  • FIG. 2 is a block diagram illustrating an example, non-limiting embodiment of a transmission device in accordance with various aspects described herein.
  • FIG. 3 is a graphical diagram illustrating an example, non-limiting embodiment of an electromagnetic field distribution in accordance with various aspects described herein.
  • FIG. 4 is a graphical diagram illustrating an example, non-limiting embodiment of an electromagnetic field distribution in accordance with various aspects described herein.
  • FIG. 5A is a graphical diagram illustrating an example, non-limiting embodiment of a frequency response in accordance with various aspects described herein.
  • FIG. 5B is a graphical diagram illustrating example, non-limiting embodiments of a longitudinal cross-section of an insulated wire depicting fields of guided electromagnetic waves at various operating frequencies in accordance with various aspects described herein.
  • FIG. 6 is a graphical diagram illustrating an example, non-limiting embodiment of an electromagnetic field distribution in accordance with various aspects described herein.
  • FIG. 7 is a block diagram illustrating an example, non-limiting embodiment of an arc coupler in accordance with various aspects described herein.
  • FIG. 8 is a block diagram illustrating an example, non-limiting embodiment of an arc coupler in accordance with various aspects described herein.
  • FIG. 9A is a block diagram illustrating an example, non-limiting embodiment of a stub coupler in accordance with various aspects described herein.
  • FIG. 9B is a diagram illustrating an example, non-limiting embodiment of an electromagnetic distribution in accordance with various aspects described herein.
  • FIGs. 10A and 10B are block diagrams illustrating example, non-limiting embodiments of couplers and transceivers in accordance with various aspects described herein.
  • FIG. 11 is a block diagram illustrating an example, non-limiting embodiment of a dual stub coupler in accordance with various aspects described herein.
  • FIG. 12 is a block diagram illustrating an example, non-limiting embodiment of a repeater system in accordance with various aspects described herein.
  • FIG. 13 illustrates a block diagram illustrating an example, non-limiting embodiment of a bidirectional repeater in accordance with various aspects described herein.
  • FIG. 14 is a block diagram illustrating an example, non-limiting embodiment of a waveguide system in accordance with various aspects described herein.
  • FIG. 15 is a block diagram illustrating an example, non-limiting embodiment of a guided-wave communications system in accordance with various aspects described herein.
  • FIGs. 16A & 16B are block diagrams illustrating an example, non-limiting embodiment of a system for managing a power grid communication system in accordance with various aspects described herein.
  • FIG. 17 A illustrates a flow diagram of an example, non-limiting embodiment of a method for detecting and mitigating disturbances occurring in a communication network of the system of FIGs. 16A and 16B.
  • FIG. 17B illustrates a flow diagram of an example, non-limiting embodiment of a method for detecting and mitigating disturbances occurring in a communication network of the system of FIGs. 16A and 16B.
  • FIGs. 18A, 18B, and 18C are block diagrams illustrating example, non- limiting embodiment of a transmission medium for propagating guided electromagnetic waves.
  • FIG. 18D is a block diagram illustrating an example, non-limiting embodiment of bundled transmission media in accordance with various aspects described herein.
  • FIG. 18E is a block diagram illustrating an example, non-limiting embodiment of a plot depicting cross-talk between first and second transmission mediums of the bundled transmission media of FIG. 18D in accordance with various aspects described herein.
  • FIG. 18F is a block diagram illustrating an example, non-limiting embodiment of bundled transmission media to mitigate cross-talk in accordance with various aspects described herein.
  • FIGs. 18G and 18H are block diagrams illustrating example, non-limiting embodiments of a transmission medium with an inner waveguide in accordance with various aspects described herein.
  • FIGs. 181 and 18J are block diagrams illustrating example, non-limiting embodiments of connector configurations that can be used with the transmission medium of FIGs. 18A, 18B, or 18C.
  • FIG. 18K is a block diagram illustrating example, non-limiting embodiments of transmission mediums for propagating guided electromagnetic waves.
  • FIG. 18L is a block diagram illustrating example, non-limiting embodiments of bundled transmission media to mitigate cross-talk in accordance with various aspects described herein.
  • FIG. 18M is a block diagram illustrating an example, non-limiting embodiment of exposed stubs from the bundled transmission media for use as antennas in accordance with various aspects described herein.
  • FIGs. 18N, 180, 18P, 18Q, 18R, 18S, 18T, 18U, 18V and 18W are block diagrams illustrating example, non-limiting embodiments of a waveguide device for transmitting or receiving electromagnetic waves in accordance with various aspects described herein.
  • FIGs. 19A and 19B are block diagrams illustrating example, non-limiting embodiments of a dielectric antenna and corresponding gain and field intensity plots in accordance with various aspects described herein.
  • FIGs. 19C and 19D are block diagrams illustrating example, non-limiting embodiments of a dielectric antenna coupled to a lens and corresponding gain and field intensity plots in accordance with various aspects described herein.
  • FIGs. 19E and 19F are block diagrams illustrating example, non-limiting embodiments of a dielectric antenna coupled to a lens with ridges and corresponding gain and field intensity plots in accordance with various aspects described herein.
  • FIG. 19G is a block diagram illustrating an example, non-limiting embodiment of a dielectric antenna having an elliptical structure in accordance with various aspects described herein.
  • FIG. 19H is a block diagram illustrating an example, non-limiting embodiment of near-field and far-field signals emitted by the dielectric antenna of FIG. 19G in accordance with various aspects described herein.
  • FIG. 191 is a block diagrams of example, non-limiting embodiments of a dielectric antenna for adjusting far-field wireless signals in accordance with various aspects described herein.
  • FIGs. 19J and 19K are block diagrams of example, non-limiting
  • a flange that can be coupled to a dielectric antenna in accordance with various aspects described herein.
  • FIG. 19L is a block diagram of example, non-limiting embodiments of the flange, waveguide and dielectric antenna assembly in accordance with various aspects described herein.
  • FIG. 19M is a block diagram of an example, non-limiting embodiment of a dielectric antenna coupled to a gimbal for directing wireless signals generated by the dielectric antenna in accordance with various aspects described herein.
  • FIG. 19N is a block diagram of an example, non-limiting embodiment of a dielectric antenna in accordance with various aspects described herein.
  • FIG. 190 is a block diagram of an example, non-limiting embodiment of an array of dielectric antennas configurable for steering wireless signals in accordance with various aspects described herein.
  • FIGs. 19P1, 19P2, 19P3, 19P4, 19P5, 19P6, 19P7 and 19P8 are side-view block diagrams of example, non-limiting embodiments of a cable, a flange, and dielectric antenna assembly in accordance with various aspects described herein.
  • FIGs. 19Q1, 19Q2 and 19Q3 are front-view block diagrams of example, non- limiting embodiments of dielectric antennas in accordance with various aspects described herein.
  • FIGs. 20A and 20B are block diagrams illustrating example, non-limiting embodiments of the transmission medium of FIG. 18A used for inducing guided electromagnetic waves on power lines supported by utility poles.
  • FIG. 20C is a block diagram of an example, non-limiting embodiment of a communication network in accordance with various aspects described herein.
  • FIG. 20D is a block diagram of an example, non-limiting embodiment of an antenna mount for use in a communication network in accordance with various aspects described herein.
  • FIG. 20E is a block diagram of an example, non-limiting embodiment of an antenna mount for use in a communication network in accordance with various aspects described herein.
  • FIG. 20F is a block diagram of an example, non-limiting embodiment of an antenna mount for use in a communication network in accordance with various aspects described herein.
  • FIG. 21A illustrates a flow diagram of an example, non-limiting embodiment of a method for transmitting downlink signals.
  • FIG. 21B illustrates a flow diagram of an example, non-limiting embodiment of a method for transmitting uplink signals.
  • FIG. 21C illustrates a flow diagram of an example, non-limiting embodiment of a method for inducing and receiving electromagnetic waves on a transmission medium.
  • FIG. 21D illustrates a flow diagram of an example, non-limiting embodiment of a method for inducing and receiving electromagnetic waves on a transmission medium.
  • FIG. 21E illustrates a flow diagram of an example, non-limiting embodiment of a method for transmitting wireless signals from a dielectric antenna.
  • FIG. 21F illustrates a flow diagram of an example, non-limiting embodiment of a method for receiving wireless signals at a dielectric antenna.
  • FIG. 21G illustrates a flow diagram of an example, non-limiting embodiment of a method for detecting and mitigating disturbances occurring in a communication network.
  • FIG. 21H is a block diagram illustrating an example, non-limiting embodiment of an alignment of fields of an electromagnetic wave to mitigate propagation losses due to water accumulation on a transmission medium in accordance with various aspects described herein.
  • FIGs. 211 and 21J are block diagrams illustrating example, non-limiting embodiments of electric field intensities of different electromagnetic waves propagating in the cable illustrated in FIG. 20H in accordance with various aspects described herein.
  • FIG. 21K is a block diagram illustrating an example, non-limiting embodiment of electric fields of a Goubau wave in accordance with various aspects described herein.
  • FIG. 21L is a block diagram illustrating an example, non-limiting embodiment of electric fields of a hybrid wave in accordance with various aspects described herein.
  • FIG. 21M is a block diagram illustrating an example, non-limiting embodiment of electric field characteristics of a hybrid wave versus a Goubau wave in accordance with various aspects described herein.
  • FIG. 21N is a block diagram illustrating an example, non-limiting embodiment of mode sizes of hybrid waves at various operating frequencies in accordance with various aspects described herein.
  • FIGs. 22A and 22B are block diagrams illustrating example, non-limiting embodiments of a waveguide device for launching hybrid waves in accordance with various aspects described herein.
  • FIG. 23 is a block diagram illustrating an example, non-limiting embodiment of a hybrid wave launched by the waveguide device of FIGs. 21A and 21B in accordance with various aspects described herein.
  • FIG. 24 illustrates a flow diagram of an example, non-limiting embodiment of a method for managing electromagnetic waves.
  • FIGs. 25A, 25B, 25C, and 25D are block diagrams illustrating example, non- limiting embodiments of a waveguide device in accordance with various aspects described herein.
  • FIGs. 25E, 25F, 25G, 25H, 251, 25J, 25K, 25L, 25M, 25N, 250, 25P, 25Q, 25R, 25S, and 25T are block diagrams illustrating example, non-limiting embodiments of wave modes and electric field plots in accordance with various aspects described herein.
  • FIG. 25U is a block diagram illustrating an example, non-limiting embodiment of a waveguide device in accordance with various aspects described herein.
  • FIGs. 25V, 25W, 25X are block diagrams illustrating example, non-limiting embodiments of wave modes and electric field plots in accordance with various aspects described herein.
  • FIG. 25Y illustrates a flow diagrams of an example, non-limiting embodiment of a method for managing electromagnetic waves.
  • FIG. 25Z is a block diagram illustrating an example, non-limiting embodiment of substantially orthogonal wave modes in accordance with various aspects described herein.
  • FIG. 25AA is a block diagram illustrating an example, non-limiting embodiment of an insulated conductor in accordance with various aspects described herein.
  • FIG. 25AB is a block diagram illustrating an example, non-limiting embodiment of an uninsulated conductor in accordance with various aspects described herein.
  • FIG. 25AC is a block diagram illustrating an example, non-limiting embodiment of an oxide layer formed on the uninsulated conductor of FIG. 25AB in accordance with various aspects described herein.
  • FIG. 25AD is a block diagram illustrating example, non-limiting embodiments of spectral plots in accordance with various aspects described herein.
  • FIG. 25AE is a block diagram illustrating example, non-limiting embodiments of spectral plots in accordance with various aspects described herein.
  • FIG. 25AF is a block diagram illustrating example, non-limiting embodiments of a wave mode and electric field plot in accordance with various aspects described herein.
  • FIG. 25AG is a block diagram illustrating example, non-limiting embodiments for transmitting orthogonal wave modes according to the method of FIG. 25Y in accordance with various aspects described herein.
  • FIG. 25AH is a block diagram illustrating example, non-limiting embodiments for transmitting orthogonal wave modes according to the method of FIG. 25Y in accordance with various aspects described herein.
  • FIG. 25AI is a block diagram illustrating example, non-limiting embodiments for selectively receiving a wave mode according to the method of FIG. 25Y in accordance with various aspects described herein.
  • FIG. 25AJ is a block diagram illustrating example, non-limiting embodiments for selectively receiving a wave mode according to the method of FIG. 25Y in accordance with various aspects described herein.
  • FIG. 25AK is a block diagram illustrating example, non-limiting embodiments for selectively receiving a wave mode according to the method of FIG. 25Y in accordance with various aspects described herein.
  • FIG. 25AL is a block diagram illustrating example, non-limiting embodiments for selectively receiving a wave mode according to the method of FIG. 25Y in accordance with various aspects described herein.
  • FIG. 26 is a block diagram of an example, non-limiting embodiment of a computing environment in accordance with various aspects described herein.
  • FIG. 27 is a block diagram of an example, non-limiting embodiment of a mobile network platform in accordance with various aspects described herein.
  • FIG. 28 is a block diagram of an example, non-limiting embodiment of a communication device in accordance with various aspects described herein.
  • a guided wave communication system for sending and receiving communication signals such as data or other signaling via guided electromagnetic waves.
  • the guided electromagnetic waves include, for example, surface waves or other electromagnetic waves that are bound to or guided by a transmission medium. It will be appreciated that a variety of transmission media can be utilized with guided wave communications without departing from example embodiments.
  • transmission media can include one or more of the following, either alone or in one or more combinations: wires, whether insulated or not, and whether single-stranded or multi-stranded; conductors of other shapes or configurations including wire bundles, cables, rods, rails, pipes; non-conductors such as dielectric pipes, rods, rails, or other dielectric members; combinations of conductors and dielectric materials; or other guided wave transmission media.
  • the inducement of guided electromagnetic waves on a transmission medium can be independent of any electrical potential, charge or current that is injected or otherwise transmitted through the transmission medium as part of an electrical circuit.
  • the transmission medium is a wire
  • the electromagnetic waves traveling on the wire therefore do not require a circuit to propagate along the wire surface.
  • the wire therefore is a single wire transmission line that is not part of a circuit.
  • a wire is not necessary, and the electromagnetic waves can propagate along a single line transmission medium that is not a wire.
  • guided electromagnetic waves or “guided waves” as described by the subject disclosure are affected by the presence of a physical object that is at least a part of the transmission medium (e.g., a bare wire or other conductor, a dielectric, an insulated wire, a conduit or other hollow element, a bundle of insulated wires that is coated, covered or surrounded by a dielectric or insulator or other wire bundle, or another form of solid or otherwise non-liquid or non-gaseous transmission medium) so as to be at least partially bound to or guided by the physical object and so as to propagate along a transmission path of the physical object.
  • a physical object e.g., a bare wire or other conductor, a dielectric, an insulated wire, a conduit or other hollow element, a bundle of insulated wires that is coated, covered or surrounded by a dielectric or insulator or other wire bundle, or another form of solid or otherwise non-liquid or non-gaseous transmission medium
  • Such a physical object can operate as at least a part of a transmission medium that guides, by way of an interface of the transmission medium (e.g., an outer surface, inner surface, an interior portion between the outer and the inner surfaces or other boundary between elements of the transmission medium), the propagation of guided electromagnetic waves, which in turn can carry energy, data and/or other signals along the transmission path from a sending device to a receiving device.
  • an interface of the transmission medium e.g., an outer surface, inner surface, an interior portion between the outer and the inner surfaces or other boundary between elements of the transmission medium
  • guided electromagnetic waves can propagate along a transmission medium with less loss in magnitude per unit distance than experienced by unguided electromagnetic waves.
  • An electrical circuit allows electrical signals to propagate from a sending device to a receiving device via a forward electrical path and a return electrical path, respectively.
  • These electrical forward and return paths can be implemented via two conductors, such as two wires or a single wire and a common ground that serves as the second conductor.
  • electrical current from the sending device (direct and/or alternating) flows through the electrical forward path and returns to the transmission source via the electrical return path as an opposing current. More particularly, electron flow in one conductor that flows away from the sending device, returns to the receiving device in the opposite direction via a second conductor or ground.
  • guided electromagnetic waves can propagate along a transmission medium (e.g., a bare conductor, an insulated conductor, a conduit, a non-conducting material such as a dielectric strip, or any other type of object suitable for the propagation of surface waves) from a sending device to a receiving device or vice-versa without requiring the transmission medium to be part of an electrical circuit (i.e., without requiring an electrical return path) between the sending device and the receiving device.
  • a transmission medium e.g., a bare conductor, an insulated conductor, a conduit, a non-conducting material such as a dielectric strip, or any other type of object suitable for the propagation of surface waves
  • electromagnetic waves can propagate in an open circuit, i.e., a circuit without an electrical return path or with a break or gap that prevents the flow of electrical current through the circuit
  • electromagnetic waves can also propagate along a surface of a transmission medium that is in fact part of an electrical circuit. That is electromagnetic waves can travel along a first surface of a transmission medium having a forward electrical path and/or along a second surface of a transmission medium having an electrical return path.
  • guided electromagnetic waves can propagate along a surface of a transmission medium from a sending device to a receiving device or vice-versa with or without an electrical circuit.
  • This also permits, for example, transmission of guided electromagnetic waves that propagate along a transmission medium having no more than a single conductor (e.g., an electromagnetic wave that propagates along the surface of a single bare conductor or along the surface of a single insulated conductor or an electromagnetic wave that propagates all or partly within the insulation of an insulated conductor).
  • a transmission medium includes one or more conductive components and the guided electromagnetic waves propagating along the transmission medium generate currents that, at times, flow in the one or more conductive components in a direction of the guided electromagnetic waves
  • such guided electromagnetic waves can propagate along the transmission medium from a sending device to a receiving device without a flow of an opposing current on an electrical return path back to the sending device from the receiving device.
  • the propagation of such guided electromagnetic waves can be referred to as propagating via a single transmission line or propagating via a surface wave transmission line.
  • a coaxial cable having a center conductor and a ground shield that are separated by an insulator.
  • a first terminal of a sending (and receiving) device can be connected to the center conductor, and a second terminal of the sending (and receiving) device can be connected to the ground shield. If the sending device injects an electrical signal in the center conductor via the first terminal, the electrical signal will propagate along the center conductor causing, at times, forward currents and a corresponding flow of electrons in the center conductor, and return currents and an opposing flow of electrons in the ground shield. The same conditions apply for a two terminal receiving device.
  • the guided wave communication system of the subject disclosure can be configured to induce guided electromagnetic waves that propagate along an outer surface of a coaxial cable (e.g., the outer jacket or insulation layer of the coaxial cable).
  • a coaxial cable e.g., the outer jacket or insulation layer of the coaxial cable.
  • the guided electromagnetic waves will cause forward currents on the ground shield, the guided electromagnetic waves will not generate opposing return currents in the center conductor (or other electrical return path).
  • the same can be said of other transmission media used by a guided wave communication system for the transmission and reception of guided electromagnetic waves.
  • guided electromagnetic waves induced by the guided wave communication system on an outer surface of a bare conductor, or an insulated conductor can propagate along the outer surface of the bare conductor or the other surface of the insulated conductor without generating opposing return currents in an electrical return path.
  • guided electromagnetic waves propagating in a guided wave communication system on an outer surface of a bare conductor cause only minimal forward currents in the bare conductor, with the majority of the signal energy of the electromagnetic wave concentrated above the outer surface of the bare conductor and not inside the bare conductor.
  • guided electromagnetic waves that are bound to the outer surface of an insulated conductor cause only minimal forward currents in the center conductor or conductors of the insulated conductor, with the majority of the signal energy of the electromagnetic wave concentrated in regions inside the insulation and/or above the outside surface of the insulated conductor - in other words, the majority of the signal energy of the electromagnetic wave is concentrated outside the center conductor(s) of the insulated conductor.
  • electrical systems that require two or more conductors for carrying forward and reverse currents on separate conductors to enable the propagation of electrical signals injected by a sending device are distinct from guided wave systems that induce guided electromagnetic waves on an interface of a transmission medium without the need of an electrical circuit to enable the propagation of the guided electromagnetic waves along the interface of the transmission medium.
  • guided electromagnetic waves as described in the subject disclosure can have an electromagnetic field structure that lies primarily or substantially outside of a transmission medium so as to be bound to or guided by the transmission medium and so as to propagate non-trivial distances on or along an outer surface of the transmission medium.
  • guided electromagnetic waves can have an electromagnetic field structure that lies primarily or substantially inside a transmission medium so as to be bound to or guided by the transmission medium and so as to propagate non-trivial distances within the transmission medium.
  • guided electromagnetic waves can have an electromagnetic field structure that lies partially inside and partially outside a transmission medium so as to be bound to or guided by the transmission medium and so as to propagate non-trivial distances along the transmission medium.
  • the desired electronic field structure in an embodiment may vary based upon a variety of factors, including the desired transmission distance, the characteristics of the transmission medium itself, and environmental conditions/characteristics outside of the transmission medium (e.g., presence of rain, fog, atmospheric conditions, etc.).
  • Various embodiments described herein relate to coupling devices, that can be referred to as “waveguide coupling devices”, “waveguide couplers” or more simply as “couplers”, “coupling devices” or “launchers” for launching and/or extracting guided electromagnetic waves to and from a transmission medium at millimeter- wave frequencies (e.g., 30 to 300 GHz), wherein the wavelength can be small compared to one or more dimensions of the coupling device and/or the transmission medium such as the circumference of a wire or other cross sectional dimension, or lower microwave frequencies such as 300MHz to 30GHz.
  • millimeter- wave frequencies e.g., 30 to 300 GHz
  • Transmissions can be generated to propagate as waves guided by a coupling device, such as: a strip, arc or other length of dielectric material; a horn, monopole, rod, slot or other antenna; an array of antennas; a magnetic resonant cavity, or other resonant coupler; a coil, a strip line, a waveguide or other coupling device.
  • the coupling device receives an electromagnetic wave from a transmitter or transmission medium.
  • the electromagnetic field structure of the electromagnetic wave can be carried inside the coupling device, outside the coupling device or some combination thereof.
  • the coupling device is in close proximity to a transmission medium, at least a portion of an electromagnetic wave couples to or is bound to the transmission medium, and continues to propagate as guided electromagnetic waves.
  • a coupling device can extract guided waves from a transmission medium and transfer these electromagnetic waves to a receiver.
  • a surface wave is a type of guided wave that is guided by a surface of a transmission medium, such as an exterior or outer surface of the wire, or another surface of the wire that is adjacent to or exposed to another type of medium having different properties (e.g., dielectric properties).
  • a surface of the wire that guides a surface wave can represent a transitional surface between two different types of media.
  • the surface of the wire can be the outer or exterior conductive surface of the bare or uninsulated wire that is exposed to air or free space.
  • the surface of the wire can be the conductive portion of the wire that meets the insulator portion of the wire, or can otherwise be the insulator surface of the wire that is exposed to air or free space, or can otherwise be any material region between the insulator surface of the wire and the conductive portion of the wire that meets the insulator portion of the wire, depending upon the relative differences in the properties (e.g., dielectric properties) of the insulator, air, and/or the conductor and further dependent on the frequency and propagation mode or modes of the guided wave.
  • properties e.g., dielectric properties
  • the term "about" a wire or other transmission medium used in conjunction with a guided wave can include fundamental guided wave propagation modes such as a guided waves having a circular or substantially circular field distribution, a symmetrical electromagnetic field distribution (e.g., electric field, magnetic field, electromagnetic field, etc.) or other fundamental mode pattern at least partially around a wire or other transmission medium.
  • fundamental guided wave propagation modes such as a guided waves having a circular or substantially circular field distribution, a symmetrical electromagnetic field distribution (e.g., electric field, magnetic field, electromagnetic field, etc.) or other fundamental mode pattern at least partially around a wire or other transmission medium.
  • a guided wave when it propagates "about" a wire or other transmission medium, it can do so according to a guided wave propagation mode that includes not only the fundamental wave propagation modes (e.g., zero order modes), but additionally or alternatively non-fundamental wave propagation modes such as higher-order guided wave modes (e.g., 1 st order modes, 2 nd order modes, etc.), asymmetrical modes and/or other guided (e.g., surface) waves that have non-circular field distributions around a wire or other transmission medium.
  • the term "guided wave mode” refers to a guided wave propagation mode of a transmission medium, coupling device or other system component of a guided wave communication system.
  • such non-circular field distributions can be unilateral or multilateral with one or more axial lobes characterized by relatively higher field strength and/or one or more nulls or null regions characterized by relatively low-field strength, zero-field strength or substantially zero-field strength.
  • the field distribution can otherwise vary as a function of azimuthal orientation around the wire such that one or more angular regions around the wire have an electric or magnetic field strength (or combination thereof) that is higher than one or more other angular regions of azimuthal orientation, according to an example embodiment.
  • the relative orientations or positions of the guided wave higher order modes or asymmetrical modes can vary as the guided wave travels along the wire.
  • millimeter-wave can refer to electromagnetic waves/signals that fall within the "millimeter-wave frequency band” of 30 GHz to 300 GHz.
  • microwave can refer to electromagnetic waves/signals that fall within a "microwave frequency band” of 300 MHz to 300 GHz.
  • radio frequency or “RF” can refer to electromagnetic waves/signals that fall within the "radio frequency band” of 10 kHz to 1 THz. It is appreciated that wireless signals, electrical signals, and guided electromagnetic waves as described in the subject disclosure can be configured to operate at any desirable frequency range, such as, for example, at frequencies within, above or below millimeter-wave and/or microwave frequency bands.
  • the frequency of the guided electromagnetic waves that are carried by the coupling device and/or propagate along the transmission medium can be below the mean collision frequency of the electrons in the conductive element.
  • the frequency of the guided electromagnetic waves that are carried by the coupling device and/or propagate along the transmission medium can be a non-optical frequency, e.g., a radio frequency below the range of optical frequencies that begins at 1 THz.
  • the term "antenna” can refer to a device that is part of a transmitting or receiving system to transmit/radiate or receive wireless signals.
  • a method includes receiving a plurality of communication signals, and generating, by a transmitting device according to the plurality of communication signals, wireless signals to induce a plurality of electromagnetic waves bound at least in part to an insulated transmission medium, wherein the plurality of electromagnetic waves propagate along the insulated transmission medium without an electrical return path, wherein each electromagnetic wave of the plurality of electromagnetic waves conveys at least one communication signal of the plurality of communication signals, wherein the plurality of electromagnetic waves have a signal multiplexing configuration that reduces interference between the plurality of electromagnetic waves and enables a receiving device to retrieve from each electromagnetic wave of the plurality of electromagnetic waves the at least one communication signal.
  • a launcher can include a generator, and a circuit coupled to the generator.
  • the controller performs operations including receiving a plurality of communication signals, and generating, according to the plurality of communication signals, signals that induce a plurality of electromagnetic waves bound at least in part to a dielectric layer of a transmission medium, wherein each electromagnetic wave of the plurality of electromagnetic waves conveys at least one communication signal of the plurality of communication signals, and wherein the plurality of electromagnetic waves has a signal multiplexing configuration that reduces interference between the plurality of electromagnetic waves.
  • a device includes means for receiving a plurality of communication signals, and means for generating, according to a plurality of communication signals, signals that induce a plurality of electromagnetic waves bound at least in part to a dielectric material, wherein each electromagnetic wave of the plurality of electromagnetic waves conveys at least one communication signal of the plurality of communication signals, wherein the plurality of electromagnetic waves has a multiplexing configuration that reduces interference between the plurality of electromagnetic waves.
  • a transmission device 101 receives one or more communication signals 110 from a communication network or other communications device that includes data and generates guided waves 120 to convey the data via the transmission medium 125 to the transmission device 102.
  • the transmission device 102 receives the guided waves 120 and converts them to communication signals 112 that include the data for transmission to a communications network or other communications device.
  • the guided waves 120 can be modulated to convey data via a modulation technique such as phase shift keying, frequency shift keying, quadrature amplitude modulation, amplitude modulation, multi-carrier modulation such as orthogonal frequency division multiplexing and via multiple access techniques such as frequency division multiplexing, time division multiplexing, code division multiplexing, multiplexing via differing wave propagation modes and via other modulation and access strategies.
  • a modulation technique such as phase shift keying, frequency shift keying, quadrature amplitude modulation, amplitude modulation, multi-carrier modulation such as orthogonal frequency division multiplexing and via multiple access techniques such as frequency division multiplexing, time division multiplexing, code division multiplexing, multiplexing via differing wave propagation modes and via other modulation and access strategies.
  • the communication network or networks can include a wireless communication network such as a mobile data network, a cellular voice and data network, a wireless local area network (e.g., WiFi or an 802.xx network), a satellite communications network, a personal area network or other wireless network.
  • the communication network or networks can also include a wired communication network such as a telephone network, an Ethernet network, a local area network, a wide area network such as the Internet, a broadband access network, a cable network, a fiber optic network, or other wired network.
  • the communication devices can include a network edge device, bridge device or home gateway, a set-top box, broadband modem, telephone adapter, access point, base station, or other fixed communication device, a mobile communication device such as an automotive gateway or automobile, laptop computer, tablet, smartphone, cellular telephone, or other communication device.
  • the guided wave communication system 100 can operate in a bi-directional fashion where transmission device 102 receives one or more communication signals 112 from a communication network or device that includes other data and generates guided waves 122 to convey the other data via the transmission medium 125 to the transmission device 101.
  • the transmission device 101 receives the guided waves 122 and converts them to communication signals 110 that include the other data for transmission to a communications network or device.
  • the guided waves 122 can be modulated to convey data via a modulation technique such as phase shift keying, frequency shift keying, quadrature amplitude modulation, amplitude modulation, multi-carrier modulation such as orthogonal frequency division multiplexing and via multiple access techniques such as frequency division multiplexing, time division multiplexing, code division multiplexing, multiplexing via differing wave propagation modes and via other modulation and access strategies.
  • a modulation technique such as phase shift keying, frequency shift keying, quadrature amplitude modulation, amplitude modulation, multi-carrier modulation such as orthogonal frequency division multiplexing and via multiple access techniques such as frequency division multiplexing, time division multiplexing, code division multiplexing, multiplexing via differing wave propagation modes and via other modulation and access strategies.
  • the transmission medium 125 can include a cable having at least one inner portion surrounded by a dielectric material such as an insulator or other dielectric cover, coating or other dielectric material, the dielectric material having an outer surface and
  • the transmission medium 125 operates as a single-wire transmission line to guide the transmission of an electromagnetic wave.
  • the transmission medium 125 can include a wire.
  • the wire can be insulated or uninsulated, and single- stranded or multi-stranded (e.g., braided).
  • the transmission medium 125 can contain conductors of other shapes or configurations including wire bundles, cables, rods, rails, pipes.
  • the transmission medium 125 can include non-conductors such as dielectric pipes, rods, rails, or other dielectric members; combinations of conductors and dielectric materials, conductors without dielectric materials or other guided wave transmission media. It should be noted that the transmission medium 125 can otherwise include any of the transmission media previously discussed.
  • the guided waves 120 and 122 can be contrasted with radio transmissions over free space / air or conventional propagation of electrical power or signals through the conductor of a wire via an electrical circuit.
  • the transmission medium 125 may optionally contain one or more wires that propagate electrical power or other communication signals in a conventional manner as a part of one or more electrical circuits.
  • the transmission device 101 or 102 includes a communications interface (I/F) 205, a transceiver 210 and a coupler 220.
  • I/F communications interface
  • transceiver 210 transceiver 210
  • coupler 220 coupler
  • the communications interface 205 receives a communication signal 110 or 112 that includes data.
  • the communications interface 205 can include a wireless interface for receiving a wireless communication signal in accordance with a wireless standard protocol such as LTE or other cellular voice and data protocol, WiFi or an 802.11 protocol, WIMAX protocol, Ultra Wideband protocol, Bluetooth protocol, Zigbee protocol, a direct broadcast satellite (DBS) or other satellite communication protocol or other wireless protocol.
  • a wireless standard protocol such as LTE or other cellular voice and data protocol, WiFi or an 802.11 protocol, WIMAX protocol, Ultra Wideband protocol, Bluetooth protocol, Zigbee protocol, a direct broadcast satellite (DBS) or other satellite communication protocol or other wireless protocol.
  • the communications interface 205 includes a wired interface that operates in accordance with an Ethernet protocol, universal serial bus (USB) protocol, a data over cable service interface specification (DOCSIS) protocol, a digital subscriber line (DSL) protocol, a Firewire (IEEE 1394) protocol, or other wired protocol.
  • DOCSIS data over cable service interface specification
  • DSL digital subscriber line
  • Firewire IEEE 1394
  • the communications interface 205 can operate in conjunction with other wired or wireless protocol.
  • the communications interface 205 can optionally operate in conjunction with a protocol stack that includes multiple protocol layers including a MAC protocol, transport protocol, application protocol, etc.
  • the transceiver 210 generates an electromagnetic wave based on the communication signal 110 or 112 to convey the data.
  • the electromagnetic wave has at least one carrier frequency and at least one corresponding wavelength.
  • the carrier frequency can be within a millimeter-wave frequency band of 30GHz - 300GHz, such as 60GHz or a carrier frequency in the range of 30-40GHz or a lower frequency band of 300 MHz - 30GHz in the microwave frequency range such as 26- 30GHz, 11 GHz, 6 GHz or 3GHz, but it will be appreciated that other carrier frequencies are possible in other embodiments.
  • the transceiver 210 merely upconverts the communications signal or signals 110 or 112 for transmission of the electromagnetic signal in the microwave or millimeter-wave band as a guided electromagnetic wave that is guided by or bound to the transmission medium 125.
  • the communications interface 205 either converts the communication signal 110 or l l2 to a baseband or near baseband signal or extracts the data from the communication signal 110 or 112 and the transceiver 210 modulates a high- frequency carrier with the data, the baseband or near baseband signal for transmission.
  • the transceiver 210 can modulate the data received via the communication signal 110 or 112 to preserve one or more data communication protocols of the communication signal 110 or 112 either by encapsulation in the payload of a different protocol or by simple frequency shifting. In the alternative, the transceiver 210 can otherwise translate the data received via the communication signal 110 or l l2 to a protocol that is different from the data communication protocol or protocols of the communication signal 110 or 112.
  • the coupler 220 couples the electromagnetic wave to the transmission medium 125 as a guided electromagnetic wave to convey the communications signal or signals 110 or 112. While the prior description has focused on the operation of the transceiver 210 as a transmitter, the transceiver 210 can also operate to receive electromagnetic waves that convey other data from the single wire transmission medium via the coupler 220 and to generate communications signals 110 or 112, via communications interface 205 that includes the other data. Consider embodiments where an additional guided electromagnetic wave conveys other data that also propagates along the transmission medium 125. The coupler 220 can also couple this additional electromagnetic wave from the transmission medium 125 to the transceiver 210 for reception.
  • the transmission device 101 or 102 includes an optional training controller 230.
  • the training controller 230 is implemented by a standalone processor or a processor that is shared with one or more other components of the transmission device 101 or 102.
  • the training controller 230 selects the carrier frequencies, modulation schemes and/or guided wave modes for the guided electromagnetic waves based on feedback data received by the transceiver 210 from at least one remote transmission device coupled to receive the guided electromagnetic wave.
  • a guided electromagnetic wave transmitted by a remote transmission device 101 or 102 conveys data that also propagates along the transmission medium 125.
  • the data from the remote transmission device 101 or 102 can be generated to include the feedback data.
  • the coupler 220 also couples the guided electromagnetic wave from the transmission medium 125 and the transceiver receives the electromagnetic wave and processes the electromagnetic wave to extract the feedback data.
  • the training controller 230 operates based on the feedback data to evaluate a plurality of candidate frequencies, modulation schemes and/or transmission modes to select a carrier frequency, modulation scheme and/or transmission mode to enhance performance, such as throughput, signal strength, reduce propagation loss, etc.
  • a transmission device 101 begins operation under control of the training controller 230 by sending a plurality of guided waves as test signals such as pilot waves or other test signals at a corresponding plurality of candidate frequencies and/or candidate modes directed to a remote transmission device 102 coupled to the transmission medium 125.
  • the guided waves can include, in addition or in the alternative, test data.
  • the test data can indicate the particular candidate frequency and/or guide-wave mode of the signal.
  • the training controller 230 at the remote transmission device 102 receives the test signals and/or test data from any of the guided waves that were properly received and determines the best candidate frequency and/or guided wave mode, a set of acceptable candidate frequencies and/or guided wave modes, or a rank ordering of candidate frequencies and/or guided wave modes.
  • This selection of candidate frequenc(ies) or/and guided-mode(s) are generated by the training controller 230 based on one or more optimizing criteria such as received signal strength, bit error rate, packet error rate, signal to noise ratio, propagation loss, etc.
  • the training controller 230 generates feedback data that indicates the selection of candidate frequenc(ies) or/and guided wave mode(s) and sends the feedback data to the transceiver 210 for transmission to the transmission device 101.
  • the transmission device 101 and 102 can then communicate data with one another based on the selection of candidate frequenc(ies) or/and guided wave mode(s).
  • the guided electromagnetic waves that contain the test signals and/or test data are reflected back, repeated back or otherwise looped back by the remote transmission device 102 to the transmission device 101 for reception and analysis by the training controller 230 of the transmission device 101 that initiated these waves.
  • the transmission device 101 can send a signal to the remote transmission device 102 to initiate a test mode where a physical reflector is switched on the line, a termination impedance is changed to cause reflections, a loop back mode is switched on to couple electromagnetic waves back to the source transmission device 102, and/or a repeater mode is enabled to amplify and retransmit the electromagnetic waves back to the source transmission device 102.
  • the training controller 230 at the source transmission device 102 receives the test signals and/or test data from any of the guided waves that were properly received and determines selection of candidate frequenc(ies) or/and guided wave mode(s).
  • each transmission device 101 or 102 can send test signals, evaluate candidate frequencies or guided wave modes via non-test such as normal transmissions or otherwise evaluate candidate frequencies or guided wave modes at other times or continuously as well.
  • the communication protocol between the transmission devices 101 and 102 can include an on-request or periodic test mode where either full testing or more limited testing of a subset of candidate frequencies and guided wave modes are tested and evaluated.
  • the re-entry into such a test mode can be triggered by a degradation of performance due to a disturbance, weather conditions, etc.
  • the receiver bandwidth of the transceiver 210 is either sufficiently wide or swept to receive all candidate frequencies or can be selectively adjusted by the training controller 230 to a training mode where the receiver bandwidth of the transceiver 210 is sufficiently wide or swept to receive all candidate frequencies.
  • a transmission medium 125 in air includes an inner conductor 301 and an insulating jacket 302 of dielectric material, as shown in cross section.
  • the diagram 300 includes different gray-scales that represent differing electromagnetic field strengths generated by the propagation of the guided wave having an asymmetrical and non-fundamental guided wave mode.
  • the electromagnetic field distribution corresponds to a modal "sweet spot" that enhances guided electromagnetic wave propagation along an insulated transmission medium and reduces end-to-end transmission loss.
  • electromagnetic waves are guided by the transmission medium 125 to propagate along an outer surface of the transmission medium - in this case, the outer surface of the insulating jacket 302.
  • Electromagnetic waves are partially embedded in the insulator and partially radiating on the outer surface of the insulator. In this fashion, electromagnetic waves are "lightly" coupled to the insulator so as to enable electromagnetic wave propagation at long distances with low propagation loss.
  • the guided wave has a field structure that lies primarily or substantially outside of the transmission medium 125 that serves to guide the electromagnetic waves.
  • the regions inside the conductor 301 have little or no field.
  • regions inside the insulating jacket 302 have low field strength.
  • the majority of the electromagnetic field strength is distributed in the lobes 304 at the outer surface of the insulating jacket 302 and in close proximity thereof.
  • the presence of an asymmetric guided wave mode is shown by the high electromagnetic field strengths at the top and bottom of the outer surface of the insulating jacket 302 (in the orientation of the diagram) - as opposed to very small field strengths on the other sides of the insulating jacket 302.
  • the example shown corresponds to a 38 GHz electromagnetic wave guided by a wire with a diameter of 1.1 cm and a dielectric insulation of thickness of 0.36 cm. Because the electromagnetic wave is guided by the transmission medium 125 and the majority of the field strength is concentrated in the air outside of the insulating jacket 302 within a limited distance of the outer surface, the guided wave can propagate longitudinally down the transmission medium 125 with very low loss. In the example shown, this "limited distance" corresponds to a distance from the outer surface that is less than half the largest cross sectional dimension of the transmission medium 125. In this case, the largest cross sectional dimension of the wire corresponds to the overall diameter of 1.82 cm, however, this value can vary with the size and shape of the transmission medium 125.
  • the transmission medium 125 be of a rectangular shape with a height of .3cm and a width of .4cm, the largest cross sectional dimension would be the diagonal of .5cm and the corresponding limited distance would be .25cm.
  • the dimensions of the area containing the majority of the field strength also vary with the frequency, and in general, increase as carrier frequencies decrease.
  • the components of a guided wave communication system can have their own cut-off frequencies for each guided wave mode.
  • the cut-off frequency generally sets forth the lowest frequency that a particular guided wave mode is designed to be supported by that particular component.
  • the particular asymmetric mode of propagation shown is induced on the transmission medium 125 by an electromagnetic wave having a frequency that falls within a limited range (such as Fc to 2Fc) of the lower cut-off frequency Fc for this particular asymmetric mode.
  • the lower cut-off frequency Fc is particular to the characteristics of transmission medium 125.
  • this cutoff frequency can vary based on the dimensions and properties of the insulating jacket 302 and potentially the dimensions and properties of the inner conductor 301 and can be determined experimentally to have a desired mode pattern. It should be noted however, that similar effects can be found for a hollow dielectric or insulator without an inner conductor. In this case, the cutoff frequency can vary based on the dimensions and properties of the hollow dielectric or insulator.
  • the asymmetric mode is difficult to induce in the transmission medium 125 and fails to propagate for all but trivial distances.
  • the asymmetric mode shifts more and more inward of the insulating jacket 302.
  • the field strength is no longer concentrated outside of the insulating jacket, but primarily inside of the insulating jacket 302.
  • the transmission medium 125 provides strong guidance to the electromagnetic wave and propagation is still possible, ranges are more limited by increased losses due to propagation within the insulating jacket 302— as opposed to the surrounding air.
  • FIG. 4 a graphical diagram 400 illustrating an example, non- limiting embodiment of an electromagnetic field distribution is shown.
  • a cross section diagram 400 similar to FIG. 3 is shown with common reference numerals used to refer to similar elements.
  • the example shown corresponds to a 60 GHz wave guided by a wire with a diameter of 1.1 cm and a dielectric insulation of thickness of 0.36 cm. Because the frequency of the guided wave is above the limited range of the cut-off frequency of this particular asymmetric mode, much of the field strength has shifted inward of the insulating jacket 302. In particular, the field strength is concentrated primarily inside of the insulating jacket 302. While the transmission medium 125 provides strong guidance to the electromagnetic wave and propagation is still possible, ranges are more limited when compared with the embodiment of FIG. 3, by increased losses due to propagation within the insulating jacket 302.
  • diagram 500 presents a graph of end-to-end loss (in dB) as a function of frequency, overlaid with electromagnetic field distributions 510, 520 and 530 at three points for a 200cm insulated medium voltage wire.
  • the boundary between the insulator and the surrounding air is represented by reference numeral 525 in each electromagnetic field distribution.
  • an example of a desired asymmetric mode of propagation shown is induced on the transmission medium 125 by an electromagnetic wave having a frequency that falls within a limited range (such as Fc to 2Fc) of the lower cut-off frequency Fc of the transmission medium for this particular asymmetric mode.
  • the electromagnetic field distribution 520 at 6 GHz falls within this modal "sweet spot" that enhances electromagnetic wave propagation along an insulated transmission medium and reduces end-to-end transmission loss.
  • guided waves are partially embedded in the insulator and partially radiating on the outer surface of the insulator. In this fashion, the electromagnetic waves are "lightly" coupled to the insulator so as to enable guided electromagnetic wave propagation at long distances with low propagation loss.
  • the asymmetric mode radiates more heavily generating higher propagation losses.
  • the asymmetric mode shifts more and more inward of the insulating jacket providing too much absorption, again generating higher propagation losses.
  • FIG. 5B a graphical diagram 550 illustrating example, non- limiting embodiments of a longitudinal cross-section of a transmission medium 125, such as an insulated wire, depicting fields of guided electromagnetic waves at various operating frequencies is shown.
  • a transmission medium 125 such as an insulated wire
  • the guided electromagnetic waves are at approximately the cutoff frequency (f c ) corresponding to the modal "sweet spot"
  • the guided electromagnetic waves are loosely coupled to the insulated wire so that absorption is reduced, and the fields of the guided electromagnetic waves are bound sufficiently to reduce the amount radiated into the environment (e.g., air). Because absorption and radiation of the fields of the guided electromagnetic waves is low, propagation losses are consequently low, enabling the guided electromagnetic waves to propagate for longer distances.
  • propagation losses increase when the operating frequency of the guided electromagnetic waves is substantially below the cutoff frequency (f c ), as shown in diagram 558.
  • the guided electromagnetic waves are weakly (or nominally) bound to the insulated wire and thereby tend to radiate into the environment (e.g., air), which in turn, raises propagation losses due to radiation of the guided electromagnetic waves.
  • a graphical diagram 600 illustrating an example, non- limiting embodiment of an electromagnetic field distribution is shown.
  • a transmission medium 602 is a bare wire, as shown in cross section.
  • the diagram 300 includes different gray-scales that represent differing electromagnetic field strengths generated by the propagation of a guided wave having a symmetrical and fundamental guided wave mode at a single carrier frequency.
  • electromagnetic waves are guided by the transmission medium 602 to propagate along an outer surface of the transmission medium - in this case, the outer surface of the bare wire.
  • Electromagnetic waves are "lightly" coupled to the wire so as to enable electromagnetic wave propagation at long distances with low propagation loss.
  • the guided wave has a field structure that lies substantially outside of the transmission medium 602 that serves to guide the electromagnetic waves.
  • the regions inside the conductor 602 have little or no field.
  • FIG. 7 a block diagram 700 illustrating an example, non- limiting embodiment of an arc coupler is shown.
  • a coupling device is presented for use in a transmission device, such as transmission device 101 or 102 presented in conjunction with FIG. 1.
  • the coupling device includes an arc coupler 704 coupled to a transmitter circuit 712 and termination or damper 714.
  • the arc coupler 704 can be made of a dielectric material, or other low-loss insulator (e.g., Teflon, polyethylene, etc.), or made of a conducting (e.g., metallic, non-metallic, etc.) material, or any combination of the foregoing materials.
  • the arc coupler 704 operates as a waveguide and has a wave 706 propagating as a guided wave about a waveguide surface of the arc coupler 704.
  • at least a portion of the arc coupler 704 can be placed near a wire 702 or other transmission medium, (such as transmission medium 125), in order to facilitate coupling between the arc coupler 704 and the wire 702 or other transmission medium, as described herein to launch the guided wave 708 on the wire.
  • the arc coupler 704 can be placed such that a portion of the curved arc coupler 704 is tangential to, and parallel or substantially parallel to the wire 702.
  • the portion of the arc coupler 704 that is parallel to the wire can be an apex of the curve, or any point where a tangent of the curve is parallel to the wire 702.
  • the wave 706 travelling along the arc coupler 704 couples, at least in part, to the wire 702, and propagates as guided wave 708 around or about the wire surface of the wire 702 and longitudinally along the wire 702.
  • the guided wave 708 can be characterized as a surface wave or other electromagnetic wave that is guided by or bound to the wire 702 or other transmission medium.
  • a portion of the wave 706 that does not couple to the wire 702 propagates as a wave 710 along the arc coupler 704.
  • the arc coupler 704 can be configured and arranged in a variety of positions in relation to the wire 702 to achieve a desired level of coupling or non-coupling of the wave 706 to the wire 702.
  • the curvature and/or length of the arc coupler 704 that is parallel or substantially parallel, as well as its separation distance (which can include zero separation distance in an embodiment), to the wire 702 can be varied without departing from example embodiments.
  • the arrangement of arc coupler 704 in relation to the wire 702 may be varied based upon considerations of the respective intrinsic characteristics (e.g., thickness, composition, electromagnetic properties, etc.) of the wire 702 and the arc coupler 704, as well as the characteristics (e.g., frequency, energy level, etc.) of the waves 706 and 708.
  • the respective intrinsic characteristics e.g., thickness, composition, electromagnetic properties, etc.
  • the characteristics e.g., frequency, energy level, etc.
  • the guided wave 708 stays parallel or substantially parallel to the wire 702, even as the wire 702 bends and flexes. Bends in the wire 702 can increase transmission losses, which are also dependent on wire diameters, frequency, and materials. If the dimensions of the arc coupler 704 are chosen for efficient power transfer, most of the power in the wave 706 is transferred to the wire 702, with little power remaining in wave 710. It will be appreciated that the guided wave 708 can still be multi-modal in nature (discussed herein), including having modes that are non-fundamental or asymmetric, while traveling along a path that is parallel or substantially parallel to the wire 702, with or without a fundamental transmission mode. In an embodiment, non-fundamental or asymmetric modes can be utilized to minimize transmission losses and/or obtain increased propagation distances.
  • parallel is generally a geometric construct which often is not exactly achievable in real systems. Accordingly, the term parallel as utilized in the subject disclosure represents an approximation rather than an exact configuration when used to describe embodiments disclosed in the subject disclosure. In an embodiment, substantially parallel can include approximations that are within 30 degrees of true parallel in all dimensions.
  • the wave 706 can exhibit one or more wave propagation modes.
  • the arc coupler modes can be dependent on the shape and/or design of the coupler 704.
  • the one or more arc coupler modes of wave 706 can generate, influence, or impact one or more wave propagation modes of the guided wave 708 propagating along wire 702. It should be particularly noted however that the guided wave modes present in the guided wave 706 may be the same or different from the guided wave modes of the guided wave 708. In this fashion, one or more guided wave modes of the guided wave 706 may not be transferred to the guided wave 708, and further one or more guided wave modes of guided wave 708 may not have been present in guided wave 706.
  • the cut-off frequency of the arc coupler 704 for a particular guided wave mode may be different than the cutoff frequency of the wire 702 or other transmission medium for that same mode.
  • the wire 702 or other transmission medium may be operated slightly above its cutoff frequency for a particular guided wave mode
  • the arc coupler 704 may be operated well above its cut-off frequency for that same mode for low loss, slightly below its cut-off frequency for that same mode to, for example, induce greater coupling and power transfer, or some other point in relation to the arc coupler's cutoff frequency for that mode.
  • the wave propagation modes on the wire 702 can be similar to the arc coupler modes since both waves 706 and 708 propagate about the outside of the arc coupler 704 and wire 702 respectively.
  • the modes can change form, or new modes can be created or generated, due to the coupling between the arc coupler 704 and the wire 702.
  • differences in size, material, and/or impedances of the arc coupler 704 and wire 702 may create additional modes not present in the arc coupler modes and/or suppress some of the arc coupler modes.
  • the wave propagation modes can comprise the fundamental transverse electromagnetic mode (Quasi-TEMoo), where only small electric and/or magnetic fields extend in the direction of propagation, and the electric and magnetic fields extend radially outwards while the guided wave propagates along the wire.
  • This guided wave mode can be donut shaped, where few of the electromagnetic fields exist within the arc coupler 704 or wire 702.
  • Waves 706 and 708 can comprise a fundamental TEM mode where the fields extend radially outwards, and also comprise other, non-fundamental (e.g., asymmetric, higher-level, etc.) modes. While particular wave propagation modes are discussed above, other wave propagation modes are likewise possible such as transverse electric (TE) and transverse magnetic (TM) modes, based on the frequencies employed, the design of the arc coupler 704, the dimensions and composition of the wire 702, as well as its surface characteristics, its insulation if present, the electromagnetic properties of the surrounding environment, etc.
  • TE transverse electric
  • TM transverse magnetic
  • guided wave 708 can travel along the conductive surface of an oxidized uninsulated wire, an unoxidized uninsulated wire, an insulated wire and/or along the insulating surface of an insulated wire.
  • a diameter of the arc coupler 704 is smaller than the diameter of the wire 702.
  • the arc coupler 704 supports a single waveguide mode that makes up wave 706. This single waveguide mode can change as it couples to the wire 702 as guided wave 708. If the arc coupler 704 were larger, more than one waveguide mode can be supported, but these additional waveguide modes may not couple to the wire 702 as efficiently, and higher coupling losses can result.
  • the diameter of the arc coupler 704 can be equal to or larger than the diameter of the wire 702, for example, where higher coupling losses are desirable or when used in conjunction with other techniques to otherwise reduce coupling losses (e.g., impedance matching with tapering, etc.).
  • the wavelength of the waves 706 and 708 are comparable in size, or smaller than a circumference of the arc coupler 704 and the wire 702.
  • the wavelength of the transmission is around 1.5 cm or less, corresponding to a frequency of 70 GHz or greater.
  • a suitable frequency of the transmission and the carrier-wave signal is in the range of 30 - 100 GHz, perhaps around 30-60 GHz, and around 38 GHz in one example.
  • the waves 706 and 708 can exhibit multiple wave propagation modes including fundamental and/or non-fundamental (symmetric and/or asymmetric) modes that propagate over sufficient distances to support various communication systems described herein.
  • the waves 706 and 708 can therefore comprise more than one type of electric and magnetic field configuration.
  • the guided wave 708 propagates down the wire 702
  • the electrical and magnetic field configurations will remain the same from end to end of the wire 702.
  • the electric and magnetic field configurations can change as the guided wave 708 propagates down wire 702.
  • the arc coupler 704 can be composed of nylon, Teflon, polyethylene, a polyamide, or other plastics. In other embodiments, other dielectric materials are possible.
  • the wire surface of wire 702 can be metallic with either a bare metallic surface, or can be insulated using plastic, dielectric, insulator or other coating, jacket or sheathing.
  • a dielectric or otherwise non-conducting/insulated waveguide can be paired with either a bare/metallic wire or insulated wire.
  • a metallic and/or conductive waveguide can be paired with a bare/metallic wire or insulated wire.
  • an oxidation layer on the bare metallic surface of the wire 702 (e.g., resulting from exposure of the bare metallic surface to oxygen/air) can also provide insulating or dielectric properties similar to those provided by some insulators or sheathings.
  • wave 706 induces or otherwise launches a guided wave 708 on a wire 702 that operates, for example, as a single wire transmission line.
  • Wave 710 represents the portion of wave 706 that remains on the arc coupler 704 after the generation of guided wave 708.
  • the actual electric and magnetic fields generated as a result of such wave propagation may vary depending on the frequencies employed, the particular wave propagation mode or modes, the design of the arc coupler 704, the dimensions and composition of the wire 702, as well as its surface characteristics, its optional insulation, the electromagnetic properties of the surrounding environment, etc.
  • arc coupler 704 can include a termination circuit or damper 714 at the end of the arc coupler 704 that can absorb leftover radiation or energy from wave 710.
  • the termination circuit or damper 714 can prevent and/or minimize the leftover radiation or energy from wave 710 reflecting back toward transmitter circuit 712.
  • the termination circuit or damper 714 can include termination resistors, and/or other components that perform impedance matching to attenuate reflection.
  • these transmitter 712 and termination circuits or dampers 714 may not be depicted in the other figures, but in those embodiments, transmitter and termination circuits or dampers may possibly be used.
  • a single arc coupler 704 is presented that generates a single guided wave 708, multiple arc couplers 704 placed at different points along the wire 702 and/or at different azimuthal orientations about the wire can be employed to generate and receive multiple guided waves 708 at the same or different frequencies, at the same or different phases, at the same or different wave propagation modes.
  • FIG. 8 a block diagram 800 illustrating an example, non-limiting embodiment of an arc coupler is shown.
  • the coupler 704 can be placed near a wire 702 or other transmission medium, (such as transmission medium 125), in order to facilitate coupling between the arc coupler 704 and the wire 702 or other transmission medium, to extract a portion of the guided wave 806 as a guided wave 808 as described herein.
  • the arc coupler 704 can be placed such that a portion of the curved arc coupler 704 is tangential to, and parallel or substantially parallel to the wire 702.
  • the portion of the arc coupler 704 that is parallel to the wire can be an apex of the curve, or any point where a tangent of the curve is parallel to the wire 702.
  • the wave 806 travelling along the wire 702 couples, at least in part, to the arc coupler 704, and propagates as guided wave 808 along the arc coupler 704 to a receiving device (not expressly shown).
  • a portion of the wave 806 that does not couple to the arc coupler propagates as wave 810 along the wire 702 or other transmission medium.
  • the wave 806 can exhibit one or more wave propagation modes.
  • the arc coupler modes can be dependent on the shape and/or design of the coupler 704.
  • the one or more modes of guided wave 806 can generate, influence, or impact one or more guide- wave modes of the guided wave 808 propagating along the arc coupler 704.
  • the guided wave modes present in the guided wave 806 may be the same or different from the guided wave modes of the guided wave 808. In this fashion, one or more guided wave modes of the guided wave 806 may not be transferred to the guided wave 808, and further one or more guided wave modes of guided wave 808 may not have been present in guided wave 806.
  • FIG. 9A a block diagram 900 illustrating an example, non- limiting embodiment of a stub coupler is shown.
  • a coupling device that includes stub coupler 904 is presented for use in a transmission device, such as transmission device 101 or 102 presented in conjunction with FIG. 1.
  • the stub coupler 904 can be made of a dielectric material, or other low-loss insulator (e.g., Teflon, polyethylene and etc.), or made of a conducting (e.g., metallic, non-metallic, etc.) material, or any combination of the foregoing materials.
  • the stub coupler 904 operates as a waveguide and has a wave 906 propagating as a guided wave about a waveguide surface of the stub coupler 904.
  • at least a portion of the stub coupler 904 can be placed near a wire 702 or other transmission medium, (such as transmission medium 125), in order to facilitate coupling between the stub coupler 904 and the wire 702 or other transmission medium, as described herein to launch the guided wave 908 on the wire.
  • the stub coupler 904 is curved, and an end of the stub coupler 904 can be tied, fastened, or otherwise mechanically coupled to a wire 702.
  • the end of the stub coupler 904 is fastened to the wire 702
  • the end of the stub coupler 904 is parallel or substantially parallel to the wire 702.
  • another portion of the dielectric waveguide beyond an end can be fastened or coupled to wire 702 such that the fastened or coupled portion is parallel or substantially parallel to the wire 702.
  • the fastener 910 can be a nylon cable tie or other type of non-conducting/dielectric material that is either separate from the stub coupler 904 or constructed as an integrated component of the stub coupler 904.
  • the stub coupler 904 can be adjacent to the wire 702 without surrounding the wire 702.
  • the guided wave 906 travelling along the stub coupler 904 couples to the wire 702, and propagates as guided wave 908 about the wire surface of the wire 702.
  • the guided wave 908 can be characterized as a surface wave or other electromagnetic wave.
  • wave 906 and 908 are presented merely to illustrate the principles that wave 906 induces or otherwise launches a guided wave 908 on a wire 702 that operates, for example, as a single wire transmission line.
  • the actual electric and magnetic fields generated as a result of such wave propagation may vary depending on one or more of the shape and/or design of the coupler, the relative position of the dielectric waveguide to the wire, the frequencies employed, the design of the stub coupler 904, the dimensions and composition of the wire 702, as well as its surface characteristics, its optional insulation, the electromagnetic properties of the surrounding environment, etc.
  • an end of stub coupler 904 can taper towards the wire 702 in order to increase coupling efficiencies. Indeed, the tapering of the end of the stub coupler 904 can provide impedance matching to the wire 702 and reduce reflections, according to an example embodiment of the subject disclosure. For example, an end of the stub coupler 904 can be gradually tapered in order to obtain a desired level of coupling between waves 906 and 908 as illustrated in FIG. 9A.
  • the fastener 910 can be placed such that there is a short length of the stub coupler 904 between the fastener 910 and an end of the stub coupler 904. Maximum coupling efficiencies are realized in this embodiment when the length of the end of the stub coupler 904 that is beyond the fastener 910 is at least several wavelengths long for whatever frequency is being transmitted.
  • FIG. 9B a diagram 950 illustrating an example, non-limiting embodiment of an electromagnetic distribution in accordance with various aspects described herein is shown.
  • an electromagnetic distribution is presented in two dimensions for a transmission device that includes coupler 952, shown in an example stub coupler constructed of a dielectric material.
  • the coupler 952 couples an electromagnetic wave for propagation as a guided wave along an outer surface of a wire 702 or other transmission medium.
  • the coupler 952 guides the electromagnetic wave to a junction at xo via a symmetrical guided wave mode. While some of the energy of the electromagnetic wave that propagates along the coupler 952 is outside of the coupler 952, the majority of the energy of this electromagnetic wave is contained within the coupler 952.
  • the junction at xo couples the electromagnetic wave to the wire 702 or other transmission medium at an azimuthal angle corresponding to the bottom of the transmission medium. This coupling induces an electromagnetic wave that is guided to propagate along the outer surface of the wire 702 or other transmission medium via at least one guided wave mode in direction 956. The majority of the energy of the guided electromagnetic wave is outside or, but in close proximity to the outer surface of the wire 702 or other transmission medium.
  • the junction at xo forms an electromagnetic wave that propagates via both a symmetrical mode and at least one asymmetrical surface mode, such as the first order mode presented in conjunction with FIG. 3, that skims the surface of the wire 702 or other transmission medium.
  • FIG. 10A illustrated is a block diagram 1000 of an example, non-limiting embodiment of a coupler and transceiver system in accordance with various aspects described herein.
  • the system is an example of transmission device 101 or 102.
  • the communication interface 1008 is an example of communications interface 205
  • the stub coupler 1002 is an example of coupler 220
  • the transmitter/receiver device 1006, diplexer 1016, power amplifier 1014, low noise amplifier 1018, frequency mixers 1010 and 1020 and local oscillator 1012 collectively form an example of transceiver 210.
  • the transmitter/receiver device 1006 launches and receives waves (e.g., guided wave 1004 onto stub coupler 1002).
  • the guided waves 1004 can be used to transport signals received from and sent to a host device, base station, mobile devices, a building or other device by way of a communications interface 1008.
  • the communications interface 1008 can be an integral part of system 1000. Alternatively, the communications interface 1008 can be tethered to system 1000.
  • the communications interface 1008 can comprise a wireless interface for interfacing to the host device, base station, mobile devices, a building or other device utilizing any of various wireless signaling protocols (e.g., LTE, WiFi, WiMAX, IEEE 802.
  • the communications interface 1008 can also comprise a wired interface such as a fiber optic line, coaxial cable, twisted pair, category 5 (CAT-5) cable or other suitable wired or optical mediums for communicating with the host device, base station, mobile devices, a building or other device via a protocol such as an Ethernet protocol, universal serial bus (USB) protocol, a data over cable service interface specification (DOCSIS) protocol, a digital subscriber line (DSL) protocol, a Firewire (IEEE 1394) protocol, or other wired or optical protocol.
  • DOCSIS data over cable service interface specification
  • DSL digital subscriber line
  • Firewire IEEE 1394
  • the output signals (e.g., Tx) of the communications interface 1008 can be combined with a carrier wave (e.g., millimeter-wave carrier wave) generated by a local oscillator 1012 at frequency mixer 1010.
  • Frequency mixer 1010 can use heterodyning techniques or other frequency shifting techniques to frequency shift the output signals from communications interface 1008.
  • signals sent to and from the communications interface 1008 can be modulated signals such as orthogonal frequency division multiplexed (OFDM) signals formatted in accordance with a Long-Term Evolution (LTE) wireless protocol or other wireless 3G, 4G, 5G or higher voice and data protocol, a Zigbee, WIMAX, UltraWideband or IEEE 802.11 wireless protocol; a wired protocol such as an Ethernet protocol, universal serial bus (USB) protocol, a data over cable service interface specification (DOCSIS) protocol, a digital subscriber line (DSL) protocol, a Firewire (IEEE 1394) protocol or other wired or wireless protocol.
  • LTE Long-Term Evolution
  • this frequency conversion can be done in the analog domain, and as a result, the frequency shifting can be done without regard to the type of communications protocol used by a base station, mobile devices, or in-building devices.
  • the communications interface 1008 can be upgraded (e.g., updated with software, firmware, and/or hardware) or replaced and the frequency shifting and transmission apparatus can remain, simplifying upgrades.
  • the carrier wave can then be sent to a power amplifier ("PA") 1014 and can be transmitted via the transmitter receiver device 1006 via the diplexer 1016.
  • PA power amplifier
  • Signals received from the transmitter/receiver device 1006 that are directed towards the communications interface 1008 can be separated from other signals via diplexer 1016.
  • the received signal can then be sent to low noise amplifier ("LNA") 1018 for amplification.
  • LNA low noise amplifier
  • a frequency mixer 1020, with help from local oscillator 1012 can downshift the received signal (which is in the millimeter-wave band or around 38 GHz in some embodiments) to the native frequency.
  • the communications interface 1008 can then receive the transmission at an input port (Rx).
  • transmitter/receiver device 1006 can include a cylindrical or non-cylindrical metal (which, for example, can be hollow in an embodiment, but not necessarily drawn to scale) or other conducting or non-conducting waveguide and an end of the stub coupler 1002 can be placed in or in proximity to the waveguide or the transmitter/receiver device 1006 such that when the transmitter/receiver device 1006 generates a transmission, the guided wave couples to stub coupler 1002 and propagates as a guided wave 1004 about the waveguide surface of the stub coupler 1002.
  • the guided wave 1004 can propagate in part on the outer surface of the stub coupler 1002 and in part inside the stub coupler 1002.
  • the guided wave 1004 can propagate substantially or completely on the outer surface of the stub coupler 1002. In yet other embodiments, the guided wave 1004 can propagate substantially or completely inside the stub coupler 1002. In this latter embodiment, the guided wave 1004 can radiate at an end of the stub coupler 1002 (such as the tapered end shown in FIG. 4) for coupling to a transmission medium such as a wire 702 of FIG. 7. Similarly, if guided wave 1004 is incoming (coupled to the stub coupler 1002 from a wire 702), guided wave 1004 then enters the transmitter / receiver device 1006 and couples to the cylindrical waveguide or conducting waveguide.
  • transmitter/receiver device 1006 is shown to include a separate waveguide — an antenna, cavity resonator, klystron, magnetron, travelling wave tube, or other radiating element can be employed to induce a guided wave on the coupler 1002, with or without the separate waveguide.
  • stub coupler 1002 can be wholly constructed of a dielectric material (or another suitable insulating material), without any metallic or otherwise conducting materials therein.
  • Stub coupler 1002 can be composed of nylon, Teflon, polyethylene, a polyamide, other plastics, or other materials that are non-conducting and suitable for facilitating transmission of electromagnetic waves at least in part on an outer surface of such materials.
  • stub coupler 1002 can include a core that is conducting/metallic, and have an exterior dielectric surface.
  • a transmission medium that couples to the stub coupler 1002 for propagating electromagnetic waves induced by the stub coupler 1002 or for supplying electromagnetic waves to the stub coupler 1002 can, in addition to being a bare or insulated wire, be wholly constructed of a dielectric material (or another suitable insulating material), without any metallic or otherwise conducting materials therein.
  • FIG. 10A shows that the opening of transmitter receiver device 1006 is much wider than the stub coupler 1002, this is not to scale, and that in other embodiments the width of the stub coupler 1002 is comparable or slightly smaller than the opening of the hollow waveguide. It is also not shown, but in an embodiment, an end of the coupler 1002 that is inserted into the transmitter/receiver device 1006 tapers down in order to reduce reflection and increase coupling efficiencies.
  • the one or more waveguide modes of the guided wave generated by the transmitter/receiver device 1006 can couple to the stub coupler 1002 to induce one or more wave propagation modes of the guided wave 1004.
  • the wave propagation modes of the guided wave 1004 can be different than the hollow metal waveguide modes due to the different characteristics of the hollow metal waveguide and the dielectric waveguide.
  • wave propagation modes of the guided wave 1004 can comprise the fundamental transverse electromagnetic mode (Quasi-TEMoo), where only small electrical and/or magnetic fields extend in the direction of propagation, and the electric and magnetic fields extend radially outwards from the stub coupler 1002 while the guided waves propagate along the stub coupler 1002.
  • the fundamental transverse electromagnetic mode wave propagation mode may or may not exist inside a waveguide that is hollow. Therefore, the hollow metal waveguide modes that are used by transmitter/receiver device 1006 are waveguide modes that can couple effectively and efficiently to wave propagation modes of stub coupler 1002.
  • a stub coupler 1002' can be placed tangentially or in parallel (with or without a gap) with respect to an outer surface of the hollow metal waveguide of the transmitter/receiver device 1006' (corresponding circuitry not shown) as depicted by reference 1000' of FIG. 10B.
  • the stub coupler 1002' can be placed inside the hollow metal waveguide of the transmitter/receiver device 1006' without an axis of the stub coupler 1002' being coaxially aligned with an axis of the hollow metal waveguide of the transmitter/receiver device 1006'.
  • the guided wave generated by the transmitter/receiver device 1006' can couple to a surface of the stub coupler 1002' to induce one or more wave propagation modes of the guided wave 1004' on the stub coupler 1002' including a fundamental mode (e.g., a symmetric mode) and/or a non-fundamental mode (e.g., asymmetric mode).
  • the guided wave 1004' can propagate in part on the outer surface of the stub coupler 1002' and in part inside the stub coupler 1002'. In another embodiment, the guided wave 1004' can propagate substantially or completely on the outer surface of the stub coupler 1002'. In yet other embodiments, the guided wave 1004' can propagate substantially or completely inside the stub coupler 1002' . In this latter embodiment, the guided wave 1004' can radiate at an end of the stub coupler 1002' (such as the tapered end shown in FIG. 9) for coupling to a transmission medium such as a wire 702 of FIG. 9.
  • a hollow metal waveguide of a transmitter/receiver device 1006 (corresponding circuitry not shown), depicted in FIG. 10B as reference 1000", can be placed tangentially or in parallel (with or without a gap) with respect to an outer surface of a transmission medium such as the wire 702 of FIG. 4 without the use of the stub coupler 1002.
  • the guided wave generated by the transmitter/receiver device 1006" can couple to a surface of the wire 702 to induce one or more wave propagation modes of a guided wave 908 on the wire 702 including a fundamental mode (e.g., a symmetric mode) and/or a non-fundamental mode (e.g., asymmetric mode).
  • the wire 702 can be positioned inside a hollow metal waveguide of a transmitter/receiver device 1006"' (corresponding circuitry not shown) so that an axis of the wire 702 is coaxially (or not coaxially) aligned with an axis of the hollow metal waveguide without the use of the stub coupler 1002— see FIGs.
  • the guided wave generated by the transmitter/receiver device 1006" ' can couple to a surface of the wire 702 to induce one or more wave propagation modes of a guided wave 908 on the wire including a fundamental mode (e.g., a symmetric mode) and/or a non-fundamental mode (e.g., asymmetric mode).
  • a fundamental mode e.g., a symmetric mode
  • a non-fundamental mode e.g., asymmetric mode
  • the guided wave 908 can propagate in part on the outer surface of the insulator and in part inside the insulator. In embodiments, the guided wave 908 can propagate substantially or completely on the outer surface of the insulator, or substantially or completely inside the insulator. In the embodiments of 1000" and 1000" ', for a wire 702 that is a bare conductor, the guided wave 908 can propagate in part on the outer surface of the conductor and in part inside the conductor. In another embodiment, the guided wave 908 can propagate substantially or completely on the outer surface of the conductor.
  • FIG. 11 a block diagram 1100 illustrating an example, non- limiting embodiment of a dual stub coupler is shown.
  • a dual coupler design is presented for use in a transmission device, such as transmission device 101 or 102 presented in conjunction with FIG. 1.
  • two or more couplers can be positioned around a wire 1102 in order to receive guided wave 1108.
  • one coupler is enough to receive the guided wave 1108.
  • guided wave 1108 couples to coupler 1104 and propagates as guided wave 1110.
  • coupler 1106 can be placed such that guided wave 1108 couples to coupler 1106.
  • four or more couplers can be placed around a portion of the wire 1102, e.g., at 90 degrees or another spacing with respect to each other, in order to receive guided waves that may oscillate or rotate around the wire 1102, that have been induced at different azimuthal orientations or that have non-fundamental or higher order modes that, for example, have lobes and/or nulls or other asymmetries that are orientation dependent.
  • couplers 1106 and 1104 are illustrated as stub couplers, any other of the coupler designs described herein including arc couplers, antenna or horn couplers, magnetic couplers, etc., could likewise be used. It will also be appreciated that while some example embodiments have presented a plurality of couplers around at least a portion of a wire 1102, this plurality of couplers can also be considered as part of a single coupler system having multiple coupler subcomponents.
  • two or more couplers can be manufactured as single system that can be installed around a wire in a single installation such that the couplers are either pre -positioned or adjustable relative to each other (either manually or automatically with a controllable mechanism such as a motor or other actuator) in accordance with the single system.
  • Receivers coupled to couplers 1106 and 1104 can use diversity combining to combine signals received from both couplers 1106 and 1104 in order to maximize the signal quality. In other embodiments, if one or the other of the couplers 1104 and 1106 receive a transmission that is above a predetermined threshold, receivers can use selection diversity when deciding which signal to use. Further, while reception by a plurality of couplers 1106 and 1104 is illustrated, transmission by couplers 1106 and 1104 in the same configuration can likewise take place. In particular, a wide range of multi-input multi- output (MIMO) transmission and reception techniques can be employed for transmissions where a transmission device, such as transmission device 101 or 102 presented in conjunction with FIG. 1 includes multiple transceivers and multiple couplers.
  • MIMO multi-input multi- output
  • wave 1108 and 1110 are presented merely to illustrate the principles that guided wave 1108 induces or otherwise launches a wave 1110 on a coupler 1104.
  • the actual electric and magnetic fields generated as a result of such wave propagation may vary depending on the frequencies employed, the design of the coupler 1104, the dimensions and composition of the wire 1102, as well as its surface characteristics, its insulation if any, the electromagnetic properties of the surrounding environment, etc.
  • FIG. 12 a block diagram 1200 illustrating an example, non- limiting embodiment of a repeater system is shown.
  • a repeater device 1210 is presented for use in a transmission device, such as transmission device 101 or 102 presented in conjunction with FIG. 1.
  • two couplers 1204 and 1214 can be placed near a wire 1202 or other transmission medium such that guided waves 1205 propagating along the wire 1202 are extracted by coupler 1204 as wave 1206 (e.g. as a guided wave), and then are boosted or repeated by repeater device 1210 and launched as a wave 1216 (e.g. as a guided wave) onto coupler 1214.
  • wave 1206 e.g. as a guided wave
  • the wave 1216 can then be launched on the wire 1202 and continue to propagate along the wire 1202 as a guided wave 1217.
  • the repeater device 1210 can receive at least a portion of the power utilized for boosting or repeating through magnetic coupling with the wire 1202, for example, when the wire 1202 is a power line or otherwise contains a power-carrying conductor.
  • couplers 1204 and 1214 are illustrated as stub couplers, any other of the coupler designs described herein including arc couplers, antenna or horn couplers, magnetic couplers, or the like, could likewise be used.
  • repeater device 1210 can repeat the transmission associated with wave 1206, and in other embodiments, repeater device 1210 can include a communications interface 205 that extracts data or other signals from the wave 1206 for supplying such data or signals to another network and/or one or more other devices as communication signals 110 or 112 and/or receiving communication signals 110 or 112 from another network and/or one or more other devices and launch guided wave 1216 having embedded therein the received communication signals 110 or 112.
  • receiver waveguide 1208 can receive the wave 1206 from the coupler 1204 and transmitter waveguide 1212 can launch guided wave 1216 onto coupler 1214 as guided wave 1217.
  • the signal embedded in guided wave 1206 and/or the guided wave 1216 itself can be amplified to correct for signal loss and other inefficiencies associated with guided wave communications or the signal can be received and processed to extract the data contained therein and regenerated for transmission.
  • the receiver waveguide 1208 can be configured to extract data from the signal, process the data to correct for data errors utilizing for example error correcting codes, and regenerate an updated signal with the corrected data.
  • the transmitter waveguide 1212 can then transmit guided wave 1216 with the updated signal embedded therein.
  • a signal embedded in guided wave 1206 can be extracted from the transmission and processed for communication with another network and/or one or more other devices via communications interface 205 as communication signals 110 or 112.
  • communication signals 110 or 112 received by the communications interface 205 can be inserted into a transmission of guided wave 1216 that is generated and launched onto coupler 1214 by transmitter waveguide 1212.
  • FIG. 12 shows guided wave transmissions 1206 and 1216 entering from the left and exiting to the right respectively, this is merely a simplification and is not intended to be limiting.
  • receiver waveguide 1208 and transmitter waveguide 1212 can also function as transmitters and receivers respectively, allowing the repeater device 1210 to be bi-directional.
  • repeater device 1210 can be placed at locations where there are discontinuities or obstacles on the wire 1202 or other transmission medium.
  • these obstacles can include transformers, connections, utility poles, and other such power line devices.
  • the repeater device 1210 can help the guided (e.g., surface) waves jump over these obstacles on the line and boost the transmission power at the same time.
  • a coupler can be used to jump over the obstacle without the use of a repeater device. In that embodiment, both ends of the coupler can be tied or fastened to the wire, thus providing a path for the guided wave to travel without being blocked by the obstacle.
  • FIG. 13 illustrated is a block diagram 1300 of an example, non-limiting embodiment of a bidirectional repeater in accordance with various aspects described herein.
  • a bidirectional repeater device 1306 is presented for use in a transmission device, such as transmission device 101 or 102 presented in conjunction with FIG. 1.
  • the couplers are illustrated as stub couplers, any other of the coupler designs described herein including arc couplers, antenna or horn couplers, magnetic couplers, or the like, could likewise be used.
  • the bidirectional repeater 1306 can employ diversity paths in the case of when two or more wires or other transmission media are present.
  • the various transmission media can be designated as a primary, secondary, tertiary, etc. whether or not such designation indicates a preference of one transmission medium over another.
  • the transmission media include an insulated or uninsulated wire 1302 and an insulated or uninsulated wire 1304 (referred to herein as wires 1302 and 1304, respectively).
  • the repeater device 1306 uses a receiver coupler 1308 to receive a guided wave traveling along wire 1302 and repeats the transmission using transmitter waveguide 1310 as a guided wave along wire 1304.
  • repeater device 1306 can switch from the wire 1304 to the wire 1302, or can repeat the transmissions along the same paths.
  • Repeater device 1306 can include sensors, or be in communication with sensors (or a network management system 1601 depicted in FIG. 16A) that indicate conditions that can affect the transmission. Based on the feedback received from the sensors, the repeater device 1306 can make the determination about whether to keep the transmission along the same wire, or transfer the transmission to the other wire.
  • FIG. 14 illustrated is a block diagram 1400 illustrating an example, non-limiting embodiment of a bidirectional repeater system.
  • a bidirectional repeater system is presented for use in a transmission device, such as transmission device 101 or 102 presented in conjunction with FIG. 1.
  • the bidirectional repeater system includes waveguide coupling devices 1402 and 1404 that receive and transmit transmissions from other coupling devices located in a distributed antenna system or backhaul system.
  • waveguide coupling device 1402 can receive a transmission from another waveguide coupling device, wherein the transmission has a plurality of subcarriers.
  • Diplexer 1406 can separate the transmission from other transmissions, and direct the transmission to low-noise amplifier ("LNA") 1408.
  • LNA low-noise amplifier
  • a frequency mixer 1428 with help from a local oscillator 1412, can downshift the transmission (which is in the millimeter-wave band or around 38 GHz in some embodiments) to a lower frequency, such as a cellular band (-1.9 GHz) for a distributed antenna system, a native frequency, or other frequency for a backhaul system.
  • An extractor (or demultiplexer) 1432 can extract the signal on a subcarrier and direct the signal to an output component 1422 for optional amplification, buffering or isolation by power amplifier 1424 for coupling to communications interface 205.
  • the communications interface 205 can further process the signals received from the power amplifier 1424 or otherwise transmit such signals over a wireless or wired interface to other devices such as a base station, mobile devices, a building, etc.
  • extractor 1432 can redirect them to another frequency mixer 1436, where the signals are used to modulate a carrier wave generated by local oscillator 1414.
  • the carrier wave, with its subcarriers, is directed to a power amplifier (“PA”) 1416 and is retransmitted by waveguide coupling device 1404 to another system, via diplexer 1420.
  • PA power amplifier
  • An LNA 1426 can be used to amplify, buffer or isolate signals that are received by the communication interface 205 and then send the signal to a multiplexer 1434 which merges the signal with signals that have been received from waveguide coupling device 1404.
  • the signals received from coupling device 1404 have been split by diplexer 1420, and then passed through LNA 1418, and downshifted in frequency by frequency mixer 1438.
  • bidirectional repeater system can be merely a repeater without the output device 1422.
  • the multiplexer 1434 would not be utilized and signals from LNA 1418 would be directed to mixer 1430 as previously described.
  • the bidirectional repeater system could also be implemented using two distinct and separate unidirectional repeaters.
  • a bidirectional repeater system could also be a booster or otherwise perform retransmissions without downshifting and upshifting.
  • the retransmissions can be based upon receiving a signal or guided wave and performing some signal or guided wave processing or reshaping, filtering, and/or amplification, prior to retransmission of the signal or guided wave.
  • FIG. 15 a block diagram 1500 illustrating an example, non- limiting embodiment of a guided wave communications system is shown.
  • This diagram depicts an exemplary environment in which a guided wave communication system, such as the guided wave communication system presented in conjunction with FIG. 1, can be used.
  • a backhaul network that links the communication cells (e.g., microcells and macrocells) to network devices of a core network correspondingly expands.
  • an extended communication system that links base station devices and their distributed antennas is desirable.
  • a guided wave communication system 1500 such as shown in FIG.
  • a waveguide coupling system can be provided to transmit and/or receive guided wave (e.g., surface wave) communications on a transmission medium such as a wire that operates as a single-wire transmission line (e.g., a utility line), and that can be used as a waveguide and/or that otherwise operates to guide the transmission of an electromagnetic wave.
  • guided wave e.g., surface wave
  • the guided wave communication system 1500 can comprise a first instance of a distribution system 1550 that includes one or more base station devices (e.g., base station device 1504) that are communicably coupled to a central office 1501 and/or a macrocell site 1502.
  • Base station device 1504 can be connected by a wired (e.g., fiber and/or cable), or by a wireless (e.g., microwave wireless) connection to the macrocell site 1502 and the central office 1501.
  • a second instance of the distribution system 1560 can be used to provide wireless voice and data services to mobile device 1522 and to residential and/or commercial establishments 1542 (herein referred to as establishments 1542).
  • System 1500 can have additional instances of the distribution systems 1550 and 1560 for providing voice and/or data services to mobile devices 1522-1524 and establishments 1542 as shown in FIG. 15.
  • Macrocells such as macrocell site 1502 can have dedicated connections to a mobile network and base station device 1504 or can share and/or otherwise use another connection.
  • Central office 1501 can be used to distribute media content and/or provide internet service provider (ISP) services to mobile devices 1522-1524 and establishments 1542.
  • the central office 1501 can receive media content from a constellation of satellites 1530 (one of which is shown in FIG. 15) or other sources of content, and distribute such content to mobile devices 1522-1524 and establishments 1542 via the first and second instances of the distribution system 1550 and 1560.
  • the central office 1501 can also be communicatively coupled to the Internet 1503 for providing internet data services to mobile devices 1522-1524 and establishments 1542.
  • Base station device 1504 can be mounted on, or attached to, utility pole 1516. In other embodiments, base station device 1504 can be near transformers and/or other locations situated nearby a power line. Base station device 1504 can facilitate connectivity to a mobile network for mobile devices 1522 and 1524. Antennas 1512 and 1514, mounted on or near utility poles 1518 and 1520, respectively, can receive signals from base station device 1504 and transmit those signals to mobile devices 1522 and 1524 over a much wider area than if the antennas 1512 and 1514 were located at or near base station device 1504.
  • FIG. 15 displays three utility poles, in each instance of the distribution systems 1550 and 1560, with one base station device, for purposes of simplicity.
  • utility pole 1516 can have more base station devices, and more utility poles with distributed antennas and/or tethered connections to establishments 1542.
  • a transmission device 1506 such as transmission device 101 or 102 presented in conjunction with FIG. 1, can transmit a signal from base station device 1504 to antennas 1512 and 1514 via utility or power line(s) that connect the utility poles 1516, 1518, and 1520.
  • radio source and/or transmission device 1506 upconverts the signal (e.g., via frequency mixing) from base station device 1504 or otherwise converts the signal from the base station device 1504 to a microwave band signal and the transmission device 1506 launches a microwave band wave that propagates as a guided wave traveling along the utility line or other wire as described in previous embodiments.
  • another transmission device 1508 receives the guided wave (and optionally can amplify it as needed or desired or operate as a repeater to receive it and regenerate it) and sends it forward as a guided wave on the utility line or other wire.
  • the transmission device 1508 can also extract a signal from the microwave band guided wave and shift it down in frequency or otherwise convert it to its original cellular band frequency (e.g., 1.9 GHz or other defined cellular frequency) or another cellular (or non-cellular) band frequency.
  • An antenna 1512 can wireless transmit the downshifted signal to mobile device 1522. The process can be repeated by transmission device 1510, antenna 1514 and mobile device 1524, as necessary or desirable.
  • Transmissions from mobile devices 1522 and 1524 can also be received by antennas 1512 and 1514 respectively.
  • the transmission devices 1508 and 1510 can upshift or otherwise convert the cellular band signals to microwave band and transmit the signals as guided wave (e.g., surface wave or other electromagnetic wave) transmissions over the power line(s) to base station device 1504.
  • guided wave e.g., surface wave or other electromagnetic wave
  • Media content received by the central office 1501 can be supplied to the second instance of the distribution system 1560 via the base station device 1504 for distribution to mobile devices 1522 and establishments 1542.
  • the transmission device 1510 can be tethered to the establishments 1542 by one or more wired connections or a wireless interface.
  • the one or more wired connections may include without limitation, a power line, a coaxial cable, a fiber cable, a twisted pair cable, a guided wave transmission medium or other suitable wired mediums for distribution of media content and/or for providing internet services.
  • the wired connections from the transmission device 1510 can be communicatively coupled to one or more very high bit rate digital subscriber line (VDSL) modems located at one or more corresponding service area interfaces (SAIs - not shown) or pedestals, each SAI or pedestal providing services to a portion of the establishments 1542.
  • VDSL modems can be used to selectively distribute media content and/or provide internet services to gateways (not shown) located in the establishments 1542.
  • the SAIs or pedestals can also be communicatively coupled to the establishments 1542 over a wired medium such as a power line, a coaxial cable, a fiber cable, a twisted pair cable, a guided wave transmission medium or other suitable wired mediums.
  • the transmission device 1510 can be communicatively coupled directly to establishments 1542 without intermediate interfaces such as the SAIs or pedestals.
  • system 1500 can employ diversity paths, where two or more utility lines or other wires are strung between the utility poles 1516, 1518, and 1520 (e.g., for example, two or more wires between poles 1516 and 1520) and redundant transmissions from base station/macrocell site 1502 are transmitted as guided waves down the surface of the utility lines or other wires.
  • the utility lines or other wires can be either insulated or uninsulated, and depending on the environmental conditions that cause transmission losses, the coupling devices can selectively receive signals from the insulated or uninsulated utility lines or other wires.
  • the selection can be based on measurements of the signal-to-noise ratio of the wires, or based on determined weather/environmental conditions (e.g., moisture detectors, weather forecasts, etc.).
  • the use of diversity paths with system 1500 can enable alternate routing capabilities, load balancing, increased load handling, concurrent bi-directional or synchronous communications, spread spectrum communications, etc.
  • transmission devices 1506, 1508, and 1510 in FIG. 15 are by way of example only, and that in other embodiments, other uses are possible.
  • transmission devices can be used in a backhaul communication system, providing network connectivity to base station devices.
  • Transmission devices 1506, 1508, and 1510 can be used in many circumstances where it is desirable to transmit guided wave communications over a wire, whether insulated or not insulated.
  • Transmission devices 1506, 1508, and 1510 are improvements over other coupling devices due to no contact or limited physical and/or electrical contact with the wires that may carry high voltages.
  • the transmission device can be located away from the wire (e.g., spaced apart from the wire) and/or located on the wire so long as it is not electrically in contact with the wire, as the dielectric acts as an insulator, allowing for cheap, easy, and/or less complex installation.
  • conducting or non-dielectric couplers can be employed, for example in configurations where the wires correspond to a telephone network, cable television network, broadband data service, fiber optic communications system or other network employing low voltages or having insulated transmission lines.
  • base station device 1504 and macrocell site 1502 are illustrated in an embodiment, other network configurations are likewise possible.
  • devices such as access points or other wireless gateways can be employed in a similar fashion to extend the reach of other networks such as a wireless local area network, a wireless personal area network or other wireless network that operates in accordance with a communication protocol such as a 802.11 protocol, WIMAX protocol, UltraWideband protocol, Bluetooth protocol, Zigbee protocol or other wireless protocol.
  • FIGs. 16A & 16B block diagrams illustrating an example, non-limiting embodiment of a system for managing a power grid communication system are shown.
  • a waveguide system 1602 is presented for use in a guided wave communications system, such as the system presented in conjunction with FIG. 15.
  • the waveguide system 1602 can comprise sensors 1604, a power management system 1605, a transmission device 101 or 102 that includes at least one communication interface 205, transceiver 210 and coupler 220.
  • the waveguide system 1602 can be coupled to a power line 1610 for facilitating guided wave communications in accordance with embodiments described in the subject disclosure.
  • the transmission device 101 or 102 includes coupler 220 for inducing electromagnetic waves on a surface of the power line 1610 that longitudinally propagate along the surface of the power line 1610 as described in the subject disclosure.
  • the transmission device 101 or 102 can also serve as a repeater for retransmitting electromagnetic waves on the same power line 1610 or for routing electromagnetic waves between power lines 1610 as shown in FIGs. 12-13.
  • the transmission device 101 or 102 includes transceiver 210 configured to, for example, up-convert a signal operating at an original frequency range to electromagnetic waves operating at, exhibiting, or associated with a carrier frequency that propagate along a coupler to induce corresponding guided electromagnetic waves that propagate along a surface of the power line 1610.
  • a carrier frequency can be represented by a center frequency having upper and lower cutoff frequencies that define the bandwidth of the electromagnetic waves.
  • the power line 1610 can be a wire (e.g., single stranded or multi- stranded) having a conducting surface or insulated surface.
  • the transceiver 210 can also receive signals from the coupler 220 and down-convert the electromagnetic waves operating at a carrier frequency to signals at their original frequency.
  • Signals received by the communications interface 205 of transmission device 101 or 102 for up-conversion can include without limitation signals supplied by a central office 1611 over a wired or wireless interface of the communications interface 205, a base station 1614 over a wired or wireless interface of the communications interface 205, wireless signals transmitted by mobile devices 1620 to the base station 1614 for delivery over the wired or wireless interface of the communications interface 205, signals supplied by in-building communication devices 1618 over the wired or wireless interface of the communications interface 205, and/or wireless signals supplied to the communications interface 205 by mobile devices 1612 roaming in a wireless communication range of the communications interface 205.
  • the communications interface 205 may or may not be included in the waveguide system 1602.
  • the electromagnetic waves propagating along the surface of the power line 1610 can be modulated and formatted to include packets or frames of data that include a data payload and further include networking information (such as header information for identifying one or more destination waveguide systems 1602).
  • the networking information may be provided by the waveguide system 1602 or an originating device such as the central office 1611, the base station 1614, mobile devices 1620, or in-building devices 1618, or a combination thereof.
  • the modulated electromagnetic waves can include error correction data for mitigating signal disturbances.
  • the networking information and error correction data can be used by a destination waveguide system 1602 for detecting transmissions directed to it, and for down-converting and processing with error correction data transmissions that include voice and/or data signals directed to recipient communication devices communicatively coupled to the destination waveguide system 1602.
  • the sensors 1604 can comprise one or more of a temperature sensor 1604a, a disturbance detection sensor 1604b, a loss of energy sensor 1604c, a noise sensor 1604d, a vibration sensor 1604e, an environmental (e.g., weather) sensor 1604f, and/or an image sensor 1604g.
  • the temperature sensor 1604a can be used to measure ambient temperature, a temperature of the transmission device 101 or 102, a temperature of the power line 1610, temperature differentials (e.g., compared to a setpoint or baseline, between transmission device 101 or 102 and 1610, etc.), or any combination thereof.
  • temperature metrics can be collected and reported periodically to a network management system 1601 by way of the base station 1614.
  • the disturbance detection sensor 1604b can perform measurements on the power line 1610 to detect disturbances such as signal reflections, which may indicate a presence of a downstream disturbance that may impede the propagation of electromagnetic waves on the power line 1610.
  • a signal reflection can represent a distortion resulting from, for example, an electromagnetic wave transmitted on the power line 1610 by the transmission device 101 or 102 that reflects in whole or in part back to the transmission device 101 or 102 from a disturbance in the power line 1610 located downstream from the transmission device 101 or 102.
  • Signal reflections can be caused by obstructions on the power line 1610.
  • a tree limb may cause electromagnetic wave reflections when the tree limb is lying on the power line 1610, or is in close proximity to the power line 1610 which may cause a corona discharge.
  • Other obstructions that can cause electromagnetic wave reflections can include without limitation an object that has been entangled on the power line 1610 (e.g., clothing, a shoe wrapped around a power line 1610 with a shoe string, etc.), a corroded build-up on the power line 1610 or an ice build-up.
  • Power grid components may also impede or obstruct with the propagation of electromagnetic waves on the surface of power lines 1610. Illustrations of power grid components that may cause signal reflections include without limitation a transformer and a joint for connecting spliced power lines. A sharp angle on the power line 1610 may also cause electromagnetic wave reflections.
  • the disturbance detection sensor 1604b can comprise a circuit to compare magnitudes of electromagnetic wave reflections to magnitudes of original electromagnetic waves transmitted by the transmission device 101 or 102 to determine how much a downstream disturbance in the power line 1610 attenuates transmissions.
  • the disturbance detection sensor 1604b can further comprise a spectral analyzer circuit for performing spectral analysis on the reflected waves.
  • the spectral data generated by the spectral analyzer circuit can be compared with spectral profiles via pattern recognition, an expert system, curve fitting, matched filtering or other artificial intelligence, classification or comparison technique to identify a type of disturbance based on, for example, the spectral profile that most closely matches the spectral data.
  • the spectral profiles can be stored in a memory of the disturbance detection sensor 1604b or may be remotely accessible by the disturbance detection sensor 1604b.
  • the profiles can comprise spectral data that models different disturbances that may be encountered on power lines 1610 to enable the disturbance detection sensor 1604b to identify disturbances locally.
  • An identification of the disturbance if known can be reported to the network management system 1601 by way of the base station 1614.
  • the disturbance detection sensor 1604b can also utilize the transmission device 101 or 102 to transmit electromagnetic waves as test signals to determine a roundtrip time for an electromagnetic wave reflection.
  • the round trip time measured by the disturbance detection sensor 1604b can be used to calculate a distance traveled by the electromagnetic wave up to a point where the reflection takes place, which enables the disturbance detection sensor 1604b to calculate a distance from the transmission device 101 or 102 to the downstream disturbance on the power line 1610.
  • the distance calculated can be reported to the network management system 1601 by way of the base station 1614.
  • the location of the waveguide system 1602 on the power line 1610 may be known to the network management system 1601, which the network management system 1601 can use to determine a location of the disturbance on the power line 1610 based on a known topology of the power grid.
  • the waveguide system 1602 can provide its location to the network management system 1601 to assist in the determination of the location of the disturbance on the power line 1610.
  • the location of the waveguide system 1602 can be obtained by the waveguide system 1602 from a pre-programmed location of the waveguide system 1602 stored in a memory of the waveguide system 1602, or the waveguide system 1602 can determine its location using a GPS receiver (not shown) included in the waveguide system 1602.
  • the power management system 1605 provides energy to the aforementioned components of the waveguide system 1602.
  • the power management system 1605 can receive energy from solar cells, or from a transformer (not shown) coupled to the power line 1610, or by inductive coupling to the power line 1610 or another nearby power line.
  • the power management system 1605 can also include a backup battery and/or a super capacitor or other capacitor circuit for providing the waveguide system 1602 with temporary power.
  • the loss of energy sensor 1604c can be used to detect when the waveguide system 1602 has a loss of power condition and/or the occurrence of some other malfunction.
  • the loss of energy sensor 1604c can detect when there is a loss of power due to defective solar cells, an obstruction on the solar cells that causes them to malfunction, loss of power on the power line 1610, and/or when the backup power system malfunctions due to expiration of a backup battery, or a detectable defect in a super capacitor. When a malfunction and/or loss of power occurs, the loss of energy sensor 1604c can notify the network management system 1601 by way of the base station 1614.
  • the noise sensor 1604d can be used to measure noise on the power line 1610 that may adversely affect transmission of electromagnetic waves on the power line 1610.
  • the noise sensor 1604d can sense unexpected electromagnetic interference, noise bursts, or other sources of disturbances that may interrupt reception of modulated electromagnetic waves on a surface of a power line 1610.
  • a noise burst can be caused by, for example, a corona discharge, or other source of noise.
  • the noise sensor 1604d can compare the measured noise to a noise profile obtained by the waveguide system 1602 from an internal database of noise profiles or from a remotely located database that stores noise profiles via pattern recognition, an expert system, curve fitting, matched filtering or other artificial intelligence, classification or comparison technique.
  • the noise sensor 1604d may identify a noise source (e.g., corona discharge or otherwise) based on, for example, the noise profile that provides the closest match to the measured noise.
  • the noise sensor 1604d can also detect how noise affects transmissions by measuring transmission metrics such as bit error rate, packet loss rate, jitter, packet retransmission requests, etc.
  • the noise sensor 1604d can report to the network management system 1601 by way of the base station 1614 the identity of noise sources, their time of occurrence, and transmission metrics, among other things.
  • the vibration sensor 1604e can include accelerometers and/or gyroscopes to detect 2D or 3D vibrations on the power line 1610.
  • the vibrations can be compared to vibration profiles that can be stored locally in the waveguide system 1602, or obtained by the waveguide system 1602 from a remote database via pattern recognition, an expert system, curve fitting, matched filtering or other artificial intelligence, classification or comparison technique.
  • Vibration profiles can be used, for example, to distinguish fallen trees from wind gusts based on, for example, the vibration profile that provides the closest match to the measured vibrations.
  • the results of this analysis can be reported by the vibration sensor 1604e to the network management system 1601 by way of the base station 1614.
  • the environmental sensor 1604f can include a barometer for measuring atmospheric pressure, ambient temperature (which can be provided by the temperature sensor 1604a), wind speed, humidity, wind direction, and rainfall, among other things.
  • the environmental sensor 1604f can collect raw information and process this information by comparing it to environmental profiles that can be obtained from a memory of the waveguide system 1602 or a remote database to predict weather conditions before they arise via pattern recognition, an expert system, knowledge-based system or other artificial intelligence, classification or other weather modeling and prediction technique.
  • the environmental sensor 1604f can report raw data as well as its analysis to the network management system 1601.
  • the image sensor 1604g can be a digital camera (e.g., a charged coupled device or CCD imager, infrared camera, etc.) for capturing images in a vicinity of the waveguide system 1602.
  • the image sensor 1604g can include an electromechanical mechanism to control movement (e.g., actual position or focal points/zooms) of the camera for inspecting the power line 1610 from multiple perspectives (e.g., top surface, bottom surface, left surface, right surface and so on).
  • the image sensor 1604g can be designed such that no electromechanical mechanism is needed in order to obtain the multiple perspectives.
  • the collection and retrieval of imaging data generated by the image sensor 1604g can be controlled by the network management system 1601, or can be autonomously collected and reported by the image sensor 1604g to the network management system 1601.
  • Other sensors that may be suitable for collecting telemetry information associated with the waveguide system 1602 and/or the power lines 1610 for purposes of detecting, predicting and/or mitigating disturbances that can impede the propagation of electromagnetic wave transmissions on power lines 1610 (or any other form of a transmission medium of electromagnetic waves) may be utilized by the waveguide system 1602.
  • block diagram 1650 illustrates an example, non- limiting embodiment of a system for managing a power grid 1653 and a communication system 1655 embedded therein or associated therewith in accordance with various aspects described herein.
  • the communication system 1655 comprises a plurality of waveguide systems 1602 coupled to power lines 1610 of the power grid 1653. At least a portion of the waveguide systems 1602 used in the communication system 1655 can be in direct communication with a base station 1614 and/or the network management system 1601.
  • Waveguide systems 1602 not directly connected to a base station 1614 or the network management system 1601 can engage in communication sessions with either a base station 1614 or the network management system 1601 by way of other downstream waveguide systems 1602 connected to a base station 1614 or the network management system 1601.
  • the network management system 1601 can be communicatively coupled to equipment of a utility company 1652 and equipment of a communications service provider 1654 for providing each entity, status information associated with the power grid 1653 and the communication system 1655, respectively.
  • the network management system 1601, the equipment of the utility company 1652, and the communications service provider 1654 can access communication devices utilized by utility company personnel 1656 and/or communication devices utilized by communications service provider personnel 1658 for purposes of providing status information and/or for directing such personnel in the management of the power grid 1653 and/or communication system 1655.
  • FIG. 17 A illustrates a flow diagram of an example, non-limiting embodiment of a method 1700 for detecting and mitigating disturbances occurring in a communication network of the systems of FIGs. 16A & 16B.
  • Method 1700 can begin with step 1702 where a waveguide system 1602 transmits and receives messages embedded in, or forming part of, modulated electromagnetic waves or another type of electromagnetic waves traveling along a surface of a power line 1610.
  • the messages can be voice messages, streaming video, and/or other data/information exchanged between communication devices communicatively coupled to the communication system 1655.
  • the sensors 1604 of the waveguide system 1602 can collect sensing data.
  • the sensing data can be collected in step 1704 prior to, during, or after the transmission and/or receipt of messages in step 1702.
  • the waveguide system 1602 (or the sensors 1604 themselves) can determine from the sensing data an actual or predicted occurrence of a disturbance in the communication system 1655 that can affect communications originating from (e.g., transmitted by) or received by the waveguide system 1602.
  • the waveguide system 1602 (or the sensors 1604) can process temperature data, signal reflection data, loss of energy data, noise data, vibration data, environmental data, or any combination thereof to make this determination.
  • the waveguide system 1602 (or the sensors 1604) may also detect, identify, estimate, or predict the source of the disturbance and/or its location in the communication system 1655.
  • the waveguide system 1602 can proceed to step 1702 where it continues to transmit and receive messages embedded in, or forming part of, modulated electromagnetic waves traveling along a surface of the power line 1610.
  • a duration threshold and a frequency of occurrence threshold can be used at step 1710 to determine when a disturbance adversely affects communications in the communication system 1655.
  • a duration threshold is set to 500 ms
  • a frequency of occurrence threshold is set to 5 disturbances occurring in an observation period of 10 sec.
  • a disturbance having a duration greater than 500ms will trigger the duration threshold.
  • any disturbance occurring more than 5 times in a 10 sec time interval will trigger the frequency of occurrence threshold.
  • a disturbance may be considered to adversely affect signal integrity in the communication systems 1655 when the duration threshold alone is exceeded.
  • a disturbance may be considered as adversely affecting signal integrity in the communication systems 1655 when both the duration threshold and the frequency of occurrence threshold are exceeded.
  • the latter embodiment is thus more conservative than the former embodiment for classifying disturbances that adversely affect signal integrity in the communication system 1655. It will be appreciated that many other algorithms and associated parameters and thresholds can be utilized for step 1710 in accordance with example embodiments.
  • the waveguide system 1602 may proceed to step 1702 and continue processing messages. For instance, if the disturbance detected in step 1708 has a duration of 1 msec with a single occurrence in a 10 sec time period, then neither threshold will be exceeded. Consequently, such a disturbance may be considered as having a nominal effect on signal integrity in the communication system 1655 and thus would not be flagged as a disturbance requiring mitigation. Although not flagged, the occurrence of the disturbance, its time of occurrence, its frequency of occurrence, spectral data, and/or other useful information, may be reported to the network management system 1601 as telemetry data for monitoring purposes.
  • the waveguide system 1602 can proceed to step 1712 and report the incident to the network management system 1601.
  • the report can include raw sensing data collected by the sensors 1604, a description of the disturbance if known by the waveguide system 1602, a time of occurrence of the disturbance, a frequency of occurrence of the disturbance, a location associated with the disturbance, parameters readings such as bit error rate, packet loss rate, retransmission requests, jitter, latency and so on.
  • the report can include a type of disturbance expected, and if predictable, an expected time occurrence of the disturbance, and an expected frequency of occurrence of the predicted disturbance when the prediction is based on historical sensing data collected by the sensors 1604 of the waveguide system 1602.
  • the network management system 1601 can determine a mitigation, circumvention, or correction technique, which may include directing the waveguide system 1602 to reroute traffic to circumvent the disturbance if the location of the disturbance can be determined.
  • the waveguide coupling device 1402 detecting the disturbance may direct a repeater such as the one shown in FIGs. 13-14 to connect the waveguide system 1602 from a primary power line affected by the disturbance to a secondary power line to enable the waveguide system 1602 to reroute traffic to a different transmission medium and avoid the disturbance.
  • the waveguide system 1602 is configured as a repeater the waveguide system 1602 can itself perform the rerouting of traffic from the primary power line to the secondary power line.
  • the repeater can be configured to reroute traffic from the secondary power line back to the primary power line for processing by the waveguide system 1602.
  • the waveguide system 1602 can redirect traffic by instructing a first repeater situated upstream of the disturbance and a second repeater situated downstream of the disturbance to redirect traffic from a primary power line temporarily to a secondary power line and back to the primary power line in a manner that avoids the disturbance. It is further noted that for bidirectional communications (e.g., full or half-duplex communications), repeaters can be configured to reroute traffic from the secondary power line back to the primary power line.
  • bidirectional communications e.g., full or half-duplex communications
  • the network management system 1601 may direct the waveguide system 1602 to instruct repeater(s) to utilize unused time slot(s) and/or frequency band(s) of the secondary power line for redirecting data and/or voice traffic away from the primary power line to circumvent the disturbance.
  • the network management system 1601 can notify equipment of the utility company 1652 and/or equipment of the communications service provider 1654, which in turn may notify personnel of the utility company 1656 and/or personnel of the communications service provider 1658 of the detected disturbance and its location if known. Field personnel from either party can attend to resolving the disturbance at a determined location of the disturbance.
  • the disturbance can be removed or otherwise mitigated by personnel of the utility company and/or personnel of the communications service provider, such personnel can notify their respective companies and/or the network management system 1601 utilizing field equipment (e.g., a laptop computer, smartphone, etc.) communicatively coupled to network management system 1601, and/or equipment of the utility company and/or the communications service provider.
  • the notification can include a description of how the disturbance was mitigated and any changes to the power lines 1610 that may change a topology of the communication system 1655.
  • the network management system 1601 can direct the waveguide system 1602 at step 1720 to restore the previous routing configuration used by the waveguide system 1602 or route traffic according to a new routing configuration if the restoration strategy used to mitigate the disturbance resulted in a new network topology of the communication system 1655.
  • the waveguide system 1602 can be configured to monitor mitigation of the disturbance by transmitting test signals on the power line 1610 to determine when the disturbance has been removed.
  • the waveguide system 1602 can autonomously restore its routing configuration without assistance by the network management system 1601 if it determines the network topology of the communication system 1655 has not changed, or it can utilize a new routing configuration that adapts to a detected new network topology.
  • FIG. 17B illustrates a flow diagram of an example, non-limiting embodiment of a method 1750 for detecting and mitigating disturbances occurring in a communication network of the system of FIGs. 16A and 16B.
  • method 1750 can begin with step 1752 where a network management system 1601 receives from equipment of the utility company 1652 or equipment of the communications service provider 1654 maintenance information associated with a maintenance schedule.
  • the network management system 1601 can at step 1754 identify from the maintenance information, maintenance activities to be performed during the maintenance schedule.
  • the network management system 1601 can detect a disturbance resulting from the maintenance (e.g., scheduled replacement of a power line 1610, scheduled replacement of a waveguide system 1602 on the power line 1610, scheduled reconfiguration of power lines 1610 in the power grid 1653, etc.).
  • a disturbance resulting from the maintenance e.g., scheduled replacement of a power line 1610, scheduled replacement of a waveguide system 1602 on the power line 1610, scheduled reconfiguration of power lines 1610 in the power grid 1653, etc.
  • the network management system 1601 can receive at step 1755 telemetry information from one or more waveguide systems 1602.
  • the telemetry information can include among other things an identity of each waveguide system 1602 submitting the telemetry information, measurements taken by sensors 1604 of each waveguide system 1602, information relating to predicted, estimated, or actual disturbances detected by the sensors 1604 of each waveguide system 1602, location information associated with each waveguide system 1602, an estimated location of a detected disturbance, an identification of the disturbance, and so on.
  • the network management system 1601 can determine from the telemetry information a type of disturbance that may be adverse to operations of the waveguide, transmission of the electromagnetic waves along the wire surface, or both.
  • the network management system 1601 can also use telemetry information from multiple waveguide systems 1602 to isolate and identify the disturbance. Additionally, the network management system 1601 can request telemetry information from waveguide systems 1602 in a vicinity of an affected waveguide system 1602 to triangulate a location of the disturbance and/or validate an identification of the disturbance by receiving similar telemetry information from other waveguide systems 1602.
  • the network management system 1601 can receive at step 1756 an unscheduled activity report from maintenance field personnel.
  • Unscheduled maintenance may occur as result of field calls that are unplanned or as a result of unexpected field issues discovered during field calls or scheduled maintenance activities.
  • the activity report can identify changes to a topology configuration of the power grid 1653 resulting from field personnel addressing discovered issues in the communication system 1655 and/or power grid 1653, changes to one or more waveguide systems 1602 (such as replacement or repair thereof), mitigation of disturbances performed if any, and so on.
  • the network management system 1601 can determine from reports received according to steps 1752 through 1756 if a disturbance will occur based on a maintenance schedule, or if a disturbance has occurred or is predicted to occur based on telemetry data, or if a disturbance has occurred due to an unplanned maintenance identified in a field activity report. From any of these reports, the network management system 1601 can determine whether a detected or predicted disturbance requires rerouting of traffic by the affected waveguide systems 1602 or other waveguide systems 1602 of the communication system 1655.
  • the network management system 1601 can proceed to step 1760 where it can direct one or more waveguide systems 1602 to reroute traffic to circumvent the disturbance.
  • the network management system 1601 can proceed to step 1770 and skip steps 1762, 1764, 1766, and 1772.
  • the network management system 1601 can direct one or more waveguide systems 1602 to use a new routing configuration that adapts to the new topology.
  • the network management system 1601 can notify maintenance personnel of the utility company 1656 or the communications service provider 1658 of a location of the disturbance, a type of disturbance if known, and related information that may be helpful to such personnel to mitigate the disturbance.
  • the network management system 1601 can direct one or more waveguide systems 1602 to reconfigure traffic routes at a given schedule (consistent with the maintenance schedule) to avoid disturbances caused by the maintenance activities during the maintenance schedule.
  • the network management system 1601 can monitor when the disturbance(s) have been mitigated by field personnel. Mitigation of a disturbance can be detected at step 1762 by analyzing field reports submitted to the network management system 1601 by field personnel over a communications network (e.g., cellular communication system) utilizing field equipment (e.g., a laptop computer or handheld computer/device). If field personnel have reported that a disturbance has been mitigated, the network management system 1601 can proceed to step 1764 to determine from the field report whether a topology change was required to mitigate the disturbance.
  • a communications network e.g., cellular communication system
  • field equipment e.g., a laptop computer or handheld computer/device
  • a topology change can include rerouting a power line 1610, reconfiguring a waveguide system 1602 to utilize a different power line 1610, otherwise utilizing an alternative link to bypass the disturbance and so on. If a topology change has taken place, the network management system 1601 can direct at step 1770 one or more waveguide systems 1602 to use a new routing configuration that adapts to the new topology.
  • the network management system 1601 can proceed to step 1766 where it can direct one or more waveguide systems 1602 to send test signals to test a routing configuration that had been used prior to the detected disturbance(s).
  • Test signals can be sent to affected waveguide systems 1602 in a vicinity of the disturbance.
  • the test signals can be used to determine if signal disturbances (e.g., electromagnetic wave reflections) are detected by any of the waveguide systems 1602. If the test signals confirm that a prior routing configuration is no longer subject to previously detected disturbance(s), then the network management system 1601 can at step 1772 direct the affected waveguide systems 1602 to restore a previous routing configuration.
  • test signals analyzed by one or more waveguide coupling device 1402 and reported to the network management system 1601 indicate that the disturbance(s) or new disturbance(s) are present, then the network management system 1601 will proceed to step 1768 and report this information to field personnel to further address field issues. The network management system 1601 can in this situation continue to monitor mitigation of the disturbance(s) at step 1762.
  • the waveguide systems 1602 can be configured to be self-adapting to changes in the power grid 1653 and/or to mitigation of disturbances. That is, one or more affected waveguide systems 1602 can be configured to self-monitor mitigation of disturbances and reconfigure traffic routes without requiring instructions to be sent to them by the network management system 1601.
  • the one or more waveguide systems 1602 that are self-configurable can inform the network management system 1601 of its routing choices so that the network management system 1601 can maintain a macro-level view of the communication topology of the communication system 1655.
  • the transmission medium 1800 can comprise a first dielectric material 1802 and a second dielectric material 1804 disposed thereon.
  • the first dielectric material 1802 can comprise a dielectric core (referred to herein as dielectric core 1802) and the second dielectric material 1804 can comprise a cladding or shell such as a dielectric foam that surrounds in whole or in part the dielectric core (referred to herein as dielectric foam 1804).
  • the dielectric core 1802 and dielectric foam 1804 can be coaxially aligned to each other (although not necessary).
  • the combination of the dielectric core 1802 and the dielectric foam 1804 can be flexed or bent at least by 45 degrees without damaging the materials of the dielectric core 1802 and the dielectric foam 1804.
  • an outer surface of the dielectric foam 1804 can be further surrounded in whole or in part by a third dielectric material 1806, which can serve as an outer jacket (referred to herein as jacket 1806).
  • the jacket 1806 can prevent exposure of the dielectric core 1802 and the dielectric foam 1804 to an environment that can adversely affect the propagation of electromagnetic waves (e.g., water, soil, etc.).
  • the dielectric core 1802 can comprise, for example, a high density polyethylene material, a high density polyurethane material, or other suitable dielectric material(s).
  • the dielectric foam 1804 can comprise, for example, a cellular plastic material such an expanded polyethylene material, or other suitable dielectric material(s).
  • the jacket 1806 can comprise, for example, a polyethylene material or equivalent.
  • the dielectric constant of the dielectric foam 1804 can be (or substantially) lower than the dielectric constant of the dielectric core 1802.
  • the dielectric constant of the dielectric core 1802 can be approximately 2.3 while the dielectric constant of the dielectric foam 1804 can be approximately 1.15 (slightly higher than the dielectric constant of air).
  • the dielectric core 1802 can be used for receiving signals in the form of electromagnetic waves from a launcher or other coupling device described herein which can be configured to launch guided electromagnetic waves on the transmission medium 1800.
  • the transmission 1800 can be coupled to a hollow waveguide 1808 structured as, for example, a circular waveguide 1809, which can receive electromagnetic waves from a radiating device such as a stub antenna (not shown).
  • the hollow waveguide 1808 can in turn induce guided electromagnetic waves in the dielectric core 1802.
  • the guided electromagnetic waves are guided by or bound to the dielectric core 1802 and propagate longitudinally along the dielectric core 1802.
  • an operating frequency of the electromagnetic waves can be chosen such that a field intensity profile 1810 of the guided electromagnetic waves extends nominally (or not at all) outside of the jacket 1806.
  • the transmission medium 1800 can be used in hostile environments without adversely affecting the propagation of the electromagnetic waves propagating therein.
  • the transmission medium 1800 can be buried in soil with no (or nearly no) adverse effect to the guided electromagnetic waves propagating in the transmission medium 1800.
  • the transmission medium 1800 can be exposed to water (e.g., rain or placed underwater) with no (or nearly no) adverse effect to the guided electromagnetic waves propagating in the transmission medium 1800.
  • the propagation loss of guided electromagnetic waves in the foregoing embodiments can be 1 to 2 dB per meter or better at an operating frequency of 60 GHz.
  • the transmission medium 1800 can in some embodiments be flexed laterally with no (or nearly no) adverse effect to the guided electromagnetic waves propagating through the dielectric core 1802 and the dielectric foam 1804.
  • FIG. 18B depicts a transmission medium 1820 that differs from the transmission medium 1800 of FIG. 18 A, yet provides a further example of the transmission medium 125 presented in conjunction with FIG 1.
  • the transmission medium 1820 shows similar reference numerals for similar elements of the transmission medium 1800 of FIG. 18A.
  • the transmission medium 1820 comprises a conductive core 1822 having an insulation layer 1823 surrounding the conductive core 1822 in whole or in part.
  • the combination of the insulation layer 1823 and the conductive core 1822 will be referred to herein as an insulated conductor 1825.
  • the insulation layer 1823 is covered in whole or in part by a dielectric foam 1804 and jacket 1806, which can be constructed from the materials previously described.
  • the insulation layer 1823 can comprise a dielectric material, such as polyethylene, having a higher dielectric constant than the dielectric foam 1804 (e.g., 2.3 and 1.15, respectively).
  • the components of the transmission medium 1820 can be coaxially aligned (although not necessary).
  • a hollow waveguide 1808 having metal plates 1809, which can be separated from the insulation layer 1823 (although not necessary) can be used to launch guided electromagnetic waves that substantially propagate on an outer surface of the insulation layer 1823, however other coupling devices as described herein can likewise be employed.
  • the guided electromagnetic waves can be sufficiently guided by or bound by the insulation layer 1823 to guide the electromagnetic waves longitudinally along the insulation layer 1823.
  • an operating frequency of the guided electromagnetic waves launched by the hollow waveguide 1808 can generate an electric field intensity profile 1824 that results in the guided electromagnetic waves being substantially confined within the dielectric foam 1804 thereby preventing the guided electromagnetic waves from being exposed to an environment (e.g., water, soil, etc.) that adversely affects propagation of the guided electromagnetic waves via the transmission medium 1820.
  • an environment e.g., water, soil, etc.
  • FIG. 18C depicts a transmission medium 1830 that differs from the transmission mediums 1800 and 1820 of FIGs. 18A and 18B, yet provides a further example of the transmission medium 125 presented in conjunction with FIG 1.
  • the transmission medium 1830 shows similar reference numerals for similar elements of the transmission mediums 1800 and 1820 of FIGs. 18A and 18B, respectively.
  • the transmission medium 1830 comprises a bare (or uninsulated) conductor 1832 surrounded in whole or in part by the dielectric foam 1804 and the jacket 1806, which can be constructed from the materials previously described.
  • the components of the transmission medium 1830 can be coaxially aligned (although not necessary).
  • a hollow waveguide 1808 having metal plates 1809 coupled to the bare conductor 1832 can be used to launch guided electromagnetic waves that substantially propagate on an outer surface of the bare conductor 1832, however other coupling devices described herein can likewise be employed.
  • the guided electromagnetic waves can be sufficiently guided by or bound by the bare conductor 1832 to guide the guided electromagnetic waves longitudinally along the bare conductor 1832.
  • an operating frequency of the guided electromagnetic waves launched by the hollow waveguide 1808 can generate an electric field intensity profile 1834 that results in the guided electromagnetic waves being substantially confined within the dielectric foam 1804 thereby preventing the guided electromagnetic waves from being exposed to an environment (e.g., water, soil, etc.) that adversely affects propagation of the electromagnetic waves via the transmission medium 1830.
  • an environment e.g., water, soil, etc.
  • the hollow launcher 1808 used with the transmission mediums 1800, 1820 and 1830 of FIGs. 18A, 18B and 18C, respectively, can be replaced with other launchers or coupling devices.
  • the propagation mode(s) of the electromagnetic waves for any of the foregoing embodiments can be fundamental mode(s), a non-fundamental (or asymmetric) mode(s), or combinations thereof.
  • FIG. 18D is a block diagram illustrating an example, non-limiting embodiment of bundled transmission media 1836 in accordance with various aspects described herein.
  • the bundled transmission media 1836 can comprise a plurality of cables 1838 held in place by a flexible sleeve 1839.
  • the plurality of cables 1838 can comprise multiple instances of cable 1800 of FIG. 18A, multiple instances of cable 1820 of FIG. 18B, multiple instances of cable 1830 of FIG. 18C, or any combinations thereof.
  • the sleeve 1839 can comprise a dielectric material that prevents soil, water or other external materials from making contact with the plurality of cables 1838.
  • each guided electromagnetic wave can be adapted to selectively induce a guided electromagnetic wave in each cable, each guided electromagnetic wave conveys different data (e.g., voice, video, messaging, content, etc.).
  • the electric field intensity profile of each guided electromagnetic wave can be fully or substantially confined within layers of a corresponding cable 1838 to reduce cross-talk between cables 1838.
  • cross-talk of electromagnetic signals can occur between cables 1838 as illustrated by signal plots associated with two cables depicted in FIG. 18E.
  • the plots in FIG. 18E show that when a guided electromagnetic wave is induced on a first cable, the emitted electric and magnetic fields of the first cable can induce signals on the second cable, which results in cross-talk.
  • an absorption material 1840 that can absorb electromagnetic fields, such as carbon can be applied to the cables 1838 as shown in FIG. 18F to polarize each guided electromagnetic wave at various polarization states to reduce cross-talk between cables 1838.
  • carbon beads can be added to gaps between the cables 1838 to reduce cross-talk.
  • a diameter of cable 1838 can be configured differently to vary a speed of propagation of guided electromagnetic waves between the cables 1838 in order to reduce cross-talk between cables 1838.
  • a shape of each cable 1838 can be made asymmetric (e.g., elliptical) to direct the guided electromagnetic fields of each cable 1838 away from each other to reduce cross-talk.
  • a filler material such as dielectric foam can be added between cables 1838 to sufficiently separate the cables 1838 to reduce cross-talk therebetween.
  • each launcher can be configured to launch a guided electromagnetic wave having a different frequency, modulation, wave propagation mode, such as an orthogonal frequency, modulation or mode, to reduce cross-talk between the cables 1838.
  • pairs of cables 1838 can be twisted in a helix to reduce cross-talk between the pairs and other cables 1838 in a vicinity of the pairs.
  • certain cables 1838 can be twisted while other cables 1838 are not twisted to reduce cross-talk between the cables 1838.
  • each twisted pair cable 1838 can have different pitches (i.e., different twist rates, such as twists per meter) to further reduce cross-talk between the pairs and other cables 1838 in a vicinity of the pairs.
  • launchers or other coupling devices can be configured to induce guided electromagnetic waves in the cables 1838 having electromagnetic fields that extend beyond the jacket 1806 into gaps between the cables to reduce cross-talk between the cables 1838. It is submitted that any one of the foregoing embodiments for mitigating cross-talk between cables 1838 can be combined to further reduce cross -talk therebetween.
  • FIGs. 18G and 18H are block diagrams illustrating example, non-limiting embodiments of a transmission medium with an inner waveguide in accordance with various aspects described herein.
  • a transmission medium 1841 can comprise a core 1842.
  • the core 1842 can be a dielectric core 1842 (e.g., polyethylene).
  • the core 1842 can be an insulated or uninsulated conductor.
  • the core 1842 can be surrounded by a shell 1844 comprising a dielectric foam (e.g., expanded polyethylene material) having a lower dielectric constant than the dielectric constant of a dielectric core, or insulation layer of a conductive core. The difference in dielectric constants enables electromagnetic waves to be bound and guided by the core 1842.
  • the shell 1844 can be covered by a shell jacket 1845.
  • the shell jacket 1845 can be made of rigid material (e.g., high density plastic) or a high tensile strength material (e.g., synthetic fiber).
  • the shell jacket 1845 can be used to prevent exposure of the shell 1844 and core 1842 from an adverse environment (e.g., water, moisture, soil, etc.).
  • the shell jacket 1845 can be sufficiently rigid to separate an outer surface of the core 1842 from an inner surface of the shell jacket 1845 thereby resulting in a longitudinal gap between the shell jacket 1854 and the core 1842.
  • the longitudinal gap can be filled with the dielectric foam of the shell 1844.
  • the transmission medium 1841 can further include a plurality of outer ring conductors 1846.
  • the outer ring conductors 1846 can be strands of conductive material that are woven around the shell jacket 1845, thereby covering the shell jacket 1845 in whole or in part.
  • the outer ring conductors 1846 can serve the function of a power line having a return electrical path similar to the embodiments described in the subject disclosure for receiving power signals from a source (e.g., a transformer, a power generator, etc.).
  • the outer ring conductors 1846 can be covered by a cable jacket 1847 to prevent exposure of the outer ring conductors 1846 to water, soil, or other environmental factors.
  • the cable jacket 1847 can be made of an insulating material such as polyethylene.
  • the core 1842 can be used as a center waveguide for the propagation of electromagnetic waves.
  • a hallow waveguide launcher 1808 such as the circular waveguide previously described, can be used to launch signals that induce electromagnetic waves guided by the core 1842 in ways similar to those described for the embodiments of FIGs. 18 A, 18B, and 18C.
  • the electromagnetic waves can be guided by the core 1842 without utilizing the electrical return path of the outer ring conductors 1846 or any other electrical return path.
  • an operating frequency of the electromagnetic waves can be chosen such that a field intensity profile of the guided electromagnetic waves extends nominally (or not at all) outside of the shell jacket 1845.
  • a transmission medium 1843 can comprise a hollow core 1842' surrounded by a shell jacket 1845' .
  • the shell jacket 1845' can have an inner conductive surface or other surface materials that enable the hollow core 1842' to be used as a conduit for electromagnetic waves.
  • the shell jacket 1845' can be covered at least in part with the outer ring conductors 1846 described earlier for conducting a power signal.
  • a cable jacket 1847 can be disposed on an outer surface of the outer ring conductors 1846 to prevent exposure of the outer ring conductors 1846 to water, soil or other environmental factors.
  • a waveguide launcher 1808 can be used to launch electromagnetic waves guided by the hollow core 1842' and the conductive inner surface of the shell jacket 1845'.
  • the hollow core 1842' can further include a dielectric foam such as described earlier.
  • Transmission medium 1841 can represent a multi-purpose cable that conducts power on the outer ring conductors 1846 utilizing an electrical return path and that provides communication services by way of an inner waveguide comprising a combination of the core 1842, the shell 1844 and the shell jacket 1845.
  • the inner waveguide can be used for transmitting or receiving electromagnetic waves (without utilizing an electrical return path) guided by the core 1842.
  • transmission medium 1843 can represent a multi- purpose cable that conducts power on the outer ring conductors 1846 utilizing an electrical return path and that provides communication services by way of an inner waveguide comprising a combination of the hollow core 1842' and the shell jacket 1845'.
  • the inner waveguide can be used for transmitting or receiving electromagnetic waves (without utilizing an electrical return path) guided the hollow core 1842' and the shell jacket 1845' .
  • FIGs. 18G-18H can be adapted to use multiple inner waveguides surrounded by outer ring conductors 1846.
  • the inner waveguides can be adapted to use to cross-talk mitigation techniques described above (e.g., twisted pairs of waveguides, waveguides of different structural dimensions, use of polarizers within the shell, use of different wave modes, etc.).
  • the transmission mediums 1800, 1820, 1830 1836, 1841 and 1843 will be referred to herein as a cable 1850 with an understanding that cable 1850 can represent any one of the transmission mediums described in the subject disclosure, or a bundling of multiple instances thereof.
  • the dielectric core 1802, insulated conductor 1825, bare conductor 1832, core 1842, or hollow core 1842' of the transmission mediums 1800, 1820, 1830, 1836, 1841 and 1843, respectively, will be referred to herein as transmission core 1852 with an understanding that cable 1850 can utilize the dielectric core 1802, insulated conductor 1825, bare conductor 1832, core 1842, or hollow core 1842' of transmission mediums 1800, 1820, 1830, 1836, 1841 and/or 1843, respectively.
  • cable 1850 can be configured with a female connection arrangement or a male connection arrangement as depicted in FIG. 181.
  • the male configuration on the right of FIG. 181 can be accomplished by stripping the dielectric foam 1804 (and jacket 1806 if there is one) to expose a portion of the transmission core 1852.
  • the female configuration on the left of FIG. 181 can be accomplished by removing a portion of the transmission core 1852, while maintaining the dielectric foam 1804 (and jacket 1806 if there is one).
  • the transmission core 1852 is hollow as described in relation to FIG.
  • the male portion of the transmission core 1852 can represent a hollow core with a rigid outer surface that can slide into the female arrangement on the left side of FIG. 181 to align the hollow cores together. It is further noted that in the embodiments of FIGs. 18G-18H, the outer ring of conductors 1846 can be modified to connect male and female portions of cable 1850.
  • the two cables 1850 having male and female connector arrangements can be mated together.
  • a sleeve with an adhesive inner lining or a shrink wrap material (not shown) can be applied to an area of a joint between cables 1850 to maintain the joint in a fixed position and prevent exposure (e.g., to water, soil, etc.).
  • the transmission core 1852 of one cable will be in close proximity to the transmission core 1852 of the other cable.
  • Guided electromagnetic waves propagating by way of either the transmission core 1852 of cables 1850 traveling from either direction can cross over between the disjoint the transmission cores 1852 whether or not the transmission cores 1852 touch, whether or not the transmission cores 1852 are coaxially aligned, and/or whether or not there is a gap between the transmission cores 1852.
  • a splicing device 1860 having female connector arrangements at both ends can be used to mate cables 1850 having male connector arrangements as shown in FIG. 18J.
  • the splicing device 1860 can be adapted to have male connector arrangements at both ends which can be mated to cables 1850 having female connector arrangements.
  • the splicing device 1860 can be adapted to have a male connector arrangement and a female connector arrangement at opposite ends which can be mated to cables 1850 having female and male connector arrangements, respectively.
  • the male and female arrangements described in FIG. 181 can be applied to the splicing device 1860 whether the ends of the splicing device 1860 are both male, both female, or a combination thereof.
  • the foregoing embodiments for connecting cables illustrated in FIGs. 18I-18J can be applied to each single instance of cable 1838 of bundled transmission media 1836. Similarly, the foregoing embodiments illustrated in FIGs. 18I-18J can be applied to each single instance of an inner waveguide for a cable 1841 or 1843 having multiple inner waveguides.
  • a transmission medium 1800' can include a core 1801, and a dielectric foam 1804' divided into sections and covered by a jacket 1806 as shown in FIG. 18K.
  • the core 1801 can be represented by the dielectric core 1802 of FIG. 18 A, the insulated conductor 1825 of FIG. 18B, or the bare conductor 1832 of FIG. 18C.
  • Each section of dielectric foam 1804' can be separated by a gap (e.g., air, gas, vacuum, or a substance with a low dielectric constant).
  • the gap separations between the sections of dielectric foam 1804' can be quasi-random as shown in FIG. 18K, which can be helpful in reducing reflections of electromagnetic waves occurring at each section of dielectric foam 1804' as they propagate longitudinally along the core 1801.
  • the sections of the dielectric foam 1804' can be constructed, for example, as washers made of a dielectric foam having an inner opening for supporting the core 1801 in a fixed position.
  • the washers will be referred to herein as washers 1804'.
  • the inner opening of each washer 1804' can be coaxially aligned with an axis of the core 1801.
  • the inner opening of each washer 1804' can be offset from the axis of the core 1801.
  • each washer 1804' can have a variable longitudinal thickness as shown by differences in thickness of the washers 1804' .
  • a transmission medium 1800' ' can include a core 1801, and a strip of dielectric foam 1804" wrapped around the core in a helix covered by a jacket 1806 as shown in FIG. 18K.
  • the strip of dielectric foam 1804" can be twisted around the core 1801 with variable pitches (i.e., different twist rates) for different sections of the strip of dielectric foam 1804". Utilizing variable pitches can help reduce reflections or other disturbances of the electromagnetic waves occurring between areas of the core 1801 not covered by the strip of dielectric foam 1804".
  • the thickness (diameter) of the strip of dielectric foam 1804" can be substantially larger (e.g., 2 or more times larger) than diameter of the core 1801 shown in FIG. 18K.
  • a transmission medium 1800" ' (shown in a cross-sectional view) can include a non-circular core 1801 ' covered by a dielectric foam 1804 and jacket 1806.
  • the non-circular core 180 can have an elliptical structure as shown in FIG. 18K, or other suitable non-circular structure.
  • the non-circular core 180 ⁇ can have an asymmetric structure.
  • a non-circular core 180 ⁇ can be used to polarize the fields of electromagnetic waves induced on the non- circular core 180 ⁇ . The structure of the non-circular core 180 ⁇ can help preserve the polarization of the electromagnetic waves as they propagate along the non-circular core 1801'.
  • a transmission medium 1800" " can include multiple cores 1801" (only two cores are shown but more are possible).
  • the multiple cores 1801" can be covered by a dielectric foam 1804 and jacket 1806.
  • the multiple cores 1801" can be used to polarize the fields of electromagnetic waves induced on the multiple cores 1801" .
  • the structure of the multiple cores 180 can preserve the polarization of the guided electromagnetic waves as they propagate along the multiple cores 1801" .
  • FIG. 18K can be used to modify the embodiments of FIGs. 18G-18H.
  • core 1842 or core 1842' can be adapted to utilized sectionalized shells 1804' with gaps therebetween, or one or more strips of dielectric foam 1804".
  • core 1842 or core 1842' can be adapted to have a non- circular core 180 that may have symmetric or asymmetric cross-sectional structure.
  • core 1842 or core 1842' can be adapted to use multiple cores 1801" in a single inner waveguide, or different numbers of cores when multiple inner waveguides are used. Accordingly, any of the embodiments shown in FIG. 18K can be applied singly or in combination to the embodiments of 18G-18H.
  • a bundled transmission medium 1836' can include variable core structures 1803. By varying the structures of cores 1803, fields of guided electromagnetic waves induced in each of the cores of transmission medium 1836' may differ sufficiently to reduce cross-talk between cables 1838.
  • a bundled transmission media 1836" can include a variable number of cores 1803' per cable 1838. By varying the number of cores 1803' per cable 1838, fields of guided electromagnetic waves induced in the one or more cores of transmission medium 1836" may differ sufficiently to reduce cross-talk between cables 1838.
  • the cores 1803 or 1803' can be of different materials.
  • the cores 1803 or 1803' can be a dielectric core 1802, an insulated conductor core 1825, a bare conductor core 1832, or any combinations thereof.
  • FIGs. 18 A- 18D and 18F- 18H can be modified by and/or combined with some of the embodiments of FIGs. 18K-18L. It is further noted that one or more of the embodiments illustrated in FIGs. 18K-18L can be combined (e.g., using sectionalized dielectric foam 1804' or a helix strip of dielectric foam 1804" with cores 1801', 1801", 1803 or 1803').
  • guided electromagnetic waves propagating in the transmission mediums 1800', 1800", 1800" ', and/or 1800"" of FIG. 18K may experience less propagation losses than guided electromagnetic waves propagating in the transmission mediums 1800, 1820 and 1830 of FIGs. 18A-18C.
  • the embodiments illustrated in FIGs. 18K-18L can be adapted to use the connectivity embodiments illustrated in FIGs. 18I-18J.
  • FIG. 18M a block diagram illustrating an example, non- limiting embodiment of exposed tapered stubs from the bundled transmission media 1836 for use as antennas 1855 is shown.
  • Each antenna 1855 can serve as a directional antenna for radiating wireless signals directed to wireless communication devices or for inducing electromagnetic wave propagation on a surface of a transmission medium (e.g., a power line).
  • the wireless signals radiated by the antennas 1855 can be beam steered by adapting the phase and/or other characteristics of the wireless signals generated by each antenna 1855.
  • the antennas 1855 can individually be placed in a pie-pan antenna assembly for directing wireless signals in various directions.
  • core can comprise any types of materials (or combinations of materials) that enable electromagnetic waves to remain bound to the core while propagating longitudinally along the core.
  • a strip of dielectric foam 1804" described earlier can be replaced with a strip of an ordinary dielectric material (e.g., polyethylene) for wrapping around the dielectric core 1802 (referred to herein for illustration purposes only as a "wrap").
  • an average density of the wrap can be small as a result of air space between sections of the wrap. Consequently, an effective dielectric constant of the wrap can be less than the dielectric constant of the dielectric core 1802, thereby enabling guided electromagnetic waves to remain bound to the core.
  • any of the embodiments of the subject disclosure relating to materials used for core(s) and wrappings about the core(s) can be structurally adapted and/or modified with other dielectric materials that achieve the result of maintaining electromagnetic waves bound to the core(s) while they propagate along the core(s).
  • a core in whole or in part as described in any of the embodiments of the subject disclosure can comprise an opaque material (e.g., polyethylene) that is resistant to propagation of electromagnetic waves having an optical operating frequency. Accordingly, electromagnetic waves guided and bound to the core will have a non-optical frequency range (e.g., less than the lowest frequency of visible light).
  • FIGs. 18N, 180, 18P, 18Q, 18R, 18S and 18T are block diagrams illustrating example, non-limiting embodiments of a waveguide device for transmitting or receiving electromagnetic waves in accordance with various aspects described herein.
  • FIG. 18N illustrates a front view of a waveguide device 1865 having a plurality of slots 1863 (e.g., openings or apertures) for emitting electromagnetic waves having radiated electric fields (e-fields) 1861.
  • slots 1863 e.g., openings or apertures
  • the radiated e-fields 1861 of pairs of symmetrically positioned slots 1863 can be directed away from each other (i.e., polar opposite radial orientations about the cable 1862). While the slots 1863 are shown as having a rectangular shape, other shapes such as other polygons, sector and arc shapes, ellipsoid shapes and other shapes are likewise possible.
  • north will refer to a relative direction as shown in the figures. All references in the subject disclosure to other directions (e.g., south, east, west, northwest, and so forth) will be relative to northern illustration.
  • the north and south slots 1863 can be arranged to have a circumferential distance between each other that is approximately one wavelength of electromagnetic waves signals supplied to these slots.
  • the waveguide 1865 can have a cylindrical cavity in a center of the waveguide 1865 to enable placement of a cable 1862.
  • the cable 1862 can comprise an insulated conductor.
  • the cable 1862 can comprise an uninsulated conductor.
  • the cable 1862 can comprise any of the embodiments of a transmission core 1852 of cable 1850 previously described.
  • the cable 1862 can slide into the cylindrical cavity of the waveguide 1865.
  • the waveguide 1865 can utilize an assembly mechanism (not shown).
  • the assembly mechanism e.g., a hinge or other suitable mechanism that provides a way to open the waveguide 1865 at one or more locations
  • the waveguide 1865 can be configured to wrap around the cable 1862 like a collar.
  • FIG. 180 illustrates a side view of an embodiment of the waveguide 1865.
  • the waveguide 1865 can be adapted to have a hollow rectangular waveguide portion 1867 that receives electromagnetic waves 1866 generated by a transmitter circuit as previously described in the subject disclosure (e.g., see FIGs. 1 and 10A).
  • the electromagnetic waves 1866 can be distributed by the hollow rectangular waveguide portion 1867 into in a hollow collar 1869 of the waveguide 1865.
  • the rectangular waveguide portion 1867 and the hollow collar 1869 can be constructed of materials suitable for maintaining the electromagnetic waves within the hollow chambers of these assemblies (e.g., carbon fiber materials). It should be noted that while the waveguide portion 1867 is shown and described in a hollow rectangular configuration, other shapes and/or other non-hollow configurations can be employed.
  • the waveguide portion 1867 can have a square or other polygonal cross section, an arc or sector cross section that is truncated to conform to the outer surface of the cable 1862, a circular or ellipsoid cross section or cross sectional shape.
  • the waveguide portion 1867 can be configured as, or otherwise include, a solid dielectric material.
  • the hollow collar 1869 can be configured to emit electromagnetic waves from each slot 1863 with opposite e-fields 1861 at pairs of symmetrically positioned slots 1863 and 1863'.
  • the electromagnetic waves emitted by the combination of slots 1863 and 1863' can in turn induce electromagnetic waves 1868 on that are bound to the cable 1862 for propagation according to a fundamental wave mode without other wave modes present— such as non-fundamental wave modes.
  • the electromagnetic waves 1868 can propagate longitudinally along the cable 1862 to other downstream waveguide systems coupled to the cable 1862.
  • slot 1863 can emit electromagnetic waves having a stronger magnitude than electromagnetic waves emitted by slot 1863' (at the southern position). To reduce magnitude differences between these slots, slot 1863' can be made larger than slot 1863.
  • the technique of utilizing different slot sizes to balance signal magnitudes between slots can be applied to any of the embodiments of the subject disclosure relating to FIGs. 18N, 180, 18Q, 18S, 18U and 18V— some of which are described below.
  • FIG. 18P depicts a waveguide 1865' that can be configured to utilize circuitry such as monolithic microwave integrated circuits (MMICs) 1870 each coupled to a signal input 1872 (e.g., coaxial cable that provides a communication signal).
  • MMICs monolithic microwave integrated circuits
  • the signal input 1872 can be generated by a transmitter circuit as previously described in the subject disclosure (e.g., see reference 101, 1000 of FIGs. 1 and 10A) adapted to provide electrical signals to the MMICs 1870.
  • Each MMIC 1870 can be configured to receive signal 1872 which the MMIC 1870 can modulate and transmit with a radiating element (e.g., an antenna) to emit electromagnetic waves having radiated e- fields 1861.
  • a radiating element e.g., an antenna
  • the MMICs 1870 can be configured to receive the same signal 1872, but transmit electromagnetic waves having e-fields 1861 of opposing orientation. This can be accomplished by configuring one of the MMICs 1870 to transmit electromagnetic waves that are 180 degrees out of phase with the electromagnetic waves transmitted by the other MMIC 1870.
  • the combination of the electromagnetic waves emitted by the MMICs 1870 can together induce electromagnetic waves 1868 that are bound to the cable 1862 for propagation according to a fundamental wave mode without other wave modes present— such as non-fundamental wave modes. In this configuration, the electromagnetic waves 1868 can propagate longitudinally along the cable 1862 to other downstream waveguide systems coupled to the cable 1862.
  • a tapered horn 1880 can be added to the embodiments of FIGs. 180 and 18P to assist in the inducement of the electromagnetic waves 1868 on cable 1862 as depicted in FIGs. 18Q and 18R.
  • the electromagnetic waves induced on the cable 1862 can have a large radial dimension (e.g., 1 meter).
  • an insulation layer 1879 can be applied on a portion of the cable 1862 at or near the cavity as depicted with hash lines in FIGs. 18Q and 18R.
  • the insulation layer 1879 can have a tapered end facing away from the waveguide 1865.
  • the added insulation enables the electromagnetic waves 1868 initially launched by the waveguide 1865 (or 1865') to be tightly bound to the insulation, which in turn reduces the radial dimension of the electromagnetic fields 1868 (e.g., centimeters).
  • the radial dimension of the electromagnetic waves 1868 begin to increase eventually achieving the radial dimension they would have had had the electromagnetic waves 1868 been induced on the uninsulated conductor without an insulation layer.
  • the tapered end begins at an end of the tapered horn 1880.
  • the tapered end of the insulation layer 1879 can begin before or after the end of the tapered horn 1880.
  • the tapered horn can be metallic or constructed of other conductive material or constructed of a plastic or other non-conductive material that is coated or clad with a dielectric layer or doped with a conductive material to provide reflective properties similar to a metallic horn.
  • cable 1862 can comprise any of the embodiments of cable 1850 described earlier.
  • waveguides 1865 and 1865' can be coupled to a transmission core 1852 of cable 1850 as depicted in FIGs. 18S and 18T.
  • the waveguides 1865 and 1865' can induce, as previously described, electromagnetic waves 1868 on the transmission core 1852 for propagation entirely or partially within inner layers of cable 1850.
  • electromagnetic waves 1868 can be bidirectional.
  • electromagnetic waves 1868 of a different operating frequency can be received by slots 1863 or MMICs 1870 of the waveguides 1865 and 1865', respectively.
  • the electromagnetic waves can be converted by a receiver circuit (e.g., see reference 101, 1000 of FIGs. 1 and 10A) for generating a communication signal for processing.
  • the waveguides 1865 and 1865' can be adapted so that the waveguides 1865 and 1865' can direct electromagnetic waves 1868 upstream or downstream longitudinally.
  • a first tapered horn 1880 coupled to a first instance of a waveguide 1865 or 1865' can be directed westerly on cable 1862
  • a second tapered horn 1880 coupled to a second instance of a waveguide 1865 or 1865' can be directed easterly on cable 1862.
  • the first and second instances of the waveguides 1865 or 1865' can be coupled so that in a repeater configuration, signals received by the first waveguide 1865 or 1865' can be provided to the second waveguide 1865 or 1865' for retransmission in an easterly direction on cable 1862.
  • the repeater configuration just described can also be applied from an easterly to westerly direction on cable 1862.
  • the waveguide 1865 of FIGs. 18N, 180, 18Q and 18S can also be configured to generate electromagnetic fields having only non-fundamental or asymmetric wave modes.
  • FIG. 18U depicts an embodiment of a waveguide 1865 that can be adapted to generate electromagnetic fields having only non-fundamental wave modes.
  • a median line 1890 represents a separation between slots where electrical currents on a backside (not shown) of a frontal plate of the waveguide 1865 change polarity.
  • electrical currents on the backside of the frontal plate corresponding to e-fields that are radially outward can in some embodiments be associated with slots located outside of the median line 1890 (e.g., slots 1863A and 1863B).
  • Electrical currents on the backside of the frontal plate corresponding to e-fields that are radially inward can in some embodiments be associated with slots located inside of the median line 1890.
  • the direction of the currents can depend on the operating frequency of the electromagnetic waves 1866 supplied to the hollow rectangular waveguide portion 1867 (see FIG. 180) among other parameters.
  • the electromagnetic waves 1866 supplied to the hollow rectangular waveguide portion 1867 have an operating frequency whereby a circumferential distance between slots 1863 A and 1863B is one full wavelength of the electromagnetic waves 1866.
  • the e-fields of the electromagnetic waves emitted by slots 1863 A and 1863B point radially outward (i.e., have opposing orientations).
  • the electromagnetic waves emitted by slots 1863 A and 1863B are combined, the resulting electromagnetic waves on cable 1862 will propagate according to the fundamental wave mode.
  • slot 1863C will generate electromagnetic waves that have e-fields that are approximately 180 degrees out of phase with the e-fields of the electromagnetic waves generated by slot 1863 A. Consequently, the e-field orientations of the electromagnetic waves generated by slot pairs 1863 A and 1863C will be substantially aligned.
  • the combination of the electromagnetic waves emitted by slot pairs 1863 A and 1863C will thus generate electromagnetic waves that are bound to the cable 1862 for propagation according to a non-fundamental wave mode.
  • waveguide 1865 can be adapted according to the embodiments depicted in FIG. 18V.
  • Configuration (A) depicts a waveguide 1865 having a plurality of symmetrically positioned slots.
  • Each of the slots 1863 of configuration (A) can be selectively disabled by blocking the slot with a material (e.g., carbon fiber or metal) to prevent the emission of electromagnetic waves.
  • a blocked (or disabled) slot 1863 is shown in black, while an enabled (or unblocked) slot 1863 is shown in white.
  • a blocking material can be placed behind (or in front) of the frontal plate of the waveguide 1865.
  • a mechanism can be coupled to the blocking material so that the blocking material can slide in or out of a particular slot 1863 much like closing or opening a window with a cover.
  • the mechanism can be coupled to a linear motor controllable by circuitry of the waveguide 1865 to selectively enable or disable individual slots 1863. With such a mechanism at each slot 1863, the waveguide 1865 can be configured to select different configurations of enabled and disabled slots 1863 as depicted in the embodiments of FIG. 18V.
  • Other methods or techniques for covering or opening slots e.g., utilizing rotatable disks behind or in front of the waveguide 1865) can be applied to the embodiments of the subject disclosure.
  • the waveguide system 1865 can be configured to enable certain slots 1863 outside the median line 1890 and disable certain slots 1863 inside the median line 1890 as shown in configuration (B) to generate fundamental waves.
  • the circumferential distance between slots 1863 outside the median line 1890 i.e., in the northern and southern locations of the waveguide system 1865
  • these slots will therefore have electric fields (e-fields) pointing at certain instances in time radially outward as previously described.
  • the slots inside the median line 1890 i.e., in the western and eastern locations of the waveguide system 1865
  • 18V can be used to generate electromagnetic waves at the northern and southern slots 1863 having e-fields that point radially outward and electromagnetic waves at the western and eastern slots 1863 with e-fields that also point radially outward, which when combined induce electromagnetic waves on cable 1862 having a fundamental wave mode.
  • the waveguide system 1865 can be configured to enable a northerly, southerly, westerly and easterly slots 1863 all outside the median line 1890, and disable all other slots 1863 as shown in configuration (C). Assuming the circumferential distance between a pair of opposing slots (e.g., northerly and southerly, or westerly and easterly) is a full wavelength apart, then configuration (C) can be used to generate electromagnetic waves having a non-fundamental wave mode with some e-fields pointing radially outward and other fields pointing radially inward.
  • configuration (C) can be used to generate electromagnetic waves having a non-fundamental wave mode with some e-fields pointing radially outward and other fields pointing radially inward.
  • the waveguide system 1865 can be configured to enable a northwesterly slot 1863 outside the median line 1890, enable a southeasterly slot 1863 inside the median line 1890, and disable all other slots 1863 as shown in configuration (D). Assuming the circumferential distance between such a pair of slots is a full wavelength apart, then such a configuration can be used to generate electromagnetic waves having a non-fundamental wave mode with e-fields aligned in a northwesterly direction.
  • the waveguide system 1865 can be configured to produce electromagnetic waves having a non-fundamental wave mode with e-fields aligned in a southwesterly direction. This can be accomplished by utilizing a different arrangement than used in configuration (D).
  • Configuration (E) can be accomplished by enabling a southwesterly slot 1863 outside the median line 1890, enabling a northeasterly slot 1863 inside the median line 1890, and disabling all other slots 1863 as shown in configuration (E). Assuming the circumferential distance between such a pair of slots is a full wavelength apart, then such a configuration can be used to generate electromagnetic waves having a non-fundamental wave mode with e-fields aligned in a southwesterly direction. Configuration (E) thus generates a non-fundamental wave mode that is orthogonal to the non-fundamental wave mode of configuration (D).
  • the waveguide system 1865 can be configured to generate electromagnetic waves having a fundamental wave mode with e-fields that point radially inward. This can be accomplished by enabling a northerly slot 1863 inside the median line 1890, enabling a southerly slot 1863 inside the median line 1890, enabling an easterly slot outside the median 1890, enabling a westerly slot 1863 outside the median 1890, and disabling all other slots 1863 as shown in configuration (F). Assuming the circumferential distance between the northerly and southerly slots is a full wavelength apart, then such a configuration can be used to generate electromagnetic waves having a fundamental wave mode with radially inward e-fields. Although the slots selected in configurations (B) and (F) are different, the fundamental wave modes generated by configurations (B) and (F) are the same.
  • e-fields can be manipulated between slots to generate fundamental or non-fundamental wave modes by varying the operating frequency of the electromagnetic waves 1866 supplied to the hollow rectangular waveguide portion 1867.
  • the operating frequency of the electromagnetic waves 1866 supplied to the hollow rectangular waveguide portion 1867 For example, assume in the illustration of FIG. 18U that for a particular operating frequency of the electromagnetic waves 1866 the circumferential distance between slot 1863 A and 1863B is one full wavelength of the electromagnetic waves 1866.
  • the e-fields of electromagnetic waves emitted by slots 1863 A and 1863B will point radially outward as shown, and can be used in combination to induce electromagnetic waves on cable 1862 having a fundamental wave mode.
  • the e-fields of electromagnetic waves emitted by slots 1863A and 1863C will be radially aligned (i.e., pointing northerly) as shown, and can be used in combination to induce electromagnetic waves on cable 1862 having a non-fundamental wave mode.
  • the operating frequency of the electromagnetic waves 1866 supplied to the hollow rectangular waveguide portion 1867 is changed so that the circumferential distance between slot 1863 A and 1863B is one-half a wavelength of the electromagnetic waves 1866.
  • the e-fields of electromagnetic waves emitted by slots 1863 A and 1863B will be radially aligned (i.e., point in the same direction). That is, the e-fields of electromagnetic waves emitted by slot 1863B will point in the same direction as the e-fields of electromagnetic waves emitted by slot 1863 A.
  • Such electromagnetic waves can be used in combination to induce electromagnetic waves on cable 1862 having a non-fundamental wave mode.
  • the e-fields of electromagnetic waves emitted by slots 1863A and 1863C will be radially outward (i.e., away from cable 1862), and can be used in combination to induce electromagnetic waves on cable 1862 having a fundamental wave mode.
  • the waveguide 1865' of FIGs. 18P, 18R and 18T can also be configured to generate electromagnetic waves having only non-fundamental wave modes. This can be accomplished by adding more MMICs 1870 as depicted in FIG. 18W. Each MMIC 1870 can be configured to receive the same signal input 1872. However, MMICs 1870 can selectively be configured to emit electromagnetic waves having differing phases using controllable phase- shifting circuitry in each MMIC 1870. For example, the northerly and southerly MMICs 1870 can be configured to emit electromagnetic waves having a 180 degree phase difference, thereby aligning the e-fields either in a northerly or southerly direction.
  • any combination of pairs of MMICs 1870 can be configured with opposing or aligned e-fields. Consequently, waveguide 1865' can be configured to generate electromagnetic waves with one or more non-fundamental wave modes, electromagnetic waves with one or more fundamental wave modes, or any combinations thereof.
  • electromagnetic waves having a non-fundamental wave mode can be generated by enabling a single slot from the plurality of slots shown in configuration (A) of FIG. 18V and disabling all other slots.
  • a single MMIC 1870 of the MMICs 1870 shown in FIG. 18W can be configured to generate electromagnetic waves having a non-fundamental wave mode while all other MMICs 1870 are not in use or disabled.
  • other wave modes and wave mode combinations can be induced by enabling other non-null proper subsets of waveguide slots 1863 or the MMICs 1870.
  • the e-field arrows shown in FIGs. 18U-18V are illustrative only and represent a static depiction of e-fields.
  • the electromagnetic waves may have oscillating e-fields, which at one instance in time point outwardly, and at another instance in time point inwardly.
  • e-fields may be aligned in one direction (e.g., northerly).
  • such waves may at another instance in time have e-fields that point in an opposite direction (e.g., southerly).
  • fundamental wave modes having e-fields that are radial may at one instance have e-fields that point radially away from the cable 1862 and at another instance in time point radially towards the cable 1862.
  • the embodiments of FIGs. 18U- 18W can be adapted to generate electromagnetic waves with one or more non-fundamental wave modes, electromagnetic waves with one or more fundamental wave modes (e.g., TM00 and HE 11 modes), or any combinations thereof.
  • such adaptions can be used in combination with any embodiments described in the subject disclosure.
  • the embodiments of FIGs. 18U-18W can be combined (e.g., slots used in combination with MMICs).
  • the waveguide systems 1865 and 1865' of FIGs. 18N-18W may generate combinations of fundamental and non-fundamental wave modes where one wave mode is dominant over the other.
  • electromagnetic waves generated by the waveguide systems 1865 and 1865' of FIGs. 18N-18W may have a weak signal component that has a non-fundamental wave mode, and a substantially strong signal component that has a fundamental wave mode. Accordingly, in this embodiment, the electromagnetic waves have a substantially fundamental wave mode.
  • the electromagnetic waves may have a weak signal component that has a fundamental wave mode, and a substantially strong signal component that has a non-fundamental wave mode. Accordingly, in this embodiment, the electromagnetic waves have a substantially non-fundamental wave mode. Further, a non-dominant wave mode may be generated that propagates only trivial distances along the length of the transmission medium.
  • the waveguide systems 1865 and 1865' of FIGs. 18N-18W can be configured to generate instances of electromagnetic waves that have wave modes that can differ from a resulting wave mode or modes of the combined electromagnetic wave. It is further noted that each MMIC 1870 of the waveguide system 1865' of FIG.
  • the waveguide system 1865' can thus be configured to generate instances of electromagnetic waves having different wave and spatial characteristics, which when combined achieve resulting electromagnetic waves having one or more desirable wave modes.
  • the waveguide systems 1865 and 1865' of FIGs. 18N-18W can be adapted to generate electromagnetic waves with one or more selectable wave modes.
  • the waveguide systems 1865 and 1865' can be adapted to select one or more wave modes and generate electromagnetic waves having a single wave mode or multiple wave modes selected and produced from a process of combining instances of electromagnetic waves having one or more configurable wave and spatial characteristics.
  • parametric information can be stored in a look-up table. Each entry in the look-up table can represent a selectable wave mode.
  • a selectable wave mode can represent a single wave mode, or a combination of wave modes.
  • the combination of wave modes can have one or dominant wave modes.
  • the parametric information can provide configuration information for generating instances of electromagnetic waves for producing resultant electromagnetic waves that have the desired wave mode.
  • the parametric information obtained from the look-up table from the entry associated with the selected wave mode(s) can be used to identify which of one or more MMICs 1870 to utilize, and/or their corresponding configurations to achieve electromagnetic waves having the desired wave mode(s).
  • the parametric information may identify the selection of the one or more MMICs 1870 based on the spatial orientations of the MMICs 1870, which may be required for producing electromagnetic waves with the desired wave mode.
  • the parametric information can also provide information to configure each of the one or more MMICs 1870 with a particular phase, frequency, magnitude, electric field orientation, and/or magnetic field orientation which may or may not be the same for each of the selected MMICs 1870.
  • a look-up table with selectable wave modes and corresponding parametric information can be adapted for configuring the slotted waveguide system 1865.
  • a guided electromagnetic wave can be considered to have a desired wave mode if the corresponding wave mode propagates non-trivial distances on a transmission medium and has a field strength that is substantially greater in magnitude (e.g., 20 dB higher in magnitude) than other wave modes that may or may not be desirable.
  • a desired wave mode or modes can be referred to as dominant wave mode(s) with the other wave modes being referred to as non-dominant wave modes.
  • a guided electromagnetic wave that is said to be substantially without the fundamental wave mode has either no fundamental wave mode or a non-dominant fundamental wave mode.
  • a guided electromagnetic wave that is said to be substantially without a non-fundamental wave mode has either no non-fundamental wave mode(s) or only non-dominant non- fundamental wave mode(s).
  • a guided electromagnetic wave that is said to have only a single wave mode or a selected wave mode may have only one corresponding dominant wave mode.
  • FIGs. 18U-18W can be applied to other embodiments of the subject disclosure.
  • the embodiments of FIGs. 18U- 18W can be used as alternate embodiments to the embodiments depicted in FIGs. 18N-18T or can be combined with the embodiments depicted in FIGs. 18N-18T.
  • FIG. 19A depicts a dielectric horn antenna 1901 having a conical structure.
  • the dielectric horn antenna 1901 is coupled to one end 1902' of a feedline 1902 having a feed point 1902" at an opposite end of the feedline 1902.
  • the dielectric horn antenna 1901 and the feedline 1902 can be constructed of dielectric materials such as a polyethylene material, a polyurethane material or other suitable dielectric material (e.g., a synthetic resin, other plastics, etc.).
  • the dielectric horn antenna 1901 and the feedline 1902 (as well as other embodiments of the dielectric antenna described below in the subject disclosure) can be adapted to be substantially or entirely devoid of any conductive materials.
  • the external surfaces 1907 of the dielectric horn antenna 1901 and the feedline 1902 can be non-conductive or substantially non-conductive with at least 95% of the external surface area being non-conductive and the dielectric materials used to construct the dielectric horn antenna 1901 and the feedline 1902 can be such that they substantially do not contain impurities that may be conductive (e.g., such as less than 1 part per thousand) or result in imparting conductive properties.
  • a limited number of conductive components can be used such as a metallic connector component used for coupling to the feed point 1902" of the feedline 1902 with one or more screws, rivets or other coupling elements used to bind components to one another, and/or one or more structural elements that do not significantly alter the radiation pattern of the dielectric antenna.
  • the feed point 1902" can be adapted to couple to a core 1852 such as previously described by way of illustration in FIGs. 181 and 18J.
  • the feed point 1902" can be coupled to the core 1852 utilizing a joint (not shown in FIG. 19A) such as the splicing device 1860 of FIG. 18J.
  • a joint such as the splicing device 1860 of FIG. 18J.
  • Other embodiments for coupling the feed point 1902" to the core 1852 can be used.
  • the joint can be configured to cause the feed point 1902" to touch an endpoint of the core 1852.
  • the joint can create a gap between the feed point 1902" and an end of the core 1852.
  • the joint can cause the feed point 1902" and the core 1852 to be coaxially aligned or partially misaligned.
  • electromagnetic waves can in whole or at least in part propagate between the junction of the feed point 1902' ' and the core 1852.
  • the cable 1850 can be coupled to the waveguide system 1865 depicted in FIG. 18S or the waveguide system 1865' depicted in FIG. 18T.
  • the waveguide system 1865' of FIG. 18T It is understood, however, that the waveguide system 1865 of FIG. 18S or other waveguide systems can also be utilized in accordance with the discussions that follow.
  • the waveguide system 1865' can be configured to select a wave mode (e.g., non-fundamental wave mode, fundamental wave mode, a hybrid wave mode, or combinations thereof as described earlier) and transmit instances of electromagnetic waves having a non-optical operating frequency (e.g., 60 GHz).
  • the electromagnetic waves can be directed to an interface of the cable 1850 as shown in FIG. 18T.
  • the instances of electromagnetic waves generated by the waveguide system 1865' can induce a combined electromagnetic wave having the selected wave mode that propagates from the core 1852 to the feed point 1902".
  • the combined electromagnetic wave can propagate partly inside the core 1852 and partly on an outer surface of the core 1852.
  • the combined electromagnetic wave can continue to propagate partly inside the feedline 1902 and partly on an outer surface of the feedline 1902.
  • the portion of the combined electromagnetic wave that propagates on the outer surface of the core 1852 and the feedline 1902 is small.
  • the combined electromagnetic wave can be said to be guided by and tightly coupled to the core 1852 and the feedline 1902 while propagating longitudinally towards the dielectric antenna 1901.
  • the combined electromagnetic wave When the combined electromagnetic wave reaches a proximal portion of the dielectric antenna 1901 (at a junction 1902' between the feedline 1902 and the dielectric antenna 1901), the combined electromagnetic wave enters the proximal portion of the dielectric antenna 1901 and propagates longitudinally along an axis of the dielectric antenna 1901 (shown as a hashed line).
  • the combined electromagnetic wave has an intensity pattern similar to the one shown by the side view and front view depicted in FIG. 19B.
  • the electric field intensity pattern of FIG. 19B shows that the electric fields of the combined electromagnetic waves are strongest in a center region of the aperture 1903 and weaker in the outer regions.
  • the wave mode of the electromagnetic waves propagating in the dielectric antenna 1901 is a hybrid wave mode (e.g., HE11)
  • the leakage of the electromagnetic waves at the external surfaces 1907 is reduced or in some instances eliminated.
  • the dielectric antenna 1901 is constructed of a solid dielectric material having no physical opening
  • the front or operating face of the dielectric antenna 1901 from which free space wireless signals are radiated or received will be referred to as the aperture 1903 of the dielectric antenna 1901 even though in some prior art systems the term aperture may be used to describe an opening of an antenna that radiates or receives free space wireless signals.
  • the far- field antenna gain pattern depicted in FIG. 19B can be widened by decreasing the operating frequency of the combined electromagnetic wave from a nominal frequency.
  • the gain pattern can be narrowed by increasing the operating frequency of the combined electromagnetic wave from the nominal frequency.
  • a width of a beam of wireless signals emitted by the aperture 1903 can be controlled by configuring the waveguide system 1865' to increase or decrease the operating frequency of the combined electromagnetic wave.
  • the dielectric antenna 1901 of FIG. 19A can also be used for receiving wireless signals, such as free space wireless signals transmitted by either a similar antenna or conventional antenna design.
  • Wireless signals received by the dielectric antenna 1901 at the aperture 1903 induce electromagnetic waves in the dielectric antenna 1901 that propagate towards the feedline 1902.
  • the electromagnetic waves continue to propagate from the feedline 1902 to the junction between the feed point 1902" and an endpoint of the core 1852, and are thereby delivered to the waveguide system 1865' coupled to the cable 1850 as shown in FIG. 18T.
  • the waveguide system 1865' can perform bidirectional communications utilizing the dielectric antenna 1901.
  • the core 1852 of the cable 1850 can be configured to be collinear with the feed point 1902" to avoid a bend shown in FIG. 19A.
  • a collinear configuration can reduce an alteration in the propagation of the electromagnetic due to the bend in cable 1850.
  • the lens 1912 can comprise a dielectric material having a first dielectric constant that is substantially similar or equal to a second dielectric constant of the dielectric antenna 1901. In other embodiments, the lens 1912 can comprise a dielectric material having a first dielectric constant that differs from a second dielectric constant of the dielectric antenna 1901. In either of these embodiments, the shape of the lens 1912 can be chosen or formed so as to equalize the delays of the various electromagnetic waves propagating at different points in the dielectric antenna 1901. In one embodiment, the lens 1912 can be an integral part of the dielectric antenna 1901 as depicted in the top diagram of FIG. 19C and in particular, the lens and dielectric antenna 1901 can be molded, machined or otherwise formed from a single piece of dielectric material.
  • the lens 1912 can be an assembly component of the dielectric antenna 1901 as depicted in the bottom diagram of FIG. 19C, which can be attached by way of an adhesive material, brackets on the outer edges, or other suitable attachment techniques.
  • the lens 1912 can have a convex structure as shown in FIG. 19C which is adapted to adjust a propagation of electromagnetic waves in the dielectric antenna 1901. While a round lens and conical dielectric antenna configuration is shown, other shapes include pyramidal shapes, elliptical shapes and other geometric shapes can likewise be implemented.
  • the curvature of the lens 1912 can be chosen in manner that reduces phase differences between near-field wireless signals generated by the aperture 1903 of the dielectric antenna 1901.
  • the lens 1912 accomplishes this by applying location- dependent delays to propagating electromagnetic waves. Because of the curvature of the lens 1912, the delays differ depending on where the electromagnetic waves emanate from at the aperture 1903. For example, electromagnetic waves propagating by way of a center axis 1905 of the dielectric antenna 1901 will experience more delay through the lens 1912 than electromagnetic waves propagating radially away from the center axis 1905. Electromagnetic waves propagating towards, for example, the outer edges of the aperture 1903 will experience minimal or no delay through the lens.
  • Propagation delay increases as the electromagnetic waves get close to the center axis 1905. Accordingly, a curvature of the lens 1912 can be configured so that near-field wireless signals have substantially similar phases. By reducing differences between phases of the near-field wireless signals, a width of far-field signals generated by the dielectric antenna 1901 is reduced, which in turn increases the intensity of the far-field wireless signals within the width of the main lobe as shown by the far- field intensity plot shown in FIG. 19D, producing a relatively narrow beam pattern with high gain.
  • FIGs. 19E and 19F block diagrams illustrating example, non- limiting embodiments of a dielectric antenna 1901 coupled to a lens 1912 with ridges (or steps) 1914 and corresponding gain and field intensity plots in accordance with various aspects described herein are shown.
  • the lens 1912 can comprise concentric ridges 1914 shown in the side and perspective views of FIG. 19E.
  • Each ridge 1914 can comprise a riser 1916 and a tread 1918.
  • the size of the tread 1918 changes depending on the curvature of the aperture 1903. For example, the tread 1918 at the center of the aperture 1903 can be greater than the tread at the outer edges of the aperture 1903.
  • each riser 1916 can be configured to have a depth representative of a select wavelength factor.
  • a riser 1916 can be configured to have a depth of one-quarter a wavelength of the electromagnetic waves propagating in the dielectric antenna 1901.
  • Such a configuration causes the electromagnetic wave reflected from one riser 1916 to have a phase difference of 180 degrees relative to the electromagnetic wave reflected from an adjacent riser 1916. Consequently, the out of phase electromagnetic waves reflected from the adjacent risers 1916 substantially cancel, thereby reducing reflection and distortion caused thereby. While a particular riser/tread configuration is shown, other configurations with a differing number of risers, differing riser shapes, etc. can likewise be implemented.
  • the lens 1912 with concentric ridges depicted in FIG. 19E may experience less electromagnetic wave reflections than the lens 1912 having the smooth convex surface depicted in FIG. 19C.
  • FIG. 19F depicts the resulting far-field gain plot of the dielectric antenna 1901 of FIG. 19E.
  • FIG. 19G a block diagram illustrating an example, non- limiting embodiment of a dielectric antenna 1901 having an elliptical structure in accordance with various aspects described herein is shown.
  • FIG. 19G depicts a side view, top view, and front view of the dielectric antenna 1901.
  • the elliptical shape is achieved by reducing a height of the dielectric antenna 1901 as shown by reference 1922 and by elongating the dielectric antenna 1901 as shown by reference 1924.
  • the resulting elliptical shape 1926 is shown in the front view depicted by FIG. 19G.
  • the elliptical shape can be formed, via machining, with a mold tool or other suitable construction technique.
  • FIG. 19H a block diagram illustrating an example, non- limiting embodiment of near- field signals 1928 and far- field signals 1930 emitted by the dielectric antenna 1901 of FIG. 19G in accordance with various aspects described herein is shown.
  • the cross section of the near-field beam pattern 1928 mimics the elliptical shape of the aperture 1903 of the dielectric antenna 1901.
  • the cross section of the far-field beam pattern 1930 have a rotational offset (approximately 90 degrees) that results from the elliptical shape of the near- field signals 1928.
  • the offset can be determined by applying a Fourier Transform to the near-field signals 1928.
  • the cross section of the near-field beam pattern 1928 and the cross section of the far-field beam pattern 1930 are shown as nearly the same size in order to demonstrate the rotational effect, the actual size of the far- field beam pattern 1930 may increase with the distance from the dielectric antenna 1901.
  • the elongated shape of the far- field signals 1930 and its orientation can prove useful when aligning a dielectric antenna 1901 in relation to a remotely located receiver configured to receive the far- field signals 1930.
  • the receiver can comprise one or more dielectric antennas coupled to a waveguide system such as described by the subject disclosure.
  • the elongated far-field signals 1930 can increase the likelihood that the remotely located receiver will detect the far- field signals 1930.
  • the elongated far- field signals 1930 can be useful in situations where a dielectric antenna 1901 coupled to a gimbal assembly such as shown in FIG.
  • actuated antenna mount including but not limited to the actuated gimbal mount described in the co-pending application entitled, COMMUNICATION DEVICE AND ANTENNA ASSEMBLY WITH ACTUATED GIMBAL MOUNT, having Attorney Docket no. 2015-0603_7785- 1210, and U.S. Patent Application, Serial No. 14/873,241, filed on October 2, 2015 the contents of which are incorporated herein by reference for any and all purposes.
  • the elongated far- field signals 1930 can be useful in situations where such as gimbal mount only has two degrees of freedom for aligning the dielectric antenna 1901 in the direction of the receiver (e.g., yaw and pitch is adjustable but roll is fixed).
  • the dielectric antenna 1901 of FIGs. 19G and 19H can have an integrated or attachable lens 1912 such as shown in FIGs. 19C and 19E to increase an intensity of the far-fields signals 1930 by reducing phase differences in the near- field signals.
  • a width of far-field wireless signals generated by the dielectric antenna 1901 can be said to be inversely proportional to a number of wavelengths of the electromagnetic waves propagating in the dielectric antenna 1901 that can fit in a surface area of the aperture 1903 of the dielectric antenna 1901.
  • the width of the far-field wireless signals increases (and its intensity decreases) proportionately.
  • the frequency of the electromagnetic waves decreases, the width of the far-field wireless signals increases proportionately.
  • the frequency of the electromagnetic waves supplied to the dielectric antenna 1901 by way of the feedline 1902 can be decreased so that the far-field wireless signals are sufficiently wide to increase a likelihood that the receiver will detect a portion of the far- field wireless signals.
  • the receiver can be configured to perform measurements on the far- field wireless signals. From these measurements the receiver can direct a waveguide system coupled to the dielectric antenna 1901 generating the far- field wireless signals.
  • the receiver can provide instructions to the waveguide system by way of an omnidirectional wireless signal or a tethered interface therebetween.
  • the instructions provided by the receiver can result in the waveguide system controlling actuators in the gimbal assembly coupled to the dielectric antenna 1901 to adjust a direction of the dielectric antenna 1901 to improve its alignment to the receiver.
  • the receiver can also direct the waveguide system to increase a frequency of the electromagnetic waves, which in turn reduces a width of the far-field wireless signals and correspondingly increases its intensity.
  • absorption sheets 1932 constructed from carbon or conductive materials and/or other absorbers can be embedded in the dielectric antenna 1901 as depicted by the perspective and front views shown in FIG. 191.
  • the electromagnetic waves are absorbed.
  • a clearance region 1934 where absorption sheets 1932 are not present will, however, allow the electromagnetic waves to propagate to the aperture 1903 and thereby emit near-field wireless signals having approximately the width of the clearance region 1934.
  • the width of the near- field wireless signals is decreases, while the width of the far-field wireless signals is increased. This property can be useful during the alignment process previously described.
  • the polarity of the electric fields emitted by the electromagnetic waves can be configured to be parallel with the absorption sheets 1932.
  • the remotely located receiver instructs a waveguide system coupled to the dielectric antenna 1901 to direct the dielectric antenna 1901 using the actuators of a gimbal assembly or other actuated mount, it can also instruct the waveguide system to incrementally adjust the alignment of the electric fields of the electromagnetic waves relative to the absorption sheets 1932 as signal measurements performed by the receiver improve. As the alignment improves, eventually waveguide system adjusts the electric fields so that they are orthogonal to the absorption sheets 1932.
  • the electromagnetic waves near the absorption sheets 1932 will no longer be absorbed, and all or substantially all electromagnetic waves will propagate to the aperture 1903. Since the near- field wireless signals now cover all or substantially all of the aperture 1903, the far- field signals will have a narrower width and higher intensity as they are directed to the receiver.
  • the receiver configured to receive the far-field wireless signals can also be configured to utilize a transmitter that can transmit wireless signals directed to the dielectric antenna 1901 utilized by the waveguide system.
  • a receiver will be referred to as a remote system that can receive far-field wireless signals and transmit wireless signals directed to the waveguide system.
  • the waveguide system can be configured to analyze the wireless signals it receives by way of the dielectric antenna 1901 and determine whether a quality of the wireless signals generated by the remote system justifies further adjustments to the far-field signal pattern to improve reception of the far-field wireless signals by the remote system, and/or whether further orientation alignment of the dielectric antenna by way of the gimbal (see FIG.
  • the waveguide system can increase the operating frequency of the electromagnetic waves, which in turn reduces a width of the far-field wireless signals and correspondingly increases its intensity.
  • the gimbal or other actuated mount can be periodically adjusted to maintain an optimal alignment.
  • the waveguide system can perform adjustments to the far-field signal pattern and/or antenna orientation adjustments based on a combination of an analysis of wireless signals generated by the remote system and messages or instructions provided by the remote system that indicate a quality of the far-field signals received by the remote system.
  • FIG. 19J block diagrams of example, non-limiting embodiments of a collar such as a flange 1942 that can be coupled to a dielectric antenna 1901 in accordance with various aspects described herein is shown.
  • the flange can be constructed with metal (e.g., aluminum) dielectric material (e.g., polyethylene and/or foam), or other suitable materials.
  • the flange 1942 can be utilized to align the feed point 1902" (and in some embodiments also the feedline 1902) with a waveguide system 1948 (e.g., a circular waveguide) as shown in FIG. 19K.
  • the flange 1942 can comprise a center hole 1946 for engaging with the feed point 1902".
  • the hole 1946 can be threaded and the feedline 1902 can have a smooth surface.
  • the flange 1942 can engage the feed point 1902' ' (constructed of a dielectric material such as polyethylene) by inserting a portion of the feed point 1902" into the hole 1946 and rotating the flange 1942 to act as a die to form complementary threads on the soft outer surface of the feedline 1902. [000319] Once the feedline 1902 has been threaded by or into the flange 1942, the feed point 1902" and portion of the feedline 1902 extending from the flange 1942 can be shortened or lengthened by rotating the flange 1942 accordingly.
  • the feedline 1902 can be pre-threaded with mating threads for engagement with the flange 1942 for improving the ease of engaging it with the flange 1942.
  • the feedline 1902 can have a smooth surface and the hole 1946 of the flange 1942 can be non-threaded.
  • the hole 1946 can have a diameter that is similar to diameter of the feedline 1902 such as to cause the engagement of the feedline 1902 to be held in place by frictional forces.
  • the flange 1942 can further include threaded holes 1944 accompanied by two or more alignment holes 1947, which can be used to align to complementary alignment pins 1949 of the waveguide system 1948, which in turn assist in aligning holes 1944' of the waveguide system 1948 to the threaded holes 1944 of the flange 1942 (see FIGs. 19K-19L).
  • the flange 1942 and waveguide system 1948 can be secured to each other with threaded screws 1950 resulting in a completed assembly depicted in FIG. 19L.
  • the feed point 1902" of the feedline 1902 can be adjusted inwards or outwards in relation to a port 1945 of the waveguide system 1948 from which electromagnetic waves are exchanged.
  • the adjustment enables the gap 1943 between the feed point 1902" and the port 1945 to be increased or decreased.
  • the adjustment can be used for tuning a coupling interface between the waveguide system 1948 and the feed point 1902" of the feedline 1902.
  • FIG. 19L also shows how the flange 1942 can be used to align the feedline 1902 with coaxially aligned dielectric foam sections 1951 held by a tubular outer jacket 1952.
  • the illustration in FIG. 19L is similar to the transmission medium 1800' illustrated in FIG. 18K.
  • the flange 1942 can be coupled to a waveguide system 1948 as depicted in FIG. 19L.
  • FIG. 19N a block diagram of an example, non-limiting embodiment of a dielectric antenna 190 in accordance with various aspects described herein is shown.
  • FIG. 19N depicts an array of pyramidal- shaped dielectric horn antennas 1901 ', each having a corresponding aperture 1903' .
  • Each antenna of the array of pyramidal- shaped dielectric horn antennas 190 can have a feedline 1902 with a corresponding feed point 1902' ' that couples to each corresponding core 1852 of a plurality of cables 1850.
  • Each cable 1850 can be coupled to a different (or a same) waveguide system 1865' such as shown in FIG. 18T.
  • the array of pyramidal-shaped dielectric horn antennas 1901 ' can be used to transmit wireless signals having a plurality of spatial orientations.
  • An array of pyramidal-shaped dielectric horn antennas 1901 ' covering 360 degrees can enable a one or more waveguide systems 1865' coupled to the antennas to perform omnidirectional communications with other communication devices or antennas of similar type.
  • the bidirectional propagation properties of electromagnetic waves previously described for the dielectric antenna 1901 of FIG. 19A are also applicable for electromagnetic waves propagating from the core 1852 to the feed point 1902" guided by the feedline 1902 to the aperture 1903' of the pyramidal-shaped dielectric horn antennas 190 , and in the reverse direction.
  • the array of pyramidal- shaped dielectric horn antennas 190 can be substantially or entirely devoid of conductive external surfaces and internal conductive materials as discussed above.
  • the array of pyramidal- shaped dielectric horn antennas 190 and their corresponding feed points 1902' can be constructed of dielectric-only materials such as polyethylene or polyurethane materials or with only trivial amounts of conductive material that does not significantly alter the radiation pattern of the antenna.
  • each antenna of the array of pyramidal- shaped dielectric horn antennas 1901 ' can have similar gain and electric field intensity maps as shown for the dielectric antenna 1901 in FIG. 19B.
  • Each antenna of the array of pyramidal- shaped dielectric horn antennas 1901 ' can also be used for receiving wireless signals as previously described for the dielectric antenna 1901 of FIG. 19A.
  • a single instance of a pyramidal- shaped dielectric horn antenna can be used.
  • multiple instances of the dielectric antenna 1901 of FIG. 19A can be used in an array configuration similar to the one shown in FIG. 19N.
  • FIG. 190 block diagrams of example, non-limiting embodiments of an array 1976 of dielectric antennas 1901 configurable for steering wireless signals in accordance with various aspects described herein is shown.
  • the array 1976 of dielectric antennas 1901 can be conical shaped antennas 1901 or pyramidal- shaped dielectric antennas 1901 ' .
  • a waveguide system coupled to the array 1976 of dielectric antennas 1901 can be adapted to utilize a circuit 1972 comprising amplifiers 1973 and phase shifters 1974, each pair coupled to one of the dielectric antennas 1901 in the array 1976.
  • the waveguide system can steer far-field wireless signals from left to right (west to east) by incrementally increasing a phase delay of signals supplied to the dielectric antennas 1901.
  • the waveguide system can provide a first signal to the dielectric antennas of column 1 ("CI") having no phase delay.
  • the waveguide system can further provide a second signal to column 2 ("C2"), the second signal comprising the first signal having a first phase delay.
  • the waveguide system can further provide a third signal to the dielectric antennas of column 3 (“C3"), the third signal comprising the second signal having a second phase delay.
  • the waveguide system can provide a fourth signal to the dielectric antennas of column 4 ("C4"), the fourth signal comprising the third signal having a third phase delay.
  • far-field signals can be steered from right to left (east to west) ("C4" to CI), north to south (“Rl” to “R4"), south to north (“R4" to “Rl”), and southwest to northeast (“C1-R4" to "C4-R1").
  • beam steering can also be performed in other directions such as southwest to northeast by configuring the waveguide system to incrementally increase the phase of signals transmitted by the following sequence of antennas: "C1-R4", “C1-R3/C2-R4", “C1-R2/C2-R3/C3-R4", “C1-R1/C2-R2/C3-R3/C4- R4", “C2-R1/C3-R2/C4-R3”, “C3-R1/C4-R2", “C4-R1".
  • beam steering can be performed northeast to southwest, northwest to southeast, southeast to northwest, as well in other directions in three-dimensional space.
  • Beam steering can be used, among other things, for aligning the array 1976 of dielectric antennas 1901 with a remote receiver and/or for directivity of signals to mobile communication devices.
  • a phased array 1976 of dielectric antennas 1901 can also be used to circumvent the use of the gimbal assembly of FIG. 19M or other actuated mount. While the foregoing has described beam steering controlled by phase delays, gain and phase adjustment can likewise be applied to the dielectric antennas 1901 of the phased array 1976 in a similar fashion to provide additional control and versatility in the formation of a desired beam pattern.
  • FIG. 19P1 depicts a cable 1850 such as described earlier, which includes a transmission core 1852.
  • the transmission core 1852 can comprise a dielectric core 1802, an insulated conductor 1825, a bare conductor 1832, a core 1842, or a hollow core 1842' as depicted in the transmission mediums 1800, 1820, 1830, 1836, 1841 and/or 1843 of FIGs. 18A-18D, and 18F-18H, respectively.
  • the cable 1850 can further include a shell (such as a dielectric shell) covered by an outer jacket such as shown in FIGs. 18A-18C.
  • the outer jacket can be conductorless (e.g., polyethylene or equivalent).
  • the outer jacket can be a conductive shield which can reduce leakage of the electromagnetic waves propagating along the transmission core 1852.
  • one end of the transmission core 1852 can be coupled to a flange 1942 as previously described in relation to FIGs. 19J-19L.
  • the flange 1942 can enable the transmission core 1852 of the cable 1850 to be aligned with a feed point 1902 of the dielectric antenna 1901.
  • the feed point 1902 can be constructed of the same material as the transmission core 1852.
  • the transmission core 1852 can comprise a dielectric core, and the feed point 1902 can comprise a dielectric material also.
  • the dielectric constants of the transmission core 1852 and the feed point 1902 can be similar or can differ by a controlled amount.
  • the difference in dielectric constants can be controlled to tune the interface between the transmission core 1852 and the feed point 1902 for the exchange of electromagnetic waves propagating therebetween.
  • the transmission core 1852 may have a different construction than the feed point 1902.
  • the transmission core 1852 can comprise an insulated conductor, while the feed point 1902 comprises a dielectric material devoid of conductive materials.
  • the transmission core 1852 can be coupled to the flange 1942 via a center hole 1946, although in other embodiments it will be appreciated that such a hole could be off-centered as well.
  • the hole 1946 can be threaded and the transmission core 1852 can have a smooth surface.
  • the flange 1942 can engage the transmission core 1852 by inserting a portion of the transmission core 1852 into the hole 1946 and rotating the flange 1942 to act as a die to form complementary threads on the outer surface of the transmission core 1852.
  • the portion of the transmission core 1852 extending from the flange 1942 can be shortened or lengthened by rotating the flange 1942 accordingly.
  • the transmission core 1852 can be pre-threaded with mating threads for engagement with the hole 1946 of the flange 1942 for improving the ease of engaging the transmission core 1852 with the flange 1942.
  • the transmission core 1852 can have a smooth surface and the hole 1946 of the flange 1942 can be non-threaded.
  • the hole 1946 can have a diameter that is similar to the diameter of the transmission core 1852 such as to cause the engagement of the transmission core 1852 to be held in place by frictional forces. It will be appreciated that there can be several other ways of engaging the transmission core 1852 with the flange 1942, including various clips, fusion, compression fittings, and the like.
  • the feed point 1902 of the dielectric antenna 1901 can be engaged with the other side of the hole 1946 of the flange 1942 in the same manner as described for transmission core 1852.
  • a gap 1943 can exist between the transmission core 1852 and the feed point 1902.
  • the gap 1943 can be adjusted in an embodiment by rotating the feed point 1902 while the transmission core 1852 is held in place or vice-versa.
  • the ends of the transmission core 1852 and the feed point 1902 engaged with the flange 1942 can be adjusted so that they touch, thereby removing the gap 1943.
  • the ends of the transmission core 1852 or the feed point 1902 engaged with the flange 1942 can intentionally be adjusted to create a specific gap size.
  • the adjustability of the gap 1943 can provide another degree of freedom to tune the interface between the transmission core 1852 and the feed point 1902.
  • an opposite end of the transmission core 1852 of cable 1850 can be coupled to a waveguide device such as depicted in FIGs. 18S and 18T utilizing another flange 1942 and similar coupling techniques.
  • the waveguide device can be used for transmitting and receiving electromagnetic waves along the transmission core 1852.
  • the electromagnetic waves can propagate within the transmission core 1852, on an outer surface of the transmission core 1852, or partly within the transmission core 1852 and the outer surface of the transmission core 1852.
  • the signals generated thereby induce electromagnetic waves that propagate along the transmission core 1852 and transition to the feed point 1902 at the junction therebetween.
  • the electromagnetic waves then propagate from the feed point 1902 into the dielectric antenna 1901 becoming wireless signals at the aperture 1903 of the dielectric antenna 1901.
  • a frame 1982 can be used to surround all or at least a substantial portion of the outer surfaces of the dielectric antenna 1901 (except the aperture 1903) to improve transmission or reception of and/or reduce leakage of the electromagnetic waves as they propagate towards the aperture 1903.
  • a portion 1984 of the frame 1982 can extend to the feed point 1902 as shown in FIG. 19P2 to prevent leakage on the outer surface of the feed point 1902.
  • the frame 1982 for example, can be constructed of materials (e.g., conductive or carbon materials) that reduce leakage of the
  • the shape of the frame 1982 can vary based on a shape of the dielectric antenna 1901.
  • the frame 1852 can have a flared straight- surface shape as shown in FIGs. 19P1-19P4.
  • the frame 1852 can have a flared parabolic- surface shape as shown in FIGs. 19P5-19P8. It will be appreciated that the frame 1852 can have other shapes.
  • the aperture 1903 can be of different shapes and sizes.
  • the aperture 1903 can utilize a lens having a convex structure 1983 of various dimensions as shown in FIGs. 19P1, 19P4, and 19P6-19P8.
  • FIGs. 19P1, 19P4, and 19P6-19P8 In other words,
  • the aperture 1903 can have a flat structure 1985 of various dimensions as shown in FIGs. 19P2 and 19P5.
  • the aperture 1903 can utilize a lens having a pyramidal structure 1986 as shown in FIG. 19P3 and 19Q1.
  • the lens of the aperture 1903 can be an integral part of the dielectric antenna 1901 or can be a component that is coupled to the dielectric antenna 1901 as shown in FIG. 19C.
  • the lens of the aperture 1903 can be constructed with the same or a different material than the dielectric antenna 1901.
  • the aperture 1903 of the dielectric antenna 1901 can extend outside the frame 1982 as shown in FIGs. 19P7-19P8 or can be confined within the frame 1982 as shown in FIGs. 19P1-19P6.
  • the dielectric constant of the lens of the apertures 1903 shown in FIGs. 19P1-19P8 can be configured to be substantially similar or different from that of the dielectric antenna 1901. Additionally, one or more internal portions of the dielectric antenna 1901, such as section 1986 of FIG. 19P4, can have a dielectric constant that differs from that of the remaining portions of the dielectric antenna.
  • the surface of the lens of the apertures 1903 shown in FIGs. 19P1-19P8 can have a smooth surface or can have ridges such as shown in FIG. 19E to reduce surface reflections of the electromagnetic waves as previously described.
  • the frame 1982 can be of different shapes and sizes as shown in the front views depicted in FIGs. 19Q1, 19Q2 and 19Q3.
  • the frame 1982 can have a pyramidal shape as shown in FIG. 19Q1.
  • the frame 1982 can have a circular shape as depicted in FIG. 19Q2.
  • the frame 1982 can have an elliptical shape as depicted in FIG. 19Q3.
  • FIGs. 19P1-19P8 and 19Q1-19Q3 can be combined in whole or in part with each other to create other embodiments contemplated by the subject disclosure. Additionally, the embodiments of FIGs. 19P1-19P8 and 19Q1-19Q3 can be combined with other embodiments of the subject disclosure.
  • the multi- antenna assembly of FIG. 20F can be adapted to utilize any one of the embodiments of FIGs. 19P1-19P8 and 19Q1-19Q3.
  • multiple instances of a multi-antenna assembly adapted to utilize one of the embodiments of FIGs. 19P1-19P8 19Q1-19Q3 can be stacked on top of each other to form a phased array that functions similar to the phased array of FIG. 190.
  • absorption sheets 1932 can be added to the dielectric antenna 1901 as shown in FIG. 191 to control the widths of near- field and far- field signals.
  • FIGs. 20A and 20B block diagrams illustrating example, non- limiting embodiments of the cable 1850 of FIG. 18A used for inducing guided electromagnetic waves on power lines supported by utility poles.
  • a cable 1850 can be coupled at one end to a microwave apparatus that launches guided electromagnetic waves within one or more inner layers of cable 1850 utilizing, for example, the hollow waveguide 1808 shown in FIGs. 18A-18C.
  • the microwave apparatus can utilize a microwave transceiver such as shown in FIG. 10A for transmitting or receiving signals from cable 1850.
  • the guided electromagnetic waves induced in the one or more inner layers of cable 1850 can propagate to an exposed stub of the cable 1850 located inside a horn antenna (shown as a dotted line in FIG. 20A) for radiating the electromagnetic waves via the horn antenna.
  • the radiated signals from the horn antenna in turn can induce guided electromagnetic waves that propagate longitudinally on power line such as a medium voltage (MV) power line.
  • MV medium voltage
  • the microwave apparatus can receive AC power from a low voltage (e.g., 220V) power line.
  • the horn antenna can be replaced with a stub antenna as shown in FIG. 20B to induce guided electromagnetic waves that propagate longitudinally on a power line such as the MV power line or to transmit wireless signals to other antenna system(s).
  • the hollow horn antenna shown in FIG. 20A can be replaced with a solid dielectric antenna such as the dielectric antenna 1901 of FIG. 19 A, or the pyramidal- shaped horn antenna 1901 ' of FIG. 19N.
  • the horn antenna can radiate wireless signals directed to another horn antenna such as the bidirectional horn antennas 2040 shown in FIG. 20C.
  • each horn antenna 2040 can transmit wireless signals to another horn antenna 2040 or receive wireless signals from the other horn antenna 2040 as shown in FIG. 20C.
  • Such an arrangement can be used for performing bidirectional wireless communications between antennas.
  • the horn antennas 2040 can be configured with an electromechanical device to steer a direction of the horn antennas 2040.
  • first and second cables 1850A' and 1850B' can be coupled to the microwave apparatus and to a transformer 2052, respectively, as shown in FIGs. 20A and 20B.
  • the first and second cables 1850A' and 1850B' can be represented by, for example, cable 1820 or cable 1830 of FIGs. 18B and 18C, respectively, each having a conductive core.
  • a first end of the conductive core of the first cable 1850A' can be coupled to the microwave apparatus for propagating guided electromagnetic waves launched therein.
  • a second end of the conductive core of the first cable 1850A' can be coupled to a first end of a conductive coil of the transformer 2052 for receiving the guided electromagnetic waves propagating in the first cable 1850A' and for supplying signals associated therewith to a first end of a second cable 1850B' by way of a second end of the conductive coil of the transformer 2052.
  • a second end of the second cable 1850B' can be coupled to the horn antenna of FIG. 20A or can be exposed as a stub antenna of FIG. 20B for inducing guided electromagnetic waves that propagate longitudinally on the MV power line.
  • a poly-rod structure of antennas 1855 can be formed such as shown in FIG. 18K.
  • Each antenna 1855 can be coupled, for example, to a horn antenna assembly as shown in FIG. 20A or a pie-pan antenna assembly (not shown) for radiating multiple wireless signals.
  • the antennas 1855 can be used as stub antennas in FIG. 20B.
  • the microwave apparatus of FIGs. 20A-20B can be configured to adjust the guided electromagnetic waves to beam steer the wireless signals emitted by the antennas 1855.
  • One or more of the antennas 1855 can also be used for inducing guided electromagnetic waves on a power line.
  • FIG. 20C a block diagram of an example, non-limiting embodiment of a communication network 2000 in accordance with various aspects described herein is shown.
  • the waveguide system 1602 of FIG. 16A can be incorporated into network interface devices (NIDs) such as NIDs 2010 and 2020 of FIG. 20C.
  • NIDs network interface devices
  • a NID having the functionality of waveguide system 1602 can be used to enhance transmission capabilities between customer premises 2002 (enterprise or residential) and a pedestal 2004 (sometimes referred to as a service area interface or SAI).
  • SAI service area interface
  • a central office 2030 can supply one or more fiber cables 2026 to the pedestal 2004.
  • the fiber cables 2026 can provide high-speed full-duplex data services (e.g., 1-100 Gbps or higher) to mini-DSLAMs 2024 located in the pedestal 2004.
  • the data services can be used for transport of voice, internet traffic, media content services (e.g., streaming video services, broadcast TV), and so on.
  • mini- DSLAMs 2024 typically connect to twisted pair phone lines (e.g., twisted pairs included in category 5e or Cat.
  • 5e unshielded twisted-pair (UTP) cables that include an unshielded bundle of twisted pair cables, such as 24 gauge insulated solid wires, surrounded by an outer insulating sheath), which in turn connect to the customer premises 2002 directly.
  • DSL data rates taper off at 100 Mbps or less due in part to the length of legacy twisted pair cables to the customer premises 2002 among other factors.
  • a mini-DSLAM 2024 can be configured to connect to NID 2020 via cable 1850 (which can represent in whole or in part any of the cable embodiments described in relation to FIGs. l8A-18D and 18F-18L singly or in combination). Utilizing cable 1850 between customer premises 2002 and a pedestal 2004, enables NIDs 2010 and 2020 to transmit and receive guide electromagnetic waves for uplink and downlink communications.
  • cable 1850 can be exposed to rain, or can be buried without adversely affecting electromagnetic wave propagation either in a downlink path or an uplink path so long as the electric field profile of such waves in either direction is confined at least in part or entirely within inner layers of cable 1850.
  • downlink communications represents a communication path from the pedestal 2004 to customer premises 2002
  • uplink communications represents a communication path from customer premises 2002 to the pedestal 2004.
  • cable 1850 can also serve the purpose of supplying power to the NID 2010 and 2020 and other equipment of the customer premises 2002 and the pedestal 2004.
  • DSL signals can originate from a DSL modem 2006 (which may have a built-in router and which may provide wireless services such as WiFi to user equipment shown in the customer premises 2002).
  • the DSL signals can be supplied to NID 2010 by a twisted pair phone 2008.
  • the NID 2010 can utilize the integrated waveguide 1602 to launch within cable 1850 guided electromagnetic waves 2014 directed to the pedestal 2004 on an uplink path.
  • DSL signals generated by the mini-DSLAM 2024 can flow through a twisted pair phone line 2022 to NID 2020.
  • the waveguide system 1602 integrated in the NID 2020 can convert the DSL signals, or a portion thereof, from electrical signals to guided electromagnetic waves 2014 that propagate within cable 1850 on the downlink path.
  • the guided electromagnetic waves 2014 on the uplink can be configured to operate at a different carrier frequency and/or a different modulation approach than the guided electromagnetic waves 2014 on the downlink to reduce or avoid interference.
  • the guided electromagnetic waves 2014 are guided by a core section of cable 1850, as previously described, and such waves can be configured to have a field intensity profile that confines the guide electromagnetic waves in whole or in part in the inner layers of cable 1850.
  • the guided electromagnetic waves 2014 are shown outside of cable 1850, the depiction of these waves is for illustration purposes only. For this reason, the guided electromagnetic waves 2014 are drawn with "hash marks" to indicate that they are guided by the inner layers of cable 1850.
  • the integrated waveguide system 1602 of NID 2010 receives the guided electromagnetic waves 2014 generated by NID 2020 and converts them back to DSL signals conforming to the requirements of the DSL modem 2006. The DSL signals are then supplied to the DSL modem 2006 via a set of twisted pair wires of phone line 2008 for processing.
  • the integrated waveguide system 1602 of NID 2020 receives the guided electromagnetic waves 2014 generated by NID 2010 and converts them back to DSL signals conforming to the requirements of the mini- DSLAM 2024.
  • the DSL signals are then supplied to the mini-DSLAM 2024 via a set of twisted pair wires of phone line 2022 for processing.
  • the DSL modem 2006 and the mini-DSLAM 2024 can send and receive DSL signals between themselves on the uplink and downlink at very high speeds (e.g., 1 Gbps to 60 Gbps or more). Consequently, the uplink and downlink paths can in most circumstances exceed the data rate limits of traditional DSL communications over twisted pair phone lines.
  • DSL devices are configured for asymmetric data rates because the downlink path usually supports a higher data rate than the uplink path.
  • cable 1850 can provide much higher speeds both on the downlink and uplink paths.
  • a firmware update a legacy DSL modem 2006 such as shown in FIG. 20C can be configured with higher speeds on both the uplink and downlink paths. Similar firmware updates can be made to the mini-DSLAM 2024 to take advantage of the higher speeds on the uplink and downlink paths.
  • NIDs 2010 and 2020 Since the interfaces to the DSL modem 2006 and mini-DSLAM 2024 remain as traditional twisted pair phone lines, no hardware change is necessary for a legacy DSL modem or legacy mini-DSLAM other than firmware changes and the addition of the NIDs 2010 and 2020 to perform the conversion from DSL signals to guided electromagnetic waves 2014 and vice-versa.
  • the use of NIDs enables a reuse of legacy modems 2006 and mini-DSLAMs 2024, which in turn can substantially reduce installation costs and system upgrades.
  • updated versions of mini-DSLAMs and DSL modems can be configured with integrated waveguide systems to perform the functions described above, thereby eliminating the need for NIDs 2010 and 2020 with integrated waveguide systems.
  • an updated version of modem 2006 and updated version of mini-DSLAM 2024 would connect directly to cable 1850 and communicate via bidirectional guided electromagnetic wave transmissions, thereby averting a need for transmission or reception of DSL signals using twisted pair phone lines 2008 and 2022.
  • NID 2010 can be configured instead to couple to a cable 1850' (similar to cable 1850 of the subject disclosure) that originates from a waveguide 108 on a utility pole 118, and which may be buried in soil before it reaches NID 2010 of the customer premises 2002.
  • Cable 1850' can be used to receive and transmit guided electromagnetic waves 2014' between the NID 2010 and the waveguide 108.
  • Waveguide 108 can connect via waveguide 106, which can be coupled to base station 104.
  • Base station 104 can provide data communication services to customer premises 2002 by way of its connection to central office 2030 over fiber 2026'.
  • FIGs. 20D-20F block diagrams of example, non-limiting embodiments of antenna mounts that can be used in the communication network 2000 of FIG. 20C (or other suitable communication networks) in accordance with various aspects described herein are shown.
  • an antenna mount 2053 can be coupled to a medium voltage power line by way of an inductive power supply that supplies energy to one or more waveguide systems (not shown) integrated in the antenna mount 2053 as depicted in FIG. 20D.
  • the antenna mount 2053 can include an array of dielectric antennas 1901 (e.g., 16 antennas) such as shown by the top and side views depicted in FIG. 20F.
  • the dielectric antennas 1901 shown in FIG. 20F can be small in dimension as illustrated by a picture comparison between groups of dielectric antennas 1901 and a conventional ballpoint pen.
  • a pole mounted antenna 2054 can be used as depicted in FIG. 20D.
  • an antenna mount 2056 can be attached to a pole with an arm assembly as shown in FIG. 20E.
  • an antenna mount 2058 depicted in FIG. 20E, can be placed on a top portion of a pole coupled to a cable 1850 such as the cables as described in the subject disclosure.
  • the array of dielectric antennas 1901 in any of the antenna mounts of FIGs. 20D-20E can include one or more waveguide systems as described in the subject disclosure by way of FIGs. 1-20.
  • the waveguide systems can be configured to perform beam steering with the array of dielectric antennas 1901 (for transmission or reception of wireless signals).
  • each dielectric antenna 1901 can be utilized as a separate sector for receiving and transmitting wireless signals.
  • the one or more waveguide systems integrated in the antenna mounts of FIGs. 20D-20E can be configured to utilize combinations of the dielectric antennas 1901 in a wide range of multi-input multi- output (MEVIO) transmission and reception techniques.
  • MEVIO multi-input multi- output
  • FIGs. 20D-20E can also be configured to apply communication techniques such as SISO, SIMO, MISO, SISO, signal diversity (e.g., frequency, time, space, polarization, or other forms of signal diversity techniques), and so on, with any combination of the dielectric antennas 1901 in any of the antenna mounts of FIGs. 20D-20E.
  • the antenna mounts of FIGs. 20D-20E can be adapted with two or more stacks of the antenna arrays shown in FIG. 20F.
  • FIGs. 21A and 21B describe embodiments for downlink and uplink communications. Method 2100 of FIG.
  • step 2102 electrical signals (e.g., DSL signals) are generated by a DSLAM (e.g., mini-DSLAM 2024 of pedestal 2004 or from central office 2030), which are converted to guided electromagnetic waves 2014 at step 2104 by NID 2020 and which propagate on a transmission medium such as cable 1850 for providing downlink services to the customer premises 2002.
  • the NID 2010 of the customer premises 2002 converts the guided electromagnetic waves 2014 back to electrical signals (e.g., DSL signals) which are supplied at step 2110 to customer premises equipment (CPE) such as DSL modem 2006 over phone line 2008.
  • CPE customer premises equipment
  • power and/or guided electromagnetic waves 2014' can be supplied from a power line 1850' of a utility grid (having an inner waveguide as illustrated in FIGs. 18G or 18H) to NID 2010 as an alternate or additional downlink (and/or uplink) path.
  • the DSL modem 2006 can supply electrical signals (e.g., DSL signals) via phone line 2008 to NID 2010, which in turn at step 2124, converts the DSL signals to guided electromagnetic waves directed to NID 2020 by way of cable 1850.
  • the NID 2020 of the pedestal 2004 or central office 2030
  • power and guided electromagnetic waves 2014' can be supplied from a power line 1850' of a utility grid (having an inner waveguide as illustrated in FIGs. 18G or 18H) to NID 2020 as an alternate or additional uplink (and/or downlink) path.
  • FIG. 21C a flow diagram of an example, non-limiting embodiment of a method 2130 for inducing and receiving electromagnetic waves on a transmission medium is shown.
  • the waveguides 1865 and 1865' of FIGs. 18N - 18T can be configured to generate first electromagnetic waves from a first communication signal (supplied, for example, by a communication device such as a base station), and induce at step 2134 the first electromagnetic waves with "only" a fundamental wave mode at an interface of the transmission medium.
  • the interface can be an outer surface of the transmission medium as depicted in FIGs. 18Q and 18R.
  • the interface can be an inner layer of the transmission medium as depicted in FIGs. 18S and 18T.
  • the waveguides 1865 and 1865' of FIGs. 18N - 18T can be configured to receive second electromagnetic waves at an interface of a same or different transmission medium described in FIG. 21C.
  • the second electromagnetic waves can have "only" a fundamental wave mode.
  • the second electromagnetic waves may have a combination of wave modes such as a fundamental and non-fundamental wave modes.
  • a second communication signal can be generated from the second electromagnetic waves for processing by, for example, a same or different communication device.
  • FIGs. 21C and 21D can be applied to any embodiments described in the subject disclosure.
  • FIG. 21D a flow diagram of an example, non-limiting embodiment of a method 2140 for inducing and receiving electromagnetic waves on a transmission medium is shown.
  • the waveguides 1865 and 1865' of FIGs. 18N - 18W can be configured to generate first electromagnetic waves from a first communication signal (supplied, for example, by a communication device), and induce at step 2144 second electromagnetic waves with "only" a non-fundamental wave mode at an interface of the transmission medium.
  • the interface can be an outer surface of the transmission medium as depicted in FIGs. 18Q and 18R.
  • the interface can be an inner layer of the transmission medium as depicted in FIGs. 18S and 18T.
  • the waveguides 1865 and 1865' of FIGs. 18N - 18W can be configured to receive electromagnetic waves at an interface of a same or different transmission medium described in FIG. 21E.
  • the electromagnetic waves can have "only" a non-fundamental wave mode.
  • the electromagnetic waves may have a combination of wave modes such as a fundamental and non-fundamental wave modes.
  • a second communication signal can be generated from the electromagnetic waves for processing by, for example, a same or different communication device.
  • FIGs. 21E and 21F can be applied to any embodiments described in the subject disclosure.
  • FIG. 21E illustrates a flow diagram of an example, non-limiting embodiment of a method 2150 for radiating signals from a dielectric antenna such as those shown in FIGs. 19A and 19N.
  • Method 2150 can begin with step 2152 where a transmitter such as waveguide system 1865' of FIG. 18T generates first electromagnetic waves including a first communication signal.
  • the first electromagnetic waves in turn induce at step 2153 second electromagnetic waves on a core 1852 of a cable 1850 coupled to a feed point of any of the dielectric antenna described in the subject disclosure.
  • the second electromagnetic waves are received at the feed point at step 2154 and propagate at step 2155 to a proximal portion of the dielectric antenna.
  • the second electromagnetic waves continue to propagate from the proximal portion of the dielectric antenna to an aperture of the antenna and thereby cause at step 2157 wireless signals to be radiated as previously described in relation to FIGs. 19A-19N.
  • FIG. 21F illustrates a flow diagram of an example, non-limiting embodiment of a method 2160 for receiving wireless signals at a dielectric antenna such as the dielectric antennas of FIGs. 19A or 19N.
  • Method 2160 can begin with step 2161 where the aperture of the dielectric antenna receives wireless signals.
  • the wireless signals induce electromagnetic waves that propagate from the aperture to the feed point of the dielectric antenna.
  • the electromagnetic waves once received at the feed point at step 2163, propagate at step 2164 to the core of the cable coupled to the feed point.
  • a receiver such as the waveguide system 1865' of FIG. 18T receives the electromagnetic waves and generates therefrom at step 2166 a second communication signal.
  • Methods 2150 and 2160 can be used to adapt the dielectric antennas of FIGs. 19A, 19C, 19E, 19G-19I, and 19L-190 for bidirectional wireless communications with other dielectric antennas such as the dielectric antennas 2040 shown in FIG. 20C, and/or for performing bidirectional wireless communications with other communication devices such as a portable communication devices (e.g., cell phones, tablets, laptops), wireless communication devices situated in a building (e.g., a residence), and so on.
  • a microwave apparatus such as shown in FIG. 20A can be configured with one or more cables 1850 that couple to a plurality of dielectric antennas 2040 as shown in FIG. 20C.
  • Methods 2150 and 2160 can be further adapted for use with the phased array 1976 of dielectric antennas 1901 of FIG. 190 by applying incremental phase delays to portions of the antennas to steer far-field wireless signals emitted. Methods 2150 and 2160 can also be adapted for adjusting the far-field wireless signals generated by the dielectric antenna 1901 and/or an orientation of the dielectric antenna 1901 utilizing the gimbal depicted in FIG.
  • the methods 2150 and 2160 can be adapted to receive instructions, messages or wireless signals from the remote system to enable the waveguide system receiving such signals by way of its dielectric antenna 1901 to perform adjustments of the far- field signals.
  • FIG. 21G illustrates a flow diagram of an example, non-limiting embodiment of a method 2170 for detecting and mitigating disturbances occurring in a communication network, such as, for example, the system of FIGs. 16A and 16B.
  • Method 2170 can begin with step 2172 where a network element, such as the waveguide system 1602 of FIGs. 16A-16B, can be configured to monitor degradation of guided electromagnetic waves on an outer surface of a transmission medium, such as power line 1610.
  • a signal degradation can be detected according to any number of factors including without limitation, a signal magnitude of the guided electromagnetic waves dropping below a certain magnitude threshold, a signal to noise ratio (SNR) dropping below a certain SNR threshold, a Quality of Service (QoS) dropping below one or more thresholds, a bit error rate (BER) exceeding a certain BER threshold, a packet loss rate (PLR) exceeding a certain PLR threshold, a ratio of reflected electromagnetic waves to forward electromagnetic waves exceeding a certain threshold, an unexpected change or alteration to a wave mode, a spectral change in the guided electromagnetic waves indicating an object or objects are causing a propagation loss or scattering of the guided electromagnetic waves (e.g., water accumulation on an outer surface of the transmission medium, a splice in the transmission medium, a broken tree limb, etc.), or any combinations thereof.
  • SNR signal to noise ratio
  • QoS Quality of Service
  • BER bit error rate
  • PLR packet loss rate
  • a sensing device such as, the disturbance sensor 1604b of FIG. 16A, can be adapted to perform one or more of the above signal measurements and determine thereby whether the electromagnetic waves are experiencing signal degradation.
  • Other sensing devices suitable for performing the above measurements are contemplated by the subject disclosure.
  • the network element can proceed to step 2176 where it can determine which object or objects may be causing the degradation, and once detected, report the detected object(s) to the network management system 1601 of FIGs. 16A-16B.
  • Object detection can be accomplished by spectral analysis or other forms of signal analysis, environmental analysis (e.g., barometric readings, rain detection, etc.), or other suitable techniques for detecting foreign objects that may adversely affect propagation of electromagnetic waves guided by the transmission medium.
  • the network element can be configured to generate spectral data derived from an electromagnetic wave received by the network element. The network element can then compare the spectral data to a plurality of spectral profiles stored in its memory. The plurality of spectral profiles can be pre-stored in a memory of the network element, and can be used to characterize or identify obstructions that may cause a propagation loss or signal degradation when such obstructions are present on an outer surface of the transmission medium.
  • an accumulation of water on an outer surface of a transmission medium may cause a signal degradation in electromagnetic waves guided by the transmission medium that may be identifiable by a spectral profile comprising spectral data that models such an obstruction.
  • the spectral profile can be generated in a controlled environment (such as a laboratory or other suitable testing environment) by collecting and analyzing spectral data generated by test equipment (e.g., a waveguide system with spectrum analysis capabilities) when receiving electromagnetic waves over an outer surface of a transmission medium that has been subjected to water (e.g., simulated rain water).
  • An obstruction such as water can generate a different spectral signature than other obstructions (e.g., a splice between transmission mediums).
  • a unique spectral signature can be used to identify certain obstructions over others.
  • spectral profiles can be generated for characterizing other obstructions such as a fallen tree limb on the transmission medium, a splice, and so on.
  • thresholds can be generated for different metrics such as SNR, BER, PLR, and so on. These thresholds can be chosen by a service provider according to desired performance measures for a communication network that utilizing guided electromagnetic waves for transport of data.
  • Some obstructions may also be detected by other methods. For example, rain water may be detected by a rain detector coupled to a network element, fallen tree limbs may be detected by a vibration detector coupled to the network element, and so on.
  • a network element does not have access to equipment to detect objects that may be causing a degradation of electromagnetic waves, then the network element can skip step 2176 and proceed to step 2178 where it notifies one or more neighboring network elements (e.g., other waveguide system(s) 1602 in a vicinity of the network element) of the detected signal degradation.
  • the network element can resort to a different medium for communicating with neighboring network element(s), such as, for example, wireless communications.
  • the network element can substantially reduce the operating frequency of the guided electromagnetic waves (e.g., from 40 GHz to 1 GHz), or communicate with neighboring network elements utilizing other guided electromagnetic waves operating at a low frequency, such as a control channel (e.g., 1 MHz).
  • a low frequency control channel may be much less susceptible to interference by the object(s) causing the signal degradation at much higher operating frequencies.
  • the network element and neighboring network elements can coordinate a process to adjust the guided electromagnetic waves to mitigate the detected signal degradation.
  • the process can include, for example, a protocol for choosing which of the network elements will perform the adjustments to the electromagnetic waves, the frequency and magnitude of adjustments, and goals to achieve a desired signal quality (e.g., QoS, BER, PLR, SNR, etc.).
  • the network elements can be configured to adjust a polarization of the electrical fields (e-fields) and/or magnetic fields (h-fields) of the electromagnetic waves to attain a radial alignment of the e-fields as shown in FIG. 21H.
  • FIG. 21H presents a block diagram 2101 illustrating an example, non-limiting embodiment of an alignment of e-fields of an electromagnetic wave to mitigate propagation losses due to water accumulation on a transmission medium in accordance with various aspects described herein.
  • the longitudinal section of a cable such as an insulated metal cable implementation of transmission medium 125, is presented along with field vectors that illustrate the e-fields associated with guided electromagnetic waves that propagate at 40 GHz. Stronger e-fields are presented by darker field vectors relative to weaker e-fields.
  • an adjustment in polarization can be accomplished by generating a specific wave mode of the electromagnetic waves (e.g., transverse magnetic (TM) mode, transverse electric (TE) mode, transverse electromagnetic (TEM) mode, or a hybrid of a TM mode and TE mode also known as an HE mode).
  • a specific wave mode of the electromagnetic waves e.g., transverse magnetic (TM) mode, transverse electric (TE) mode, transverse electromagnetic (TEM) mode, or a hybrid of a TM mode and TE mode also known as an HE mode.
  • TM transverse magnetic
  • TE transverse electric
  • TEM transverse electromagnetic
  • HE mode transverse electromagnetic
  • e-fields of electromagnetic waves that are tightly bound to an insulation layer such as, Goubau waves (or TM00 waves— see block diagram 2131 of FIG. 21K), will experience higher propagation losses even though the e-fields may be perpendicular (or radially aligned) to the water film because more of the field strength is concentrated in the region of the water.
  • electromagnetic waves with e-fields perpendicular (or approximately perpendicular) to a water film having a higher proportion of the field strength in a region of air (i.e., above the water film) will experience less propagation loss than tightly bound electromagnetic waves having more field strength in the insulating or water layers or electromagnetic waves having e-fields in the direction of propagation within the region of the water film that generate greater losses.
  • FIG. 21H depicts, in a longitudinal view of an insulated conductor, e-field for TM01 electromagnetic waves operating at 40 GHz.
  • FIGs. 211 and 21 J depict cross- sectional views 2111 and 2121, respectively, of the insulated conductor of FIG. 21H illustrating the field strength of e-fields in the direction of propagation of the electromagnetic waves (i.e., e-fields directed out of the page of FIGs. 211 and 21J).
  • the electromagnetic waves shown in FIGs. 211 and 21 J have a TM01 wave mode at 45 GHz and 40 GHz, respectively.
  • FIG. 211 shows that the intensity of the e-fields in the direction of propagation of the electromagnetic waves is high in a region between the outer surface of the insulation and the outer surface of the water film (i.e., the region of the water film).
  • the high intensity is depicted by a light color (the lighter the color the higher the intensity of the e-fields directed out of the page).
  • FIG. 211 illustrates that there is a high concentration of e-fields polarized longitudinally in the region of the water film, which causes high currents in the water film and consequently high propagation losses.
  • electromagnetic waves at 45 GHz having a TM01 wave mode
  • FIG. 21J shows that the intensity of the e-fields in the direction of propagation of the electromagnetic waves is weaker in the region of the water film.
  • the lower intensity is depicted by the darker color in the region of the water film.
  • the lower intensity is a result of the e-fields being polarized mostly perpendicular or radial to the water film.
  • the radially aligned e-fields also are highly concentrated in the region of air as shown in FIG. 21H.
  • electromagnetic waves at 40 GHz having a TM01 wave mode
  • the electromagnetic waves of FIG. 21J exhibit properties more suitable for reducing propagation losses due to a water film or droplets accumulating on an outer surface of an insulated conductor.
  • a network element can be configured to choose from a look-up table at step 2186 a starting point for adjusting electromagnetic waves.
  • entries of the look-up table can be searched for matches to a type of object detected at step 2176 (e.g., rain water).
  • the look-up table can be searched for matches to spectral data derived from the affected electromagnetic wave received by the network elements.
  • Table entries can provide specific parameters for adjusting electromagnetic waves (e.g., frequency, phase, amplitude, wave mode, etc.) to achieve at least a coarse adjustment that achieves similar e-field properties as shown in FIG. 21H.
  • a coarse adjustment can serve to improve the likelihood of converging on a solution that achieves the desirable propagation properties previously discussed in relation to FIGs. 21H and 21J.
  • the network element can determine at step 2184 whether the adjustment has improved signal quality to a desirable target.
  • Step 2184 can be implemented by a cooperative exchange between network elements. For example, suppose the network element at step 2186 generates an adjusted electromagnetic wave according to parameters obtained from the look-up table and transmits the adjusted electromagnetic wave to a neighboring network element.
  • the network element can determine whether the adjustment has improved signal quality by receiving feedback from a neighboring network element receiving the adjusted electromagnetic waves, analyzing the quality of the received waves according to agreed target goals, and providing the results to the network element. Similarly, the network element can test adjusted electromagnetic waves received from neighboring network elements and can provide feedback to the neighboring network elements including the results of the analysis.
  • steps 2182, 2186 and 2184 represent an adjustment and testing process performed by the network element and its neighbor(s).
  • a network element determines that signal quality has not achieved one or more desired parametric targets (e.g., SNR, BER, PLR, etc.)
  • desired parametric targets e.g., SNR, BER, PLR, etc.
  • the network element can be configured to adjust a magnitude, phase, frequency, wave mode and/or other tunable features of the electromagnetic waves incrementally until a target goal is achieved.
  • a network element can be configured with the waveguide system 1865' of FIG. 18W.
  • the network element (and its neighbors) can utilize two or more MMICs 1870 to incrementally adjust one or more operational parameters of the electromagnetic waves to achieve e-fields polarized in a particular direction (e.g., away from the direction of propagation in the region of the water film).
  • the two or more MMICs 1870 can also be configured to incrementally adjust one or more operational parameters of the electromagnetic waves that achieve e-fields having a high concentration in a region of air (outside the obstruction).
  • the iteration process can be a trial-and-error process coordinated between network elements to reduce a time for converging on a solution that improves upstream and downstream communications.
  • one network element can be configured to adjust a magnitude but not a wave mode of the electromagnetic waves, while another network element can be configured to adjust the wave mode and not the magnitude.
  • the number of iterations and combination of adjustments to achieve desirable properties in the electromagnetic waves to mitigate obstructions on an outer surface of a transmission medium can be established by a service provider according to experimentation and/or simulations and programmed into the network elements.
  • the network elements can proceed to step 2188 and resume communications according to the adjusted upstream and downstream electromagnetic waves. While communications take place at step 2188, the network elements can be configured to transmit upstream and downstream test signals based on the original electromagnetic waves to determine if the signal quality of such waves has improved. These test signals can be transmitted at periodic intervals (e.g., once every 30 seconds or other suitable periods).
  • Each network element can, for example, analyze spectral data of the received test signals to determine if they achieve a desirable spectral profile and/or other parametric target (e.g. SNR, BER, PLR, etc.). If the signal quality has not improved or has improved nominally, the network elements can be configured to continue communications at step 2188 utilizing the adjusted upstream and downstream electromagnetic waves.
  • the network element(s) can proceed to step 2192 to restore settings (e.g., original wave mode, original magnitude, original frequency, original phase, original spatial orientation, etc.) that produce the original electromagnetic waves.
  • Signal quality may improve as a result of a removal of the obstruction (e.g., rain water evaporates, field personnel remove a fallen tree limb, etc.).
  • the network elements can initiate communications utilizing the original electromagnetic waves and perform upstream and downstream tests. If the network elements determine at step 2196 from tests performed at step 2194 that signal quality of the original electromagnetic waves is satisfactory, then the network elements can resume communications with the original electromagnetic waves and proceed to step 2172 and subsequent steps as previously described.
  • a successful test can be determined at step 2196 by analyzing test signals according to parametric targets associated with the original electromagnetic waves (e.g., BER, SNR, PLR, etc.). If the tests performed at step 2194 are determined to be unsuccessful at step 2196, the network element(s) can proceed to steps 2182, 2186 and 2184 as previously described. Since a prior adjustment to the upstream and downstream electromagnetic waves may have already been determined successfully, the network element(s) can restore the settings used for the previously adjusted electromagnetic waves. Accordingly, a single iteration of any one of steps 2182, 2186 and 2184 may be sufficient to return to step 2188.
  • parametric targets associated with the original electromagnetic waves e.g., BER, SNR, PLR, etc.
  • restoring the original electromagnetic waves may be desirable if, for example, data throughput when using the original electromagnetic waves is better than data throughput when using the adjusted electromagnetic waves.
  • the network element(s) may instead be configured to continue from step 2188.
  • FIGs. 21H and 21K describe a TM01 wave mode
  • other wave modes e.g., HE waves, TE waves, TEM waves, etc.
  • wave modes may achieve the desired effects shown in FIG. 21H.
  • a wave mode singly or in combination with one or more other wave modes may generate electromagnetic waves with e-field properties that reduce propagation losses as described in relation to FIGs. 21H and 21J.
  • Such wave modes are therefore contemplated as possible wave modes the network elements can be configured to produce.
  • FIG. 21L depicts a block diagram 2141 of an example, non-limiting embodiment of electric fields of a hybrid wave in accordance with various aspects described herein.
  • Waves having an HE mode have linearly polarized e-fields which point away from a direction of propagation of electromagnetic waves and can be perpendicular (or approximately perpendicular) to a region of obstruction (e.g., water film shown in FIGs. 21H-21 J).
  • Waves with an HE mode can be configured to generate e-fields that extend substantially outside of an outer surface of an insulated conductor so that more of the total accumulated field strength is in air. Accordingly, some electromagnetic waves having an HE mode can exhibit properties of a large wave mode with e-fields orthogonal or approximately orthogonal to a region of obstruction. As described earlier, such properties can reduce propagation losses. Electromagnetic waves having an HE mode also have the unique property that they do not have a cutoff frequency (i.e., they can operate near DC) unlike other wave modes which have non-zero cutoff frequencies.
  • FIG. 21M a block diagram 2151 illustrating an example, non- limiting embodiment of electric field characteristics of a hybrid wave versus a Goubau wave in accordance with various aspects described herein is shown.
  • Diagram 2158 shows a distribution of energy between HE 11 mode waves and Goubau waves for an insulated conductor.
  • the energy plots of diagram 2158 assume that the amount of power used to generate the Goubau waves is the same as the HE11 waves (i.e., the area under the energy curves is the same).
  • Goubau waves have a steep drop in power when Goubau waves extend beyond the outer surface of an insulated conductor, while HE 11 waves have a substantially lower drop in power beyond the insulation layer.
  • Diagram 2167 depicts similar Goubau and HE 11 energy curves when a water film is present on the outer surface of the insulator.
  • the difference between the energy curves of diagrams 2158 and 2167 is that the drop in power for the Goubau and the HE11 energy curves begins on an outer edge of the insulator for diagram 2158 and on an outer edge of the water film for diagram 2167.
  • the energy curves diagrams 2158 and 2167 depict the same behavior. That is, the electric fields of Goubau waves are tightly bound to the insulation layer, which when exposed to water results in greater propagation losses than electric fields of HE 11 waves having a higher concentration outside the insulation layer and the water film. These properties are depicted in the HE11 and Goubau diagrams 2168 and 2159, respectively.
  • e-fields of HE11 waves can be configured to extend substantially above a thin water film as shown in block diagram 2169 of FIG. 21N having a greater accumulated field strength in areas in the air when compared to fields in the insulator and a water layer surrounding the outside of the insulator.
  • FIG. 21N depicts a wire having a radius of 1 cm and an insulation radius of 1.5cm with a dielectric constant of 2.25.
  • the e-fields extend outwardly expanding the size of the wave mode.
  • the wave mode expansion can be substantially greater than the diameter of the insulated wire and any obstructions that may be present on the insulated wire.
  • HE11 waves By having e-fields that are perpendicular to a water film and by placing most of its energy outside the water film, HE11 waves have less propagation loss than Goubau waves when a transmission medium is subjected to water or other obstructions.
  • Goubau waves have radial e-fields which are desirable, the waves are tightly coupled to the insulation layer, which results in the e-fields being highly concentrated in the region of an obstruction. Consequently, Goubau waves are still subject to high propagation losses when an obstruction such as a water film is present on the outer surface of an insulated conductor.
  • the waveguide system 2200 can comprise probes 2202 coupled to a slideable or rotatable mechanism 2204 that enables the probes 2202 to be placed at different positions or orientations relative to an outer surface of an insulated conductor 2208.
  • the mechanism 2204 can comprise a coaxial feed 2206 or other coupling that enables transmission of electromagnetic waves by the probes 2202.
  • the coaxial feed 2206 can be placed at a position on the mechanism 2204 so that the path difference between the probes 2202 is one-half a wavelength or some odd integer multiple thereof.
  • electromagnetic waves can be induced on the outer surface of the insulated conductor 2208 having a hybrid mode (such as an HE11 mode).
  • the mechanism 2204 can also be coupled to a motor or other actuator (not shown) for moving the probes 2202 to a desirable position.
  • the waveguide system 2200 can comprise a controller that directs the motor to rotate the probes 2202 (assuming they are rotatable) to a different position (e.g., east and west) to generate electromagnetic waves that have a horizontally polarized HE11 mode as shown in a block diagram 2300 of FIG. 23.
  • the waveguide system 2200 can further comprise a tapered horn 2210 shown in FIG. 22B.
  • the tapered horn 2210 can be coaxially aligned with the insulated conductor 2208.
  • an additional insulation layer (not shown) can placed on the insulated conductor 2208.
  • the additional insulation layer can be similar to the tapered insulation layer 1879 shown in FIGs. 18Q and 18R.
  • the additional insulation layer can have a tapered end that points away from the tapered horn 2210.
  • the tapered insulation layer 1879 can reduce a size of an initial electromagnetic wave launched according to an HE11 mode. As the electromagnetic waves propagate towards the tapered end of the insulation layer, the HE 11 mode expands until it reaches its full size as shown in FIG. 23. In other embodiments, the waveguide system 2200 may not need to use the tapered insulation layer 1879.
  • FIG. 23 illustrates that HE11 mode waves can be used to mitigate obstructions such as rain water.
  • rain water has caused a water film to surround an outer surface of the insulated conductor 2208 as shown in FIG. 23.
  • water droplets have collected at the bottom of the insulated conductor 2208.
  • the water film occupies a small fraction of the total HE11 wave.
  • the water droplets are in a least- intense area of the HE11 waves reducing losses caused by the droplets. Consequently, the HE11 waves experience much lower propagation losses than Goubau waves or waves having a mode that is tightly coupled to the insulated conductor 2208 and thus greater energy in the areas occupied by the water.
  • the waveguide system 2200 of FIGs. 22A-22B can be replaced with other waveguide systems of the subject disclosure capable of generating electromagnetic waves having an HE mode.
  • the waveguide system 1865' of FIG. 18W can be configured to generate electromagnetic waves having an HE mode.
  • two or more MMICs 1870 of the waveguide system 1865' can be configured to generate electromagnetic waves of opposite phase to generate polarized e- fields such as those present in an HE mode.
  • different pairs of MMICs 1870 can be selected to generate HE waves that are polarized at different spatial positions (e.g., north and south, west and east, northwest and southeast, northeast and southeast, or other sub-fractional coordinates).
  • the waveguide systems of FIGs. 18N-18W can be configured to launch electromagnetic waves having an HE mode onto the core 1852 of one or more embodiments of cable 1850 suitable for propagating HE mode waves.
  • HE waves can have desirable characteristics for mitigating obstructions on a transmission medium
  • certain wave modes having a cutoff frequency e.g., TE modes, TM modes, TEM modes or combinations thereof
  • Method 2070 can be adapted, for example, to generate such wave modes from a look-up table at step 2086.
  • Wave modes having a cutoff frequency that exhibit, for example, a wave mode larger than the obstruction and polarized e-fields perpendicular (or approximately perpendicular) to the obstruction can be determined by experimentation and/or simulation.
  • parameters e.g., magnitude, phase, frequency, wave mode(s), spatial positioning, etc.
  • the parametric results for each wave can be stored in a look-up table in a memory of a waveguide system.
  • wave modes with cutoff frequencies exhibiting properties that reduce propagation losses can also be generated iteratively by any of the search algorithms previously described in the process of steps 2082-2084.
  • FIG. 24 illustrates a flow diagram of an example, non-limiting embodiment of a method 2400 for sending and receiving electromagnetic waves.
  • Method 2400 can be adapted for the waveguides 2522 shown in FIGs. 25A through 25C.
  • Method 2400 can begin at step 2402 where a generator generates a first electromagnetic wave.
  • a waveguide guides the first electromagnetic wave to an interface of a transmission medium, which in turn induces at step 2406 a second electromagnetic wave at the interface of the transmission medium.
  • Steps 2402-2406 can be applied to the waveguides 2522 of FIGs. 25A, 25B and 25C.
  • the generator can be an MMIC 1870 or slot 1863 as shown in FIGs. 18N through 18W.
  • the generator is assumed to be an MMIC 2524 positioned within the waveguide 2522 as shown in FIGs. 25A through 25C.
  • FIGs. 25A through 25C illustrate in a longitudinal view of cylindrical waveguides 2522, the waveguides 2522 can be adapted to other structural shapes (e.g., square, rectangular, etc.).
  • the waveguide 2522 covers a first region 2506 of a core 2528. Within the first region 2506, waveguide 2522 has an outer surface 2522A and an inner surface 2523.
  • the inner surface 2523 of the waveguide 2522 can be constructed from a metallic material, carbon, or other material that reflects electromagnetic waves and thereby enables the waveguide 2522 to be configured at step 2404 to guide the first electromagnetic wave 2502 towards the core 2528.
  • the core 2528 can comprise a dielectric core (as described in the subject disclosure) that extends to the inner surface 2523 of the waveguide 2522.
  • the dielectric core can be surrounded by cladding (such as shown in FIG. 18 A), whereby the cladding extends to the inner surface 2523 of the waveguide 2522.
  • the core 2528 can comprise an insulated conductor, where the insulation extends to the inner surface 2523 of the waveguide 2522.
  • the insulated conductor can be a power line, a coaxial cable, or other types of insulated conductors.
  • the core 2528 comprises an interface 2526 for receiving the first electromagnetic wave 2502.
  • the interface 2526 of the core 2528 can be configured to reduce reflections of the first electromagnetic wave 2502.
  • the interface 2526 can be a tapered structure to reduce reflections of the first electromagnetic wave 2502 from a surface of the core 2528.
  • Other structures can be used for the interface 2526.
  • the interface 2526 can be partially tapered with a rounded point. Accordingly, any structure, configuration, or adaptation of the interface 2526 that can reduced reflections of the first electromagnetic wave 2502 is contemplated by the subject disclosure.
  • the first electromagnetic wave 2502 induces (or otherwise generates) a second electromagnetic wave 2504 that propagates within the core 2528 in the first region 2506 covered by the waveguide 2522.
  • the inner surface 2523 of the waveguide 2522 confines the second electromagnetic wave 2504 within the core 2528.
  • a second region 2508 of the core 2528 is not covered by the waveguide 2522, and is thereby exposed to the environment (e.g., air).
  • the second electromagnetic wave 2504 expands outwardly beginning from the discontinuity between the edge of the waveguide 2522 and the exposed core 2528.
  • the core 2528 can be configured to have a tapered structure 2520. As the second electromagnetic wave 2504 propagates along the tapered structure 2520, the second electromagnetic wave 2504 remains substantially bound to the tapered structure 2520 thereby reducing radiation losses.
  • the tapered structure 2520 ends at a transition from the second region 2508 to a third region 2510.
  • the core has a cylindrical structure 2529 having a diameter equal to the endpoint of the tapered structure 2520 at the juncture between the second region 2508 and the third region 2510.
  • the second electromagnetic wave 2504 experiences a low propagation loss. In one embodiment, this can be accomplished by selecting a diameter of the core 2528 that enables the second electromagnetic wave 2504 to be loosely bound to the outer surface of the core 2528 in the third region 2510.
  • propagation losses of the second electromagnetic wave 2504 can be reduced by configuring the MMICs 2524 to adjust a wave mode, wave length, operating frequency, or other operational parameter of the first electromagnetic wave 2502.
  • FIG. 25D illustrates a portion of the waveguide 2522 of FIG. 25A depicted as a cylindrical ring (that does not show the MMICs 2524 or the tapered structure 2526 of FIG. 25A).
  • a first electromagnetic wave is injected at the endpoint of the core 2528 shown in FIG. 25D.
  • the simulation assumes no reflections of the first electromagnetic wave based on an assumption that a tapered structure 2526 (or other suitable structure) is used to reduce such reflections.
  • the simulations are shown as two longitudinal cross-sectional views of the core 2528 covered in part by waveguide section 2523A, and an orthogonal cross-sectional view of the core 2528. In the case of the longitudinal cross-sectional views, one of the illustrations is a blown up view of a portion of the first illustration.
  • electromagnetic wave fields 2532 of the second electromagnetic wave 2504 are confined within the core 2528 by the inner surface 2523 of the waveguide section 2523A.
  • the tapered structure 2520 reduces radiation losses of the electromagnetic wave fields 2532 as it expands over the outer tapered surface of the core 2528.
  • the electromagnetic wave fields 2532 stabilize and thereafter remain loosely coupled to the core 2528 (depicted in the longitudinal and orthogonal cross-sectional views), which reduces propagation losses.
  • FIG. 25B provides an alternative embodiment to the tapered structure 2520 in the second region 2508.
  • the tapered structure 2520 can be avoided by extending the waveguide 2522 into the second region 2508 with a tapered structure 2522B and maintaining the diameter of the core 2528 throughout the first, second and third regions 2506, 2508 and 2510 of the core 2528 as depicted in FIG. 25B.
  • the horn structure 2522B can be used to reduce radiation losses of the second electromagnetic wave 2504 as the second electromagnetic wave 2504 transitions from the first region 2506 to the second region 2508.
  • the core 2528 is exposed to the environment.
  • the core 2528 is configured in the third region 2510 to reduce propagation losses by the second electromagnetic wave 2504.
  • this can be accomplished by selecting a diameter of the core 2528 that enables the second electromagnetic wave 2504 to be loosely bound to the outer surface of the core 2528 in the third region 2510.
  • propagation losses of the second electromagnetic wave 2504 can be reduced by adjusting a wave mode, wave length, operating frequency, or other performance parameter of the first electromagnetic wave 2502.
  • the waveguides 2522 of FIGs. 25 A and 25B can also be adapted for receiving electromagnetic waves.
  • the waveguide 2522 of FIG. 25 A can be adapted to receive an electromagnetic wave at step 2412. This can be represented by an electromagnetic wave 2504 propagating in the third region 2510 from east to west (orientation shown at bottom right of FIGs. 25A-25B) towards the second region 2508.
  • the electromagnetic wave 2504 Upon reaching the second region 2508, the electromagnetic wave 2504 gradually becomes more tightly coupled to the tapered structure 2520.
  • the electromagnetic wave 2504 propagates within the core 2528 confined by the inner surface 2523 of the waveguide 2522.
  • One or more antennas of the MMICs 2524 can be configured to receive the electromagnetic wave 2502 thereby converting the electromagnetic wave 2502 to an electrical signal at step 2414 which can be processed by a processing device (e.g., a receiver circuit and microprocessor).
  • a processing device e.g., a receiver circuit and microprocessor.
  • a remote waveguide system that transmitted the electromagnetic wave 2504 that is received by the waveguide 2522 of FIG.
  • Electromagnetic waves can be received by the waveguide 2522 of FIG. 25B in a similar manner as described above.
  • the waveguide 2522 of FIG. 25B can be adapted to support transmission mediums 2528 that have no endpoints such as shown in FIG. 25C.
  • the waveguide 2522 comprises a chamber 2525 in a first region 2506 of the core 2528.
  • the chamber 2525 creates a gap 2527 between an outer surface 2521 of the core 2528 and the inner surface 2523 of the waveguide 2522.
  • the gap 2527 provides sufficient room for placement of the MMICs 2524 on the inner surface 2523 of the waveguide 2522.
  • the waveguide 2522 can be configured with symmetrical regions: 2508 and 2508', 2510 and 2510', and 2512, and 2512' .
  • the chamber 2525 of the waveguide 2522 has two tapered structures 2522B' and 2522B" . These tapered structures 2522B' and 2522B" enable an electromagnetic wave to gradually enter or exit the chamber 2525 from either direction of the core 2528.
  • the MMICs 2524 can be configured with directional antennas to launch a first electromagnetic wave 2502 directed from east-to-west or from west-to-east in relation to the longitudinal view of the core 2528.
  • the directional antennas of the MMICs 2524 can be configured to receive an electromagnetic waves propagating longitudinally on the core 2528 from east-to-west or from west-to-east.
  • the process for transmitting electromagnetic waves is similar to that described for FIG. 25B depending on whether the directional antennas of the MMICs 2524 are transmitting from east-to-west or from west-to-east.
  • the waveguide 2522 of FIG. 25C can be configured with a mechanism such as one or more hinges that enable splitting the waveguide 2522 into two parts that can be separated.
  • the mechanism can be used to enable installation of the waveguide 2522 onto a core 2528 without endpoints.
  • Other mechanisms for installation of the waveguide 2522 of FIG. 25C on a core 2528 are contemplated by the subject disclosure.
  • the waveguide 2522 can be configured with a slot opening that spans the entire waveguide structure longitudinally.
  • the regions 2522C and 2522C of the waveguide 2522 can be configured so that the inner surface 2523 of the waveguide 2522 is tightly coupled to the outer surface of the core 2528.
  • a tight coupling in the regions 2522C and 2522C can also be applied to a hinged design of the waveguide 2522.
  • the waveguides 2522 shown in FIGs. 25 A, 25B and 25C can be adapted to perform one or more embodiments described in other figures of the subject disclosure. Accordingly, it is contemplated that such embodiments can be applied to the waveguide 2522 of FIGs. 25A, 25B and 25C. Additionally, any adaptations in the subject disclosure of a core can be applied to the waveguide 2522 of FIGs. 25 A, 25B and 25C.
  • the waveguide launchers 2522 of FIGs. 25A-25D and/or other waveguide launchers described and shown in the figures of the subject disclosure can be adapted to generate on a transmission medium having an outer surface composed of, for example, a dielectric material (e.g., insulation, oxidation, or other material with dielectric properties) a single wave mode or combination of wave modes that reduce propagation losses when propagating through a substance, such as a liquid (e.g., water produced by humidity, snow, dew, sleet and/or rain), disposed on the outer surface of the transmission medium.
  • a dielectric material e.g., insulation, oxidation, or other material with dielectric properties
  • a single wave mode or combination of wave modes that reduce propagation losses when propagating through a substance, such as a liquid (e.g., water produced by humidity, snow, dew, sleet and/or rain), disposed on the outer surface of the transmission medium.
  • a liquid e.g., water produced by humidity, snow
  • 25E, 25F, 25G, 25H, 251, 25J, 25K, 25L, 25M, 25N, 250, 25P, 25Q, 25R, 25S and 25T are block diagrams illustrating example, non-limiting embodiments of wave modes (and electric field plots associated therewith) that can be generated on an outer surface of a transmission medium by one or more of the waveguides of the subject disclosure and adaptations thereof.
  • FIG. 25E an illustration is provided that depicts a longitudinal cross-section of a transmission medium 2542.
  • the transmission medium 2542 can comprise a conductor 2543, a dielectric material 2544 (e.g., insulation, oxidation, etc.) disposed on the conductor 2543, and a substance / water film 2545 (or other accumulation of water, liquid, or other substance) disposed on the outer surface of the dielectric material 2544.
  • the transmission medium 2542 can be exposed to a gaseous substance such as atmosphere or air 2546 (or can be located in a vacuum).
  • the respective thicknesses of the conductor 2543, dielectric material 2544, and water film 2545 are not drawn to scale and are therefore meant only to be illustrative. Although not shown in FIG.
  • the conductor 2543 can be a cylindrical conductor e.g., single conductor, braided multi-strand conductor, etc.) surrounded by the dielectric material 2544, and air 2546. To simplify the illustration of the subject disclosure, only a portion of the conductor 2543 near the upper (or first) surface is shown. Furthermore, a symmetrical portion of the dielectric material 2544, water film 2545, and air 2546, which would be located under (or on an opposite/bottom side of) the conductor 2543, in the longitudinal cross section of FIG. 25E, is not shown.
  • gravitational forces can cause the water film 2545 to be concentrated predominantly on a limited portion of the outer surface of the transmission medium 2542 (e.g., on a bottom side of the transmission medium 2542). It is therefore not necessary in the present illustration for the outer surface of the dielectric material to be completely surrounded by the water film 2545. It is further noted that the water film 2545 can be droplets or beads of water rather than a contiguous water film.
  • 25E illustrates an insulated conductor (i.e., conductor 2543 surrounded by the dielectric material 2544), other configurations of the transmission medium 2542 are possible and applicable to the subject disclosure, such as, for example, a transmission medium 2542 composed of a bare wire or other uninsulated conductor or solely of a dielectric material of various structural shapes (e.g., cylindrical structure, rectangular structure, square structure, etc.).
  • FIG. 25E further depicts electric fields of a fundamental transverse magnetic wave mode in the form of TM00 wave mode, sometimes referred to as the Goubau wave mode, launched onto the outer surface of the transmission medium 2542 by one of the waveguide launchers described in the subject disclosure or an adaptation thereof and that travels in a longitudinal direction along the transmission medium 2542 corresponding to the direction of wave propagation shown.
  • TM00 wave mode sometimes referred to as the Goubau wave mode
  • Electromagnetic waves that propagate along a transmission medium via a transverse magnetic (TM) mode have electric fields with both radial rho-field components that extend radially outward from the transmission medium and are perpendicular to the longitudinal direction and longitudinal z-field components that vary as a function of time and distance of propagation that are parallel to the longitudinal direction but no azimuthal phi-field components that are perpendicular to both the longitudinal direction and the radial direction.
  • TM transverse magnetic
  • the TM00 Goubau wave mode produces electric fields with predominant radial rho-field components extending away from the conductor at a high field strength throughout the dielectric in the region 2550.
  • the TM00 Goubau wave mode also produces electric fields with predominant radial rho-field components extending into the conductor at a high field strength throughout the dielectric in the region 2550".
  • electric fields with smaller magnitudes and with predominant longitudinal z-field components are produced. The presence of these electric fields inside the dielectric produces some attenuation, but losses in these regions are insignificant compared with the effects of a thin water film as will be discussed below.
  • FIG. 25E An expanded view 2548 of a small region of the transmission medium 2542 (depicted by a dashed oval) is shown at the bottom right of FIG. 25E.
  • the expanded view 2548 depicts a higher resolution of the electric fields present in the small region of the transmission medium 2542.
  • the expanded view shows electric fields in the dielectric material 2544, the water film 2545 and the air 2546.
  • a substantial portion of the electric fields depicted in region 2547 of the expanded view 2548 has a significant longitudinal component, particularly in the region near the outer surface of the dielectric material 2544 in an area of the water film 2545.
  • FIG. 25F depicts a cross-sectional longitudinal view of simulated electromagnetic waves having a TM00 (Goubau) wave mode, and the effects when such waves propagate on a dry versus wet transmission medium 2542 implemented as a 1 -meter (in length) insulated conductor.
  • TM00 Goubau
  • the simulation assumes a lossless insulator to focus the analysis on a degree of attenuation caused by a 0.1 mm water film.
  • the waves having the TM00 (Goubau) wave mode propagate on the dry transmission medium 2452, the waves experience minimal propagation losses.
  • FIG. 25G illustrates a simulation depicting the magnitude and frequency properties of electromagnetic waves having a TM00 Goubau wave mode that propagate on a dry insulated conductor 2542 versus a wet insulated conductor 2542.
  • the simulation assumes a lossless insulator to focus the analysis on the degree of attenuation caused by a 0.1 mm water film.
  • the plots show that when the transmission medium 2542 is wet, electromagnetic waves having a TM00 Goubau wave mode experience attenuations of approximately 200 dB/M for a range of frequencies of 24- 40 GHz.
  • the plot for the dry insulated conductor 2542 experiences nearly no attenuation in the same range of frequencies.
  • FIGs. 25H and 251 illustrate electric field plots of an electromagnetic wave having TM00 Goubau wave mode with an operating frequency of 3.5 GHz and 10 GHz, respectively.
  • the vertical axis represents field intensity and not distance
  • hash lines have been superimposed on the plots of FIGs. 25H and 251 (as well as the plots of FIGs. 25M-25S) to depict the respective portions of the conductor, insulator and water film relative to their position indicated by the x-axis.
  • the field strengths were calculated in FIGs. 25H and 251 (as well as the plots of FIGs. 25M-25S) based on a condition where no water is present
  • the plot shown in FIG. 25H nevertheless helps explain why a TM00 Goubau wave mode at lower frequencies has low propagation losses when water is present on the outer surface of the dielectric material 2544 in the position shown.
  • rho- fields represent electric fields that extend radially outward from or inward to (perpendicular to the longitudinal axis) the conductor 2543 through the dielectric material 2544, a water film 2545 that may be present, and the air 2546.
  • z-fields are electric fields that are aligned with the dielectric material 2544, the water film 2545, or the air 2546 in a manner that is parallel to the longitudinal axis of the transmission medium 2542.
  • a propagating electromagnetic wave having solely electric field components that are radial or perpendicular to a water film 2545 does not experience a significant loss in field strength as the electromagnetic wave propagates longitudinally (from left-to-right or right-to-left) along the outer surface of the transmission medium 2542.
  • a propagating electromagnetic wave having electric field components that are parallel (or longitudinal), i.e., z-fields aligned with the water film 2545, having a field strength substantially greater than 0 will experience a substantial loss in field strength (i.e., propagation loss) as the electromagnetic wave propagates longitudinally (from left-to-right or right-to-left) along the outer surface of the transmission medium 2542.
  • the z-field component of the electric fields has a field strength that is small relative to the rho-field (radial) component beginning from the outer surface of the dielectric material 2544 and through the position where a water film 2545 could be present as shown in FIG. 25H.
  • the plot 25H indicates the magnitude of the field strength of the rho-field and z-field components, at a point in time when they are at their peak, as a function of radial distance away from the center of a transmission medium. While the field strengths were calculated based on a condition where no water is present, the plot shown in FIG.
  • TM00 Goubau wave mode at lower frequencies has low propagation losses when water is present on the outer surface of the dielectric material 2544 in the position shown.
  • the electric fields have large radial components (e.g., radial rho fields) that are perpendicular to the propagation direction, and conversely relatively small longitudinal components (e.g., z-fields) at the region of the substance / water film, then there can be relatively low propagation losses.
  • an electromagnetic wave having a TM00 Goubau wave mode at 3.5 GHz will not experience a substantial attenuation when the water film 2545 is disposed on the outer surface of the dielectric material 2544 (due to rain, snow, dew, sleet and/or excess humidity). This is not true for all frequencies however, particularly as frequencies approach the millimeter wave range.
  • FIG. 251 depicts a plot of a TM00 wave mode at 10 GHz.
  • the field strength of the z-field component in the region of the water film is relatively large when compared to the rho-field (radial) component. Consequently, propagation losses are very high.
  • FIG. 25J shows that when a water film having a thickness of 0.1mm is present on the external surface of the insulated conductor, a TM00 wave mode at 4 GHz experiences an attenuation of 0.62 dB/M which is significantly lower than a TM00 wave mode at 10 GHz, which experiences an attenuation of 45 dB/M. Accordingly, a TM00 wave mode operating at high frequencies reaching millimeter wave frequencies can experience a substantial propagation loss when a water film is present on the outer surface of a transmission medium.
  • FIG. 25K an illustration is provided that depicts an electromagnetic wave having a TM01 wave mode(e.g., a non-fundamental wave mode) that propagates on the outer surface of the dielectric material 2544.
  • region 2547 illustrates that the electric fields of the electromagnetic wave having a TM01 wave mode have a significant radial rho-field component, and insignificant longitudinal z-field component in the region near the outer surface of the dielectric material 2544 in an area of the water film 2545.
  • TM01 wave modes have a cutoff frequency greater than zero Hertz.
  • the electromagnetic wave having a TM01 wave mode When the electromagnetic wave having a TM01 wave mode is configured by a waveguide launcher of the subject disclosure (an adaptation thereof or other launcher) to operate in a frequency range near its cutoff frequency, a small fraction of power is carried by the dielectric material 2544, while most of the power is concentrated in the air 2546. [000414]
  • the TM01 wave mode produces electric fields in the region 2551 with predominant radial rho-field components extending away from the conductor that reverse in the dielectric 2544 and point inward from the air into the dielectric 2544 at the surface of the dielectric.
  • the TM01 wave mode also produces electric fields in the region 2551" with predominant radial rho-field components extending into the conductor that reverse in the dielectric 2544 and point outward into the air from the dielectric 2544 at the surface of the dielectric. Furthermore, in the region 255 between regions 2551 and 2551", electric fields with predominant longitudinal z-field components are produced within the dielectric layer 2544. As in the case of the TM00 mode, the presence of these electric fields inside the dielectric 2544 produces some attenuation, but losses in these regions may not be significant enough to prevent propagation of a TM01 wave over significant distances.
  • the electric fields of the TM01 wave mode in region 2547 of the water film 2545 are predominantly radial and have relatively insignificant longitudinal components. Consequently, the propagating wave does not experience large propagation losses as the electromagnetic wave with this field structure propagates longitudinally (from left-to-right or right-to-left) along the outer surface of the transmission medium 2542.
  • FIG. 25L depicts a cross-sectional longitudinal view of electromagnetic waves having a TM01 wave mode, and the effects when such waves propagate on a dry versus wet transmission medium 2542 at a millimeter wave frequency or slightly below.
  • the waves experience minimal propagation losses.
  • the electromagnetic wave having a TM00 Goubau wave mode at similar frequencies when the electromagnetic waves having TM01 wave mode propagate in the wet transmission medium 2542, they experience only a modest additional attenuation.
  • Electromagnetic waves having a TM01 wave mode in a millimeter frequency range are therefore much less susceptible to increased propagation losses due to the presence of the water film 2545 than electromagnetic waves having a TM00 Goubau wave mode in this same frequency range.
  • FIG. 25M provides an illustration of an electric field plot of a radial rho-field component and longitudinal z-field component of the electric fields of a TM01 wave mode having an operating frequency at 30.437 GHz, which is 50 MHz above its cutoff frequency.
  • the cutoff frequency is at 30.387 GHz based on a 4mm radius of the conductor 2543 and 4mm thickness of the dielectric material 2544.
  • a higher or lower cutoff frequency for a TM01 wave mode is possible when the dimensions of the conductor 2543 and dielectric material 2544 differ from the present illustration.
  • the plot indicates the magnitude of the field strength of the rho-field and z-field components, at a point in time when they are at their peak, as a function of radial distance away from the center of a transmission medium. While the field strengths were calculated based on a condition where no water is present, the plot shown in FIG. 25M nevertheless helps explain why a TM01 wave mode has low propagation losses when water is present on the outer surface of the dielectric material 2544 in the position shown.
  • electric fields that are substantially perpendicular to the water film 2545 do not experience a significant loss in field strength, while electric fields that are parallel/longitudinal to the outer surface of the dielectric material 2544 within the area of the water film 2545 will experience a substantial loss in field strength as the electromagnetic wave having this field structure propagates along the transmission medium 2542.
  • the longitudinal z-field component of the electric fields can have a field strength that is extremely small relative to the magnitude of the radial field beginning from the outer surface of the dielectric material 2544 and through the water film 2545 as shown in FIG. 25M. Consequently, an electromagnetic wave having a TM01 wave mode at 30.437 GHz will experience much less attenuation than a TM00 Goubau wave mode at a frequency greater than 6 GHz (e.g., at 10 GHz— see FIG. 25J) when a water film 2545 is disposed on the outer surface of the dielectric material 2544 (due to rain, dew, snow, sleet and/or excess humidity).
  • FIG. 25N illustrates a plot depicting the magnitude and frequency properties of electromagnetic waves having a TM01 wave mode that propagate on a dry transmission medium 2542 versus a wet transmission medium 2542.
  • the plots show that when the transmission medium 2542 is wet, electromagnetic waves having a TM01 wave mode experience a modest attenuation when the TM01 wave mode is operating in a frequency range (e.g., 28 GHz - 31 GHz) near its cutoff frequency.
  • the TM00 Goubau wave mode experiences a significant attenuation of 200 dB/M as shown in the plot of FIG. 25G over this same frequency range.
  • the plot of FIG. 25N thus confirms the results of the dry versus wet simulations shown in FIG. 25L.
  • FIGs. 250, 25P, 25Q, 25R and 25S depict other wave modes that can exhibit similar properties like those shown for a TM01 wave mode.
  • FIG. 250 provides an illustration of an electric field plot of a radial rho-field component and a longitudinal z-field component of the electric fields of a TM02 wave mode having an operating frequency at 61.121 GHz, which is 50 MHz above its cutoff frequency.
  • the cutoff frequency can be higher or lower when the dimensions of the conductor 2543 and dielectric material 2544 differ from the present illustration.
  • the plot indicates the magnitude of the field strength of the rho-field and z-field components, at a point in time when they are at their peak, as a function of radial distance away from the center of a transmission medium. While the field strengths were calculated based on a condition where no water is present, the z-field component of the electric fields can have a field strength that is extremely small relative to the magnitude of the radial rho-field beginning from the outer surface of the dielectric material 2544 and through the position that would be occupied by the water film 2545 as shown in FIG. 250. Consequently, an electromagnetic wave exhibiting a TM02 wave mode will experience much less attenuation due to an accumulation of water on an outer surface of a dielectric layer than wave modes with more significant longitudinal z-field components in a position corresponding to the water film.
  • FIG. 25P provides an illustration of an electric field plot of a radial rho-field component, a longitudinal z-field component, and an azimuthal phi-field component of the electric fields of a hybrid wave mode; specifically, an EH 11 wave mode having an operating frequency at 31.153 GHz, which is 50 MHz above its cutoff frequency.
  • the cutoff frequency in the illustration of FIG. 25P can be higher or lower depending on the dimensions of the conductor 2543 and dielectric material 2544.
  • Non-TM wave modes such as hybrid EH wave modes can have azimuthal field components that are perpendicular to the radial rho-field and longitudinal z-field components and that tangentially encircle the circumference of the transmission medium 2542 in a clockwise and/or counterclockwise direction.
  • phi- field (azimuthal) components at the outer surface of the dielectric 2544 can cause significant propagation losses in the presence of a thin film of water 2545.
  • 25P indicates the magnitudes of the field strength of the rho-field, phi-field and z- field components, at a point in time when they are at their peak, as a function of radial distance away from the center of a transmission medium 2542. While the field strengths were calculated based on a condition where no water is present, the z-field and phi-field components of the electric field each have a field strength that is very small relative to the magnitude of the radial field beginning from the outer surface of the dielectric material 2544 and through the position that would be occupied by the water film 2545.
  • an electromagnetic wave having an EH11 wave mode will experience much less attenuation due to an accumulation of water on an outer surface of a dielectric layer than wave modes with more significant longitudinal z-field and phi-field components in a position corresponding to the water film.
  • FIG. 25Q provides an illustration of an electric field plot of a radial rho-field component, a longitudinal z-field component, and an azimuthal phi-field component of the electric fields of a higher order hybrid wave mode; specifically, an EH12 wave mode having an operating frequency at 61.5 GHz, which is 50 MHz above its cutoff frequency.
  • the cutoff frequency can be higher or lower depending on the dimensions of the conductor 2543 and dielectric material 2544.
  • the plot indicates the magnitudes of the field strength of the rho-field, phi-field and z-field components, at a point in time when they are at their peak, as a function of radial distance away from the center of a transmission medium.
  • the z-field and phi-field components of the electric field each have a field strength that is very small relative to the magnitude of the radial field beginning from the outer surface of the dielectric material 2544 and through the position that would be occupied by the water film 2545. Consequently, an electromagnetic wave exhibiting an EH 12 wave mode will experience much less attenuation due to an accumulation of water on an outer surface of a dielectric layer than wave modes with more significant longitudinal z-field and phi-field components in a position corresponding to the water film.
  • FIG. 25R provides an illustration of an electric field plot of a radial rho-field component, a longitudinal z-field component, and an azimuthal phi-field component of the electric fields of a hybrid wave mode; specifically, an HE22 wave mode having an operating frequency at 36.281 GHz, which is 50 MHz above its cutoff frequency.
  • the cutoff frequency can be higher or lower depending on the dimensions of the conductor 2543 and dielectric material 2544.
  • the plot indicates the magnitudes of the field strength of the rho-field, phi-field and z-field components, at a point in time when they are at their peak, as a function of radial distance away from the center of a transmission medium.
  • the z-field and phi-field components of the electric field each have a field strength that is small relative to the magnitude of the radial field beginning from the outer surface of the dielectric material 2544 and through the position that would be occupied by the water film 2545. Consequently, an electromagnetic wave exhibiting an EH22 wave mode will experience much less attenuation due to an accumulation of water on an outer surface of a dielectric layer than wave modes with more significant longitudinal z-field and phi-field components in a position corresponding to the water film.
  • FIG. 25S provides an illustration of an electric field plot of a radial rho-field component, a longitudinal z-field component, and an azimuthal phi-field component of the electric fields of a higher order hybrid wave mode; specifically, an HE23 wave mode having an operating frequency at 64.425 GHz, which is 50 MHz above its cutoff frequency.
  • the cutoff frequency can be higher or lower depending on the dimensions of the conductor 2543 and dielectric material 2544.
  • the plot indicates the magnitudes of the field strength of the rho-field, phi- field and z-field components, at a point in time when they are at their peak, as a function of radial distance away from the center of a transmission medium.
  • the z-field and phi-field components of the electric field each have a field strength that is small relative to the magnitude of the radial field beginning from the outer surface of the dielectric material 2544 and through the position that would be occupied by the water film 2545. Consequently, an electromagnetic wave exhibiting an HE23 wave mode will experience much less attenuation due to an accumulation of water on an outer surface of a dielectric layer than wave modes with more significant longitudinal z-field and phi-field components in a position corresponding to the water film.
  • the waveguide launchers 2522 of FIGs. 25A-25D and/or other waveguide launchers described and shown in the figures of the subject disclosure can be adapted to generate or induce on a transmission medium having an outer surface composed of, for example, a dielectric material (e.g., insulation, oxidation, or other material with dielectric properties) an electromagnetic wave having a TMOm wave mode or an EHlm wave mode (where m > 0), an HE2m wave mode (where m > 1), or any other type of wave mode that exhibits a low field strength for a z-field component (and azimuthal field component if present) in a proximal region above the outer surface of the transmission medium where a water film may be present.
  • a dielectric material e.g., insulation, oxidation, or other material with dielectric properties
  • an electromagnetic wave having a TMOm wave mode or an EHlm wave mode (where m > 0), an HE2m wave mode (where m > 1), or any other type
  • the waveguide launchers of the subject disclosure can be adapted to generate singly, or when suitable, in combination, an electromagnetic wave(s) having the aforementioned wave mode properties to reduce propagation losses when propagating through a substance, such as a liquid (e.g., water produced by humidity and/or rain), disposed on the outer surface of the transmission medium.
  • a substance such as a liquid (e.g., water produced by humidity and/or rain)
  • the transmission medium used to propagate one or more of the aforementioned wave modes can be composed solely of a dielectric material.
  • region 2549 in the expanded view 2548 shows electric field vectors exhibiting the behavior of an eddy (e.g., a circular or whirlpool-like pattern).
  • an eddy e.g., a circular or whirlpool-like pattern
  • certain electric field vectors in region 2549 have longitudinal field components located within the water film 2545, such vectors have a very low field strength and are also substantially less in quantity when compared to the higher strength radial field components located within region 2547 (without including region 2549).
  • the few electric field vectors with non-zero longitudinal components in region 2549 can be a contributing factor to the modest attenuation described earlier in relation to the wet transmission medium 2542 of FIG. 25L.
  • the adverse effects of the electric field vectors in the small eddy region 2549 of FIG. 25K are substantially less than the adverse effects caused by the substantial number of electric field vectors with significant longitudinal components in region 2547 of the TM00 Gaubau wave mode of FIG. 25E, which have a much higher field strength and are within the water film 2545.
  • the electric field vectors in region 2547 of the TM00 Gaubau wave mode cause a much higher propagation loss (as much as 200 dB/M attenuation) at frequencies above 6 GHz as depicted by the wet transmission medium 2542 of FIGs. 25F-25G, 251 and 25J, which is not the case for a TM01 wave mode.
  • FIGs. 25E and 25K are not static in time and space. That is, as an electromagnetic wave propagates in space longitudinally along a transmission medium, the electric fields associated with the electromagnetic wave change when viewed at a static location of the transmission medium as time progresses. Consequently, the electric field plots shown in FIGs. 25H, 251, 25M and 250-25S, are non-static and can expand and contract, as well as, reverse in polarity.
  • the average field strength of the z-field component (and azimuthal field component when present) for a TMOm wave mode and EHlm wave mode (where m > 0), and HE2m wave mode (where m > 1) is substantially lower than that exhibited by z-field component of a TM00 Goubau wave mode above 6 GHz. Consequently, a TMOm wave mode and EHlm wave mode (where m > 0), and HE2m wave mode (where m > 1) experience a much lower propagation loss than a TM00 Goubau wave mode in the range of frequencies above 6 GHz in the presence of a water film 2545.
  • the electric fields of a TM00 Goubau wave mode differ substantially from a TMOm wave mode and EHlm wave mode (where m > 0), and a HE2m wave mode (where m > 1).
  • a TM00 Goubau wave mode and a TM01 wave mode depicted in an orthogonal cross-sectional view of the transmission medium 2542 shown in FIG. 25T.
  • the TM00 Goubau wave mode depicts radial electric fields extending away from the conductor at a high field strength throughout the dielectric. This behavior is depicted in the region 2550 of FIG. 25E at an instance in time and space of the transmission medium 2542.
  • the TM01 wave mode depicts electric fields that extend away from the conductor, decrease substantially in field strength at a midpoint of the dielectric, and reverse in polarity and increase in field strength towards the outer surface of the dielectric. This behavior is depicted in the region 2551 of FIG. 25K at an instance in time and space of the transmission medium 2542.
  • electromagnetic wave modes described in FIGs. 25E-25T and in other sections of the subject disclosure can be launched singly or in combination as multiple wave modes in whole or in part on an outer surface, or embedded within any one of the transmission media described in the subject disclosure (e.g., FIGs. 18A-18L). It is further noted that these electromagnetic wave modes can be converted into wireless signals by any of the antennas described in the subject disclosure (e.g., FIGs. 18M, 19A-19F, 20A-20F) or converted from wireless signals received by an antenna back to one or more electromagnetic wave modes that propagate along one of the aforementioned transmission media.
  • any of the waveguide launchers can be configured to induce or generate on a transmission medium one or more electromagnetic waves having a target field structure or target wave mode that exhibits a spatial alignment of electric fields for purposes of reducing propagation losses and/or signal interference.
  • the waveguide device of FIG. 25U provides a non-limiting illustration of an adaptation of the waveguide launchers of the subject disclosure.
  • FIG. 25U there is illustrated a diagram of an example, non- limiting embodiment of a waveguide device 2522 in accordance with various aspects described herein.
  • the waveguide device 2522 is similar to the waveguide device 2522 shown in FIG. 25C with a few adaptations.
  • the waveguide device 2522 is coupled to a transmission medium 2542 comprising a conductor 2543 and insulation layer 2543, which together form an insulated conductor such as the one shown in drawings of FIGs. 25E and 25K.
  • the waveguide device 2522 can be constructed in two halves, which can be connected together at one longitudinal end with one or more mechanical hinges to enable opening a longitudinal edge at an opposite end of the one or more hinges for placement of the waveguide device 2522 over the transmission medium 2542. Once placed, one or more latches at the longitudinal edge opposite the one or more hinges can be used to secure the waveguide device 2522 to the transmission medium 2542. Other embodiments for coupling the waveguide device 2522 to the transmission medium 2542 can be used and are therefore contemplated by the subject disclosure.
  • the chamber 2525 of the waveguide device 2522 of FIG. 25U includes a dielectric material 2544' .
  • the dielectric material 2544' in the chamber 2525 can have a dielectric constant similar to the dielectric constant of the dielectric layer 2544 of the insulated conductor.
  • a disk 2525' having a center-hole 2525 can be used to divide the chamber 2525 in two halves for transmission or reception of electromagnetic waves.
  • the disk 2525' can be constructed of a material (e.g., carbon, metal or other reflective material) that does not allow electromagnetic waves to progress between the halves of the chamber 2525.
  • the MMICs 2524' can be located inside the dielectric material 2544' of the chamber 2525 as shown in FIG. 25U.
  • FIG. 25U shows an expanded view 2524A'of an MMIC 2524' that includes an antenna 2524B' (such as a monopole antenna, dipole antenna or other antenna) that can be configured to be longitudinally aligned with the outer surface of the dielectric layer 2543 of the transmission medium 2542.
  • the antenna 2524B' can be configured to radiate signals that have a longitudinal electric field directed east or west as will be discussed shortly. It will be appreciated that other antenna structures that can radiate signals that have a longitudinal electric field can be used in place of the dipole antenna 2524B' of FIG. 25U.
  • FIG. 18W shows a transverse cross-sectional view of a cable (such as the transmission medium 2542) surrounded by a waveguide device with 8 MMICs located in positions: north, south, east, west, northeast, northwest, southeast, and southwest.
  • the two MMICs 2524' shown in FIG. 25U can be viewed, for illustration purposes, as MMICs 2524' located in the north and south positions shown in FIG. 18W.
  • the waveguide device 2522 of FIG. 25U can be further configured with MMICs 2524' at western and eastern positions as shown in FIG. 18W.
  • the waveguide device 2522 of FIG. 25U can be further configured with MMICs at northwestern, northeastern, southeastern and southeastern positions as shown in FIG. 18W. Accordingly, the waveguide device 2522 can be configured with more than the 2 MMICs shown in FIG. 25U.
  • FIGs. 25V, 25W, 25X illustrate diagrams of example, non-limiting embodiments of wave modes and electric field plots in accordance with various aspects described herein.
  • FIG. 25V illustrates the electric fields of a TM01 wave mode. The electric fields are illustrated in a transverse cross- sectional view (top) and a longitudinal cross-sectional view (below) of a coaxial cable having a center conductor with an external conductive shield separated by insulation.
  • FIG. 25W illustrates the electric fields of a TM11 wave mode.
  • the electric fields are also illustrated in a transverse cross-sectional view and a longitudinal cross-sectional view of a coaxial cable having a center conductor with an external conductive shield separated by an insulation.
  • FIG. 25X further illustrates the electric fields of a TM21 wave mode.
  • the electric fields are illustrated in a transverse cross-sectional view and a longitudinal cross- sectional view of a coaxial cable having a center conductor with an external conductive shield separated by an insulation.
  • the TM01 wave mode has circularly symmetric electric fields (i.e., electric fields that have the same orientation and intensity at different azimuthal angles), while the transverse cross-sectional views of the TM11 and TM21 wave modes shown in FIGs. 25W-25X, respectively, have non-circularly symmetric electric fields (i.e., electric fields that have different orientations and intensities at different azimuthal angles).
  • the electric fields in the longitudinal cross-sectional views of the TM01, TM11 and TM21 wave modes are substantially similar with the exception that that the electric field structure of the TM11 wave mode has longitudinal electric fields above the conductor and below the conductor that point in opposite longitudinal directions, while the longitudinal electric fields above the conductor and below the conductor for the TM01 and TM21 wave modes point in the same longitudinal direction.
  • the longitudinal cross-sectional views of the coaxial cable of FIGs. 25V, 25W and 25X can be said to have a similar structural arrangement to the longitudinal cross- section of the waveguide device 2522 in region 2506' shown in FIG. 25U.
  • the coaxial cable has a center conductor and a shield separated by insulation
  • region 2506' of the waveguide device 2522 has a center conductor 2543, a dielectric layer 2544, covered by the dielectric material 2544' of the chamber 2525, and shielded by the reflective inner surface 2523 of the waveguide device 2522.
  • the coaxial configuration in region 2506' of the waveguide device 2522 continues in the tapered region 2506" of the waveguide device 2522.
  • the coaxial configuration continues in regions 2508 and 2510 of the waveguide device 2522 with the exception that no dielectric material 2544' is present in these regions other than the dielectric layer 2544 of the transmission medium 2542.
  • the transmission medium 2542 is exposed to the environment (e.g., air) and thus the coaxial configuration is no longer present.
  • the electric field structure of a TM01 wave mode is circularly symmetric in a transverse cross- sectional view of the coaxial cable shown in FIG. 25V. For illustration purposes, it will be assumed that the waveguide device 2522 of FIG.
  • the 4 MMICs 2524' of the waveguide device 2522 in FIG 25U can be configured to launch from a common signal source a TM01 wave mode on the transmission medium 2542. This can be accomplished by configuring the north, south, east and west MMICs 2524' to launch wireless signals with the same phase (polarity).
  • the wireless signals generated by the 4 MMICs 2524' combine via superposition of their respective electric fields in the dielectric material 2544' of the chamber 2525 and the dielectric layer 2544 (since both dielectric materials have similar dielectric constants) to form a TM01 electromagnetic wave 2502' bound to these dielectric materials with the electric field structure shown in longitudinal and transverse views of FIG. 25V.
  • the electromagnetic wave 2502' having the TM01 wave mode in turn propagates toward the tapered structure 2522B of the waveguide device 2522 and thereby becomes an electromagnetic wave 2504' embedded within the dielectric layer 2544 of the transmission medium 2542' in region 2508.
  • the electromagnetic wave 2504' having the TM01 wave mode expands in region 2510 and eventually exits the waveguide device 2522 without change to the TM01 wave mode.
  • the waveguide device 2522 can be configured to launch a TM11 wave mode having a vertical polarity in region 2506'. This can be accomplished by configuring the MMIC 2524' in the northern position to radiate from a signal source a first wireless signal having a phase (polarity) opposite to the phase (polarity) of a second wireless signal radiated from the same signal source by the southern MMIC 2524' . These wireless signals combine via superposition of their respective electric fields to form an electromagnetic wave having a TM11 wave mode (vertically polarized) bound to the dielectric materials 2544' and 2544 with the electric field structures shown in the longitudinal and transverse cross-sectional views shown in FIG. 25W.
  • the waveguide device 2522 can be configured to launch a TM11 wave mode having a horizontal polarity in region 2506' . This can be accomplished by configuring the MMIC 2524' in the eastern position to radiate a first wireless signal having a phase (polarity) opposite to the phase (polarity) of a second wireless signal radiated by the western MMIC 2524'.
  • the TM 11 wave mode remains unaltered.
  • the electromagnetic wave 2504' having the TM11 wave mode exits the waveguide device 2522 in region 2512 the inner wall 2523 is no longer present and the TM11 wave mode becomes a hybrid wave mode, specifically, an EH11 wave mode (vertically polarized, horizontally polarized, or both if two electromagnetic waves are launched in region 2506').
  • the waveguide device 2522 can also be configured to launch a TM21 wave mode in region 2506' .
  • This can be accomplished by configuring the MMIC 2524' in the northern position to radiate from a signal source a first wireless signal having a phase (polarity) that is in phase (polarity) to a second wireless signal generated from the same signal source by the southern MMIC 2524' .
  • the MMIC 2524' in the western position is configured to radiate from the same signal source a third wireless signal that is in phase with a fourth wireless signal radiated from the same signal source by the MMIC 2524' located in the eastern position.
  • the north and south MMICs 2524' generate first and second wireless signals of opposite polarity to the polarity of the third and fourth wireless signals generated by the western and eastern MMICs 2524' .
  • the four wireless signals of alternating polarity combine via superposition of their respective electric fields to form an electromagnetic wave having a TM21 wave mode bound to the dielectric materials 2544' and 2544 with the electric field structures shown in the longitudinal and transverse cross-sectional views shown in FIG. 25X.
  • the electromagnetic wave 2504' exits the waveguide device 2522 it may be transformed to a hybrid wave mode such as, for example, an HE21 wave mode, an EH21 wave mode, or a hybrid wave mode with a different radial mode (e.g., HE2m or EH2m, where m > 1).
  • a hybrid wave mode such as, for example, an HE21 wave mode, an EH21 wave mode, or a hybrid wave mode with a different radial mode (e.g., HE2m or EH2m, where m > 1).
  • FIGs. 25U-25X illustrate several embodiments for launching TM01, EH11, and other hybrid wave modes utilizing the waveguide device 2522 of FIG. 25U.
  • the MMICs 2524' can be further configured in other ways to launch other wave modes (e.g., EH12, HE22, etc.) that have a low intensity z-field component and phi-field component in the electric field structures near the outer surface of a transmission medium 2542, which is useful for mitigating propagation losses due to a substance such as water, droplets or other substances that can cause an attenuation of the electric fields of an electromagnetic wave propagating along the outer surface of the transmission medium 2542.
  • FIG. 25Y illustrates a flow diagram of an example, non-limiting embodiment of a method 2560 for sending and receiving electromagnetic waves.
  • Method 2560 can be applied to waveguides 2522 of FIGs. 25A-25D and/or other waveguide systems or launchers described and shown in the figures of the subject disclosure (e.g., FIGs. 7-14, 18N-18W, 22A-22B and other drawings) for purposes of launching or receiving substantially orthogonal wave modes such as those shown in FIG. 25Z.
  • FIG. 25Z depicts three cross-sectional views of an insulated conductor where a TM00 fundamental wave mode, an HE 11 wave mode with horizontal polarization, and an HE 11 wave mode with vertical polarization, propagates respectively.
  • the wave modes shown in FIG. 25Z can vary over time and is therefore an illustrative representation at a certain instance or snapshot in time.
  • the wave modes shown in FIG. 25Z are orthogonal to each other. That is, a dot product of corresponding electric field vectors between any pair of the wave modes at each point of space and time produces a summation of zero. This property enables the TM00 wave mode, the HE11 wave mode with horizontal polarization, and the HE11 wave mode with vertical polarization to propagate simultaneously along a surface of the same transmission medium in the same frequency band without signal interference.
  • a waveguide system of the subject disclosure can be adapted to receive communication signals from a source (e.g., a base station, a wireless signal transmitted by a mobile or stationary device to an antenna of the waveguide system as described in the subject disclosure, or by way of another communication source.).
  • the communication signals can be, for example, communication signals modulated according to a specific signaling protocol (e.g., LTE, 5G, DOCSIS, DSL, etc.) operating in a native frequency band (e.g., 900 MHz, 1.9 GHz, 2.4 GHz, 5 GHz, etc.), baseband signals, analog signals, other signals, or any combinations thereof.
  • the waveguide system can be adapted to generate or launch on a transmission medium a plurality of electromagnetic waves according to the communication signals by up-converting (or in some instances down-converting) such communication signals to one or more operating frequencies of the plurality of electromagnetic waves.
  • the transmission medium can be an insulated conductor as shown in FIG. 25AA, or an uninsulated conductor that is subject to environmental exposure to oxidation (or other chemical reaction based on environmental exposure) as shown in FIGs. 25AB and 25AC.
  • the transmission medium can be a dielectric material such as a dielectric core described in FIG. 18 A.
  • the waveguide system can be adapted to simultaneously launch at step 2564 a first electromagnetic wave using a TM00 wave mode, a second electromagnetic wave using an HE 11 wave mode with horizontal polarization, and a third electromagnetic wave using an HE11 wave mode with vertical polarization— see FIG. 25Z. Since the first, second and third electromagnetic waves are orthogonal (i.e., non- interfering) they can be launched in the same frequency band without interference or with a small amount of acceptable interference.
  • the combined transmission of three orthogonal electromagnetic wave modes in the same frequency band constitutes a form of wave mode division multiplexing, which provides a means for increasing the information bandwidth by a factor of three.
  • bandwidth can be further increased by configuring the waveguide system to launch a fourth electromagnetic wave using a TM00 wave mode, a fifth electromagnetic wave using an HE 11 wave mode with horizontal polarization, and a sixth electromagnetic wave using an HE 11 wave mode with vertical polarization in a second frequency band that does not overlap with the first frequency band of the first, second and third orthogonal electromagnetic waves.
  • a fourth electromagnetic wave using a TM00 wave mode
  • a fifth electromagnetic wave using an HE 11 wave mode with horizontal polarization
  • a sixth electromagnetic wave using an HE 11 wave mode with vertical polarization in a second frequency band that does not overlap with the first frequency band of the first, second and third orthogonal electromagnetic waves.
  • each of three orthogonal electromagnetic waves in a first frequency band supports 1 GHz of transmission bandwidth.
  • each of three orthogonal electromagnetic waves in a second frequency band also supports 1 GHz of transmission bandwidth.
  • 6 GHz of information bandwidth is possible for conveying communication signals by way of electromagnetic surface waves utilizing these wave modes.
  • the bandwidth can be increased further.
  • the waveguide system can be configured to select from several options for transmitting electromagnetic waves.
  • the waveguide system can be configured at step 2564 to transmit first through third electromagnetic waves using wave mode division multiplexing at a first frequency band (e.g., at 1 GHz), third through fourth electromagnetic waves using wave mode division multiplexing at a second frequency band (e.g., at 2.1 GHz), seventh through ninth electromagnetic waves using wave mode division multiplexing at a third frequency band (e.g., at 3.2 GHz), and so on. Assuming each electromagnetic wave supports 1 GHz of bandwidth, collectively the first through ninth electromagnetic waves can support 9 GHz of bandwidth.
  • the waveguide system can be configured at step 2564 to transmit on the insulated conductor one or more high frequency electromagnetic waves (e.g., millimeter waves).
  • the one or more high frequency electromagnetic waves can be configured in non-overlapping frequencies bands according to one or more corresponding wave modes that are less susceptible to a water film such as a TMOm wave mode and EHlm wave mode (where m > 0), or an HE2m wave mode (where m > 1) as previously described.
  • the waveguide system can instead be configured to transmit one or more high frequency electromagnetic waves in non- overlapping frequency bands according to one or more corresponding wave modes that have longitudinal and/or azimuthal fields near the surface of the transmission medium that may be susceptible to water, but nonetheless exhibit low propagation losses when the transmission medium is dry.
  • a waveguide system can thus be configured to transmit several combinations of wave modes on an insulated conductor (as well as a dielectric-only transmission medium such as a dielectric core) when the insulated conductor is dry.
  • uninsulated conductor in the form of an uninsulated conductor (see FIGs. 25AB-25AC) is used for surface wave transmissions. Further consider that the uninsulated conductor or bare conductor is exposed to an environment subject to various levels of moisture and/or rain (as well as air and atmospheric gases like oxygen). Uninsulated conductors, such as overhead power lines and other uninsulated wires, are often made of aluminum which is sometimes reinforced with steel. Aluminum can react spontaneously with water and/or air to form aluminum oxide. An aluminum oxide layer can be thin (e.g., nano to micrometers in thickness). An aluminum oxide layer has dielectric properties and can therefore serve as a dielectric layer.
  • uninsulated conductors can propagate not only TM00 wave modes, but also other wave modes such as an HE 11 wave mode with horizontal polarization, and an HE 11 wave mode with vertical polarization at high frequencies based at least in part on the thickness of the oxide layer.
  • uninsulated conductors having an environmentally formed dielectric layer such as an oxide layer can be used for transmitting electromagnetic waves using wave mode division multiplexing and frequency division multiplexing.
  • Other electromagnetic waves having a wave mode (with or without a cutoff frequency) that can propagate on an oxide layer are contemplated by the subject disclosure and can be applied to the embodiments described in the subject disclosure.
  • the term "environmentally formed dielectric layer" can represent an uninsulated conductor that is exposed to an environment that is not artificially created in a laboratory or other controlled setting (e.g., bare conductor exposed to air, humidity, rain, etc. on a utility pole or other exposed environment).
  • an environmentally formed dielectric layer can be formed in a controlled setting such as a manufacturing facility that exposes uninsulated conductors to a controlled environment (e.g., controlled humidity, or other gaseous substance) that forms a dielectric layer on the outer surface of the uninsulated conductor.
  • the uninsulated conductor can also be "doped" with particular substances/compounds (e.g., a reactant) that facilitate chemical reactions with other substances/compounds that are either available in a natural environment or in an artificially created laboratory or controlled setting, thereby resulting in the creation of the environmentally formed dielectric layer.
  • substances/compounds e.g., a reactant
  • Wave mode division multiplexing and frequency division multiplexing can prove useful in mitigating obstructions such as water accumulating on an outer surface of a transmission medium.
  • a waveguide system can be configured at step 2566 to determine if an obstruction is present on the transmission medium.
  • a film of water (or water droplets) collected on an outer surface of the transmission medium due to rain, condensation, and/or excess humidity can be one form of an obstruction that can cause propagation losses in electromagnetic waves if not mitigated.
  • a splicing of a transmission medium or other object coupled to the outer surface of the transmission medium can also serve as an obstruction.
  • Obstructions can be detected by a source waveguide system that transmits electromagnetic waves on a transmission medium and measures reflected electromagnetic waves based on these transmissions.
  • the source waveguide system can detect obstructions by receiving communication signals (wireless or electromagnetic waves) from a recipient waveguide system that receives and performs quality metrics on electromagnetic waves transmitted by the source waveguide system.
  • the waveguide system can be configured to identify options to update, modify, or otherwise change the electromagnetic waves being transmitted.
  • TM01 wave mode with a frequency band that starts at 30 GHz having a large bandwidth (e.g., 10 GHz) when the insulated conductor is dry such as shown in FIG. 25N.
  • the illustration in FIG. 25N is based on simulations which may not take into account all possible environmental conditions or properties of a specific insulated conductor. Accordingly, a TM01 wave mode may have a lower bandwidth than shown. For illustration purposes, however, a 10 GHz bandwidth will be assumed for an electromagnetic wave having a TM01 wave mode.
  • a TM01 wave mode has a desirable electric field alignment that is not longitudinal and not azimuthal near the outer surface, it can nonetheless be subject to some signal attenuation which in turn reduces its operating bandwidth when a water film (or droplets) accumulates on the insulated conductor.
  • This attenuation is illustrated in FIG. 25N which shows that an electromagnetic wave having a TM01 wave mode with a bandwidth of approximately 10 GHz (30 to 40 GHz) on a dry insulated conductor drops to a bandwidth of approximately 1 GHz (30 to 31 GHz) when the insulated conductor is wet.
  • the waveguide system can be configured to launch electromagnetic waves at much lower frequencies (e.g., less than 6 GHz) using wave mode division multiplexing and frequency division multiplexing.
  • the waveguide system can be configured to transmit a first set of electromagnetic waves; specifically, a first electromagnetic wave having a TM00 wave mode, a second electromagnetic wave having an HE 11 wave mode with horizontal polarization, and a third electromagnetic wave having an HE 11 wave mode with vertical polarization, each electromagnetic wave having a center frequency at 1 GHz.
  • a useable frequency band from 500 MHz to 1.5 GHz to convey communication signals
  • each electromagnetic wave can provide 1 GHz of bandwidth, and collectively 3 GHz of system bandwidth.
  • the waveguide system is configured to transmit a second set of electromagnetic waves; specifically, a fourth electromagnetic wave having a TM00 wave mode, a fifth electromagnetic wave having an HE 11 wave mode with horizontal polarization, and a sixth electromagnetic wave having an HE 11 wave mode with vertical polarization, each electromagnetic wave having a center frequency at 2.1 GHz.
  • a frequency band from 1.6 GHz to 2.6 GHz with a guard band of 100 MHz between the first and second sets of electromagnetic waves
  • each electromagnetic wave can provide 1 GHz of bandwidth, and collectively 3 GHz of additional bandwidth, thereby now providing up to 6 GHz of system bandwidth.
  • the waveguide system is also configured to transmit a third set of electromagnetic waves; specifically, a seventh electromagnetic wave having a TM00 wave mode, an eighth electromagnetic wave having an HE 11 wave mode with horizontal polarization, and a ninth electromagnetic wave having an HE 11 wave mode with vertical polarization, each electromagnetic wave having a center frequency at 3.2 GHz.
  • a third set of electromagnetic waves specifically, a seventh electromagnetic wave having a TM00 wave mode, an eighth electromagnetic wave having an HE 11 wave mode with horizontal polarization, and a ninth electromagnetic wave having an HE 11 wave mode with vertical polarization, each electromagnetic wave having a center frequency at 3.2 GHz.
  • each electromagnetic wave can provide 1 GHz of bandwidth, and collectively 3 GHz of additional bandwidth, thereby now providing up to 9 GHz of system bandwidth.
  • FIG. 25AD illustrates a process for performing mitigation of a TM01 wave mode subject to an obstruction such as a water film detected at step 2566.
  • 25 AD illustrates a transition from a dry insulated conductor that supports a high bandwidth TM01 wave mode to a wet insulated conductor that supports a lower bandwidth TM01 wave mode that is combined with low frequency TM00 and HE 11 wave modes configured according to wave mode division multiplexing (WMDM) and frequency division multiplexing (FDM) schemes to restore losses in system bandwidth.
  • WMDM wave mode division multiplexing
  • FDM frequency division multiplexing
  • TM00 wave mode with a frequency band that starts at 10 GHz having a large bandwidth (e.g., 10 GHz).
  • transmission medium propagating the 10 GHz TM00 wave mode is exposed to an obstruction such as water.
  • a high frequency TM00 wave mode on an insulated conductor is subject to a substantial amount of signal attenuation (e.g., 45 dB/M at 10 GHz— see FIG. 25J) when a water film (or droplets) accumulates on the outer surface of the insulated conductor.
  • TMOO wave mode propagating on an "uninsulated" conductor.
  • An environmentally exposed uninsulated conductor e.g., aluminum
  • TMOO wave mode propagating on an insulated conductor exhibits a much lower attenuation (e.g., 0.62 dB/M at 4 GHz— see FIG. 25J).
  • a TM00 wave mode operating at less than 6 GHz would similarly exhibit low propagation losses on an uninsulated conductor.
  • the waveguide system can be configured to launch electromagnetic waves having a TM00 wave mode at lower frequencies (e.g., 6 GHz or less) and electromagnetic waves having an HE11 wave mode configured for WMDM and FDM at higher frequencies.
  • a waveguide system can be configured to mitigate the obstruction by transmitting a first electromagnetic wave configured with a TM00 wave mode having a center frequency at 2.75 GHz. Assuming a useable frequency band from 500 MHz to 5.5 GHz to convey communication signals, the electromagnetic waves can provide 5 GHz of system bandwidth.
  • FIG. 25 AF provides an illustration of an electric field plot of an HE 11 wave mode at 200 GHz on a bare conductor with a thin aluminum oxide layer (4 um).
  • the plot indicates the magnitude of the field strength of the rho-field, z-field, and phi-field components, at a point in time when they are at their peak, as a function of radial distance away from the center of a bare conductor.
  • the waveguide system can be configured to transmit a second electromagnetic wave having an HE11 wave mode with horizontal polarization, and a third electromagnetic wave having an HE 11 wave mode with vertical polarization, each electromagnetic wave having a center frequency at 200 GHz (other lower or higher center frequencies can be used).
  • each electromagnetic wave is configured according to an HE vertically polarized wave mode and HE horizontally polarized wave mode, respectively, having a 2.5 GHz bandwidth
  • these waves collectively provide 5 GHz of additional bandwidth.
  • system bandwidth can be restored to 10 GHz.
  • HE wave modes at other center frequencies and bandwidth may be possible depending on the thickness of the oxide layer, the characteristics of the uninsulated conductor, and/or other environmental factors.
  • FIG. 25AE illustrates a process for performing mitigation of a high frequency TM00 wave mode subject to an obstruction such as a water film detected at step 2566.
  • FIG. 25AD illustrates a transition from a dry uninsulated conductor that supports a high bandwidth TM00 wave mode to a wet uninsulated conductor that combines a low frequency TM00 wave mode and high frequency HE11 wave modes configured according to WMDM and FDM schemes to restore losses in system bandwidth.
  • the aforementioned mitigation techniques are non-limiting.
  • the center frequencies described above can differ between systems.
  • the original wave mode used before an obstruction is detected can differ from the illustrations above.
  • an EH11 wave mode can be used singly or in combination with a TM01 wave mode.
  • WMDM and FDM techniques can be used to transmit electromagnetic waves at all times and not just when an obstruction is detected at step 2566.
  • other wave modes that can support WMDM and/or FDM techniques can be applied to and/or combined with the embodiments described in the subject disclosure, and are therefore contemplated by the subject disclosure.
  • the waveguide system can be configured at step 2568 to notify one or more other waveguide systems of the mitigation scheme intended to be used for updating one or more electromagnetic waves prior to executing the update at step 2570.
  • the notification can be sent wirelessly to one or more other waveguide systems utilizing antennas if signal degradation in the electromagnetic waves is too severe. If signal attenuation is tolerable, then the notification can be sent via the affected electromagnetic waves.
  • the waveguide system can be configured to skip step 2568 and perform the mitigation scheme using WMDM and/or FDM at step 2570 without notification.
  • This embodiment can be applied in cases where, for example, other recipient waveguide system(s) know beforehand what kind of mitigation scheme would be used, or the recipient waveguide system(s) are configured to use signal detection techniques to discover the mitigation scheme.
  • the waveguide system can continue to process received communication signals at steps 2562 and 2564 as described earlier using the updated configuration of the electromagnetic waves.
  • the waveguide system can monitor if the obstruction is still present. This determination can be performed by sending test signals (e.g., electromagnetic surface waves in the original wave mode) to other waveguide system(s) and awaiting test results back from the waveguide systems if the situation has improved, and/or by using other obstruction detection techniques such as signal reflection testing based on the sent test signals. Once the obstruction is determined to have been removed (e.g., the transmission medium becomes dry), the waveguide system can proceed to step 2572 and determine that a signal update was performed at step 2568 using WMDM and/or FDM as a mitigation technique.
  • test signals e.g., electromagnetic surface waves in the original wave mode
  • the waveguide system can then be configured to notify recipient waveguide system(s) at step 2568 of the intent to restore transmissions to the original wave mode, or bypass this step and proceed to step 2570 where it restores transmissions to an original wave mode and assumes the recipient waveguide system(s) know the original wave modes and corresponding transmission parameters, or can otherwise detect this change.
  • a waveguide system can also be adapted to receive electromagnetic waves configured for WMDM and/or FDM.
  • WMDM wideband
  • FDM frequency division multiple access
  • a recipient waveguide system can be configured to process the single electromagnetic wave with the TMOl wave mode under normal condition.
  • the source waveguide system transitions to transmitting electromagnetic waves using WMDM and FDM along with a TMOl wave mode with a lower bandwidth on the insulated conductor, as previously described in FIG. 25 AD.
  • the recipient waveguide system would have to process multiple electromagnetic waves of different wave modes.
  • the recipient waveguide system would be configured at step 2582 to selectively process each of the first through ninth electromagnetic waves using WMDM and FDM and the electromagnetic wave using the TMOl wave mode as shown in FIG. 25 AD.
  • the recipient waveguide can be configured to use signal processing techniques to obtain the communication signals that were conveyed by the electromagnetic wave(s) generated by the source waveguide system at step 2564 (and/or step 2570 if an update has occurred).
  • the recipient waveguide system can also determine if the source waveguide system has updated the transmission scheme. The update can be detected from data provided in the electromagnetic waves transmitted by the source waveguide system, or from wireless signals transmitted by the source waveguide system. If there are no updates, the recipient waveguide system can continue to receive and process electromagnetic waves at steps 2582 and 2584 as described before. If, however, an update is detected at step 2586, the recipient waveguide system can proceed to step 2588 to coordinate the update with the source waveguide system and thereafter receive and process updated electromagnetic waves at steps 2582 and 2584 as described before.
  • method 2560 can be used in any communication scheme including simplex and duplex communications between waveguide systems. Accordingly, a source waveguide system that performs an update for transmitting electromagnetic waves according to other wave modes will in turn cause a recipient waveguide system to perform similar steps for return electromagnetic wave transmissions. It will also be appreciated that the aforementioned embodiments associated with method 2560 of FIG. 25Y and the embodiments shown in FIGs. 25Z through 25AE can be combined in whole or in part with other embodiments of the subject disclosure for purposes of mitigating propagation losses caused by an obstruction at or in a vicinity of an outer surface of a transmission medium (e.g., insulated conductor, uninsulated conductor, or any transmission medium having an external dielectric layer).
  • a transmission medium e.g., insulated conductor, uninsulated conductor, or any transmission medium having an external dielectric layer.
  • the obstruction can be a liquid (e.g., water), a solid object disposed on the outer surface of the transmission medium (e.g., ice, snow, a splice, a tree limb, etc.), or any other objects located at or near the outer surface of the transmission medium.
  • a liquid e.g., water
  • a solid object disposed on the outer surface of the transmission medium e.g., ice, snow, a splice, a tree limb, etc.
  • any other objects located at or near the outer surface of the transmission medium e.g., water
  • FIG. 25AG depicts an embodiment for simultaneously transmitting a TM00 wave mode, an HE 11 wave mode with vertical polarization, and an HE 11 wave mode with horizontal polarization as depicted in an instance in time in FIG. 25Z.
  • these orthogonal wave modes can be transmitted with a waveguide launcher having eight (8) MMICs as shown in FIG. 18 located at symmetrical locations (e.g., north, northeast, east, southeast, south, southwest, west, and northwest).
  • the waveguide launcher of FIG. 18R (or FIG.
  • the waveguide launcher can be configured with these 8 MMICs.
  • the waveguide launcher can be configured with a cylindrical sleeve 2523A and tapered dielectric that wraps around the transmission medium (e.g., insulated conductor, uninsulated conductor, or other cable with a dielectric layer such as dielectric core).
  • the housing assembly of the waveguide launcher (not shown) can be configured to include a mechanism (e.g., a hinge) to enable a longitudinal opening of the waveguide launcher for placement and latching around a circumference of a transmission medium.
  • the waveguide launcher can include three transmitters (TX1, TX2, and TX3) coupled to MMICs having various coordinate positions (see FIG. 25 AG and FIG. 18W).
  • the interconnectivity between the transmitters (TX1, TX2, and TX3) and the MMICs can be implemented with a common printed circuit board or other suitable interconnecting technology.
  • the first transmitter (TX1) can be configured to launch a TM00 wave mode
  • the second transmitter (TX2) can be configured to launch an HE 11 vertical polarization wave mode
  • the third transmitter (TX3) can be configured to launch an HE11 horizontal polarization wave mode.
  • a first signal port (shown as "SP1") of the first transmitter (TX1) can be coupled in parallel to each of the 8 MMICs.
  • a second signal port (shown as "SP2") of the first transmitter (TX1) can be coupled to a conductive sleeve 2523 A that is placed on the transmission medium by the waveguide launcher as noted above.
  • the first transmitter (TX1) can be configured to receive a first group of the communication signals described in step 2562 of FIG. 25Y.
  • the first group of communication signals can be frequency- shifted by the first transmitter (TX1) from their native frequencies (if necessary) for an orderly placement of the communication signals in channels of a first electromagnetic wave configured according to the TM00 wave mode.
  • the 8 MMICs coupled to the first transmitter (TX1) can be configured to up-convert (or down-convert) the first group of the communication signals to the same center frequency (e.g., 1 GHz for the first electromagnetic wave as described in relation to FIG. 25 AD). All 8 MMICs would have synchronized reference oscillators that can be phase locked using various synchronization techniques.
  • the 8 MMICs Since the 8 MMICs receive signals from the first signal port of the first transmitter (TX1) based on the reference provided by the second signal port, the 8 MMICs thereby receive signals with the same polarity. Consequently, once these signals have been up-converted (or down-converted) and processed for transmission by the 8 MMICs, one or more antennas of each of the 8 MMICs simultaneously radiates signals with electric fields of the same polarity.
  • MMICs that are opposite in location to each other e.g., MMIC north and MMIC south
  • the field structure shown in FIG. 25Z will radiate inward.
  • the collection of opposing MMICs contribute to the inducement of a first electromagnetic wave having a TM00 wave mode that propagates on a transmission medium with a dielectric layer and can convey the first group of the communication signals to a receiving waveguide system.
  • this transmitter has a first signal port (SP1) coupled to MMICs located in north, northeast and northwest positions, while a second signal port (SP2) of the second transmitter (TX2) is coupled to the MMICs located in south, southeast and southwest positions (see FIG. 18W).
  • the second transmitter (TX2) can be configured to receive a second group of the communication signals described in step 2562 of FIG. 25Y, which differs from the first group of the communication signals received by the first transmitter (TX1).
  • the second group of communication signals can be frequency- shifted by the second transmitter (TX2) from their native frequencies (if necessary) for an orderly placement of the communication signals in channels of a second electromagnetic wave configured according to an HE 11 wave mode with vertical polarization.
  • the 6 MMICs coupled to the second transmitter (TX2) can be configured to up-convert (or down-conversion) the second group of the communication signals to the same center frequency as used for the TM00 wave mode (i.e., 1 GHz as described in relation to FIG. 25 AD). Since a TM00 wave mode is orthogonal to an HE 11 wave mode with vertical polarization, they can share the same center frequency in an overlapping frequency band without interference.
  • the first signal port (SP1) of the second transmitter (TX2) generates signals of opposite polarity to the signals of the second signal port (SP2).
  • the electric field alignment of signals generated by one or more antennas of the northern MMIC will be of opposite polarity to the electric field alignment of signals generated by one or more antennas of the southern MMIC.
  • the electric fields of the north and south MMICs will have an electric field structure that is vertically aligned in the same direction, thereby creating at a certain instance in time a northern field structure like the HE11 wave mode with vertical polarization shown in FIG. 25Z.
  • the HE 11 wave mode will have a southern field structure.
  • these MMICs will generate at a certain instance in time the curved electric field structure shown on the east side of the HE11 wave mode with vertical polarization depicted in FIG. 25Z.
  • these MMICs will generate at a certain instance in time the curved electric field structure shown on the west side of the HE 11 wave mode with vertical polarization depicted in FIG. 25Z.
  • the collection of signals with a directionally aligned field structure contribute to the inducement of a second electromagnetic wave having the HE 11 wave mode with vertical polarization shown in FIG. 25Z.
  • the second electromagnetic wave propagates along the "same" transmission medium as previously described for the first transmitter (TXl). Given the orthogonality of a TM00 wave mode and an HE 11 wave mode with vertical polarization, there will be ideally no interference between the first electromagnetic wave and the second electromagnetic wave. Consequently, the first and second electromagnetic waves having overlapping frequency bands propagating along the same transmission medium can successfully convey the first and second groups of the communication signals to the same (or other) receiving waveguide system.
  • this transmitter has a first signal port (SP1) coupled to MMICs located in east, northeast and southeast positions, while a second signal port (SP2) of the third transmitter (TX3) is coupled to the MMICs located in west, northwest and southwest positions (see FIG. 18W).
  • the third transmitter (TX3) can be configured to receive a third group of the communication signals described in step 2562 of FIG. 25Y, which differs from the first and second groups of the communication signals received by the first transmitter (TXl) and the second transmitter (TX2), respectively.
  • the third group of communication signals can be frequency- shifted by the third transmitter (TX3) from their native frequencies (if necessary) for an orderly placement of the communication signals in channels of a second electromagnetic wave configured according to an HE11 wave mode with horizontal polarization.
  • the 6 MMICs coupled to the third transmitter (TX3) can be configured to up-convert (or down- conversion) the third group of the communication signals to the same center frequency as used for the TM00 wave mode and HE11 wave mode with vertical polarization (i.e., 1 GHz as described in relation to FIG. 25 AD). Since a TM00 wave mode, an HE 11 wave mode with vertical polarization, and an HE 11 wave mode with horizontal polarization are orthogonal, they can share the same center frequency in an overlapping frequency band without interference.
  • the first signal port (SP1) of the third transmitter (TX3) generates signals of opposite polarity to the signals of the second signal port (SP2).
  • the electric field alignment of signals generated by one or more antennas of the eastern MMIC will be of opposite polarity to the electric field alignment of signals generated by one or more antennas of the western MMIC.
  • the electric fields of the east and west MMICs will have an electric field structure that is horizontally aligned in the same direction, thereby creating at a certain instance in time a western field structure like the HE 11 wave mode with horizontal polarization shown in FIG. 25Z.
  • the HE 11 wave mode will have an eastern field structure.
  • these MMICs will generate at a certain instance in time the curved electric field structure shown on the north side of the HE11 wave mode with horizontal polarization depicted in FIG. 25Z.
  • these MMICs will generate at a certain instance in time the curved electric field structure shown on the south side of the HE 11 wave mode with horizontal polarization depicted in FIG. 25Z.
  • a recipient waveguide system can be configured to selectively retrieve the first electromagnetic wave having the TM00 wave mode, the second electromagnetic wave having the HEl 1 wave mode with vertical polarization, and the third electromagnetic wave having the HE 11 wave mode with horizontal polarization. After processing each of these electromagnetic waves, the recipient waveguide system can be further configured to obtain the first, second and third group of the communication signals conveyed by these waves.
  • FIG. 25AH illustrates a block diagram for selectively receiving each of the first, second and third electromagnetic waves.
  • the first electromagnetic wave having the TM00 wave mode can be selectively received by a first receiver (RX1) shown in FIG. 25 AH by taking the difference between the signals received by all 8 MMICs and the signal reference provided by the metal sleeve 2523 A as depicted in the block diagram in FIG. 25AI.
  • the second electromagnetic wave having the HE 11 wave mode with vertical polarization can be selectively received by a second receiver (RX2) shown in FIG. 25AH by taking the difference between the signals received by the MMICs located in north, northeast and northwest positions and the signals received by the MMICs located in south, southeast and southwest positions as depicted in the block diagram in FIG. 25AJ.
  • FIG. 25AL illustrates a simplified functional block diagram of an MMIC.
  • the MMIC can, for example, utilize a mixer coupled to a reference (TX) oscillator that shifts one of the communication signals supplied by one of the signal ports (SPl or SP2) of one of the transmitters (TXl, TX2 or TX3) to a desired center frequency in accordance with the configurations shown in FIG.
  • TX reference
  • the communication signal from SPl is supplied to a transmit path of each of the MMICs (i.e., NE, NW, SE, SW, N, S, E, and W).
  • the communication signal from SPl is supplied to another transmit path of three MMICs (i.e., N, E, and NW).
  • the transmit paths used by MMICs N, E and W for the communication signal supplied by SPl of TX2 are different from the transmit paths used by the MMICs for the communication signal supplied by SPl of TXl.
  • the communication signal from SP2 of TX2 is supplied to another transmit path of three other MMICs (i.e., S, SE, and SW).
  • the transmit paths used by MMICs S, SE and SW for the communication signal supplied by SP2 of TX2 are different from the transmit paths used by the MMICs for the communication signals from SPl of TXl, and SPl of TX2.
  • the communication signal from SPl is supplied to yet another transmit path of three MMICs (i.e., E, NE, and SE).
  • the transmit paths used for MMICs E, NE, and SE for the communication signal from SPl of TX3 are different from the transmit paths used by the MMICs for the communication signals supplied by SPl of TXl, SPl of TX2, and SP2 of TX2.
  • the communication signal from SP2 of TX3 is supplied to another transmit path of three other MMICs (i.e., W, NW, and SW). Again, the transmit paths used by MMICs W, NW, and SW for the communication signal supplied by SP2 of TX3 are different from the transmit paths used by the MMICs for the communication signals from SPl of TXl, SPl of TX2, and SP2 of TX2, and SPl of TX3.
  • the communication signals have been frequency- shifted by the mixer shown in the transmit path, he frequency- shifted signal generated by the mixer can then be filtered by a bandpass filter that removes spurious signals.
  • the output of the bandpass filter in turn can be provided to a power amplifier that couples to an antenna by way of a duplexer for radiating signals in the manner previously described.
  • the duplexer can be used to isolate a transmit path from a receive path.
  • the illustration of FIG. 25AL is intentionally oversimplified to enable ease of illustration.
  • other components such as an impedance matching circuit, phase lock loop, or other suitable components for improving the accuracy and efficiency of the transmission path (and receive path) is contemplated by the subject disclosure.
  • the transmit path can be repeated N times using the same reference oscillator.
  • N can represent an integer associated with the number of instances the MMIC is used to generate each of the wave modes. For example, in FIG.
  • the transmit path can be further repeated using different reference oscillator(s) that are centered at the other frequency band(s).
  • N signals supplied by N antennas via the duplexer of each transmit path in the MMIC can be filtered by a corresponding N bandpass filters, which supply their output to N low-noise amplifiers.
  • the N low-noise amplifiers in turn supply their signals to N mixers to generate N intermediate-frequency received signals.
  • N is representative of the number of instances the MMIC is used for receiving wireless signals for different wave modes.
  • Y received signals supplied by receiver paths of certain MMICs (or a reference from the metal sleeve 2523 A of FIG. 25D) is subtracted from X received signals supplied by other MMICs based on the configurations shown in FIGs. 25AI-25AK.
  • a TM00 signal is reconstructed by supplying the received signals of all MMICs (NE, NW, SE, SW, N, S, E, W) to the plus port of the summer (i.e., X signals), while the reference signal from the metal sleeve 2523A of FIG. 25D is supplied to the negative port of the summer (i.e., Y signal)— see FIG. 25 AI.
  • the difference between the X and Y signals results in the TM00 signal.
  • the received signals of MMICs N, NE, and NW are supplied to the plus port of the summer (i.e., X signals), while the received signals of MMICs S, SE, and SW are supplied to the negative port of the summer (i.e., Y signals)— see FIG. 25 AJ.
  • the difference between the X and Y signals results in the HE11 vertical signal.
  • the received signals of MMICs E, NE, and SE are supplied to the plus port of the summer (i.e., X signals), while the received signals of MMICs W, NW, and SW are supplied to the negative port of the summer (i.e., Y signals)— see FIG. 25AK.
  • X signals the received signals of MMICs E, NE, and SE
  • Y signals the negative port of the summer
  • Each of these reconstructed signals is at intermediate frequencies. These intermediate-frequency signals are provided to receivers (RX1, RX2 and RX3) which include circuitry (e.g., a DSP, A/D converter, etc.) for processing and to selectively obtain communication signals therefrom. Similar to the transmit paths, the reference oscillators of the three receiver paths can be configured to be synchronized with phase lock loop technology or other suitable synchronization technique. If frequency division multiplexing is employed for the same wave modes in other frequency band(s) (see FIGs. 25 AD and 25 AE), the receiver paths can be further repeated using a different reference oscillator that is centered at the other frequency band(s).
  • FIG. 26 there is illustrated a block diagram of a computing environment in accordance with various aspects described herein.
  • FIG. 26 and the following discussion are intended to provide a brief, general description of a suitable computing environment 2600 in which the various embodiments of the subject disclosure can be implemented. While the embodiments have been described above in the general context of computer-executable instructions that can run on one or more computers, those skilled in the art will recognize that the embodiments can be also implemented in combination with other program modules and/or as a combination of hardware and software.
  • program modules comprise routines, programs, components, data structures, etc., that perform particular tasks or implement particular abstract data types.
  • inventive methods can be practiced with other computer system configurations, comprising single-processor or multiprocessor computer systems, minicomputers, mainframe computers, as well as personal computers, hand-held computing devices, microprocessor-based or programmable consumer electronics, and the like, each of which can be operatively coupled to one or more associated devices.
  • a processing circuit includes processor as well as other application specific circuits such as an application specific integrated circuit, digital logic circuit, state machine, programmable gate array or other circuit that processes input signals or data and that produces output signals or data in response thereto. It should be noted that while any functions and features described herein in association with the operation of a processor could likewise be performed by a processing circuit.
  • Computing devices typically comprise a variety of media, which can comprise computer-readable storage media and/or communications media, which two terms are used herein differently from one another as follows.
  • Computer-readable storage media can be any available storage media that can be accessed by the computer and comprises both volatile and nonvolatile media, removable and non-removable media.
  • Computer-readable storage media can be implemented in connection with any method or technology for storage of information such as computer-readable instructions, program modules, structured data or unstructured data.
  • Computer-readable storage media can comprise, but are not limited to, random access memory (RAM), read only memory (ROM), electrically erasable programmable read only memory (EEPROM), flash memory or other memory technology, compact disk read only memory (CD-ROM), digital versatile disk (DVD) or other optical disk storage, magnetic cassettes, magnetic tape, magnetic disk storage or other magnetic storage devices or other tangible and/or non-transitory media which can be used to store desired information.
  • RAM random access memory
  • ROM read only memory
  • EEPROM electrically erasable programmable read only memory
  • flash memory or other memory technology
  • CD-ROM compact disk read only memory
  • DVD digital versatile disk
  • magnetic cassettes magnetic tape
  • magnetic disk storage magnetic disk storage devices or other tangible and/or non-transitory media which can be used to store desired information.
  • tangible or “non-transitory” herein as applied to storage, memory or computer-readable media, are to be understood to exclude only propagating transitory signals per se as modifiers and do not relinquish rights to all standard storage, memory or computer-readable media that are not only propagating transitory signals per se.
  • Computer-readable storage media can be accessed by one or more local or remote computing devices, e.g., via access requests, queries or other data retrieval protocols, for a variety of operations with respect to the information stored by the medium.
  • Communications media typically embody computer-readable instructions, data structures, program modules or other structured or unstructured data in a data signal such as a modulated data signal, e.g., a carrier wave or other transport mechanism, and comprises any information delivery or transport media.
  • modulated data signal or signals refers to a signal that has one or more of its characteristics set or changed in such a manner as to encode information in one or more signals.
  • communication media comprise wired media, such as a wired network or direct- wired connection, and wireless media such as acoustic, RF, infrared and other wireless media.
  • the example environment can comprise a computer 2602, the computer 2602 comprising a processing unit 2604, a system memory 2606 and a system bus 2608.
  • the system bus 2608 couple' s system components including, but not limited to, the system memory 2606 to the processing unit 2604.
  • the processing unit 2604 can be any of various commercially available processors. Dual microprocessors and other multiprocessor architectures can also be employed as the processing unit 2604.
  • the system bus 2608 can be any of several types of bus structure that can further interconnect to a memory bus (with or without a memory controller), a peripheral bus, and a local bus using any of a variety of commercially available bus architectures.
  • the system memory 2606 comprises ROM 2610 and RAM 2612.
  • a basic input/output system (BIOS) can be stored in a non-volatile memory such as ROM, erasable programmable read only memory (EPROM), EEPROM, which BIOS contains the basic routines that help to transfer information between elements within the computer 2602, such as during startup.
  • the RAM 2612 can also comprise a high-speed RAM such as static RAM for caching data.
  • the computer 2602 further comprises an internal hard disk drive (HDD) 2614 (e.g., EIDE, SATA), which internal hard disk drive 2614 can also be configured for external use in a suitable chassis (not shown), a magnetic floppy disk drive (FDD) 2616, (e.g., to read from or write to a removable diskette 2618) and an optical disk drive 2620, (e.g., reading a CD-ROM disk 2622 or, to read from or write to other high capacity optical media such as the DVD).
  • the hard disk drive 2614, magnetic disk drive 2616 and optical disk drive 2620 can be connected to the system bus 2608 by a hard disk drive interface 2624, a magnetic disk drive interface 2626 and an optical drive interface 2628, respectively.
  • the interface 2624 for external drive implementations comprises at least one or both of Universal Serial Bus (USB) and Institute of Electrical and Electronics Engineers (IEEE) 1394 interface technologies. Other external drive connection technologies are within contemplation of the embodiments described herein.
  • the drives and their associated computer-readable storage media provide nonvolatile storage of data, data structures, computer-executable instructions, and so forth.
  • the drives and storage media accommodate the storage of any data in a suitable digital format.
  • computer-readable storage media refers to a hard disk drive (HDD), a removable magnetic diskette, and a removable optical media such as a CD or DVD, it should be appreciated by those skilled in the art that other types of storage media which are readable by a computer, such as zip drives, magnetic cassettes, flash memory cards, cartridges, and the like, can also be used in the example operating environment, and further, that any such storage media can contain computer- executable instructions for performing the methods described herein.
  • a number of program modules can be stored in the drives and RAM 2612, comprising an operating system 2630, one or more application programs 2632, other program modules 2634 and program data 2636. All or portions of the operating system, applications, modules, and/or data can also be cached in the RAM 2612.
  • the systems and methods described herein can be implemented utilizing various commercially available operating systems or combinations of operating systems. Examples of application programs 2632 that can be implemented and otherwise executed by processing unit 2604 include the diversity selection determining performed by transmission device 101 or 102.
  • a user can enter commands and information into the computer 2602 through one or more wired/wireless input devices, e.g., a keyboard 2638 and a pointing device, such as a mouse 2640.
  • Other input devices can comprise a microphone, an infrared (IR) remote control, a joystick, a game pad, a stylus pen, touch screen or the like.
  • IR infrared
  • These and other input devices are often connected to the processing unit 2604 through an input device interface 2642 that can be coupled to the system bus 2608, but can be connected by other interfaces, such as a parallel port, an IEEE 1394 serial port, a game port, a universal serial bus (USB) port, an IR interface, etc.
  • a monitor 2644 or other type of display device can be also connected to the system bus 2608 via an interface, such as a video adapter 2646. It will also be appreciated that in alternative embodiments, a monitor 2644 can also be any display device (e.g., another computer having a display, a smart phone, a tablet computer, etc.) for receiving display information associated with computer 2602 via any communication means, including via the Internet and cloud-based networks. In addition to the monitor 2644, a computer typically comprises other peripheral output devices (not shown), such as speakers, printers, etc.
  • the computer 2602 can operate in a networked environment using logical connections via wired and/or wireless communications to one or more remote computers, such as a remote computer(s) 2648.
  • the remote computer(s) 2648 can be a workstation, a server computer, a router, a personal computer, portable computer, microprocessor-based entertainment appliance, a peer device or other common network node, and typically comprises many or all of the elements described relative to the computer 2602, although, for purposes of brevity, only a memory/storage device 2650 is illustrated.
  • the logical connections depicted comprise wired/wireless connectivity to a local area network (LAN) 2652 and/or larger networks, e.g., a wide area network (WAN) 2654.
  • LAN and WAN networking environments are commonplace in offices and companies, and facilitate enterprise-wide computer networks, such as intranets, all of which can connect to a global communications network, e.g., the Internet.
  • the computer 2602 can be connected to the local network 2652 through a wired and/or wireless communication network interface or adapter 2656.
  • the adapter 2656 can facilitate wired or wireless communication to the LAN 2652, which can also comprise a wireless AP disposed thereon for communicating with the wireless adapter 2656.
  • the computer 2602 can comprise a modem 2658 or can be connected to a communications server on the WAN 2654 or has other means for establishing communications over the WAN 2654, such as by way of the Internet.
  • the modem 2658 which can be internal or external and a wired or wireless device, can be connected to the system bus 2608 via the input device interface 2642.
  • program modules depicted relative to the computer 2602 or portions thereof can be stored in the remote memory/storage device 2650. It will be appreciated that the network connections shown are example and other means of establishing a communications link between the computers can be used.
  • the computer 2602 can be operable to communicate with any wireless devices or entities operatively disposed in wireless communication, e.g., a printer, scanner, desktop and/or portable computer, portable data assistant, communications satellite, any piece of equipment or location associated with a wirelessly detectable tag (e.g., a kiosk, news stand, restroom), and telephone.
  • any wireless devices or entities operatively disposed in wireless communication e.g., a printer, scanner, desktop and/or portable computer, portable data assistant, communications satellite, any piece of equipment or location associated with a wirelessly detectable tag (e.g., a kiosk, news stand, restroom), and telephone.
  • This can comprise Wireless Fidelity (Wi-Fi) and BLUETOOTH® wireless technologies.
  • Wi-Fi Wireless Fidelity
  • BLUETOOTH® wireless technologies can be a predefined structure as with a conventional network or simply an ad hoc communication between at least two devices.
  • Wi-Fi can allow connection to the Internet from a couch at home, a bed in a hotel room or a conference room at work, without wires.
  • Wi-Fi is a wireless technology similar to that used in a cell phone that enables such devices, e.g., computers, to send and receive data indoors and out; anywhere within the range of a base station.
  • Wi-Fi networks use radio technologies called IEEE 802.11 (a, b, g, n, ac, ag etc.) to provide secure, reliable, fast wireless connectivity.
  • a Wi-Fi network can be used to connect computers to each other, to the Internet, and to wired networks (which can use IEEE 802.3 or Ethernet).
  • Wi- Fi networks operate in the unlicensed 2.4 and 5 GHz radio bands for example or with products that contain both bands (dual band), so the networks can provide real-world performance similar to the basic lOBaseT wired Ethernet networks used in many offices.
  • FIG. 27 presents an example embodiment 2700 of a mobile network platform 2710 that can implement and exploit one or more aspects of the disclosed subject matter described herein.
  • the mobile network platform 2710 can generate and receive signals transmitted and received by base stations (e.g., base station devices 1504, macrocell site 1502, or base stations 1614), central office (e.g., central office 1501 or 1611),or transmission device 101 or 102 associated with the disclosed subject matter.
  • base stations e.g., base station devices 1504, macrocell site 1502, or base stations 1614
  • central office e.g., central office 1501 or 1611
  • transmission device 101 or 102 associated with the disclosed subject matter.
  • wireless network platform 2710 can comprise components, e.g., nodes, gateways, interfaces, servers, or disparate platforms, that facilitate both packet-switched (PS) (e.g., internet protocol (IP), frame relay, asynchronous transfer mode (ATM)) and circuit- switched (CS) traffic (e.g., voice and data), as well as control generation for networked wireless telecommunication.
  • PS packet-switched
  • IP internet protocol
  • ATM asynchronous transfer mode
  • CS circuit- switched
  • wireless network platform 2710 can be included in telecommunications carrier networks, and can be considered carrier-side components as discussed elsewhere herein.
  • Mobile network platform 2710 comprises CS gateway node(s) 2722 which can interface CS traffic received from legacy networks like telephony network(s) 2740 (e.g., public switched telephone network (PSTN), or public land mobile network (PLMN)) or a signaling system #7 (SS7) network 2770.
  • Circuit switched gateway node(s) 2722 can authorize and authenticate traffic (e.g., voice) arising from such networks.
  • CS gateway node(s) 2722 can access mobility, or roaming, data generated through SS7 network 2770; for instance, mobility data stored in a visited location register (VLR), which can reside in memory 2730.
  • VLR visited location register
  • CS gateway node(s) 2722 interfaces CS-based traffic and signaling and PS gateway node(s) 2718.
  • CS gateway node(s) 2722 can be realized at least in part in gateway GPRS support node(s) (GGSN). It should be appreciated that functionality and specific operation of CS gateway node(s) 2722, PS gateway node(s) 2718, and serving node(s) 2716, is provided and dictated by radio technology(ies) utilized by mobile network platform 2710 for telecommunication.
  • PS gateway node(s) 2718 can authorize and authenticate PS-based data sessions with served mobile devices.
  • Data sessions can comprise traffic, or content(s), exchanged with networks external to the wireless network platform 2710, like wide area network(s) (WANs) 2750, enterprise network(s) 2770, and service network(s) 2780, which can be embodied in local area network(s) (LANs), can also be interfaced with mobile network platform 2710 through PS gateway node(s) 2718.
  • WANs 2750 and enterprise network(s) 2760 can embody, at least in part, a service network(s) like IP multimedia subsystem (IMS).
  • IMS IP multimedia subsystem
  • packet-switched gateway node(s) 2718 can generate packet data protocol contexts when a data session is established; other data structures that facilitate routing of packetized data also can be generated.
  • PS gateway node(s) 2718 can comprise a tunnel interface (e.g., tunnel termination gateway (TTG) in 3GPP UMTS network(s) (not shown)) which can facilitate packetized communication with disparate wireless network(s), such as Wi-Fi networks.
  • TSG tunnel termination gateway
  • wireless network platform 2710 also comprises serving node(s) 2716 that, based upon available radio technology layer(s) within technology resource(s) 2717, convey the various packetized flows of data streams received through PS gateway node(s) 2718.
  • serving node(s) 2716 can deliver traffic without reliance on PS gateway node(s) 2718; for example, server node(s) can embody at least in part a mobile switching center.
  • serving node(s) 2716 can be embodied in serving GPRS support node(s) (SGSN).
  • server(s) 2714 in wireless network platform 2710 can execute numerous applications that can generate multiple disparate packetized data streams or flows, and manage (e.g., schedule, queue, format ...) such flows.
  • Such application(s) can comprise add-on features to standard services (for example, provisioning, billing, customer support ...) provided by wireless network platform 2710.
  • Data streams e.g., content(s) that are part of a voice call or data session
  • PS gateway node(s) 2718 for authorization/authentication and initiation of a data session
  • serving node(s) 2716 for communication thereafter.
  • server(s) 2714 can comprise utility server(s), a utility server can comprise a provisioning server, an operations and maintenance server, a security server that can implement at least in part a certificate authority and firewalls as well as other security mechanisms, and the like.
  • security server(s) secure communication served through wireless network platform 2710 to ensure network's operation and data integrity in addition to authorization and authentication procedures that CS gateway node(s) 2722 and PS gateway node(s) 2718 can enact.
  • provisioning server(s) can provision services from external network(s) like networks operated by a disparate service provider; for instance, WAN 2750 or Global Positioning System (GPS) network(s) (not shown).
  • GPS Global Positioning System
  • Provisioning server(s) can also provision coverage through networks associated to wireless network platform 2710 (e.g., deployed and operated by the same service provider), such as the distributed antennas networks shown in FIG. 1 that enhance wireless service coverage by providing more network coverage.
  • Repeater devices such as those shown in FIGs 7, 8, and 9 also improve network coverage in order to enhance subscriber service experience by way of UE 2775.
  • server(s) 2714 can comprise one or more processors configured to confer at least in part the functionality of macro network platform 2710. To that end, the one or more processor can execute code instructions stored in memory 2730, for example. It is should be appreciated that server(s) 2714 can comprise a content manager 2715, which operates in substantially the same manner as described hereinbefore.
  • memory 2730 can store information related to operation of wireless network platform 2710. Other operational information can comprise provisioning information of mobile devices served through wireless platform network 2710, subscriber databases; application intelligence, pricing schemes, e.g., promotional rates, flat-rate programs, couponing campaigns; technical specification(s) consistent with telecommunication protocols for operation of disparate radio, or wireless, technology layers; and so forth. Memory 2730 can also store information from at least one of telephony network(s) 2740, WAN 2750, enterprise network(s) 2770, or SS7 network 2760. In an aspect, memory 2730 can be, for example, accessed as part of a data store component or as a remotely connected memory store.
  • FIG. 27, and the following discussion are intended to provide a brief, general description of a suitable environment in which the various aspects of the disclosed subject matter can be implemented. While the subject matter has been described above in the general context of computer-executable instructions of a computer program that runs on a computer and/or computers, those skilled in the art will recognize that the disclosed subject matter also can be implemented in combination with other program modules. Generally, program modules comprise routines, programs, components, data structures, etc. that perform particular tasks and/or implement particular abstract data types.
  • FIG. 28 depicts an illustrative embodiment of a communication device 2800.
  • the communication device 2800 can serve as an illustrative embodiment of devices such as mobile devices and in-building devices referred to by the subject disclosure (e.g., in FIGs.15, 16A and 16B).
  • the communication device 2800 can comprise a wireline and/or wireless transceiver 2802 (herein transceiver 2802), a user interface (UI) 2804, a power supply 2814, a location receiver 2816, a motion sensor 2818, an orientation sensor 2820, and a controller 2806 for managing operations thereof.
  • the transceiver 2802 can support short- range or long-range wireless access technologies such as Bluetooth ® , ZigBee ® , WiFi, DECT, or cellular communication technologies, just to mention a few (Bluetooth ® and ZigBee are trademarks registered by the Bluetooth Special Interest Group and the ZigBee ® Alliance, respectively).
  • Cellular technologies can include, for example, CDMA- IX, UMTS/HSDPA, GSM/GPRS, TDMA/EDGE, EV/DO, WiMAX, SDR, LTE, as well as other next generation wireless communication technologies as they arise.
  • the transceiver 2802 can also be adapted to support circuit- switched wireline access technologies (such as PSTN), packet-switched wireline access technologies (such as TCP/IP, VoIP, etc.), and combinations thereof.
  • the UI 2804 can include a depressible or touch- sensitive keypad 2808 with a navigation mechanism such as a roller ball, a joystick, a mouse, or a navigation disk for manipulating operations of the communication device 2800.
  • the keypad 2808 can be an integral part of a housing assembly of the communication device 2800 or an independent device operably coupled thereto by a tethered wireline interface (such as a USB cable) or a wireless interface supporting for example Bluetooth ® .
  • the keypad 2808 can represent a numeric keypad commonly used by phones, and/or a QWERTY keypad with alphanumeric keys.
  • the UI 2804 can further include a display 2810 such as monochrome or color LCD (Liquid Crystal Display), OLED (Organic Light Emitting Diode) or other suitable display technology for conveying images to an end user of the communication device 2800.
  • a display 2810 such as monochrome or color LCD (Liquid Crystal Display), OLED (Organic Light Emitting Diode) or other suitable display technology for conveying images to an end user of the communication device 2800.
  • a portion or all of the keypad 2808 can be presented by way of the display 2810 with navigation features.
  • the display 2810 can use touch screen technology to also serve as a user interface for detecting user input.
  • the communication device 2800 can be adapted to present a user interface having graphical user interface (GUI) elements that can be selected by a user with a touch of a finger.
  • GUI graphical user interface
  • the touch screen display 2810 can be equipped with capacitive, resistive or other forms of sensing technology to detect how much surface area of a user's finger has been placed on a portion of the touch screen display. This sensing information can be used to control the manipulation of the GUI elements or other functions of the user interface.
  • the display 2810 can be an integral part of the housing assembly of the communication device 2800 or an independent device communicatively coupled thereto by a tethered wireline interface (such as a cable) or a wireless interface.
  • the UI 2804 can also include an audio system 2812 that utilizes audio technology for conveying low volume audio (such as audio heard in proximity of a human ear) and high volume audio (such as speakerphone for hands free operation).
  • the audio system 2812 can further include a microphone for receiving audible signals of an end user.
  • the audio system 2812 can also be used for voice recognition applications.
  • the UI 2804 can further include an image sensor 2813 such as a charged coupled device (CCD) camera for capturing still or moving images.
  • CCD charged coupled device
  • the power supply 2814 can utilize common power management technologies such as replaceable and rechargeable batteries, supply regulation technologies, and/or charging system technologies for supplying energy to the components of the communication device 2800 to facilitate long-range or short-range portable communications.
  • the charging system can utilize external power sources such as DC power supplied over a physical interface such as a USB port or other suitable tethering technologies.
  • the location receiver 2816 can utilize location technology such as a global positioning system (GPS) receiver capable of assisted GPS for identifying a location of the communication device 2800 based on signals generated by a constellation of GPS satellites, which can be used for facilitating location services such as navigation.
  • GPS global positioning system
  • the motion sensor 2818 can utilize motion sensing technology such as an accelerometer, a gyroscope, or other suitable motion sensing technology to detect motion of the communication device 2800 in three-dimensional space.
  • the orientation sensor 2820 can utilize orientation sensing technology such as a magnetometer to detect the orientation of the communication device 2800 (north, south, west, and east, as well as combined orientations in degrees, minutes, or other suitable orientation metrics).
  • the communication device 2800 can use the transceiver 2802 to also determine a proximity to a cellular, WiFi, Bluetooth ® , or other wireless access points by sensing techniques such as utilizing a received signal strength indicator (RSSI) and/or signal time of arrival (TO A) or time of flight (TOF) measurements.
  • the controller 2806 can utilize computing technologies such as a microprocessor, a digital signal processor (DSP), programmable gate arrays, application specific integrated circuits, and/or a video processor with associated storage memory such as Flash, ROM, RAM, SRAM, DRAM or other storage technologies for executing computer instructions, controlling, and processing data supplied by the aforementioned components of the communication device 2800.
  • computing technologies such as a microprocessor, a digital signal processor (DSP), programmable gate arrays, application specific integrated circuits, and/or a video processor with associated storage memory such as Flash, ROM, RAM, SRAM, DRAM or other storage technologies for executing computer instructions, controlling, and processing data supplied by the aforementioned components of
  • the communication device 2800 can include a slot for adding or removing an identity module such as a Subscriber Identity Module (SIM) card or Universal Integrated Circuit Card (UICC).
  • SIM Subscriber Identity Module
  • UICC Universal Integrated Circuit Card
  • SIM or UICC cards can be used for identifying subscriber services, executing programs, storing subscriber data, and so on.
  • the memory components described herein can be either volatile memory or nonvolatile memory, or can comprise both volatile and nonvolatile memory, by way of illustration, and not limitation, volatile memory, non-volatile memory, disk storage, and memory storage.
  • nonvolatile memory can be included in read only memory (ROM), programmable ROM (PROM), electrically programmable ROM (EPROM), electrically erasable ROM (EEPROM), or flash memory.
  • Volatile memory can comprise random access memory (RAM), which acts as external cache memory.
  • RAM is available in many forms such as synchronous RAM (SRAM), dynamic RAM (DRAM), synchronous DRAM (SDRAM), double data rate SDRAM (DDR SDRAM), enhanced SDRAM (ESDRAM), Synchlink DRAM (SLDRAM), and direct Rambus RAM (DRRAM).
  • SRAM synchronous RAM
  • DRAM dynamic RAM
  • SDRAM synchronous DRAM
  • DDR SDRAM double data rate SDRAM
  • ESDRAM enhanced SDRAM
  • SLDRAM Synchlink DRAM
  • DRRAM direct Rambus RAM
  • the disclosed memory components of systems or methods herein are intended to comprise, without being limited to comprising, these and any other suitable types of memory.
  • Some of the embodiments described herein can also employ artificial intelligence (AI) to facilitate automating one or more features described herein.
  • AI artificial intelligence
  • artificial intelligence can be used in optional training controller 230 evaluate and select candidate frequencies, modulation schemes, MEVIO modes, and/or guided wave modes in order to maximize transfer efficiency.
  • the embodiments e.g., in connection with automatically identifying acquired cell sites that provide a maximum value/benefit after addition to an existing communication network
  • the classifier can be employed to determine a ranking or priority of the each cell site of the acquired network.
  • Such classification can employ a probabilistic and/or statistical-based analysis (e.g., factoring into the analysis utilities and costs) to prognose or infer an action that a user desires to be automatically performed.
  • a support vector machine (SVM) is an example of a classifier that can be employed. The SVM operates by finding a hypersurface in the space of possible inputs, which the hypersurface attempts to split the triggering criteria from the non-triggering events.
  • Other directed and undirected model classification approaches comprise, e.g., naive Bayes, Bayesian networks, decision trees, neural networks, fuzzy logic models, and probabilistic classification models providing different patterns of independence can be employed.
  • Classification as used herein also is inclusive of statistical regression that is utilized to develop models of priority.
  • one or more of the embodiments can employ classifiers that are explicitly trained (e.g., via a generic training data) as well as implicitly trained (e.g., via observing UE behavior, operator preferences, historical information, receiving extrinsic information).
  • SVMs can be configured via a learning or training phase within a classifier constructor and feature selection module.
  • the classifier(s) can be used to automatically learn and perform a number of functions, including but not limited to determining according to a predetermined criteria which of the acquired cell sites will benefit a maximum number of subscribers and/or which of the acquired cell sites will add minimum value to the existing communication network coverage, etc.
  • the terms "component,” “system” and the like are intended to refer to, or comprise, a computer- related entity or an entity related to an operational apparatus with one or more specific functionalities, wherein the entity can be either hardware, a combination of hardware and software, software, or software in execution.
  • a component may be, but is not limited to being, a process running on a processor, a processor, an object, an executable, a thread of execution, computer-executable instructions, a program, and/or a computer.
  • an application running on a server and the server can be a component.
  • One or more components may reside within a process and/or thread of execution and a component may be localized on one computer and/or distributed between two or more computers. In addition, these components can execute from various computer readable media having various data structures stored thereon. The components may communicate via local and/or remote processes such as in accordance with a signal having one or more data packets (e.g., data from one component interacting with another component in a local system, distributed system, and/or across a network such as the Internet with other systems via the signal).
  • a signal having one or more data packets (e.g., data from one component interacting with another component in a local system, distributed system, and/or across a network such as the Internet with other systems via the signal).
  • a component can be an apparatus with specific functionality provided by mechanical parts operated by electric or electronic circuitry, which is operated by a software or firmware application executed by a processor, wherein the processor can be internal or external to the apparatus and executes at least a part of the software or firmware application.
  • a component can be an apparatus that provides specific functionality through electronic components without mechanical parts, the electronic components can comprise a processor therein to execute software or firmware that confers at least in part the functionality of the electronic components. While various components have been illustrated as separate components, it will be appreciated that multiple components can be implemented as a single component, or a single component can be implemented as multiple components, without departing from example embodiments.
  • the various embodiments can be implemented as a method, apparatus or article of manufacture using standard programming and/or engineering techniques to produce software, firmware, hardware or any combination thereof to control a computer to implement the disclosed subject matter.
  • article of manufacture as used herein is intended to encompass a computer program accessible from any computer-readable device or computer-readable storage/communications media.
  • computer readable storage media can include, but are not limited to, magnetic storage devices (e.g., hard disk, floppy disk, magnetic strips), optical disks (e.g., compact disk (CD), digital versatile disk (DVD)), smart cards, and flash memory devices (e.g., card, stick, key drive).
  • magnetic storage devices e.g., hard disk, floppy disk, magnetic strips
  • optical disks e.g., compact disk (CD), digital versatile disk (DVD)
  • smart cards e.g., card, stick, key drive
  • terms such as “user equipment,” “mobile station,” “mobile,” subscriber station,” “access terminal,” “terminal,” “handset,” “mobile device” can refer to a wireless device utilized by a subscriber or user of a wireless communication service to receive or convey data, control, voice, video, sound, gaming or substantially any data-stream or signaling- stream.
  • the foregoing terms are utilized interchangeably herein and with reference to the related drawings.
  • processor can refer to substantially any computing processing unit or device comprising, but not limited to comprising, single-core processors; single-processors with software multithread execution capability; multi-core processors; multi-core processors with software multithread execution capability; multi- core processors with hardware multithread technology; parallel platforms; and parallel platforms with distributed shared memory.
  • a processor can refer to an integrated circuit, an application specific integrated circuit (ASIC), a digital signal processor (DSP), a field programmable gate array (FPGA), a programmable logic controller (PLC), a complex programmable logic device (CPLD), a discrete gate or transistor logic, discrete hardware components or any combination thereof designed to perform the functions described herein.
  • ASIC application specific integrated circuit
  • DSP digital signal processor
  • FPGA field programmable gate array
  • PLC programmable logic controller
  • CPLD complex programmable logic device
  • processors can exploit nano-scale architectures such as, but not limited to, molecular and quantum-dot based transistors, switches and gates, in order to optimize space usage or enhance performance of user equipment.
  • a processor can also be implemented as a combination of computing processing units.
  • a flow diagram may include a "start” and/or “continue” indication.
  • the “start” and “continue” indications reflect that the steps presented can optionally be incorporated in or otherwise used in conjunction with other routines.
  • start indicates the beginning of the first step presented and may be preceded by other activities not specifically shown.
  • continue indicates that the steps presented may be performed multiple times and/or may be succeeded by other activities not specifically shown.
  • a flow diagram indicates a particular ordering of steps, other orderings are likewise possible provided that the principles of causality are maintained.
  • the term(s) "operably coupled to”, “coupled to”, and/or “coupling” includes direct coupling between items and/or indirect coupling between items via one or more intervening items.
  • Such items and intervening items include, but are not limited to, junctions, communication paths, components, circuit elements, circuits, functional blocks, and/or devices.
  • a signal conveyed from a first item to a second item may be modified by one or more intervening items by modifying the form, nature or format of information in a signal, while one or more elements of the information in the signal are nevertheless conveyed in a manner than can be recognized by the second item.
  • an action in a first item can cause a reaction on the second item, as a result of actions and/or reactions in one or more intervening items.

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  • Engineering & Computer Science (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Signal Processing (AREA)
  • Near-Field Transmission Systems (AREA)

Abstract

Des aspects de la présente invention peuvent consister à recevoir une pluralité de signaux de communication, et à générer, en fonction de la pluralité de signaux de communication, des signaux qui induisent une pluralité d'ondes électromagnétiques liées au moins en partie à une surface extérieure d'un support de transmission. L'invention concerne également d'autres modes de réalisation.
EP16785674.9A 2015-10-16 2016-10-14 Appareil et procédés de génération d'ondes électromagnétiques sur un support de transmission Withdrawn EP3363071A1 (fr)

Applications Claiming Priority (4)

Application Number Priority Date Filing Date Title
US14/885,463 US9722318B2 (en) 2015-07-14 2015-10-16 Method and apparatus for coupling an antenna to a device
US14/965,523 US10033107B2 (en) 2015-07-14 2015-12-10 Method and apparatus for coupling an antenna to a device
US15/274,987 US10170840B2 (en) 2015-07-14 2016-09-23 Apparatus and methods for sending or receiving electromagnetic signals
PCT/US2016/057161 WO2017066654A1 (fr) 2015-10-16 2016-10-14 Appareil et procédés de génération d'ondes électromagnétiques sur un support de transmission

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US10305545B2 (en) 2015-07-14 2019-05-28 At&T Intellectual Property I, L.P. Method and apparatus for coupling an antenna to a device
US10320586B2 (en) 2015-07-14 2019-06-11 At&T Intellectual Property I, L.P. Apparatus and methods for generating non-interfering electromagnetic waves on an insulated transmission medium
US10341142B2 (en) 2015-07-14 2019-07-02 At&T Intellectual Property I, L.P. Apparatus and methods for generating non-interfering electromagnetic waves on an uninsulated conductor
US10382072B2 (en) 2015-07-14 2019-08-13 At&T Intellectual Property I, L.P. Method and apparatus for coupling an antenna to a device
US10439290B2 (en) 2015-07-14 2019-10-08 At&T Intellectual Property I, L.P. Apparatus and methods for wireless communications
US10511346B2 (en) 2015-07-14 2019-12-17 At&T Intellectual Property I, L.P. Apparatus and methods for inducing electromagnetic waves on an uninsulated conductor
US10587048B2 (en) 2015-07-14 2020-03-10 At&T Intellectual Property I, L.P. Apparatus and methods for communicating utilizing an antenna array
US10594039B2 (en) 2015-07-14 2020-03-17 At&T Intellectual Property I, L.P. Apparatus and methods for sending or receiving electromagnetic signals
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US10305545B2 (en) 2015-07-14 2019-05-28 At&T Intellectual Property I, L.P. Method and apparatus for coupling an antenna to a device
US10320586B2 (en) 2015-07-14 2019-06-11 At&T Intellectual Property I, L.P. Apparatus and methods for generating non-interfering electromagnetic waves on an insulated transmission medium
US10341142B2 (en) 2015-07-14 2019-07-02 At&T Intellectual Property I, L.P. Apparatus and methods for generating non-interfering electromagnetic waves on an uninsulated conductor
US10382072B2 (en) 2015-07-14 2019-08-13 At&T Intellectual Property I, L.P. Method and apparatus for coupling an antenna to a device
US10439290B2 (en) 2015-07-14 2019-10-08 At&T Intellectual Property I, L.P. Apparatus and methods for wireless communications
US10469107B2 (en) 2015-07-14 2019-11-05 At&T Intellectual Property I, L.P. Apparatus and methods for transmitting wireless signals
US10511346B2 (en) 2015-07-14 2019-12-17 At&T Intellectual Property I, L.P. Apparatus and methods for inducing electromagnetic waves on an uninsulated conductor
US10587048B2 (en) 2015-07-14 2020-03-10 At&T Intellectual Property I, L.P. Apparatus and methods for communicating utilizing an antenna array
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US10686496B2 (en) 2015-07-14 2020-06-16 At&T Intellecutal Property I, L.P. Method and apparatus for coupling an antenna to a device
US10741923B2 (en) 2015-07-14 2020-08-11 At&T Intellectual Property I, L.P. Method and apparatus for coupling an antenna to a device
US10790593B2 (en) 2015-07-14 2020-09-29 At&T Intellectual Property I, L.P. Method and apparatus including an antenna comprising a lens and a body coupled to a feedline having a structure that reduces reflections of electromagnetic waves
US10819542B2 (en) 2015-07-14 2020-10-27 At&T Intellectual Property I, L.P. Apparatus and methods for inducing electromagnetic waves on a cable
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