EP3012901A1 - Résonateur, filtre de fréquence radio et procédé de filtrage - Google Patents

Résonateur, filtre de fréquence radio et procédé de filtrage Download PDF

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Publication number
EP3012901A1
EP3012901A1 EP14290315.2A EP14290315A EP3012901A1 EP 3012901 A1 EP3012901 A1 EP 3012901A1 EP 14290315 A EP14290315 A EP 14290315A EP 3012901 A1 EP3012901 A1 EP 3012901A1
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EP
European Patent Office
Prior art keywords
resonator
posts
wall
chamber
gap
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Granted
Application number
EP14290315.2A
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German (de)
English (en)
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EP3012901B1 (fr
Inventor
Senad Bulja
Martin Gimersky
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Alcatel Lucent SAS
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Alcatel Lucent SAS
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Priority to EP14290315.2A priority Critical patent/EP3012901B1/fr
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P7/00—Resonators of the waveguide type
    • H01P7/10—Dielectric resonators
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P7/00—Resonators of the waveguide type
    • H01P7/04—Coaxial resonators

Definitions

  • the present invention relates to filters for telecommunications, in particular to radio-frequency filters.
  • Filters are widely used in telecommunications. Applications include base stations for wireless cellular communications, radar systems, amplifier linearization systems, point-to-point radio, and RF signal cancellation systems, to name just a few. Although a specific filter is chosen or designed dependent on the particular application, it is generally desirable for a filter to have low insertion loss in the pass-band and high attenuation in the stop-band. Furthermore, in some applications, the frequency separation (known as the guard-band) between stop-band and pass-band needs to be small, so a filter of a high order is required. Of course as the order of a filter is increased so does its complexity in terms of the number of components the filter requires and hence the filter's size. Furthermore, although increasing the order of a filter increases stop-band attenuation, insertion loss in the pass-band is also thereby increased.
  • a filter it is sometimes important for a filter to have good tunability, in other words to be able to vary its operating frequency and percentage bandwidth. This is particularly desirable if the variation in operating frequency and bandwidth of the filter do not significantly deteriorate other important filter characteristics, for example pass-band loss and rejection.
  • PCB printed-circuit-board
  • electronic tunability is achieved using a varactor diode suitably connected to an open-ended part of a resonator.
  • both power handling of such a resonator/filter is reduced due to the poor intermodulation performance of the varactor diode and, at the same time, the insertion losses of such a resonator/filter are increased, due to the parasitic resistance of the diode.
  • the standard building block of a cavity filter is a combline resonator, depicted in its basic form in Figure 1 .
  • the combline resonator includes a resonator post in a cavity, and resonates at the frequency at which the resonator post's height is one quarter-wavelength of the electric current, I, induced on the surface of the resonator post.
  • a single combline resonator is provided, and as there is no significant capacitive loading at the top of the resonator post, the electrical length of the combline resonator needs to be approximately 90 degrees at the frequency of operation. This electrical length of 90 degrees means that the resonator behaves as an impedance transformer, namely where the resonator post has a short-circuit ended bottom and an open-circuit ended top.
  • a tuning screw extends from the top of the cavity toward the resonator post's ungrounded end so as to effectively balance undesired effects caused by manufacturing tolerances.
  • the tuning screw allows the resonator to be tuned to the resonant frequency for which the resonator was designed.
  • the tuning screw can also be used to retune the resonator to a different frequency.
  • the range of tunability achievable this way is in practice only a few per cent. This is primarily because the volume of space between the cavity top and the ungrounded end of the resonator is the region within the entire cavity where, at resonance, the electric field in the cavity is the strongest, i.e., the region is very susceptible to arcing.
  • the tuning screw further reduces the size of the gap between the cavity top and the ungrounded end of the resonator, thus reducing the power-handling capability of the resonator. For reasons of power handling, the minimal size of the gap found in practical filters for wireless cellular-communication applications is about 1 mm.
  • the electronically controllable device is usually a varactor diode (in which case the resultant filter exhibits the same problems as its PCB counterpart) or in the form of micro-electro-mechanical systems (MEMS).
  • MEMS micro-electro-mechanical systems
  • the variation in resonant frequency as a function of tuning screw insertion is shown in Figure 4 .
  • the cavity is 20 mm by 20 mm by 40 mm where 40 mm is the height, and the resonator post is 39 mm long.
  • the screw is inserted between 0 and 0.5 mm.
  • a frequency tuning range of only about 2% is achievable.
  • An example of the present invention is a resonator comprising a resonant chamber, each chamber comprising a first wall, a second wall opposite the first wall, and side walls; in which the resonant chamber houses two resonator posts, the two resonator posts being separated by a gap and in proximity with each other for magnetic field coupling of the two posts; one of the two posts being grounded on the first wall so as to extend into the chamber from the first wall; the other of the two posts being grounded on the second wall so as to extend into the chamber from the second wall.
  • the magnetic fields created by the currents in the resonator posts act to reinforce each other in the gap between the resonators. This makes the coupling between the resonator posts readily adjustable, and hence the resonant frequency readily adjustable.
  • the first wall may be a top wall and the second wall may be a bottom wall.
  • Some embodiments include the two resonator posts for reduced size and increased frequency tenability. Some embodiments provide a mechanically tunable resonator structure with high power handling and low insertion loss.
  • Some embodiments provide (a) reduced dimensions (as compared to using a single resonator post) and (b) a large tunable frequency range.
  • filters are made up of one or more of the resonator structures; for example the resonator structure are put together with inlet and outlet apertures between their chambers so as to form a radio-frequency Combline filter.
  • Filter minituarisation is desirable as in a typical base station for mobile communications filters are among the heaviest and bulkiest components, for example taking 30 % or more of the volume of the remote radiohead part of a base station.
  • a size reduction by a factor of 2 and a tunable frequency range of 30% is possible.
  • Frequency tuning is possible without the need to open the filter so there is no consequential risk of degradation of RF characteristics of the filter by contamination from the outside.
  • the resultant filters are suitable for Remote Radio Heads, being relatively small and so of lighter weight compared to known filters.
  • the electromagnetic characteristics that arise from replacing a single resonator post by two resonator posts are exploited in which a tuning element is introduced between the two posts.
  • Some preferred embodiments provide a resonator, in which the resonator posts are shaped so that the gap between the resonator posts allows a body portion of a tuning screw to be extended into the gap between the resonator posts.
  • the resonator posts each have a respective longitudinal channel along their gap facing surface.
  • each resonator post is at least substantially C-shaped in cross-section.
  • the two resonator posts are each of at least substantially circular cross-section.
  • the resonator posts are at least substantially semi-circular in cross-section so the gap is of a substantially constant width.
  • the resonator comprises a tuning element mounted in proximity to an end of one of the resonator posts that extends into the chamber, the tuning element between mounted on the wall opposite to the wall on which that resonator post is grounded.
  • the tuning element is a screw.
  • the present invention also relates to corresponding radio frequency filters and methods of filtering.
  • Another example of the present invention relates to a radio frequency filter comprising at least one resonator as outlined above.
  • Another example of the present invention relates to a method of radio frequency filtering comprising passing a signal for filtering through at least one resonator; each resonator comprising a resonant chamber, each chamber comprising a first wall, a second wall opposite the first wall, and side walls, in which the resonant chamber houses two resonator posts, the two resonator posts being separated by a gap and in proximity with each other for magnetic field coupling of the two posts; one of the two posts being grounded on the first wall so as to extend into the chamber from the first wall; the other of the two posts being grounded on the second wall so as to extend into the chamber from the second wall.
  • a useful resonator structure 2 may be provided in which there are two resonator posts 4, 6, one 4 of which is grounded on the bottom 8 of a resonator cavity 10 and the other 6 of which is grounded on the top 12 of the resonator cavity 10.
  • top wall bottom wall, sides walls, is intended to distinguish the walls from each other and resonators may function in any orientation relative to the Earth.
  • Figure 6 corresponds to two of the resonators each represented by their own equivalent - parallel LC (inductor-capacitor) - circuit connected through an admittance transformer, Y t .
  • the inventors then inferred from equation (2) that the first term on the right corresponds to the susceptance of inductor L 0 , while the second term represents the equivalent capacitive susceptance, composed of the susceptance of capacitor C 0 and the susceptance contribution of the second resonator.
  • Equation (5) indicates that the introduction of an admittance transformer, Y t , results in two resonant frequencies: one above and the other below the resonant frequency of an individual resonator.
  • the resonant frequencies of the resonator structure 2 shown in Figure 6 can be adjusted by a selection of the admittance transformer, Y t .
  • the inventors realised that this enables a way of obtaining frequency tunability, which, rather than focusing on the variation of the equivalent capacitance of a single resonator, introduces frequency tunability as a function of the coupling between two adjacent resonators.
  • the admittance transformer, Y t is allowed to vary from 0.0033 S (equivalent to 300 ⁇ ) to 0.05 S (equivalent to 20 ⁇ ).
  • circles represent resonant frequency of each of the two resonator posts 4,6, squares represent the lower bound to the operating frequency range, and triangles represent the upper bound to the operating frequency range.
  • frequency tunability is obtained by controlling the impedance transformation between the two resonator posts.
  • the inventors also realised that by using two resonator posts not only is frequency tunability achievable, but also the frequency of operation is reduced, leading to reduced physical dimensions (miniaturization).
  • Coupled represents the amount of energy that one resonator post intercepts from another resonator post and can be expressed equally well by an equivalent loading "impedance” that one resonator post exhibits when another resonator post is placed in its vicinity.
  • the loading impedance is infinite, no coupling exists between the resonator posts. In practice, this corresponds to the case of infinite physical separation between resonator posts.
  • the resonators are positioned at opposite sides from each other. This means that the directions of the surface currents on the respective resonator posts 4,6 are such that the magnetic fields created by these two currents reinforce each other in the space 16 between the resonators. This implies that the coupling between the two resonator posts 4, 6 is strong, the resonator posts 4,6 exhibit a great deal of influence on each other, and this influence can be controlled by manipulating the amount of coupling between the two resonator posts 4,6. As explained earlier with reference to Figure 6 , coupling can be represented by an equivalent impedance/admittance transformer between the two resonators.
  • this notional impedance/admittance transformer has a tunable electrical length.
  • each individual resonator post has an electrical length of 90° in isolation and that the electrical length of the transformer is adjustable, the overall electrical length of the resonant structure shown in Figure 5 can be arbitrarily long, resulting in reduced frequencies of operation compared to a single resonator in isolation.
  • FIG. 8 Another example is shown in Figure 8 .
  • the two resonator posts 4', 6' are shaped to take a C-shape cross-section for strong coupling between the resonators.
  • the resonator post 4' is mounted on the inner bottom surface 8' of a resonant cavity 10', and resonator post 6' is mounted on an inner top surface 12' of the cavity 10'.
  • the cavity is defined by metallic walls 11, which provide the inner top 8' and inner bottom 12' surfaces, on which a respective resonator post 4', 6' is grounded.
  • the resonator posts 4,6' may be considered as together constituting a split resonator where each resonator post 4'6' has two respective flat faces 26.
  • Each flat face 26 of a resonator post 4',6' is located proximal to but not touching a corresponding flat face 26 of the other resonator post 6',4'.
  • the resonator posts 4',6' when located proximally in this way provide a recess 28 within which a tuning screw 30 that intrudes into the cavity 10' may extend.
  • the length of extension 32 of the tuning screw 30 is adjustable and may be substantial as indicated schematically in Figure 8 (a) .
  • each resonator post 4',6' has a semicircular cross-section with a semicircular cross -section cut-out that forms the recess 28 which accommodates the extending portion 34 of the tuning screw 30.
  • the surface current distribution around circumference of the portion of the tuning screw that extends into the cavity 10' is essentially constant, giving the tuning screw a high tuning effect and allowing good power handling by the resonator structure 24'.
  • the tuning screw 30 has the effect of decreasing the capacitive coupling between the two split resonators and, as such, to increase the overall coupling.
  • increased coupling results in a reduced frequency of operation.
  • the overall coupling, k can be increased by either increasing the amount of magnetic coupling, k m , or reducing the amount of capacitive coupling, k e .
  • the increase of the overall coupling , k is achieved by the reduction of capacitive coupling, k e , by virtue of a tuning screw 30.
  • the surface currents on the first and second resonator posts 20,20 give rise to magnetic fields. Due to the current directions, the magnetic fields introduced by these two currents are such that in the space 22 between the resonator posts 20,20 the magnetic fields tend to cancel each other.
  • the resultant magnetic field between the two resonator posts 20,20 is very low.
  • the low density of the magnetic field between the two resonator posts 20,20 implies there is little interaction between the two resonator posts 20,20 and, as such, the frequency behaviour of the resonant structure 24 is similar to the behaviour of an individual resonator shown in Figure 1 (PRIOR ART).
  • Figure 11 For comparison with the example embodiment shown in Figure 8 , a further example of the alternative proposal is shown in Figure 11 . This is similar in structure to the Figure 8 example except that the two resonator posts are mounted on the same bottom surface.
  • the cavity size is identical, 20mm x 20mm x 40 mm, where 40mm is the height.
  • the resonant frequency for the case of a corresponding single resonator is equal to 1543 MHz.
  • the tunable resonator shown in Figure 8 can be compared with the obtainable tunable frequency range of a single resonator, Figure 2 (PRIOR ART) having a tuning screw on top.
  • the same size of cavity was considered in the single resonator post example ( Figure 2 ) and the second example embodiment ( Figure 8 ).
  • the cavity is 20 by 20 by 40 mm where 40 mm is the height.
  • the resonator post is 39 mm long.
  • the screw is inserted between 0 and 0.5 mm. It is not advisable to have a gap between the top of the resonator and the tuning screw smaller than 0.5 mm, as that would negatively influence the power-handling capability of the device.
  • a minimum gap of 1 mm was allowed.
  • the resonator structure 24' example shown in Figure 8 has a useful reduction in frequency of operation as compared to if there were a single resonator post ( Figure 2 ).
  • the proposed relative compact and tunable resonator structure is used together with an additional tuning screw near the top of the or each resonator post. Consequently, additional fine-tuning using the additional tuning screw(s) is possible following the tuning using the first tuning screw having the portion that extends into the space between the two resonator posts.
  • program storage devices e.g., digital data storage media, which are machine or computer readable and encode machine executable or computer-executable programs of instructions, wherein said instructions perform some or all of the steps of said above-described methods.
  • the program storage devices may be, e.g., digital memories, magnetic storage media such as a magnetic disks and magnetic tapes, hard drives, or optically readable digital data storage media.
  • Some embodiments involve computers programmed to perform said steps of the above-described methods.

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EP14290315.2A 2014-10-21 2014-10-21 Résonateur, filtre de fréquence radio et procédé de filtrage Active EP3012901B1 (fr)

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EP14290315.2A EP3012901B1 (fr) 2014-10-21 2014-10-21 Résonateur, filtre de fréquence radio et procédé de filtrage

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EP14290315.2A EP3012901B1 (fr) 2014-10-21 2014-10-21 Résonateur, filtre de fréquence radio et procédé de filtrage

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EP3012901A1 true EP3012901A1 (fr) 2016-04-27
EP3012901B1 EP3012901B1 (fr) 2020-07-15

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Cited By (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP3285331A1 (fr) * 2016-08-17 2018-02-21 Nokia Technologies Oy Resonateur
EP3301752A1 (fr) * 2016-09-28 2018-04-04 Nokia Technologies Oy Résonateur
EP3333967A1 (fr) * 2016-12-12 2018-06-13 Nokia Technologies OY Résonateur

Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0038996A1 (fr) * 1980-04-28 1981-11-04 Oki Electric Industry Company, Limited Filtre aux hautes fréquences
JPS5714201A (en) * 1980-06-30 1982-01-25 Murata Mfg Co Ltd Filter using dielectric resonator
US20040051603A1 (en) * 2002-09-17 2004-03-18 Pance Kristi Dhimiter Cross-coupled dielectric resonator circuit
EP1575118A1 (fr) * 2004-03-12 2005-09-14 M/A-Com, Inc. Méthode et mécanisme pour accorder des circuits de résonateurs diélectriques
WO2007149423A2 (fr) * 2006-06-21 2007-12-27 M/A-Com, Inc. Circuits de résonateurs diélectriques

Patent Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0038996A1 (fr) * 1980-04-28 1981-11-04 Oki Electric Industry Company, Limited Filtre aux hautes fréquences
JPS5714201A (en) * 1980-06-30 1982-01-25 Murata Mfg Co Ltd Filter using dielectric resonator
US20040051603A1 (en) * 2002-09-17 2004-03-18 Pance Kristi Dhimiter Cross-coupled dielectric resonator circuit
EP1575118A1 (fr) * 2004-03-12 2005-09-14 M/A-Com, Inc. Méthode et mécanisme pour accorder des circuits de résonateurs diélectriques
WO2007149423A2 (fr) * 2006-06-21 2007-12-27 M/A-Com, Inc. Circuits de résonateurs diélectriques

Cited By (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP3285331A1 (fr) * 2016-08-17 2018-02-21 Nokia Technologies Oy Resonateur
EP3301752A1 (fr) * 2016-09-28 2018-04-04 Nokia Technologies Oy Résonateur
EP3333967A1 (fr) * 2016-12-12 2018-06-13 Nokia Technologies OY Résonateur

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