EP2309586A1 - Elektrisch abstimmbare Bandpassfilter - Google Patents

Elektrisch abstimmbare Bandpassfilter Download PDF

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Publication number
EP2309586A1
EP2309586A1 EP10185327A EP10185327A EP2309586A1 EP 2309586 A1 EP2309586 A1 EP 2309586A1 EP 10185327 A EP10185327 A EP 10185327A EP 10185327 A EP10185327 A EP 10185327A EP 2309586 A1 EP2309586 A1 EP 2309586A1
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EP
European Patent Office
Prior art keywords
resonator
filter
electric
ferro
film
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Granted
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EP10185327A
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English (en)
French (fr)
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EP2309586B1 (de
Inventor
Stanley S. Toncich
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Qualcomm Inc
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Qualcomm Inc
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/20—Frequency-selective devices, e.g. filters
    • H01P1/201—Filters for transverse electromagnetic waves
    • H01P1/203—Strip line filters
    • H01P1/20327—Electromagnetic interstage coupling
    • H01P1/20336—Comb or interdigital filters
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/20—Frequency-selective devices, e.g. filters
    • H01P1/201—Filters for transverse electromagnetic waves
    • H01P1/203—Strip line filters

Definitions

  • This invention relates generally to electronic filters. More specifically, this invention is directed to electrically tunable bandpass filters.
  • BPF tuned bandpass filters
  • IL low passband insertion loss
  • IL close-in rejection conflict.
  • Portions of the filter transfer function representing the edges of the passband have a finite slope (the passband cutoff is gradual rather than an ideal perfectly abrupt transition from 'pass' to 'no-pass'). The more sharp the cut off required, the higher the order of the filter must be. Higher order filters are more bulky and have a greater IL than lower order filters and may require extensive turning to meet specifications.
  • a tunable filter can be dynamically tuned to different frequency ranges within a specific band, and if sufficiently tunable, different frequency ranges within multiple bands.
  • Tunable filters have several advantages over non-tunable filters. For example, tunable filters need not have a broad passband if the passband is dynamically adjustable. A narrow transfer function with high close-in rejection can be implemented with a lower order filter than can a wide transfer function with similar close-in rejection. Therefore, unlike a fixed tuned BPF, a tunable filter can be of a lower order and still meet desired rejection specifications. Lower order tunable filters are smaller in size, have a lower profile, lower IL, and can be built using lower precision components using a simpler fabrication processes, which in turn lowers cost. In addition, one filter topology can be optimized to cover multiple bands if the tuning range is wide enough. Thus multiple filter designs are no longer needed. Also, split-band designs along with the associated switches become unnecessary.
  • Fig. 1 shows a typical implementation of a top coupled BPF 100.
  • One or more resonators 106 are coupled to an input 102 and an output 104 via capacitors 108.
  • the resonators are constructed and arranged so as to have a reactance that has at least one resonant frequency. At frequencies below 200 - 300 MHz. the resonators can be constructed from discrete components (i.e. separate capacitors and inductors). Tuning involves changing the resonant frequency of the reactance by changing the values of the discrete components. At higher frequencies a more distributed layout is required because the inherent reactances of all circuit components become more significant at higher frequencies. At higher frequencies, resonators utilizing a monoblock design are commonly used.
  • a high frequency resonator is essentially a transmission medium with impedance discontinuities at both of its ends. Reflections at these discontinuities causes energy to build up within the resonator, a fraction of which is released during each cycle.
  • a quality factor, Q is defined as the ratio of the energy stored within the resonator to that dissipated during one cycle. Due to boundary conditions that must be obeyed by the electric and magnetic fields, only signals with wavelengths that divide the length of the resonator by certain discrete multiples will be maximally reflected and constructively interfere. These correspond to the resonant frequencies. Typically, the resonator is made sufficiently short such that only one resonant frequency exists within the frequency range to be filtered. Signals at other frequencies are increasingly transmitted to ground as their frequency difference from the resonance frequency increases, resulting in significant signal attenuation outside the passband.
  • the wavelength at a particular frequency within a particular transmission medium is a function of the reactance of that medium.
  • the resonant frequency is changed by changing the length of the resonator as measured with respect to the wavelength of the signal such that the constructive interference underlying resonance occurs at the new resonance frequency.
  • Electrical tuning can be accomplished either by changing the functional dependence of the local wavelength on the frequency or by changing the electrical length of the resonator.
  • the wavelength dependence on frequency within a transmission medium is a function of the reactance of the medium.
  • This functional dependence of the wavelength is varied in YIG (Yttrium-Iron Garnet) resonators with the application of a variable magnetic field. But such resonators are expensive, require bulky magnetic field generating coils, and are unsuited for the low power, low profile, low cost requirements of mobile communication systems.
  • bulk f-e resonators may require the application of rather high control voltages considering the relatively large geometries involved.
  • electrical tuning can also be accomplished by changing the electrical length of the resonator. This is accomplished in the prior art via the use of varicaps in which one or more varactor diode is coupled to one end of the resonator. This arrangement electrically extends that end of the resonator because the capacitance of the varactor prevents that end from being either totally closed or totally open. Varactors provide a variable capacitance as a function of an applied dc voltage, and therefore changes the length of the resonator in response to changes in the voltage. But they are noisy, temperature dependent and have low Q's at UHF and above.
  • the invention is a tunable bandpass filter comprising: at least one resonator having a reactance with a resonant frequency, a ferroelectric f-e film having a dielectric constant with a value that changes with an applied electric field, and an electric field generating device for generating relatively constant electric fields of different strengths.
  • the ferroelectric film is electrically coupled to the resonator so that the reactance of the resonator and therefore the resonant frequency of the resonator and the passband of the filter depends on the dielectric constant of the ferroelectric film.
  • the electric field generating device is constructed and arranged to generate relatively constant electric fields within the ferroelectric film, thereby making the resonant frequency of the resonator and the passband of the filter a function of the strength of the relatively constant electric field.
  • the relative permittivity, ⁇ r which determines the dielectric constant of a dielectric may be varied in f-e materials under the application of a slowly varying ("near DC") electric field (E-field).
  • E-field a slowly varying electric field
  • the loss tangent of bulk f-e dielectrics is significant, that of applicable f-e thin or thick films fabricated on a wide range of microwave ceramics may be much better, approximating that of some commonly used microwave ceramics. Therefore, rather than use a varactor or bulk f-e dielectrics for electrical tuning, thin f-e films may be used to modify the local capacitance of the transmission medium and thereby provide an adjustable reactance that changes the resonant frequency of the resonator.
  • these f-e capacitors When properly designed and fabricated, these f-e capacitors may provide a higher capacitance and Q than varactors at frequencies above 1 GHz. They are available as thin or thick films and are ideal for tuning distributed or lumped element resonators. Their electrical properties from lot-to-lot are also more consistent than that of varactors.
  • Thin/thick f-e films are widely used in high temperature superconductivity work, and there are several hundred of such known materials. Film thicknesses on the order of 0.1 ⁇ m to 1 mm are typical. Barium strontium titanate, Ba x Sr( 1-x )TiO 3 (BSTO) is the most popular for room temperature operation where x is preferably between 0.3 and 0.7. Their tuning speed is about 0.3 - 1.0 ⁇ s for an applied constant E-field, so they are not modulated by a rf signals. An applied dc voltage V dc is generally used to create the E-field. It is not uncommon to have films with ⁇ r / ⁇ V dc > 3.
  • Fig. 2 is an example of a microstrip resonator 200 comprised of a microstrip filament layer 202, a ground plane 204, and a dielectric substrate 206.
  • a f-e film layer 208 is positioned between the microstrip filament layer and the dielectric substrate.
  • the wavelength of a propagated signal is a function of the dielectric constant of the transmission medium of the resonator and is therefore a function of the relative permittivity of the f-e film 208.
  • a voltage applied by a dc voltage source 210 positively biases the microstrip filament 202 with respect to the ground plane 204, and creates an electric field (E-tield) 212 across the f-e film that changes of the film and therefore the resonant frequency of the resonator.
  • the voltage is controlled by external control signal 214.
  • Fig. 3 is a first example of a coplanar waveguide 300 comprised of a central conductor 302, two grounded outer conductors 304, a ground plane 322, and a dielectric substrate 306.
  • An f-e film layer 308 is positioned between the stripline conductors 302 and 304, and the dielectric substrate.
  • a voltage applied by the dc voltage source 310 positively biases the central conductor with respect to the two outer conductors and creates an electric field (E-field) 312 across the f-e film, but in this case the choice of bias arrangement is better than that of Fig. 2 because the E-field 312 is more concentrated within the f-e film and is therefore greater for the same voltage and substrate thickness.
  • the voltage is controlled by external control signal 314.
  • Fig. 4 is an example of a dielectric loaded waveguide (DLWG) resonator filter 400.
  • An input signal introduced via input port 416 resonates at the resonant frequency within a first half of the waveguide 424 and is coupled via 2 nd order aperture 420 to a second half of the waveguide 426, which having the same resonant frequency, combine to form a second order filter.
  • An output signal is taken via output port 418.
  • the body of the filter, formed on substrate 406, is comprised of a high ⁇ r dielectric 402.
  • An f-e film 408, shown mounted on the surfaces parallel to the x-y plane at the aperture, is overlaid by conducting planes 422.
  • a voltage applied between the two conducting planes 422 generates an E-field within the f-e film 408 that changes its reactance, resulting in a change of the resonant frequency within the waveguide.
  • the voltage applied by dc voltage source 410 is controlled by control signal 414.
  • the f-e film 408 and conducting planes 422 could also be mounted on the surfaces parallel to the x-y plane.
  • a DLWG resonator can provide a Q of about 1000 within the PCS band (i.e. around 2 GHz) with an I.L. of about 1.6 dB at a 3dB bandwidth of 10 MHz.
  • Fig. 5 shows a second example of a stripline resonator 600 comprised of a central conductor 602, two grounded outer conductors 604, and a dielectric substrate 606.
  • the f-e film 608 is mounted between the central conductor 602 and the dielectric substrate 606.
  • a dc voltage source 610 controlled by control signal 614 is applied between the central conductor 602 and the two outer conductors 604 so as to generate an E-field within the f-e film and thereby dynamically adjust the resonant frequency of the resonator 600.
  • a stripline resonator can provide a Q of about 750 within the PCS band with an I.L. of about 2.2 dB at a 3dB bandwidth of 6 MHz.
  • Filter tuning with f-e films can also be implemented according to a similar scheme as that described for tuning with varactors where tuning is accomplished by adjusting the effective electrical length of one end of the resonator.
  • the film is coupled to the transmission medium by mounting it as an overlay capacitor as illustrated for the overlay capacitor coupled resonator 700 shown in Fig. 6 .
  • the basic resonator 701 which can be coaxial, stripline or microstrip, is mounted atop a ceramic substrate 706 with an underlying rf ground plane 704.
  • An f-e film layer 708 of thickness d is positioned towards one end of the resonator and sandwiched between the resonator's grounded outer layer and an overlaid metal layer 722, thereby forming the overlay capacitor.
  • Coupling to such a resonator can be achieved by either electromagnetic coupling, capacitive coupling, or by a direct tap into and out of the resonator (or filter) structure.
  • F-e thin film layers of about 1 micro-meter seem to provide high dc R fields for a given (small) dc voltage.
  • both ends of the resonators inner conductor 702 can be grounded as shown.
  • a dc voltage source 710 controlled by control signal 714 generates the E-field used to adjust the capacitance of the overlay capacitor.
  • Direct f-2 thin film deposition can be done on some substrates, or with buffer layers on others.
  • the packaging of an f-3 device may eliminate the need for a substrate.
  • multiple resonators can be electrically coupled to obtain a higher order filter with a filter transfer function that, while centered about the same resonant frequency as that of the resonator, has a more abrupt cutoff and a flatter peak than each individual resonator's transfer function.
  • a number of different filter topologies utilizing different resonator types are possible.
  • Popular topologies utilizing stripline and microstrip resonators include interdigitated filters, combline filters, and edge coupled and hairpin filters.
  • Fig. 7 is the top view of an example of an interdigitated filter topology utilizing f-e film electrical tuning in which the wavelength-frequency relationship within the resonator is varied.
  • the input signal via transmission line 802 is electromagnetically coupled to each resonator in turn as it travels across the resonators (vertically in the figure), and is output via transmission line 806.
  • Each resonator has one capacitively loaded and one shorted end. The relative placement of which is alternated for adjacent filter.
  • the resonance frequency of the resonator is electrically adjusted as described above for f-e film electrical tuning utilizing the wavelength-frequency relationship adjustment.
  • Fig. 8 shows the same topology as that of Fig. 7 but with tuning achieved via the use of overlay capacitors 908 coupled to what would otherwise have been the open end of the resonators 904.
  • Fig. 9 is the top view of an example of a second order electromagnetically coupled planar combline filter topology utilizing overlay capacitors 1008.
  • the signal input via transmission line 1002 is electromagnetically coupled to each resonator in turn as it travels across the resonators 1004 (horizontally in the figure), and is outputted via transmission line 1006.
  • Such a filter may have a 10 mhz bandwidth in the PCS band. With a 20 mil thick MgO substrate, no buffer layer may be needed.
  • the structure of the resonators is not limited to that shown in Figs. 2-6 .
  • Any resonator structure where an f-e film is coupled to the transmission medium is contemplated by the invention.
  • the f-e film could be mounted on one or more outside surface of the coaxial or stripline resonator similarly to the arrangement shown in Fig. 4 for the DLWG resonator.
  • the f-e layers need not be limited to coupling apertures of the DLWG shown in Fig. 4 .
  • f-e film can be deposited on the I/O (Input/Output) surfaces on the waveguide as well as on one or more surfaces on the outside.
  • Fig. 10 is a table generally illustrating some of the design options, benefits and issues associated with a variety of f-e device designs. Designs, 3, 4 and 5 generally range from minimum insertion loss, maximum size to minimum size maximum insertion loss.

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  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Control Of Motors That Do Not Use Commutators (AREA)
  • Networks Using Active Elements (AREA)
  • Piezo-Electric Or Mechanical Vibrators, Or Delay Or Filter Circuits (AREA)
  • Oscillators With Electromechanical Resonators (AREA)
EP10185327.3A 2001-09-27 2002-09-27 Elektrisch abstimmbare Bandpassfilter Expired - Lifetime EP2309586B1 (de)

Applications Claiming Priority (4)

Application Number Priority Date Filing Date Title
US32570101P 2001-09-27 2001-09-27
US41300902P 2002-09-23 2002-09-23
EP02778409A EP1433219B1 (de) 2001-09-27 2002-09-27 Elektrisch abstimmbare bandpassfilter
EP09177702.9A EP2164129B1 (de) 2001-09-27 2002-09-27 Elektrisch abstimmbare Bandpassfilter

Related Parent Applications (2)

Application Number Title Priority Date Filing Date
EP02778409.9 Division 2002-09-27
EP09177702.9 Division 2009-12-02

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EP2309586A1 true EP2309586A1 (de) 2011-04-13
EP2309586B1 EP2309586B1 (de) 2014-01-01

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EP09177702.9A Expired - Lifetime EP2164129B1 (de) 2001-09-27 2002-09-27 Elektrisch abstimmbare Bandpassfilter
EP10185327.3A Expired - Lifetime EP2309586B1 (de) 2001-09-27 2002-09-27 Elektrisch abstimmbare Bandpassfilter
EP02778409A Expired - Lifetime EP1433219B1 (de) 2001-09-27 2002-09-27 Elektrisch abstimmbare bandpassfilter

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EP (3) EP2164129B1 (de)
JP (1) JP4071712B2 (de)
KR (2) KR101250060B1 (de)
CN (1) CN1592985A (de)
AT (1) ATE473528T1 (de)
BR (1) BR0212843A (de)
CA (1) CA2461886A1 (de)
DE (1) DE60236947D1 (de)
IL (1) IL161064A0 (de)
MX (1) MXPA04002907A (de)
NO (1) NO20041903L (de)
RU (1) RU2004112757A (de)
WO (1) WO2003028146A1 (de)

Families Citing this family (7)

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Publication number Priority date Publication date Assignee Title
WO2005091429A1 (en) * 2004-03-19 2005-09-29 Huawei Technologies Co., Ltd. A method for providing ability of tuning resonance frequency for different applications
CN100392910C (zh) * 2005-11-25 2008-06-04 中国科学院物理研究所 一种铁电薄膜可调带通滤波器
US8207907B2 (en) * 2006-02-16 2012-06-26 The Invention Science Fund I Llc Variable metamaterial apparatus
WO2010125806A1 (ja) * 2009-04-28 2010-11-04 日本電気株式会社 導波管フィルタ、通信アクセス装置
US20100295634A1 (en) 2009-05-20 2010-11-25 Tamrat Akale Tunable bandpass filter
JP6685643B2 (ja) * 2013-12-18 2020-04-22 スカイワークス ソリューションズ, インコーポレイテッドSkyworks Solutions, Inc. 同調可能な共振器システム、同調可能な共振器システムを含むフィルタリングシステム、および同調可能な共振器システムを形成する方法
RU189237U1 (ru) * 2018-02-07 2019-05-16 Федеральное государственное бюджетное научное учреждение "Федеральный исследовательский центр "Красноярский научный центр Сибирского отделения Российской академии наук" Сверхширокополосный полосковый фильтр

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US325701A (en) 1885-09-08 sharpneck
US3192397A (en) * 1960-11-30 1965-06-29 Ibm Bistable circuit having an adjustable phase shifter responsive to output signal
US5241291A (en) * 1991-07-05 1993-08-31 Motorola, Inc. Transmission line filter having a varactor for tuning a transmission zero
EP0590612A1 (de) * 1992-09-29 1994-04-06 Matsushita Electric Industrial Co., Ltd. Frequenzabstimmbarer Resonator mit einem Varaktor
WO1994028592A1 (en) * 1993-05-27 1994-12-08 E.I. Du Pont De Nemours And Company High tc superconductor/ferroelectric tunable microwave circuits
FR2714217A1 (fr) * 1993-12-17 1995-06-23 Thomson Csf Filtre hyperfréquence à résonateurs couplés accordés par des capacités variables, à structure triplaque et à agilité de fréquence.
EP0843374A2 (de) * 1996-11-19 1998-05-20 Sharp Kabushiki Kaisha Spannungsgeregeltes Passbandfilter und hochfrequentes Schaltungsmodul mit solch einem Filter
US5900390A (en) * 1994-09-20 1999-05-04 Das; Satyendranath Ferroelectric tunable coaxial filter
US5908811A (en) * 1997-03-03 1999-06-01 Das; Satyendranath High Tc superconducting ferroelectric tunable filters
US5935910A (en) * 1994-08-16 1999-08-10 Das; Satyendranath High power superconductive filters

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DE3201064A1 (de) * 1982-01-15 1983-07-28 Hoechst Ag, 6230 Frankfurt "verfahren zur herstellung von natriumhydrogensulfat"
WO1994013028A1 (en) * 1992-12-01 1994-06-09 Superconducting Core Technologies, Inc. Tunable microwave devices incorporating high temperature superconducting and ferroelectric films
US5617104A (en) 1995-03-28 1997-04-01 Das; Satyendranath High Tc superconducting tunable ferroelectric transmitting system

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US325701A (en) 1885-09-08 sharpneck
US3192397A (en) * 1960-11-30 1965-06-29 Ibm Bistable circuit having an adjustable phase shifter responsive to output signal
US5241291A (en) * 1991-07-05 1993-08-31 Motorola, Inc. Transmission line filter having a varactor for tuning a transmission zero
EP0590612A1 (de) * 1992-09-29 1994-04-06 Matsushita Electric Industrial Co., Ltd. Frequenzabstimmbarer Resonator mit einem Varaktor
WO1994028592A1 (en) * 1993-05-27 1994-12-08 E.I. Du Pont De Nemours And Company High tc superconductor/ferroelectric tunable microwave circuits
FR2714217A1 (fr) * 1993-12-17 1995-06-23 Thomson Csf Filtre hyperfréquence à résonateurs couplés accordés par des capacités variables, à structure triplaque et à agilité de fréquence.
US5935910A (en) * 1994-08-16 1999-08-10 Das; Satyendranath High power superconductive filters
US5900390A (en) * 1994-09-20 1999-05-04 Das; Satyendranath Ferroelectric tunable coaxial filter
EP0843374A2 (de) * 1996-11-19 1998-05-20 Sharp Kabushiki Kaisha Spannungsgeregeltes Passbandfilter und hochfrequentes Schaltungsmodul mit solch einem Filter
US5908811A (en) * 1997-03-03 1999-06-01 Das; Satyendranath High Tc superconducting ferroelectric tunable filters

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Title
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LIANG X-P ET AL: "HYBRID RESONATOR MICROSTRIP LINE ELECTRICALLY TUNABLE FILTER", 2001 IEEE MTT-S INTERNATIONAL MICROWAVE SYMPOSIUM DIGEST.(IMS 2001). PHOENIX, AZ, MAY 20 - 25, 2001, IEEE MTT-S INTERNATIONAL MICROWAVE SYMPOSIUM, NEW YORK, NY: IEEE, US, vol. 3 OF 3, 20 May 2001 (2001-05-20), pages 1457 - 1460, XP001067495, ISBN: 0-7803-6538-0 *

Also Published As

Publication number Publication date
EP2164129A1 (de) 2010-03-17
RU2004112757A (ru) 2005-03-27
KR20090074274A (ko) 2009-07-06
DE60236947D1 (de) 2010-08-19
EP1433219A1 (de) 2004-06-30
EP2309586B1 (de) 2014-01-01
EP1433219B1 (de) 2010-07-07
KR101250060B1 (ko) 2013-04-03
NO20041903L (no) 2004-06-15
CN1592985A (zh) 2005-03-09
BR0212843A (pt) 2005-06-28
JP4071712B2 (ja) 2008-04-02
KR20040037175A (ko) 2004-05-04
JP2006503445A (ja) 2006-01-26
MXPA04002907A (es) 2004-07-05
KR101036117B1 (ko) 2011-05-23
EP2164129B1 (de) 2013-07-17
IL161064A0 (en) 2004-08-31
CA2461886A1 (en) 2003-04-03
WO2003028146A1 (en) 2003-04-03
ATE473528T1 (de) 2010-07-15

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