EP1906484A1 - Capacité distribuée dans des lignes à ruban, filtres, transformateurs, résonateurs et combinateurs - Google Patents

Capacité distribuée dans des lignes à ruban, filtres, transformateurs, résonateurs et combinateurs Download PDF

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Publication number
EP1906484A1
EP1906484A1 EP06425668A EP06425668A EP1906484A1 EP 1906484 A1 EP1906484 A1 EP 1906484A1 EP 06425668 A EP06425668 A EP 06425668A EP 06425668 A EP06425668 A EP 06425668A EP 1906484 A1 EP1906484 A1 EP 1906484A1
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EP
European Patent Office
Prior art keywords
track
transmission line
profile
portions
capacitive component
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP06425668A
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German (de)
English (en)
Inventor
Carlo Delvecchio
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Selex Elsag Datamat SpA
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Selex Communications SpA
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Filing date
Publication date
Application filed by Selex Communications SpA filed Critical Selex Communications SpA
Priority to EP06425668A priority Critical patent/EP1906484A1/fr
Publication of EP1906484A1 publication Critical patent/EP1906484A1/fr
Withdrawn legal-status Critical Current

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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P3/00—Waveguides; Transmission lines of the waveguide type
    • H01P3/02—Waveguides; Transmission lines of the waveguide type with two longitudinal conductors
    • H01P3/08—Microstrips; Strip lines
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/20—Frequency-selective devices, e.g. filters
    • H01P1/201—Filters for transverse electromagnetic waves
    • H01P1/203—Strip line filters
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/20—Frequency-selective devices, e.g. filters
    • H01P1/201—Filters for transverse electromagnetic waves
    • H01P1/203—Strip line filters
    • H01P1/2039—Galvanic coupling between Input/Output
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P5/00—Coupling devices of the waveguide type
    • H01P5/12—Coupling devices having more than two ports
    • H01P5/16—Conjugate devices, i.e. devices having at least one port decoupled from one other port
    • H01P5/18—Conjugate devices, i.e. devices having at least one port decoupled from one other port consisting of two coupled guides, e.g. directional couplers
    • H01P5/184—Conjugate devices, i.e. devices having at least one port decoupled from one other port consisting of two coupled guides, e.g. directional couplers the guides being strip lines or microstrips

Definitions

  • the present invention relates to transmission lines in the form of conductive strips for microwaves, and in particular to microstrip lines for power applications intended for the use of radio frequency and microwave filters and components.
  • the invention relates to a conductive strip transmission line according to the preamble of Claim 1, and to electromagnetic structures and circuit arrangements based on conductive strip transmission lines.
  • microwave radar transmitters for which a non-negligible quantity of energy is dispersed in frequency components different from the carrier frequency or from the conventional sideband modulation components. At the output of these devices it is therefore necessary to provide power filters for transmitting the useful carrier frequency while suppressing the spurious emissions.
  • the first step in the design of a filter is the definition of the circuit parameters according to the required filter characteristic.
  • Low-pass filters and wideband bandpass filters operating in the frequency range from 100 MHz to 10 GHz, and therefore having distributed parameters, are conveniently made from short portions of transmission lines which approximate to lumped circuit components.
  • Figure 1 shows, by way of example, the equivalent T and ⁇ circuits of a portion of TEM mode transmission line, ideally non-dispersive.
  • the equivalent reactance (X) and susceptance (B) are given by: X 2 ⁇ Z 0 ⁇ ⁇ ⁇ l 2 ⁇ ⁇ B ⁇ Y 0 ⁇ ⁇ ⁇ l ⁇ for the T circuit, and by: X ⁇ Z 0 ⁇ ⁇ ⁇ l ⁇ B 2 ⁇ Y 0 ⁇ ⁇ ⁇ l 2 ⁇ ⁇ for the ⁇ circuit, in which Z 0 is the characteristic impedance of the line, ⁇ is the pulsation and ⁇ is the field propagation velocity along the line.
  • a short portion of line with a high characteristic impedance, in the approximation in which the length of the portion is much less than the propagation wavelength of the radiation, is the most common implementation of a serial inductance, and a short portion of line with a low characteristic impedance, again in the aforesaid approximation, is the most common implementation of a parallel capacitor, particularly in microwave filters for circuits operating in TEM modes.
  • a conventional low-pass filter therefore consists of a sequence of portions as shown in Figure 2a, while a conventional bandpass filter is shown in Figure 2b, in which the length and spacing of the stubs determines the frequency behaviour.
  • Microstrip transmission lines have intrinsic limitations in respect of the maximum transmissible power level.
  • microstrip line to sustain high-power signals, such as pulsed signals of brief duration (of the order of a few tens of microseconds) with a low mean power level but peaks of high pulse power, depends on its configuration, and in particular is limited by the phenomenon of impact ionization and consequent breakdown, in air or in the dielectric.
  • the breakdown phenomenon occurs when the electrical field in the proximity of the edges of the line is greater than the limit field supported by the dielectric in which the discharge takes place.
  • the discharge in this case is known as a "no-electrode" discharge, since many of the free electrons undergo numerous cycles of oscillation (and collisions) before reaching an electrode.
  • the minimum intensity of the breakdown field is found at a field radio frequency equal to the collision frequency of the gas forming the atmosphere of the medium in which the line is located.
  • the maximum transfer of energy between the electromagnetic field and the gas subject to breakdown is produced in this condition.
  • the critical pressure at which the discharge occurs can be calculated approximately by means of the equation p ⁇ ⁇ ⁇ 47.4 Pa ⁇ m
  • the probability of discharge also depends on the electrical field intensity (due to geometrical factors) and increases with a decrease in the pressure of the aforesaid gas.
  • the electrical field value for which a breakdown occurs in air and at a pressure of 760 mmHg (or 1 atm) is approximately 3 kV/mm, this value decreasing at low pressures, in accordance with the preceding equation.
  • the electrical breakdown field strength is greater by an order of magnitude than that of air, for example 30 kV/mm for FR4 material and 15 kV/mm for alumina.
  • the rigidity values of the dielectric materials are such that the discharge phenomena take place predominantly in the air surrounding the microstrip.
  • Microstrip power circuits including filters for the elimination of the spurious components at the undesired frequencies have geometries which promote the development of the breakdown phenomenon (see Figures 2a and 2b) and are difficult to use for carrying power in excess of a peak value of 1 kW.
  • the object of the present invention is to avoid the drawbacks of the known art by providing a conductive strip circuit configuration which limits the development of the breakdown phenomenon as much as possible.
  • this object is achieved by means of a conductive strip transmission line having the characteristics claimed in Claim 1.
  • the invention also proposes electromagnetic structures and circuit arrangements such as a low-pass filter, a bandpass filter, a ⁇ /4 transformer and a parallel LC resonator, comprising transmission lines according to the invention.
  • the present invention is based on the principle of replacing the rectangular shapes of the capacitive components of a conventional conductive strip transmission line, such as a microstrip line, with geometries free of angular points, in other words track areas with a polygonal profile with rounded angles, or with a wholly curved profile.
  • these track areas can be formed by any two-dimensional domain having a diameter of less than ⁇ g /4, where ⁇ g denotes the radiation propagation wavelength in the transmission line in question for which the area shows capacitive and non-resonant behaviour. Otherwise, track areas with a diameter in the range from ⁇ g /4 to ⁇ g would act as resonators.
  • the conductive track area of the capacitive component is a regular geometrical figure, for example a circular or elliptical configuration (generally referred to as areas whose profile is a closed conic section), for which it is possible to determine - at least approximately - an analytical formula for the characteristic impedance as a function of the geometrical parameters of the figure.
  • the innovative layout reduces the probability of impact ionization and thus limits the consequent breakdown phenomenon in the dielectric.
  • the strength of the electrical field which would otherwise be present in the angular points of microstrip lines is reduced by a factor of approximately 2.
  • the capacitive component according to the invention can be connected to one or more track portions of an electromagnetic structure or circuit arrangement by portions of its profile separated by a predetermined angle, for example diametrically opposed portions.
  • the proposed circuit configurations are a low-pass filter including at least one LC cell with distributed parameters, a bandpass filter including at least one LC resonant cell with distributed parameters, a ⁇ /4 transformer, a parallel LC resonator, a 90 degree hybrid divider/combiner and a Wilkinson divider, all comprising capacitive components with a conductive track area in the form of a pad with a profile free of angular points.
  • the proposed geometries improve the power carrying capacity of a microstrip circuit, for example one comprising low-pass filters for eliminating the spurious frequency components, reducing the electrical field strength around the line, and thus increasing the maximum transmissible power at which the breakdown phenomenon occurs. It has been found experimentally that the transmission lines proposed by the invention can support power levels at least twice those supported by conventional lines, up to a peak of approximately 3 kW.
  • Figures 2a and 2b show, respectively, a low-pass filter and a conventional bandpass filter in a planar microstrip circuit, constructed from short portions of transmission lines which can be represented by the equivalent T and ⁇ circuits of Figure 1, which have already been discussed in the introductory part of this description and are therefore not described further.
  • Figure 3 shows an embodiment of a low-pass filter 10 according to the invention in a planar microstrip circuit, operating at frequencies of the order of GHz, including a plurality of LC cells with distributed parameters, each cell comprising, in combination, an inductive component including a straight track portion, and a capacitive component with a circular configuration, in series with the inductive portion.
  • the circular track area 12 of the capacitive components is connected to the straight inductive track portions 14 for the input and output of the propagation mode guided by the line, through two diametrically opposed profile portions 12a.
  • the characteristic impedance of the capacitive component in the form of a portion of transmission line, can be calculated from the approximate analytical formulae 377 ⁇ 2 ⁇ R h ⁇ 3 ⁇ ⁇ r , SUB ⁇ r , SUB ⁇ 2 and 377 ⁇ 2 ⁇ R h ⁇ 3 2 ⁇ ⁇ r , SUB + 1 ⁇ r , SUB > 2
  • R is the radius of the circular track area
  • h is the thickness of the dielectric material
  • ⁇ r,SUB is the dielectric constant of the substrate.
  • An analytical formula for the approximate evaluation of the upper power limit which can be transmitted in such a structure is as follows: P 2 ⁇ h 2 KW inc 2 ⁇ 25 ⁇ R h ⁇ 3 2 ⁇ ⁇ r , SUB + 1 ⁇ t 2 ⁇ h 0.01
  • P is the peak power measured in kW
  • R is the radius of the circular track area
  • h is the thickness of the dielectric material
  • t is the thickness of the conductive strip
  • ⁇ r,SUB is the dielectric constant of the substrate.
  • Such a low-pass filter configuration can also be produced by using capacitive components with an elliptical track area (not shown), connected to the inductive straight track portions by means of two diametrically opposed profile portions located at the vertices of the elliptical profile curve of the area.
  • a bandpass filter 20 in a planar microstrip circuit includes a plurality of series LC resonant cells with distributed parameters comprising a main straight track portion 21, from which stubs, each including a capacitive component, branch off.
  • the track area 22 of the capacitive component is connected to the end of a straight track portion 24 belonging to the stub via a profile portion 22a.
  • a conductive strip transmission line in which the capacitive component with distributed parameters are represented by pads having the aforementioned shapes, can conveniently be used in applications which require printed capacitors or resonator circuits with low characteristic impedance.
  • Figure 5 shows an embodiment of a ⁇ /4 transformer 30 in a planar microstrip circuit, which includes a pair of capacitive components of circular configuration, whose track areas 32 are interconnected by means of a lumped inductive component 34.
  • Figure 6 shows an embodiment of a parallel LC resonator 40 in a planar microstrip circuit, which includes a capacitive component with a track area 42 of circular configuration, connected via first diametrically opposed profile portions 42a to a pair of inductive straight track portions 44 connected to a ground plane GND.
  • the resonator configuration can be connected to portions of a main track 46 for the propagation of a mode, at second profile portions 42b of the track area 42 of the capacitive component, intermediate between the first portions 42a.
  • the resonator can be produced by connecting the track area 42 of the capacitive component to only one inductive straight track portion 44, the resonator configured in this way being connectable to a main track portion 46 for propagating the mode at a profile portion 42b of the track area 42 diametrically opposed to the profile portion 42a through which the aforesaid track area is connected to the inductive track portion 44.
  • Figure 7a shows an embodiment of a wide-band 90 degree hybrid divider/combiner circuit 50 made in microstrip planar technology, which includes capacitive components with track areas of circular configuration, connected to inductive track portions and to lumped inductive components.
  • the 90 degree divider/combiner circuit has a pair of input ports IN1 and IN2, the second of which is closed on to a matched impedance in the divider configuration illustrated here, and a pair of output ports OUT1 and OUT2. Between the input ports and the output ports, the circuit has a pair of meshes with distributed parameters, including track portions which approximate to lumped components.
  • the meshes include a pair of branches for direct connection between an input port and an output port (the horizontal branches in the arrangement shown in the figure), and transverse branches between the direct connection branches (vertical in the arrangement shown in the figure).
  • Each of the direct connection branches comprises a pair of terminal circular track areas 52', forming capacitive components with distributed parameters, connected, to an input port and to an output port of the circuit, respectively, and an intermediate circular track area 52'' connected to the terminal track areas via ⁇ /4 inductive track portions 54' (with reference to the central operating frequency) consisting of a sequence of straight segments arranged in a tortuous path.
  • the transverse branches which connect the terminal track areas 52' consist of an air-cored conducting wire 54'' forming a lumped inductive component, while the transverse branch which connects the intermediate track areas 52'' is another ⁇ /4 inductive track portion 54' consisting of a sequence of straight segments arranged in a tortuous path.
  • Each of the terminal track areas 52' is connected to the adjoining input/output port and to the track portions 54' of the corresponding connecting branch at profile portions.
  • the intermediate track areas 52" have diametrically opposed profile portions for connection to the track portions 54' of the direct connecting branch, and a profile portion for connection to the transverse track portion 54' which is intermediate between the preceding portions, in other words separated from them by an angle of 90 degrees.
  • Capacitive components with distributed parameters and a smaller capacitance correspond to circular track areas with a smaller diameter.
  • the track areas 52' have a diameter of 5 mm each
  • the track areas 52" have a diameter of 7.5 mm each
  • the whole circuit has overall dimensions of 4 x 3 cm, excluding the connectors.
  • the capacitive components with distributed parameters are made from track areas (or transmission line portions) 52', 52" in the form of circular areas rather than square or rectangular areas
  • the aforesaid circuit has a reduced number of angles of the planar track configuration, which would concentrate the electrical field and promote the initiation of breakdown, as compared with the prior art.
  • Square or rectangular track areas with a capacitive effect and with dimensions suitable for the use of the aforesaid circuit would have their shapes circumscribed on the circular area actually constructed, and would also result in a higher consumption of conductive material.
  • the illustrated circuit can overcome the construction problems which would require the provision at this position of a ⁇ /4 track portion with distributed parameters and with the necessary impedance, which would require a very narrow track, of the order of hundredths of a millimetre, which cannot be produced by present-day technological processes.
  • FIG. 8a Another example of a circuit embodiment based on the transmission lines proposed by the invention is the Wilkinson divider configuration shown in Figure 8a, the equivalent circuit of which being shown in Figure 8b.
  • the Wilkinson divider circuit indicated by the numeral 60 in the figure, comprises two ⁇ /4 lines formed by capacitive components of circular configuration whose track areas 62', 62" are interconnected via corresponding inductive components 64, which can be made with distributed parameters as printed track portions (as shown in the figure, for example) or as lumped elements, as air-cored windings.
  • the two ⁇ /4 lines have a common first track area 62' of greater surface area, and the second track areas with a smaller surface area 62'' are interconnected by a lumped resistor 65.
  • the track area 62' of greater surface area is formed by the collapse of two track areas similar to the track areas 62", and has a surface area approximately twice as large as the surface area of the track area 62''.
  • the embodiment with circular transmission line portions not only supports a higher power transmission level, as mentioned above for the other configurations described, but also provides further advantages from the electromagnetic and architectural point of view.
EP06425668A 2006-09-28 2006-09-28 Capacité distribuée dans des lignes à ruban, filtres, transformateurs, résonateurs et combinateurs Withdrawn EP1906484A1 (fr)

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Application Number Priority Date Filing Date Title
EP06425668A EP1906484A1 (fr) 2006-09-28 2006-09-28 Capacité distribuée dans des lignes à ruban, filtres, transformateurs, résonateurs et combinateurs

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Application Number Priority Date Filing Date Title
EP06425668A EP1906484A1 (fr) 2006-09-28 2006-09-28 Capacité distribuée dans des lignes à ruban, filtres, transformateurs, résonateurs et combinateurs

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EP1906484A1 true EP1906484A1 (fr) 2008-04-02

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Cited By (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2011003724A1 (fr) * 2009-07-07 2011-01-13 Thales Coupleur de wilkinson intégré dans un circuit imprimé et dispositif hyperfréquence comportant un tel coupleur
RU2474041C1 (ru) * 2012-01-17 2013-01-27 Открытое акционерное общество Центральное конструкторское бюро аппаратостроения Синфазный делитель мощности с неравным делением
CN103560309A (zh) * 2013-10-14 2014-02-05 西安交通大学苏州研究院 正弦加窗型电磁带隙带阻滤波器
EP2747192A1 (fr) * 2012-12-20 2014-06-25 Microelectronics Technology Inc. Filtre passe-bande avec configuration de boucle
WO2014091458A3 (fr) * 2012-12-13 2014-11-06 Poynting Antennas (Pty) Limited Agencement d'antennes à plaque à double polarisation
WO2017032879A1 (fr) * 2015-08-27 2017-03-02 Kathrein Mobilcom Austria Gmbh Filtre hf de type à cavité pourvu d'une ligne de dérivation de signaux et de tensions à basses fréquences

Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3769617A (en) * 1971-12-09 1973-10-30 Rca Corp Transmission line using a pair of staggered broad metal strips
US5043682A (en) * 1990-03-02 1991-08-27 The United States Of America As Represented By The United States Department Of Energy Printed circuit dispersive transmission line
EP0660438A2 (fr) * 1993-12-27 1995-06-28 Matsushita Electric Industrial Co., Ltd. Résonateur et élément de circuit hyperfréquence l'utilisant
US5600740A (en) * 1995-06-20 1997-02-04 Asfar; Omar R. Narrowband waveguide filter

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3769617A (en) * 1971-12-09 1973-10-30 Rca Corp Transmission line using a pair of staggered broad metal strips
US5043682A (en) * 1990-03-02 1991-08-27 The United States Of America As Represented By The United States Department Of Energy Printed circuit dispersive transmission line
EP0660438A2 (fr) * 1993-12-27 1995-06-28 Matsushita Electric Industrial Co., Ltd. Résonateur et élément de circuit hyperfréquence l'utilisant
US5600740A (en) * 1995-06-20 1997-02-04 Asfar; Omar R. Narrowband waveguide filter

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
NEMAI CHANDRA KARMAKAR ET AL: "Investigations Into Nonuniform Photonic-Bandgap Microstripline Low-Pass Filters", IEEE TRANSACTIONS ON MICROWAVE THEORY AND TECHNIQUES, IEEE SERVICE CENTER, PISCATAWAY, NJ, US, vol. 51, no. 2, February 2003 (2003-02-01), XP011076872, ISSN: 0018-9480 *

Cited By (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2011003724A1 (fr) * 2009-07-07 2011-01-13 Thales Coupleur de wilkinson intégré dans un circuit imprimé et dispositif hyperfréquence comportant un tel coupleur
FR2947959A1 (fr) * 2009-07-07 2011-01-14 Thales Sa Coupleur de wilkinson integre dans un circuit imprime et dispositif hyperfrequence comportant un tel coupleur
RU2474041C1 (ru) * 2012-01-17 2013-01-27 Открытое акционерное общество Центральное конструкторское бюро аппаратостроения Синфазный делитель мощности с неравным делением
WO2014091458A3 (fr) * 2012-12-13 2014-11-06 Poynting Antennas (Pty) Limited Agencement d'antennes à plaque à double polarisation
EP2747192A1 (fr) * 2012-12-20 2014-06-25 Microelectronics Technology Inc. Filtre passe-bande avec configuration de boucle
CN103560309A (zh) * 2013-10-14 2014-02-05 西安交通大学苏州研究院 正弦加窗型电磁带隙带阻滤波器
WO2017032879A1 (fr) * 2015-08-27 2017-03-02 Kathrein Mobilcom Austria Gmbh Filtre hf de type à cavité pourvu d'une ligne de dérivation de signaux et de tensions à basses fréquences

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