EP1629691A1 - Suppression d'oscillation - Google Patents

Suppression d'oscillation

Info

Publication number
EP1629691A1
EP1629691A1 EP04734786A EP04734786A EP1629691A1 EP 1629691 A1 EP1629691 A1 EP 1629691A1 EP 04734786 A EP04734786 A EP 04734786A EP 04734786 A EP04734786 A EP 04734786A EP 1629691 A1 EP1629691 A1 EP 1629691A1
Authority
EP
European Patent Office
Prior art keywords
signal
oscillation
phase
frequency band
feedback
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP04734786A
Other languages
German (de)
English (en)
Inventor
Peter John Blamey
Benjamin John Smith
Brenton Robert Steele
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Dynamic Hearing Pty Ltd
Original Assignee
Dynamic Hearing Pty Ltd
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Priority claimed from AU2003902587A external-priority patent/AU2003902587A0/en
Priority claimed from US10/445,463 external-priority patent/US20040252853A1/en
Application filed by Dynamic Hearing Pty Ltd filed Critical Dynamic Hearing Pty Ltd
Publication of EP1629691A1 publication Critical patent/EP1629691A1/fr
Withdrawn legal-status Critical Current

Links

Classifications

    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04R—LOUDSPEAKERS, MICROPHONES, GRAMOPHONE PICK-UPS OR LIKE ACOUSTIC ELECTROMECHANICAL TRANSDUCERS; DEAF-AID SETS; PUBLIC ADDRESS SYSTEMS
    • H04R25/00—Deaf-aid sets, i.e. electro-acoustic or electro-mechanical hearing aids; Electric tinnitus maskers providing an auditory perception
    • H04R25/45—Prevention of acoustic reaction, i.e. acoustic oscillatory feedback
    • H04R25/453—Prevention of acoustic reaction, i.e. acoustic oscillatory feedback electronically
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04R—LOUDSPEAKERS, MICROPHONES, GRAMOPHONE PICK-UPS OR LIKE ACOUSTIC ELECTROMECHANICAL TRANSDUCERS; DEAF-AID SETS; PUBLIC ADDRESS SYSTEMS
    • H04R3/00—Circuits for transducers, loudspeakers or microphones
    • H04R3/002—Damping circuit arrangements for transducers, e.g. motional feedback circuits
    • H—ELECTRICITY
    • H04—ELECTRIC COMMUNICATION TECHNIQUE
    • H04R—LOUDSPEAKERS, MICROPHONES, GRAMOPHONE PICK-UPS OR LIKE ACOUSTIC ELECTROMECHANICAL TRANSDUCERS; DEAF-AID SETS; PUBLIC ADDRESS SYSTEMS
    • H04R3/00—Circuits for transducers, loudspeakers or microphones
    • H04R3/02—Circuits for transducers, loudspeakers or microphones for preventing acoustic reaction, i.e. acoustic oscillatory feedback

Definitions

  • the present invention relates to oscillation suppression and, more particularly, concerns a method and apparatus for suppressing oscillation in a signal identified as or suspected of containing an oscillation due to feedback.
  • the present invention may be used in conjunction with a suitable approach to identifying such oscillation, such as the method and apparatus for identifying oscillation in a signal due to feedback described in applicant's co-pending international application entided Oscillation Detection', based on Australian provisional patent application AU-2003902588.
  • Acoustic amplifiers are used in many common applications such as telephones, radios, headsets, hearing aids, and public address systems.
  • an application comprises a microphone or other input transducer to pick up sounds and convert them into an electrical signal, an electronic amplifier to increase the power of the electrical signal, and a speaker or other output transducer to convert the amplified electrical signal back into sound.
  • the output acoustic signal may be picked up by the input transducer and fed back into the amplifier with a delay, the delay being the time taken for the sound to travel from the output transducer to the input transducer (plus any delay due to the electrical processing of the signal) .
  • Electrical feedback can also occur if the electrical signal at the output is coupled back to the input, for example by inductive or capacitive coupling. Further, mechanical feedback can also occur if vibrations are transmitted from the output transducer to the input transducer via the body or case of the amplification system.
  • Figure 1 illustrates a feedback loop, showing diagrammatically the components in an acoustic amplifier circuit, namely microphone 1, amplifier 2 and speaker 3, with feedback loop 4 representing the output signal feeding back to the input transducer.
  • Loop Delay N x period (eq. 2)
  • Loop Phase Change 2N ⁇ r radians (eq. 3)
  • Any electronic system containing a microphone and speaker in close proximity may suffer from acoustic feedback. In hearing aids, this often results in the wearer experiencing unpleasant audible effects such as loud whistling tones at certain frequencies, usually high frequencies.
  • the traditional procedure for increasing the stability of a hearing aid is to reduce the gain at high frequencies, as suggested in, for example, US Patent 4,689,818. This may be done by setting the maximum gain value for each frequency, or automatic high frequency (HF) gain roll-off may be used. Controlling feedback by modifying the system frequency response, however, means that the desired high-frequency response of the instrument must be sacrificed in order to maintain stability.
  • HF high frequency
  • a technique commonly used to suppress feedback in public address systems is a frequency shift, in which the input signal is altered by a few Hertz prior to being output at the receiver.
  • This approach has not been particularly successful in hearing aids because a large frequency shift is required to achieve a significant increase in gain.
  • the distance between microphone and receiver is much smaller than in public address systems, and thus a feedback signal with only a small frequency shift may still be relatively closely in phase with the input.
  • Signal phase can also be altered by using a time-varying delay [1]. While this can provide l-2dB of additional useable gain, it can also result in an audible 'warbling' effect.
  • All pass filters have also been used to modify the phase response of the feedback loop, but it can be difficult to achieve satisfactory phase at all frequencies. Methods have been proposed to push danger regions in the phase response to frequencies outside the primary audio range where suppression can be applied without loss of sound quality [2] [3]. These techniques still assume that the feedback path is constant however, and no suggestion has been made that an adaptive implementation may be developed.
  • US Patents 4,232,192 and 4,079,199 propose systems using a phase locked loop (PLL) adapted to recognize an oscillation when it occurs.
  • PLL phase locked loop
  • US Patent 4,845,757 describes another oscillation recognition circuit. This circuit detects oscillations by looking for long-lasting alternating voltages having relatively large amplitude and relatively high frequency. This is problematic in many applications because it means that the signal may contain feedback oscillations for some time before they are identified by such a circuit.
  • the invention provides, in accordance with a first aspect, a method for suppressing oscillation in a signal identified as or suspected of containing an oscillation, the method comprising the following steps: converting the signal into frequency bands in the frequency domain; applying, for a selected period of time, a randomly changing phase to the signal in at least one of said frequency bands; and reconverting the converted signal into an output waveform signal.
  • This method has the effect of disrupting the consistent constructive addition of the feedback signal to the input signal, providing a simple but very effective solution to the suppression problem.
  • said selected period is divided into a series of successive time windows, and for each successive time window a newly generated random or pseudo-random phase is applied to the signal. This technique thus provides the randomly changing signal phase.
  • the method may be applied in combination with a method for detecting oscillation due to feedback in said signal in each of said frequency bands, a randomly changing phase applied in each frequency band for which said oscillation has been detected.
  • the oscillation detection technique may comprise calculating, for each frequency band, the change in signal phase and/or signal amplitude from a time window to a subsequent time window, and comparing, for some or all of said frequency bands, the results of the calculation step to defined criteria to provide a measure of whether oscillation due to feedback is present in the signal.
  • the oscillation detection technique may be a phase locked loop method, or may involve detection of a large sustained amplitude in a particular frequency band.
  • the randomly changing phase may be applied in each frequency band to a gain value to be applied to the signal.
  • the method includes the step of, for a particular frequency band, generating a complex number with random or pseudo-random phase and amplitude 1.0 for each successive time window, and applying this complex number to the signal in that frequency band.
  • a real gain value for said frequency band may be multiplied by said complex number before the gain is applied to the signal.
  • the method may include the step of, for a particular frequency band and in each successive time window, replacing the signal or signal gain with a signal or signal gain having equal amplitude and a random or pseudo-random phase.
  • the invention provides, in accordance with a second aspect, an apparatus for suppressing oscillations in a signal identified as or suspected of containing an oscillation, comprising: means for converting the signal into frequency bands in the frequency domain; means for applying, for a selected period of time, a randomly changing phase to the signal in at least one of said frequency bands; and means for reconverting the converted signal into an output waveform signal.
  • the apparatus preferably includes means for dividing the signal into a series of successive time windows, and means for applying to the signal, for each successive time window, a newly generated random or pseudo-random phase.
  • the apparatus is provided in combination with a means for detecting oscillation due to feedback in said signal in each of said frequency bands, the means for applying arranged to apply a random phase in each frequency band for which said oscillation has been detected.
  • the means for detecting oscillation may comprise means for calculating, for each frequency band, the change in signal phase and/or signal amplitude from a time window to the next, and means for comparing, for some or all of said frequency bands, the results of the calculation step to defined criteria to provide a measure of whether oscillation due to feedback is present in the signal.
  • the means for oscillation detection may comprise phase locked loop circuitry, or means for detection of a large sustained amplitude in a particular frequency band.
  • the means for applying are arranged to apply the randomly changing phase in each frequency band to a gain value to be applied to the signal.
  • the apparatus may include means for generating a complex number with random or pseudo-random phase and amplitude 1.0 for each successive time window, and means for applying this complex number to the signal in that frequency band.
  • means are included for multiplying a real gain value for said frequency band by said complex number before applying the gain to the signal.
  • the apparatus includes means for, for a particular frequency band and in each successive time window, replacing the signal or signal gain with a signal or signal gain having a random or pseudo-random phase.
  • the invention provides alteration of the feedback loop in a manner that disrupts the feedback oscillation conditions and suppresses the oscillation without significantly affecting the system frequency response. If used with an appropriate oscillation detection technique, oscillation can be detected and suppressed very rapidly, and before audible ringing results.
  • the randomly changing phase is added in successive time windows over a certain length of time, for example approximately 8 seconds, to any frequency that appears to be in a state of oscillation.
  • the length of time may be preselected, or may be dynamically determined with reference to the result of oscillation detection in that frequency band.
  • the random phase variation suppresses the oscillation by disrupting the consistent constructive addition of the feedback signal to the input signal.
  • the feedback suppression method of the invention may be used with any suitable feedback detection approach.
  • the method may be used in a system which involves deriving gain values for the frequency bands in accordance with a specified signal processing algorithm.
  • the derived gain may be compared (for some or all of said frequency bands) with a prescribed gain limit, in order to provide a measure as to whether oscillation due to feedback is present in the signal, and this to trigger the oscillation suppression.
  • Fig. 1 is a block diagram schematically illustrating a feedback loop
  • Fig. 2 is a block diagram of an apparatus according to the present invention
  • Fig. 3 is a flow diagram illustrating the logic and process of feedback detection
  • Fig. 4 is a flow diagram illustrating the logic and process of feedback suppression
  • Figs. 5 and 6 are block diagrams of alternative architectures of apparatus according to the invention. DETAILED DESCRIPTION OF THE DRAWINGS
  • An acoustic system 10 in accordance with the invention is schematically depicted in Figure 2.
  • a microphone 11 converts an acoustic signal, such as the speech, into an analogue electrical signal proportional to the acoustic signal, which signal is then converted by an A/D converter 12 into a digital signal.
  • the output of A D converter 12 is connected to the input of a Discrete Fourier Transform (DFT) unit - such as a Fast Fourier Transform (FFT) unit 13 - for analysing the frequency components of the signal, whilst unit 14 enables analysis of 64 frequency bands across the spectrum of the signal.
  • DFT Discrete Fourier Transform
  • FFT Fast Fourier Transform
  • a suitable unit is the Toccata Plus integrated circuit designed and developed by the Dspfactory, operating with 16 kHz sampling rate and using 128 point windows of 8 millisecond duration with 50% overlap to yield 64 linearly spaced frequency bands at
  • Module 20 is a feedback detector arranged to monitor the phase and amplitude of the signal in each frequency band in the spectrum (adjusted if appropriate, as explained further below) during successive sampling windows at short intervals, such as successive 8 millisecond windows with 50% overlap, calculated every 4 milliseconds.
  • the apparatus includes a counter for each frequency band, which can be incremented or reset at each successive time window.
  • the measured phase from the previous window is subtracted from the phase in the current window to calculate the change in phase at a particular frequency band.
  • This change in phase is compared to the previous change in phase. If the values are within a defined variation (ie the change in the phase change is within the threshold) then the counter is incremented, otherwise the counter is reset. Further, the amplitude in the current window is compared with the amplitude in the previous window. If the current amplitude is less than the previous amplitude, then the counter is reset.
  • the feedback detector is programmed to respond - by triggering feedback suppression - to the counter reaching a value M.
  • the present invention contemplates that either the change in phase change criterion (counter reaches M p ) or the change in amplitude criterion (counter reaches M a ) may be considered for suppression triggering, or both.
  • the example represented in Figure 3 illustrates, for a time window, the process of detection using the change in phase change criterion. For each of the 64 bands, the state of the band is determined (30). If that band is already being suppressed (31), no calculations are performed. Otherwise, the phase is calculated (32), and the previous phase value calculated for that band (which value has been stored - see below) is subtracted from the current phase value (33) to provide a current value of phase change.
  • the next step (34) is to subtract the previous phase change value from the current phase change value, to output a value of change of phase change. This value is then checked (35) and (37), and if it is within a certain prescribed threshold for phase change variation, the counter is incremented by 1 (41). The subtraction of 2 ⁇ r radians (36) and second check (37) ensure that output is dependent on the magnitude of the change of phase change, irrespective of whether the change has increased or decreased. If the value is not within the threshold, the counter is reset to 0 (38), the current phase and phase change value is saved (39), and the next band is selected (40).
  • the amplitude is monitored from one time window to the next and, if it is increasing over the prescribed number M a of successive windows, this measure can he applied in determining whether an oscillation is present in the signal in that frequency band (reference 44 in Figure 3).
  • M a M p simplifies the detection apparatus and method, as the process can then readily be implemented using a common counter. If only one criterion is to be employed in detecting feedback, the M a or M p value may be increased to avoid false triggering of feedback suppression.
  • phase module 21 generates a complex number with random phase and amplitude 1.0 for each window, and multiplies the real gain value at module 22 for the frequency band by this complex number before the gain is applied to the signal via gain unit 23 to provide an adjusted spectrum 24.
  • the loop illustrated in Figure 2 indicates that the phase of the gain multipliers depends on the apply phase unit, which operates in accordance with the output of the feedback detector unit.
  • Apply phase module 21 continues to apply random phase to the gain for a prescribed length of time (for example, around 8 s), to allow the conditions which created the feedback path to change.
  • the example represented in Figure 4 illustrates the process of suppression for a time window, appropriate for the example embodiments illustrated in Figures 5 and 6.
  • the state of a selected band is checked (50), to determine whether it is flagged for suppression (51) . If not, the next band is selected (57) . If it is flagged for suppression, the magnitude of the signal at that band is obtained (52) and multiplied by the real part of the generated random complex number (53), the resulting new real component being saved (54). Further, the magnitude of the signal is multiplied by the corresponding imaginary part of the generated random complex number (55), and the resulting new imaginary component saved (56) .
  • the signal passes through MPO unit (Maximum Power Output) 25 (see Figure 2), and is then reconverted into a time domain waveform by inverse FFT module 26.
  • a D/A converter 27 then converts the digital signal to an electrical analogue signal before supplying it to the hearing aid output terminal to drive speaker 28.
  • the 'magnitude of the signal' in a band referred to above in the context of Figure 4 may be the output spectrum value (for the embodiments shown in Figures 5 and 6), or may be the gain value (for the embodiment shown in Figure 2), and the invention may be implemented using either approach, the selection depending at least in part on the hardware employed for the processing.
  • feedback detector 20 and oscillation suppression module 21 it is not necessary to apply feedback detector 20 and oscillation suppression module 21 together.
  • An alternative form of feedback detector such as a phase locked loop (PLL) circuit, may be employed, apply phase module 21 being used to apply a random phase to the signal in that particular frequency band once feedback has been detected.
  • PLL phase locked loop
  • ADROTM adaptive dynamic range optimisation
  • a further criterion is considered by the feedback detection algorithm, namely, for each of the 64 frequency bands, a comparison of the gain in each time window with a prescribed threshold level. This step is schematically illustrated by reference 45 in Figure 3, as a factor in determining whether oscillation is present in the signal (46) in the relevant frequency band.
  • the signal phase criterion (described above) and the gain criterion are satisfied, then it is concluded that feedback is occurring, and feedback suppression is triggered.
  • This technique has the advantage that the risk of false triggering is reduced.
  • this method ensures that feedback will only be detected when gain values are relatively high, application of a gain reduction suppression technique to suppress the feedback will not reduce the gain to an undesirably low level.
  • the gain threshold when employed in combination with an adaptive gain system such as ADROTM, is defined as a fixed number of dB below the maximum limit placed on the gain by the adaptive gain system.
  • This approach can also be taken in other nonlinear or adaptive systems that employ variable gain, such as in so-called 'compression' systems which apply lower gains to loud input signals and higher gains to softer input signals.
  • the present invention has been described above with reference to an implementation involving real-time feedback detection (eg in use by a hearing aid wearer), in order to trigger real-time suppression measures.
  • the oscillation detection technique described above can also be used for feedback management, applied at a setup (or adjustment) phase, in order to set parameters of the signal processing system. The feedback management step is therefore undertaken only once during the setup phase of the amplifying system, or during any subsequent resetting of the apparatus.
  • the feedback detection technique is used to detect the onset of feedback while amplifier gain limits are adjusted during the setup phase. This serves to remove steady state feedback, whilst the real-time feedback detection/suppression system then operates during normal use of the apparatus to reduce the occurrence of transitory feedback caused by changing environmental conditions.
  • the signal spectrum may be split into a plurality of discrete frequency bands, or alternatively neighbouring bands may overlap.

Landscapes

  • Physics & Mathematics (AREA)
  • Engineering & Computer Science (AREA)
  • Acoustics & Sound (AREA)
  • Signal Processing (AREA)
  • Health & Medical Sciences (AREA)
  • General Health & Medical Sciences (AREA)
  • Otolaryngology (AREA)
  • Neurosurgery (AREA)
  • Soundproofing, Sound Blocking, And Sound Damping (AREA)

Abstract

L'invention porte sur la suppression d'oscillation et, notamment, sur un procédé et sur un appareil permettant de supprimer une oscillation dans un signal identifié comme contenant ou susceptible de contenir une oscillation due à la réaction. Le procédé consiste à convertir le signal en bandes de fréquence dans le domaine de fréquence, appliquer, sur une durée sélectionnée, une phase de variation de manière aléatoire au signal dans au moins une des bandes de fréquence et reconvertir le signal converti en signal de forme d'onde de sortie. La durée sélectionnée est divisée en une série de fenêtres temporelles, et pour chaque fenêtre temporelle successive, une phase aléatoire ou pseudo-aléatoire récemment générée est appliquée au signal. Le procédé peut être utilisé en combinaison avec un procédé de détection d'oscillation dans le signal dans chacune des bandes de fréquence, une phase à variation aléatoire est appliquée dans chaque bande de fréquence dans laquelle une oscillation a été détectée. L'invention peut notamment s'appliquer aux prothèses auditives.
EP04734786A 2003-05-26 2004-05-26 Suppression d'oscillation Withdrawn EP1629691A1 (fr)

Applications Claiming Priority (3)

Application Number Priority Date Filing Date Title
AU2003902587A AU2003902587A0 (en) 2003-05-26 2003-05-26 Oscillation suppression
US10/445,463 US20040252853A1 (en) 2003-05-27 2003-05-27 Oscillation suppression
PCT/AU2004/000702 WO2004105430A1 (fr) 2003-05-26 2004-05-26 Suppression d'oscillation

Publications (1)

Publication Number Publication Date
EP1629691A1 true EP1629691A1 (fr) 2006-03-01

Family

ID=33477356

Family Applications (1)

Application Number Title Priority Date Filing Date
EP04734786A Withdrawn EP1629691A1 (fr) 2003-05-26 2004-05-26 Suppression d'oscillation

Country Status (2)

Country Link
EP (1) EP1629691A1 (fr)
WO (1) WO2004105430A1 (fr)

Families Citing this family (18)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US7809150B2 (en) 2003-05-27 2010-10-05 Starkey Laboratories, Inc. Method and apparatus to reduce entrainment-related artifacts for hearing assistance systems
EP1718110B1 (fr) * 2005-04-27 2017-09-13 Oticon A/S Moyens de détection et suppression de rétroaction audio
US8477952B2 (en) 2005-04-27 2013-07-02 Oticon A/S Audio system with feedback detection means
US8553899B2 (en) 2006-03-13 2013-10-08 Starkey Laboratories, Inc. Output phase modulation entrainment containment for digital filters
US8116473B2 (en) 2006-03-13 2012-02-14 Starkey Laboratories, Inc. Output phase modulation entrainment containment for digital filters
US8199948B2 (en) 2006-10-23 2012-06-12 Starkey Laboratories, Inc. Entrainment avoidance with pole stabilization
DK2080408T3 (da) 2006-10-23 2012-11-19 Starkey Lab Inc Undgåelse af medrivning med et auto-regressivt filter
US8452034B2 (en) 2006-10-23 2013-05-28 Starkey Laboratories, Inc. Entrainment avoidance with a gradient adaptive lattice filter
US8509465B2 (en) 2006-10-23 2013-08-13 Starkey Laboratories, Inc. Entrainment avoidance with a transform domain algorithm
EP2015604A1 (fr) 2007-07-10 2009-01-14 Oticon A/S Génération d'un bruit de sonde dans un système d'annulation de retour
US8571244B2 (en) 2008-03-25 2013-10-29 Starkey Laboratories, Inc. Apparatus and method for dynamic detection and attenuation of periodic acoustic feedback
EP2148526B1 (fr) * 2008-07-24 2020-08-19 Oticon A/S Modification de contenu spectral pour évaluation de canal de réponse robuste
DK2190217T3 (da) 2008-11-24 2012-05-21 Oticon As Fremgangsmåde til reduktion af tilbagekobling i høreapparater samt tilsvarende anordning og tilsvarende computerprogramprodukt
AU2009339343A1 (en) 2009-02-06 2011-08-18 Oticon A/S Spectral band substitution to avoid howls and sub-oscillation
US9654885B2 (en) 2010-04-13 2017-05-16 Starkey Laboratories, Inc. Methods and apparatus for allocating feedback cancellation resources for hearing assistance devices
US8917891B2 (en) 2010-04-13 2014-12-23 Starkey Laboratories, Inc. Methods and apparatus for allocating feedback cancellation resources for hearing assistance devices
US8942398B2 (en) 2010-04-13 2015-01-27 Starkey Laboratories, Inc. Methods and apparatus for early audio feedback cancellation for hearing assistance devices
US10885896B2 (en) 2018-05-18 2021-01-05 Bose Corporation Real-time detection of feedforward instability

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US6434246B1 (en) * 1995-10-10 2002-08-13 Gn Resound As Apparatus and methods for combining audio compression and feedback cancellation in a hearing aid
US6498858B2 (en) * 1997-11-18 2002-12-24 Gn Resound A/S Feedback cancellation improvements

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