EP0964476B1 - Vorrichtung zur optischen Steuerung eines Breitbandradars zum Senden und Empfangen - Google Patents

Vorrichtung zur optischen Steuerung eines Breitbandradars zum Senden und Empfangen Download PDF

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EP0964476B1
EP0964476B1 EP99401312A EP99401312A EP0964476B1 EP 0964476 B1 EP0964476 B1 EP 0964476B1 EP 99401312 A EP99401312 A EP 99401312A EP 99401312 A EP99401312 A EP 99401312A EP 0964476 B1 EP0964476 B1 EP 0964476B1
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frequency
signal
light
mixer
wavelength
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EP0964476A1 (de
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Thomas THOMSON-CSF P.I.D.B. Merlet
Olivier THOMSON-CSF P.I.D.B. Maas
Daniel THOMSON-CSF P.I.D.B. Dolfi
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Thales SA
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
    • H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
    • H01Q3/2676—Optically controlled phased array

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  • the present invention relates to an optical control device for transmitting and receiving a broadband radar. It applies to the control of broadband electronic scanning antennas, to ensure both the formation of a beam on transmission and the reception of a beam reflected by a target.
  • An electronic scanning antenna has a plurality of radiating elements that provide both the transmission and the reception of a microwave signal.
  • a transmission or reception beam is formed by all the signals transmitted or received by each element.
  • To orient a beam in a given direction ⁇ it is necessary to create time delays between signals transmitted or received by the different radiating elements. To obtain a similar effect, it was known to create a phase lag between these signals.
  • the phase shift ⁇ 1 - ⁇ 2 is equal to 2 ⁇ f (T 1 -T 2 ).
  • the preceding relation (1) shows a major disadvantage in that the phase shift depends on the frequency. As a result, if the frequency varies, the dotting angle also varies. This method of orientation of a beam is therefore not suitable for a broadband radar.
  • the microwave techniques do not allow to create a time delay between the signals other than by creating the previous phase shift, except to implement a prohibitive device from the point of view of size and cost. Indeed, a priori simpler solution would be to create a delay directly between the signals supplied to the different radiating elements, but this would require circuits microwave cumbersome and expensive, in particular due to the unavoidable dimensions imposed by the wavelengths involved.
  • optical control solutions of electronic scanning antennas have already been implemented.
  • optical control architectures have therefore already been proposed to control the radiation pattern on transmission.
  • An example of an optical architecture is for example presented in the patent French FR 2 659 754 .
  • a beam formation using time delays requires a very important dynamic of all the delays, still inaccessible to the optical components.
  • a direct architecture based on the reversible operation of the command developed for the issue does not seem to be possible in the short or medium term.
  • a correlation architecture has been defined in particular according to the description of the patent. FR 2,725,076 or EP 0 708 491 .
  • Such an architecture is restricted to low bandwidth radars, typically 10 MHz.
  • This disadvantage of a correlation architecture stems in particular from the fact that the use of complementary delays is incompatible with local oscillator and remote transmission signal frequencies, for example 500 MHz, which characterize a broadband radar. However this frequency shift is inevitable for the proper functioning of a radar, in particular to avoid problems related to the aliasing of the spectrum.
  • the two beams are modulated at the transmission frequency, and for each reception signal of a radiating element, the local oscillator frequency is output from a photomixer by mixing the frequency of the received signal carried by the optical wave and an intermediate frequency, then the frequency of the reception signal supplied to the radar processing means, an intermediate frequency increased by the Doppler frequency of the received signal is obtained at the output of a microwave mixer by mixing the local oscillator frequency with the transmission frequency.
  • the main advantages of the invention are that it avoids the transposition on an optical carrier of the reception signal, while benefiting from the broadband processing offered by a time delay architecture and that it is simple to implement.
  • FIG. 1 illustrates an optical control device operating in transmission and reception, of the type for example of that described by the patent.
  • French n ° 94 11498 The signals derived therefrom serve, on transmission, to supply active modules or radiating elements and, on reception, to generate a local oscillator adapted in frequency and direction.
  • the beam light F1, F2 is frequency modulated.
  • a first source L1 emits a single-frequency light beam F1 of wavelength ⁇ 1 (pulsation ⁇ 1).
  • a frequency translator T1 receives this light and transmits light to ⁇ 1 and light to ⁇ 1 + 2 ⁇ f e modulated using a frequency signal f e .
  • the frequency translator T1 is for example an acousto-optical Bragg cell for frequencies substantially lower than or equal to 5 GHz or an integrated optical device for higher frequencies.
  • a second light source emits another single frequency light beam F2 of wavelength ⁇ 2 (pulsation ⁇ 2).
  • a frequency translator T2 receives this light and transmits light at ⁇ 2 and light at ⁇ 2 + 2 ⁇ (f e + f o ) modulated by a frequency signal f e + f o .
  • the frequency f e is located in the microwave range and corresponds to the antenna transmission frequency.
  • the frequency f o takes place of local oscillator frequency for the mode of reception of the antenna in the following description.
  • the light emitted by the translator T1 is polarized in a determined direction. That emitted by the translator T2 is polarized in a direction perpendicular to that emitted by T1.
  • An optical mixer system ME superimposes the light from the translator T1 to that from the translator T2.
  • the resulting beam therefore comprises light polarized along two orthogonal directions, as is symbolized in FIG. 1, and at the different frequencies originating from the translators T1 and T2.
  • the resulting beam is extended by a beam splitter SE so as to be distributed over the different inputs of a set of DCR delay circuits.
  • This set of DCR delay circuits can for example be produced as described in the patent application. French No. 92 34 467 .
  • Each delay circuit delays differently the light from the source L1 and the light from the source L2. More specifically, according to an exemplary embodiment, if T is the maximum delay induced by a delay circuit, the light from the source L1 is delayed by a time ti and the light from the source L2 is delayed by a time T-ti complementary to the time T.
  • the times T of the different delay circuits are for example equal.
  • DCR delay circuits comprise a set of spatial light modulators comprising pxp pixels (same number of pixels as antenna radiators) and for controlling the phase shift and delay assigned to each of the pxp channels thus cut.
  • DCR delay circuits provide geometrically progressive delays so that only N spatial modulators are required to obtain 2 N distinct delay values on each of the pxp channels of the architecture.
  • the delay switching is based on the controlled rotation, thanks to the spatial light modulators, of the polarization of the beams.
  • the property of the DCR which is to generate, on each channel complementary delays for input crossed polarization states is exploited. Indeed, if the beam from L 1 is delayed on the channel i, then the beam from L 2 undergoes a delay Tt i , T being the crossing time of the DCR.
  • Each output Sd of a delay circuit provides light at the wavelength ⁇ 1 modulated at the frequency f e and light at the wavelength ⁇ 2 modulated at the frequency f e + f o .
  • Detection circuits PDRi and PDRn are connected to the outputs Sd for example by optical fibers. These circuits are for example made as shown in the lower right of Figure 1. Each circuit has a chromatic separator MD separating the light at the wavelength ⁇ 1 of the light at the wavelength ⁇ 2.
  • the light at the wavelength ⁇ 1 is transmitted to a photodetector PDRi, 1 which emits a photocurrent of frequency f e to a radiating element ED1.
  • This photocurrent results from the beat between the light at ⁇ 1 and the light at ⁇ 1 + 2 ⁇ f e .
  • the transmitted photocurrent is amplified by an amplifier so as to be compatible with the radiated power necessary for the emission of the radiating element of the radar.
  • the antenna radiation pattern is monitored.
  • the transmission direction of the antenna is thus controlled optically.
  • the light at the wavelength ⁇ 2 is transmitted to another photodetector PDRi, 2 by the chromatic separator. This emits a photocurrent resulting from the beating between the light at ⁇ 2 and ⁇ 2 + 2 ⁇ (f e + f o ).
  • This photocurrent is applied to a microwave mixer Mk which also receives a signal received by an antenna element.
  • a directional coupler CD makes it possible to couple, on the one hand, the photocurrent of PDRi, 1 to an antenna element in the transmission direction and to couple, on the other hand, a detection current of an antenna element (in the receiving direction) to the frequency mixer Mk.
  • the set of signals from photodetectors PDRI, 2 is in fact a local oscillator (homodyne or heterodyne) adapted to the direction of transmission of the antenna.
  • the signal received by an antenna element EDk is amplified and is applied together with the signal from PDR k2 , on a microwave mixer Mk.
  • the signal transmitted by the antenna element EDk is of the form S (t- ⁇ k )
  • the same element receives a signal R (t '+ ⁇ k ) which must therefore be mixed with a local oscillator S' (t '+ T + ⁇ k ).
  • FIG. 2 presents a network consisting of two radiating elements S 1 , S 2 separated by a distance d and fed by variable delays I 1 , I 2 .
  • An angle ⁇ represents the angle of aim or pointing of the beam.
  • a plane 21, perpendicular to the pointing direction 22 noted ⁇ , represents an equiphase plane, that is to say a plane where all the signals have the same phase.
  • the reception signals are transposed on an optical carrier.
  • the system being reciprocal, the condition on the delays to be introduced to capture a wave in the direction ⁇ is, in this case, strictly identical.
  • mixers are introduced behind each radiating element as shown in FIG. 3.
  • the mixers M1, M2 located behind each radiating element receive the signal in reception and the signal OL of FIG. oscillator local having suffered a delay I 1 ', I 2 '.
  • the intermediate frequency signals Fi1, Fi2 result from the mixing of the received signal at the RF transmission frequency and the OL signal of the local oscillator. This mixing results in subtraction of the frequencies and phases of the signals.
  • ⁇ RF and ⁇ OL respectively represent the pulses of the reception signals and the local oscillator, c representing the speed of light.
  • the phases ⁇ r1 and ⁇ r2 represent the phases received on the dipoles.
  • the frequency of the local oscillator OL is chosen outside the band of agility of the radar, in particular to avoid problems related to the aliasing spectrum. Therefore, the use in reception mode of such an architecture is restricted to low bandwidth radars, for example of the order of 10 MHz. It therefore appears necessary to make modifications to the operation of an architecture of the type of that of FIG. 1, so as to maintain the broadband property of the optically controlled architectures using time delays.
  • the local oscillator OL of frequency f OL is formed by mixing the frequency of transmission with an intermediate frequency f i made for example by a frequency generator common to all channels.
  • the two beams F1, F2 are both modulated at the same frequency f e , which is the transmission frequency.
  • FIG. 4 This figure shows the circuits associated with a radiating element EDk of order k.
  • the polarized light 41 at the output of the optical mixer ME undergoes a delay 42 by passing for example in the beam splitter SE and the delay circuit DCR as shown in FIG. 1.
  • the direct and complementary delays are printed on the same frequency e .
  • a chromatic separator MD is located in output of the delay elements 42, more particularly on each of the outputs of the DCR delay circuit. This separator MD separates the light at the wavelength ⁇ 1 from the light at the wavelength ⁇ 2 .
  • the light at the wavelength ⁇ 1 is transmitted to a first photodetector PD1 which emits a photocurrent of emission frequency f e to the radiating element EDk.
  • a directional coupler CD is interposed between this first photodetector PD1 and the radiating element EDk.
  • the light at the wavelength ⁇ 2 is transmitted to a second photodetector PD2 which emits a photocurrent of emission frequency f e to an input of a first microwave mixer Mk1.
  • the other input of this mixer receives the aforementioned intermediate frequency f i .
  • the output of the first mixer Mk1 gives a signal of frequency f e + f i , this signal acting as a local oscillator signal, the aforementioned frequency f OL being equal to f e + f i .
  • the output of the first mixer Mk1 is connected to the input of a second mixer Mk2 which therefore receives the frequency signal f e + f i .
  • the other input of the second mixer Mk2 is connected to an output of the directional coupler CD, knowing that one of its inputs is connected to the output of the first photodetector PD1 and the other input / output is connected to the radiating element ED1 .
  • This directional coupler therefore makes it possible, on the one hand, to couple in the direction of emission the photocurrent created by the first photodetector PD1 to the radiating element EDk, and secondly to couple in the sense of reception the radiating element.
  • the reception signal supplied to this second mixer Mk2, via the directional coupler CD has a frequency equal to that of the transmission signal f e increased by a Doppler frequency f D.
  • the reception signal entering the second mixer therefore has a frequency equal to f e + f D.
  • the output signal of the second mixer consequently has a frequency equal to f i + f D , that is to say a frequency equal to the sum of the intermediate frequency and the Doppler frequency. In other words, thus recovering at the output of the second mixer a signal at the intermediate frequency offset from the Doppler frequency. This signal is then processed by conventional processing means for radar operations.
  • FIG. 5 illustrates an equiphase plane 51 of a wave emitted from radiating elements EDk pointing towards a target 52.
  • Each radiating element is affected by a delay ⁇ k , produced in accordance with FIGS. 1 and 4.
  • the magnitude T represents the time of going and returning of a signal transmitted to the target 52, more particularly for a signal transmitted from a first group of radiating elements ED1, as illustrated in particular in FIG.
  • the second term 2 ⁇ f e ( ⁇ - ⁇ k ) of the relation (11) represents a phase ramp at the transmission frequency, which makes this phase follow an inclination law as a function of the transmission frequency. e .
  • f D is of the order of 10 3 Hz and where ⁇ and ⁇ k are of the order of 10 -8 s, the term f D ( ⁇ - ⁇ k ) is negligible.
  • the signals on the different channels associated with the different radiating elements EDk can therefore be summed in phase since there are no more terms dependent on the delays ⁇ k .
  • the first term of the relation (13) 2 ⁇ (f i + f D ) t gives the information on the speed of the target and the second term 2 ⁇ (f e + f D ) T, which is constant with respect to the time t , gives the information on the distance of the target, more precisely by the calculation of the magnitude T from which the distance is deduced.
  • the relationship (13) therefore shows that the signals from the different radiating elements EDk can be summed in phase, and this without bandwidth limitation. The property of very wide band allowed by an optical control is thus preserved for the reception.
  • an optical control device having a correlation architecture the dynamic stress on the optical links is replaced by a stability constraint on the stability signal of the local oscillator.
  • a double mixing architecture according to the invention makes it possible to avoid the transposition on an optical carrier of the reception signal, while benefiting from the broadband treatment offered by a time delay optical architecture.
  • FIG. 6 shows an alternative embodiment of a device according to the invention.
  • the first mixture is for example made by the second photodetector PD2.
  • the latter is therefore in this case both office of photodetection and microwave mixing. In this way, the number of mixers is halved for the entire antenna.
  • the generation of the additional delays necessary for the inclined local oscillator can also be obtained by doubling the number of pixels of the delay circuit DCR.
  • pxp pixels are for example assigned to the generation of the signals to be transmitted and pxp other pixels are each used for the generation of the local oscillator assigned to each radiating element.
  • This variant embodiment has the advantage of greater flexibility of use. In particular, it makes it possible to obtain different transmission and reception diagrams. The delay law applied to the local oscillator is totally independent of that applied to the transmitted signal.
  • ⁇ k e, ⁇ e j represent the delays applied to the issue with the channel k and channel j firstly respectively
  • ⁇ k OL, OL ⁇ j represent the delays applied respectively to the channel k and to the path j of the local oscillator on the other hand
  • FIG. 7 illustrates a third variant embodiment of a device according to the invention.
  • the functions of the two mixers Mk1, Mk2 are inverted.
  • the intermediate frequency signal f i is mixed with the frequency receiving signal f e + f D by the second mixer Mk2 to form a local oscillator signal at the output of this second mixer.
  • This local oscillator signal in reception is then mixed with the local oscillator signal in transmission, the frequency of which is in fact the transmission frequency f e , by the first mixer Mk1.
  • This second mixture gives a frequency signal f i + f D , that is to say an intermediate frequency increased by the Doppler frequency of the received signal.
  • This second mixture can also be carried out directly by the second photodetector PD2 according to the first variant presented with reference to FIG.

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Claims (7)

  1. Optische Steuervorrichtung für eine Antenne mit elektronischem Abtasten, die zu steuernde Strahlungselemente (ED1, EDk) aufweist, wobei diese Vorrichtung eine Einheit (DCR) optischer Schaltungen mit Verzögerungen (42) aufweist, die jeweils Folgendes empfangen:
    - ein erstes Lichtbündel (F1), das entlang einer ersten Richtung polarisiert ist und eine erste Wellenlänge (λ1) aufweist, wobei diesem ersten Bündel eine entsprechende Verzögerung zugewiesen ist, und
    - ein zweites Lichtbündel (F2), das entlang einer zweiten Richtung polarisiert ist und eine zweite Wellenlänge (λ2) aufweist;
    wobei die zwei Lichtbündel (F1, F2) mit Sendefrequenz (fe) moduliert sind,
    wobei jede optische Schaltung mit Verzögerungen (42) ergänzende Verzögerungen (ti, T-ti) im Vergleich zu einem bestimmten Zeitwert (T) auf dem Licht jeweils des ersten und des zweiten Bündels, das sie empfängt, induziert, wobei sich ein Farbaufteiler (CD) am Ausgang jeder optischen Schaltung mit Verzögerungen (42) befindet und das Licht mit der ersten Wellenlänge (λ1) von dem Licht mit der zweiten Wellenlänge (λ2) trennt, wobei jedes Strahlungselement der Antenne (EDk) mit dem Ausgang einer optischen Schaltung mit Verzögerungen (42) durch einen ersten Lichtsensor (PD1) gekoppelt ist,
    dadurch gekennzeichnet, dass für jedes Empfangssignal eines Strahlungselements (EDk) die Lokaloszillatorfrequenz (fOL) am Ausgang eines ersten Hyperfrequenzmischers (MK1) durch Mischen der Sendefrequenz (fe) und einer Zwischenfrequenz (fi) geliefert wird, dass dann die Frequenz des Signals, die an die Radarverarbeitungsmittel geliefert wird, mit Zwischenfrequenz erhöht um die Dopplerfrequenz (fD) des empfangenen Signals, am Ausgang eines zweiten Hyperfrequenzmischers (MK2) durch Mischen der Lokaloszillatorfrequenz mit der Frequenz des empfangenen Signals (fe + fD) erzielt wird.
  2. Vorrichtung nach Anspruch 1, dadurch gekennzeichnet, dass:
    - das Licht mit der ersten Wellenlänge (λ1) an den ersten Lichtsensor (PD1) übertragen wird, der einen Fotostrom mit Sendefrequenz (fe) zu dem Strahlungselement (EDk) sendet, wobei ein Richtkoppler (CD) zwischen diesem ersten Lichtsensor (PD1) und dem Strahlungselement (EDk) eingefügt ist;
    - das Licht mit der zweiten Wellenlänge (λ2) an einen zweiten Lichtsensor (PD2) übertragen wird, der einen Fotostrom mit Sendefrequenz (fe) zu einem Eingang des ersten Hyperfrequenzmischers (Mk1) sendet, wobei der andere Eingang dieses Mischers eine Zwischenfrequenz (fi) empfängt, wobei das Ausgangssignal dieses Mischers als Lokaloszillatorsignal dient, wobei der Ausgang des ersten Mischers (Mk1) mit dem Eingang des zweiten Mischers (Mk2), der das Lokaloszillatorsignal empfängt, verbunden ist, wobei der andere Eingang des zweiten Mischers (Mk2) von dem Richtkoppler (CD) das von dem Strahlungselement (EDk) empfangene Signal empfängt, um auf seinen Ausgang ein Signal zu liefern, dessen Frequenz die Summe der Zwischenfrequenz (fi) und der Dopplerfrequenz (fD) des empfangenen Signals ist.
  3. Optische Steuervorrichtung für eine Antenne mit elektronischem Abtasten, die zu steuernde Strahlungselemente (ED1, EDk) aufweist, wobei diese Vorrichtung eine Einheit (DCR) optischer Schaltungen mit Verzögerungen (42) aufweist, die jeweils Folgendes empfangen:
    - ein erstes Lichtbündel (F1), das entlang einer ersten Richtung polarisiert ist und eine erste Wellenlänge (λ1) aufweist, wobei diesem ersten Bündel eine entsprechende Verzögerung zugewiesen ist, und
    - ein zweites Lichtbündel (F2), das entlang einer zweiten Richtung polarisiert ist und eine zweite Wellenlänge (λ2) aufweist,
    wobei die zwei Bündel (F1, F2) mit der Sendefrequenz fe moduliert sind,
    wobei jede optische Schaltung mit Verzögerungen (42) ergänzende Verzögerungen (ti, T-ti) im Vergleich zu einem bestimmten Zeitwert (T) an dem Licht des ersten und des zweiten Bündels, das sie empfängt, induziert, wobei sich am Ausgang jeder optischen Schaltung mit Verzögerungen (42) ein Farbaufteiler (CD) befindet und das Licht mit der ersten Wellenlänge (λ1) von dem Licht mit der zweiten Wellenlänge (λ2) trennt, wobei jedes Strahlungselement der Antenne (EDk) mit dem Ausgang einer optischen Schaltung mit Verzögerungen (42) durch einen ersten Lichtsensor (PD1) gekoppelt ist,
    dadurch gekennzeichnet, dass für jedes Empfangssignal eines Strahlungselements (EDk) die Lokaloszillatorfrequenz (fOL) am Ausgang eines ersten Hyperfrequenzmischers (Mk2) durch Mischen des empfangenen Signals (fe + fD) mit einer Zwischenfrequenz (fi) geliefert wird, dass dann die Frequenz des an die Radarverarbeitungsmittel gelieferten Signals, mit Zwischenfrequenz erhöht um die Dopplerfrequenz (fD) des empfangenen Signals, am Ausgang eines zweiten Hyperfrequenzmischers (Mk1) durch Mischen der Lokaloszillatorfrequenz mit der Sendefrequenz (fe) erzielt wird.
  4. Vorrichtung nach Anspruch 3, dadurch gekennzeichnet, dass:
    - das Licht mit der ersten Wellenlänge (λ1) an den ersten Lichtsensor (PD1) übertragen wird, der einen ersten Fotostrom mit Sendefrequenz (fe) zu dem Strahlungselement (EDk) sendet, wobei ein Richtkoppler (CD) zwischen diesen ersten Lichtsensor (PD1) und das Strahlungselement (EDk) eingefügt ist;
    - ein Eingang des ersten Hyperfrequenzmischers (Mk2) auf einem ersten Eingang das von dem Strahlungselement (EDk) über den Richtkoppler (CD) empfangene Signal empfängt, wobei der andere Eingang des ersten Mischers eine Zwischenfrequenz (fi) empfängt,
    - das Licht mit der zweiten Wellenlänge (λ2) an einen zweiten Lichtsensor (PD2) übertragen wird, der einen Fotostrom mit Sendefrequenz (fe) zu einem Eingang des zweiten Hyperfrequenzmischers (Mk1) sendet, wobei der andere Eingang dieses Mischers mit dem Ausgang des ersten Mischers (Mk2) verbunden ist, um ein Signal zu ergeben, dessen Frequenz die Summe der Zwischenfrequenz (fi) und der Dopplerfrequenz (fD) des empfangenen Signals ist.
  5. Vorrichtung nach einem der vorhergehenden Ansprüche, dadurch gekennzeichnet, dass der zweite Lichtsensor (PD2) auch ein Hyperfrequenzmischer (Mk1) ist.
  6. Vorrichtung nach einem der vorhergehenden Ansprüche, dadurch gekennzeichnet, dass die Antenne pxp Strahlungselemente aufweist, wobei die Einheit der Schaltungen mit Verzögerungen (DCR) eine Einheit Licht-Raummodulatoren aufweist, die pxp Pixel aufweisen, die dem Erzeugen der zu sendenden Signale zugewiesen sind, wobei diese Einheit ferner pxp weitere Pixel aufweist, die jeweils zum Erzeugen des Lokaloszillators, der jedem Strahlungselement zugewiesen ist, verwendet werden.
  7. Vorrichtung nach Anspruch 6, dadurch gekennzeichnet, dass die Größen τk e, τj e, die Verzögerungen darstellen, die auf das Senden jeweils an den Kanal k, der dem Strahlungselement mit Rang k zugewiesen ist, und an den Kanal j, der dem Strahlungselement mit Rang j zugewiesen ist, angewandt werden, und τk OL, τj OL die Verzögerungen darstellen, die jeweils an den Kanal k und an den Kanal j des Lokaloszillators andererseits angewandt werden, während die Frequenz fOL des Lokaloszillators der folgenden Gleichung entspricht: τ k OL - τ j OL ⁢ f OL = τ k e - τ j e ⁢ f e ,
    Figure imgb0018
    wobei fe die Frequenz des Sendesignals darstellt.
EP99401312A 1998-06-09 1999-06-01 Vorrichtung zur optischen Steuerung eines Breitbandradars zum Senden und Empfangen Expired - Lifetime EP0964476B1 (de)

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FR9807240 1998-06-09
FR9807240A FR2779579B1 (fr) 1998-06-09 1998-06-09 Dispositif de commande optique pour l'emission et la reception d'un radar large bande
US09/457,376 US6313792B1 (en) 1998-06-09 1999-12-09 Optical control device for electronic scanning antenna

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FR2779579A1 (fr) 1999-12-10
EP0964476A1 (de) 1999-12-15
FR2779579B1 (fr) 2000-08-25
US6313792B1 (en) 2001-11-06

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